WO2020015376A1 - 一种提高开关电源重载切轻载动态响应的控制方法 - Google Patents

一种提高开关电源重载切轻载动态响应的控制方法 Download PDF

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Publication number
WO2020015376A1
WO2020015376A1 PCT/CN2019/079175 CN2019079175W WO2020015376A1 WO 2020015376 A1 WO2020015376 A1 WO 2020015376A1 CN 2019079175 W CN2019079175 W CN 2019079175W WO 2020015376 A1 WO2020015376 A1 WO 2020015376A1
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mode
module
pid
output
cycle
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PCT/CN2019/079175
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English (en)
French (fr)
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徐申
陈明刚
沈为冬
王冲
孙伟锋
陆生礼
时龙兴
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东南大学
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H02M3/33523—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop

Definitions

  • the invention relates to a switching power supply, in particular to a control method for improving the dynamic response of a switching power supply under heavy load and light load.
  • the power supply is an indispensable part of each electronic device. Its performance is directly related to the technical specifications of the electronic device and whether it can work safely and reliably.
  • switching power supply also called switching converter, is a kind of power supply that uses modern power electronics technology to make the output voltage constant by adjusting the conduction ratio or frequency of the switching device.
  • the performance requirements for the dynamic response of the power supply are getting higher and higher.
  • Good dynamic effects require small voltage changes and voltage recovery times.
  • the power load of the washing machine changes very quickly, so that the power output voltage introduces overvoltage and undervoltage.
  • the overvoltage and undervoltage are too large, the load on the washing machine is more harmful; in addition, the mobile phone is charged In the middle, when the charger is on standby, the mobile phone is suddenly loaded, the output voltage is reduced, and when it is lowered to the normal voltage of the battery, it will cause certain damage to the battery, so the dynamic performance needs to be improved.
  • the general power supply chooses a multi-mode control method.
  • the multi-mode control method will introduce the problem of dynamic performance degradation.
  • the switching frequency is usually reduced in order to reduce the circuit loss.
  • 1A load as load A
  • the switching frequency f A is 70kHz
  • the circuit has higher efficiency
  • 0.7A load is load B
  • switching frequency f B is 70kHz
  • 0.2A load is load C
  • switching frequency f C is 20kHz
  • the 0.05A load is load D
  • the switching frequency f D is 20kHz.
  • the switching frequency at the load point is selected according to the system efficiency requirements.
  • the PWM mode When the load is between AB, the PWM mode is used, the load is between BC, the PFM mode is used, the load is between the CD, the PWM mode is used, and it is referred to as the DPWM mode.
  • the load is less than the load D, the PFM mode is used.
  • DPFM mode the working mode from light to heavy is DPFM-DPWM-PFM-PWM. If the load is standby, the standby frequency is assumed to be 2kHz according to the size of the dummy load. At this time, the control mode is DPFM mode. If the load suddenly changes to full load, the output voltage decreases at a rapid rate. According to the compensation results, the control modes will be different.
  • sampling can only be performed once in a cycle.
  • the output voltage can only be sampled before the secondary current drops to zero. In this way, when the load is cut by light, the switching frequency of DPWM is low. Even if the PI adjustment is large, the dynamic process is slower to ensure stability.
  • the prior art also discloses a method for obtaining the size of the load according to the relationship between the slope and the one-to-one monotonicity of the load, thereby obtaining the corresponding switching period after switching, but it can only be used for non-resonant conventional switching power supplies.
  • the present invention proposes a control method for improving the dynamic response of switching heavy-duty heavy-load and light-load, which can limit the output voltage overshoot within a certain range and reduce the dynamic recovery time. Improving dynamic performance will not cause system instability in multi-mode control, making the circuit design dynamic performance better.
  • the present invention adopts the following technical solutions:
  • a control method for improving the dynamic response of a switching power supply from heavy load to light load which is characterized in that the control system is based on a control system including a sampling module, a dynamic control module, an error calculation module, a PID module, a mode control module, and a PWM module. Connected with controlled switching power supply to form a closed loop;
  • the sampling module includes a sampling circuit and a sampling calculation module.
  • the sampling circuit obtains the output voltage information by dividing the output voltage of the switching power supply.
  • the sampling calculation module calculates the sampling voltage V o corresponding to the output voltage according to the output voltage information and outputs it to the error at the same time. Calculation module and dynamic control module;
  • the dynamic control module includes a voltage monitoring module and a switching cycle calculation module.
  • the voltage monitoring module includes two comparators and a logic unit. One of the comparators is used to compare the size between the sampling voltage Vo and the set upper limit value Vomax of the sampling voltage Vo. Another comparator is used to compare the magnitude between the sampling voltage Vo and the reference voltage V ref . The comparison results of the two comparators are output to the logic unit respectively.
  • the logic unit outputs the mode judgment result mode_F and determines whether to adopt the mode judgment result mode_F. Dynamic mode, where V ref ⁇ V omax ;
  • the voltage monitoring module outputs the mode judgment result mode_F to the mode control module and the switching cycle calculation module.
  • the switching cycle calculation module outputs the switching cycle T S to the mode control module.
  • the switching cycle calculation module is based on the sampling voltage V o and the voltage monitoring output by the sampling module.
  • the mode judgment result mode_F output by the module is calculated.
  • the error calculation module calculates the difference between the reference voltage Vref minus the sampling voltage V o according to the sampling voltage V o output by the sampling module, which is the current sampling error, records it as e1, and outputs it to the PID module;
  • the input of the PID module is the error signal e1 output by the error calculation module.
  • the control signal PI_ctrl output by the mode control module and the value V PIO are assigned.
  • the PID module In the dynamic mode, the PID module is turned off.
  • the dynamic mode switches to the first switching cycle of the normal working mode, first Assign the initial value V PIO to the PID module operation, and then perform the PID operation to obtain the compensation result V PI output to the mode control module and PWM module. After that, the PID operation is performed in each cycle of the normal working mode, and the compensation result V PI is output to the mode control module and PWM module;
  • mode_F 1 is a dynamic mode, the mode control module turns off the PID module by outputting a control signal PI_ctrl, and controls the PWM module to receive the switching period T S (n + 1) and the duty cycle D HTL or peak current of the dynamic mode output by the mode control module.
  • the PWM module generates a duty cycle waveform according to the switching period T S (n + 1) of the dynamic mode and the duty cycle D HTL or the peak current; when the mode control module jumps out of the dynamic mode and enters the first working mode, Switching cycle, the mode control module calculates the corresponding output load size based on the cycle size T S (n + 1) of the switching cycle at this time, turns on the PID module through the control signal PI_ctrl and assigns the current sampling result to V PIO before PID calculation , V PIO is the output value of the PID module corresponding to the load in the steady state after the load changes. After assignment, the PID module performs PI based on the output error e1 of the error module.
  • PID operation result V PI is fed back to the mode control module for mode selection and control in normal working mode; when the mode control module jumps out of the dynamic mode and enters the second switching cycle of normal working mode and later, PI_ctrl turns on the PID module for For calculation, the PID module performs PID calculation according to the output error e1 of the error module. The calculation result V PI is fed back to the mode control module for mode selection and control in the normal working mode. In the normal working mode, the PWM module receives the compensation result V output from the PID. The control mode of the normal working mode given by the PI and mode control module. This control mode is recorded as mode_ctrl. The switching period and the duty cycle / current information are calculated. The PWM module generates Space ratio waveform
  • the PWM module includes a PWM unit and a drive unit.
  • the input of the PWM unit is the PI_ctrl control signal output by the mode control module, the switching period T S (n + 1) of the dynamic mode and the duty cycle D HTL or peak current Ip.
  • the mode control module is in Control mode result mode_ctrl and PID module compensation result V PI in normal working mode; PID module compensation result V PI and normal mode control mode mode_ctrl signal given by the mode control module are calculated to obtain the switching cycle and duty during normal control After obtaining the cycle and duty cycle / peak current information, the drive unit outputs the duty cycle waveform to realize the loop control of the gate of the switching power supply power tube; then the output voltage of the switching power supply is sampled again, and Repeat the above process to cycle control the switching on and off of the power tube of the switching power supply to make the system more stable and obtain a higher dynamic response.
  • the logic unit output mode_F 1 enters the dynamic mode.
  • the dynamic mode refers to when the sampling voltage Vo increases greatly when the heavy load is switched to the light load.
  • the sampling voltage V o quickly returns to a stable voltage.
  • the sampling voltage V o drops to the reference voltage V ref , it jumps out of the dynamic mode and enters the normal mode.
  • the initial state of the normal mode is given by the mode control module;
  • the switching period calculation module output voltage monitoring module mode_F 1, the period calculation module is activated switch, and then calculate the size of the next cycle of the switching period T S (n + 1) is determined by the change of the sampling of the voltage V o;
  • the switching cycle calculation module passes the obtained cycle size T s (n + 1) of the next switching cycle to the mode control module, thereby controlling the switching of the main power tube.
  • the two comparators in the voltage monitoring module are COMP1 and COMP2.
  • the positive input terminal of the comparator COMP1 is connected to Vomax
  • the negative input terminal is connected to the sampling voltage V o
  • the positive input terminal of the comparator COMP2 is connected to the sampling voltage V o .
  • the input terminal is connected to the reference voltage V ref
  • the output of the comparator COMP1 and the output of the comparator COMP2 are connected to the logic unit, and the logic unit outputs a mode judgment result mode_F.
  • the PID module includes PID calculation and PID parameter selection.
  • the PID module works under the control of the control signal PI_ctrl output by the mode control module and the mode selection result mode_ctrl of the normal working mode.
  • PI_ctrl When PI_ctrl is PI_off, the PID module is turned off; when PI_ctrl is PI_set
  • PID operation parameters are selected according to the mode selection result mode_ctrl of the normal working mode, including proportional parameter K P , integral parameter K i and differential parameter K d for PID operation.
  • PI_set When PI_on, PID parameters are selected according to the mode selection result mode_ctrl of the normal working mode, PID calculation is performed, and the compensation result V PI is output to the mode control module and the PWM module.
  • the dynamic control method proposed by the present invention can make the output fast and stable through heavy load and light load mode with small energy when the sampling voltage V o exceeds the upper limit voltage Vomax.
  • the voltage change is greatly reduced and the dynamic recovery time is greatly reduced. small.
  • the dynamic control method proposed by the present invention monitors the change of the output voltage in the heavy-load cutting light-load mode to calculate the period of the next switching cycle, and obtains the size of the load according to the switching cycle.
  • the method of obtaining the switching cycle is iterative. After jumping out of the dynamic mode, it jumps to the working state of the corresponding load point. After the jump, the energy and the steady state consumption of the load are not much different, eliminating the subsequent voltage oscillations and reducing the dynamic recovery time.
  • the present invention can be used for both non-resonant power and non-resonant power, especially for non-resonant power such as single-tube resonance.
  • the advantages are more obvious, because non-linear power cannot be directly as linear power. Calculate the steady-state operating point.
  • the present invention can be applied to various types of switching power supply circuit structures, and has universality, reusability, and portability.
  • FIG. 1 is a system block diagram of a control method of the present invention
  • FIG. 2 is a structural block diagram of the voltage monitoring module in FIG. 1;
  • FIG. 2 is a structural block diagram of the voltage monitoring module in FIG. 1;
  • FIG. 3 is an application schematic diagram of a heavy load cutting light load HLT mode
  • FIG. 4a is a block diagram of a switching cycle calculation module in FIG. 1;
  • FIG. 4b is a schematic diagram of a midpoint iterative control algorithm;
  • FIG. 5 is an embodiment of a closed-loop circuit structure of a single-mode resonant flyback converter with a multi-mode control of the present invention
  • FIG. 6 is a curve of the dynamic response of the present invention to the multi-mode control of the single-tube resonant flyback converter circuit of FIG. 5 when the load is switched, and FIG. 6a is the dynamic result when the load is switched from 10 ⁇ to 500 ⁇ without using the present invention; Figure 6b is the dynamic result when the method of the present invention is adopted when the load is switched from 10 ⁇ to 500 ⁇ .
  • FIG. 1 is a system block diagram of a control method of the present invention.
  • the solid line arrow is the signal flow used by the control loop in normal operation mode, and the dotted arrow and the solid line arrow coexist are the signal flow in the control loop in dynamic mode.
  • the control method for improving the dynamic response of a switching power supply according to the present invention is based on a control system including a sampling module, a dynamic control module, an error calculation module, a PID module, a mode control module, and a PWM module.
  • the control system is connected to a controlled switching power supply to form a control system. A closed loop.
  • the sampling circuit in the sampling module samples the output voltage of the switching power supply and inputs the output voltage information to the sampling calculation module.
  • the sampling calculation module obtains the output voltage signal V o according to the sampling algorithm and inputs the current sampling voltage V o to the dynamic state.
  • the control module and the error calculation module calculate the current voltage error.
  • Dynamic control module comprises a voltage monitoring module and the switching period calculation module; voltage monitoring module receives the sampling module samples the output voltage V o, V omax and the upper limit value in accordance with the magnitude of V o respectively set V o, the reference voltage V ref Size relationship, to determine whether to use dynamic mode, where V ref ⁇ V omax ; dynamic mode refers to when the sampling voltage V o increases greatly when the heavy load cuts light load, the sampling voltage is reduced by reducing the input power of the entire system V o quickly returns to a stable voltage.
  • the input of the error calculation module is the sampling voltage V o , and the difference between the calculated reference voltage V ref and the sampling voltage V o is the current sampling error, which is recorded as e1 and output to the PID module.
  • the input of the mode control module is the output mode_F of the voltage monitoring module, the output T S (n + 1) of the switching cycle calculation module, and the operation result V PI of the PID module.
  • the control module turns off the PID module by outputting a control signal PI_ctrl, and controls the PWM module to receive the switching period T S (n + 1) and the duty cycle D HTL (or peak current) of the dynamic mode output by the control module.
  • the switching period T S (n + 1) of the mode and the duty cycle D HTL (or the magnitude of the peak current) generate a duty cycle waveform; when the mode control module jumps out of the dynamic mode and enters the normal switching mode, the mode control The module calculates the corresponding output load size according to the switching period T S (n + 1) of the module at this time.
  • the PID module is turned on and the current sampling result is assigned to V PIO before PID calculation.
  • V PIO is The output value of the PID module corresponding to the load in the steady state after the load changes. After the assignment, the PID module performs PID calculation based on the output error of the error module.
  • the PID calculation result V PI is inverse
  • the feed mode control module performs mode selection and control in the normal working mode; when the mode control module jumps out of the dynamic mode and enters the second switching cycle of the normal working mode, and after that, PI_ctrl turns on the PID module to perform calculations, and the PID module is based on the error module's The output error is subjected to PID calculation.
  • the calculation result V PI is fed back to the mode control module for mode selection and control in the normal working mode.
  • the PWM module receives the PID output compensation result V PI and the normal given by the mode control module.
  • the control mode is recorded as mode_ctrl.
  • the switching period and the duty cycle / current information are obtained through calculation.
  • the PWM module generates a duty cycle waveform according to the switching period and the duty cycle signal.
  • the PID module includes PID calculation function and PID parameter selection.
  • the PID module works under the control of the control signal (PI_ctrl) output by the mode control module and the mode selection result (mode_ctrl) of the normal operating mode.
  • PI_ctrl When PI_ctrl is PI_off, the PID module is turned off; PI_ctrl
  • V PI When PI_set, V PI is assigned by V PIO output by the mode control module, and PID operation parameters are selected according to the mode selection result (mode_ctrl) of the normal working mode, including proportional parameter K P , integral parameter K i , and differential parameter K d for PID. Operation.
  • PID parameters are selected according to the mode selection result (mode_ctrl) of the normal working mode, including the proportional parameter K P , the integral parameter K i , and the differential parameter K d . PID calculation is performed to compensate the result V PI input mode control Module and PWM module.
  • the input of the PWM module is the PI_ctrl control signal output by the mode control module, the switching period T S (n + 1) and the duty cycle D HTL (or peak current) of the dynamic mode, and the control mode result of the mode control module in the normal operating mode.
  • the drive circuit outputs a duty cycle waveform to implement loop control on the gate of the switching power supply power tube; then the output voltage of the switching power supply is sampled again and the above process is repeated to control the switching power supply in a loop.
  • the power tube is turned on and off to make the system more stable, so as to obtain a higher dynamic response.
  • FIG. 2 is a structural block diagram of a voltage monitoring module.
  • Voltage monitoring module receives the sampling module samples the output voltage value V o and V omax according to the size of the V o V o respectively set, the reference voltage V ref magnitude relationship, judges whether dynamic mode, where V ref ⁇ V omax ; dynamic mode means that when the heavy load is switched to the light load, when the output voltage increases greatly, the sampling voltage V o is quickly returned to the stable voltage by inputting a small power method.
  • the voltage monitoring module outputs the mode selection result mode_F to the mode control module and the switching cycle calculation module.
  • the switching cycle calculation module calculates the cycle T S of the next switching cycle; If in normal operation mode, the output latch of the control switching period calculation module is unchanged; when the voltage monitoring module outputs HTL mode, the switching period calculation module calculates the period T S of the next switching cycle; in the normal operation mode, the switching period calculation module The switching period is not calculated, and the period T S remains unchanged; the result T S of the switching period calculation module is output to the mode control module.
  • V o is greater than the upper limit voltage V omax
  • the logic unit outputs a dynamic mode. The output is quickly dropped to the reference voltage V ref by inputting small power and exits this mode to enter the normal mode. The initial state of the normal mode is given by the mode control module. . If V o does not change much, no dynamic mode is needed. Loop control through normal PI control methods and mode control is called normal working mode.
  • FIG. 3 is a schematic diagram of an application of a heavy-load-cut-light-load (HTL) mode.
  • HTL heavy-load-cut-light-load
  • FIG. 4a is a block diagram of a switching cycle calculation module.
  • the input signal of the switching cycle calculation module is the sampling voltage V o , and the judgment of the sampling voltage V o is performed to calculate the cycle value T s (n + 1) of the next cycle. If the sampling voltage V o of the current cycle increases, that is, when V o (n + 1)> V o (n), the current cycle T s (n) ⁇ T s_s is described , where T s_s is a steady state switching cycle.
  • T s_min T s (n)
  • T s_max T s (n) / 2
  • the sampling voltage V o of the current cycle drops, V o (n When +1)> V o (n)
  • the switching cycle calculation module obtains the cycle size
  • FIG. 4b is a schematic diagram of the midpoint iterative control algorithm.
  • the working process of midpoint iteration is given here.
  • the heavy load is switched to the light load, the output voltage will continue to rise.
  • the sampling voltage V o reaches the upper limit V omax , the circuit enters the dynamic control mode. Assume that the current period is T o , as shown in FIG. 4b, and the sampling voltage V o is in the rising state at this time, indicating that the switching period at this time is less than the stable switching period T s_s , and the switching period of the next period is adjusted to 2 T o , such as Figure 4b.
  • the sampling voltage V o is in a falling state, which indicates that the switching period at this time is greater than the switching period T s_s when it is stable, and the switching period of the next cycle is adjusted to 1.5 T o by using the midpoint iteration.
  • the stable switching period T s_s is finally reached, and the sampling voltage V o is still near V omax at this time.
  • the switching period is lengthened to reduce the input power, and the low-frequency step-down is used to make the output voltage reach the standard value.
  • FIG. 5 is an embodiment of a closed-loop circuit structure diagram of a multi-mode control single-tube resonance flyback converter according to the present invention.
  • the method and system used in the present invention can also be used in other types of switching power supply circuit structures.
  • a primary flyback circuit is used as an example.
  • the input of the flyback converter is 90 ⁇ 265V, the output is 5V, the maximum current is 1A, the inductance is 1.6mH, the transformer turns ratio is 104/6, and the output is constant voltage.
  • the converter adopts DCM control method and realizes digital control through multi-mode control method.
  • the working modes of existing circuits under different loads are given below. Based on this mode, the working method of optimizing dynamic performance in this example is added.
  • FIG. 6 is a curve of the dynamic response of the present invention to the multi-mode control of the single-tube resonant flyback converter circuit of FIG. 5 when the load is switched; and a curve of the dynamic response using the technique for improving the dynamic response herein; this is the implementation of the present invention example.
  • Fig. 6a is the dynamic result before the method of improving dynamics in this article is not adopted when the load is switched from 10 ⁇ to 500 ⁇ ;
  • Fig. 6b is the dynamic result after the load is switched from 10 ⁇ to 500 ⁇ using the method of improving dynamics of the present invention.
  • PI adjustment is adopted, with a recovery time of 20.48ms and an overshoot voltage of 0.525V; after the method of improving the dynamic response of the present invention is adopted, the recovery time is 2.232ms and the overshoot voltage is 0.52V, and the dynamic performance is greatly improved.

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Abstract

一种提高开关电源重载切轻载动态响应的控制方法，基于包括采样模块、动态控制模块、误差计算模块、PID模块、模式控制模块以及PWM模块构成的控制系统，该控制系统与受控的开关电源连接起来构成一个闭环，在开关电源输出电压超出其设定上限电压时，通过小能量的重载切轻载模式使得输出快速稳定，在重载切轻载模式中监测输出电压的变化进而计算下一开关周期的周期，并根据开关周期得到负载的大小，当跳出动态模式后，跳到对应负载点的工作状态，跳变后能量与负载稳态消耗相差不大，消除了后续的电压振荡，减小动态回复时间。

Description

一种提高开关电源重载切轻载动态响应的控制方法 技术领域
本发明涉及开关电源，尤其涉及一种提高开关电源重载切轻载动态响应的控制方法。
技术背景
电源是各个电子设备不可或缺的组成部分，其性能的优劣直接关系到电子设备的技术指标以及其能否安全可靠的工作，而目前主流应用是开关电源(Switch Mode Power Supply)。开关电源又称之为开关变换器，是利用现代电力电子技术，通过调整开关器件的导通比或者频率来使输出电压恒定的一种电源。
由于开关电源需要适应于不同的工作条件，对电源的动态响应的性能要求越来越高。好的动态效果要求与有小的电压变化以及电压恢复时间。举例而言在家电应用中，洗衣机的电源负载变化很快很大，这样电源输出电压引入过压与欠压，当过压与欠压过大时对洗衣机的负载伤害较大；另外在手机充电中，当充电器待机，手机突然加载，输出电压降低，当降低到电池的正常电压下，对电池有一定的伤害，因此动态性能需要提高。
在现在的电源管理中，为了使得电源有较高的效率，一般的电源选择多模式的控制方法，多模式控制方法会引入动态性能下降的问题。以5V，1A输出的反激变换器为例，当负载功耗减小时，为了减小电路损耗通常会减小开关频率。定义1A负载，为负载A，开关频率f A为70kHz，电路具有较高的效率，0.7A负载为负载B，开关频率f B为70kHz，0.2A负载为负载C，开关频率f C为20kHz，0.05A负载为负载D，开关频率f D为20kHz，负载点的开关频率选择是根据系统效率要求而选择的。当负载介于AB之间，采用PWM模式，负载介于BC之间，采用PFM模式，负载介于CD之间，采用PWM模式，记为DPWM模式，负载小于负载D时，采用PFM模式，记为DPFM模式，负载从轻到重的工作模式为DPFM-DPWM-PFM-PWM。若负载为待机时，根据假负载的大小，假定待机频率为2kHz，此时控制模式为DPFM模式，若负载突然改变为满载，输出电压以很快的速度下降，根据补偿结果控制模式将会分别经过DPWM，PFM，PWM模式，在补偿结果未达到满载的条件时，输出电压是一直在下降的，这可能造成严重电压下降，在有的条件下是无法忍受的；同样的在满载切换到轻载时，中间的模式控制过程会造成电压的持续上升，电压会产生很大的过冲。另外，在有的条件下，为了防止模式切换时，在切换点附近，控制模式在两个模式之间来回切换，从一个模式切换到另一个模式需要经过几个周期来确认需要切换模式控制，这种条件下，动态的效果会进一步降低。
此外，在一些控制中，只能在一个周期采样一次，例如在原边反馈的反激电源中，输出电压在只能在次级电流下降到零之前来采样。这样当负载由轻切重时，DPWM的开关频率低，即使PI调整很大，但为了保证稳定性，动态过程更加缓慢。
另外，有的控制方法为了加快动态响应的速度，会提高PI参数来加快补偿，以此来提高动态效果，但在多模式控制对提高动态性能效果改善不大。
现有技术还公开了一种根据斜率与负载的一一对应单调性质的关系得到负载的大小，从而得到切换后的对应的开关周期，但只能用于非谐振的常规开关电源。
因此，由于动态性能要求越来越高，多模式控制方法带来的动态问题，提出一种提高开关电源重载切轻载动态响应的控制方法。对减小电压过冲，减小动态回复时间有很好的效果，对提高电路的动态性能很有必要。
发明内容
为克服现有技术的局限和不足，本发明提出了一种提高开关电源重载切轻载动态响应的控制方法，可以限制输出电压的过冲在一定的范围内，并减小动态回复时间，提高动态性能，在多模式控制中不会引起系统的不稳定，使得电路的设计动态性能更优秀。
为了实现上述目的，本发明采用如下的技术方案：
一种提高开关电源重载切轻载动态响应的控制方法，其特征在于：基于包括采样模块、动态控制模块、误差计算模块、PID模块、模式控制模块以及PWM模块构成的控制系统，该控制系统与受控的开关电源连接起来构成一个闭环；
采样模块包括采样电路和采样计算模块，采样电路通过开关电源输出分压得到输出电压的信息，采样计算模块根据该输出电压的信息，计算得到对应输出电压大小的采样电压V o并同时输出给误差计算模块和动态控制模块；
动态控制模块包括电压监测模块和开关周期计算模块，电压监测模块包含两个比较器以及一个逻辑单元，其中一个比较器用于比较采样电压Vo与采样电压Vo的设定上限值Vomax之间的大小，另一个比较器用于比较采样电压Vo与参考电压V ref之间的大小，两个比较器的比较结果分别输出给逻辑单元，逻辑单元输出模式判断结果mode_F并根据该模式判断结果mode_F确定是否采用动态模式，其中V ref＜V omax；
电压监测模块将模式判断结果mode_F分别输出给模式控制模块和开关周期计算模块，开关周期计算模块输出开关周期T S给模式控制模块，开关周期计算模块根据采样模块输出的采样电压V o和电压监测模块输出的模式判断结果mode_F进行计算，当mode_F＝1进入动态 模式时，计算下一开关周期的周期T S＝T S(n+1)，当mode_F＝0时进入正常模式时，开关周期计算模块不工作，输出开关周期T S＝T S(n+1)通过锁存保持不变；
误差计算模块根据采样模块输出的采样电压V o计算参考电压Vref减去采样电压V o的差，即为当前采样误差，记为e1，输出给PID模块；
PID模块输入为误差计算模块输出的误差信号e1、模式控制模块输出的控制信号PI_ctrl以及赋值V PIO，动态模式时，PID模块关闭，动态模式切换到正常工作模式的第一个开关周期时，首先对PID模块运算赋初值V PIO，然后进行PID运算得到补偿结果V PI输出给模式控制模块和PWM模块，之后正常工作模式的每个周期进PID运算，补偿结果V PI输出给模式控制模块和PWM模块；
模式控制模块的输入分别为电压监测模块输出的模式判断结果mode_F、开关周期计算模块的输出的开关周期T S＝T S(n+1)以及PID模块的补偿结果V PI；当电压监测模块输出mode_F＝1为动态模式时，模式控制模块通过输出控制信号PI_ctrl关闭PID模块、控制PWM模块接收模式控制模块输出的动态模式的开关周期T S(n+1)与占空比D HTL或峰值电流，PWM模块此时根据动态模式的开关周期T S(n+1)与占空比D HTL或峰值电流大小产生占空比波形；当模式控制模块在跳出动态模式进入正常工作模式的第一个开关周期，模式控制模块根据此时开关周期计算模块的周期大小T S(n+1)得到对应的输出负载的大小，通过控制信号PI_ctrl开启PID模块并在PID计算前将当前采样结果赋值V PIO，V PIO为负载变化后在稳定状态时负载对应的PID模块的输出值，赋值后PID模块根据误差模块的输出误差e1进行PID运算，PID运算结果V PI反馈给模式控制模块进行正常工作模式中的模式选择与控制；当模式控制模块在跳出动态模式进入正常工作模式的第二个开关周期以及以后，PI_ctrl开启PID模块进行运算，PID模块根据误差模块的输出误差e1进行PID运算，运算结果V PI反馈给模式控制模块进行正常工作模式中的模式选择与控制，在正常工作模式中，PWM模块接收PID输出的补偿结果V PI与模式控制模块给出的正常工作模式的控制模式，该控制模式记为mode_ctrl，通过计算得到开关周期与占空比/电流信息，PWM模块此时根据 该开关周期与占空比信号产生占空比波形；
PWM模块包括PWM单元和驱动单元，PWM单元的输入为模式控制模块输出的PI_ctrl控制信号、动态模式的开关周期T S(n+1)与占空比D HTL或峰值电流Ip、模式控制模块在正常工作模式时的控制模式结果mode_ctrl以及PID模块的补偿结果V PI；通过PID模块补偿结果V PI与模式控制模块给出的正常工作模式的控制模式mode_ctrl信号计算得到正常控制时开关周期与占空比的信息，得到周期与占空比/峰值电流信息后，通过驱动单元输出占空比波形，对开关电源功率管的栅极实现环路控制；然后再次对开关电源的输出电压进行采样，并重复上述过程进行循环控制开关电源功率管的开通和关断，以使系统更加稳定，从而获得更高的动态响应。
当V o比上限电压V omax大时，逻辑单元输出mode_F＝1进入动态模式，动态模式是指当重载切轻载时，采样电压Vo增加很大时，通过给系统输入小功率的方法使得采样电压V o快速返回到稳定电压，当采样电压V o下降到参考电压V ref后跳出动态模式，进入正常模式，正常模式的起始状态由模式控制模块给定；
如果采样电压V o变化不大，无需动态模式，通过正常的PID控制方法与模式控制实现环路控制，称为正常工作模式。
所述的开关周期计算模块在电压监测模块输出mode_F＝1时，开关周期计算模块被激活，通过判断采样电压V o的变化趋势进而计算下一开关周期的周期大小T S(n+1)；
在当前周期的采样电压V o增加，即V o(n+1)＞V o(n)时，说明当前周期T s(n)＜T s_s，其中T s_s是稳定状态的开关周期，此时令T s_min＝T s(n)，则下一周期的大小T s(n+1)＝(T smin+T smax)/2；
在当前周期的采样电压V o下降，即V o(n+1)＞V o(n)时，说明此时T s(n)＞T s_s，此时令T s(n)＝T s_max，则下一周期的大小为T s(n+1)＝(T smin+T smax)/2；
在当前周期的采样电压V o保持不变，即V o(n+1)＝V o(n)时，说明此时T s(n)＞T s_s，此 时令T s(n)＞T s_s，则下一周期的大小为T s(n+1)＝(T smin+T smax)/2；
开关周期计算模块将得到的下一开关周期的周期大小T s(n+1)传递给模式控制模块，进而控制主功率管的开关。
所述电压监测模块中的两个比较器分别为COMP1和COMP2，比较器COMP1的正输入端连接Vomax，负输入端连接采样电压V o，比较器COMP2的正输入端连接采样电压V o，负输入端连接参考电压V ref，比较器COMP1的输出和比较器COMP2的输出均连接至逻辑单元，逻辑单元输出模式判断结果mode_F。
所述PID模块包括PID运算与PID参数选择，PID模块在模式控制模块输出的控制信号PI_ctrl与正常工作模式的模式选择结果mode_ctrl的控制下工作，PI_ctrl为PI_off时，PID模块关闭；PI_ctrl为PI_set时，V PI被模式控制模块输出的V PIO赋值后，根据正常工作模式的模式选择结果mode_ctrl选择PID运算参数，包括比例参数K P、积分参数K i及微分参数K d进行PID运算，当PI_set为PI_on时，根据正常工作模式的模式选择结果mode_ctrl选择PID参数，进行PID运算，补偿结果V PI输出给模式控制模块和PWM模块。
本发明的优点及显著效果：
1、本发明提出的动态控制方法，能够在采样电压V o超出上限电压Vomax时，通过小能量的重载切轻载模式使得输出快速稳定，电压变化大幅度减小，动态回复时间大幅度减小。
2、本发明提出的动态控制方法在重载切轻载模式中监测输出电压的变化进而计算下一开关周期的周期，并根据开关周期得到负载的大小，得到开关周期的方法是迭代。当跳出动态模式后，跳到对应负载点的工作状态，跳变后能量与负载稳态消耗相差不大，消除了后续的电压振荡，减小动态回复时间。
3、本发明增加重载切轻载工作模式以及周期判断工作点的方法对一般的多模式设计环路的稳定性不会产生影响。
4、本发明既能用于非谐振电源，也能用于非谐振电源，尤其是对于像单管谐振这样的非线性电源的优势更加明显，这是因为非线性电源不能够像线性电源那样直接计算稳态工作点。
5、本发明能适用于各类开关电源电路结构，具备通用性，可复用性和可移植性。
附图说明
图1是本发明控制方法的系统结构框图；
图2是图1中的电压监测模块结构框图；
图3是重载切轻载HLT模式的应用示意图；
图4a是图1中的开关周期计算模块结构框图；图4b是中点迭代控制算法的原理示意图；
图5是具有本发明的多模式控制单管谐振反激变换器的闭环电路结构图实施例；
图6是本发明对图5的单管谐振反激变换器电路在负载切换时多模式控制的动态响应的曲线，图6a是负载从10Ω切换到500Ω时，未采用本发明前的动态结果；图6b是负载从10Ω切换到500Ω时，采用了本发明方法后的动态结果。
具体实施方式
为了更清楚地说明本发明，下面将结合附图及实施例，对本发明的技术方案进行清楚、完整的描述。
图1为本发明控制方法的系统结构框图。实线箭头是正常工作模式中控制环路使用的信号流程，虚线箭头与实线箭头并存是动态模式中控制环路中的信号流程。
本发明提高开关电源动态响应的控制方法，基于包括采样模块、动态控制模块、误差计算模块、PID模块、模式控制模块以及PWM模块构成的控制系统，该控制系统与受控的开关电源连接起来构成一个闭环。
采样模块中的采样电路对开关电源的输出电压进行采样，得到输出电压信息输入到采样计算模块，采样计算模块根据采样算法得到输出电压大小的信号V o，将当前的采样电压V o输入到动态控制模块与误差计算模块，误差计算模块计算当前的电压误差。
动态控制模块包括电压监测模块和开关周期计算模块；电压监测模块接收采样模块输出的采样电压V o，并根据V o的大小分别与设定的V o上限值V omax、参考电压V ref的大小关系，判断是否采用动态模式，其中V ref＜V omax；动态模式是指当重载切轻载时，采样电压V o增加很大时，通过减小整个系统的输入功率的方法使得采样电压V o快速返回到稳定电压。
误差计算模块的输入是采样电压V o，根据计算参考电压V ref减去采样电压V o的差，即为当前采样误差，记为e1，输出给PID模块。
模式控制模块的输入分别为电压监测模块的输出mode_F、开关周期计算模块的输出T S(n+1)以及PID模块的运算结果V PI；当电压监测模块输出mode_F＝1时为动态模式， 模式控制模块通过输出控制信号PI_ctrl关闭PID模块，控制PWM模块接收模式控制模块输出的动态模式的开关周期T S(n+1)与占空比D HTL(或峰值电流)，PWM模块此时根据动态模式的开关周期T S(n+1)与占空比D HTL(或峰值电流大小)产生占空比波形；当模式控制模块在跳出动态模式进入正常工作模式的第一个开关周期，模式控制模块根据此时开关周期计算模块的周期大小T S(n+1)得到对应的输出负载的大小，通过控制信号PI_ctrl，开启PID模块并在PID计算前将当前采样结果赋值V PIO，V PIO为负载变化后在稳定状态时负载对应的PID模块的输出值，赋值后PID模块根据误差模块的输出误差进行PID运算，PID运算结果V PI反馈给模式控制模块进行正常工作模式中的模式选择与控制；当模式控制模块在跳出动态模式进入正常工作模式的第二个开关周期以及以后，PI_ctrl开启PID模块进行运算，PID模块根据误差模块的输出误差进行PID运算，运算结果V PI反馈给模式控制模块进行正常工作模式中的模式选择与控制，在正常工作模式中，PWM模块接收PID输出的补偿结果V PI与模式控制模块给出的正常工作模式的控制模式，该控制模式记为mode_ctrl，通过计算得到开关周期与占空比/电流信息，PWM模块此时根据该开关周期与占空比信号产生占空比波形。
PID模块包括PID运算功能与PID参数选择，PID模块在模式控制模块输出的控制信号(PI_ctrl)与正常工作模式的模式选择结果(mode_ctrl)的控制下工作，PI_ctrl为PI_off时，PID模块关闭；PI_ctrl为PI_set时，V PI被模式控制模块输出的V PIO赋值后，根据正常工作模式的模式选择结果(mode_ctrl)选择PID运算参数，包括比例参数K P，积分参数K i，微分参数K d进行PID运算，当PI_set为PI_on时，根据正常工作模式的模式选择结果(mode_ctrl)选择PID参数，包括比例参数K P，积分参数K i，微分参数K d，进行PID运算，补偿结果V PI输入模式控制模块与PWM模块。
PWM模块的输入为模式控制模块输出的PI_ctrl控制信号、动态模式的开关周期T S(n+1)与占空比D HTL(或峰值电流)、模式控制模块在正常工作模式时的控制模式结果 mode_ctrl以及PID模块的补偿结果V PI；通过PID模块补偿结果V PI与模式控制模块给出的正常工作模式的控制模式mode_ctrl信号计算得到正常控制时开关周期与占空比的信息，得到周期与占空比/峰值电流信息后，通过驱动电路输出占空比波形，对开关电源功率管的栅极实现环路控制；然后再次对开关电源的输出电压进行采样，并重复上述过程进行循环控制开关电源功率管的开通和关断，以使系统更加稳定，从而获得更高的动态响应。
图2是电压监测模块结构框图。电压监测模块接收采样模块输出的采样电压V o并根据V o的大小分别与设定的V o上限值V omax、参考电压V ref的大小关系，判断是否采用动态模式，其中V ref＜V omax；动态模式是指当重载切轻载时，输出电压增加很大时，通过输入小功率的方法使得采样电压V o快速返回到稳定电压。电压监测模块将模式选择结果mode_F输出到模式控制模块与开关周期计算模块，若电压监测模块输出mode_F＝1，即判断系统进入动态模式时，开关周期计算模块计算下一开关周期的周期T S；若正常工作模式时，控制开关周期计算模块的输出锁存不变；开关周期计算模块在电压监测模块输出HTL模式时计算下一开关周期的周期T S；采用正常工作模式时，开关周期计算模块不计算开关周期，周期T S保持不变；开关周期计算模块的结果T S输出给模式控制模块。当V o比上限电压V omax大，逻辑单元输出动态模式，通过输入小功率使得输出快速下降到参考电压V ref后跳出该模式，进入正常模式，正常模式的起始状态由模式控制模块给定。如果V o变化不大，无需动态模式，通过正常的PI控制方法与模式控制实现环路控制称为正常工作模式。
图3是重载切轻载(HTL)模式的应用示意图。在重载切轻载时，从该示意图可以看到当采样电压V o大于V omax时，采用HTL模式。若采用PID调节则如粗虚线所示，在采样电压上升到V omax后电压任然会有所上升，动态恢复时间也很长；采用HTL模式，当采样电压V o大于V omax时，立刻采用HTL模式，由于该模式的输入功率一般小于待机功率，采样电压V o立刻开始下降，不会再有所上升，在采样电压V o下降到稳定值前，这是最快的动态方法，当采样电压V o与稳定电压相同时，可以通过斜率大小得到输出负载大小，使得跳出HTL模式的工作模式能量与负载功耗相近，去掉后续能量不吻合引入的谐振，如实线所示；可以看到若跳出HTL模式后，若工作状态从待机开始，其输入能量偏低，引入电压谐振，如细虚 线所示。
图4a是开关周期计算模块结构框图。在电压监测模块输出mode_F＝1时，开关周期计算模块被激活。开关周期计算模块的输入信号是采样电压V o，通过对采样电压V o进行判断，从而计算出下一周期的周期值T s(n+1)。若当前周期的采样电压V o增加时，即V o(n+1)＞V o(n)时，说明当前周期T s(n)＜T s_s，其中T s_s是稳定状态的开关周期，此时令T s_min＝T s(n)，则下一周期的大小T s(n+1)＝(T smin+T smax)/2；若当前周期的采样电压V o下降时，即V o(n+1)＞V o(n)时，说明此时T s(n)＞T s_s，此时令T s(n)＝T s_max，则下一周期的大小为T s(n+1)＝(T smin+T smax)/2；若当前周期的采样电压V o保持不变时，即V o(n+1)＝V o(n)时，说明此时T s(n)＝T s_s，此时令T s(n)＝T s_s，则下一周期的大小为T s(n+1)＝(T smin+T smax)/2。开关周期计算模块得到下一开关周期的周期大小T s(n+1)，并将其传递给模式控制模块，进而控制主功率管的开关。
图4b是中点迭代控制算法的原理示意图。为了更加清楚地说明开关周期计算过程中的“中点迭代”的原理，这里给出了中点迭代的工作过程。在重载切轻载的时候，输出电压会持续上升，当采样电压V o达到上限V omax时，电路进入动态控制模式。假设当前周期为T o，如图4b所示，此时采样电压V o处于上升状态，说明此时的开关周期小于稳定时的开关周期T s_s，调整下一周期的开关周期为2T o，如图4b所示。此时采样电压V o处于下降状态，说明此时的开关周期大于稳定时的开关周期T s_s，利用中点迭代调整下一周期的开关周期为1.5T o。以此类推，最终达到稳定的开关周期T s_s，此时采样电压V o仍处于V omax附近，此时拉长开关周期，使输入功率减小，采用低频降压，使输出电压达到标准值。
图5是具有本发明的多模式控制单管谐振反激变换器的闭环电路结构图实施例。本发明使用的方法和系统也可用于其他类型的开关电源电路结构，此处以原边反馈的反激电路为例。反激变换器实例的输入为90～265V，输出为5V，电流最大为1A，电感大小为1.6mH，变压器匝比为104/6，输出恒压。变换器采用DCM的控制方法，通过多模式控制方法实现数字控制，下面给出已有电路的在不同负载下的工作模式，在该模式的基础上，增加本实 例中优化动态性能的工作方法。
图6为本发明对图5的单管谐振反激变换器电路在负载切换时多模式控制的动态响应的曲线；以及采用了本文提高动态响应的技术的动态响应的曲线；此为本发明实施例。图6a为负载从10Ω切换到500Ω时，未采用本文的提高动态方法前的动态结果；图6b为负载从10Ω切换到500Ω时，采用本发明的提高动态方法后的动态结果。在未采用前，采用PI调节，恢复时间20.48ms，过冲电压0.525V；在采用了本发明的提高动态响应的方法之后，恢复时间2.232ms，过冲电压0.52V，动态性能大幅度提升。
从上面的实例中可以看出，采用本发明方法后，尤其对于多模式控制系统，动态性能得到了大幅度的提高。
以上内容是结合具体的优选实施方式对本发明所作的进一步详细说明，不能认定本发明的具体实施只局限于这些说明，在此描述的本发明可以有许多变化(轻负载切换重负载)，这些变化不能人为偏离本发明的精神和范围。因此，所有对本领域技术人员显而易见的改变，都包括在本权利要求书的涵盖范围之内。

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  1. 一种提高开关电源重载切轻载动态响应的控制方法，其特征在于：基于包括采样模块、动态控制模块、误差计算模块、PID模块、模式控制模块以及PWM模块构成的控制系统，该控制系统与受控的开关电源连接起来构成一个闭环；
    采样模块包括采样电路和采样计算模块，采样电路通过开关电源输出分压得到输出电压的信息，采样计算模块根据该输出电压的信息，计算得到对应输出电压大小的采样电压V o并同时输出给误差计算模块和动态控制模块；
    动态控制模块包括电压监测模块和开关周期计算模块，电压监测模块包含两个比较器以及一个逻辑单元，其中一个比较器用于比较采样电压Vo与采样电压Vo的设定上限值Vomax之间的大小，另一个比较器用于比较采样电压Vo与参考电压V ref之间的大小，两个比较器的比较结果分别输出给逻辑单元，逻辑单元输出模式判断结果mode_F并根据该模式判断结果mode_F确定是否采用动态模式，其中V ref＜V omax；
    电压监测模块将模式判断结果mode_F分别输出给模式控制模块和开关周期计算模块，开关周期计算模块输出开关周期T S给模式控制模块，开关周期计算模块根据采样模块输出的采样电压V o和电压监测模块输出的模式判断结果mode_F进行计算，当mode_F＝1进入动态模式时，计算下一开关周期的周期T S＝T S(n+1)，当mode_F＝0时进入正常模式时，开关周期计算模块不工作，输出开关周期T S＝T S(n+1)通过锁存保持不变；
    误差计算模块根据采样模块输出的采样电压V o计算参考电压Vref减去采样电压V o的差，即为当前采样误差，记为e1，输出给PID模块；
    PID模块输入为误差计算模块输出的误差信号e1、模式控制模块输出的控制信号PI_ctrl以及赋值V PIO，动态模式时，PID模块关闭，动态模式切换到正常工作模式的第一个开关周期时，首先对PID模块运算赋初值V PIO，然后进行PID运算得到补偿结果V PI输出给模式控制模块和PWM模块，之后正常工作模式的每个周期进PID运算，补偿结果V PI输出给模式控制模块和PWM模块；
    模式控制模块的输入分别为电压监测模块输出的模式判断结果mode_F、开关周期计算模块的输出的开关周期T S＝T S(n+1)以及PID模块的补偿结果V PI；当电压监测模块输出mode_F＝1为动态模式时，模式控制模块通过输出控制信号PI_ctrl关闭PID模块、控制PWM 模块接收模式控制模块输出的动态模式的开关周期T S(n+1)与占空比D HTL或峰值电流，PWM模块此时根据动态模式的开关周期T S(n+1)与占空比D HTL或峰值电流大小产生占空比波形；当模式控制模块在跳出动态模式进入正常工作模式的第一个开关周期，模式控制模块根据此时开关周期计算模块的周期大小T S(n+1)得到对应的输出负载的大小，通过控制信号PI_ctrl开启PID模块并在PID计算前将当前采样结果赋值V PIO，V PIO为负载变化后在稳定状态时负载对应的PID模块的输出值，赋值后PID模块根据误差模块的输出误差e1进行PID运算，PID运算结果V PI反馈给模式控制模块进行正常工作模式中的模式选择与控制；当模式控制模块在跳出动态模式进入正常工作模式的第二个开关周期以及以后，PI_ctrl开启PID模块进行运算，PID模块根据误差模块的输出误差e1进行PID运算，运算结果V PI反馈给模式控制模块进行正常工作模式中的模式选择与控制，在正常工作模式中，PWM模块接收PID输出的补偿结果V PI与模式控制模块给出的正常工作模式的控制模式，该控制模式记为mode_ctrl，通过计算得到开关周期与占空比/电流信息，PWM模块此时根据该开关周期与占空比信号产生占空比波形；
    PWM模块包括PWM单元和驱动单元，PWM单元的输入为模式控制模块输出的PI_ctrl控制信号、动态模式的开关周期T S(n+1)与占空比D HTL或峰值电流Ip、模式控制模块在正常工作模式时的控制模式结果mode_ctrl以及PID模块的补偿结果V PI；通过PID模块补偿结果V PI与模式控制模块给出的正常工作模式的控制模式mode_ctrl信号计算得到正常控制时开关周期与占空比的信息，得到周期与占空比/峰值电流信息后，通过驱动单元输出占空比波形，对开关电源功率管的栅极实现环路控制；然后再次对开关电源的输出电压进行采样，并重复上述过程进行循环控制开关电源功率管的开通和关断，以使系统更加稳定，从而获得更高的动态响应。
  2. 根据权利要求1所述的提高开关电源重载切轻载动态响应的控制方法，其特征在于：当V o比上限电压V omax大时，逻辑单元输出mode_F＝1进入动态模式，动态模式是指当重载切轻载时，采样电压Vo增加很大时，通过给系统输入小功率的方法使得采样电压V o快速返回到 稳定电压，当采样电压V o下降到参考电压V ref后跳出动态模式，进入正常模式，正常模式的起始状态由模式控制模块给定；
    如果采样电压V o变化不大，无需动态模式，通过正常的PID控制方法与模式控制实现环路控制，称为正常工作模式。
  3. 根据权利要求1所述的提高开关电源重载切轻载动态响应的控制方法，其特征在于：所述的开关周期计算模块在电压监测模块输出mode_F＝1时，开关周期计算模块被激活，通过判断采样电压V o的变化趋势进而计算下一开关周期的周期大小T S(n+1)；
    在当前周期的采样电压V o增加，即V o(n+1)＞V o(n)时，说明当前周期T s(n)＜T s_s，其中T s_s是稳定状态的开关周期，此时令T s_min＝T s(n)，则下一周期的大小T s(n+1)＝(T smin+T smax)/2；
    在当前周期的采样电压V o下降，即V o(n+1)＞V o(n)时，说明此时T s(n)＞T s_s，此时令T s(n)＝T s_max，则下一周期的大小为T s(n+1)＝(T smin+T smax)/2；
    在当前周期的采样电压V o保持不变，即V o(n+1)＝V o(n)时，说明此时T s(n)＝T s_s，此时令T s(n)＝T s_s，则下一周期的大小为T s(n+1)＝(T smin+T smax)/2；
    开关周期计算模块将得到的下一开关周期的周期大小T s(n+1)传递给模式控制模块，进而控制主功率管的开关。
  4. 根据权利要求1所述的提高开关电源重载切轻载动态响应的控制方法，其特征在于：所述电压监测模块中的两个比较器分别为COMP1和COMP2，比较器COMP1的正输入端连接Vomax，负输入端连接采样电压V o，比较器COMP2的正输入端连接采样电压V o，负输入端连接参考电压V ref，比较器COMP1的输出和比较器COMP2的输出均连接至逻辑单元，逻辑单元输出模式判断结果mode_F。
  5. 根据权利要求1所述的提高开关电源重载切轻载动态响应的控制方法，其特征在于：所述PID模块包括PID运算与PID参数选择，PID模块在模式控制模块输出的控制信号PI_ctrl 与正常工作模式的模式选择结果mode_ctrl的控制下工作，PI_ctrl为PI_off时，PID模块关闭；PI_ctrl为PI_set时，V PI被模式控制模块输出的V PIO赋值后，根据正常工作模式的模式选择结果mode_ctrl选择PID运算参数，包括比例参数K P、积分参数K i及微分参数K d进行PID运算，当PI_set为PI_on时，根据正常工作模式的模式选择结果mode_ctrl选择PID参数，进行PID运算，补偿结果V PI输出给模式控制模块和PWM模块。
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