WO2018202038A1 - 一种确定上行同步定时偏差的方法及装置 - Google Patents

一种确定上行同步定时偏差的方法及装置 Download PDF

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WO2018202038A1
WO2018202038A1 PCT/CN2018/085328 CN2018085328W WO2018202038A1 WO 2018202038 A1 WO2018202038 A1 WO 2018202038A1 CN 2018085328 W CN2018085328 W CN 2018085328W WO 2018202038 A1 WO2018202038 A1 WO 2018202038A1
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value
radians
base station
preamble signal
preamble
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PCT/CN2018/085328
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English (en)
French (fr)
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喻理
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大唐移动通信设备有限公司
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Priority to US16/610,518 priority Critical patent/US10897744B2/en
Priority to EP18793802.2A priority patent/EP3621241B1/en
Priority to JP2019560316A priority patent/JP6824442B2/ja
Publication of WO2018202038A1 publication Critical patent/WO2018202038A1/zh

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/003—Arrangements for allocating sub-channels of the transmission path
    • H04L5/0048—Allocation of pilot signals, i.e. of signals known to the receiver
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W56/00—Synchronisation arrangements
    • H04W56/0005—Synchronisation arrangements synchronizing of arrival of multiple uplinks
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/69—Spread spectrum techniques
    • H04B1/713—Spread spectrum techniques using frequency hopping
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/0224—Channel estimation using sounding signals
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2662—Symbol synchronisation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2662—Symbol synchronisation
    • H04L27/2663—Coarse synchronisation, e.g. by correlation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2668—Details of algorithms
    • H04L27/2669—Details of algorithms characterised by the domain of operation
    • H04L27/2672—Frequency domain
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2668—Details of algorithms
    • H04L27/2673—Details of algorithms characterised by synchronisation parameters
    • H04L27/2675—Pilot or known symbols
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2689—Link with other circuits, i.e. special connections between synchronisation arrangements and other circuits for achieving synchronisation
    • H04L27/2695—Link with other circuits, i.e. special connections between synchronisation arrangements and other circuits for achieving synchronisation with channel estimation, e.g. determination of delay spread, derivative or peak tracking
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W56/00—Synchronisation arrangements
    • H04W56/001—Synchronization between nodes
    • H04W56/0015—Synchronization between nodes one node acting as a reference for the others
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W56/00—Synchronisation arrangements
    • H04W56/004—Synchronisation arrangements compensating for timing error of reception due to propagation delay
    • H04W56/0045—Synchronisation arrangements compensating for timing error of reception due to propagation delay compensating for timing error by altering transmission time
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W56/00—Synchronisation arrangements
    • H04W56/0055—Synchronisation arrangements determining timing error of reception due to propagation delay
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/0001—Arrangements for dividing the transmission path
    • H04L5/0003—Two-dimensional division
    • H04L5/0005—Time-frequency
    • H04L5/0007—Time-frequency the frequencies being orthogonal, e.g. OFDM(A), DMT
    • H04L5/0012—Hopping in multicarrier systems

Definitions

  • the present invention relates to the field of communications technologies, and in particular, to a method and apparatus for determining an uplink synchronization timing offset.
  • the Narrow Band Internet of Things (NB-IoT) system is a terminal device (English: User Equipment, UE for short).
  • the distance between the base stations is uncertain.
  • the UE needs to establish uplink synchronization with the base station through the random access procedure.
  • the base station detects that the UE sends the preamble preamble signal, estimates the uplink synchronization timing deviation through the received preamble signal, and obtains the uplink synchronization timing deviation.
  • the inbound response sends an uplink synchronization timing offset to the UE.
  • the UE calculates the timing advance and adjusts the transmission time of the uplink signal, thereby implementing uplink synchronization.
  • Preamble sequences are generated by cyclic shifting of ZC sequences derived from the root sequence of one or more ZC sequences.
  • the uplink synchronization timing deviation calculation method used in the LTE system is that the base station performs the following processing on the preamble signals transmitted by the UE through the respective antennas, and performs FFT transformation to transform the Preamble signal from the time domain to the frequency domain, and performs subcarrier demapping. deal with. Then, the preamble signal subjected to the subcarrier demapping process is transformed into the time domain by an inverse discrete Fourier transform (IDFT), thereby obtaining a cyclic correlation result of the time domain signal, and then the UE is obtained.
  • IDFT inverse discrete Fourier transform
  • the IDFT-converted preamble signals transmitted by the antennas are combined, and finally the peaks of the combined signals are compared with the peaks in the detection window to estimate the uplink timing advance (English: Taming Advancing, referred to as TA) and fed back to The UE enables the UE to adjust the transmission time of the uplink signal based on the TA to implement uplink synchronization.
  • TA Taming Advancing
  • the Preamble sequence is composed of ZC sequences in the LTE system, the ZC sequence has good autocorrelation and low cross-correlation. Therefore, the Preamble sequence can exhibit obvious peaks in the detection window after being transformed by FFT and IDFT. The accuracy of the TA is estimated to be higher based on the peak values presented within the detection window.
  • the Preamble sequence is composed of 4 symbol groups, and each symbol group includes 1 CP and 5 OFDM symbols. Since the signals transmitted on the 5 OFDM symbols in each symbol group are the same, the base station displays the Preamble sequence through the FFT and the IDFT and the like, and the peaks appearing in the detection window are not obvious, so that the peak value is determined according to the peak presented in the detection window. The accuracy of the uplink synchronization timing deviation is low, thereby reducing the accuracy of the uplink synchronization.
  • the embodiment of the invention provides a method and a device for determining an uplink synchronization timing offset, which are used to solve the problem that the base station in the NB-IoT system existing in the prior art determines the uplink synchronization timing deviation by performing the FFT and IDFT transformation processing on the Preamble sequence. Less sexual problems.
  • an embodiment of the present invention provides a method for determining an uplink synchronization timing offset, including:
  • the base station performs conjugate multiplication on the channel estimation value corresponding to each symbol group to obtain a first radian value based on the hopping pattern used by the preamble signal, and determines the terminal device based on the first radians value. Uplink synchronization timing deviation.
  • the base station receives the preamble preamble signal sent by the terminal device, and then determines the channel estimation value of the frequency domain channel occupied by each symbol group in the preamble signal, and then uses the preamble signal based on the preamble signal.
  • a frequency hopping pattern conjugate multiplied by a channel estimation value corresponding to each symbol group to obtain a first radians value, and determining an uplink synchronization timing deviation of the terminal device based on the first radians value, due to a phase difference of the preamble signal Because of the uplink synchronization timing deviation, the phase difference of the preamble signal can accurately reflect the uplink synchronization timing deviation of the terminal device.
  • the base station performs the FFT and IDFT conversion processing on the preamble sequence.
  • the first radian value is obtained by multiplying the channel estimation values corresponding to each symbol group in the preamble signal, and the phase difference of the preamble signal is determined according to the first radian value, thereby determining the uplink synchronization timing. The accuracy of the deviation.
  • the base station performs conjugate multiplication on a channel estimation value corresponding to each symbol group based on a frequency hopping pattern used by the preamble signal.
  • the first radians value including:
  • the base station performs conjugate multiplication on channel estimation values of any two hopping intervals of the M subcarriers of the preamble signal to obtain at least two results based on the hopping pattern, and obtain at least two results.
  • the result of multiplication of the conjugates is summed to obtain a first radian value, wherein the M is a positive integer.
  • the base station performs conjugate multiplication on a channel estimation value corresponding to each symbol group based on a frequency hopping pattern used by the preamble signal.
  • the first radians value including:
  • the base station performs conjugate multiplication of channel estimation values of any two hopping intervals of the symbol groups of the N subcarriers in the preamble signal to obtain at least two results based on the hopping pattern, and obtain at least two results.
  • the result of multiplication of the conjugates is summed to obtain a second radian value, wherein the N is a positive integer;
  • the base station performs conjugate multiplication on channel estimation values of any two hopping intervals of the sub-carriers of the H sub-carriers based on the hopping pattern to obtain at least two results, and obtain at least two
  • the result of multiplication of conjugates is summed to obtain a third radians value, wherein H is a positive integer, where N is less than H;
  • the base station sums the second radian value and the third radian value to obtain the first radian value.
  • the base station may perform conjugate multiplication on channel estimation values of any two symbol groups in the preamble signal according to the hopping pattern to obtain at least two results, and obtain at least two conjugates. Multiplying the result and obtaining the first radian value; or,
  • the base station may also perform conjugate multiplication on channel estimation values of two pre-selected symbol groups in the preamble signal based on the hopping pattern, and use the obtained conjugate multiplied result as the first radians value.
  • the base station may also obtain the first radians value by other means, which is not specifically limited herein.
  • the uplink synchronization timing offset meets the following formula requirements:
  • TA represents the uplink synchronization timing deviation
  • ⁇ s1 represents an angle value obtained by converting the second radians value
  • ⁇ l1 represents an angle value obtained by converting the third radians value
  • N FFT is the preamble signal The number of points of the Fourier transform FFT is performed.
  • the method further includes:
  • the base station performs phase compensation on the angle value obtained by converting the third radians value, and the angle value obtained by the phase-compensated third radians value is converted according to the following formula:
  • ⁇ l2 angle(R l e -j6 ⁇ s2 );
  • ⁇ l2 represents an angle value obtained by converting the third radians after phase compensation
  • R l represents the third radians
  • ⁇ s2 represents an angle obtained by converting the second radians.
  • the receiving, by the base station, the preamble preamble signal sent by the terminal device includes:
  • the method further includes: after the base station performs conjugate multiplication to obtain a first radians value, based on the hopping pattern used by the base station to transmit the preamble signal.
  • the base station receives the sending by the terminal device
  • the preamble preamble signal includes:
  • the method further includes:
  • the base station determines a second average of the first radian values of the preamble signal transmitted through the plurality of antennas, and determines an uplink synchronization timing offset of the terminal device based on the second average value.
  • an apparatus for determining an uplink synchronization timing offset including:
  • a receiving module configured to receive a preamble preamble signal sent by the terminal device
  • a determining module configured to determine a channel estimation value of a frequency domain channel occupied by each of the preamble signals received by the receiving module; and a hopping pattern used for transmitting the preamble signal, for each symbol
  • the corresponding channel estimation value is conjugate multiplied to obtain a first radians value, and the uplink synchronization timing deviation of the terminal device is determined based on the first radians value.
  • the determining module is configured to conjugate a channel estimation value corresponding to each symbol group based on a frequency hopping pattern that is used to send the preamble signal When multiplying to get the first radians value, it is specifically used to:
  • the determining module is configured to conjugate a channel estimation value corresponding to each symbol group based on a frequency hopping pattern that is used to send the preamble signal When multiplying to get the first radians value, it is specifically used to:
  • the uplink synchronization timing offset meets the following formula requirements:
  • TA represents the uplink synchronization timing deviation
  • ⁇ s1 represents an angle value obtained by converting the second radians value
  • ⁇ l1 represents an angle value obtained by converting the third radians value
  • N FFT is the preamble signal The number of points of the Fourier transform FFT is performed.
  • the device further includes:
  • phase compensation module configured to perform, after the determining module determines an uplink synchronization timing deviation of the terminal device based on the first radiance value, an angle value obtained by converting the third radians value determined by the determining module
  • the phase compensation, the angle value obtained by the phase-compensated third radians value after conversion is in accordance with the following formula:
  • ⁇ l2 angle(R l e -j6 ⁇ s2 );
  • ⁇ l2 represents an angle value obtained by converting the third radians after phase compensation
  • R l represents the third radians
  • ⁇ s2 represents an angle obtained by converting the second radians.
  • the receiving module is specifically configured to:
  • the determining module is further configured to:
  • the receiving module is specific Used for:
  • the determining module is further configured to:
  • Determining by using a hopping pattern that is sent by the preamble signal, conjugate multiplication of channel estimation values corresponding to each symbol group to obtain a first radians value, and determining the number of the preamble signals transmitted through the plurality of antennas a second average value of a radian value, and determining an uplink synchronization timing offset of the terminal device based on the second average value.
  • the base station receives the preamble preamble signal sent by the terminal device, and then determines the channel estimation value of the frequency domain channel occupied by each symbol group in the preamble signal, and then uses the preamble signal based on the preamble signal.
  • a frequency hopping pattern conjugate multiplied by a channel estimation value corresponding to each symbol group to obtain a first radians value, and determining an uplink synchronization timing deviation of the terminal device based on the first radians value, due to a phase difference of the preamble signal Because of the uplink synchronization timing deviation, the phase difference of the preamble signal can reflect the uplink synchronization timing deviation of the terminal device.
  • the method for performing the FFT and IDFT conversion processing on the preamble sequence by the base station is implemented by the present invention.
  • the first radians value is obtained by conjugate multiplying the channel estimation values corresponding to each symbol group in the preamble signal, and the phase difference of the preamble signal is determined according to the first radians value, thereby improving the accuracy of determining the uplink synchronization timing deviation. Sex.
  • FIG. 1 is a schematic diagram of uplink synchronization of a terminal device according to an embodiment of the present invention
  • FIG. 2 is a schematic diagram of a frequency hopping pattern according to an embodiment of the present invention.
  • FIG. 3 is a flowchart of a method for determining an uplink synchronization timing offset according to an embodiment of the present invention
  • FIG. 4 is a flowchart of a method for determining an uplink synchronization timing offset according to an embodiment of the present invention
  • FIG. 5 is a flowchart of a method for determining an uplink synchronization timing offset according to an embodiment of the present invention
  • FIG. 6 is a flowchart of a method for determining an uplink synchronization timing offset according to an embodiment of the present invention
  • FIG. 7 is a schematic structural diagram of an apparatus for determining an uplink synchronization timing deviation according to an embodiment of the present invention.
  • FIG. 8 is a schematic structural diagram of a base station device according to an embodiment of the present invention.
  • the Narrow Band Internet of Things (NB-IoT) system is a terminal device (English: User Equipment, UE for short).
  • the distance between the base stations is uncertain.
  • the UE needs to establish uplink synchronization with the base station through the random access procedure.
  • the base station detects that the UE sends the preamble preamble signal, estimates the uplink synchronization timing deviation through the received preamble signal, and obtains the uplink synchronization timing deviation.
  • the inbound response sends an uplink synchronization timing offset to the UE.
  • the UE calculates the timing advance and adjusts the transmission time of the uplink signal, thereby implementing uplink synchronization, as shown in FIG.
  • the Preamble sequence is generated by cyclic shifting of ZC sequences, which are derived from a ZC root sequence.
  • the base station After receiving the preamble signal sent by the UE, the base station determines the uplink synchronization timing deviation by the following process:
  • the base station removes the cyclic prefix (English: Cyclic Prefix, CP for short) portion of the Preamble signal according to the Preamble format type of the received preamble signal, and reserves the Preamble sequence portion.
  • cyclic prefix English: Cyclic Prefix, CP for short
  • the base station performs spectrum shifting on the Preamble sequence, Cascade Integrator Comb (CIC) downsampling, and Fast Fourier Transformation (FFT).
  • the Preamble sequence is transformed from the time domain to the frequency domain, and subcarrier demapping is performed on the Preamble sequence transformed into the frequency domain.
  • the base station processes the Preamble sequence that has been demapped by the subcarrier through frequency domain automatic gain control (English: Automatic Gain Control, AGC) to ensure that the amplitude of the Preamble sequence after subcarrier demapping remains within a preset interval. .
  • frequency domain automatic gain control English: Automatic Gain Control, AGC
  • the base station multiplies the ZC root sequence by the frequency domain AGC-processed Preamble sequence.
  • the base station performs inverse discrete Fourier transform (English: Inverse Discrete Fourier Transform, IDFT) on the frequency domain multiplied Preamble sequence, so that the Preamble sequence is transformed from the frequency domain correlation result to the time domain, thereby obtaining the time The cyclic correlation result of the domain signal.
  • inverse discrete Fourier transform English: Inverse Discrete Fourier Transform, IDFT
  • the base station performs the AGC recovery process on the Preamble signal transformed into the time domain, so that the amplitude of the Preamble sequence transformed into the time domain recovers the original amplitude when the base station arrives.
  • the base station combines the signal power of the Preamble signal sent by the UE through each antenna, that is, merges the Preamble sequence that the UE sends back to the original amplitude through each antenna.
  • the base station estimates the signal power and the noise power of the physical random access channel (English: Physical Random Access Channel, PRACH); and determines whether there is a Preamble signal by combining the signal power and the signal power of the PRACH and the noise power.
  • Access if there is Preamble signal access, estimate the uplink timing advance according to the maximum path or the position of the first path in the detection window.
  • the maximum diameter represents the peak of the combined signal power amplitude
  • the first diameter represents the peak of the combined signal power being greater than the preset threshold.
  • the base station is configured with one or more Narrowband Physical Random Access Channels (NPRs), each NPRACH is composed of 12 subcarriers, and the preamble signal sent by each UE is in one.
  • the frequency hopping of the 12 subcarriers of NPRACH is transmitted.
  • the Preamble signal is composed of 4 symbol groups, each of which includes 1 CP and 5 OFDM symbols, and the signals transmitted on the 5 OFDM symbols are the same, and both can be 1, so that multiple PRACHs can be configured in the frequency domain.
  • Different Preamble signals are orthogonal between each other.
  • Tcp represents the length of the CP in the preamble signal
  • Tseq represents the length of the preamble sequence in the preamble signal
  • Total represents the total length of the preamble signal.
  • Each symbol group is transmitted with only one subcarrier and is transmitted according to a preset hopping pattern.
  • a preset hopping pattern two levels of hopping intervals are arranged between symbol groups in the hopping pattern, between symbol group 1 and symbol group 2, symbol group 3 and symbol group 4
  • the hopping direction of the symbol group 1 and the symbol group 2 is opposite to the hopping direction of the symbol group 3 and the symbol group 4, and the hopping direction of the symbol group 1 and the symbol group 4 is the same as the hopping direction of the symbol group 2 and the symbol group 3.
  • the preamble signal is sent for a long time and can be sent multiple times.
  • the 3GPP standard defines that the preamble signal can be repeatedly sent [1, 2, 4, 8, 16, 32, 64, 128], and the base station can select one of them. The number of 3 types of repeated transmissions is configured.
  • the preamble signal that is repeatedly sent is continually transmitted in time and hopped in the frequency domain.
  • the hopping mode can use the LTE physical uplink shared channel (English: Physical Uplink Shared Channel, PUSCH) type 2 frequency hopping mode. After the preamble is sent 64 times, it needs to add a guard interval of 40ms (English: guard period, GP for short).
  • the preamble signal selects different initial subcarrier transmissions by means of frequency hopping at different times to obtain anti-interference and frequency domain diversity combining and gain.
  • Different starting subcarriers correspond to different hopping paths, and one subcarrier can only carry one user's preamble signal at a certain time.
  • the Preamble signal in the LTE system is a ZC sequence
  • the ZC sequences have good autocorrelation and good mutual irrelevance. Therefore, after the Preamble signal in the LTE system is transformed by the FFT and the IDFT, the base station can distinguish the multipath, so that the signal power of the Preamble signal transmitted by the UE through each antenna can be combined, and then the uplink synchronization timing offset is determined according to the combined signal power.
  • the Preamble sequence in the NB-IoT system consists of 4 symbol groups. Each symbol group includes 1 CP and 5 OFDM symbols, and the signals transmitted on the 5 OFDM symbols are the same.
  • Multipath refers to the propagation phenomenon of a Preamble signal sent by a terminal device to a base station through multiple antennas.
  • the terminal since the preamble signal in the NB-IoT system lasts for a long time in time, that is, the time for transmitting a symbol group is long, and the interval between adjacent groups of symbol groups is long, so that the frequency of the downlink synchronization of the terminal device cannot be performed.
  • the terminal may have a large residual frequency offset after downlink synchronization, and the residual frequency offset will cause an additional phase difference, thereby affecting the accuracy of determining the uplink synchronization timing deviation. For example, a group of symbols lasts for 1.6ms, and the residual frequency offset of 50Hz will bring a phase difference of 0.16 ⁇ .
  • the method of determining the uplink synchronization timing offset by performing the FFT and IDFT conversion processing on the preamble signal cannot process the residual frequency offset, thereby causing the accuracy of the determined uplink synchronization timing offset to be low.
  • an embodiment of the present invention provides a method and apparatus for determining an uplink synchronization timing offset, which is used to solve the problem that the base station determines the uplink synchronization timing by performing FFT and IDFT conversion processing on the NB-IoT system existing in the prior art.
  • the method and the device are based on the same inventive concept. Since the principles of the method and the device for solving the problem are similar, the implementation of the device and the method can be referred to each other, and the repeated description is not repeated.
  • a flowchart of a method for determining an uplink synchronization timing offset may specifically include the following:
  • the base station receives a preamble preamble signal sent by the terminal device.
  • the base station determines, to send a channel estimation value of a frequency domain channel occupied by each symbol group in the preamble signal.
  • the base station performs conjugate multiplication on a channel estimation value corresponding to each symbol group according to a hopping pattern used by the preamble signal to obtain a first radians value, and determines the terminal based on the first radians value. Uplink synchronization timing deviation of the device.
  • the base station receives the preamble preamble signal sent by the terminal device, and then determines the channel estimation value of the frequency domain channel occupied by each symbol group in the preamble signal, and then uses the preamble signal based on the preamble signal.
  • a frequency hopping pattern conjugate multiplied by a channel estimation value corresponding to each symbol group to obtain a first radians value, and determining an uplink synchronization timing deviation of the terminal device based on the first radians value, due to a phase difference of the preamble signal Because of the uplink synchronization timing deviation, the phase difference of the preamble signal can reflect the uplink synchronization timing deviation of the terminal device.
  • the method for performing the FFT and IDFT conversion processing on the preamble sequence by the base station is implemented by the present invention.
  • the first radians value is obtained by conjugate multiplying the channel estimation values corresponding to each symbol group in the preamble signal, and the phase difference of the preamble signal is determined according to the first radians value, thereby improving the accuracy of determining the uplink synchronization timing deviation. Sex.
  • the base station performs conjugate multiplication on the channel estimation value corresponding to each symbol group according to the hopping pattern used by the preamble signal to obtain the first radians value, which can be implemented by using either of the following two methods: :
  • Manner 1 The base station performs conjugate multiplication of channel estimation values of any two hopping intervals of the M subcarriers in the preamble signal according to the hopping pattern to obtain at least two results, and obtains The result of multiplying at least two conjugates is summed to obtain a first radians value, wherein said M is a positive integer.
  • Manner 2 A1
  • the base station conjugates channel estimation values of any two hopping intervals of N subcarriers in the preamble signal according to the hopping pattern to obtain at least two results, and obtains at least two results, and The result of multiplying the obtained at least two conjugates is summed to obtain a second radian value, wherein the N is a positive integer.
  • the base station performs conjugate multiplication of channel estimation values of any two hopping intervals of the sub-carriers of the H sub-carriers according to the hopping pattern to obtain at least two results, and obtains the obtained
  • the result of multiplying at least two conjugates is summed to obtain a third radians value, wherein H is a positive integer, where N is less than H.
  • the base station sums the second radian value and the third radian value to obtain the first radian value.
  • the base station may perform conjugate multiplication on channel estimation values of any two symbol groups in the preamble signal according to the hopping pattern to obtain at least two results, and obtain at least two conjugates. Multiplying the result and obtaining the first radian value; or,
  • the base station may also perform conjugate multiplication on channel estimation values of two pre-selected symbol groups in the preamble signal based on the hopping pattern, and use the obtained conjugate multiplied result as the first radians value.
  • the base station may also obtain the first radians value by other means, which is not specifically limited herein.
  • the hopping pattern used by the preamble signal is a hopping pattern shown in FIG. 2, and the preamble signal includes a symbol group 1, a symbol group 2,
  • the symbol group 3 and the symbol group 4 are taken as an example, and the process of determining the uplink synchronization timing deviation after the base station receives the preamble preamble signal sent by the terminal device is described in detail.
  • Scenario 1 The base station performs conjugate multiplication on the channel estimation values corresponding to each symbol group according to the hopping pattern shown in FIG. 2 to obtain the first radians value by using mode 1, and M is equal to 1.
  • the process for determining, by the base station, the uplink synchronization timing offset includes:
  • the base station removes the CP portion of the Preamble signal according to the Preamble format type of the received preamble signal.
  • the base station removes the preamble signal of the CP part to perform a 1/2 subcarrier, that is, a 1.875 kHz frequency shift.
  • the base station avoids the influence of the DC component by performing a 1/2 subcarrier frequency shift on the preamble signal from which the CP portion is removed.
  • the base station performs FFT transformation on the preamble signal of the 1/2 subcarrier frequency offset to obtain a frequency domain sequence, and then determines a center frequency of the channel where each OFDM symbol is located according to the hopping pattern shown in FIG. 2, and performs a preamble signal.
  • the frequency domain sequence extracts frequency domain data corresponding to the center frequency of the channel where each OFDM symbol is located.
  • the base station performs frequency domain AGC processing on the frequency domain data corresponding to each OFDM symbol to ensure that the amplitude of the frequency domain data corresponding to each OFDM symbol is maintained within a preset interval.
  • the base station determines an average value of frequency domain data corresponding to 5 OFDM symbols processed by the frequency domain AGC in each symbol group as a channel estimation value of a frequency domain channel occupied by each symbol group, and
  • the channel estimation values of the symbol group 1 and the symbol group 2 of the preamble signal with the hopping interval of 1 subcarrier are conjugate multiplied, and the channel estimation values of the symbol group 3 and the symbol group 4 with the hopping interval of 1 subcarrier are shared.
  • the yoke is multiplied and the result of multiplying the two conjugates is summed to obtain a first radians value, wherein the first radians value meets the following formula requirements:
  • R s y 1 * y 2 +y 3 y 4 * ;
  • R s represents a first radians value
  • y 1 represents a channel estimation value of symbol group 1
  • y 2 represents a channel estimation value of symbol group 2
  • y 3 represents a channel estimation value of symbol group 3
  • y 4 represents a channel estimation of symbol group 4; value.
  • the process of performing coarse synchronization by the base station may be implemented as follows:
  • the base station determines a first radians value corresponding to each of the preamble signals.
  • the symbol group 1 of each of the preamble signals may be hopped to the symbol group 2 by a positive hop, that is, a frequency domain channel occupied by the symbol group 2
  • the center frequency of the frequency domain channel occupied by the symbol group 1 is greater than the center frequency of the frequency domain channel occupied by the symbol group 1; or the center frequency of the frequency domain channel occupied by the symbol group 2 is smaller than the center frequency of the frequency domain channel occupied by the symbol group 1 .
  • the first radians of the plurality of preamble signals are corrected in the embodiment of the present invention.
  • the base station may correct the symbol group 1 by using a positive hop frequency hopping to a first radians value of the preamble signal of the symbol group 2, and the corrected first radians value conforms to the following formula:
  • R s (y 1 * y 2 + y 3 y 4 * ) * .
  • the base station may also perform the correction by using the negative hop frequency hopping to the first radians of the preamble signal of the symbol group 2, which is not limited herein.
  • the base station determines a radian average value of the first radian values of the plurality of preamble signals, where the radian average value meets the following formula:
  • N rep indicates the number of times the terminal device repeats the transmission.
  • the base station converts the average value of the arc into a first angle value, and the first angle value meets the following formula:
  • ⁇ s represents the first angle value
  • step S406 is performed.
  • the base station determines, for each of the preamble signals, a first angle value corresponding to each of the preamble signals, and then determines a plurality of a first angular average of the first angular value of the preamble signal, the first angular average conforming to the following formula:
  • N aR represents the number of antennas through which the terminal device transmits the preamble signal. Represents the first angle value of the preamble signal transmitted through the jth antenna.
  • the base station determines the uplink synchronization timing deviation based on the first angle average value, and the uplink synchronization timing deviation meets the following formula requirements:
  • TA represents the uplink synchronization timing offset
  • N FFT is a number of points of the Fourier transform FFT of the preamble signal.
  • Scenario 2 The base station performs conjugate multiplication on the channel estimation value corresponding to each symbol group according to the hopping pattern shown in FIG. 2 to obtain the first radians value by using mode 1, and M is equal to 6.
  • the process for determining, by the base station, the uplink synchronization timing offset includes:
  • step S501 to S504 refer to step S401 to step S404 shown in FIG. 4, and details of the embodiments of the present invention are not repeated herein.
  • the base station determines an average value of frequency domain data corresponding to five OFDM symbols processed by the frequency domain AGC in each symbol group as a channel estimation value of a frequency domain channel occupied by each symbol group, and
  • the channel estimation values of the symbol group 1 and the symbol group 4 of the preamble signal with the hopping interval of 6 subcarriers are conjugate multiplied, and the channel estimation values of the symbol group 2 and the symbol group 3 with the hopping interval of 6 subcarriers are common.
  • the yoke is multiplied, and the result of multiplying the two conjugates is summed to obtain a second radians value, wherein the second radians value meets the following formula requirements:
  • R l y 1 * y 4 e j ⁇ + y 3 y 2 * e j3 ⁇ ;
  • R l represents a second radians value
  • y 1 represents a channel estimation value of symbol group 1
  • y 2 represents a channel estimation value of symbol group 2
  • y 3 represents a channel estimation value of symbol group 3
  • y 4 represents a channel estimation of symbol group 4
  • Value ⁇ meets the following formula requirements:
  • ⁇ f represents the residual frequency offset value of the terminal device
  • T represents the length of time during which a symbol group is transmitted.
  • the process of performing fine timing synchronization by the base station may be implemented as follows:
  • the base station determines a second radian value corresponding to each of the preamble signals.
  • the symbol group 2 of each of the preamble signals may be hopped to the symbol group 3 by a positive hop, that is, a frequency domain channel occupied by the symbol group 2
  • the center frequency of the frequency domain channel occupied by the symbol group 3 is smaller than the center frequency of the frequency domain channel occupied by the symbol group 3; that is, the center frequency of the frequency domain channel occupied by the symbol group 2 is greater than the center frequency of the frequency domain channel occupied by the symbol group 3.
  • the second radians of the plurality of preamble signals are corrected.
  • the base station corrects the symbol group 2 by the positive hop frequency hopping to the second radians value of the preamble signal of the symbol group 3, and the corrected second radians value conforms to the following formula:
  • R l (y 1 * y 4 e j ⁇ + y 3 y 2 * e j3 ⁇ ) * .
  • the base station may also perform the correction by using the negative hop frequency hopping to the second radians of the preamble signal of the symbol group 3.
  • the embodiment of the present invention is not limited herein.
  • the base station determines a radian average value of the second radian values of the plurality of preamble signals, where the radian average value meets the following formula:
  • N rep indicates the number of times the terminal device repeats the transmission.
  • the base station converts the average value of the arc into a second angle value, and the second angle value meets the following formula:
  • ⁇ l represents a second angle value
  • step S506 is performed.
  • the base station determines, for each of the preamble signals, a second angle value corresponding to each of the preamble signals, and then determines a plurality of a second angular average of the second angle value of the preamble signal, the second angle average conforming to the following formula:
  • N aR represents the number of antennas through which the terminal device transmits the preamble signal.
  • the base station determines an uplink synchronization timing offset based on the second angle average value, and the uplink synchronization timing offset meets the following formula:
  • TA represents the uplink synchronization timing offset
  • N FFT is a number of points of the Fourier transform FFT of the preamble signal.
  • Scenario 3 The base station performs conjugate multiplication on the channel estimation value corresponding to each symbol group according to the hopping pattern shown in FIG. 2 to obtain the first radians value by using mode 2, and N is equal to 6, and H is equal to 6.
  • the process for determining, by the base station, the uplink synchronization timing offset includes:
  • step S601 to S604 refer to step S401 to step S404 shown in FIG. 4, and details of the embodiments of the present invention are not repeated herein.
  • the base station determines a channel estimation value of a frequency domain channel occupied by each symbol group in the preamble signal, and determines a first angle value ⁇ s based on the frequency hopping pattern shown in FIG. 2 .
  • the first angle value ⁇ s is determined based on the hopping pattern shown in FIG. 2 , and reference may be made to step S405 shown in FIG. 4 , and the embodiments of the present invention are not repeated here.
  • the base station determines a channel estimation value of a frequency domain channel occupied by each symbol group in the preamble signal, and determines a second angle value ⁇ l based on the frequency hopping pattern shown in FIG. 2 .
  • the second angle value ⁇ l is determined based on the hopping pattern shown in FIG. 2 , and reference may be made to step S505 shown in FIG. 5 , and the embodiments of the present invention are not repeated herein.
  • the steps S605 and S606 are not strictly defined.
  • the S606 may be executed after the S605 is executed, or the S606 may be executed after the S606 is executed, and the S605 and the S606 may be executed at the same time.
  • the embodiment of the present invention is not limited herein.
  • step S607 is performed.
  • the base station performs phase compensation on the second angle value ⁇ l based on the first angle value ⁇ s , and the ⁇ l after the phase compensation meets the following formula requirements:
  • ⁇ l1 angle(R l e -j6 ⁇ s );
  • ⁇ l1 represents ⁇ l after phase compensation
  • R l represents the second radians value
  • the base station mainly considers the following factors when performing phase compensation on the second angle value ⁇ l :
  • the terminal residual frequency offset value determined by the base station is less than the second threshold.
  • the uplink signal to noise ratio detected by the base station is lower than the third threshold.
  • the base station does not phase compensate the second angle value ⁇ l .
  • step S608 is performed.
  • the base station determines a first angle average value. And a second angle average
  • the base station determines the uplink synchronization timing deviation based on the average value of the angle, and the uplink synchronization timing deviation meets the following formula requirements:
  • TA represents the uplink synchronization timing offset
  • N FFT is a number of points of the Fourier transform FFT of the preamble signal.
  • the base station receives the preamble preamble signal sent by the terminal device, and then determines the channel estimation value of the frequency domain channel occupied by each symbol group in the preamble signal, and then uses the preamble signal based on the preamble signal.
  • a frequency hopping pattern conjugate multiplied by a channel estimation value corresponding to each symbol group to obtain a first radians value, and determining an uplink synchronization timing deviation of the terminal device based on the first radians value, due to a phase difference of the preamble signal Because of the uplink synchronization timing deviation, the phase difference of the preamble signal can reflect the uplink synchronization timing deviation of the terminal device.
  • the method for performing the FFT and IDFT conversion processing on the preamble sequence by the base station is implemented by the present invention.
  • the first radians value is obtained by conjugate multiplying the channel estimation values corresponding to each symbol group in the preamble signal, and the phase difference of the preamble signal is determined according to the first radians value, thereby improving the accuracy of determining the uplink synchronization timing deviation. Sex.
  • an embodiment of the present invention provides an apparatus 70 for determining an uplink synchronization timing offset, which may be applied to a base station apparatus.
  • the structure of the device 70 is as shown in FIG. 7, and includes a receiving module 71 and a determining module 72, wherein:
  • the receiving module 71 is configured to receive a preamble preamble signal sent by the terminal device.
  • a determining module 72 configured to determine a channel estimation value of a frequency domain channel occupied by each of the preamble signals received by the receiving module 71; and a frequency hopping pattern adopted by transmitting the preamble signal, for each
  • the channel estimation values corresponding to the symbol groups are conjugate multiplied to obtain a first radians value, and the uplink synchronization timing deviation of the terminal device is determined based on the first radians value.
  • the determining module 72 performs conjugate multiplication on a channel estimation value corresponding to each symbol group based on a hopping pattern used to transmit the preamble signal to obtain a first radians value. Specifically used for:
  • the determining module 72 performs conjugate multiplication on a channel estimation value corresponding to each symbol group based on a hopping pattern used to transmit the preamble signal to obtain a first radians value. Specifically for:
  • D1 based on the hopping pattern, conjugate multi-multiply channel estimation values of any two hopping intervals of the symbol group of the N subcarriers to obtain at least two results, and obtain at least two The result of the conjugate multiplication is summed to obtain a second radian value, wherein the N is a positive integer.
  • the uplink synchronization timing deviation meets the following formula requirements:
  • TA represents the uplink synchronization timing deviation
  • ⁇ s1 represents an angle value obtained by converting the second radians value
  • ⁇ l1 represents an angle value obtained by converting the third radians value
  • N FFT is the preamble signal The number of points of the Fourier transform FFT is performed.
  • the device further includes a phase compensation module 73, configured to determine, by the determining module 72, before the determining module 72 determines an uplink synchronization timing deviation of the terminal device based on the first radian value.
  • the angle value obtained by converting the third radians value is phase-compensated, and the angle value obtained by the phase-compensated third radians value is converted according to the following formula:
  • ⁇ l2 angle(R l e -j6 ⁇ s2 );
  • ⁇ l2 represents an angle value obtained by converting the third radians after phase compensation
  • R l represents the third radians
  • ⁇ s2 represents an angle obtained by converting the second radians.
  • the receiving module 71 is specifically configured to: receive, by the terminal device, a plurality of the preamble signals repeatedly sent by the terminal device;
  • the determining module 72 is further configured to: after conjugate multiplying the channel estimation values corresponding to each symbol group to obtain a first radians value based on the hopping pattern used to send the preamble signal, determine the repeated transmission Determining a first average of the first radian values of the plurality of preamble signals, and determining an uplink synchronization timing offset of the terminal device based on the first average value.
  • the receiving module 71 is specifically configured to: receive the preamble signal sent by the terminal device by using multiple antennas;
  • the determining module 72 is further configured to: after conjugate multiplying the channel estimation values corresponding to each symbol group by the hopping pattern used to send the preamble signal to obtain a first radians value, determining to pass multiple antennas And transmitting a second average of the first radian values of the preamble signal, and determining an uplink synchronization timing offset of the terminal device based on the second average value.
  • the base station receives the preamble preamble signal sent by the terminal device, and then determines the channel estimation value of the frequency domain channel occupied by each symbol group in the preamble signal, and then uses the preamble signal based on the preamble signal.
  • a frequency hopping pattern conjugate multiplied by a channel estimation value corresponding to each symbol group to obtain a first radians value, and determining an uplink synchronization timing deviation of the terminal device based on the first radians value, due to a phase difference of the preamble signal Because of the uplink synchronization timing deviation, the phase difference of the preamble signal can reflect the uplink synchronization timing deviation of the terminal device.
  • the method for performing the FFT and IDFT conversion processing on the preamble sequence by the base station is implemented by the present invention.
  • the first radians value is obtained by conjugate multiplying the channel estimation values corresponding to each symbol group in the preamble signal, and the phase difference of the preamble signal is determined according to the first radians value, thereby improving the accuracy of determining the uplink synchronization timing deviation. Sex.
  • an embodiment of the present invention further provides a base station device.
  • the structure of the base station device is as shown in FIG. 8, and includes a processor 801, a memory 802, and a transceiver 803, where:
  • the processor 801 is configured to read a program in the memory 802 and perform the following process:
  • the information is received and transmitted by the transceiver 803, and the method described in the embodiment corresponding to FIG. 3 described above is executed.
  • the transceiver 803 is configured to receive and transmit information under the control of the processor 801.
  • the memory 802 is configured to store a software program.
  • bus 800 may include any number of interconnected buses and bridges, and bus 800 will include one or more processors represented by processor 801 and memory represented by memory 802. The various circuits are linked together.
  • the bus 800 can also link various other circuits, such as peripherals, voltage regulators, and power management circuits, as is known in the art, and therefore, will not be further described herein.
  • Bus interface 804 provides an interface between bus 800 and transceiver 803.
  • Transceiver 803 can be an element or a plurality of elements, such as multiple receivers and transmitters, providing means for communicating with various other devices on a transmission medium.
  • the processor 801 is responsible for managing the bus 800 and the usual processing, and can also provide various functions including timing, peripheral interfaces, voltage regulation, power management, and other control functions.
  • the memory 802 can be used to store data used by the processor 801 when performing operations.
  • the processor 801 can be a central processing unit (English: Central Processing Unit, CPU for short), an application specific integrated circuit (ASIC), and a field programmable gate array (English: Field) -Programmable Gate Array, referred to as: FPGA) or complex programmable logic device (English: Complex Programmable Logic Device, referred to as: CPLD), digital signal processor (English: Digital Signal Processing, referred to as: DSP) and so on.
  • CPU Central Processing Unit
  • ASIC application specific integrated circuit
  • FPGA field programmable gate array
  • FPGA Field -Programmable Gate Array
  • CPLD Complex Programmable Logic Device
  • DSP Digital Signal Processing
  • embodiments of the present invention can be provided as a method, system, or computer program product. Accordingly, the present invention may take the form of an entirely hardware embodiment, an entirely software embodiment, or a combination of software and hardware. Moreover, the invention can take the form of a computer program product embodied on one or more computer-usable storage media (including but not limited to disk storage, CD-ROM, optical storage, etc.) including computer usable program code.
  • computer-usable storage media including but not limited to disk storage, CD-ROM, optical storage, etc.
  • the computer program instructions can also be stored in a computer readable memory that can direct a computer or other programmable data processing device to operate in a particular manner, such that the instructions stored in the computer readable memory produce an article of manufacture comprising the instruction device.
  • the apparatus implements the functions specified in one or more blocks of a flow or a flow and/or block diagram of the flowchart.
  • These computer program instructions can also be loaded onto a computer or other programmable data processing device such that a series of operational steps are performed on a computer or other programmable device to produce computer-implemented processing for execution on a computer or other programmable device.
  • the instructions provide steps for implementing the functions specified in one or more of the flow or in a block or blocks of a flow diagram.

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Abstract

本发明公开了一种确定上行同步定时偏差的方法及装置，用以解决现有技术中存在的NB-IoT系统中基站通过将Preamble序列经过FFT以及IDFT等变换处理确定上行同步定时偏差时准确性较低的问题。所述方法具体包括：基站接收终端设备发送的前导码preamble信号；确定发送所述preamble信号中的每个符号组所占用的频域信道的信道估计值；基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，并基于所述第一弧度值确定所述终端设备的上行同步定时偏差。

Description

一种确定上行同步定时偏差的方法及装置
本申请要求在2017年5月4日提交中国专利局、申请号为201710309229.7、发明名称为一种确定上行同步定时偏差的方法及装置的中国专利申请的优先权，其全部内容通过引用结合在本申请中。
技术领域
本发明涉及通信技术领域，特别涉及一种确定上行同步定时偏差的方法及装置。
背景技术
同长期演进(英文：Long Term Evolution，简称：LTE)系统相同，窄带物联网(英文：Narrow Band Internet of Things，简称：NB-IoT)系统由于终端设备(英文：User Equipment，简称：UE)和基站间的距离是不确定的，UE需要通过随机接入过程同基站建立上行同步，基站检测到UE发送了前导码preamble信号，通过接收到的preamble信号估计出上行同步定时偏差，并通过随机接入响应发送上行同步定时偏差给UE，UE接收到随机接入响应之后，计算定时提前量并调整上行信号的发送时间，从而实现了上行同步。
LTE系统中，Preamble序列是由ZC序列经过循环移位生成的，它们源自一个或多个ZC序列的根序列。LTE系统中采用的上行同步定时偏差计算方法为，基站将UE经过各路天线发送的preamble信号均经过如下处理，经过FFT变换，将Preamble信号由时域变换到频域，并进行子载波解映射处理。然后将经过子载波解映射处理后的preamble信号经过离散傅里叶反变换(英文：Inverse Discrete Fourier Transform，简称：IDFT)变换到时域，从而得到时域信号的循环相关结果，然后将该UE经过各路天线发送的、经过IDFT变换的preamble信号进行合并，最后将合并后的信号的峰值与检测窗内的峰值进行比较估计上行定时提前量(英文：Taming Advancing，简称：TA)并反馈给 UE，使得UE可以基于TA调整上行信号的发送时间，实现上行同步。
由于LTE系统中，Preamble序列由ZC序列构成，ZC序列具有良好的自相关性以及很低的互相关性，因此Preamble序列经过FFT以及IDFT等变换后在检测窗内能够呈现出明显的峰值，使得根据检测窗内呈现的峰值估计TA的准确性较高。而NB-IoT系统中，Preamble序列由4个符号组组成，每个符号组包括1个CP以及5个OFDM符号。由于每个符号组中的5个OFDM符号上发送的信号相同，因此基站将Preamble序列经过FFT以及IDFT等变换后在检测窗内呈现出的峰值不明显，使得根据检测窗内呈现的峰值确定的上行同步定时偏差准确性较低，从而降低了上行同步的准确性。
发明内容
本发明实施例提供一种确定上行同步定时偏差的方法及装置，用以解决现有技术中存在的NB-IoT系统中基站通过将Preamble序列经过FFT以及IDFT等变换处理确定上行同步定时偏差时准确性较低的问题。
第一方面，本发明实施例提供了一种确定上行同步定时偏差的方法，包括：
基站接收终端设备发送的前导码preamble信号；
所述基站确定发送所述preamble信号中的每个符号组所占用的频域信道的信道估计值；
所述基站基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，并基于所述第一弧度值确定所述终端设备的上行同步定时偏差。
本发明实施例中通过基站接收终端设备发送的前导码preamble信号，然后确定发送所述preamble信号中的每个符号组所占用的频域信道的信道估计值，之后基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，并基于所述第一弧度值确定所述终端设备的上行同步定时偏差，由于preamble信号的相位差由于上行同步定 时偏差造成的，因此preamble信号的相位差可以比较准确的反映终端设备的上行同步定时偏差，相比于现有技术中，采用基站将preamble序列进行FFT以及IDFT等变换处理的方法，本发明实施例中通过将preamble信号中每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，根据所述第一弧度值确定preamble信号的相位差，提高了确定上行同步定时偏差的准确性。
结合第一方面，在第一方面的第一种可能的实施方式中，所述基站基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，包括：
所述基站基于所述跳频图样，将所述preamble信号中任意两个跳频间隔为M个子载波的符号组的信道估计值进行共轭相乘得到至少两个结果，并将得到的至少两个共轭相乘的结果作和得到第一弧度值，其中，所述M为正整数。
结合第一方面，在第一方面的第二种可能的实施方式中，所述基站基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，包括：
所述基站基于所述跳频图样，将所述preamble信号中任意两个跳频间隔为N个子载波的符号组的信道估计值进行共轭相乘得到至少两个结果，并将得到的至少两个共轭相乘的结果作和得到第二弧度值，其中，所述N为正整数；
所述基站基于所述跳频图样，将所述preamble信号中任意两个跳频间隔为H个子载波的符号组的信道估计值进行共轭相乘得到至少两个结果，并将得到的至少两个共轭相乘的结果作和得到第三弧度值，其中，所述H为正整数，其中N小于H；
所述基站将所述第二弧度值以及所述第三弧度值作和得到所述第一弧度值。
可选的，所述基站可以基于所述跳频图样，将所述preamble信号中任意两个符号组的信道估计值进行共轭相乘得到至少两个结果，并将得到的至少 两个共轭相乘的结果作和得到第一弧度值；或者，
所述基站也可以基于所述跳频图样，将所述preamble信号中预先选择的两个符号组的信道估计值进行共轭相乘，并将得到的共轭相乘的结果作为第一弧度值；所述基站也可以通过其他方式得到第一弧度值，本发明实施例在这里不做具体限定。
结合第一方面的第二种可能的实施方式，在第一方面的第三种可能的实施方式中，所述上行同步定时偏差符合下述公式要求：
Figure PCTCN2018085328-appb-000001
其中，TA表示所述上行同步定时偏差；θ s1表示所述第二弧度值经过转换得到的角度值；θ l1表示所述第三弧度值经过转换得到的角度值；N FFT为所述preamble信号进行傅里叶变换FFT的点数。
结合第一方面的第二种可能的实施方式，在第一方面的第四种可能的实施方式中，在所述基站基于所述第一弧度值确定所述终端设备的上行同步定时偏差之前，所述方法还包括：
所述基站对所述第三弧度值经过转换得到的角度值进行相位补偿，经过相位补偿后的所述第三弧度值经过转换得到的角度值符合下述公式要求：
θ l2＝angle(R le -j6θs2)；
其中，θ l2表示经过相位补偿后的所述第三弧度值经过转换得到的角度值；R l表示所述第三弧度值；θ s2表示所述第二弧度值经过转换得到的角度值。
结合第一方面，在第一方面的第五种可能的实施方式中，基站接收终端设备发送的前导码preamble信号，包括：
所述基站接收所述终端设备重复发送的若干个所述preamble信号；
在所述基站基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值之后，所述方法还包括：
所述基站确定重复发送的所述若干个所述preamble信号的所述第一弧度值的第一平均值，并基于所述第一平均值确定所述终端设备的上行同步定时 偏差。
结合第一方面和第一方面的第一种可能的实施方式至第五种可能的实施方式中的任一种，在第一方面的第六种可能的实施方式中，基站接收终端设备发送的前导码preamble信号，包括：
所述基站接收所述终端设备通过多个天线发送的所述preamble信号；
所述基站在基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值之后，所述方法还包括：
所述基站确定通过多个天线发送的所述preamble信号的所述第一弧度值的第二平均值，并基于所述第二平均值确定所述终端设备的上行同步定时偏差。
第二方面，本发明实施例提供了一种确定上行同步定时偏差的装置，包括：
接收模块，用于接收终端设备发送的前导码preamble信号；
确定模块，用于确定发送所述接收模块接收的所述preamble信号中的每个符号组所占用的频域信道的信道估计值；基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，并基于所述第一弧度值确定所述终端设备的上行同步定时偏差。
结合第二方面，在第二方面的第一种可能的实施方式中，所述确定模块，在基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值时，具体用于：
基于所述跳频图样，将所述preamble信号中任意两个跳频间隔为M个子载波的符号组的信道估计值进行共轭相乘得到至少两个结果，并将得到的至少两个共轭相乘的结果作和得到第一弧度值，其中，所述M为正整数。
结合第二方面，在第二方面的第二种可能的实施方式中，所述确定模块，在基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值时，具体用于：
基于所述跳频图样，将所述preamble信号中任意两个跳频间隔为N个子 载波的符号组的信道估计值进行共轭相乘得到至少两个结果，并将得到的至少两个共轭相乘的结果作和得到第二弧度值，其中，所述N为正整数；
基于所述跳频图样，将所述preamble信号中任意两个跳频间隔为H个子载波的符号组的信道估计值进行共轭相乘得到至少两个结果，并将得到的至少两个共轭相乘的结果作和得到第三弧度值，其中，所述H为正整数，其中N小于H；
将所述第二弧度值以及所述第三弧度值作和得到所述第一弧度值。
结合第二方面的第二种可能的实施方式，在第二方面的第三种可能的实施方式中，所述上行同步定时偏差符合下述公式要求：
Figure PCTCN2018085328-appb-000002
其中，TA表示所述上行同步定时偏差；θ s1表示所述第二弧度值经过转换得到的角度值；θ l1表示所述第三弧度值经过转换得到的角度值；N FFT为所述preamble信号进行傅里叶变换FFT的点数。
结合第二方面的第二种可能的实施方式，在第二方面的第四种可能的实施方式中，所述装置还包括：
相位补偿模块，用于在所述确定模块基于所述第一弧度值确定所述终端设备的上行同步定时偏差之前，对所述确定模块确定的所述第三弧度值经过转换得到的角度值进行相位补偿，经过相位补偿后的所述第三弧度值经过转换得到的角度值符合下述公式要求：
θ l2＝angle(R le -j6θs2)；
其中，θ l2表示经过相位补偿后的所述第三弧度值经过转换得到的角度值；R l表示所述第三弧度值；θ s2表示所述第二弧度值经过转换得到的角度值。
结合第二方面，在第二方面的第五种可能的实施方式中，所述接收模块，具体用于：
接收所述终端设备重复发送的若干个所述preamble信号；
所述确定模块，还用于：
在基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值之后，确定重复发送的所述若干个所述preamble信号的所述第一弧度值的第一平均值，并基于所述第一平均值确定所述终端设备的上行同步定时偏差。
结合第二方面和第二方面的第一种可能的实施方式至第五种可能的实施方式中的任一种，在第二方面的第六种可能的实施方式中，所述接收模块，具体用于：
接收所述终端设备通过多个天线发送的所述preamble信号；
所述确定模块，还用于：
在基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值之后，确定通过多个天线发送的所述preamble信号的所述第一弧度值的第二平均值，并基于所述第二平均值确定所述终端设备的上行同步定时偏差。
本发明实施例中通过基站接收终端设备发送的前导码preamble信号，然后确定发送所述preamble信号中的每个符号组所占用的频域信道的信道估计值，之后基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，并基于所述第一弧度值确定所述终端设备的上行同步定时偏差，由于preamble信号的相位差由于上行同步定时偏差造成的，因此preamble信号的相位差可以反映终端设备的上行同步定时偏差，相比于现有技术中，采用基站将preamble序列进行FFT以及IDFT等变换处理的方法，本发明实施例中通过将preamble信号中每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，根据所述第一弧度值确定preamble信号的相位差，提高了确定上行同步定时偏差的准确性。
附图说明
图1为本发明实施例提供的终端设备上行同步的示意图；
图2为本发明实施例提供的跳频图样的示意图；
图3为本发明实施例提供的一种确定上行同步定时偏差的方法的流程图；
图4为本发明实施例提供的一种确定上行同步定时偏差的方法的流程图；
图5为本发明实施例提供的一种确定上行同步定时偏差的方法的流程图；
图6为本发明实施例提供的一种确定上行同步定时偏差的方法的流程图；
图7为本发明实施例提供的一种确定上行同步定时偏差的装置的结构示意图；
图8为本发明实施例提供的一种基站设备的结构示意图。
具体实施方式
为了使本发明的目的、技术方案和优点更加清楚，下面将结合附图对本发明作进一步地详细描述，显然，所描述的实施例仅仅是本发明一部分实施例，而不是全部的实施例。基于本发明中的实施例，本领域普通技术人员在没有做出创造性劳动前提下所获得的所有其它实施例，都属于本发明保护的范围。
同长期演进(英文：Long Term Evolution，简称：LTE)系统相同，窄带物联网(英文：Narrow Band Internet of Things，简称：NB-IoT)系统由于终端设备(英文：User Equipment，简称：UE)和基站间的距离是不确定的，UE需要通过随机接入过程同基站建立上行同步，基站检测到UE发送了前导码preamble信号，通过接收到的preamble信号估计出上行同步定时偏差，并通过随机接入响应发送上行同步定时偏差给UE，UE接收到随机接入响应之后，计算定时提前量并调整上行信号的发送时间，从而实现了上行同步，如图1所示。
LTE系统中，Preamble序列是ZC序列经过循环移位生成的，它们源自一个ZC根序列。基站在接收到UE发送的preamble信号后，通过如下过程确定上行同步定时偏差：
第一步，基站根据接收到的preamble信号的Preamble格式类型去除Preamble信号的循环前缀(英文：CyclicPrefix，简称：CP)部分，保留Preamble 序列部分。
第二步，基站针对Preamble序列进行频谱搬移、积分梳状滤波器(英文：Cascade Integrator Comb，简称：CIC)降采样及快速傅氏变换(英文：Fast Fourier Transformation，简称：FFT)等操作，将Preamble序列由时域变换到频域，并对变换到频域的Preamble序列进行子载波解映射。
第三步，基站将经过子载波解映射的Preamble序列经过频域自动增益控制(英文：Automatic Gain Control，简称：AGC)处理，确保经过子载波解映射的Preamble序列的幅度保持在预设区间内。
第四步，基站将ZC根序列与经过频域AGC处理的Preamble序列进行频域相乘。
第五步，基站将经过频域相乘的Preamble序列进行离散傅里叶反变换(英文：Inverse Discrete Fourier Transform，简称：IDFT)，使Preamble序列由频域相关结果变换到时域，从而得到时域信号的循环相关结果。
第六步，基站将变换到时域的Preamble信号经过AGC恢复处理，使得变换到时域的Preamble序列的幅度恢复到达基站时的原始幅度。
第七步，基站合并该UE通过各路天线发送的Preamble信号的信号功率，即合并该UE通过各路天线发送的恢复到原始幅度的Preamble序列。
第八步，基站估计物理随机接入信道(英文：Physical Random Access Channel，简称：PRACH)的信号功率和噪声功率；通过经过合并的信号功率和PRACH的信号功率以及噪声功率，判断是否有Preamble信号接入，若有Preamble信号接入，根据检测窗内最大径或第一径的位置估计上行定时提前量。其中，最大径表示经过合并的信号功率幅度最大的峰值，第一径表示经过合并的信号功率第一个大于预设阈值的峰值。
NB-IoT系统中，基站配置一个或多个窄带物理随机接入信道(英文：Narrowband Physical Random Access Channel，简称：NPRACH)，每个NPRACH由12个子载波构成，每个UE发送的preamble信号在一个NPRACH的12个子载波内跳频发送。Preamble信号由4个符号组组成，每个符号组包括1个 CP以及5个OFDM符号，且5个OFDM符号上发送的信号相同，可以都为1，因此可以保证频域上配置多个PRACH时，不同的Preamble信号之间是正交的。Preamble信号的格式及符号长度如表1所示，其中T s＝1/1.92/10^6，两种格式preamble信号的CP长度不同，格式format0支持10km小区半径，format1支持40km小区半径。
表1
Figure PCTCN2018085328-appb-000003
其中，Tcp表示preamble信号中CP的长度；Tseq表示preamble信号中preamble序列的长度；Total表示preamble信号总长度。
每个符号组发送时均只占用一个子载波，且按照预设的跳频图样进行发送。以图2所示的跳频图样为例进行说明，跳频图样中在符号组之间配置两个等级的跳频间隔，符号组1和符号组2之间、符号组3和符号组4之间配置第1等级的跳频间隔，第1等级的跳频间隔为一个子载波FH1＝3.75kHz，称为符号组小跳；符号组2和符号组3之间配置第2等级的跳频间隔，第2等级的跳频间隔为六个子载波FH2＝22.5kHz，称为符号组大跳。并且符号组1和符号组2跳频方向同符号组3和符号组4跳频方向相反，符号组1和符号组4跳频方向同符号组2和符号组3跳频方向相同。
preamble信号时间上持续较长时间发送，且可以重复发送多次，3GPP标准定义preamble信号可以重复发送的次数为[1，2，4，8，16，32，64，128]，基站可以选择其中的3种重复发送的次数进行配置。每次重复发送的preamble信号在时间上连续，在频域上跳频发送，跳频方式可以采用LTE物理上行共享信道(英文：Physical UplinkShared Channel，简称：PUSCH)type2跳频方式。preamble重复发送64次后需要添加40ms的保护间隔(英文：guard period， 简称：GP)。preamble信号不同时刻通过跳频的方式选择不同的起始子载波发送，以获得抗干扰和频域分集合并增益。不同的起始子载波对应不同的跳频路径，一个子载波在某个时刻只能承载一个用户的preamble信号。
由于LTE系统中Preamble信号是ZC序列，ZC序列均具有良好的自相关性以及良好的互不相关性。因此LTE系统中Preamble信号经过FFT以及IDFT等变换后基站可以分辨出多径，从而可以合并该UE通过各路天线发送的Preamble信号的信号功率，之后根据合并得到的信号功率确定上行同步定时偏差。而NB-IoT系统中Preamble序列由4个符号组组成。每个符号组包括1个CP以及5个OFDM符号，且5个OFDM符号上发送的信号相同，因此NB-IoT系统中Preamble信号经过FFT以及IDFT等变换后基站无法分辨出多径，无法合并该UE通过各路天线发送的Preamble信号的信号功率，从而造成确定上行同步定时偏差的准确性较低。多径指终端设备发送的Preamble信号经过多个天线抵达基站的传播现象。
并且，由于NB-IoT系统中preamble信号在时间上持续的时间较长，即发送一个符号组的时间较长，相邻两组符号组间间隔时间较长从而进行终端设备进行下行同步时频率不能做到很好的同步，因此终端在下行同步后可能有较大的残留频偏，而残留频偏会造成额外的相位差，从而影响上行同步定时偏差确定的准确性。例如一组符号组持续1.6ms，50Hz的残留频偏会带来0.16π的相位差。而通过将preamble信号进行FFT以及IDFT等变换处理确定上行同步定时偏差的方式无法对这种残留频偏进行处理，从而造成确定的上行同步定时偏差准确性较低。
基于此，本发明实施例提供一种确定上行同步定时偏差的方法及装置，用以解决现有技术中存在的NB-IoT系统中基站通过将Preamble序列经过FFT以及IDFT等变换处理确定上行同步定时偏差时准确性较低的问题。其中，方法和装置是基于同一发明构思的，由于方法及装置解决问题的原理相似，因此装置与方法的实施可以相互参见，重复之处不再赘述。
在本发明实施例的描述中，“第一”、“第二”等词汇，仅用于区分描述的目 的，而不能理解为指示或暗示相对重要性，也不能理解为指示或暗示顺序。
下面结合附图对本发明优选的实施方式进行详细说明。
参阅图3所示，为本发明实施例提供的一种确定上行同步定时偏差的方法的流程图，具体可以包括如下：
S301，基站接收终端设备发送的前导码preamble信号。
S302，所述基站确定发送所述preamble信号中的每个符号组所占用的频域信道的信道估计值。
S303，所述基站基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，并基于所述第一弧度值确定所述终端设备的上行同步定时偏差。
本发明实施例中通过基站接收终端设备发送的前导码preamble信号，然后确定发送所述preamble信号中的每个符号组所占用的频域信道的信道估计值，之后基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，并基于所述第一弧度值确定所述终端设备的上行同步定时偏差，由于preamble信号的相位差由于上行同步定时偏差造成的，因此preamble信号的相位差可以反映终端设备的上行同步定时偏差，相比于现有技术中，采用基站将preamble序列进行FFT以及IDFT等变换处理的方法，本发明实施例中通过将preamble信号中每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，根据所述第一弧度值确定preamble信号的相位差，提高了确定上行同步定时偏差的准确性。
具体的，所述基站基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，可以通过如下两种方式的任一种实现：
方式一：所述基站基于所述跳频图样，将所述preamble信号中任意两个跳频间隔为M个子载波的符号组的信道估计值进行共轭相乘得到至少两个结果，并将得到的至少两个共轭相乘的结果作和得到第一弧度值，其中，所述M为正整数。
方式二：A1，所述基站基于所述跳频图样，将所述preamble信号中任意两个跳频间隔为N个子载波的符号组的信道估计值进行共轭相乘得到至少两个结果，并将得到的至少两个共轭相乘的结果作和得到第二弧度值，其中，所述N为正整数。
A2，所述基站基于所述跳频图样，将所述preamble信号中任意两个跳频间隔为H个子载波的符号组的信道估计值进行共轭相乘得到至少两个结果，并将得到的至少两个共轭相乘的结果作和得到第三弧度值，其中，所述H为正整数，其中N小于H。
A3，所述基站将所述第二弧度值以及所述第三弧度值作和得到所述第一弧度值。
可选的，所述基站可以基于所述跳频图样，将所述preamble信号中任意两个符号组的信道估计值进行共轭相乘得到至少两个结果，并将得到的至少两个共轭相乘的结果作和得到第一弧度值；或者，
所述基站也可以基于所述跳频图样，将所述preamble信号中预先选择的两个符号组的信道估计值进行共轭相乘，并将得到的共轭相乘的结果作为第一弧度值；所述基站也可以通过其他方式得到第一弧度值，本发明实施例在这里不做具体限定。
为了更好地理解本发明实施例，以下给出具体应用场景，以所述preamble信号采用的跳频图样为图2所示的跳频图样，所述preamble信号包括符号组1，符号组2，符号组3以及符号组4为例，对基站接收终端设备发送的前导码preamble信号之后，确定上行同步定时偏差的过程具体详细描述。
场景一：所述基站基于图2所示的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值通过方式一实现，且M等于1。
参阅图4所示，基站确定上行同步定时偏差的过程具体包括：
S401，去CP。
具体的，基站根据接收到的preamble信号的Preamble格式类型去除Preamble信号的CP部分。
S402，1/2子载波频率偏移。
具体的，基站将去除CP部分的preamble信号进行1/2子载波即1.875kHz频移。
基站通过将去除CP部分的preamble信号进行1/2子载波频移，避免了直流分量的影响。
S403，同步信号解调。
具体的，基站将经过1/2子载波频率偏移的preamble信号进行FFT变换得到频域序列，然后根据图2所示的跳频图样确定每个OFDM符号所在信道的中心频率，并在preamble信号的频域序列中抽取每个OFDM符号所在信道的中心频率对应的频域数据。
S404，频域AGC处理。
具体的，基站将每个OFDM符号对应的频域数据经过频域AGC处理，确保每个OFDM符号对应的频域数据的幅度均保持在预设区间内。
S405，粗定时同步。
具体的，所述基站确定每个符号组中经过频域AGC处理的5个OFDM符号对应的频域数据的平均值为每个符号组所占用的频域信道的信道估计值，并将所述preamble信号中跳频间隔为1个子载波的符号组1和符号组2的信道估计值进行共轭相乘，以及跳频间隔为1个子载波的符号组3和符号组4的信道估计值进行共轭相乘，并将两个共轭相乘的结果作和得到第一弧度值，其中，第一弧度值符合如下公式要求：
R s＝y 1 *y 2+y 3y 4 *；
R s表示第一弧度值，y 1表示符号组1的信道估计值；y 2表示符号组2的信道估计值；y 3表示符号组3的信道估计值；y 4表示符号组4的信道估计值。
在一种可能的实施方式中，当接收到所述终端设备重复发送的若干个所述preamble信号时，基站进行粗定时同步的过程可以通过如下方式实现：
B1，针对每一个所述preamble信号，基站确定所述每一个所述preamble 信号对应的第一弧度值。
当终端设备基于不同的跳频图样重复发送所述preamble信号时，每个所述preamble信号的符号组1跳频到符号组2时可能是通过正跳，即符号组2所占用的频域信道的中心频率大于符号组1所占用的频域信道的中心频率；也可能是通过负跳，即符号组2所占用的频域信道的中心频率小于符号组1所占用的频域信道的中心频率。为了保证相位的一致性，本发明实施例中对若干个所述preamble信号的第一弧度值进行修正。
具体的，针对若干个所述preamble信号，基站可以将符号组1通过正跳跳频到符号组2的所述preamble信号的第一弧度值进行修正，修正后的第一弧度值符合如下公式：
R s＝(y 1 *y 2+y 3y 4 *) *。
或者，针对若干个所述preamble信号，基站也可以将符号组1通过负跳跳频到符号组2的所述preamble信号的第一弧度值进行修正，本发明实施例在这里不作具体限定。
B2，基站确定若干个所述preamble信号的第一弧度值的弧度平均值，所述弧度平均值符合如下公式要求：
Figure PCTCN2018085328-appb-000004
其中，
Figure PCTCN2018085328-appb-000005
表示弧度平均值，N rep表示终端设备重复发送的次数，
Figure PCTCN2018085328-appb-000006
表示第i次发送的preamble信号的第一弧度值。
B3，基站将所述弧度平均值转换成第一角度值，第一角度值符合如下公式要求：
Figure PCTCN2018085328-appb-000007
其中，θ s表示第一角度值。
可选的，在步骤S405之后，S407之前，执行步骤S406。
S406，天线合并。
具体的，当接收所述终端设备通过多个天线发送的若干个所述preamble信号时，针对每一个所述preamble信号，基站确定每一个所述preamble信号对应的第一角度值，然后确定若干个所述preamble信号的第一角度值的第一角度平均值，所述第一角度平均值符合如下公式要求：
Figure PCTCN2018085328-appb-000008
其中，
Figure PCTCN2018085328-appb-000009
表示第一角度平均值，N aR表示终端设备发送preamble信号通过天线的数量，
Figure PCTCN2018085328-appb-000010
表示通过第j个天线发送的preamble信号的第一角度值。
S407，确定上行同步定时偏差。
具体的，基站基于第一角度平均值确定上行同步定时偏差，上行同步定时偏差符合如下公式要求：
Figure PCTCN2018085328-appb-000011
其中，TA表示所述上行同步定时偏差；N FFT为所述preamble信号进行傅里叶变换FFT的点数。
场景二：所述基站基于图2所示的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值通过方式一实现，且M等于6。
参阅图5所示，基站确定上行同步定时偏差的过程具体包括：
S501，去CP。
S502，1/2子载波频率偏移。
S503，同步信号解调。
S504，频域AGC处理。
S501至S504，参见图4所示的步骤S401至步骤S404，本发明实施例在这里不再重复赘述。
S505，细定时同步。
具体的，所述基站确定每个符号组中经过频域AGC处理的5个OFDM 符号对应的频域数据的平均值为每个符号组所占用的频域信道的信道估计值，并将所述preamble信号中跳频间隔为6个子载波的符号组1和符号组4的信道估计值进行共轭相乘，以及跳频间隔为6个子载波的符号组2和符号组3的信道估计值进行共轭相乘，并将两个共轭相乘的结果作和得到第二弧度值，其中，第二弧度值符合如下公式要求：
R l＝y 1 *y 4e jφ+y 3y 2 *e j3φ；
R l表示第二弧度值，y 1表示符号组1的信道估计值；y 2表示符号组2的信道估计值；y 3表示符号组3的信道估计值；y 4表示符号组4的信道估计值；φ符合如下公式要求：
φ＝2πΔfT；
其中，Δf表示终端设备的残留频偏值，T表示发送一个符号组的时间长度。
在一种可能的实施方式中，当接收到所述终端设备重复发送的若干个所述preamble信号时，基站进行细定时同步的过程可以通过如下方式实现：
C1，针对每一个所述preamble信号，基站确定所述每一个所述preamble信号对应的第二弧度值。
当终端设备基于不同的跳频图样重复发送所述preamble信号时，每个所述preamble信号的符号组2跳频到符号组3时可能是通过正跳，即符号组2所占用的频域信道的中心频率小于符号组3所占用的频域信道的中心频率；也可能是通过负跳，即符号组2所占用的频域信道的中心频率大于符号组3所占用的频域信道的中心频率。为了保证相位的一致性，本发明实施例中对若干个所述preamble信号的第二弧度值进行修正。
具体的，针对若干个所述preamble信号，基站将符号组2通过正跳跳频到符号组3的所述preamble信号的第二弧度值进行修正，修正后的第二弧度值符合如下公式：
R l＝(y 1 *y 4e jφ+y 3y 2 *e j3φ) *。
或者，针对若干个所述preamble信号，基站也可以将符号组2通过负跳跳频到符号组3的所述preamble信号的第二弧度值进行修正，本发明实施例在这里不作具体限定。
C2，基站确定若干个所述preamble信号的第二弧度值的弧度平均值，所述弧度平均值符合如下公式要求：
Figure PCTCN2018085328-appb-000012
其中，
Figure PCTCN2018085328-appb-000013
表示弧度平均值，N rep表示终端设备重复发送的次数，
Figure PCTCN2018085328-appb-000014
表示第i次发送的preamble信号的第二弧度值。
C3，基站将所述弧度平均值转换成第二角度值，第二角度值符合如下公式要求：
Figure PCTCN2018085328-appb-000015
其中，θ l表示第二角度值。
可选的，在步骤S505之后，S507之前，执行步骤S506。
S506，天线合并。
具体的，当接收所述终端设备通过多个天线发送的若干个所述preamble信号时，针对每一个所述preamble信号，基站确定每一个所述preamble信号对应的第二角度值，然后确定若干个所述preamble信号的第二角度值的第二角度平均值，所述第二角度平均值符合如下公式要求：
Figure PCTCN2018085328-appb-000016
其中，
Figure PCTCN2018085328-appb-000017
表示第二角度平均值，N aR表示终端设备发送preamble信号通过天线的数量，
Figure PCTCN2018085328-appb-000018
表示通过第j个天线发送的preamble信号的第二角度值。
S507，确定上行同步定时偏差。
具体的，基站基于第二角度平均值确定上行同步定时偏差，上行同步定时偏差符合如下公式要求：
Figure PCTCN2018085328-appb-000019
其中，TA表示所述上行同步定时偏差；N FFT为所述preamble信号进行傅里叶变换FFT的点数。
场景三：所述基站基于图2所示的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值通过方式二实现，且N等于6，H等于6。
参阅图6所示，基站确定上行同步定时偏差的过程具体包括：
S601，去CP。
S602，1/2子载波频率偏移。
S603，同步信号解调。
S604，频域AGC处理。
S601至S604，参见图4所示的步骤S401至步骤S404，本发明实施例在这里不再重复赘述。
S605，粗定时同步。
具体的，所述基站确定发送所述preamble信号中的每个符号组所占用的频域信道的信道估计值，并基于图2所示的跳频图样确定第一角度值θ s。
具体如何基于图2所示的跳频图样确定第一角度值θ s，可以参阅图4所示的步骤S405，本发明实施例在这里不做重复赘述。
S606，细定时同步。
具体的，所述基站确定发送所述preamble信号中的每个符号组所占用的频域信道的信道估计值，并基于图2所示的跳频图样确定第二角度值θ l。
具体如何基于图2所示的跳频图样确定第二角度值θ l，可以参阅图5所示的步骤S505，本发明实施例在这里不做重复赘述。
其中，步骤S605和S606没有严格的先后顺序，可以先执行S605后执行S606，也可以先执行S606后执行S605，也可以同时执行S605和S606，本发 明实施例在这里不做具体限定。
可选的，在步骤S606之后，步骤S609之前，执行S607。
S607，相位补偿。
具体的，所述基站基于第一角度值θ s对第二角度值θ l进行相位补偿，经过相位补偿后的θ l符合下述公式要求：
θ l1＝angle(R le -j6θs)；
其中，θ l1表示经过相位补偿后的θ l；R l表示所述第二弧度值。
需要说明的是，由于频偏估计的准确性对确定上行定时定时同步偏差的影响较大，当重复次数较多信噪比较低时或残留频偏小的情况下，由于频偏估计不准确导致频偏补偿后系统性能反而恶化了。因此，基站对第二角度值θ l进行相位补偿时主要考虑如下因素:
a)终端设备重复发送preamble信号的次数小于第一阈值。
b)基站确定的终端残留频偏值小于第二阈值。
c)基站检测到的上行信噪比低于第三阈值。
当满足以上至少一个条件时，基站对第二角度值θ l不进行相位补偿。
可选的，在步骤S607之后，S609之前，执行步骤S608。
S608，天线合并。
具体的，当接收所述终端设备通过多个天线发送的若干个所述preamble信号时，基站确定第一角度平均值
Figure PCTCN2018085328-appb-000020
以及第二角度平均值
Figure PCTCN2018085328-appb-000021
具体如何确定第一角度平均值
Figure PCTCN2018085328-appb-000022
可以参阅图4所示的步骤S406，本发明实施例在这里不做重复赘述。
具体如何确定第二角度平均值
Figure PCTCN2018085328-appb-000023
可以参阅图5所示的步骤S506，本发明实施例在这里不做重复赘述。
S609，确定上行同步定时偏差。
具体的，基站基于角度平均值确定上行同步定时偏差，上行同步定时偏差符合如下公式要求：
Figure PCTCN2018085328-appb-000024
其中，TA表示所述上行同步定时偏差；N FFT为所述preamble信号进行傅里叶变换FFT的点数。
本发明实施例中通过基站接收终端设备发送的前导码preamble信号，然后确定发送所述preamble信号中的每个符号组所占用的频域信道的信道估计值，之后基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，并基于所述第一弧度值确定所述终端设备的上行同步定时偏差，由于preamble信号的相位差由于上行同步定时偏差造成的，因此preamble信号的相位差可以反映终端设备的上行同步定时偏差，相比于现有技术中，采用基站将preamble序列进行FFT以及IDFT等变换处理的方法，本发明实施例中通过将preamble信号中每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，根据所述第一弧度值确定preamble信号的相位差，提高了确定上行同步定时偏差的准确性。
基于与图3对应的方法实施例的同一发明构思，本发明实施例提供了一种确定上行同步定时偏差的装置70，所述装置可以应用于基站设备。该装置70的结构如图7所示，包括接收模块71以及确定模块72，其中：
接收模块71，用于接收终端设备发送的前导码preamble信号。
确定模块72，用于确定发送所述接收模块71接收的所述preamble信号中的每个符号组所占用的频域信道的信道估计值；基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，并基于所述第一弧度值确定所述终端设备的上行同步定时偏差。
在一种可能的实施方式中，所述确定模块72，在基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值时，具体用于：
基于所述跳频图样，将所述preamble信号中任意两个跳频间隔为M个子载波的符号组的信道估计值进行共轭相乘得到至少两个结果，并将得到的至 少两个共轭相乘的结果作和得到第一弧度值，其中，所述M为正整数。
在另一种可能的实施方式中，所述确定模块72，在基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值时，具体用于：
D1，基于所述跳频图样，将所述preamble信号中任意两个跳频间隔为N个子载波的符号组的信道估计值进行共轭相乘得到至少两个结果，并将得到的至少两个共轭相乘的结果作和得到第二弧度值，其中，所述N为正整数。
D2，基于所述跳频图样，将所述preamble信号中任意两个跳频间隔为H个子载波的符号组的信道估计值进行共轭相乘得到至少两个结果，并将得到的至少两个共轭相乘的结果作和得到第三弧度值，其中，所述H为正整数，其中N小于H。
D3，将所述第二弧度值以及所述第三弧度值作和得到所述第一弧度值。
可选的，所述上行同步定时偏差符合下述公式要求：
Figure PCTCN2018085328-appb-000025
其中，TA表示所述上行同步定时偏差；θ s1表示所述第二弧度值经过转换得到的角度值；θ l1表示所述第三弧度值经过转换得到的角度值；N FFT为所述preamble信号进行傅里叶变换FFT的点数。
可选的，所述装置还包括相位补偿模块73，用于在所述确定模块72基于所述第一弧度值确定所述终端设备的上行同步定时偏差之前，对所述确定模块72确定的所述第三弧度值经过转换得到的角度值进行相位补偿，经过相位补偿后的所述第三弧度值经过转换得到的角度值符合下述公式要求：
θ l2＝angle(R le -j6θs2)；
其中，θ l2表示经过相位补偿后的所述第三弧度值经过转换得到的角度值；R l表示所述第三弧度值；θ s2表示所述第二弧度值经过转换得到的角度值。
可选的，所述接收模块71，具体用于：接收所述终端设备重复发送的若干个所述preamble信号；
所述确定模块72，还用于：在基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值之后，确定重复发送的所述若干个所述preamble信号的所述第一弧度值的第一平均值，并基于所述第一平均值确定所述终端设备的上行同步定时偏差。
可选的，所述接收模块71，具体用于：接收所述终端设备通过多个天线发送的所述preamble信号；
所述确定模块72，还用于：在基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值之后，确定通过多个天线发送的所述preamble信号的所述第一弧度值的第二平均值，并基于所述第二平均值确定所述终端设备的上行同步定时偏差。
本发明实施例中通过基站接收终端设备发送的前导码preamble信号，然后确定发送所述preamble信号中的每个符号组所占用的频域信道的信道估计值，之后基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，并基于所述第一弧度值确定所述终端设备的上行同步定时偏差，由于preamble信号的相位差由于上行同步定时偏差造成的，因此preamble信号的相位差可以反映终端设备的上行同步定时偏差，相比于现有技术中，采用基站将preamble序列进行FFT以及IDFT等变换处理的方法，本发明实施例中通过将preamble信号中每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，根据所述第一弧度值确定preamble信号的相位差，提高了确定上行同步定时偏差的准确性。
基于与图3对应的方法实施例的同一发明构思，本发明实施例还提供了一种基站设备。该基站设备的结构如图8所示，包括处理器801、存储器802以及收发器803，其中：
处理器801，用于读取存储器802中的程序，执行下列过程：
通过收发器803接收和发送信息，并执行与上述图3对应的实施例中所述的方法。
收发器803，用于在处理器801的控制下接收和发送信息。
存储器802，用于存储软件程序。
在图8中，总线架构(用总线800来代表)，总线800可以包括任意数量的互联的总线和桥，总线800将包括由处理器801代表的一个或多个处理器和存储器802代表的存储器的各种电路链接在一起。总线800还可以将诸如外围设备、稳压器和功率管理电路等之类的各种其他电路链接在一起，这些都是本领域所公知的，因此，本文不再对其进行进一步描述。总线接口804在总线800和收发器803之间提供接口。收发器803可以是一个元件，也可以是多个元件，比如多个接收器和发送器，提供用于在传输介质上与各种其他装置通信的单元。
处理器801负责管理总线800和通常的处理，还可以提供各种功能，包括定时，外围接口，电压调节、电源管理以及其他控制功能。而存储器802可以被用于存储处理器801在执行操作时所使用的数据。
可选的，处理器801可以是中央处埋器(英文：Central Processing Unit，简称：CPU)、专用集成电路(英文：Application Specific Integrated Circuit，简称：ASIC)、现场可编程门阵列(英文：Field－Programmable Gate Array，简称：FPGA)或复杂可编程逻辑器件(英文：Complex Programmable Logic Device，简称：CPLD)、数字信号处理器(英文：Digital Signal Processing，简称：DSP)等等。
本领域内的技术人员应明白，本发明的实施例可提供为方法、系统、或计算机程序产品。因此，本发明可采用完全硬件实施例、完全软件实施例、或结合软件和硬件方面的实施例的形式。而且，本发明可采用在一个或多个其中包含有计算机可用程序代码的计算机可用存储介质(包括但不限于磁盘存储器、CD-ROM、光学存储器等)上实施的计算机程序产品的形式。
本发明是参照根据本发明实施例的方法、设备(系统)、和计算机程序产品的流程图和/或方框图来描述的。应理解可由计算机程序指令实现流程图和/或方框图中的每一流程和/或方框、以及流程图和/或方框图中的流程和/或方框的结合。可提供这些计算机程序指令到通用计算机、专用计算机、 嵌入式处理机或其他可编程数据处理设备的处理器以产生一个机器，使得通过计算机或其他可编程数据处理设备的处理器执行的指令产生用于实现在流程图一个流程或多个流程和/或方框图一个方框或多个方框中指定的功能的装置。
这些计算机程序指令也可存储在能引导计算机或其他可编程数据处理设备以特定方式工作的计算机可读存储器中，使得存储在该计算机可读存储器中的指令产生包括指令装置的制造品，该指令装置实现在流程图一个流程或多个流程和/或方框图一个方框或多个方框中指定的功能。
这些计算机程序指令也可装载到计算机或其他可编程数据处理设备上，使得在计算机或其他可编程设备上执行一系列操作步骤以产生计算机实现的处理，从而在计算机或其他可编程设备上执行的指令提供用于实现在流程图一个流程或多个流程和/或方框图一个方框或多个方框中指定的功能的步骤。
尽管已描述了本发明的优选实施例，但本领域内的技术人员一旦得知了基本创造性概念，则可对这些实施例作出另外的变更和修改。所以，所附权利要求意欲解释为包括优选实施例以及落入本发明范围的所有变更和修改。
显然，本领域的技术人员可以对本发明进行各种改动和变型而不脱离本发明的精神和范围。这样，倘若本发明的这些修改和变型属于本发明权利要求及其等同技术的范围之内，则本发明也意图包含这些改动和变型在内。

Claims (14)

  1. 一种确定上行同步定时偏差的方法，其特征在于，包括：
    基站接收终端设备发送的前导码preamble信号；
    所述基站确定发送所述preamble信号中的每个符号组所占用的频域信道的信道估计值；
    所述基站基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，并基于所述第一弧度值确定所述终端设备的上行同步定时偏差。
  2. 如权利要求1所述的方法，其特征在于，所述基站基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，包括：
    所述基站基于所述跳频图样，将所述preamble信号中任意两个跳频间隔为M个子载波的符号组的信道估计值进行共轭相乘得到至少两个结果，并将得到的至少两个共轭相乘的结果作和得到第一弧度值，其中，所述M为正整数。
  3. 如权利要求1所述的方法，其特征在于，所述基站基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，包括：
    所述基站基于所述跳频图样，将所述preamble信号中任意两个跳频间隔为N个子载波的符号组的信道估计值进行共轭相乘得到至少两个结果，并将得到的至少两个共轭相乘的结果作和得到第二弧度值，其中，所述N为正整数；
    所述基站基于所述跳频图样，将所述preamble信号中任意两个跳频间隔为H个子载波的符号组的信道估计值进行共轭相乘得到至少两个结果，并将得到的至少两个共轭相乘的结果作和得到第三弧度值，其中，所述H为正整数，其中N小于H；
    所述基站将所述第二弧度值以及所述第三弧度值作和得到所述第一弧度值。
  4. 如权利要求3所述的方法，其特征在于，所述上行同步定时偏差符合下述公式要求：
    Figure PCTCN2018085328-appb-100001
    其中，TA表示所述上行同步定时偏差；θ s1表示所述第二弧度值经过转换得到的角度值；θ l1表示所述第三弧度值经过转换得到的角度值；N FFT为所述preamble信号进行傅里叶变换FFT的点数。
  5. 如权利要求3所述的方法，其特征在于，在所述基站基于所述第一弧度值确定所述终端设备的上行同步定时偏差之前，所述方法还包括：
    所述基站对所述第三弧度值经过转换得到的角度值进行相位补偿，经过相位补偿后的所述第三弧度值经过转换得到的角度值符合下述公式要求：
    Figure PCTCN2018085328-appb-100002
    其中，θ l2表示经过相位补偿后的所述第三弧度值经过转换得到的角度值；R l表示所述第三弧度值；θ s2表示所述第二弧度值经过转换得到的角度值。
  6. 如权利要求1所述的方法，其特征在于，基站接收终端设备发送的前导码preamble信号，包括：
    所述基站接收所述终端设备重复发送的若干个所述preamble信号；
    在所述基站基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值之后，所述方法还包括：
    所述基站确定重复发送的所述若干个所述preamble信号的所述第一弧度值的第一平均值，并基于所述第一平均值确定所述终端设备的上行同步定时偏差。
  7. 如权利要求1至6任一项所述的方法，其特征在于，基站接收终端设备发送的前导码preamble信号，包括：
    所述基站接收所述终端设备通过多个天线发送的所述preamble信号；
    所述基站在基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值之后，所述方法还包括：
    所述基站确定通过多个天线发送的所述preamble信号的所述第一弧度值的第二平均值，并基于所述第二平均值确定所述终端设备的上行同步定时偏差。
  8. 一种确定上行同步定时偏差的装置，其特征在于，包括：
    接收模块，用于接收终端设备发送的前导码preamble信号；
    确定模块，用于确定发送所述接收模块接收的所述preamble信号中的每个符号组所占用的频域信道的信道估计值；基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值，并基于所述第一弧度值确定所述终端设备的上行同步定时偏差。
  9. 如权利要求8所述的装置，其特征在于，所述确定模块，在基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值时，具体用于：
    基于所述跳频图样，将所述preamble信号中任意两个跳频间隔为M个子载波的符号组的信道估计值进行共轭相乘得到至少两个结果，并将得到的至少两个共轭相乘的结果作和得到第一弧度值，其中，所述M为正整数。
  10. 如权利要求8所述的装置，其特征在于，所述确定模块，在基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值时，具体用于：
    基于所述跳频图样，将所述preamble信号中任意两个跳频间隔为N个子载波的符号组的信道估计值进行共轭相乘得到至少两个结果，并将得到的至少两个共轭相乘的结果作和得到第二弧度值，其中，所述N为正整数；
    基于所述跳频图样，将所述preamble信号中任意两个跳频间隔为H个子载波的符号组的信道估计值进行共轭相乘得到至少两个结果，并将得到的至少两个共轭相乘的结果作和得到第三弧度值，其中，所述H为正整数，其中N小于H；
    将所述第二弧度值以及所述第三弧度值作和得到所述第一弧度值。
  11. 如权利要求10所述的装置，其特征在于，所述上行同步定时偏差符合下述公式要求：
    Figure PCTCN2018085328-appb-100003
    其中，TA表示所述上行同步定时偏差；θ s1表示所述第二弧度值经过转换得到的角度值；θ l1表示所述第三弧度值经过转换得到的角度值；N FFT为所述preamble信号进行傅里叶变换FFT的点数。
  12. 如权利要求10所述的装置，其特征在于，所述装置还包括：
    相位补偿模块，用于在所述确定模块基于所述第一弧度值确定所述终端设备的上行同步定时偏差之前，对所述确定模块确定的所述第三弧度值经过转换得到的角度值进行相位补偿，经过相位补偿后的所述第三弧度值经过转换得到的角度值符合下述公式要求：
    Figure PCTCN2018085328-appb-100004
    其中，θ l2表示经过相位补偿后的所述第三弧度值经过转换得到的角度值；R l表示所述第三弧度值；θ s2表示所述第二弧度值经过转换得到的角度值。
  13. 如权利要求8所述的装置，其特征在于，所述接收模块，具体用于：
    接收所述终端设备重复发送的若干个所述preamble信号；
    所述确定模块，还用于：
    在基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值之后，确定重复发送的所述若干个所述preamble信号的所述第一弧度值的第一平均值，并基于所述第一平均值确定所述终端设备的上行同步定时偏差。
  14. 如权利要求8至13任一项所述的装置，其特征在于，所述接收模块，具体用于：
    接收所述终端设备通过多个天线发送的所述preamble信号；
    所述确定模块，还用于：
    在基于发送所述preamble信号采用的跳频图样，对每个符号组对应的信道估计值进行共轭相乘得到第一弧度值之后，确定通过多个天线发送的所述preamble信号的所述第一弧度值的第二平均值，并基于所述第二平均值确定所述终端设备的上行同步定时偏差。
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