WO2017216894A1 - Émetteur - Google Patents

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Publication number
WO2017216894A1
WO2017216894A1 PCT/JP2016/067756 JP2016067756W WO2017216894A1 WO 2017216894 A1 WO2017216894 A1 WO 2017216894A1 JP 2016067756 W JP2016067756 W JP 2016067756W WO 2017216894 A1 WO2017216894 A1 WO 2017216894A1
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WO
WIPO (PCT)
Prior art keywords
amplifier
signal
digital
characteristic
transmission signal
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Application number
PCT/JP2016/067756
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English (en)
Japanese (ja)
Inventor
一二三 能登
秀樹 森重
檜枝　護重
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三菱電機株式会社
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Application filed by 三菱電機株式会社 filed Critical 三菱電機株式会社
Priority to PCT/JP2016/067756 priority Critical patent/WO2017216894A1/fr
Publication of WO2017216894A1 publication Critical patent/WO2017216894A1/fr

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    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/32—Modifications of amplifiers to reduce non-linear distortion

Definitions

  • the present invention relates to a transmitter used for satellite communication, terrestrial microwave communication, and mobile communication.
  • Patent Document 1 discloses a technique for improving the linearity of a communication base station transmitter. Patent Document 1 uses a power series method in order to create predistortion in the digital predistortion method, and considers up to the seventh-order distortion component.
  • a predistortion is created in the digital part, and the DAC
  • the data is output to the analog unit via (Digital to Analog Converter).
  • the non-linear characteristic of the analog unit may be any characteristic.
  • the DAC requires a band three times the signal band, so the DAC band is less than the 100 MHz band.
  • the present invention has been made to solve the above-described problems, and an object thereof is to suppress quantization noise generated in a DAC without increasing the number of bits of the DAC.
  • the transmitter of the present invention includes a digital circuit that generates a digital transmission signal, a digital-to-analog converter that converts the predistorted transmission signal into an analog signal, and amplifies the analog transmission signal output by the digital-analog converter.
  • An amplifier is provided between the amplifier and the digital-analog converter and the amplifier, and the amplitude of the analog transmission signal output from the digital-analog converter is changed so that the AM-AM characteristic combined with the amplifier becomes a gain expansion characteristic.
  • An expansion generation circuit for outputting to the digital signal, and a distortion compensation circuit that is provided between the digital circuit and the digital-analog converter and predistorts the distortion of the transmission signal amplified by the amplifier.
  • quantization noise generated in the DAC can be suppressed without increasing the number of DAC bits.
  • FIG. 1 is a block diagram showing a configuration example of a transmitter according to Embodiment 1 of the present invention.
  • the transmitter includes a modem 1 and an RF module 9.
  • the modem 1 includes a DSP (Digital-Signal-Processor) 2, a modulation unit 3, a signal comparison unit 4, a PD (Pre-Distortion) signal generation unit 5, a PD unit 6, a DAC 7, and an ADC (Analog to Digital Converter) 8.
  • DSP Digital-Signal-Processor
  • modulation unit 3 a modulation unit 3
  • signal comparison unit 4 a PD (Pre-Distortion) signal generation unit 5
  • a PD unit 6 a DAC 7, and an ADC (Analog to Digital Converter) 8.
  • ADC Analog to Digital Converter
  • the DSP 2 includes a modulation unit 3, generates a digital signal, converts the digital signal into a baseband signal by the modulation unit 3, and outputs the digital signal.
  • the DSP 2 is connected to the PD 6 and the signal comparison unit 4.
  • the signal comparison unit 4 compares the modulation wave signal output from the modulation unit 3 with the feedback modulation wave signal output from the AD 8, and compares the complex signal vector difference (in the case of the LUT (Look Up Table) method with the amplitude). It is a signal comparison unit that outputs a phase difference) to the PD signal generation unit 5.
  • the signal comparison unit 4 is connected to the DSP 2 and the ADC 8.
  • the PD signal generation unit 5 is a PD signal generation unit that generates an inverse signal that cancels distortion generated from the DAC 7 to the amplifier 15 according to the comparison result output from the signal comparison unit 4.
  • the PD signal generation unit 5 is connected to the PD 6 and the signal comparison unit 4.
  • a method of generating an inverse signal by the PD signal generation unit 5 for example, an LUT method, a polynomial method, a power series method, a memory polynomial method, or a Volterra series method is used.
  • PD 6 is a PD that superimposes the reverse signal generated by the PD signal generation unit 5 and the baseband signal generated by the modulation unit 3 and outputs the superimposed signal.
  • the PD 6 is connected to the DSP 2 and the DAC 7.
  • the DAC 7 is a DAC that converts a digital signal output from the PD 6 into an analog signal.
  • the DAC 7 is connected to the PD 6 and the BPF 10.
  • the ADC 8 is an ADC that changes an analog signal output from the BPF 21 into a digital signal.
  • the ADC 8 is connected to the BPF 21 and the signal comparison unit 4.
  • the DSP 2, the signal comparison unit 4, the PD signal generation unit 5, and the PD 6 are configured by an FPGA (Field-Programmable Gate Array), an ASIC (Application Specific Integrated Circuit), and the like.
  • the DAC 7 and the ADC 8 may be configured to be built in the FPGA.
  • the RF module 9 includes a BPF (Band-Pass Filter) 10, a mixer 11, an LO (Local Signal Source) 12, a BPF 13, an ECC (Expansion / Characteristics / Circuit) 14, an amplifier 15, a coupler 16, an isolator 17, an LPF (Low-Pass Filter). ) 18, an antenna 19, a mixer 20, and a BPF 21.
  • BPF Band-Pass Filter
  • LO Local Signal Source
  • BPF 13 Low-Pass Filter
  • ECC Exposure / Characteristics / Circuit
  • the BPF 10 is a BPF that blocks unnecessary waves from the modulation signal output from the DAC 7 and outputs a modulation signal that blocks unnecessary waves.
  • the BPF 10 is connected to the DAC 7 and the mixer 11.
  • the mixer 11 is a mixer that mixes the modulation signal output from the BPF 11 and the local signal of the LO 12 and converts the frequency of the modulation signal.
  • the mixer 11 has an LO terminal connected to the LO 12, an IF terminal connected to the BPF 11, and an RF terminal connected to the BPF 13.
  • LO 12 is an oscillator that outputs a local signal used for frequency conversion in the mixer 11.
  • the LO 12 is connected to the mixer 11 and the mixer 20.
  • the BPF 13 is a BPF that blocks unnecessary waves outside the desired band from the frequency-converted modulated signal and outputs a modulated signal that blocks unnecessary waves.
  • the BPF 13 is connected to the mixer 11 and the ECC 14.
  • the ECC 14 is an analog circuit that performs gain expansion (gain expansion) on the AM-AM characteristic of the modulation signal.
  • the ECC 14 is connected to the BPF 13 and the amplifier 15.
  • FIG. 2 is a circuit diagram showing a configuration example and characteristics of the ECC 14 according to the first embodiment of the present invention.
  • FIG. 2A shows an example in which an amplifier whose operation class is from class B to class AB is used, and has a characteristic that the gain increases with respect to the output power.
  • Vc is a bias voltage of the amplifier, and Vc is adjusted to set a bias in a range from class B to class AB.
  • FIG. 2B shows an example in which a parallel diode linearizer is used, and has a characteristic of increasing the gain with respect to output power by using the nonlinear characteristic of the diode.
  • FIG. 2C is a modification of FIG. 2B in which the ECC 14 is configured using a diode and a hybrid. The characteristic of increasing the gain with respect to the output power using the nonlinear characteristic of the diode is shown. Give it.
  • the gain characteristic with respect to the output power has been described as an example, but the gain characteristic with respect to the input power is the same as that with the output power.
  • the amplifier 15 is an amplifier that receives a gain-expanded modulation signal and amplifies the modulation signal.
  • the amplifier 15 is connected to the ECC 14 and the coupler 16.
  • the coupler 16 is a coupler that extracts a part of the amplified modulation signal.
  • the coupler 16 is connected to the amplifier 15 and the isolator 17.
  • the isolator 17 is an isolator that allows a modulated signal to pass and absorbs a reflected wave generated by a component connected to a subsequent stage.
  • the isolator 17 is connected to the coupler 16 and the LPF 18.
  • the LPF 18 is an LPF that blocks unnecessary waves outside the desired band from the modulation signal and outputs a modulation signal that blocks unnecessary waves.
  • the LPF 18 is connected to the isolator 17 and the antenna 19.
  • the antenna 19 is an antenna that transmits the modulation signal output from the LPF 18.
  • the antenna 19 is connected to the LPF 18.
  • the mixer 20 is a mixer that mixes the local signal of the LO 12 and the modulation signal amplified by the amplifier 15 and converts the frequency of the modulation signal.
  • the mixer 20 has an RF terminal connected to the coupler 16, an LO terminal connected to the LO 12, and an IF terminal connected to the BPF 21.
  • the BPF 21 is a BPF that blocks unnecessary waves from the modulation signal frequency-converted by the mixer 20 and outputs a modulation signal that blocks unnecessary waves.
  • the BPF 21 is connected to the mixer 20 and the ADC 8.
  • the DSP 2 outputs the modulation wave signal generated by the modulation unit 3 in the DSP 2 to the DAC 7 via the PD 6.
  • the DAC 7 converts the input baseband signal into an analog signal and outputs the analog signal to the BPF 10.
  • the BPF 10 suppresses unnecessary waves outside the passband of the BPF 10 from the analog signal output by the DAC 7, and outputs an analog signal in which unnecessary waves are suppressed to the mixer 11.
  • the mixer 11 up-converts the analog signal output from the BPF 10 using the local signal of the LO 12 and converts it into an RF signal.
  • the mixer 11 outputs an RF signal to the BPF 13.
  • the mixer 11 When the mixer 11 performs frequency conversion, an analog signal and a local signal are mixed, so that an unnecessary wave is output in addition to a desired RF signal.
  • the BPF 11 blocks unnecessary waves from the output signal of the mixer 11 and outputs a desired RF signal to the ECC 14.
  • the ECC 14 has an AM-AM characteristic having a gain expansion characteristic, changes the gain according to the power of the input RF signal, and outputs the gain to the amplifier 15. Details of this point will be described later.
  • the amplifier 15 amplifies the RF signal output from the ECC 14 and outputs the amplified RF signal to the LPF 18 via the coupler 16 and the isolator 17.
  • the LPF 18 suppresses unnecessary waves in the RF signal amplified by the amplifier 15 and outputs an RF signal in which unnecessary waves are suppressed to the antenna 19.
  • the antenna 19 transmits the RF signal output from the LPF 18.
  • the coupler 16 takes out a part of the RF signal and outputs it to the mixer 20 in order to feed back the RF signal amplified by the amplifier 15.
  • the mixer 20 uses the local signal of the LO 12 to down-convert the RF signal input from the coupler 16 and convert it into a baseband signal.
  • the BPF 21 suppresses unnecessary waves in the output signal of the mixer 20 and outputs a baseband signal in which unnecessary waves are suppressed to the ADC 8.
  • the ADC 8 converts the baseband signal into a digital signal and outputs it to the signal comparison unit 4.
  • the signal comparison unit 4 compares the modulation signal generated by the DSP 2 with the modulation signal fed back through the ECC 14 and the amplifier 15, and outputs the difference to the PD signal generation unit 5.
  • the PD signal generation unit 5 generates an inverse signal that cancels distortion generated in the ECC 14 and the amplifier 15 in accordance with the output signal of the signal comparison unit 4 and outputs the reverse signal to the PD 6.
  • the PD 6 superimposes an inverse signal that compensates for distortion of the ECC 14 and the amplifier 15 on the modulation signal generated by the DSP 2, and outputs the superimposed modulation signal to the DAC 7.
  • the generated modulation signal is compared with the modulation signal fed back through the ECC 14 and the amplifier 15, and an inverse signal that cancels the nonlinear characteristics of the ECC 14 and the amplifier 15 is superimposed on the modulation signal.
  • the distortion generated in the amplifier 15 is compensated. This distortion compensation is called predistortion.
  • FIG. 3 is a diagram showing AM-AM characteristics and distortion characteristics in a general amplifier.
  • the AM-AM characteristic of an amplifier changes in the order of dotted line ⁇ broken line ⁇ solid line
  • the distortion characteristic deteriorates in the order of broken line ⁇ dotted line ⁇ solid line. This is because the flatter the AM-AM characteristic, the better the distortion characteristic.
  • the AM-AM characteristic and the distortion characteristic are related, and it is desired to flatten the AM-AM characteristic in order to improve the distortion.
  • FIG. 4 shows AM-AM characteristics when the ECC 14 and the amplifier 15 according to the first embodiment of the present invention are combined.
  • the broken line is the conventional characteristic (characteristic when there is no ECC 14)
  • the dotted line is the characteristic when the distortion characteristic is good
  • an analog circuit corresponding to the ECC 14 is provided at the front stage of the amplifier as shown by the dotted line in FIG. 4, but the ECC 14 is such that the AM-AM characteristic of the ECC 14 and the amplifier 15 is the solid line in FIG.
  • the gain is expanded according to the power of the input signal. That is, the ECC 14 does not compensate for the distortion of the amplifier 15 but causes the AM-AM characteristic of the ECC 14 and the amplifier 15 to be the gain expansion characteristic even if the distortion of the amplifier 15 is deteriorated. Thereby, although the distortion of the signal is deteriorated, the maximum value of the power output from the DAC 7 can be reduced as will be described later. The deteriorated distortion is compensated by the PD 6.
  • FIG. 5 is a diagram showing a cumulative distribution of instantaneous power with respect to the average power of the modulated wave signal.
  • the vertical axis is CCDF (Complementary Cumulative Distribution Function), and the horizontal axis is instantaneous power.
  • PAPR peak to average power ratio
  • the DAC 7 requires a dynamic range of 10 dB for PAPR and Ad dB for distortion compensation of PD6 when there is no ECC14. .
  • the gain of the amplifier decreases as the input power increases. Therefore, it is necessary to increase the gain of AdB in order to compensate for the decrease in the gain.
  • the wider the band of the modulation signal and the larger the PAPR the more the amplifier operates non-linearly and the amount of distortion compensation increases, so the dynamic range required for the DAC 7 increases.
  • the operation speed of the DAC is decreased.
  • FIG. 6 is a conceptual diagram showing signal quantization in the DAC 7 according to the first embodiment of the present invention.
  • a dotted line is an input signal waveform when the ECC 14 is not present, and a solid line is an input signal waveform when the ECC 14 is present.
  • the gain is expanded by the ECC 14, so that the amplitude of the signal output from the DAC 7 is smaller than when the ECC 14 is not present. Therefore, when the number of bits of the DAC 7 is X bits, the resolution per bit (corresponding to the step width in FIG.
  • FIG. 7 is a diagram showing a frequency spectrum before and after distortion compensation of the transmitter according to Embodiment 1 of the present invention.
  • the noise floor after distortion compensation is increased because the quantization noise is increased by the amount of gain expansion by the DAC 7.
  • the quantization noise is lowered, the distortion noise is reduced.
  • the noise floor after compensation can be lowered.
  • FIG. 8 is a characteristic diagram showing distortion characteristics of the RF module 9 when the number of bits of the DAC 7 according to Embodiment 1 of the present invention is 10.
  • the vertical axis is ACPR (Adjacent Channel Power Ratio), and the horizontal axis is Pout.
  • ACPR Adjacent Channel Power Ratio
  • Pout the horizontal axis
  • the ECC 14 is used to change the AM-AM characteristic of the amplifier 15 to the gain expansion characteristic, so that an increase in quantization noise of the DAC 7 can be suppressed.
  • the RF module 9 of the first embodiment does not have a reception function, but may have a reception function.
  • FIG. 9 is a block diagram showing a configuration example of a transmitter according to Embodiment 2 of the present invention. 9, the same reference numerals as those in FIG. 1 denote the same or corresponding parts. 1 is different from FIG. 1 in that a VGA (Variable Gain Amplifier) 22, a VGA 23, a TS 24a, and a control unit 25a are provided.
  • VGA Very Gain Amplifier
  • BPF 10 and BPF 10a mixer 11 and mixer 11a, LO 12 and LO 12a, BPF 13 and BPF 13a, ECC 14 and ECC 14a, amplifier 15 and amplifier 15a, coupler 16 and coupler 16a, isolator 17 and isolator 17a, LPF 18 and LPF 18a, antenna 19 and antenna 19a, the mixer 20 and the mixer 20a, and the BPF 21 and the BPF 21a correspond to each other.
  • the VGA 22 is a VGA that is provided in front of the ECC 14 and adjusts the power level of the signal input to the ECC 14 by changing the gain.
  • the VGA 23 is a VGA that is provided at the subsequent stage of the ECC 14 and adjusts the power level of the signal output from the ECC 14 by changing the gain.
  • the TS 24 a is a temperature sensor that monitors the temperature of the RF module 9.
  • the TS 24a is connected to the control unit 25a and transmits temperature information to the control unit 25a.
  • the control unit 25 a is a control unit that controls the bias voltages of the VGAs 22 and 23, the ECC 14, and the amplifier 15.
  • the control unit 25a receives temperature information from the TS 24a, and controls the gains of the VGAs 22 and 23, the ECC 14, and the amplifier 15 by changing the bias voltage according to the temperature information.
  • the RF module 9 has different characteristics depending on the temperature, as shown in FIG. 9, the modulation signal generated by the signal comparison unit 4 is compared with the modulated signal fed back, and predistortion is performed by the PD 6 so that the two match.
  • the characteristic variation due to temperature is compensated for distortion by feedback control.
  • the characteristic of the RF module 9 is not the gain expansion characteristic, the quantization noise increases in the DAC 7 and the noise floor increases. Therefore, it is necessary to perform control so that the RF module 9 has a gain expansion characteristic even when a temperature change occurs.
  • the current flowing through the ECC 14 becomes small, so that the characteristic that the gain increases with respect to the input power (gain expansion characteristic) becomes small. Further, the gain of the amplifier 15 and the saturated output power are also reduced, and the amplifier 15 has a characteristic that the gain is reduced with respect to the input power.
  • the temperature is detected by the TS 24a, and the bias voltage or bias current of the ECC 14 and the ECC 15 is adjusted so that the AM-AM characteristic of the RF module 9 becomes the gain expansion characteristic according to the temperature. Thereby, even if temperature changes, the RF module 9 can maintain a gain expansion characteristic.
  • FIG. 10 is a characteristic diagram showing characteristics of the RF module 9 with and without temperature compensation according to Embodiment 2 of the present invention.
  • the broken line is the characteristic of the RF module 9 when the ECC 14 and the bias voltage of the amplifier 15 are not controlled with respect to the temperature
  • the solid line is the characteristic of the RF module 9 when the bias voltage of the ECC 14 and the amplifier 15 is controlled with respect to the temperature. It is a characteristic.
  • a dotted line is a characteristic of the RF module 9 when the gain characteristic is flat, and is a characteristic to be compared with a solid line and a broken line.
  • a characteristic in which the gain is higher than this characteristic is a gain expansion characteristic.
  • the control unit 25a also controls the gains of the VGAs 22 and 23 according to the temperature so that the overall gain of the RF module 9 becomes constant regardless of the temperature. As a result, even if the temperature changes, the overall gain of the RF module 9 can be maintained and the gain expansion characteristic can be maintained.
  • the gain of the ECC 14 and the amplifier 15 is controlled so that the RF module 9 maintains the gain expansion characteristic even when the temperature changes. An increase in noise can be suppressed.
  • FIG. 11 is a block diagram showing another configuration example of the transmitter according to the second embodiment of the present invention. 9 and 11 are compared, the modem 1 and the modem 1a, the DSP 2 and the DSP 2a, the modulation unit 3 and the modulation unit 3a, the signal comparison unit 4 and the signal comparison units 4a and 4b, the PD signal generation unit 5 and the PD signal generation unit.
  • FIG. 11 shows a configuration in which a plurality of RF modules 9a shown in FIG. 9 are arranged, the DSP 2a is shared by the plurality of RF modules, and a transmitter configuration of Massive-Input MIMO (Multiple-Input and Multi-Output) is used. Even with this configuration, the same effects as those of the second embodiment are obtained.
  • FIG. 11 shows an example in which two RF modules are provided, but two or more RF modules may be provided.
  • FIG. 12 is a block diagram showing another configuration example of the transmitter according to Embodiment 2 of the present invention. 12, the same reference numerals as those in FIG. 9 indicate the same or corresponding parts, and thus the description thereof is omitted. Further, for example, the components having the same numbers correspond to each other like the amplifier 15a and the amplifier 15b, and thus the description thereof is omitted. Further, the RF module 9a in FIG. 9 corresponds to the RF modules 90a, 90b, 90c, and 90d in FIG. 9 is compared with FIG. 11, in the configuration of the RF module 90a of FIG. 12, the phase shifter 28a is provided in the front stage of the amplifier 15, and the phase shifter 29a is provided in the front stage of the mixer 20a.
  • a DIV 26 and a Com 27 are provided between the modem 1 and the RF modules 90a, 90b, 90c, and 90d.
  • the DIV 26 is a distribution circuit that distributes the output signal of the modem 1 to the RF modules 90a, 90b, 90c, and 90d.
  • Com 27 is a combining circuit that combines the output signals of the RF modules 90 a, 90 b, 90 c, and 90 d and outputs the combined signals to the modem 1.
  • FIG. 12 shows an active phased array transmitter having an analog subarray configuration in which a plurality of RF modules of FIG. 9 are arranged. The signal is distributed to each RF module by the DIV 26, and the signal fed back is synthesized by the Com 27.
  • a phase shifter 28a is inserted into the RF module 90a.
  • the phase shifter 29a is a phase shifter for returning the phase changed by the phase shifter 28a when performing distortion compensation. Even with this configuration, the same effects as those of the second embodiment are obtained.
  • the phase shifters 29a, 29b, 29c, and 29d return the phase even when the phases of the phase shifters 28a, 28b, 28c, and 28d are changed and the transmission beam is shaken.
  • the feedback signals 91a, 91b, 91c, and 91d can be in phase.
  • the feedback signal having the same phase is synthesized by Com27 and predistortion is performed using the synthesized signal. Therefore, even if the direction of the transmission beam is changed, the distortion is low with respect to the front direction of the transmission beam.
  • a signal can be output.
  • the local sources 12a, 12b, 12c, and 12d there are two methods for bringing the local sources 12a, 12b, 12c, and 12d into the same phase in order to make the feedback signal in the same phase.
  • One is to make the local sources 12a, 12b, 12c, and 12d in phase by synchronizing reference signals (reference signals) that drive the local sources.
  • the local sources 12a, 12b are controlled by controlling and correcting the load enable signal for controlling the rising of the local sources 12a, 12b, 12c, 12d.
  • 12c, 12d are in phase.
  • FIG. 13 is a block diagram showing another configuration example of the transmitter according to Embodiment 2 of the present invention.
  • FIG. 13 is a modification of FIG. 12, in which the ECC of each RF module is unified.
  • the same reference numerals as those in FIG. since the components with the same number correspond to each other, the description thereof is omitted.
  • the RF modules 90a, 90b, 90c, and 90d correspond to the RF modules 91a, 91b, 91c, and 91d, respectively.
  • the ECC module 30 is shared by the RF modules 91a, 91b, 91c, and 91d.
  • the ECC module 30 includes a VGA 22, a VGA 23, an ECC 14, a DIV 26, a COM 27, and a control unit 31.
  • the control unit 31 controls the VGA 22 so that the input power entering the ECC 14 becomes the same even when the temperature changes, and the average gain from the ECC 14 to the input ends of the amplifiers 15a, 15b, 15c, and 15d is constant.
  • the VGA 23 is controlled so that Even with this configuration, the same effects as those of the second embodiment are obtained.

Abstract

Selon la présente invention, un émetteur classique présente un problème d'augmentation du bruit de quantification au niveau d'un convertisseur numérique-analogique (CNA) lorsqu'un signal d'émission est à large bande. Un émetteur selon la présente invention comporte : un circuit numérique qui génère un signal d'émission numérique ; un convertisseur numérique-analogique qui convertit un signal d'émission prédistordu en un signal analogique ; un amplificateur qui amplifie le signal d'émission analogique délivré par le convertisseur numérique-analogique ; un circuit de génération d'expansion qui est disposé entre le convertisseur numérique-analogique et l'amplificateur, et qui change, et délivre à l'amplificateur, l'amplitude du signal d'émission analogique délivré par le convertisseur numérique-analogique de manière qu'une caractéristique AM-AM établie pour correspondre à l'amplificateur devienne une caractéristique d'expansion de gain ; et un circuit de compensation de distorsion qui est disposé entre le circuit numérique et le convertisseur numérique-analogique, et qui effectue une prédistorsion du signal d'émission amplifié par l'amplificateur de manière à compenser la distorsion du signal d'émission, et délivre le signal d'émission prédistordu au convertisseur numérique-analogique.
PCT/JP2016/067756 2016-06-15 2016-06-15 Émetteur WO2017216894A1 (fr)

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Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2002009555A (ja) * 2000-06-16 2002-01-11 Toshiba Corp 増幅装置およびプリディストータ
JP2003037451A (ja) * 2001-06-08 2003-02-07 Trw Inc マイクロ波増幅器を線形化するためのプリディストーション回路としてのドハーティ増幅器の応用
JP2008277908A (ja) * 2007-04-25 2008-11-13 Mitsubishi Electric Corp デジタルプレディストータ
JP2012044297A (ja) * 2010-08-16 2012-03-01 Nec Corp Ａｍ−ａｍ歪発生器、ａｍ−ｐｍ歪発生器、歪発生器、ａｍ−ａｍ歪発生方法および歪発生方法
JP2015061204A (ja) * 2013-09-19 2015-03-30 三菱電機株式会社 歪補償回路および歪補償方法
JP2015099972A (ja) * 2013-11-18 2015-05-28 三菱電機株式会社 送信機モジュール

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2002009555A (ja) * 2000-06-16 2002-01-11 Toshiba Corp 増幅装置およびプリディストータ
JP2003037451A (ja) * 2001-06-08 2003-02-07 Trw Inc マイクロ波増幅器を線形化するためのプリディストーション回路としてのドハーティ増幅器の応用
JP2008277908A (ja) * 2007-04-25 2008-11-13 Mitsubishi Electric Corp デジタルプレディストータ
JP2012044297A (ja) * 2010-08-16 2012-03-01 Nec Corp Ａｍ−ａｍ歪発生器、ａｍ−ｐｍ歪発生器、歪発生器、ａｍ−ａｍ歪発生方法および歪発生方法
JP2015061204A (ja) * 2013-09-19 2015-03-30 三菱電機株式会社 歪補償回路および歪補償方法
JP2015099972A (ja) * 2013-11-18 2015-05-28 三菱電機株式会社 送信機モジュール

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