WO2017128678A1 - 基于容性负载的超宽带定值移相器 - Google Patents

基于容性负载的超宽带定值移相器 Download PDF

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Publication number
WO2017128678A1
WO2017128678A1 PCT/CN2016/093395 CN2016093395W WO2017128678A1 WO 2017128678 A1 WO2017128678 A1 WO 2017128678A1 CN 2016093395 W CN2016093395 W CN 2016093395W WO 2017128678 A1 WO2017128678 A1 WO 2017128678A1
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Prior art keywords
coupler
spiral
capacitive load
phase shifter
wideband
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PCT/CN2016/093395
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English (en)
French (fr)
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盖川
夏冬
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南京米乐为微电子科技有限公司
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Priority to RU2017134113A priority Critical patent/RU2676192C1/ru
Priority to US15/511,713 priority patent/US10249923B2/en
Publication of WO2017128678A1 publication Critical patent/WO2017128678A1/zh

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/18—Phase-shifters
    • H01P1/185—Phase-shifters using a diode or a gas filled discharge tube
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/18—Phase-shifters
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/18—Phase-shifters
    • H01P1/182—Waveguide phase-shifters
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/18—Phase-shifters
    • H01P1/184—Strip line phase-shifters
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
    • H03H7/01—Frequency selective two-port networks
    • H03H7/17—Structural details of sub-circuits of frequency selective networks
    • H03H7/1708—Comprising bridging elements, i.e. elements in a series path without own reference to ground and spanning branching nodes of another series path
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
    • H03H7/18—Networks for phase shifting
    • H03H7/185—Networks for phase shifting comprising distributed impedance elements together with lumped impedance elements
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
    • H03H7/18—Networks for phase shifting
    • H03H7/19—Two-port phase shifters providing a predetermined phase shift, e.g. "all-pass" filters
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
    • H03H7/18—Networks for phase shifting
    • H03H7/20—Two-port phase shifters providing an adjustable phase shift
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
    • H03H7/18—Networks for phase shifting
    • H03H7/21—Networks for phase shifting providing two or more phase shifted output signals, e.g. n-phase output
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/12—Coupling devices having more than two ports
    • H01P5/16—Conjugate devices, i.e. devices having at least one port decoupled from one other port
    • H01P5/18—Conjugate devices, i.e. devices having at least one port decoupled from one other port consisting of two coupled guides, e.g. directional couplers
    • H01P5/184—Conjugate devices, i.e. devices having at least one port decoupled from one other port consisting of two coupled guides, e.g. directional couplers the guides being strip lines or microstrips

Definitions

  • the invention relates to a phase shifter, in particular to an ultra-wideband fixed value phase shifter.
  • phase shifter As a key component of beam steering, phase shifter has been one of the key components in the antenna transceiver module due to its large working state and technical indicators, large occupied area, high performance requirements, and difficult design and fabrication.
  • the development of phased array radar puts forward higher requirements on the bandwidth, phase shift accuracy and integrated area of phase shifters. Therefore, the research on broadband and ultra-wideband high performance phase shifters is of great significance and practical application value. .
  • phase shifter when the phase shifter is actually applied in the communication system, there are often some non-ideal factors.
  • an actual multi-channel system such as a phased array
  • the phases are not uniform in each channel, and there are some differences. . Therefore, it is very necessary to develop a broadband fixed-value phase shifter that is easy to debug in the system and can correct the phase of the wideband system.
  • the present patent provides an ultra-wideband fixed value phase shifter based on a capacitive load.
  • the capacitive load-based ultra-wideband fixed value phase shifter provided by the present invention:
  • the N-channel phase shifting unit including the physical separation realizes the N-1 phase shifting state by accessing the signal input end and the signal output end of the different phase shifting units.
  • Each phase shifting unit includes a quadrature coupler, first and second transmission lines, and first and second capacitive loads, wherein the orthogonal coupler includes an input end, a coupling end, a through end, and an isolated end, One end of the first transmission line serves as a signal input end of the phase shifting unit, and the other end is connected to an input end of the quadrature coupler, and one end of the second transmission line serves as a signal output end of the phase shifting unit, and the other end is orthogonal
  • the isolated end of the coupler is connected; one end of the first capacitive load is connected to the coupled end of the orthogonal coupler, and the other end is grounded; one end of the second capacitive load is connected to the through end of the orthogonal coupler, and the other end is grounded.
  • the first and second capacitive loads respectively connected to the orthogonal coupler coupling end and the through end of each phase shifting unit are pure capacitive elements.
  • the first and second passes respectively connected to the orthogonal coupler input and the isolated end
  • the characteristic impedance of the transmission line is 50 ohms.
  • the same orthogonal coupler is used in the N-channel phase shifting unit.
  • the orthogonal coupler is an ultra-wideband quadrature coupler that is cascaded by a spiral inductive coupling unit; each of the spiral inductive coupling units includes two spiral inductors coupled to each other; two adjacent spirals The inductive coupling unit realizes the cascade of the front and rear stages by connecting two spiral inductors of the previous stage and one of the two spiral inductors of the latter stage respectively;
  • One end of one of the first-stage spiral inductive coupling units connected in cascade in the coupler is a coupling end of the coupler, and the other end of the spiral inductor is an input end of the coupler;
  • the coupling One end of the spiral inductive coupling unit in the last stage of the spiral inductor is located at the outer end of the coupler, and the other end of the spiral inductor is the isolated end of the coupler;
  • the coupling pitch or microstrip line width of each spiral inductive coupling unit in the external to internal coupler is gradually decreased.
  • the spiral inductive coupling unit is coupled to each other by two spiral inductors in the same layer of metal and by marginal coupling, or the spiral inductive coupling unit is located in different layers of metal through its two spiral inductors, and the combined margin The coupling and the upper and lower layers are coupled to each other.
  • two of the spiral inductive coupling units are connected across the same side of the port with a jumper capacitor, and both ends of the jumper capacitor are grounded through a grounding capacitor.
  • the circuit structure of the coupler is bilaterally symmetric, vertically symmetrical, and both are lumped elements.
  • the capacitive load-based ultra-wideband constant value phase shifter provided by the present invention has the following advantages:
  • each phase shifting unit circuit after the orthogonal coupler circuit design is completed, by adjusting the capacitance values of the first and second capacitive loads, by adjusting the electrical lengths of the first and second transmission lines, Obtaining different phase shift values greatly simplifies the design of the phase shifter. Further, the present invention can employ the same orthogonal coupler as the core circuit of the phase shifter, further simplifying the design of the phase shifter.
  • the capacitive load does not deteriorate the bandwidth of the phase shifter. That is, the operating bandwidth of the phase shifter is mainly determined by the operating bandwidth of the quadrature coupler.
  • phase shifting unit circuit 4 It includes multiple phase shifting unit circuits, no power supply and logic control circuit are required, and different phase shifting unit circuits can be selected to correct the phase in the system channel, which is very easy to use in system debugging.
  • an ultra-wideband quadrature coupler composed of a spiral coupling inductor cascade is used in the phase shifting unit circuit to maintain good phase flatness in the bandwidth range of the quadrature coupler, and is more excellent. Ultra-wideband phase shifting performance.
  • the capacitive load-based ultra-wideband fixed value phase shifter provided by the invention has the advantages of compact structure, simple design method, small insertion loss, no additional power supply and logic control, and can be widely applied to the broadband active phase.
  • FIG. 1 is a schematic block diagram showing the principle of a capacitive load-based ultra-wideband fixed value phase shifter provided by the present invention
  • FIG. 2 is a schematic diagram showing phase shift simulation results of 30 degree, 45 degree, and 60 degree phase shifts of an ultra-wideband fixed value phase shifter composed of four ideal components as exemplified in Embodiment 1;
  • FIG. 3 is a schematic block diagram showing the structure of a 4-way ultra-wideband constant value phase shifter provided in Embodiment 2;
  • Embodiment 4 is a phase shift test result of a 4-channel ultra-wideband fixed value phase shifter provided by Embodiment 2, which provides phase shifts of 20 degrees, 40 degrees, and 60 degrees;
  • Embodiment 5 is a 4-channel ultra-wideband fixed value phase shifter provided by Embodiment 2, which provides phase shift error test results under phase shifts of 20 degrees, 40 degrees, and 60 degrees;
  • the ultra-wideband fixed value phase shifter based on capacitive load provided by the invention can realize a wider working bandwidth with a small circuit area and has good phase shifting smoothness.
  • the capacitive load-based ultra-wideband fixed value phase shifter provided by the present invention comprises an N-channel phase shifting unit, which is physically separated and connected to different phase shifting units.
  • the signal input end and the signal output end, physically switching different phase shifting units, can realize N-1 kinds of phase shifting states, wherein.
  • the method includes a quadrature coupler N, a first transmission line, a second transmission line, and a first capacitive load and a second capacitive load
  • the orthogonal coupler includes an input C a coupling end A, a straight end B and an isolated end D
  • one end of the first transmission line is used as a signal input end of the phase shifting unit, and is used for receiving an input signal as an input N and an input end of the orthogonal coupler as an input end C is connected
  • one end of the second transmission line is used as a signal output end of the phase shifting unit, and is used to output an output signal as an output N, and the other end is connected to the isolated end D of the orthogonal coupler
  • one end of the first capacitive load is The coupled end of the quadrature coupler is connected, and the other end is grounded
  • one end of the second capacitive load is connected to the through end B of the quadrature coupler, and the other end is grounded.
  • the same orthogonal coupler can be used in each of the above phase shifting units.
  • FIG. 1 is a schematic diagram showing the principle of an ultra-wideband fixed value phase shifter including an N-channel phase shifting unit provided by the present invention, wherein the present embodiment provides a principle simulation of an ultra-wideband fixed value phase shifter based on a capacitive load:
  • the orthogonal coupler used in the simulation has an ideal response at any frequency, that is, the amplitude of the output end and the coupled end are equal, and the phase difference is 90. Degree; the isolation port is completely isolated.
  • the capacitive load uses an ideal capacitive element (infinite quality factor), and the transmission line is an ideal transmission line with a characteristic impedance of 50 ohms.
  • Table 1 The specific circuit parameters are shown in Table 1.
  • phase shift characteristics of the above four-way ideal-valued phase shifters are shown in Fig. 2.
  • the orthogonal coupler used in the present invention can be implemented in various ways, such as a branch line coupler, a direct coupler based on a distributed coupled transmission line, or a lumped unit that implements a distributed effect through a lumped element. Coupler, etc.
  • the second embodiment provides an ultra-wideband fixed value phase shifter based on a capacitive load.
  • the structure of the phase shifting unit is the same as the above description of the structure, and the orthogonal coupler used is coupled by a spiral inductive coupling.
  • the cells are cascaded into an ultra-wideband quadrature coupler.
  • the quadrature coupler has the advantages of miniaturization, low insertion loss and high isolation.
  • FIG. 3 is a schematic block diagram showing the structure of an ultra-wideband fixed value phase shifter including a 4-channel phase shifting unit circuit provided in the second embodiment, and the ultra-wideband fixed value shift based on the capacitive load provided in the second embodiment.
  • the phaser can realize three phase shifting states.
  • the structures of the corresponding 4-channel phase shifting units are the same as those of the phase shifting unit structure described above, and are not described again.
  • the ultra-wideband quadrature coupler used in the second embodiment is implemented by a lumped element such as an inductive coupling unit circuit and a coupling capacitor to reduce the circuit size; to increase the operating bandwidth of the quadrature coupler,
  • the ultra-wideband quadrature coupler is formed by cascading multi-stage spiral inductive coupling units, and each stage of the spiral inductive coupling unit includes two spiral inductors coupled to each other; in the second embodiment, in order to increase the operation of the orthogonal coupler Bandwidth, the ultra-wideband quadrature coupler in each phase shifting unit is formed by cascading four spiral inductive coupling units, and the embodiment is taken as an example to introduce the present invention.
  • each spiral inductive coupling unit circuit has the same structural form, and the first-stage spiral inductive coupling unit of the wideband coupler 1 in the first phase shifting unit is selected as an example to illustrate, including mutual coupling in the circuit of the stage.
  • the first spiral inductor L 11 and the second spiral inductor L 12 , the first and second inductors are connected across the port on the left side with a jumper capacitor C 0 , and the first and second inductors are located on the right side of the port.
  • a jumper capacitor C 2 is connected across the capacitor, and the two ends of the jumper capacitor C 0 are respectively grounded through the grounding capacitors C 01 and C 02 , and the two ends of the jumper capacitor C 2 pass through the grounding capacitors C 21 and C respectively.
  • the upper and lower two tightly coupled spiral inductors provide inductive coupling, in which the two spiral inductors are located in the same layer of metal and are coupled with each other by marginal coupling, or the spiral inductive coupling unit passes through two spirals
  • the inductors are located in different layers of metal, coupled with the marginal coupling and the upper and lower layers to achieve mutual coupling.
  • the four grounding capacitors C 01 , C 02 , C 21 , C 22 and the jump capacitors C 0 and C 2 between the two spiral inductors are used to provide a suitable even-mode impedance to achieve the coupling function.
  • the spiral inductive coupling units of the stages are connected by the left port of the rear stage unit and the right side port of the front stage unit to realize multi-level cascade.
  • the adjacent two-stage spiral inductive coupling unit realizes the cascade connection of the front and rear stages by connecting two spiral inductors of the previous stage in series with one of the two spiral inductors of the latter stage.
  • the spiral inductive coupling units of adjacent stages are connected in series by the first spiral inductor of the previous stage, and the first spiral inductor of the first stage and the second spiral of the previous stage are connected in series to the second spiral of the first stage.
  • the inductor realizes the cascade of the front and rear stages, or the spiral inductive coupling unit of the adjacent stage is connected in series with the first spiral inductor of the previous stage, and the second spiral inductor of the first stage and the second spiral inductor of the previous stage are connected in series.
  • the first spiral inductor of the stage realizes front and rear cascade.
  • the front and rear stages of the spiral inductive coupling unit circuit combine and share the grounding capacitance of the jump capacitor and both ends thereof.
  • One end of one of the first-stage spiral inductive coupling units connected in cascade in the coupler is a coupling end of the coupler, and the other end of the spiral inductor is an input end of the coupler;
  • the coupling One end of the spiral inductive coupling unit in the last stage of the spiral inductor is located at the outer end of the coupler is the through end of the coupler, and the other end of the spiral inductor is located at the opposite end of the coupler; specifically, the coupling in this embodiment
  • the upper left and lower left ports of the inductive coupling unit of the first stage are the coupling end A and the input end C of the coupler respectively;
  • the upper right port and the lower right port of the inductive coupling unit located in the last stage are the throughs of the coupler respectively. End B and isolation End D.
  • the two spiral inductive coupling units located outside the coupler in the present embodiment that is, the two spiral inductors coupled to each other in the first-stage and fourth-stage spiral inductive coupling units have a larger pitch and a smaller coupling coefficient.
  • the coupling pitch of each spiral inductive coupling unit from the external to the internal coupler is gradually reduced, and the coupling coefficient is externally to internally gradual, thereby realizing the ultra-wideband coupling of the coupler.
  • the UWB quadrature coupler is formed by cascading multi-stage spiral inductive coupling units of level 2 or higher, such as level 2, level 3, level 4, level 5, level 6, level 7
  • the coupling coefficient of the spiral inductive coupling units of each stage can be gradually adjusted by the coupling pitch or the microstrip line width of the two spiral inductors that are mutually coupled to each other, and the ultra-wideband provided by the present invention is further The coupling pitch or microstrip line width of each of the spiral inductive coupling units in the cross coupler from the outside to the internal coupler is gradually decreased.
  • the coupling distance and the capacitance value of each spiral inductive coupling unit are optimized by electromagnetic simulation, and the required ultra-wide operating frequency band can be obtained.
  • the RF/microwave signal output from the through-end and the coupled-end is the same as the input signal, achieving a 3dB power equalization.
  • the output signals of the through port and the coupled port are 90 degrees apart, and a structure for converting between the single-ended signal and the orthogonal signal is realized.
  • the first capacitive load and the second capacitive load in the ultra-wideband fixed value phase shifter are respectively connected to the coupled end A and the through end B of the coupler, as shown in FIG.
  • the use of pure capacitive components as the load of the coupler through port and the coupling port avoids the use of inductor elements with lower quality factor, saves chip size and reduces chip loss; not only that, pure capacitive components act as loads
  • the bandwidth of the phase shifter is not degraded, ie the bandwidth of the phase shifter is completely dependent on the bandwidth of the quadrature coupler.
  • the traditional LC series-parallel load on the one hand, is large in size and high in loss.
  • the selection of the value of the inductance and capacitance may be difficult to achieve or easily limit the working bandwidth of the phase shifter.
  • the first transmission line and the second transmission line in the ultra-wideband constant value phase shifter are respectively connected to the input terminal C and the isolation terminal D of the coupler, as shown in FIG.
  • the functions of the first and second transmission lines are mainly as follows: 1). Selecting the capacitance value of the capacitive load to adjust the phase of the input port and the output port of the phase shifter together; 2) the transmission line can reduce the number of the transmission line
  • the input (or output) of the multiple phase shifting unit circuits is separated by a distance, so that the input end (or output) of the phase shifter is more compact, which is convenient for the bonding in actual use.
  • the present invention can select the capacitive load capacitance value and the transmission line electrical length in each phase shifting unit circuit according to actual needs.
  • the transmission line in the phase shifting unit circuit is implemented by a 50 ohm microstrip line, and the characteristic impedances of the first and second transmission lines are 50. Ohmic; the capacitive loads in the phase shifting unit circuit are all implemented with MMIC capacitors.
  • the parameters in the reference phase shifting unit circuit 1 are first determined.
  • the parameters are symmetrically selected, ie, .
  • the electrical lengths of the first and second transmission lines in the reference channel 1 can be arbitrarily selected.
  • the selection of the capacitive capacitance value needs to take into account the following problems: 1).
  • the capacitive capacitance value is relatively small; 2).
  • the too small capacitance value will cause the phase reference deviation of the reference path to be large due to the influence of the machining error.
  • the capacitive load capacitance value of the reference path 1 can be arbitrarily selected.
  • the parameters in the non-reference phase shifting unit circuit N are determined; for the phase between the non-reference path phase shifting unit and the reference path phase shifting unit, obtained by increasing the capacitance value and the electrical length, the optimum value requires simulation optimization.
  • the performance of the capacitive load-based ultra-wideband fixed value phase shifter provided in the required operating bandwidth of 6-18 GHz is shown in Figures 4-7 by using the ultra-wideband quadrature coupler.
  • the 4-way ultra-wideband fixed value phase shifter exemplified in the above embodiment 2 can provide three kinds of phase shifting states, which are 20 degrees, 40 degrees, and 60 degrees, respectively.
  • the ultra-wideband fixed value phase shifter has small variation in the phase shift error and high precision.
  • the insertion loss of the 4-channel phase shifting unit is less than 3.5 dB in the wide band of 6-18 GHz, which is smaller than the loss of the digital phase shifter.
  • the ultra-wideband constant value phase shifter has excellent return loss characteristics.
  • phase shifting states can be obtained by changing the electrical length of the transmission line and the load capacitance value, and the design is convenient, the phase shifting performance is superior, and good amplitude uniformity can be achieved; and the orthogonal coupling of the N-channel phase shifting unit
  • the device can be of identical design to simplify the design; further phase shifting unit circuits with the UWB quadrature coupler formed by the spiral coupled inductor cascade provided by the present invention can make the bandwidth of the quadrature coupler Maintaining good phase flatness in the range, and obtaining superior ultra-wideband phase shifting performance, it has the advantages of miniaturization, low insertion loss and high isolation.
  • the fixed value phase shifter can also be used as a standard digital phase shifting circuit if the input and output respectively match the related single-pole N-throw switch selection circuit, and has the advantages of simple design, accurate phase shifting and high additional amplitude consistency.

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Abstract

本发明公开了一种基于容性负载的超宽带定值移相器，包括物理分离的N路移相单元，每路移相单元中，包括正交耦合器、第一和第二传输线，以及第一和第二容性负载，其中所述正交耦合器包括输入端、耦合端、直通端和隔离端，所述第一传输线的一端作为该移相单元的信号输入端，另一端与正交耦合器的输入端连接，所述第二传输线一端作为该移相单元的信号输出端，另一端与正交耦合器的隔离端连接；第一容性负载的一端与正交耦合器的耦合端连接，另一端接地；第二容性负载的一端与正交耦合器的直通端连接，另一端接地。其结构紧凑，占用面积小，插入损耗小，不需额外的供电及逻辑控制，可广泛推广应用。

Description

基于容性负载的超宽带定值移相器 技术领域
本发明涉及一种移相器，具体涉及一种超宽带定值移相器。
背景技术
随着宽带有源相控阵雷达的不断发展，人们对天线波束控制的需求不断提高，对控制电路的研究也更加深入。
移相器作为波束控制的关键器件，由于其工作状态及技术指标较多，占用面积大，性能要求高，设计和制作难度大，一直是天线收发组件中关键的器件之一。相控阵雷达的发展对移相器的带宽，移相精度和集成面积等方面提出了更高的要求，因此，对宽带以及超宽带高性能移相器的研究具有重要的意义及实际应用价值。
然后，在通信系统中实际应用移相器时，往往存在一些非理想的因素。例如，在实际的多通道系统(例如相控阵)中，由于布板时通路传输线长度差异、键合金丝长度差异、芯片本身相位特性的差异性，导致各个通道中相位并不一致，存在一定差异。因此十分有必要研究出一种易于系统调试，能够校正宽带系统相位的宽带定值移相器。
发明内容
发明目的：为了解决现有技术中的不足，本专利提供一种基于容性负载的超宽带定值移相器。
技术方案：为解决上述技术问题，本发明提供的基于容性负载的超宽带定值移相器：
包括物理分离的N路移相单元，通过接入不同移相单元的信号输入端与信号输出端，实现N-1种移相状态。
每路移相单元中，包括正交耦合器、第一和第二传输线，以及第一和第二容性负载，其中所述正交耦合器包括输入端、耦合端、直通端和隔离端，所述第一传输线的一端作为该移相单元的信号输入端，另一端与正交耦合器的输入端连接，所述第二传输线一端作为该移相单元的信号输出端，另一端与正交耦合器的隔离端连接；第一容性负载的一端与正交耦合器的耦合端连接，另一端接地；第二容性负载的一端与正交耦合器的直通端连接，另一端接地。
优选的，所述各移相单元中分别与正交耦合器耦合端和直通端连接的第一和第二容性负载为纯电容元件。优选的，分别与正交耦合器输入端和隔离端连接的第一和第二传 输线的特性阻抗均为50欧姆。
优选的，所述N路移相单元中采用完全相同的正交耦合器。
进一步优选的，所述正交耦合器为由螺旋形电感耦合单元级联而成超宽带正交耦合器；每级螺旋形电感耦合单元包括相互耦合的两个螺旋电感；相邻两级的螺旋形电感耦合单元通过前一级的两个螺旋电感分别与后一级的两个螺旋电感之一串联实现前后级级联；
该耦合器中级联连接的第一级螺旋形电感耦合单元中的其中一螺旋电感位于外侧的一端为耦合器的耦合端，另一螺旋电感位于外侧的一端为耦合器的输入端；该耦合器中最后一级螺旋形电感耦合单元中的其中一螺旋电感位于外侧的一端为耦合器的直通端，另一螺旋电感位于外侧的一端为耦合器的隔离端；
从外部到内部耦合器中各螺旋形电感耦合单元的耦合间距或微带线宽逐渐递减。
进一步优选的，所述螺旋形电感耦合单元通过其两个螺旋电感位于同层金属并采用边际耦合实现相互耦合，或所述螺旋形电感耦合单元通过其两个螺旋电感位于不同层金属，结合边际耦合和上下层耦合实现相互耦合。
作为进一步优选的，所述各螺旋形电感耦合单元中的两个螺旋电感位于同一侧的端口之间跨接有跨接电容，所述跨接电容的两端分别通过接地电容接地。
作为优选的，所述耦合器的电路结构左右对称，上下对称，且均为集总元件。
有益效果：本发明提供的基于容性负载的超宽带定值移相器，其具有如下优点：
1、容性负载的使用，避免了传统电容电感串/并联形式的负载中的大尺寸螺旋电感的使用，减小了电路尺寸，降低成本；另一方面，避免引入传统结构中螺旋电感的额外损耗，使得移相器整体插入损耗更小。
2、每路移相单元电路中，在正交耦合器电路设计完成后，通过调整第一、第二容性负载的容值大小，通过调整第一、第二传输线的电长度大小，即可获得不同的移相值，大大简化移相器的设计。进一步的，本发明可采用完全相同的正交耦合器作为移相器的核心电路，进一步简化移相器的设计。
3、容性负载不会恶化移相器的带宽，即移相器的工作带宽主要由正交耦合器的工作带宽决定。
4、包含多个移相单元电路，不需要供电和逻辑控制电路，选择不同的移相单元电路，即可进行系统通道内相位的校正，非常易于在系统调试中使用。
5、进一步地，移相单元电路中配合采用由螺旋形耦合电感级联构成的超宽带正交耦合器，可以使得在正交耦合器的带宽范围内保持良好的相位平坦度，获得更为优异的超宽带移相性能。
总体而言，本发明提供的基于容性负载的超宽带定值移相器，其结构紧凑，设计方法简单，插入损耗小，不需要额外的供电及逻辑控制，可以广泛应用在宽带有源相控阵雷达系统调试中。
附图说明
图1为本发明提供的基于容性负载的超宽带定值移相器的原理示意框图；
图2为实施例1中举例的4路理想元器件构成的超宽带定值移相器提供30度、45度以及60度相移下的相移仿真结果；
图3为实施例2提供的4路超宽带定值移相器的结构示意框图；
图4为实施例2提供的4路超宽带定值移相器提供20度、40度以及60度相移下的相移测试结果；
图5为实施例2提供的4路超宽带定值移相器提供20度、40度以及60度相移下的相移误差测试结果；
图6为实施例2提供的4路超宽带定值移相器的插入损耗测试结果；
图7为实施例2提供的4路超宽带定值移相器的回波损耗测试结果。
具体实施方式
下面结合实施例和附图对本发明做进一步的详细说明，以下实施例对本发明不构成限定。
本发明提供的基于容性负载的超宽带定值移相器，可以用较小的电路面积实现较宽的工作带宽，具有良好的相移平稳度。如图1所示，本发明提供的基于容性负载的超宽带定值移相器，包括N路移相单元，这N路移相单元是物理分离的，且通过接入不同移相单元的信号输入端与信号输出端，物理切换不同的移相单元，可实现N-1种移相状态，其中。以第N路移相单元为例说明，包括正交耦合器N、第一传输线、第二传输线，以及第一容性负载和第二容性负载，其中所述正交耦合器包括输入端C、耦合端A、直通端B和隔离端D，所述第一传输线的一端作为该移相单元的信号输入端，用于作为输入N接收一输入信号，另一端与正交耦合器的输入端C连接，所述第二传输线一端作为该移相单元的信号输出端，用于作为输出N输出一输出信号，另一端与正交耦合器的隔离端D连接；第一容性负载的一端与正交耦合器的耦合端A连接，另一端接地；第二容性负载的一端与正交耦合器的直通端B连接，另一端接地。即：正交耦合 器的耦合端通过第一容性负载接地，正交耦合器的直通端通过第二容性负载接地。
上述各路移相单元中可以采用完全相同的正交耦合器。
实施例1：
图1给出了本发明提供的包含N路移相单元的超宽带定值移相器的原理示意图，其中，本实施例提供基于容性负载的超宽带定值移相器的原理仿真：
以时的包括四路移相单元的超宽带定值移相器为例来仿真，仿真所采用的正交耦合器其任意频率都为理想响应，即输出端和耦合端幅度相等，相位差90度；隔离端口完全隔离。容性负载采用理想电容元件(品质因数无限大)，传输线是特征阻抗50欧姆的理想传输线。具体电路参数如表1所示。
表1四路理想定值移相器电路参数(电容:pF,电长度:deg@30GHz)
               
0.3 0.3 0 0 0.47 0.47 8.95 8.95
               
0.6 0.6 13.9 13.9 0.79 0.79 19.4 19.4
上述四路理想定值移相器的移相特性仿真结果如图2所示，在频率5-30GHz范围内，实现30度、45度和60度移相。由于采用了理想元器件仿真，因此其传输特性和回波特性都是理想的，及传输系数＝1，驻波系数＝1。通过上述理想元器件的仿真实验，证明了该结构原理上可在6倍频程内实现较小的相移波动。
实施例2：
实际应用中，本发明中采用的正交耦合器的实现方法有很多种，例如分支线耦合器，基于分布式耦合传输线的直接耦合器，或者是将分布式效应通过集总元件实现的集总耦合器等。本实施例2提供了一种基于容性负载的超宽带定值移相器，其移相单元的结构与上述结构描述一致，不再赘述，其采用的正交耦合器为由螺旋形电感耦合单元级联而成超宽带正交耦合器。该正交耦合器具有小型化、低插损及高隔离度的优势。
图3给出了本实施例2提供的以包含4路移相单元电路为例的超宽带定值移相器的结构示意框图，本实施例2提供的基于容性负载的超宽带定值移相器可以实现3种移相状态。分别对应的这4路移相单元的结构与上述移相单元结构描述一致，不再赘述。
如图3所示，本实施例2中采用的超宽带正交耦合器由电感耦合单元电路及耦合电容等集总元件实现，以减小电路尺寸；为增加正交耦合器的工作带宽，该超宽带正交耦合器由多级螺旋形电感耦合单元级联而成，每级螺旋形电感耦合单元包括相互耦合的两个螺旋电感；在本实施例2中，为增加正交耦合器的工作带宽，各路移相单元中的超宽带正交耦合器由4个螺旋形电感耦合单元级联而成，此处以此实施例为例介绍本发明进 一步提供的超宽带正交耦合器的具体实施方式：
如图3所示，各螺旋形电感耦合单元电路结构形式相同，选取第1路移相单元中宽带耦合器1的第1级螺旋形电感耦合单元为例来说明，包括该级电路中相互耦合的第一螺旋电感L11和第二螺旋电感L12，第一、第二电感同位于左侧的端口之间跨接有跨接电容C0，第一、第二电感同位于右侧的端口之间跨接有跨接电容C2，所述跨接电容C0的两端分别通过接地电容C01、C02接地，所述跨接电容C2的两端分别通过接地电容C21、C22接地。上下两个紧耦合的螺旋电感提供电感耦合，在螺旋形电感耦合单元中通过其两个螺旋电感位于同层金属并采用边际耦合实现相互耦合，或所述螺旋形电感耦合单元通过其两个螺旋电感位于不同层金属，结合边际耦合和上下层耦合实现相互耦合。四个接地电容C01、C02、C21、C22以及两个螺旋电感间的跨接电容C0、C2用来提供合适的奇偶模阻抗，共同实现耦合功能。
各级螺旋形电感耦合单元之间通过后级单元的左侧端口和前级单元的右侧端口连接，实现多级级联。相邻两级的螺旋形电感耦合单元通过前一级的两个螺旋电感分别与后一级的两个螺旋电感之一串联实现前后级级联。具体的，相邻级的螺旋形电感耦合单元之间通过前一级的第一螺旋电感串联后一级的第一螺旋电感，及前一级的第二螺旋电感串联后一级的第二螺旋电感实现前后级级联，或相邻级的螺旋形电感耦合单元之间通过前一级的第一螺旋电感串联后一级的第二螺旋电感，及前一级的第二螺旋电感串联后一级的第一螺旋电感实现前后级联。前后级螺旋形电感耦合单元电路之间，合并且共用跨接电容及其两端的接地电容。
为简化电路设计，该正交耦合器电路结构上下对称，左右对称，即：C01＝C02＝C81＝C82；C21＝C22＝C61＝C62；C41＝C42；C0＝C8；C2＝C6；L11＝L12＝L71＝L72；L31＝L32＝L51＝L52；此外，M1、M3、M5、M7分别表示第一、第二、第三、第四级螺旋形电感耦合单元中两个紧耦合的螺旋电感的耦合系数，因为电路结构的对称性，所以M1＝M7，M3＝M5。
该耦合器中级联连接的第一级螺旋形电感耦合单元中的其中一螺旋电感位于外侧的一端为耦合器的耦合端，另一螺旋电感位于外侧的一端为耦合器的输入端；该耦合器中最后一级螺旋形电感耦合单元中的其中一螺旋电感位于外侧的一端为耦合器的直通端，另一螺旋电感位于外侧的一端为耦合器的隔离端；具体在本实施例的各耦合器中，位于第一级的电感耦合单元的左上和左下端口分别为耦合器的耦合端A和输入端C；位于最后一级的电感耦合单元的右上端口和右下端口分别为耦合器的直通端B和隔离 端D。
同时，本例耦合器中位于外部的两个螺旋形电感耦合单元，即第1级和第4级螺旋形电感耦合单元中相互耦合的两个螺旋电感的间距较大，耦合系数较小，而相对位于中心内部的两个螺旋形电感耦合单元，即第2级和第3级螺旋形电感耦合单元中相互耦合的两个螺旋电感的间距较小，实现紧密耦合，耦合系数较大，从而有M1＝M7<M3＝M5。这种耦合器结构，从外部到内部耦合器中各螺旋形电感耦合单元的耦合间距逐渐递减，实现了耦合系数由外部到内部的渐变，从而实现耦合器的超宽带耦合。
当然，上述实施例仅仅为本发明的举例，本发明中基于容性负载的超宽带定值移相器中可以采用各种形式的正交耦合器，当采用本发明进一步提供的超宽带正交耦合器时，根据实际需要，该超宽带正交耦合器由2级以上的多级螺旋形电感耦合单元级联而成，如2级、3级、4级、5级、6级、7级甚至更多，从外部到内部，各级螺旋形电感耦合单元的耦合系数可通过各自相互耦合的两个螺旋电感的耦合间距或微带线宽实现渐变可调，本发明进一步提供的超宽带正交耦合器中从外部到内部耦合器中各螺旋形电感耦合单元的耦合间距或微带线宽逐渐递减。
在本发明提供的结构基础上，设置参考阻抗阻抗均为50欧姆的前提下，通过电磁仿真优化各螺旋形电感耦合单元的耦合间距以及电容容值，即可获得所需的超宽工作频带，直通端与耦合端输出的射频/微波信号频率与输入信号相同，实现3dB功率等分。相位上，直通端口与耦合端口的输出信号相差90度，实现了单端信号与正交信号之间转化的结构。
当然，上述实施例仅仅为本发明中所提供的超宽带正交耦合器的实施方式举例，以上实施列对本发明不构成限定。
该超宽带定值移相器中的第一容性负载和第二容性负载，分别连接在耦合器的耦合端A与直通端B，如图1所示。采用纯容性元件作为耦合器直通端口和耦合端口的负载，避免了品质因数较低的电感元件的使用，节省芯片尺寸的同时，又降低了芯片的损耗；不仅如此，纯容性元件作为负载不会恶化移相器的带宽，即移相器的带宽完全取决于正交耦合器的带宽。传统的LC串并联的负载，一方面是尺寸大、损耗高，另一方面其电感电容值的选取可能难于实现或者容易限制移相器的工作带宽。
该超宽带定值移相器中的第一传输线和第二传输线，分别连接在耦合器的输入端C与隔离端D，如图1所示。第一、第二传输线的作用主要有：1).配合容性负载的电容值选取，共同调整移相器的输入端口和输出端口的相位；2).传输线可以减小芯片中的 多个移相单元电路输入端(或输出端)相距距离，使得移相器输入端(或输出端)更加紧凑，便于实际使用中键合。
本发明在完成正交耦合器的设计选取后，可根据实际需要进行各个移相单元电路中容性负载电容值以及传输线电长度的选取。以上述实施例2中举例说明的4路移相单元为例来继续举例说明，其移相单元电路中的传输线均采用50欧姆微带线实现，第一和第二传输线的特性阻抗均为50欧姆；移相单元电路中的容性负载均采用MMIC电容实现。通常地，首先确定参考移相单元电路1中的参数。优选的，为简化设计复杂度，对称选取参数，即，。对于参考路1中第一、第二传输线的电长度可以任意选择，此处可令；容性电容值的选取，需要兼顾如下问题：1).对于参考电路，容性电容值相对较小；2).过小的电容值将由于加工误差的影响导致参考路的相位参考偏差较大。在满足上述两个条件下，参考路1的容性负载电容值可以任意选取。随后，确定非参考移相单元电路N中的参数；对于非参考路移相单元与参考路移相单元间的相位，通过增加电容值和电长度获得，最优值需要仿真优化。
通过在片实测，采用超宽带正交耦合器时，本发明提供的基于容性负载的超宽带定值移相器在所需工作带宽6-18GHz内的性能如图4～7所示。如图4所示，上述实施例2中举例的4路超宽带定值移相器能够提供3种移相状态，分别为20度、40度以及60度。如图5所示，该超宽带定值移相器的宽带移相误差变化较小，精度较高。如图6所示，该4路移相单元的插入损耗在6-18GHz宽带范围内小于3.5dB，小于数字移相器的损耗。如图7所示，该超宽带定值移相器的回波损耗特性优良。
本发明中，通过改变传输线电长度和负载电容值即可获得不同的移相状态，设计方便，移相性能优越，可达到良好的幅度一致性；而且所述N路移相单元的正交耦合器可以采用完全相同的设计，以简化设计；进一步的移相单元电路中配合采用本发明提供的由螺旋形耦合电感级联构成的超宽带正交耦合器，可以使得在正交耦合器的带宽范围内保持良好的相位平坦度，获得更为优异的超宽带移相性能，具有小型化、低插损及高隔离度的优势。此外，不同于传统的数控移相器，本设计不需要额外供电及逻辑电路，非常适于批量生产多通道系统时，在调试过程中进行相位校正。同时，该定值移相器如果在输入输出分别匹配相关的单刀N掷的开关选择电路，也可以作为标准数字移相电路使用，具有设计简洁，移相精确，附加幅度一致性高的优点。
以上仅是本发明的优选实施方式，应当指出以上实施列对本发明不构成限定，相关 工作人员在不偏离本发明技术思想的范围内，所进行的多样变化和修改，均落在本发明的保护范围内。

Claims (8)

  1. 一种基于容性负载的超宽带定值移相器，其特征在于：
    包括物理分离的N路移相单元，通过接入不同移相单元的信号输入端与信号输出端，实现N-1种移相状态；
    每路移相单元中，包括正交耦合器、第一和第二传输线，以及第一和第二容性负载，其中所述正交耦合器包括输入端、耦合端、直通端和隔离端，所述第一传输线的一端作为该移相单元的信号输入端，另一端与正交耦合器的输入端连接，所述第二传输线一端作为该移相单元的信号输出端，另一端与正交耦合器的隔离端连接；第一容性负载的一端与正交耦合器的耦合端连接，另一端接地；第二容性负载的一端与正交耦合器的直通端连接，另一端接地。
  2. 根据权利要求1所述的基于容性负载的超宽带定值移相器，其特征在于：所述各移相单元中分别与正交耦合器耦合端和直通端连接的第一和第二容性负载为纯电容元件。
  3. 根据权利要求1所述的基于容性负载的超宽带定值移相器，其特征在于：分别与正交耦合器输入端和隔离端连接的第一和第二传输线的特性阻抗均为50欧姆。
  4. 根据权利要求1所述的基于容性负载的超宽带定值移相器，其特征在于：所述N路移相单元中采用完全相同的正交耦合器。
  5. 根据权利要求1所述的基于容性负载的超宽带定值移相器，其特征在于：所述正交耦合器为由螺旋形电感耦合单元级联而成超宽带正交耦合器；每级螺旋形电感耦合单元包括相互耦合的两个螺旋电感；相邻两级的螺旋形电感耦合单元通过前一级的两个螺旋电感分别与后一级的两个螺旋电感之一串联实现前后级级联；
    该耦合器中级联连接的第一级螺旋形电感耦合单元中的其中一螺旋电感位于外侧的一端为耦合器的耦合端，另一螺旋电感位于外侧的一端为耦合器的输入端；该耦合器中最后一级螺旋形电感耦合单元中的其中一螺旋电感位于外侧的一端为耦合器的直通端，另一螺旋电感位于外侧的一端为耦合器的隔离端；
    从外部到内部耦合器中各螺旋形电感耦合单元的耦合间距或微带线宽逐渐递减。
  6. 根据权利要求5所述的基于容性负载的超宽带定值移相器，其特征在于：所述螺旋形电感耦合单元通过其两个螺旋电感位于同层金属并采用边际耦合实现相互耦合，或所述螺旋形电感耦合单元通过其两个螺旋电感位于不同层金属，结合边际耦合和上下层耦合实现相互耦合。
  7. 根据权利要求5所述的基于容性负载的超宽带定值移相器，其特征在于：所述 各螺旋形电感耦合单元中的两个螺旋电感位于同一侧的端口之间跨接有跨接电容，所述跨接电容的两端分别通过接地电容接地。
  8. 根据权利要求5所述的基于容性负载的超宽带定值移相器，其特征在于：所述耦合器的电路结构左右对称，上下对称，且均为集总元件。
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