WO2016079906A1 - 送信機、信号合成回路および信号合成方法 - Google Patents
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/02—Transmitters
- H04B1/04—Circuits
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
- H03F1/56—Modifications of input or output impedances, not otherwise provided for
- H03F1/565—Modifications of input or output impedances, not otherwise provided for using inductive elements
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
- H03F3/20—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers
- H03F3/21—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers with semiconductor devices only
- H03F3/211—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers with semiconductor devices only using a combination of several amplifiers
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
- H03F3/20—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers
- H03F3/21—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers with semiconductor devices only
- H03F3/217—Class D power amplifiers; Switching amplifiers
- H03F3/2173—Class D power amplifiers; Switching amplifiers of the bridge type
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
- H03F3/20—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers
- H03F3/21—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers with semiconductor devices only
- H03F3/217—Class D power amplifiers; Switching amplifiers
- H03F3/2178—Class D power amplifiers; Switching amplifiers using more than one switch or switching amplifier in parallel or in series
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
- H03F3/20—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers
- H03F3/24—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers of transmitter output stages
- H03F3/245—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers of transmitter output stages with semiconductor devices only
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
- H03F3/60—Amplifiers in which coupling networks have distributed constants, e.g. with waveguide resonators
- H03F3/602—Combinations of several amplifiers
- H03F3/604—Combinations of several amplifiers using FET's
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
- H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
- H03H7/01—Frequency selective two-port networks
- H03H7/0153—Electrical filters; Controlling thereof
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
- H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
- H03H7/01—Frequency selective two-port networks
- H03H7/09—Filters comprising mutual inductance
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
- H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
- H03H7/01—Frequency selective two-port networks
- H03H7/17—Structural details of sub-circuits of frequency selective networks
- H03H7/1741—Comprising typical LC combinations, irrespective of presence and location of additional resistors
- H03H7/175—Series LC in series path
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
- H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
- H03H7/01—Frequency selective two-port networks
- H03H7/17—Structural details of sub-circuits of frequency selective networks
- H03H7/1741—Comprising typical LC combinations, irrespective of presence and location of additional resistors
- H03H7/1775—Parallel LC in shunt or branch path
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
- H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
- H03H7/38—Impedance-matching networks
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/0003—Software-defined radio [SDR] systems, i.e. systems wherein components typically implemented in hardware, e.g. filters or modulators/demodulators, are implented using software, e.g. by involving an AD or DA conversion stage such that at least part of the signal processing is performed in the digital domain
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/02—Transmitters
- H04B1/04—Circuits
- H04B1/0458—Arrangements for matching and coupling between power amplifier and antenna or between amplifying stages
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/02—Transmitters
- H04B1/04—Circuits
- H04B1/0475—Circuits with means for limiting noise, interference or distortion
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/02—Transmitters
- H04B1/04—Circuits
- H04B1/0483—Transmitters with multiple parallel paths
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F2200/00—Indexing scheme relating to amplifiers
- H03F2200/111—Indexing scheme relating to amplifiers the amplifier being a dual or triple band amplifier, e.g. 900 and 1800 MHz, e.g. switched or not switched, simultaneously or not
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F2200/00—Indexing scheme relating to amplifiers
- H03F2200/336—A I/Q, i.e. phase quadrature, modulator or demodulator being used in an amplifying circuit
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F2200/00—Indexing scheme relating to amplifiers
- H03F2200/387—A circuit being added at the output of an amplifier to adapt the output impedance of the amplifier
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/02—Transmitters
- H04B1/04—Circuits
- H04B2001/0408—Circuits with power amplifiers
Definitions
- the present invention relates to a transmitter, a signal synthesis circuit, and a signal synthesis method, and more particularly, to a transmitter, a signal synthesis circuit, and a signal synthesis method that can handle signal synthesis of a plurality of radio frequencies.
- the present invention can be suitably applied, for example, as a transmitter that synthesizes and transmits an output signal after amplifying a multi-bit digital signal including a radio frequency band component by a plurality of switch mode amplifiers.
- the base station of the wireless communication system transmits a signal having a large difference between the average power and the peak power.
- a baseband signal to be transmitted is converted into a digital transmission signal including a radio frequency band component and amplified.
- Transmitters have been studied, and switch mode amplifiers such as class D amplifiers and class S amplifiers have been studied as applied amplifiers.
- the switch mode amplifier assumes a pulse waveform signal as an input signal, and performs power amplification while maintaining the pulse waveform of the input signal.
- the pulse waveform signal amplified in the switch mode amplifier is output from the digital transmitter after removing frequency components other than the band of the desired radio signal.
- CA carrier aggregation
- FIG. 7 is a block diagram showing the overall configuration of the transmitter described in Patent Document 1, and includes a digital baseband signal generation unit 410, a modulation circuit 420, switch mode amplifiers 100-1 and 100-2, signal synthesis.
- the signal synthesis circuit 200 includes a band limiting unit and a voltage / current source conversion unit, as will be described later.
- Non-Patent Document 2 has a signal corresponding to a single transmission frequency or two transmission frequencies.
- a configuration using a plurality of transmission lines as shown in FIGS. 8A and 8B is shown.
- FIG. 8A is a block diagram showing a configuration example in which the voltage-current source conversion unit described in Patent Document 1 is made to correspond to two frequencies
- FIG. 8B is a voltage-current source described in Patent Document 1. It is a block diagram which shows the other structural example which makes a conversion part respond
- the signal synthesis circuit includes a band limiting unit and a voltage / current source conversion unit, and a voltage / current source conversion In the unit, a quarter wavelength transmission line as shown in FIGS. 8A and 8B of the synthesis circuit unit is provided for each of the transmission frequencies f 1 , f 2 ,..., And a changeover switch (RF switch) as shown in FIG. There is a means of switching by 220-3, 220-4, 220-5, 220-6,.
- FIG. 9 is a block diagram showing a configuration example in which the signal synthesis circuit described in Patent Document 1 is made to correspond to a plurality of frequencies.
- N is the number of combined power amplifiers (PA) and M is the number of transmission frequency bands
- (N ⁇ M) 1/4 wavelength transmission lines are provided.
- the scale of the signal synthesis circuit increases as the number of synthesis and the number of bands increases.
- a passive element such as a variable capacitor or a variable inductor using RF-MEMS (Radio Frequency Micro-Electro-Mechanical System) is used.
- RF-MEMS Radio Frequency Micro-Electro-Mechanical System
- a means of adapting to the signal synthesis circuit having the lumped constant configuration shown in Document 1 is also conceivable.
- a variable inductor has a large loss, a low Q value (quality factor), and is difficult to adapt to a power amplifier filter and a signal synthesis circuit that require high efficiency. Therefore, in practice, the variable passive elements that can be adapted are limited only to the capacitance.
- the present invention has been made in view of such a problem, and even if the circuit configuration is such that the variable unit is limited to only a variable capacitor, a plurality of output signals from a plurality of switch mode amplifiers can be output without increasing the circuit scale. It is an object of the present invention to provide a transmitter, a signal synthesis circuit, and a signal synthesis method capable of synthesizing signals while maintaining impedance characteristics with respect to the transmission frequency.
- the transmitter, the signal synthesis circuit, and the signal synthesis method according to the present invention mainly adopt the following characteristic configuration.
- a transmitter includes: A modulation circuit that modulates a baseband signal into a multi-bit digital signal including a component of a radio frequency band, and a multi-bit digital signal that is arranged corresponding to each bit of the multi-bit digital signal output from the modulation circuit.
- a transmitter having a switch mode amplifier that amplifies the signal for each bit, a signal synthesis circuit that synthesizes the multi-bit digital signal output from each of the switch mode amplifiers as a transmission signal, and an antenna that transmits the transmission signal
- the signal synthesis circuit includes: A frequency-variable band limiting unit that band-limits an output signal from each of the switch mode amplifiers; A voltage-current source conversion unit that includes at least a variable capacitor and converts an output signal from each of the band limiting units from a voltage to a current; Connecting the output nodes of each of the voltage-current source converters, and combining the output signals output from the voltage-current source converters, Furthermore, an impedance correction unit for correcting impedance is provided on a signal path between the synthesis point of the signal synthesis circuit and the antenna as a load.
- a signal synthesizing circuit comprises: A modulation circuit that modulates a baseband signal into a multi-bit digital signal including a component of a radio frequency band, and a multi-bit digital signal that is arranged corresponding to each bit of the multi-bit digital signal output from the modulation circuit. Is arranged in a transmitter having a switch mode amplifier for amplifying each bit and an antenna for transmitting a transmission signal, and the multi-bit digital signal output from each of the switch mode amplifiers is combined as a transmission signal.
- a signal synthesis circuit A frequency-variable band limiting unit that band-limits an output signal from each of the switch mode amplifiers; A voltage-current source conversion unit that includes at least a variable capacitor and converts an output signal from each of the band limiting units from a voltage to a current; Connecting the output nodes of each of the voltage-current source converters, and combining the output signals output from the voltage-current source converters, Furthermore, the output signal from the synthesis point is output to the antenna via an impedance correction unit that corrects impedance.
- a signal synthesis method includes: A modulation circuit that modulates a baseband signal into a multi-bit digital signal including a component of a radio frequency band, and a multi-bit digital signal that is arranged corresponding to each bit of the multi-bit digital signal output from the modulation circuit.
- Signal combining method for combining the multi-bit digital signal output from each of the switch mode amplifiers as the transmission signal in a transmitter having a switch mode amplifier for amplifying each bit and an antenna for transmitting a transmission signal Because A frequency-variable band-limiting step for band-limiting each signal amplified in each of the switch-mode amplifiers; A voltage-current source conversion step of converting each signal band-limited in the band-limiting step from voltage to current using at least a variable capacitor; A synthesis step of synthesizing the respective signals converted into currents in the voltage-current source conversion step; And an impedance correction step for correcting the impedance of the signal synthesized in the synthesis step and then outputting the signal to the antenna.
- the signal synthesis circuit According to the transmitter, the signal synthesis circuit, and the signal synthesis method of the present invention, the following effects can be obtained.
- the transmitter of the present invention includes a modulation circuit that modulates a baseband signal into a multi-bit digital signal including a component in a radio frequency band, and a switch mode that amplifies the multi-bit digital signal output from the modulation circuit for each bit.
- An amplifier a frequency-variable band limiting unit that band-limits each of the output signals from the switch mode amplifier, a voltage-current source conversion unit that converts each of the output signals from the band-limiting unit, and the voltage-current source conversion At least a combination point for combining output signals from the unit, and an impedance correction unit for correcting impedance on a signal path between the combination point and the load antenna, and the variable unit is limited to the variable capacitance unit only Therefore, the output signals of multiple switch mode amplifiers (multi-bit digital Le transmission signal), for a plurality of transmission frequencies, while maintaining the impedance characteristics, and signal combining, can be transmitted as a transmission signal.
- multi-bit digital Le transmission signal multi-bit digital Le transmission signal
- FIG. 2 is a block diagram illustrating a first configuration example of a basic configuration of a signal synthesis circuit in the transmitter illustrated in FIG. 1. It is a block diagram which shows the 2nd structural example of the basic composition of the signal synthetic
- FIG. 7 is a block diagram illustrating a third configuration example of a basic configuration of a signal synthesis circuit in the transmitter illustrated in FIG. 1. It is a circuit diagram which shows the structural example of the voltage-current source conversion part of the signal synthetic
- FIG. 2A shows the variable filter which is a variable band limiting part as a first example of the structure.
- FIG. 2B shows the structural example in the case of sharing a part of circuit element of the voltage-current source conversion part of the signal composition circuit shown in FIG. 2B and the variable filter which is a variable band limiting part as a second structural example.
- FIG. 2B shows the example of a structure in the case of sharing a part of circuit element of the variable filter and impedance correction
- FIG. 1 shows the whole structure of the transmitter of the said patent document 1.
- the present invention provides a modulation circuit that modulates a baseband signal into a multi-bit digital signal including a component of a radio frequency band, and is arranged corresponding to each bit of the multi-bit digital signal output from the modulation circuit, A switch mode amplifier that amplifies a multi-bit digital signal for each bit; a signal synthesis circuit that synthesizes the multi-bit digital signal output from each of the switch mode amplifiers as a transmission signal; and an antenna that transmits the transmission signal; , Wherein the signal synthesis circuit includes a frequency variable band limiting unit that limits a band of an output signal from each of the switch mode amplifiers, and at least a variable capacitor, A voltage-current source converter for converting an output signal from the limiter from a voltage to a current; and the voltage-current source converter Each of the output nodes, and a synthesis point that synthesizes the output signals output from each
- the transmitter according to the present invention synthesizes the output signals of a plurality of switch mode amplifiers while maintaining the impedance characteristics for a plurality of transmission frequencies without increasing the circuit scale. It is possible to transmit as a signal.
- FIG. 1 is a block diagram illustrating an example of the overall configuration of a transmitter according to an embodiment of the present invention.
- the transmitter according to the present embodiment includes a digital baseband (DBB: Digital Base-Band, hereinafter abbreviated as DBB) signal generation unit 410, a modulation circuit 420, a switch mode amplifier 100-1, 100-2, a signal synthesis circuit 200, an impedance correction unit 203, and an antenna (load) 300 are included at least.
- DBB Digital Base-Band
- the impedance correction unit 203 is arranged in the subsequent stage of the signal synthesis circuit 200 separately from the signal synthesis circuit 200, but depending on the case, the signal synthesis circuit 200 (that is, it is arranged in the final stage on the output side in the signal synthesis circuit 200).
- a radio signal is converted into DBB signals I and Q of 10 bits or more by the DBB signal generator 410. Generated. Thereafter, the generated DBB signals I and Q are modulated by a modulation circuit 420 into a multi-bit digital transmission signal including radio frequency band components.
- the modulation circuit 420 includes at least an IQ modulator 421, a converter 422, a modulator 423, an accumulator 424, and a decoder 425.
- the number of bits that can be input to amplifiers applied to the switch mode amplifiers 100-1 and 100-2, for example, class D amplifiers is generally smaller than the number of bits of the DBB signal. Therefore, in order to make the DBB signal a signal that can be input to the class D amplifier, it is necessary to reduce the number of bits. In general, in the method of simply truncating the lower bits, the quantization noise increases by 6 dB each time one bit is discarded.
- a delta-sigma ( ⁇ ) modulator that can be suitably used as the modulator 423 is a circuit technology that can reduce the number of bits while avoiding an increase in quantization noise in a band near a desired frequency. However, the modulator 423 may use a modulator other than the delta sigma modulator.
- the DBB signals I and Q generated by the DBB signal generation unit 410 are input to the IQ modulator 421 of the modulation circuit 420, and the pulse phase signal ⁇ that is rectangularized by the IQ modulator 421 is generated.
- the DBB signals I and Q are also input to the converter 422 of the modulation circuit 420, and the converter 422 performs an operation of (I 2 + Q 2 ) 1/2 to generate an amplitude signal r. .
- the amplitude signal r is modulated by the modulator 423.
- the number of bits of the output signal of the modulator 423 is set equal to the number of bits that can be input to the subsequent class D amplifier. In the configuration shown in FIG. 1, since two switch mode amplifiers 100-1 and 100-2 are provided as class D amplifiers, the number of bits that can be input is two.
- the output signal of the modulator 423 is integrated by the rectangularized pulse phase signal ⁇ and the accumulator 424 to obtain a multi-bit including a desired radio frequency band component (2 bits in the configuration shown in FIG. 1).
- a digital transmission signal of two or more bits is generated.
- the rectangular pulse phase signal ⁇ is assigned high to “1” and low to “0”
- the number of bits of the output signal of the accumulator 424 is the modulator 423. Is equal to the number of bits of the output signal.
- the multi-bit digital transmission signal generated by the accumulator 424 is input to the switch mode amplifiers 100-1 and 100-2 via the decoder 425.
- the MSB (Most Significant Bit) side signal of the multi-bit digital transmission signal is input to one switch mode amplifier 100-1, and the LSB (Least Significant Bit) side signal is the other side.
- the signal is input to the switch mode amplifier 100-2, and is amplified and output at each.
- the output signals of the two switch mode amplifiers 100-1 and 100-2 are synthesized by the signal synthesis circuit 200, and the synthesized signal is subjected to impedance correction by the impedance correction unit 203, and then the antenna (load ) 300 is transmitted.
- the configuration of the signal synthesis circuit 200 has several configurations that can support a plurality of transmission frequencies while reducing the circuit scale and reducing the size. An example will be described.
- FIG. 2A is a block diagram showing a first configuration example of the basic configuration of the signal synthesis circuit 200 in the transmitter shown in FIG.
- the signal synthesis circuit 200 in the first configuration example includes the output signal of one switch mode amplifier 100-1 that amplifies the MSB-side digital transmission signal among the multi-bit digital transmission signals.
- the output signal of the other switch mode amplifier 100-2 that amplifies the digital transmission signal on the LSB side is band-limited to a desired frequency band, and then converted from voltage to current and then combined.
- the respective digital transmission signals are combined and output, and the signals are supplied to the load 300 via the impedance correction unit 203.
- the signal path between one switch mode amplifier 100-1 and the synthesis point X has a variable filter 201-1 as a variable band limiting unit, a variable capacitor, And a voltage / current source conversion unit 202-1 for performing voltage / current conversion.
- the signal path between the other switch mode amplifier 100-2 and the synthesis point X has a variable filter 201-2 that is a variable band limiting unit, and a voltage current source that has a variable capacitor and performs voltage-current conversion.
- a conversion unit 202-2 In addition, an impedance correction unit 203 having a variable capacitor and correcting impedance is provided in a signal path between the synthesis point X and the load 300 that is an antenna.
- One switch mode amplifier 100-1 that amplifies the MSB digital transmission signal among the multi-bit digital transmission signals is connected in series between the power source of the power supply voltage Vdd and the ground, as shown in FIG. 2A.
- One switch element is inserted, and the two switch elements are controlled so that one of them is turned on. That is, the output voltage of the switch mode amplifier 100-1 is the power supply voltage Vdd when the switch element on the power supply side is ON and the switch element on the ground side is OFF, and is the ground potential in the opposite case. Therefore, in any case, the switch mode amplifier 100-1 is equivalent to a grounded state in terms of high frequency, and the output of the switch mode amplifier 100-1 is a voltage source having a low impedance. Can be considered.
- one variable filter 201-1 that receives the output signal from one switch mode amplifier 100-1 is a circuit that limits the band of the output signal of the switch mode amplifier 100-1, and has a fundamental frequency f 0. Only signals in the vicinity are allowed to pass, and signals in other frequency regions are reflected. In particular, the harmonic signal is totally reflected.
- the variable filter 201-1 for example, by using an LC filter, specifically, as shown in FIG. 5A, using the LC series resonant circuit and a variable capacitor C f and inductor L f are connected in series It is desirable to configure.
- FIG. 5A is a circuit diagram showing a circuit configuration example of one variable filter 201-1 of the signal synthesis circuit 200 shown in FIG. 2A as a first configuration example.
- the variable capacitor C f is set so as to satisfy the following expression (1) according to the frequency f 0 of the transmission signal.
- one voltage / current source converter 202-1 that receives an output signal from one variable filter 201-1 converts the voltage of the output signal from one variable filter 201-1 into a current I1 and outputs the current I1. .
- the other switch mode amplifier 100-2 side that amplifies the LSB side digital transmission signal performs the same operation as the one switch mode amplifier 100-1 side. Only the signal in the vicinity of the fundamental frequency f 0 is passed by the variable filter 201-2, the signal in the other frequency region is reflected, and only the signal in the band that has passed through the other variable filter 201-2 is the other voltage current. The voltage is supplied to the source converter 202-2, and the current I2 is output from the other voltage / current source converter 202-2.
- the impedance in the vicinity of the fundamental wave before the synthesis point X is determined when the switch elements of the switch mode amplifiers 100-1 and 100-2 are turned on / off.
- the output of the switch mode amplifiers 100-1 and 100-2 can be regarded as a voltage source because the impedance is low at high frequencies. Therefore, the voltage-current conversion of the voltage / current source conversion units 202-1 and 202-2 connected to the subsequent stage of each of the switch mode amplifiers 100-1 and 100-2 via the variable filters 201-1 and 201-2, respectively.
- the signal synthesis circuit 200 becomes equivalent to a circuit in which the current source of the current I1 and the current source of the current I2 are connected to the synthesis point X. Therefore, in each port of the synthesis point X, it is possible to ensure isolation from other ports.
- the current I1 output from one switch mode amplifier 100-1 side that amplifies the MSB side digital transmission signal and the other switch mode amplifier 100-2 side that amplifies the LSB side digital transmission signal By combining the current I2 with the current I2 at the synthesis point X, the output signals from the switch mode amplifiers 100-1 and 100-2 can be synthesized.
- FIG. 3A is a circuit diagram showing a configuration example of the voltage / current source converters 202-1 and 202-2 of the signal synthesis circuit 200 shown in FIG. 2A as a first configuration example.
- This bridged T-coil circuit is described in, for example, T.A. S.
- the shunt capacitance C s and variable capacitance C s is a variable displacement adjusting the capacitance value of the series capacitance C p which is proportional.
- variable capacitor C s is electrically connected even in the changed frequency band.
- ⁇ a ⁇ / 2
- the characteristic impedance Z a (af 0 ) at the frequency af 0 is the characteristic at the frequency f 0 as shown in the following expression (5). It changes to a times the impedance Z a (f 0 ).
- the impedance Z out viewed from the load Z L side largely fluctuates with respect to the transmission frequency f, and although the signal can be synthesized, there is a problem that the output power cannot be kept constant with respect to the frequency change. Arise.
- FIG. 4A is a circuit diagram illustrating a specific circuit configuration example of the impedance correction unit 203 disposed in the subsequent stage of the signal synthesis circuit 200 illustrated in FIG. 2A as the first configuration example.
- the equivalent circuit parameters (C s ′: shunt capacitance, C p ′: series capacitance, L s ′: series inductor, L m ′: mutual inductance) of FIG. 4A are obtained. And expressed as the following equation (7).
- the frequency of the transmitted signal from f 0 to a ⁇ f 0
- the characteristic impedance Z a (af 0 ) at the frequency af 0 changes to a times the characteristic impedance Z a (f 0 ) at the frequency f 0 as shown in the following equation (8).
- signals combined load from the combining point X of the circuit 200 Z L impedance at frequencies af 0 viewed side Z X (af 0) is, as shown in the following equation (9), the impedance at the frequency f 0 Z X ( f 0 ) a 2 times as large.
- the impedance Z out (af 0 ) at the frequency af 0 when the load Z L side is viewed from the output terminals of the switch mode amplifiers 100-1, 100-2,... Is expressed by the following equation (10).
- the impedance Z out (f 0 ) at the frequency f 0 becomes the same value. That is, by disposing the impedance correction unit 203 at the subsequent stage of the signal synthesis circuit 200, the load Z L side can be seen from the output terminals of the switch mode amplifiers 100-1, 100-2,. The impedance Z out can be maintained at the same value.
- the transmitter it is possible to ensure isolation between the switch mode amplifiers 100-1, 100-2,...
- the S / N ratio (signal to noise ratio) can also be improved.
- the voltage / current source conversion units 202-1 and 202-2 and the impedance correction unit 203 in the first configuration example are limited to the circuit configurations of the bridged T coils shown in FIGS. 3A and 4A, respectively. It is not a thing.
- a ⁇ -type equivalent circuit of a quarter wavelength transmission line configured using a variable shunt capacitor as shown in FIGS. 3B and 4B, or the voltage / current source conversion units 202-1 and 202-2 is shown in FIG.
- a T-type equivalent circuit of a quarter wavelength transmission line configured using a variable series capacitor as shown in 3C can also be used.
- an equivalent circuit configured with other variable capacitors can be similarly implemented.
- FIG. 3B is a circuit diagram showing another configuration example of the voltage / current source converters 202-1 and 202-2 of the signal synthesis circuit 200 shown in FIG. 2A as a first configuration example
- FIG. It is a circuit diagram which shows the other specific circuit structural example of the impedance correction
- FIG. 3C is a circuit diagram showing a further different configuration example of the voltage / current source conversion units 202-1 and 202-2 of the signal synthesis circuit shown in FIG. 2A as the first configuration example.
- the impedance correction unit 203 in the first configuration example switches the impedance transformer transmission lines 204-1 to 204-2 corresponding to each transmission frequency for each frequency. , 220-2 can be used for the circuit configuration.
- FIG. 4C is a circuit diagram illustrating a further different specific circuit configuration example of the impedance correction unit 203 disposed in the subsequent stage of the signal synthesis circuit 200 illustrated in FIG. 2A as the first configuration example.
- the impedance transformer transmission lines 204-1, 204-2,... include a quarter wavelength transmission line corresponding to each transmission frequency, a bridged T coil circuit that is a lumped constant equivalent circuit, a ⁇ -type equivalent circuit, T A type equivalent circuit or the like can be used.
- FIG. 6A shows one example of voltage-to-current source converters 202-1 and 202-2 and variable filters 201-1 and 201-2 that are variable band limiting units of the signal synthesis circuit 200 shown in FIG. 2A as a first configuration example.
- FIG. 6 is a circuit diagram showing a configuration example in the case where the circuit elements of the unit are shared, and shows a case where the inductor surrounded by the alternate long and short dash line is shared.
- the signal synthesis circuit 200 in the first configuration example is not limited to the configuration shown in FIG. 2A, and various modifications can be made.
- a configuration example different from FIG. 2A of the signal synthesis circuit 200 applied to the transmitter according to the embodiment of the present invention will be further described.
- FIG. 2B is a block diagram illustrating a second configuration example of the basic configuration of the signal synthesis circuit 200A in the transmitter illustrated in FIG. 1, and is illustrated in FIG. 2A as the first configuration example.
- the symbol “A” is added to the end and the signal synthesizing circuit 200A is expressed here.
- a signal synthesis circuit 200A shown in FIG. 2B as the second configuration example is compared with the configuration of the signal synthesis circuit 200 shown in FIG. 2A as the first configuration example. 1 and the voltage / current source conversion unit 202-1 are interchanged, and the positions of the variable filter 201-2 and the voltage / current source conversion unit 202-2, which are the other variable band limiting units, are also interchanged. Yes.
- FIG. 5B is a circuit diagram illustrating a circuit configuration example of the variable filters 201-1 and 201-2 of the signal synthesis circuit 200A illustrated in FIG. 2B as a second configuration example.
- FIG. 6B shows one example of voltage-current source converters 202-1 and 202-2 and variable filters 201-1 and 201-2 which are variable band limiting units of the signal synthesis circuit 200A shown in FIG. 2B as a second configuration example. It is a circuit diagram which shows the structural example in the case of sharing the circuit element of a part, and has shown the case where the variable capacity
- FIG. 2C is a block diagram illustrating a third configuration example of the basic configuration of the signal synthesis circuit 200B in the transmitter illustrated in FIG. 1, and is illustrated in FIG. 2A as the first configuration example.
- the symbol “B” is added to the end and the signal synthesizing circuit 200B is expressed.
- the signal synthesis circuit 200B shown in FIG. 2C as the third configuration example is different from the configuration of the signal synthesis circuit 200 shown in FIG. 2A as the first configuration example, and the variable filters 201-1 and 202-2 are deleted.
- variable filter 201-1A is newly arranged on the subsequent stage side of the synthesis point X (that is, the signal path between the synthesis point X and the impedance correction unit 203).
- the variable filter 201-1A arranged on the subsequent stage side of the synthesis point X constitutes a variable band limiting unit.
- signals other than the fundamental wave are reflected by the variable filter 201-1A and are not transmitted to the load 300 side. Therefore, it is possible to increase the efficiency of the transmission amplifier and improve the spurious characteristics.
- Other effects are the same as those of the signal synthesis circuit 200 shown in FIG. 2A as the first configuration example.
- the voltage / current conversion is performed by the voltage / current source conversion units 202-1 and 202-2 arranged in the preceding stage of the variable filter 201-1A.
- Is equivalently connected to a current source of current I L ( I1 + I2). Therefore, in the variable filter 201-1A, as in the case of the variable filters 201-1 and 201-2 of the second configuration example, as shown in FIG. 5B, the variable capacitor C f and the inductor L f are connected in parallel. It is desirable to use an LC parallel resonant circuit.
- variable filter 201-1A and the impedance correction unit 203 which are variable band limiting units in the third configuration example, share some circuit elements such as variable capacitance units. It is also possible to reduce the number of elements.
- FIG. 6C shows a third configuration example in which a part of circuit elements of the variable filter 201-1A, which is the variable band limiting unit of the signal synthesis circuit 200B shown in FIG. 2C, and the impedance correction unit 203 are shared.
- FIG. 6 is a circuit diagram showing a case where a variable capacitance portion surrounded by a one-dot chain line is shared.
- variable filters 201-1, 201-2, 201-1A, the voltage / current source conversion units 202-1 and 202-2, the impedance correction unit 203, and the switch mode amplifiers 100-1 and 100 The operation and effect of synthesizing a multi-bit signal are described assuming that each element constituting -2 has ideal characteristics. However, depending on the actual element used, the parasitic component of the element can be compensated, the line shape or element value can be changed to bring the phase of the voltage waveform or current waveform closer to the ideal signal synthesis operation, and It goes without saying that changes such as addition of a compensation element are naturally possible.
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Abstract
Description
本発明は、かかる問題に鑑みてなされたものであり、可変部を可変容量のみに限定した回路構成であっても、回路規模を増大させることなく、複数のスイッチモード増幅器の出力信号を、複数の送信周波数に対して、インピーダンス特性を保ちつつ、信号合成することが可能な送信機、信号合成回路および信号合成方法を提供することをその目的としている。
ベースバンド信号を無線周波数帯の成分を含む多ビットデジタル信号に変調する変調回路と、前記変調回路から出力された前記多ビットデジタル信号の各ビットごとに対応して配置し、前記多ビットデジタル信号を各ビットごとに増幅するスイッチモード増幅器と、前記スイッチモード増幅器それぞれから出力された前記多ビットデジタル信号を送信信号として信号合成する信号合成回路と、前記送信信号を送信するアンテナとを有する送信機であって、
前記信号合成回路は、
前記スイッチモード増幅器それぞれからの出力信号を帯域制限する周波数可変な帯域制限部と、
少なくとも可変容量を備えて、前記帯域制限部それぞれからの出力信号を電圧から電流に変換する電圧電流源変換部と、
前記電圧電流源変換部それぞれの出力ノードを接続し、前記電圧電流源変換部それぞれから出力される出力信号を合成する合成点と
を含み、
さらに、前記信号合成回路の前記合成点と負荷である前記アンテナとの間の信号経路上に、インピーダンスの補正を行うインピーダンス補正部
を備えていることを特徴とする。
ベースバンド信号を無線周波数帯の成分を含む多ビットデジタル信号に変調する変調回路と、前記変調回路から出力された前記多ビットデジタル信号の各ビットごとに対応して配置し、前記多ビットデジタル信号を各ビットごとに増幅するスイッチモード増幅器と、送信信号を送信するアンテナとを有する送信機内に配置されて、前記スイッチモード増幅器それぞれから出力された前記多ビットデジタル信号を前記送信信号として信号合成する信号合成回路であって、
前記スイッチモード増幅器それぞれからの出力信号を帯域制限する周波数可変な帯域制限部と、
少なくとも可変容量を備えて、前記帯域制限部それぞれからの出力信号を電圧から電流に変換する電圧電流源変換部と、
前記電圧電流源変換部それぞれの出力ノードを接続し、前記電圧電流源変換部それぞれから出力される出力信号を合成する合成点と
を含み、
さらに、前記合成点からの出力信号を、インピーダンスの補正を行うインピーダンス補正部を介して、前記アンテナに対して出力する
ことを特徴とする。
ベースバンド信号を無線周波数帯の成分を含む多ビットデジタル信号に変調する変調回路と、前記変調回路から出力された前記多ビットデジタル信号の各ビットごとに対応して配置し、前記多ビットデジタル信号を各ビットごとに増幅するスイッチモード増幅器と、送信信号を送信するアンテナとを有する送信機において、前記スイッチモード増幅器それぞれから出力された前記多ビットデジタル信号を前記送信信号として信号合成する信号合成方法であって、
前記スイッチモード増幅器それぞれにおいて増幅されたそれぞれの信号を帯域制限する周波数可変な帯域制限ステップと、
前記帯域制限ステップにおいて帯域制限されたそれぞれの信号を少なくとも可変容量を用いて電圧から電流に変換する電圧電流源変換ステップと、
前記電圧電流源変換ステップにおいて電流に変換したそれぞれの信号を合成する合成ステップと、
さらに、前記合成ステップにおいて合成した信号を、インピーダンスの補正を行った後、前記アンテナに対して出力するインピーダンス補正ステップと
を有していることを特徴とする。
本発明の実施形態の説明に先立って、本発明の特徴についてその概要をまず説明する。本発明は、ベースバンド信号を無線周波数帯の成分を含む多ビットデジタル信号に変調する変調回路と、前記変調回路から出力された前記多ビットデジタル信号の各ビットごとに対応して配置し、前記多ビットデジタル信号を各ビットごとに増幅するスイッチモード増幅器と、前記スイッチモード増幅器それぞれから出力された前記多ビットデジタル信号を送信信号として信号合成する信号合成回路と、前記送信信号を送信するアンテナと、を少なくとも含んで構成される送信機であって、前記信号合成回路は、前記スイッチモード増幅器それぞれからの出力信号を帯域制限する周波数可変な帯域制限部と、少なくとも可変容量を備えて、前記帯域制限部からの出力信号を電圧から電流に変換する電圧電流源変換部と、前記電圧電流源変換部それぞれの出力ノードを接続し、前記電圧電流源変換部それぞれから出力される出力信号を合成する合成点と、を少なくとも含んで構成され、さらに、前記信号合成回路の前記合成点と負荷である前記アンテナとの間の信号経路上に、インピーダンスの補正を行うインピーダンス補正部、を備えていることを主要な特徴としている。
本発明の一実施形態に係る送信機の構成例について、図1を参照して詳細に説明する。図1は、本発明の実施形態に係る送信機の全体構成の一例を示すブロック図である。図1に示すように、本実施形態に係る送信機は、デジタルベースバンド(DBB:Digital Base-Band。以降、DBBと略記する)信号生成部410、変調回路420、スイッチモード増幅器100-1,100-2、信号合成回路200、インピーダンス補正部203、および、アンテナ(負荷)300を少なくとも含んで構成される。なお、本実施形態においては、インピーダンス補正部203を、信号合成回路200とは別個に、該信号合成回路200の後段に配置している場合を示しているが、場合によっては、該信号合成回路200内に配置する(すなわち、該信号合成回路200内の出力側の最終段に配置する)ようにしても良い。
図2Aは、図1に示した送信機における信号合成回路200の基本構成の第1の構成例を示すブロック図である。図2Aに示すように、本第1の構成例における信号合成回路200は、多ビットのデジタル送信信号のうち、MSB側のデジタル送信信号を増幅する一方のスイッチモード増幅器100-1の出力信号と、LSB側のデジタル送信信号を増幅する他方のスイッチモード増幅器100-2の出力信号と、を、それぞれ、所望の周波数帯に帯域制限した後、さらに、電圧→電流の変換を施してから、合成点Xにてそれぞれのデジタル送信信号を信号合成して出力し、インピーダンス補正部203を介して、信号を負荷300に供給する。
図2Bは、図1に示した送信機における信号合成回路200Aの基本構成の第2の構成例を示すブロック図であり、第1の構成例として図2Aに示した信号合成回路200との混同を避けるために、ここでは、末尾に符号‘A’を付して信号合成回路200Aと表現している。第2の構成例として図2Bに示す信号合成回路200Aは、第1の構成例として図2Aに示した信号合成回路200の構成と比較して、一方の可変帯域制限部である可変フィルタ201-1と電圧電流源変換部202-1との位置を入れ替えるとともに、他方の可変帯域制限部である可変フィルタ201-2と電圧電流源変換部202-2との位置をも入れ替えた構成になっている。
図2Cは、図1に示した送信機における信号合成回路200Bの基本構成の第3の構成例を示すブロック図であり、第1の構成例として図2Aに示した信号合成回路200との混同を避けるために、ここでは、末尾に符号‘B’を付して信号合成回路200Bと表現している。第3の構成例として図2Cに示す信号合成回路200Bは、第1の構成例として図2Aに示した信号合成回路200の構成と比較して、可変フィルタ201-1,202-2を削除して、前段のスイッチモード増幅器100-1,100-2それぞれの出力ノードを電圧電流源変換部202-1,202-2それぞれに直接接続するとともに、可変フィルタ201-1,202-2を削除した代わりに、合成点Xの後段側(すなわち、合成点Xとインピーダンス補正部203との間の信号経路)に可変フィルタ201-1Aを新たに配置した構成になっている。かかる構成においては、合成点Xの後段側に配置した可変フィルタ201-1Aが、可変帯域制限部を構成していることになる。
以上、本発明に係る実施形態を参照しながら本発明を詳細に説明した。しかし、かかる実施形態は、本発明の単なる例示に過ぎず、本発明は前記実施形態の記載内容のみに限定されるものではなく、本発明の構成や詳細については、当然のことながら、本発明の範囲内において当業者が理解し得る様々な変更を行うことができる。例えば、前記実施形態においては、デジタル送信信号が2ビットである場合についてのみ記載したが、本発明はかかるビット数のみに限らず、2以上の多ビットのデジタル送信信号に対しても対応することが可能である。
100-2 スイッチモード増幅器
200 信号合成回路
200A 信号合成回路
200B 信号合成回路
201-1 可変フィルタ(可変帯域制限部)
201-1A 可変フィルタ(可変帯域制限部)
201-2 可変フィルタ(可変帯域制限部)
202-1 電圧電流源変換部
202-2 電圧電流源変換部
203 インピーダンス補正部
204-1 インピーダンストランス伝送線路
204-2 インピーダンストランス伝送線路
205-1 オープンスタブ
205-2 オープンスタブ
206-1 オープンスタブ
207-1 伝送線路トランス
208-1 伝送線路トランス
208-2 伝送線路トランス
220-1 切り替えスイッチ
220-2 切り替えスイッチ
220-3 切り替えスイッチ
220-4 切り替えスイッチ
220-5 切り替えスイッチ
220-6 切り替えスイッチ
300 アンテナ(負荷)
410 デジタルベースバンド信号生成部(DBB信号生成部)
420 変調回路
421 IQモジュレータ
422 変換器
423 変調器
424 積算器
425 デコーダ
X 合成点
Claims (10)
- ベースバンド信号を無線周波数帯の成分を含む多ビットデジタル信号に変調する変調回路と、前記変調回路から出力された前記多ビットデジタル信号の各ビットごとに対応して配置し、前記多ビットデジタル信号を各ビットごとに増幅するスイッチモード増幅器と、前記スイッチモード増幅器それぞれから出力された前記多ビットデジタル信号を送信信号として信号合成する信号合成回路と、前記送信信号を送信するアンテナとを有し、
前記信号合成回路は、
前記スイッチモード増幅器それぞれからの出力信号を帯域制限する周波数可変な帯域制限手段と、
少なくとも可変容量を備えて、前記帯域制限手段それぞれからの出力信号を電圧から電流に変換する電圧電流源変換手段と、
前記電圧電流源変換手段それぞれの出力ノードを接続し、前記電圧電流源変換手段それぞれから出力される出力信号を合成する合成点と
を含み、
さらに、前記信号合成回路の前記合成点と負荷である前記アンテナとの間の信号経路上に、インピーダンスの補正を行うインピーダンス補正手段
を備えていることを特徴とする送信機。 - 前記インピーダンス補正手段の特性インピーダンスの周波数依存性が、前記可変容量を備えた前記電圧電流源変換手段の特性インピーダンスの周波数依存性と一致することを特徴とする請求項1に記載の送信機。
- 前記可変容量を備えた電圧電流源変換手段が、ブリッジドTコイル回路、π型LC回路またはT型LC回路のいずれかから構成されていることを特徴とする請求項1または2に記載の送信機。
- 前記インピーダンス補正手段が、可変容量部を備えたブリッジドTコイル回路、可変容量部を備えたπ型LC回路若しくは可変容量部を備えたT型LC回路のいずれかから構成されているか、又は、各送信周波数に対応して配置したインピーダンストランス伝送線路と、送信周波数ごとに前記インピーダンストランス伝送線路を切り替えて用いるための切り替えスイッチとを含む回路から構成されていることを特徴とする請求項1ないし3のいずれかに記載の送信機。
- 前記帯域制限手段が、可変容量とインダクタとを直列に接続したLC直列共振回路から構成されていることを特徴とする請求項1ないし4のいずれかに記載の送信機。
- 前記帯域制限手段と前記電圧電流源変換手段との配置位置を入れ替えて、
前記電圧電流源変換手段が、前記スイッチモード増幅器それぞれからの出力信号を電圧から電流に変換し、
前記帯域制限手段が、前記電圧電流源変換手段それぞれからの出力信号を帯域制限する、
ことを特徴とする請求項1ないし4のいずれかに記載の送信機。 - 前記帯域制限手段が、可変容量とインダクタとを並列に接続したLC並列共振回路のいずれかから構成されていることを特徴とする請求項6に記載の送信機。
- 前記帯域制限手段を削除する代わりに、前記合成点と前記インピーダンス補正手段との間の信号経路上に、帯域制限を行うための可変フィルタを新たに配置して構成されていることを特徴とする請求項1ないし4のいずれかに記載の送信機。
- ベースバンド信号を無線周波数帯の成分を含む多ビットデジタル信号に変調する変調回路と、前記変調回路から出力された前記多ビットデジタル信号の各ビットごとに対応して配置し、前記多ビットデジタル信号を各ビットごとに増幅するスイッチモード増幅器と、送信信号を送信するアンテナとを有する送信機内に配置されて、前記スイッチモード増幅器それぞれから出力された前記多ビットデジタル信号を前記送信信号として信号合成する信号合成回路であって、
前記スイッチモード増幅器それぞれからの出力信号を帯域制限する周波数可変な帯域制限手段と、
少なくとも可変容量を備えて、前記帯域制限手段それぞれからの出力信号を電圧から電流に変換する電圧電流源変換手段と、
前記電圧電流源変換手段それぞれの出力ノードを接続し、前記電圧電流源変換手段それぞれから出力される出力信号を合成する合成点と
を含み、
さらに、前記合成点からの出力信号を、インピーダンスの補正を行うインピーダンス補正手段を介して、前記アンテナに対して出力する
ことを特徴とする信号合成回路。 - ベースバンド信号を無線周波数帯の成分を含む多ビットデジタル信号に変調する変調回路と、前記変調回路から出力された前記多ビットデジタル信号の各ビットごとに対応して配置し、前記多ビットデジタル信号を各ビットごとに増幅するスイッチモード増幅器と、送信信号を送信するアンテナとを有する送信機において、前記スイッチモード増幅器それぞれから出力された前記多ビットデジタル信号を前記送信信号として信号合成する信号合成方法であって、
前記スイッチモード増幅器それぞれにおいて増幅されたそれぞれの信号を帯域制限する周波数可変な帯域制限ステップと、
前記帯域制限ステップにおいて帯域制限されたそれぞれの信号を少なくとも可変容量を用いて電圧から電流に変換する電圧電流源変換ステップと、
前記電圧電流源変換ステップにおいて電流に変換したそれぞれの信号を合成する合成ステップと、
さらに、前記合成ステップにおいて合成した信号を、インピーダンスの補正を行った後、前記アンテナに対して出力するインピーダンス補正ステップと
を有していることを特徴とする信号合成方法。
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JP2016559786A JP6620757B2 (ja) | 2014-11-19 | 2015-07-30 | 送信機、信号合成回路および信号合成方法 |
US15/525,197 US10044379B2 (en) | 2014-11-19 | 2015-07-30 | Transmitter, signal synthesis circuit, and signal synthesis method |
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US10770802B2 (en) | 2014-11-10 | 2020-09-08 | Qorvo Us, Inc. | Antenna on a device assembly |
US10187019B1 (en) | 2018-03-26 | 2019-01-22 | Qorvo Us, Inc. | Phased array antenna system |
JP2020181651A (ja) * | 2019-04-23 | 2020-11-05 | 東京エレクトロン株式会社 | 補正関数を決定する方法 |
EP4054082A4 (en) * | 2019-11-29 | 2022-11-16 | Huawei Technologies Co., Ltd. | RADIO FREQUENCY TRANSMITTER |
Citations (5)
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JP2002510927A (ja) * | 1998-04-02 | 2002-04-09 | エリクソン インコーポレイテッド | Chireix/dohertyハイブリッド増幅器の電力波形合成 |
US20080290938A1 (en) * | 2007-05-21 | 2008-11-27 | Hypres, Inc. | Multibit digital amplifier for radio-frequency transmission |
WO2012017580A1 (ja) * | 2010-08-03 | 2012-02-09 | 日本電気株式会社 | 送信装置及びその制御方法 |
WO2014042205A1 (ja) * | 2012-09-14 | 2014-03-20 | 日本電気株式会社 | 送信機、信号合成回路、信号合成方法 |
JP5609890B2 (ja) * | 2009-12-08 | 2014-10-22 | 日本電気株式会社 | 送信装置 |
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US6311046B1 (en) | 1998-04-02 | 2001-10-30 | Ericsson Inc. | Linear amplification systems and methods using more than two constant length vectors |
US5930128A (en) | 1998-04-02 | 1999-07-27 | Ericsson Inc. | Power waveform synthesis using bilateral devices |
US6133788A (en) | 1998-04-02 | 2000-10-17 | Ericsson Inc. | Hybrid Chireix/Doherty amplifiers and methods |
US20120032738A1 (en) * | 2009-04-28 | 2012-02-09 | Panasonic Corporation | Power amplifier |
US9330545B2 (en) | 2013-07-17 | 2016-05-03 | Google Inc. | Determining input received via tactile input device |
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Patent Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
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JP2002510927A (ja) * | 1998-04-02 | 2002-04-09 | エリクソン インコーポレイテッド | Chireix/dohertyハイブリッド増幅器の電力波形合成 |
US20080290938A1 (en) * | 2007-05-21 | 2008-11-27 | Hypres, Inc. | Multibit digital amplifier for radio-frequency transmission |
JP5609890B2 (ja) * | 2009-12-08 | 2014-10-22 | 日本電気株式会社 | 送信装置 |
WO2012017580A1 (ja) * | 2010-08-03 | 2012-02-09 | 日本電気株式会社 | 送信装置及びその制御方法 |
WO2014042205A1 (ja) * | 2012-09-14 | 2014-03-20 | 日本電気株式会社 | 送信機、信号合成回路、信号合成方法 |
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US10044379B2 (en) | 2018-08-07 |
JPWO2016079906A1 (ja) | 2017-08-31 |
JP6620757B2 (ja) | 2019-12-18 |
US20170317697A1 (en) | 2017-11-02 |
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