WO2015159760A1 - Dispositif de conversion de puissance - Google Patents

Dispositif de conversion de puissance Download PDF

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Publication number
WO2015159760A1
WO2015159760A1 PCT/JP2015/060852 JP2015060852W WO2015159760A1 WO 2015159760 A1 WO2015159760 A1 WO 2015159760A1 JP 2015060852 W JP2015060852 W JP 2015060852W WO 2015159760 A1 WO2015159760 A1 WO 2015159760A1
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WIPO (PCT)
Prior art keywords
voltage
smoothing capacitor
relay
value
set value
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PCT/JP2015/060852
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English (en)
Japanese (ja)
Inventor
治信 温品
洋平 久保田
圭一 石田
慧 小川
Original Assignee
東芝キヤリア株式会社
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
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Application filed by 東芝キヤリア株式会社 filed Critical 東芝キヤリア株式会社
Priority to CN201580003687.7A priority Critical patent/CN105874702B/zh
Priority to JP2016513728A priority patent/JP6255088B2/ja
Publication of WO2015159760A1 publication Critical patent/WO2015159760A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/06—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode

Definitions

  • Embodiment of this invention is related with the power converter device which converts the voltage of AC power supply into DC, and converts the DC voltage into the AC voltage of a predetermined frequency.
  • a rectifier circuit that converts the voltage of the commercial AC power source into DC, a smoothing capacitor that smoothes the output voltage of the rectifier circuit, an inverter that converts the voltage of the smoothing capacitor into an AC voltage of a predetermined frequency, a commercial AC power source and a rectifier circuit,
  • a power conversion device in which a PTC thermistor for preventing an inrush current (a resistor whose resistance increases with a rise in temperature) is inserted and connected to a power line between and a relay contact is connected in parallel to the PTC thermistor.
  • This power converter prevents inrush current when the power is turned on by opening the relay contact and putting the PTC thermistor into the current path.
  • the relay contact is closed to form a short circuit to the PTC thermistor, and the PTC thermistor is disconnected. Even when the voltage of the commercial AC power supply temporarily decreases and the voltage of the smoothing capacitor falls below the output voltage of the rectifier circuit, the relay contact is opened and a PTC thermistor is turned on to prevent inrush current.
  • a relay is used to turn on and off the PTC thermistor.
  • the relay changes an electrical signal into a mechanical contact movement, there is a delay of several milliseconds from when the electrical signal is received until the contact is actually opened and closed. This time delay may prevent the inrush current from being prevented.
  • An object of an embodiment of the present invention is to provide a power conversion device that can reliably prevent an inrush current.
  • the power conversion device is a converter that converts a voltage of a commercial AC power source into a DC voltage, a smoothing capacitor connected to an output terminal of the converter, a voltage of the smoothing capacitor is converted into an AC voltage, and the AC voltage Output as drive power to the load, a resistor for preventing inrush current disposed in a current path between the converter and the smoothing capacitor, and a relay having a contact connected in parallel to the resistor, Control means for closing the relay when the voltage of the smoothing capacitor rises above a specified value, and opening the relay when the voltage of the smoothing capacitor drops below a set value.
  • the set value is higher than the minimum voltage value of the smoothing capacitor necessary for the current flowing through the converter not to exceed the maximum allowable current of the converter.
  • FIG. 1 is a block diagram showing the configuration of each embodiment.
  • FIG. 2 is a flowchart showing the control of the first embodiment.
  • FIG. 3 is a time chart showing the voltage change of the smoothing capacitor, the change of the relay drive signal, and the change of the normally open contact in the first embodiment.
  • FIG. 4 is a flowchart showing the control of the second embodiment.
  • FIG. 5 is a time chart showing a voltage change of a smoothing capacitor, a change of a relay drive signal, and a change of a normally open contact in the second embodiment.
  • FIG. 6 is a flowchart showing the control of the third embodiment.
  • FIG. 7 is a time chart showing the voltage change of the smoothing capacitor, the change of the relay drive signal, and the change of the normally open contact in the third embodiment.
  • FIG. 8 is a flowchart showing the control of the fourth embodiment.
  • a converter 2 is connected to a commercial three-phase AC power source 1.
  • Converter 2 includes a plurality of switching elements and a plurality of diodes, and converts the AC voltage of commercial three-phase AC power supply 1 into a DC voltage.
  • a smoothing capacitor (electrolytic capacitor) 4 is connected to the output end of the converter 2 via a parallel circuit of the resistor 3 and the relay contact 30a.
  • the resistor 3 is, for example, a PTC thermistor for preventing inrush current.
  • the relay contact 30 a is a normally open contact of the relay 30.
  • an inverter 10 is connected to the smoothing capacitor 4, and a load, for example, a brushless DC motor (also referred to as a permanent magnet synchronous motor) M is connected to the output terminal of the inverter 10.
  • the inverter 10 includes a U-phase series circuit of two switching elements T1 and T2 each having a reflux diode connected in antiparallel, and a V-phase series circuit of two switching elements T3 and T4 each having a reflux diode connected in antiparallel, It includes a W-phase series circuit of two switching elements T5 and T6 each having a reverse diode connected in reverse parallel, converts the voltage of the smoothing capacitor 4 into an AC voltage of a predetermined frequency, and converts the AC voltage to the brushless DC motor M. Output as drive power. Phase windings Lu, Lv, and Lw of the brushless DC motor M are connected to interconnection points of both switching elements in each series circuit of the inverter 10, respectively.
  • the DC voltage Vd is applied to the relay 30 via the collector / emitter of the NPN transistor 22.
  • the base of the NPN transistor 22 is connected to the main controller 20.
  • the NPN transistor 22 is turned on when the relay drive signal D supplied from the main controller 20 is at a high level, and turned off when the relay drive signal D is at a low level.
  • the NPN transistor 22 is turned on, the exciting coil of the relay 30 is energized and the relay contact 30a is closed. That is, the relay 30 is closed.
  • the NPN transistor 22 is turned off, the exciting coil of the relay 30 is de-energized and the relay contact 30a is opened. That is, the relay 30 opens.
  • the voltage detector 21 is connected to both ends of the smoothing capacitor 4.
  • the voltage detector 21 detects the voltage Vdc generated in the smoothing capacitor 4. This voltage detector 21 is connected to the main controller 20.
  • Current sensors (current transformers) 11, 12, and 13 are disposed on each phase energization line between the output terminal of the inverter 10 and the brushless DC motor M.
  • Current sensors 11, 12, and 13 detect currents (phase currents) flowing through the phase windings Lu, Lv, and Lw of the brushless DC motor M, respectively. These current sensors 11, 12, and 13 are connected to the main control unit 20.
  • the sensorless vector controller 50 is further connected to the main controller 20.
  • the sensorless vector control unit 50 includes a current detection unit 51, a speed estimation calculation unit 52, an integration unit 53, a subtraction unit 54, a speed control unit 55, a calculation unit 56, subtraction units 57 and 58, a current control unit (first current control). Unit) 61, a current control unit (second current control unit) 62, and a PWM signal generation unit 63.
  • the current detection unit 51 performs three-phase to two-phase conversion on the detection currents of the current sensors 11, 12, and 13, and field axis (d axis) coordinates and torque axis (q axis) coordinates on the rotor axis in the brushless DC motor M.
  • d axis field axis
  • q axis torque axis
  • Iq torque component current
  • the speed estimation calculation unit 52 estimates the rotor speed ⁇ est of the brushless DC motor M by calculation based on the field component current Id and the torque component current Iq detected by the current detection unit 51.
  • brushless operation is performed by calculation using the field component current Id, the torque component current Iq, the field component voltage Vd obtained by the current control unit 61, and the torque component voltage Vq obtained by the current control unit 62.
  • a field component speed electromotive force (referred to as d-axis speed electromotive force) Ed in the DC motor M is estimated, and an estimated rotor speed ⁇ est is obtained based on a proportional / integral control (PI control) calculation of the d-axis speed electromotive force Ed.
  • PI control proportional / integral control
  • the integrating unit 53 obtains an estimated rotor position ⁇ est by integrating the estimated rotor speed ⁇ est obtained by the speed estimation calculating unit 52.
  • the estimated rotor position ⁇ est is supplied to the current detection unit 51 and the PWM signal generation unit 63.
  • the subtracting unit 54 obtains a speed deviation between the target speed ⁇ ref and the estimated rotor speed ⁇ est by subtracting the estimated rotor speed ⁇ est from the target speed ⁇ ref commanded from the main control unit 20.
  • the speed control unit 55 calculates a target value Iqref of the torque component current Iq by calculating a proportional / integral control (PI control) on the speed deviation obtained by the subtracting unit 54.
  • PI control proportional / integral control
  • the calculation unit 56 obtains the target value Idref of the field component current Id from the target value Iqref of the torque component current Iq.
  • the subtracting unit 57 obtains a deviation ⁇ Id between the target value Idref and the field component current Id by subtracting the field component current Id from the target value Idref.
  • the subtraction unit 58 obtains a deviation ⁇ Iq between the target value Iqref and the torque component current Iq by subtracting the torque component current Iq from the target value Iqref.
  • the current control unit 61 obtains the field component voltage Vd converted into the d-axis coordinate on the rotor shaft in the brushless DC motor M by the proportional / integral control (PI control) calculation of the deviation ⁇ Id.
  • the current control unit 62 obtains a torque component voltage Vq converted into q-axis coordinates on the rotor shaft in the brushless DC motor M by proportional / integral control (PI control) calculation of the deviation ⁇ Iq.
  • the PWM signal generation unit 63 generates a switching pulse width modulation signal (referred to as a PWM signal) for the inverter 10 according to the field component voltage Vd, the torque component voltage Vq, and the estimated rotor position ⁇ est.
  • the switching elements T1 to T6 of the inverter 10 are turned on and off, and drive voltages Vu, Vv, and Vw for the phase windings Lu, Lv, and Lw of the brushless DC motor M are output from the inverter 10.
  • the speed of the brushless DC motor M is controlled so as to reach the target speed in a short time.
  • the main control unit 20 has the following means (1) to (3) as main functions.
  • the first set value V1 ′ is a specified value V2 or less, and is a value that is higher by a predetermined value than the minimum voltage value V1 of the smoothing capacitor 4 that is necessary for the current flowing through the converter 2 not to exceed the allowable maximum current of the converter 2. It is.
  • the allowable maximum current of the converter 2 is, for example, the maximum rated current of a switching element or a diode in the converter 2.
  • the inrush current Ix (in accordance with the difference “Va ⁇ Vdc” between the output voltage Va of the converter 2 and the voltage Vdc of the smoothing capacitor 4 and the line impedance Z from the commercial three-phase AC power supply 1 to the smoothing capacitor 4. Va ⁇ Vdc) / Z tends to flow from the converter 2 to the smoothing capacitor 4.
  • the main control unit 20 determines the magnitude of the load based on the torque component current Iq in the sensorless vector control unit 50 (Step S1). S5). Specifically, when the torque component current Iq is less than a certain value, the main control unit 20 determines that the load is a light load with a value less than a predetermined value, and when the torque component current Iq is greater than or equal to a certain value. It is determined that the load is a medium load or a heavy load greater than or equal to a predetermined value.
  • the main control unit 20 compares the voltage Vdc of the smoothing capacitor 4 with the first set value V1 ′ (step S6) when determining that the load is a light load (YES in step S5).
  • the main control unit 20 sets the relay drive signal D to a low level to turn off the transistor 22,
  • the relay 30 is de-energized (opening operation) (step S7).
  • the relay contact 30a is opened, and the resistor 3 is put in the energization path between the converter 2 and the smoothing capacitor 4.
  • the relay contact 30a is a mechanical contact that moves mechanically, a time delay t1 of several milliseconds occurs after the relay drive signal D is set to a low level until the relay contact 30a is actually opened.
  • the first set value V1 ′ higher than the minimum voltage value V1 necessary for preventing the inrush current is selected for deactivating the relay 30, before the voltage Vdc drops below the minimum voltage value V1.
  • the relay contact 30a is opened and the resistor 3 is turned on. Therefore, even if the voltage Vdc falls below the minimum voltage value V1, since the resistor 3 is already turned on at that time, no inrush current occurs. That is, the semiconductor switch and the diode of the converter 2 can be prevented from being destroyed.
  • main controller 20 determines that voltage Vdc of smoothing capacitor 4 is decreasing (NO in step S1, YES in step S4), and determines that the load is medium load or heavy load (NO in step S5).
  • the main control unit 20 sets the relay drive signal D to a low level and turns off the transistor 22, thereby
  • the relay 30 is de-energized (step S7).
  • the relay 30 is de-energized, the relay contact 30a is opened, and the resistor 3 is put in the energization path between the converter 2 and the smoothing capacitor 4.
  • the load is a medium load or a heavy load
  • the voltage Vdc descends quickly, and a time delay t1 of several msec from when the relay drive signal D is set to a low level until the relay contact 30a is actually opened.
  • the relay contact 30a is opened before the voltage Vdc drops to the minimum voltage value V1, and the resistance is reduced.
  • Container 3 is turned on. That is, even when the voltage Vdc falls below the minimum voltage value V1, since the resistor 3 is already turned on at that time, no inrush current occurs. Therefore, destruction of the semiconductor switch and the diode of the converter 2 can be prevented.
  • the main control unit 20 stops switching of the inverter 10.
  • the relay 30 when the voltage Vdc drops, the relay 30 is de-energized at a timing when the voltage Vdc falls below the first set value V1 ′ or the second set value V2 that is higher than the minimum voltage value V1 for preventing inrush current. Even if there is a time delay in opening and closing the relay contact 30a, the inrush current can be reliably prevented.
  • the first set value V1 ′ is selected for de-energizing the relay 30 at light load
  • the voltage Vdc is applied during the switching time delay t2 of the relay contact 30a even if there is a sudden drop in the voltage Vdc at the time of heavy load. Is selected to a minimum value that does not reach the minimum voltage value V1 for preventing inrush current. Thereby, the introduction of the resistor 3 can be extended to the last timing of inrush current generation.
  • the resistor 3 When the resistor 3 is turned on, the input power (current) is limited. When this input power is less than the driveable power of the inverter 10, the inverter 10 cannot be driven. However, as described above, the insertion of the resistor 3 can be extended until the timing of the inrush current generation, so that the drive stop of the inverter 10 due to the limitation of the input power can be postponed as much as possible. As a result, the operation rate of the inverter 10 can be increased. In addition, when the resistor 3 is turned on, the power consumed by the resistor 3 is wasted. However, as described above, the turning on of the resistor 3 can be extended to the last timing of inrush current generation. Save energy.
  • Step S1 When the voltage Vdc of the smoothing capacitor 4 decreases (NO in Step S1, YES in Step S4), the main control unit 20 determines the magnitude of the load based on the torque component current Iq in the sensorless vector control unit 50 (Step S1). S5).
  • step S5 When it is determined that the load is a light load (YES in step S5), the main control unit 20 compares the voltage Vdc of the smoothing capacitor 4 with the first set value V1 ′ (step S6). When the voltage Vdc of the smoothing capacitor 4 falls below the first set value V1 ′ (YES in step S6), the main control unit 20 sets the relay drive signal D to a low level to turn off the transistor 22 and thereby the relay 30 is deactivated (opening operation) (step S7). When the relay 30 is de-energized, the relay contact 30a is opened, and the resistor 3 is put in the energization path between the converter 2 and the smoothing capacitor 4. Subsequently, the main control unit 20 cancels the output torque reduction described later (step S10).
  • main controller 20 determines that voltage Vdc of smoothing capacitor 4 is decreasing (NO in step S1, YES in step S4), and determines that the load is medium load or heavy load (NO in step S5).
  • the voltage Vdc of the smoothing capacitor 4 is compared with the second set value V2 (step S8).
  • the main control unit 20 outputs the output of the inverter 10 so that the load becomes a light load that is less than a predetermined value.
  • Torque is reduced (step S9).
  • the main control unit 20 reduces the torque component current Iq in the sensorless vector control unit 50 so that the load becomes a light load less than a predetermined value.
  • the main control unit 20 returns to the determination in step S1 after reducing the torque component current Iq. If the voltage Vdc continues to decrease (NO in step S1, YES in step S4), the main control unit 20 determines whether the load has become a light load (step S5).
  • step S5 If the magnitude of the load is reduced to a light load (YES in step S5), the main control unit 20 compares the voltage Vdc of the smoothing capacitor 4 with the first set value V1 ′ (step S6). When the voltage Vdc of the smoothing capacitor 4 falls below the first set value V1 ′ (YES in step S6), the main control unit 20 sets the relay drive signal D to a low level to turn off the transistor 22, Thus, the relay 30 is de-energized (step S7). When the relay 30 is de-energized, the relay contact 30a is opened, and the resistor 3 is put in the energization path between the converter 2 and the smoothing capacitor 4.
  • the main control unit 20 cancels the reduction of the torque component current Iq (output torque reduction) in the sensorless vector control unit 50 (step S10).
  • the voltage Vdc of the smoothing capacitor 4 is lowered and the load is a light load with a magnitude less than a predetermined value
  • the voltage Vdc is higher than the minimum voltage value V1 for preventing inrush current. Since the relay 30 is deenergized at a timing lower than ', even if there is a time delay in opening and closing the relay contact 30a, an inrush current can be reliably prevented.
  • the output torque of the inverter 10 is reduced so that the load size becomes a light load less than the predetermined value, thereby reducing the rate of decrease in the voltage Vdc. Since the speed is reduced to the lowering speed at light load, the lowering of the voltage Vdc can be reliably captured. That is, inrush current can be reliably prevented without being affected by the size of the load. Other effects are the same as those of the first embodiment.
  • the main control unit 20 has the following means (11) to (13) as main functions.
  • Second control means for opening the relay contact 30a by opening the relay 30 when the voltage Vdc of the smoothing capacitor 4 falls below the first set value V1 ′.
  • step S1 When the voltage Vdc of the smoothing capacitor 4 increases (YES in step S1), the main control unit 20 cancels the allowable minimum operating frequency Fmin described later (step S1a), and cancels the voltage Vdc and the second voltage Vdc. 2
  • the set value V2 is compared (step S2).
  • the main control unit 20 sets the relay drive signal D to a high level based on the determination that the inrush current has been eliminated.
  • the transistor 22 is turned on, thereby energizing (closing operation) the relay 30 (step S3).
  • steps S1 to S3 is different from the first and second embodiments only in that the process of step S1a is added.
  • step S11 When the voltage Vdc of the smoothing capacitor 4 falls (NO in step S1, YES in step S4), the main control unit 20 compares the voltage Vdc of the smoothing capacitor 4 with the first set value V1 ′ (step S11).
  • the main control unit 20 compares the voltage Vdc of the smoothing capacitor 4 with the second set value V2 (step S12).
  • the main control unit 20 sets the torque component current Iq in the sensorless vector control unit 50 to a negative value, thereby The inverter 10 is operated in the regeneration mode (step S13).
  • the inverter 10 operates in the regenerative mode, the voltage Vdc of the smoothing capacitor 4 turns upward and the output frequency F of the inverter 10 gradually decreases.
  • step S14 When the output frequency F of the inverter 10 decreases to the allowable minimum operating frequency Fmin (YES in step S14), the main control unit 20 returns the torque component current Iq to a positive value and ends the operation of the inverter 10 in the regeneration mode. At the same time (step S15), the output torque (torque component current Iq) of the inverter 10 is controlled so that the output frequency F of the inverter 10 maintains the allowable minimum operating frequency Fmin (step S16). Then, the main control unit 20 returns to the process of step S1 while continuing this output torque control.
  • step S18 When the voltage Vdc of the smoothing capacitor 4 falls below the set value V1 ′ while continuing the output torque control of the inverter 10 (NO in step S1, YES in step S4, YES in step S11), the main control unit 20 deactivates the relay 30 (step S17), and cancels the control for maintaining the output frequency F at the allowable minimum operating frequency Fmin (output torque control of the inverter 10) (step S18).
  • the relay 30 is de-energized at a timing when the voltage Vdc falls below the first set value V1 ′ that is higher than the minimum voltage value V1 for preventing inrush current. Even if there is a time delay in opening and closing the relay contact 30a, inrush current can be reliably prevented.
  • the inverter 10 when the voltage Vdc of the smoothing capacitor 4 is lowered, the inverter 10 is operated in the regeneration mode at a timing when the voltage Vdc falls below the second specified value V2 higher than the first set value V1 ′, and the smoothing capacitor 4 is generated by the regenerative energy. Since the voltage Vdc is once changed to the rising side, the introduction of the resistor 3 based on the first set value V1 ′ can be made as late as possible. Thereby, the power loss in the resistor 3 can be reduced. Stopping of the inverter 10 based on the set value V0 can be avoided as much as possible. Other effects are the same as those of the first embodiment.
  • the magnitude of the load of the brushless DC motor M is determined by the magnitude of the fluctuation of the voltage Vdc of the smoothing capacitor 4.
  • the main control unit 20 has the following means (21) to (24) as main functions.
  • (21) The voltage of the smoothing capacitor 4 when the commercial three-phase AC power supply 1 is stable is obtained as a reference voltage, and the difference between the reference voltage and the voltage of the smoothing capacitor 4 (the detection voltage of the voltage detection unit 21) Vdc at this time Calculation means for obtaining the change amount ⁇ Vdc.
  • the reference voltage for example, an average value Vdcx of the voltage Vdc of the smoothing capacitor 4 over a predetermined time is obtained.
  • the average value Vdcx is a value obtained by integrating the voltage Vdc over a long period of time, and is obtained by, for example, low-pass filter processing with a large time constant.
  • First control means for closing the relay contact 30a by closing the relay 30 when the voltage of the smoothing capacitor 4 (detection voltage of the voltage detection unit 21) Vdc rises to the second set value V2 or more.
  • Third control means for opening the relay contact 30a by opening the relay 30 when the determination result is a medium load or a heavy load and the voltage Vdc of the smoothing capacitor 4 falls below the second set value V2.
  • Other configurations are the same as those of the first embodiment.
  • the main control unit 20 sequentially obtains an average value Vdcx of the voltage Vdc of the smoothing capacitor 4 by, for example, a low-pass filter process having a large time constant, and calculates a difference between the average value Vdcx and the current voltage Vdc of the smoothing capacitor 4 as a voltage change amount. It calculates as (DELTA) Vdc (step S0).
  • the main control unit 20 compares the voltage Vdc of the smoothing capacitor 4 with the specified value V2 when the voltage Vdc of the smoothing capacitor 4 increases (YES in Step S1) (Step S2).
  • the main control unit 20 sets the relay drive signal D to a high level based on the determination that the inrush current has been eliminated.
  • the transistor 22 is turned on, thereby energizing (closing operation) the relay 30 (step S3). By this energization, the relay contact 30 a is closed, a short circuit path for the resistor 3 is formed, and the resistor 3 is disconnected from the energization path between the converter 2 and the smoothing capacitor 4.
  • step S5a When the voltage Vdc of the smoothing capacitor 4 decreases (NO in step S1, YES in step S4), the main control unit 20 compares the obtained voltage change amount ⁇ Vdc with the predetermined amount ⁇ Vs (step S5a).
  • step S5a When the voltage change amount ⁇ Vdc is as small as less than the predetermined amount ⁇ Vs (YES in step S5a), the main control unit 20 determines that the load is a light load less than the predetermined value and the voltage Vdc of the smoothing capacitor 4 1 set value V1 'is compared (step S6). When the voltage Vdc of the smoothing capacitor 4 falls below the set value V1 ′ (YES in step S6), the main control unit 20 sets the relay drive signal D to a low level to turn off the transistor 22 and thereby the relay 30 is deactivated (step S7). By deactivating the relay 30, the relay contact 30a is opened and the resistor 3 is turned on.
  • the main control unit 20 determines the voltage of the smoothing capacitor 4 based on the determination that the load is a medium load or a heavy load greater than the predetermined value. Vdc and the second set value V2 are compared (step S8). When the voltage Vdc of the smoothing capacitor 4 falls below the second set value V2 (YES in step S8), the main control unit 20 sets the relay drive signal D to a low level and turns off the transistor 22, thereby The relay 30 is de-energized (step S7). By deactivating the relay 30, the relay contact 30a is opened and the resistor 3 is turned on.
  • the average value Vdcx of the voltage Vdc of the smoothing capacitor 4 is sequentially obtained as the reference voltage, and the difference between the average value Vdcx and the current voltage Vdc of the smoothing capacitor 4 is obtained as the voltage change amount ⁇ Vdc.
  • the magnitude of the load is determined from the amount ⁇ Vdc, the first set value V1 ′ is selected for deactivation of the relay 30 at light load, and the second higher than the first set value V1 ′ at medium load or heavy load.
  • the average value Vdcx of the voltage Vdc of the smoothing capacitor 4 is used as the reference voltage.
  • the voltage Vdc before a predetermined time in which a fluctuation such as a drop in the power supply voltage occurs is stored and used as the reference voltage. It may be used as
  • the specified value V2 for relay energization for the rising voltage Vdc is used as it is as the second setting value for relay de-energization for the falling voltage Vdc. It is not limited to. That is, the second set value may be a value higher than the set value V1 ′, and may be determined as appropriate according to the time delay of opening and closing of the relay 30 and the power consumption of the inverter 10.
  • SYMBOLS 1 Commercial three-phase alternating current power supply, 2 ... Converter, 3 ... Resistor for inrush current prevention, 4 ... Room smoothing capacitor, 10 ... Inverter, M ... Brushless DC motor (load), 11, 12, 13 ... Current sensor, DESCRIPTION OF SYMBOLS 20 ... Main control part, 21 ... Voltage detection part, 22 ... NPN type transistor, 30 ... Relay, 30a ... Relay contact, 50 ... Sensorless vector control part

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  • Power Engineering (AREA)
  • Inverter Devices (AREA)
  • Rectifiers (AREA)

Abstract

La présente invention concerne une résistance (3) de prévention de courant d'appel disposée trouve sur le trajet du courant entre un convertisseur (2) et un condensateur de lissage (4) et le contact (30a) d'un relais (30) connecté en parallèle avec la résistance (3). Lorsque la tension du condensateur de lissage (4) s'élève à une valeur spécifiée ou plus, le relais (30) est autorisé à effectuer une opération de fermeture et lorsque la tension du condensateur de lissage (4) tombe à moins qu'une valeur fixée, le relais (30) est autorisé à effectuer une opération d'ouverture. La valeur de consigne est supérieure à la valeur de tension minimale du condensateur de lissage (4), qui est nécessaire pour que le courant s'écoulant à travers le convertisseur (2) ne dépasse pas le courant maximum admissible du convertisseur (2). Selon ce dispositif de conversion de puissance, le courant d'appel peut être prévenu de façon fiable.
PCT/JP2015/060852 2014-04-17 2015-04-07 Dispositif de conversion de puissance WO2015159760A1 (fr)

Priority Applications (2)

Application Number Priority Date Filing Date Title
CN201580003687.7A CN105874702B (zh) 2014-04-17 2015-04-07 电力变换装置
JP2016513728A JP6255088B2 (ja) 2014-04-17 2015-04-07 電力変換装置

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JP2018014813A (ja) * 2016-07-20 2018-01-25 東芝シュネデール・インバータ株式会社 インバータ装置
EP3379712A4 (fr) * 2015-11-18 2019-07-10 Hitachi Industrial Equipment Systems Co., Ltd. Dispositif de conversion de puissance

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CN110098722B (zh) * 2019-05-06 2021-04-13 阳光电源股份有限公司 一种切换方法、装置及系统

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JPS62196072A (ja) * 1986-02-21 1987-08-29 Mitsubishi Electric Corp インバ−タ装置の突入電流制限回路
JPS63124766A (ja) * 1986-11-13 1988-05-28 Matsushita Electric Ind Co Ltd 突入電流制限回路
JPS63262026A (ja) * 1987-04-16 1988-10-28 日本電気株式会社 Ａｃ−ｄｃスイツチング電源入力電圧監視回路
JP2012147548A (ja) * 2011-01-11 2012-08-02 Konica Minolta Business Technologies Inc 電源装置

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JPS62196072A (ja) * 1986-02-21 1987-08-29 Mitsubishi Electric Corp インバ−タ装置の突入電流制限回路
JPS63124766A (ja) * 1986-11-13 1988-05-28 Matsushita Electric Ind Co Ltd 突入電流制限回路
JPS63262026A (ja) * 1987-04-16 1988-10-28 日本電気株式会社 Ａｃ−ｄｃスイツチング電源入力電圧監視回路
JP2012147548A (ja) * 2011-01-11 2012-08-02 Konica Minolta Business Technologies Inc 電源装置

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Publication number Priority date Publication date Assignee Title
EP3379712A4 (fr) * 2015-11-18 2019-07-10 Hitachi Industrial Equipment Systems Co., Ltd. Dispositif de conversion de puissance
JP2018014813A (ja) * 2016-07-20 2018-01-25 東芝シュネデール・インバータ株式会社 インバータ装置

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