WO2014136621A1 - 非相反伝送線路装置 - Google Patents
非相反伝送線路装置 Download PDFInfo
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- WO2014136621A1 WO2014136621A1 PCT/JP2014/054552 JP2014054552W WO2014136621A1 WO 2014136621 A1 WO2014136621 A1 WO 2014136621A1 JP 2014054552 W JP2014054552 W JP 2014054552W WO 2014136621 A1 WO2014136621 A1 WO 2014136621A1
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- transmission line
- nonreciprocal
- stub
- line device
- angular frequency
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P1/00—Auxiliary devices
- H01P1/18—Phase-shifters
- H01P1/19—Phase-shifters using a ferromagnetic device
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P1/00—Auxiliary devices
- H01P1/32—Non-reciprocal transmission devices
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P3/00—Waveguides; Transmission lines of the waveguide type
- H01P3/02—Waveguides; Transmission lines of the waveguide type with two longitudinal conductors
- H01P3/08—Microstrips; Strip lines
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
- H01Q13/20—Non-resonant leaky-waveguide or transmission-line antennas; Equivalent structures causing radiation along the transmission path of a guided wave
Definitions
- the present invention relates to a non-reciprocal transmission line device in which a forward propagation constant and a reverse propagation constant are different from each other, and an antenna device including the non-reciprocal transmission line device.
- a right / left-handed composite transmission line (hereinafter referred to as a CRLH (Composite Right / Left-Handed) transmission line) is known.
- the CRLH transmission line has a negative effective permeability and a negative effective permittivity in a predetermined frequency band, and the capacitive element is substantially periodically arranged in a series branch of the line at an interval sufficiently smaller than the wavelength.
- the inductive element is inserted into the shunt branch substantially periodically.
- a nonreciprocal (also called nonreciprocal) phase-shifted CRLH transmission line in which a function of nonreciprocal transmission is added to the CRLH transmission line has been proposed (see, for example, Patent Documents 1 to 3).
- the nonreciprocal phase-shifted CRLH transmission line can exhibit a positive refractive index when an electromagnetic wave having the same frequency propagates in the forward direction, and can exhibit a negative refractive index when propagated in the reverse direction.
- a transmission line resonator When a transmission line resonator is configured using a nonreciprocal phase-shifting CRLH transmission line, the resonator size can be freely changed without changing the resonance frequency. Further, the electromagnetic field distribution on the resonator is similar to the electromagnetic field distribution on the traveling wave resonator. For this reason, using a transmission line resonator using a nonreciprocal phase-shifted CRLH transmission line, the amplitude of the electromagnetic field is uniform and the phase of the electromagnetic field changes linearly with a constant gradient along the line. A traveling wave resonator can be constructed. At this time, the phase gradient of the electromagnetic field distribution on the resonator is determined by the irreversible phase shift characteristic of the transmission line constituting the resonator.
- a transmission line device using a nonreciprocal phase-shifted CRLH transmission line is referred to as a nonreciprocal transmission line device or a nonreciprocal transmission line device.
- Non-Patent Document 1 An antenna based on a pseudo traveling wave resonator that has been greatly developed from a zeroth-order resonator (see, for example, Non-Patent Document 1) has been proposed, although it is more compact than a conventional leaky wave antenna. Without increasing gain and directivity.
- non-reciprocal transmission line devices proposed so far have a structure in which a vertically magnetized ferrite rod is embedded under the central strip line of a conventional right / left-handed composite transmission line device composed of a microstrip line. Is adopted. At this time, the direction of the radiation beam from the antenna device provided with the pseudo traveling wave resonator composed of the nonreciprocal transmission line device is determined by the phase gradient of the electromagnetic field distribution on the resonator. If the ferrite is a soft magnetic material, the irreversible phase shift characteristic of the line is changed by changing the magnitude or direction of the externally applied magnetic field, so that beam scanning can be performed.
- Non-Patent Document 1 it is proposed to apply a pseudo traveling wave resonator including a nonreciprocal transmission line device to a beam scanning antenna.
- the beam scanning antenna provided with the pseudo traveling wave resonator has a drawback that the operation band is narrow, it has a very high radiation efficiency compared with the conventional leaky wave antenna.
- Beam squint is a well-known phenomenon in conventional phased array antennas, and is a phenomenon in which the beam radiation angle varies with frequency. As a result, the operating bandwidth is suppressed (for example, see Non-Patent Document 6).
- the main cause of beam squint is the dispersibility of delay elements.
- One of the methods for solving this is a tunable like an active CRLH delay element described in Non-Patent Document 8. Use a simple time delay element. In the case of CRLH metamaterial, such a compensation circuit does not make sense, and beam squint reduction was possible only in the upper band of both the series resonant frequency of the series branch and the parallel resonant frequency of the shunt branch. (For example, refer nonpatent literature 7.).
- An object of the present invention is to solve the above problems and provide a nonreciprocal transmission line device that does not substantially generate a beam squint in the vicinity of the center frequency of an operating band and an antenna device including the nonreciprocal transmission line device. is there.
- a non-reciprocal transmission line device includes a microwave transmission line part, a series branch circuit that equivalently includes a capacitive element, and an inductive element provided by branching from the transmission line part. And at least one unit cell having a circuit of first and second shunt branches (parallel branches) that equivalently includes a cascade connection between the first and second ports, and forward propagation.
- the transmission line part of each unit cell is magnetized in a direction different from the propagation direction of the microwave and has a gyro anisotropy or is magnetized by an external magnetic field
- the first parallel branch circuit is a first stub conductor having a first electrical length
- the second parallel branch circuit is a second stub conductor having a second electrical length shorter than the first electrical length;
- the function is a function proportional to an operating angular frequency.
- the first stub conductor has a first admittance
- the second stub conductor has a second admittance
- the first and second electrical lengths are (A) the first admittance substantially coincides with the second admittance at a predetermined operating angular frequency lower than the operating angular frequency at the intersection; and (b) the first admittance at the predetermined operating angular frequency.
- Each imaginary part of the first and second admittances is negative.
- the first stub conductor is a short-circuit stub and the first electrical length is set to be longer than 1 ⁇ 2 of the guide wavelength.
- the second stub conductor is a short-circuit stub and the second electric length is set to be shorter than 1 ⁇ 4 of the guide wavelength.
- the first stub conductor is an open stub and the first electrical length is set to be longer than 1 ⁇ 4 of the guide wavelength
- the second stub conductor is a short-circuit stub and the second electrical length is set to be shorter than 1 ⁇ 4 of the guide wavelength.
- the nonreciprocal transmission line device further includes a ground conductor provided between the first stub conductors and shielding between the first stub conductors.
- An antenna device is characterized by including the first or second nonreciprocal transmission line device.
- FIG. 1 It is a block diagram which shows the structure of the nonreciprocal transmission line apparatus 70B comprised by connecting the unit cells 60B of FIG. 2 in cascade. It is a block diagram which shows the structure of 70 C of nonreciprocal transmission line apparatuses comprised by connecting the unit cell 60C of FIG. 3 in cascade. It is a block diagram which shows the structure of nonreciprocal transmission line apparatus 70D comprised by connecting the unit cell 60D of FIG. 4 in cascade. It is a perspective view which shows the structure of the nonreciprocal transmission line apparatus 70E which concerns on embodiment of this invention. It is a perspective view which shows the structure of the nonreciprocal transmission line apparatus 70E which concerns on the modification of embodiment of this invention. FIG.
- 13B is a longitudinal sectional view of a ferrite square bar 15A in the irreversible line portion NRS of FIG. 13A. It is a perspective view which shows the structure of the nonreciprocal transmission line apparatus 70G which concerns on a comparative example. It is a graph which shows the simulation calculation value of the frequency characteristic of the dispersion
- FIG. 18 It is a top view which shows the specific structure of the nonreciprocal transmission line apparatus 70E of FIG. 13A. Simulation calculations of the dispersion curve and the frequency characteristic of the nonreciprocal phase shift amount beta NR nonreciprocal transmission line apparatus 70E of Figure 13A and the non-reciprocal transmission line apparatus 70E of Figure 13A the experimental values when formed as shown in FIG. 18 It is a graph to show. It is a perspective view which shows the structure of the nonreciprocal transmission line apparatus 70F which concerns on the modification of embodiment of this invention. It is a perspective view which shows the structure of the modification of the nonreciprocal transmission line apparatus 70F of FIG. 20A.
- FIG. 22 is an enlarged view of FIG. 21. It is a top view which shows typically the structure of the nonreciprocal transmission line apparatus 70F when the stub conductor 13A of FIG. 20A is an open stub.
- 24 is a graph showing the operating angular frequency dependency of admittances Y 1 and Y 2 and the frequency dependency of the irreversible phase shift amount ⁇ NR in the non-reciprocal transmission line device 70F of FIG.
- FIG. 26 is a perspective view of the nonreciprocal transmission line device 70 ⁇ / b> F of FIG. 25. It is a graph which shows the simulation calculation value of the frequency characteristic of the dispersion
- FIG. 26 is a perspective view illustrating a configuration of a pseudo traveling wave resonance antenna device using the nonreciprocal transmission line device 70 ⁇ / b> F of FIG. 25.
- It is a numerical calculation result of the pseudo traveling wave resonance antenna apparatus of FIG. 31A and is a graph showing the normalized amplitude of the magnetic field distribution and the electric field distribution along the longitudinal direction of the nonreciprocal transmission line apparatus 70F.
- FIG. 31A It is a numerical calculation result of the pseudo traveling wave resonance antenna apparatus of FIG. 31A, and is a graph showing the phase gradient of the magnetic field distribution along the longitudinal direction of the nonreciprocal transmission line apparatus 70F. It is a numerical calculation result of the pseudo traveling wave resonance antenna apparatus of FIG. 31A, and shows a frequency characteristic of a radiation beam angle in a broad side direction of the pseudo traveling wave resonance antenna apparatus. It is a numerical calculation result of the pseudo traveling wave resonance antenna apparatus of FIG. 31A, and shows a radiation pattern on a plane including the longitudinal direction of the pseudo traveling wave resonance antenna apparatus and the normal line of the substrate.
- FIG. 31B is a photograph showing a prototype example of the pseudo traveling wave resonance antenna apparatus of FIG. 31A.
- 32B is a graph showing experimental results of the pseudo traveling wave resonance antenna apparatus according to the prototype of FIG. 32A and showing the frequency characteristics of the radiation beam angle in the broadside direction of the pseudo traveling wave resonance antenna apparatus.
- 32B is a graph showing an experimental result of the pseudo traveling wave resonance antenna apparatus according to the prototype of FIG. 32A and showing a radiation pattern on a plane including the longitudinal direction of the pseudo traveling wave resonance antenna apparatus and the normal line of the substrate.
- nonreciprocal transmission line device also referred to as a non-reciprocal transmission line device
- FIGS. 1-10 the basic configuration and operation principle of a nonreciprocal transmission line device (also referred to as a non-reciprocal transmission line device) according to the present invention will be described with reference to FIGS.
- the numerical formula used in this specification the number enclosed in the parenthesis shown after each formula is referred.
- the nonreciprocal transmission line devices 70A to 70F according to the embodiments of the present invention are configured by cascading unit cells of a transmission line.
- 1 to 4 are equivalent circuit diagrams of exemplary transmission line unit cells 60A to 60D in the nonreciprocal transmission line device according to the embodiment of the present invention.
- each unit cell includes a transmission line portion having a nonreciprocal phase transition characteristic having different propagation constants in the forward direction and the reverse direction, and a capacitive element is equivalent to a series branch circuit and an inductive element is equivalent to a parallel branch circuit. (See FIGS. 1 to 4).
- a circuit or device to which the configuration of the nonreciprocal transmission line device according to the present invention can be applied is used in microwaves, millimeter waves, quasi-millimeter waves, terahertz waves such as strip lines, microstrip lines, slot lines, coplanar lines, etc.
- printed circuit board circuits, waveguides, dielectric lines, etc. in addition to these, all configurations that support waveguide modes or attenuation modes including plasmons, polaritons, magnons, etc., or combinations thereof, can be described as equivalent circuits Including all free space.
- the electromagnetic waves transmitted by the nonreciprocal transmission line device include, for example, microwaves, millimeter waves, quasi-millimeter waves, and terahertz waves having a frequency band of UHF (Ultra High Frequency) band or higher. It is called “microwave”.
- UHF Ultra High Frequency
- a transmission line device having non-reciprocal phase shift characteristics includes a material having gyro anisotropy in part or in whole among the above-described transmission lines, and a magnetization direction different from the propagation direction of electromagnetic waves (more preferably Is configured using a transmission line having a structure that is asymmetric with respect to a plane formed by the propagation direction and the magnetization direction.
- a transmission line having non-reciprocal phase shift characteristics a lumped constant element having an equivalent non-reciprocal phase shift function and sufficiently smaller than the wavelength can be used in addition to the transmission line described above.
- a material having gyro anisotropy includes a dielectric constant tensor or a magnetic permeability tensor representing the characteristics of a material by spontaneous magnetization, magnetization induced by a direct-current or low-frequency magnetic field applied from the outside, or circular motion of a free charge, or its tensor. It includes all cases where both are expressed as states with gyro anisotropy.
- Specific examples of materials having gyro anisotropy include ferrimagnetic materials such as ferrite used in microwaves and millimeter waves, ferromagnetic materials, solid plasmas (semiconductor materials, etc.) and liquids, gas plasma media, and finer materials. Examples thereof include a magnetic artificial medium constituted by processing or the like.
- Capacitive elements inserted in series branch circuits are not limited to capacitors that are often used in electric circuits, distributed constant capacitors used in microwaves, millimeter waves, etc., but equivalently, they propagate through transmission lines. It may be a circuit or a circuit element in which the effective permeability of the electromagnetic wave mode has a negative value.
- a microwave circuit that operates in a waveguide mode or an attenuation mode having a negative effective permeability can be used, such as an edge mode that propagates in a negative direction.
- the capacitive element inserted into the series branch circuit may be a series connection, a parallel connection, or a combination of a capacitive element and an inductive element other than those described above.
- the element or circuit of the part to be inserted may be capacitive as a whole.
- Inductive elements inserted into parallel branch circuits are not only lumped constant type elements such as coils used in electric circuits, and distributed constant type inductive elements such as short-circuited stub conductors used in microwaves and millimeter waves.
- a circuit or an element having a negative effective dielectric constant of the electromagnetic wave mode propagating through the transmission line can be used.
- the parallel branch In order to show a negative effective dielectric constant, it is necessary to describe the parallel branch equivalently as a transmission line that operates predominantly as an inductive element.
- Spatial arrangement including at least one electric resonator such as a thin metal wire or metal sphere, or a spatial arrangement of a dielectric resonator in an electric resonance state as well as a metal, or a waveguide in which the TE mode is in the cutoff region
- a microwave circuit that operates in a waveguide mode or an attenuation mode having a negative effective dielectric constant, such as a tube or a parallel plate line, can be used.
- the inductive element inserted into the parallel branch circuit may be a series connection, a parallel connection, or a combination of a capacitive element and an inductive element other than those described above.
- the part to be inserted may be a circuit or an element that exhibits inductivity as a whole.
- the equivalent circuit of the line includes both a nonreciprocal phase transition portion and a series capacitance element portion.
- the equivalent circuit of the same line includes both a nonreciprocal phase transition portion and a parallel inductive element portion.
- 1 and 2 show cases where the unit cells 60A and 60B have an asymmetric T-type structure and an asymmetric ⁇ -type structure, respectively.
- 3 and 4 show cases where the unit cells 60C and 60D have a symmetric T-type structure and a symmetric ⁇ -type structure, respectively, as simpler cases.
- the line structures shown in FIGS. 1 to 4 are simple and have predetermined line lengths (the line lengths p1 and p2 in FIGS. 1 and 2 and the line length p / 2 in FIGS. 3 and 4), respectively.
- a capacitive element or a capacitive network is inserted into a serial branch circuit of a transmission line including two transmission line portions 61 and 62, and an inductive element or an inductive network is inserted into a parallel branch circuit. ing.
- capacitors C1 and C2 and an inductor L are respectively inserted.
- the capacitor C and the inductors L1 and L2 are illustrated as being inserted.
- Each of the transmission line portions 61 and 62 is configured to have a nonreciprocal phase transition characteristic in which the propagation constants in the forward direction and the reverse direction are different.
- An imaginary part that is, a phase constant is used.
- the phase constant and the characteristic impedance in the forward direction (referring to the direction from the port P11 to the port P12) are represented as ⁇ Np1 and Z p1 , respectively, and the reverse direction (from the port P12) These are denoted as ⁇ Nm1 and Z m1 respectively.
- phase constant and the characteristic impedance in the forward direction are represented as ⁇ Np2 and Z p2 , respectively, and those in the reverse direction are represented as ⁇ Nm2 and Z m2 , respectively.
- 1 and 2 is asymmetric in the two transmission line portions 61 and 62, but the transmission line in FIGS.
- ⁇ and ⁇ represent the operating angular frequency and the phase constant of the electromagnetic wave propagating along the periodic structure, respectively. Since Expression (1) represents the relationship between the operating angular frequency ⁇ and the phase constant ⁇ , it becomes a dispersion relation ( ⁇ - ⁇ diagram).
- FIG. 5 is a graph showing a dispersion curve in a non-equilibrium state in a reciprocal transmission line device according to the prior art
- FIG. 6 is a graph showing a dispersion curve in a balanced state in the reciprocal transmission line device according to the prior art. It is.
- the graphs of FIGS. 5 and 6 show the characteristics of the angular frequency ⁇ with respect to the normalized phase constant ⁇ ⁇ p / ⁇ .
- a typical dispersion curve is represented as shown in FIG. 5, and generally a right-handed (RH) transmission characteristic and a left-handed (LH) transmission. A forbidden band appears between the bands showing the characteristics.
- RH right-handed
- LH left-handed
- the result of the equation (5) is that the impedance ⁇ (L / C) formed by the capacitor C that is a capacitive element inserted in the series branch circuit and the inductor L that is an inductive element inserted in the parallel branch circuit. but if the same as the characteristic impedance Z p of the insertion destination of the transmission line portions 61 and 62 are those that no gap, which is a kind of impedance matching condition.
- the dispersion curve in that case is shown in FIG.
- FIG. 7 is a graph illustrating a dispersion curve in a non-equilibrium state in the non-reciprocal transmission line device according to the embodiment
- FIG. 8 illustrates a dispersion curve in a balanced state in the non-reciprocal transmission line device according to the embodiment. It is a graph to show.
- the non-reciprocal transmission line device is greatly different from the reciprocal transmission line device in that the symmetry axis of the dispersion curve is shifted from the ⁇ axis to the right side or the left side, which is obtained from the equation (1).
- the nonreciprocal phase shift amount ⁇ NR is obtained by using forward and reverse phase constants ⁇ p and ⁇ m instead of the formula (6). Can also be expressed. As a result, it can be classified into the following five types of transmission bands (A) to (E).
- B The forward direction is left-handed transmission, and the backward direction has a propagation constant of zero and an in-tube wavelength of infinity.
- C Left-handed transmission in the forward direction and right-handed transmission in the reverse direction.
- D Right-handed transmission is in the forward direction, and the propagation constant is zero and the guide wavelength is infinite in the reverse direction.
- a stop band (prohibited band) appears in the center.
- the transmission band indicated by RH / LH in FIGS. 7 and 8 is used, even if a microwave signal is input bi-directionally (forward and reverse) to each port, The flow is directed in the same predetermined direction (left-handed transmission and right-handed transmission).
- Equation (1) becomes a quadratic equation regarding the angular frequency ⁇ 2 , and is a multiple solution in order not to generate a band gap. The following formula is obtained.
- ⁇ p and ⁇ p represent effective dielectric constant and permeability in the forward direction in the nonreciprocal transmission line portions 61 and 62 of the unit cells 60A to 60D, and ⁇ m and ⁇ m represent those in the reverse direction.
- the condition for preventing the gap from occurring near the intersection of the two modes is the impedance matching condition, similar to Equation (5) of the reciprocal transmission line device.
- the inductor L and the capacitor C may be inserted so that matching can be achieved in either the forward direction or the reverse direction, and the impedance matching condition is more gradual than in the case of the reciprocal transmission line device.
- the entire nonreciprocal transmission line device includes at least one unit cell 60A to 60D shown in FIGS. 1 to 4 and is connected in cascade.
- the FIG. 9 is a block diagram showing a configuration of a nonreciprocal transmission line device 70A configured by cascading unit cells 60A of FIG. In FIG. 9, a plurality of unit cells 60A are connected in cascade between a port P1 and a port P2, thereby forming a nonreciprocal transmission line device 70A.
- FIG. 10 is a block diagram showing a configuration of a nonreciprocal transmission line device 70B configured by cascading unit cells 60B of FIG. In FIG.
- FIG. 10 is a block diagram showing a configuration of a nonreciprocal transmission line device 70C configured by cascading unit cells 60C of FIG.
- FIG. 11 is a block diagram showing a configuration of a nonreciprocal transmission line device 70C configured by cascading unit cells 60C of FIG.
- a plurality of unit cells 60C are connected in cascade between a port P1 and a port P2, thereby configuring a nonreciprocal transmission line device 70C.
- FIG. 12 is a block diagram showing a configuration of a nonreciprocal transmission line device 70D configured by cascading unit cells 60D of FIG. In FIG.
- a plurality of unit cells 60D are connected in cascade between a port P1 and a port P2, thereby constituting a nonreciprocal transmission line device 70D. Even when a plurality of unit cells 60A to 60D are connected in cascade, it is not always necessary to use a single type of unit cells 60A to 60D, but different types of unit cells can be combined. May be connected in cascade.
- the beam direction of the pseudo traveling wave resonator antenna device including the nonreciprocal transmission line devices 70A to 70F and the direction perpendicular to the dielectric substrate (hereinafter referred to as the radiation angle ⁇ ) is expressed by the following equation in the vicinity of the central angular frequency ⁇ C (see Non-Patent Document 1).
- ⁇ 0 is the phase constant of the electromagnetic wave in vacuum.
- the radiation angle of the radio wave ⁇ radiated from the non-reciprocal transmission line device 70A ⁇ 70B are operation
- the beam squint which is a phenomenon that changes according to the frequency
- the nonreciprocal phase shift amount ⁇ NR may be proportional to the operating angular frequency ⁇ in the vicinity of the central angular frequency ⁇ C.
- the nonreciprocal transmission line devices 70A to 70F according to the present embodiment and the following embodiments are configured to satisfy the equation (9), thereby preventing the occurrence of beam squint.
- FIG. 13A is a perspective view showing a configuration of a nonreciprocal transmission line device 70E according to the embodiment of the present invention.
- an irreversible transmission line device 70E includes a ground conductor 11 provided parallel to the XY plane, a ferrite square bar (ferrite rod) 15A extending along the Y axis on the ground conductor 11, and a ground conductor.
- 11 includes a dielectric substrate 10 provided on both the + X side and the ⁇ X side of the ferrite square bar 15A, a strip conductor 12, a stub conductor 13A, a stub conductor 13B, and a capacitor Cse. .
- the ferrite square bar 15A, the strip conductor 12, the stub conductor 13A, the stub conductor 13B, and the capacitor Cse constitute a microstrip line 12E extending between the ports P1 and P2 along the Y axis.
- the microwave signal is supplied from the port P1 or P2.
- the ferrite square bar 15A has spontaneous magnetization so that it is magnetized in a magnetization direction different from the propagation direction of electromagnetic waves and has gyro anisotropy.
- the saturation magnetization M S and the internal magnetic field H 0 of the ferrite square bar 15A are indicated by arrows.
- the magnetization direction is preferably a direction (for example, + Z direction) orthogonal to the propagation direction of the electromagnetic wave (direction along the Y axis).
- a ferrite square bar not having spontaneous magnetization may be used, and a magnetic field may be applied by the external magnetic field generator 80 of FIG. 13B.
- the microstrip line 12E is configured by cascading unit cells 60E of transmission lines having a periodic length p.
- Each unit cell 60E includes a strip conductor 12 extending along the Y-axis on the ferrite square bar 15A, a capacitor Cse, and stub conductors 13A and 13B.
- the capacitor Cse is connected to the + Y side end of the strip conductor 12, and the capacitor Cse is further connected to the strip conductor 12 of the unit cell 60E adjacent to the + Y side of the unit cell 60A. Accordingly, each capacitor Cse is inserted in series with the microstrip line 12E.
- capacitors having a capacitance 2Cse that is twice the capacitor Cse between the strip conductors 12 are inserted at both ends of the microstrip line 12E.
- the stub conductor 13A has an electrical length La and extends to the ⁇ X side of the strip conductor 12.
- the stub conductor 13B has an electrical length Lb shorter than the electrical length La, and extends to the + X side of the strip conductor 12.
- the stub conductors 13A and 13B are branched from the strip conductor 12 and provided as two parallel branch circuits corresponding to the inductor L (parallel branch circuit) of FIG. Specifically, the stub conductor 13A extends on the dielectric substrate 10 along the X axis in the ⁇ X direction, one end of which is connected to the strip conductor 12, and the other end is the end portion of the dielectric substrate 10 on the ⁇ X side.
- the ground conductor 11 is short-circuited via the ground conductor 17A (short-circuit stub).
- the stub conductor 13B extends on the dielectric substrate 10 along the X axis in the + X direction, one end of which is connected to the strip conductor 12, and the other end is grounded at the end of the dielectric substrate 10 on the + X side. Shorted to the ground conductor 11 via the conductor 17B.
- the stub conductors 13A and 13B depend on the propagation direction of the microstrip line 12E (for example, + Y direction or -Y direction: indicated by an arrow on the microstrip line 12E in FIG. 13A) and the magnetization direction (for example, + Z direction). It forms on a mutually different side with respect to the surface (YZ surface) to be formed.
- the stub conductors 13A and 13B function as inductive elements.
- the equivalent circuit of the unit cell 60E configured as described above is the same as the equivalent circuit of the unit cell 60A in FIG.
- the nonreciprocal transmission line device 70E of FIG. 13A is used to realize a resonance type leaky wave antenna.
- the nonreciprocal transmission line device 70E includes the microstrip line 12E provided between the ports P1 and P2 and embedded with the ferrite square bar 15A.
- stub conductors 13A and 13B which are strip conductors, and a capacitor Cse are periodically inserted into the microstrip line 12E with a periodic length p.
- the main mode of the nonreciprocal transmission line device 70E is the edge guide mode, and the stub conductors 13A and 13B are inserted asymmetrically with respect to the line, so the nonreciprocal transmission line device 70E exhibits nonreciprocal transmission characteristics.
- the structure of the nonreciprocal transmission line device 70E is formed by the propagation direction and the magnetization direction of the microstrip line 12E. Asymmetric with respect to the plane (YZ plane).
- the propagation constant in the forward direction (direction from port P1 to P2) and the propagation constant in the reverse direction (direction from port P2 to P1) are different from each other, the right-handed mode propagates in the forward direction, and the reverse direction.
- a state in which the left-handed mode propagates can be realized.
- the irreversible magnitude can be changed by adjusting the electrical lengths La and Lb of the stub conductors 13A and 13B.
- the electrical lengths La and Lb of the stub conductors 13A and 13B are set so that beam squint does not substantially occur in the antenna device using the nonreciprocal transmission line device 70E.
- the propagation characteristics of the TE mode propagating along the microstrip line 12E in which the ferrite rods 15A are embedded vary depending on the boundary conditions of the side surfaces on both sides of the microstrip line 12E.
- the inventors of the present application analyzed general irreversible dispersion characteristics of the nonreciprocal transmission line device 70E.
- ⁇ 0 represents a phase constant in vacuum.
- non-reciprocal phase shift beta NR as in equation (6), an average value of the phase constant beta p and beta m for the two propagation directions can power flow, the irreversible phase constant beta size It represents.
- the variation ⁇ of the radiation angle ⁇ due to the operation angular frequency omega is changed by ⁇ from the center angular frequency omega C is given approximately by the following equation in the non-patent document 1.
- nonreciprocal CRLH leaky wave antenna resonant type provided with a non-reciprocal transmission line device 70E, in order to prevent the occurrence of beam Quint in the vicinity of the center angular frequency omega C, in the vicinity of the center angular frequency omega C, nonreciprocal It needs only strictly proportional with respect to the amount of phase shift beta NR operating angular frequency omega.
- the leaky wave antenna resonant type using a non-reciprocal transmission line device 70E substantially the beam Quint
- the conditions of the stub conductors 13A and 13B not to be generated automatically are derived by eigenmode analysis.
- the nonreciprocal transmission line device 70E is analyzed by a combination of electromagnetic field analysis and a transmission line model.
- the nonreciprocal transmission line device 70E is an irreversible line having an electric length LNR in the Y-axis direction along the propagation direction of electromagnetic waves (direction along the Y-axis), as in Non-Patent Document 3.
- the portion (nonreciprocal section: NRS) and the reversible line portion (reciprocal section: RS) are handled separately.
- the pair of line portions NR and NRS becomes a T-type unit cell 60E having a periodic length p.
- the serial branch on either side of the cascaded unit cells 60E, lumped capacitor is inserted respectively having capacitance 2C se.
- FIG. 14 is a vertical cross-sectional view of the ferrite square bar 15A in the irreversible line portion NRS of FIG. 13A.
- the stub conductors 13A and 13B are provided for the microstrip line 12E between the ports P1 and P2, the ⁇ X side and the + X side of the microstrip line 12E.
- the boundary condition at each boundary is expressed using different equivalent admittances Y 1 and Y 2 .
- the admittances Y 1 and Y 2 are respectively provided by stub conductors 13A and 13B made of a finite-length microstrip line having a short-circuit termination or an open termination.
- stub conductors are not provided in either the ⁇ X direction or the + X direction with respect to the microstrip line 12E in which the ferrite square bar 15A is embedded. For this reason, the boundary conditions at the ⁇ X side and + X side boundaries of the microstrip line 12E are both magnetic walls (impedance is infinite).
- Non-Patent Document 2 When a magnetic wall type boundary condition is applied to the reversible line portion RS, a simple dispersion relation of the edge guide mode described in Non-Patent Document 2 is obtained.
- omega represents the operating angular frequency
- w is the width of the ferrite rectangular bar 15A
- c is the speed of light in vacuum
- epsilon r is the relative permittivity of the ferrite rectangular bar 15A
- mu ⁇ mu a is Polder relative permeability tensor of ferrite square bar 15A magnetized in the positive Z-axis direction Represents a diagonal component and a non-diagonal component.
- ⁇ 0 is the permeability of vacuum and ⁇ 0 is the permittivity of vacuum.
- k x which means the wave number in the horizontal direction is given by the following equation.
- the characteristic impedance is calculated from the electromagnetic field distribution as a ratio between the integral value of the pointing vector in the cross section and the surface current along the microstrip line 12E. Estimated. The relationship between the electric field component E Z of the electromagnetic wave and the magnetic field components H X and H Y can be obtained from the Maxwell equation. If there is no transmission loss, the characteristic impedance is reversible.
- the characteristics of the structure of the nonreciprocal transmission line device 70E can be obtained from the ABCD matrix F UC for the unit cell 60E.
- the dispersion relation is obtained by the following equation.
- ⁇ MM represents a complex propagation constant of a mode propagating along the periodic structure.
- non-reciprocal phase shift amount in the non-reversible line portion NRS can be approximately represented by a perturbation method.
- the magnitude of the nonreciprocal phase shift amount ⁇ NR is given by the following equation.
- ⁇ M is (
- This term represents the sum of the admittances Y 1 and Y 2 of the two stub conductors 13A and 13B (see Non-Patent Document 4).
- the imaginary part of the total admittance of the inductive stub having a negative dielectric constant takes a negative value. In the case of lossless, nonreciprocity appears only in the phase constant, as pointed out in Non-Patent Document 3, for example.
- FIG. 15 is a perspective view showing a configuration of a nonreciprocal transmission line device 70G according to a comparative example.
- the non-reciprocal transmission line device 70G of FIG. 15 is different from the non-reciprocal transmission line device 70E according to the present embodiment in that a unit cell 60G is provided instead of the unit cell 60E.
- the unit cell 60G is different from the unit cell 60E in that the stub conductor 13A is not provided and the stub conductor 13B is provided only on the + X side of the strip conductor 12.
- the stub conductor 13B is periodically inserted only on the + X side of the microstrip line 12E, and a propagation characteristic with a negative dielectric constant is obtained.
- the characteristic of the nonreciprocal transmission line device 70G is analyzed in a simple case in which a propagation characteristic having a negative dielectric constant is given.
- Figure 16 is a graph showing a simulation calculated values of the dispersion curve and the frequency characteristic of the nonreciprocal phase shift amount beta NR nonreciprocal transmission line apparatus 70G of Figure 15.
- FIG. 17 is a graph showing the simulation calculation of the frequency characteristic of the dispersion curve and nonreciprocal phase shift amount beta NR nonreciprocal transmission line apparatus 70E of Figure 13A.
- the non-reciprocal phase shift amount ⁇ NR is approximately inversely proportional to the operating angular frequency ⁇ . (See FIG. 16).
- the nonreciprocal phase shift amount ⁇ NR is equal to the operating angular frequency ⁇ . (See FIG. 17).
- the non-reciprocal transmission line apparatus 70G of Figure 15 by inserting the stub conductors 13B on only one side of a microstrip line 12E, first-order of the operation angular frequency ⁇ of the nonreciprocal phase shift amount beta NR
- the derivative d ⁇ NR ( ⁇ ) / d ⁇ is d ⁇ NR ( ⁇ ) / d ⁇ ⁇ 0 (see Non-Patent Documents 1, 3 and 4).
- the non-reciprocal transmission line apparatus 70E of Figure 13A inserting the stub conductors 13A and 13B on both sides of the microstrip line 12E, the center angular frequency omega predetermined operating angular frequency lower than the C omega Z when nonreciprocal phase shift amount beta NR is zero, the sign of the first derivative d ⁇ NR ( ⁇ ) / d ⁇ related to the operation angular frequency omega of the nonreciprocal phase shift amount beta NR is reversed, d.beta NR (omega) / D ⁇ > 0.
- the nonreciprocal phase shift amount beta NR is substantially proportional to the operating angular frequency omega in the vicinity of the center angular frequency omega C, it can be designed nonreciprocal transmission line device 70E as beam Quint does not substantially occur I understand.
- the admittances Y 1 and Y 2 are used. Take advantage of the fact that it varies with frequency.
- admittances Y 1 ( ⁇ ) and Y 2 ( ⁇ ) can be expressed by using a relational expression of input impedance in a finite-length microstrip line having a load impedance connected to the terminal.
- the input admittance when the termination is shorted or open, the input admittance includes a cot function or a tan function, so it has a singularity at a given frequency and exhibits discontinuities.
- a non-reciprocal transmission line device 70E simulation calculated values and 13A of the frequency characteristic of the dispersion curve and nonreciprocal phase shift amount beta NR nonreciprocal transmission line apparatus 70E of Figure 13A It is a graph which shows an experimental value when it forms.
- the phase constants ⁇ p and ⁇ m each simulation calculation values of the nonreciprocal phase shift amount beta NR which is calculated on the basis of the showing.
- the finite element method was used for the simulation.
- the central angular frequency ⁇ C of the antenna using the nonreciprocal transmission line device 70E is defined by the operating angular frequency of the intersection of two dispersion curves of the left-handed mode and the right-handed mode, and is 6.8 GHz in FIG. Can be confirmed. Further, in the vicinity of the central angular frequency ⁇ C , the nonreciprocal phase shift amount ⁇ NR is close to the ideal nonreciprocal phase shift amount ⁇ NRZ in which no beam squint is generated, and substantially no beam squint occurs. I understand that.
- FIG. 18 is a plan view showing a specific configuration of the nonreciprocal transmission line device 70E of FIG. 13A.
- an experimental model of the nonreciprocal transmission line device 70E was prototyped.
- a ferrite square bar 15A made of yttrium iron garnet (YIG) having a cross-sectional dimension of 0.8 mm ⁇ 0.8 mm is embedded under the microstrip line 12E.
- the stub conductors 13A and 13B were formed on the dielectric substrate 10 of Resolite (registered trademark) 2200.
- the electrical length La of the stub conductor 13A is set to 25 mm
- the electrical length Lb of the stub conductor 13B is set to 2.5 mm
- the width of the stub conductors 13A and 13B is set to 1 mm
- the periodic length of the unit cell 60E. p was set to 3 mm.
- the capacitance of the capacitor Cse was set to 0.5 pF so as to obtain a dispersion characteristic without a band gap between the right-handed mode and the left-handed mode.
- a ground conductor 18 having a width smaller than that of the stub conductor 13A is formed between adjacent stubs 13A.
- FIG. 19 shows the phase constants ⁇ p and ⁇ m and the non-reciprocal phase shift amount ⁇ NR when the non-reciprocal transmission line device 70E of FIG. 13A is prototyped as shown in FIG. As shown in FIG. 19, each experimental value agrees well with the simulation calculation value.
- the dispersion characteristics of the nonreciprocal phase shift amount beta NR is a non-reciprocal phase shift beta NRZ in an ideal case where Beams Quint is not generated in the pseudo traveling wave resonator antenna It matches well. That is, according to the non-reciprocal transmission line device 70E according to this embodiment, the center angular frequency omega C near the operating band beam Quint can realize an antenna device of a resonance type which does not substantially occur.
- a beam squint is not substantially generated in the antenna device using the nonreciprocal transmission line device 70E. Showed that it would be possible. Further, when a non-reciprocal transmission line device 70E was prototyped and transmission characteristics were measured, it was confirmed that the experimental values agreed well with the simulation calculation values. Therefore, if the nonreciprocal transmission line device 70E is applied to a resonance type leaky wave antenna, a beam scanning antenna device in which beam squint does not substantially occur can be realized.
- FIG. 20A is a perspective view showing a configuration of a nonreciprocal transmission line device 70F according to a modification of the embodiment of the present invention.
- the nonreciprocal transmission line device 70F is different from the nonreciprocal transmission line device 70E according to the embodiment in that a unit cell 60F is provided instead of the unit cell 60E.
- the unit cell 60F differs from the unit cell 60E only in that it further includes a capacitor Csh that is a chip capacitor. Only differences from the embodiment will be described below.
- one electrode of the capacitor Csh is connected to a predetermined connection point of the longer stub conductor 13A of the stub conductors 13A and 13B, while the other electrode of the capacitor Csh is connected via the via conductor 19.
- the ground conductor 11 To the ground conductor 11.
- the admittances Y 1 and Y 2 of the stub conductors 13A and 13B give frequency dependency to the boundary conditions of the ⁇ X side surface and the + X side surface of the microstrip line 12E.
- the stub conductors 13A and 13B having admittance Y 1 and Y 2 mutually different are inserted on both sides of the microstrip line 12E respectively, at a center angular frequency omega predetermined operating angular frequency lower than the C ⁇ Z ⁇ NR
- an equivalent admittance Y 1 of the longer stub conductors 13A which is grounded, and the characteristic impedance Z st of the microstrip line including a stub conductor 13A, and the effective dielectric constant epsilon st, the electrical length La of the stub conductors 13A Is expressed by the following formula.
- the fact that the nonreciprocal phase shift amount ⁇ NR ( ⁇ ) is an increasing function of the operating angular frequency ⁇ does not mean that the beam squint can be easily eliminated, and is described in the embodiment. Thus, the maximum radiation beam angle may be deteriorated.
- the admittance Y1 of the longer stub conductor 13A is adjusted by providing an additional capacitor Csh. Thereby, the controllability of the nonreciprocal phase shift amount ⁇ NR ( ⁇ ) can be improved as compared with the embodiment.
- the non-reciprocal transmission line device 70F is set so as to be substantially ⁇ NR ( ⁇ ) ⁇ in the vicinity of the central angular frequency ⁇ C.
- the magnetic field may be applied by the external magnetic field generator 80 of FIG. 20B using the ferrite square bar which does not have spontaneous magnetization.
- Figure 21 is a graph showing the simulation calculation of the frequency characteristic of the dispersion curve and nonreciprocal phase shift amount beta NR nonreciprocal transmission line device 70F of FIG. 20A
- FIG. 22 is an enlarged view of FIG. 21.
- the finite element method was used for the simulation.
- a ferrite square bar 15A made of yttrium iron garnet (YIG) having a cross-sectional dimension of 0.8 mm ⁇ 0.8 mm was embedded under the microstrip line 12E.
- YIG yttrium iron garnet
- the non-reciprocal phase shift beta NR becomes zero at a lower 5GHz than the frequency corresponding to the center angular frequency omega C
- setting the electrical length La of the stub conductors 13A to 25.5 mm the electrical length of the stub conductors 13B Lb was set to 1.3 mm, and the widths of the stub conductors 13A and 13B were set to 1 mm.
- the capacitance of the capacitor Csh is set to 0.4 pF so that beam squint is not substantially generated, and the capacitance of the capacitor Cse is set so that the dispersion characteristic has no band gap between the right-handed mode and the left-handed mode.
- the dielectric constant of the dielectric substrate 10 was set to 2.6.
- the electrical lengths La and Lb of the stub conductors 13A and 13B are set to 25.5 mm and 1.3 mm, respectively, and the nonreciprocal transmission line device 70F has a strong asymmetric structure with respect to the microstrip line 12E.
- the operating frequency ⁇ C / (2 ⁇ ) at the intersection of the two dispersion curves was 6.0 GHz.
- the non-reciprocal phase shift amount ⁇ NR is proportional to the frequency in the vicinity of the operating frequency ⁇ C / (2 ⁇ ) and is close to the non-reciprocal phase shift amount ⁇ NRZ when the beam squint does not occur completely.
- the magnitude of the obtained nonreciprocal phase shift amount ⁇ NRZ is converted into the radiation beam angle of the antenna device designed based on this structure, it was confirmed that the beam can be scanned up to 28 degrees.
- the nonreciprocal transmission line devices 70E and 70F are configured by cascading unit cells 60E or 60F between the ports P1 and P2, and the forward propagation constant and the reverse propagation constant. Are different from each other.
- each unit cell 60E and each unit cell 60F are branched from the transmission line portion 12 of the microwave, the capacitor Cse which is a series branch circuit equivalently including a capacitive element, and the transmission line portion 12, respectively.
- first and second parallel branch circuits that are provided and equivalently include inductive elements.
- the transmission line portion 12 is magnetized in a direction different from the propagation direction of the microwave and has spontaneous magnetization so as to have gyro anisotropy, or is magnetized by external magnetization.
- the circuit of the first parallel branch is a stub conductor 13A having an electrical length La
- the circuit of the second parallel branch is a stub conductor 13B having an electrical length Lb shorter than the electrical length La.
- a beam squint is substantially generated in the vicinity of the central angular frequency ⁇ C that is the operating angular frequency of the intersection of the two dispersion curves described above.
- the nonreciprocal phase shift amount beta NR has to be proportional to the operating angular frequency omega. That is, in the vicinity of the center angular frequency omega C, it is necessary to the following equation is substantially satisfied.
- the electric length Lb of the stub conductor 13B, first and admittance Y 2 of admittance Y 1 and the stub conductors 13B of the stub conductor 13A is less It is set so as to satisfy the second condition.
- the nonreciprocal phase shift amount ⁇ NR is 0 at a predetermined operating angular frequency ⁇ Z in the vicinity of the central angular frequency ⁇ C of the antenna device including the non-reciprocal transmission line device 70F and lower than the central angular frequency ⁇ C.
- ⁇ Z the operating angular frequency omega Z
- the second condition: the operation angular frequency omega Z described above, admittance Y 1 and Y 2 must both inductive (inductance). That is, in the operation angular frequency omega Z, so must the stub conductors 13A and 13B are inducible stub having a negative dielectric constant, Im (Y 1) Im (Y 2) ⁇ 0.
- one end of the stub conductor 13A is grounded, but may be opened.
- the inventors of the present application have the following additional electrical lengths La and Lb (La> Lb): It was found that it should be set to satisfy the third and fourth conditions. In each of the following conditions, ⁇ is the guide wavelength.
- the stub conductor 13A is a short-circuit stub.
- Third condition The stub conductor 13A is a short-circuit stub that satisfies La> ⁇ / 2.
- Second case (when the stub conductor 13A is an open stub): Third condition: The stub conductor 13A is an open stub that satisfies La> ⁇ / 4. Fourth condition: The stub conductor 13B is a short-circuit stub that satisfies Lb ⁇ / 4.
- a non-reciprocal phase shift amount ⁇ NR is obtained by additionally connecting a lumped constant capacitor such as a chip capacitor to a predetermined connection point of the stub conductor 13A.
- a lumped constant capacitor such as a chip capacitor
- FIG. 23 is a plan view schematically showing the configuration of the nonreciprocal transmission line device 70F when the stub conductor 13A of FIG. 20A is an open stub.
- FIG. 24 is a graph showing the operating angular frequency dependency of the admittances Y 1 and Y 2 and the frequency dependency of the irreversible phase shift amount ⁇ NR in the nonreciprocal transmission line device 70F of FIG.
- both stub conductors 13A and 13B operate as inductive stub conductors.
- the electrical length La is set so as to satisfy La> ⁇ / 4
- the electrical length Lb is set so as to satisfy Lb ⁇ / 4.
- admittance Y 1 becomes tangent function (tan) of the operation angular frequency omega.
- admittance Y 2 is a cotangent function related to the operation angular frequency ⁇ (cot).
- the center angular frequency omega C lower operating angular frequency omega Z from near and center angular frequency omega C of nonreciprocal phase shift beta NR becomes zero.
- admittance Y 1 and Y 2 is inductive (inductance)
- the imaginary part of the admittance Y 1 and Y 2 has a negative value.
- the nonreciprocal phase shift amount ⁇ NR has a factor proportional to (Y 2 ⁇ Y 1 ), which is dependent on the frequency dependence of the nonreciprocal phase shift amount ⁇ NR .
- the frequency is affected by the frequency dependence of (Y 2 -Y 1 ).
- the admittance Y 2 has no very slowly altered singularities for an operating angular frequency.
- the admittance Y 1 changes more rapidly than the admittance Y 2 with respect to the operating angular frequency, and has a plurality of periodic singularities.
- the operating angular frequency ⁇ Z at which the nonreciprocal phase shift amount ⁇ NR becomes zero is substantially determined by the operating angular frequency corresponding to the singular point of the admittance Y 1 .
- the admittance Y 2 changes more slowly than the admittance Y 1 , in the calculation of the nonreciprocal phase shift amount ⁇ NR (that is, the calculation of (Y 2 ⁇ Y 1 )), the nonreciprocal phase shift amount ⁇ NR It only acts to increase the value and shift to the right in FIG.
- the gradient d ⁇ NR / d ⁇ of the nonreciprocal phase shift amount ⁇ NR with respect to the operating angular frequency ⁇ is determined by the operating angular frequency dependency of (Y 2 -Y 1 ).
- the frequency of this nonreciprocal phase shift amount ⁇ NR The dependence also determines the maximum radiation beam angle. Specifically, the maximum radiation beam angle increases as the value of d ⁇ NR / d ⁇ increases.
- the nonreciprocal transmission line device 70E has a capacitor Csh connected to a predetermined connection point of the longer stub conductor 13A.
- the maximum radiation beam angle can be greatly improved while maintaining a state in which the beam squint is not substantially generated.
- FIG. 25 is a plan view showing a specific configuration used for the simulation of the nonreciprocal transmission line device 70F of FIG. 23, and FIG. 26 is a perspective view of the nonreciprocal transmission line device 70F of FIG.
- the width of the strip conductor 12 is set to 0.8 mm
- the electrical length La of the stub conductor 13A is set to 14 mm
- the electrical length Lb of the stub conductor 13B is set to 1.7 mm
- the stub conductors 13A and 13B are set.
- the width of each was set to 1 mm
- the distance between the strip conductor 12 and the capacitor Csh was set to 2.65 mm.
- the cycle length p was set to 3 mm, the cycle number was set to 15, the capacitance of the capacitor Cse was set to 0.4 pF, and the capacitance of the capacitor Csh was set to 0.1 pF.
- the stub conductor 13A is an open stub, and the stub conductor 13B is a short-circuit stub.
- the reflector R1 is connected to the port P1
- the reflector R2 is connected to the port P2
- the feeder line F is connected to the reflector R1.
- the width of the reflectors R1 and R2 in the X-axis direction was set to 4.5 mm.
- the width of the reflector R1 in the Y-axis direction is set to 19.2 mm, which is about 3/4 of the in-tube wavelength, and the width of the reflector R2 in the Y-axis direction is about 1/4 of the in-tube wavelength.
- the cross-sectional dimension of the ferrite square bar 15A was set to 0.8 mm ⁇ 0.8 mm.
- a ground conductor 50 having a width narrower than that of the stub conductor 13A is formed between the adjacent stubs 13A.
- Figure 27 is a graph showing a simulation calculated values of the dispersion curve and the frequency characteristic of the nonreciprocal phase shift amount beta NR nonreciprocal transmission line device 70F in Figure 25. As shown in FIG. 27, the simulation calculation value of the non-reciprocal phase shift beta NR It can be seen that good agreement to the nonreciprocal phase shift amount beta NRZ when Beams Quint is quite ideal not occur.
- FIG. 28 is a graph showing the radiation characteristics of the nonreciprocal transmission line device 70F of FIG. FIG. 28 shows a case where the operating frequency is 7.35 GHz. From FIG. 28, it can be confirmed that the radiation angle ⁇ of the main beam is 19 degrees inclined from 0 degrees.
- FIG. 29 is a graph showing the frequency characteristic of the radiation angle ⁇ of the nonreciprocal transmission line device 70F of FIG. 25, and FIG. 30 is a graph showing the frequency characteristic of the radiation gain of the nonreciprocal transmission line device 70F of FIG. .
- the radiation angle ⁇ is substantially constant from 7.20 GHz to 7.55 GHz. Therefore, it can be seen that an operation ratio band of 4% or more in which beam squint is not substantially generated is realized. That is, according to this embodiment, the operation ratio band in which beam squint does not substantially occur is 2% when the stub conductor is provided only on one side of the strip conductor of the microstrip line 12E (Non-patent Document 1). (See reference).
- FIG. 31A is a perspective view showing a configuration of a pseudo traveling wave resonance antenna device using the nonreciprocal transmission line device 70F of FIG.
- the lengths of the two reflectors R1 and R2 are adjusted so as to be short-circuited at the ports P1 and P2, respectively, when viewed from the nonreciprocal transmission line apparatus 70F.
- the reflector R2 on the side connected to the feeder line F has a structure that is longer by a half wavelength than the reflector R2 on the non-connection side in order to secure the connection portion of the feeder line F, and as a result.
- the reflector R2 employs a shielding structure by a metal shielding plate 90.
- Figure 31B is a numerical calculation results of a pseudo traveling wave resonance antenna device of FIG. 31A, a graph showing a frequency characteristic of the reflection coefficient S 11 of the case from the feed line F viewed pseudo traveling wave resonance antenna device.
- the graph of FIG. 31B means that the antenna apparatus resonates at three frequencies at which reflection is reduced, and as a result, electromagnetic waves are radiated from the antenna apparatus.
- resonance in the 6.5 GHz and 7.4 GHz bands is half-wave resonance in the CRLH line.
- the resonance state at 6.9 GHz operates as the pseudo traveling wave resonance noticed in the present embodiment.
- FIG. 31C is a graph showing the numerical calculation results of the pseudo traveling wave resonance antenna apparatus of FIG. 31A and the normalized amplitudes of the magnetic field distribution and electric field distribution along the longitudinal direction of the nonreciprocal transmission line apparatus 70F.
- the magnetic field becomes the dominant resonance, and the electric field component becomes small.
- FIG. 31D is a graph showing the numerical calculation result of the pseudo traveling wave resonance antenna apparatus of FIG. 31A and showing the phase gradient of the magnetic field distribution along the longitudinal direction of the nonreciprocal transmission line apparatus 70F. As is clear from FIG. 31D, in the non-reciprocal transmission line device 70F, a phase change of about 70 degrees with respect to the length of 30 mm is confirmed.
- FIG. 31E is a graph showing the frequency characteristics of the radiation beam angle in the broadside direction of the pseudo traveling wave resonance antenna apparatus, which is a numerical calculation result of the pseudo traveling wave resonance antenna apparatus of FIG. 31A. That is, FIG. 31E shows the radiation beam angle from the pseudo traveling wave resonant antenna device as a function of the operating frequency, taking the broadside direction as a reference.
- the beam direction is almost constant and the beam squint is reduced in the range of 4% of the specific band from 6.85 GHz to 7.15 GHz.
- FIG. 31F is a graph showing a numerical calculation result of the pseudo traveling wave resonance antenna apparatus of FIG. 31A and showing a radiation pattern in a plane perpendicular to the longitudinal direction of the pseudo traveling wave resonance antenna apparatus.
- a radiation gain of 8 dBi is obtained with respect to an input signal with an operating frequency of 7 GHz.
- FIG. 32A is a photograph showing a prototype of the pseudo traveling wave resonant antenna apparatus of FIG. 31A
- FIG. 32B is an experimental result of the pseudo traveling wave resonant antenna apparatus according to the prototype of FIG. It is a graph which shows the frequency characteristic of the radiation beam angle of the broadside direction of an apparatus.
- the band in which the beam squint whose radiation beam angle does not change with frequency is exactly 0 is smaller than the numerical calculation result shown in FIG. In comparison, the operating band where the beam squint is reduced is greatly improved.
- FIG. 32C is a graph showing an experimental result of the pseudo traveling wave resonance antenna apparatus according to the prototype of FIG. 32A and showing a radiation pattern on a plane perpendicular to the longitudinal direction of the pseudo traveling wave resonance antenna apparatus.
- the beam has a beam slightly rearward from the center in the longitudinal direction of the pseudo traveling wave resonance antenna apparatus.
- the electrical lengths La and Lb of the stub conductors 13A and 13B may be set as described in the embodiment and its modifications.
- the nonreciprocal transmission line apparatuses 70A to 70F according to the present invention are useful as signal transmission devices and antenna apparatuses.
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Abstract
Description
上記各単位セルの伝送線路部分は、上記マイクロ波の伝搬方向に対して異なる方向に磁化されてジャイロ異方性を有するように自発磁化を有するか又は外部磁界により磁化され、
上記第1の並列枝の回路は、第1の電気長を有する第1のスタブ導体であり、
上記第2の並列枝の回路は、第1の電気長より短い第2の電気長を有する第2のスタブ導体であり、
上記順方向で伝搬する第1のモードの位相定数をβpとし、上記逆方向で伝搬する第2のモードの位相定数をβmとしたとき、上記第1の電気長及び上記第2の電気長は、位相定数βpと動作角周波数との関係を示す分散曲線と、位相定数βmと動作角周波数との関係を示す分散曲線との交点の近傍において、動作角周波数に対する非相反移相量βNR=(βp-βm)/2の関数が、上記非相反伝送線路装置から放射される電磁波の放射方向が周波数に応じて変化する現象であるビームスクイントが発生しないときの、動作角周波数に対する非相反移相量βNRの関数に近接するように設定されたことを特徴とする。
上記第1及び第2の電気長は、
(a)上記交点における動作角周波数より低い所定の動作角周波数において、上記第1のアドミタンスが上記第2のアドミタンスに実質的に一致し、かつ
(b)上記所定の動作角周波数において、上記第1及び第2のアドミタンスの各虚部が負であることを特徴とする。
(B)順方向が左手系伝送、逆方向は伝搬定数がゼロで管内波長が無限大となる。
(C)順方向が左手系伝送、逆方向が右手系伝送。
(D)順方向が右手系伝送、逆方向は伝搬定数がゼロで管内波長が無限大となる。
(E)順方向及び逆方向伝搬共に右手系伝送。但し、伝搬定数の大きさは互いに異なる。
図20Aは、本発明の実施形態の変形例に係る非相反伝送線路装置70Fの構成を示す斜視図である。図20Aにおいて、非相反伝送線路装置70Fは、実施形態に係る非相反伝送線路装置70Eに比較して、単位セル60Eに代えて単位セル60Fを備えた点が異なる。また、単位セル60Fは、単位セル60Eに比較して、チップキャパシタであるキャパシタCshをさらに備えた点のみが異なる。以下、実施形態との間の相違点のみを説明する。図20Aにおいて、キャパシタCshの一方の電極は、スタブ導体13A及び13Bのうちの長い方のスタブ導体13Aの所定の接続点に接続される一方、キャパシタCshの他方の電極は、ビア導体19を介して接地導体11に接続される。
第2の条件:上述した動作角周波数ωZにおいて、アドミタンスY1及びY2はともに誘導的(インダクタンス)でなければならない。すなわち、動作角周波数ωZにおいて、スタブ導体13A及び13Bは負の誘電率を有する誘導性スタブでなければならないので、Im(Y1)=Im(Y2)<0である。
第3の条件:スタブ導体13Aは、La>λ/2を満たす短絡スタブである。
第4の条件:スタブ導体13Bは、Lb<λ/4を満たす短絡スタブである。
第3の条件:スタブ導体13Aは、La>λ/4を満たす開放スタブである。
第4の条件:スタブ導体13Bは、Lb<λ/4を満たす短絡スタブである。
11,18,19,22,23,50…接地導体、
12,21,24…ストリップ導体、
12A…コプレーナ線路、
12E…マイクロストリップ線路、
13A,13B…スタブ導体、
15…フェライト板、
15A…フェライト角棒、
17A,17B…接地導体、
60A~60F…単位セル、
61,62…伝送線路部分、
70A~60F…非相反伝送線路装置、
80…外部磁界発生器、
C,C1,C2,C60,Cse,Csh…キャパシタ、
P1,P2,P11,P12…ポート。
Claims (7)
- マイクロ波の伝送線路部分と、容量性素子を等価的に含む直列枝の回路と、上記伝送線路部分からそれぞれ分岐して設けられかつ誘導性素子を等価的に含む第1及び第2の並列枝の回路とを有する少なくとも1つの単位セルを、第1と第2のポートの間で縦続接続して構成され、順方向の伝搬定数と逆方向の伝搬定数とが互いに異なる非相反伝送線路装置において、
上記各単位セルの伝送線路部分は、上記マイクロ波の伝搬方向に対して異なる方向に磁化されてジャイロ異方性を有するように自発磁化を有するか又は外部磁界により磁化され、
上記第1の並列枝の回路は、第1の電気長を有する第1のスタブ導体であり、
上記第2の並列枝の回路は、第1の電気長より短い第2の電気長を有する第2のスタブ導体であり、
上記順方向で伝搬する第1のモードの位相定数をβpとし、上記逆方向で伝搬する第2のモードの位相定数をβmとしたとき、上記第1の電気長及び上記第2の電気長は、位相定数βpと動作角周波数との関係を示す分散曲線と、位相定数βmと動作角周波数との関係を示す分散曲線との交点の近傍において、動作角周波数に対する非相反移相量βNR=(βp-βm)/2の関数が、上記非相反伝送線路装置から放射される電磁波の放射方向が周波数に応じて変化する現象であるビームスクイントが発生しないときの、動作角周波数に対する非相反移相量βNRZの関数に近接するように設定されたことを特徴とする非相反伝送線路装置。 - 上記関数は、動作角周波数に比例する関数であることを特徴とする請求項1記載の非相反伝送線路装置。
- 上記第1のスタブ導体は第1のアドミタンスを有し、
上記第2のスタブ導体は第2のアドミタンスを有し、
上記第1及び第2の電気長は、
(a)上記交点における動作角周波数より低い所定の動作角周波数において、上記第1のアドミタンスが上記第2のアドミタンスに実質的に一致し、かつ
(b)上記所定の動作角周波数において、上記第1及び第2のアドミタンスの各虚部が負であることを特徴とする請求項2記載の非相反伝送線路装置。 - 上記第1のスタブ導体は短絡スタブでありかつ上記第1の電気長は管内波長の1/2より長いように設定され、
上記第2のスタブ導体は短絡スタブでありかつ上記第2の電気長は上記管内波長の1/4より短いように設定されたことを特徴とする請求項3記載の非相反伝送線路装置。 - 上記第1のスタブ導体は開放スタブでありかつ上記第1の電気長は管内波長の1/4より長いように設定され、
上記第2のスタブ導体は短絡スタブでありかつ上記第2の電気長は上記管内波長の1/4より短いように設定されたことを特徴とする請求項3記載の非相反伝送線路装置。 - 上記各第1のスタブ導体の間に設けられ、上記各第1のスタブ導体間を遮蔽する接地導体をさらに備えたことを特徴とする請求項1~5のうちのいずれか1つに記載の非相反伝送線路装置。
- 請求項1乃至6のうちのいずれか1つに記載の非相反伝送線路装置を備えたことを特徴とするアンテナ装置。
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