WO2013001746A1 - Onduleur et dispositif de conversion électrique équipé de celui-ci - Google Patents

Onduleur et dispositif de conversion électrique équipé de celui-ci Download PDF

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Publication number
WO2013001746A1
WO2013001746A1 PCT/JP2012/003997 JP2012003997W WO2013001746A1 WO 2013001746 A1 WO2013001746 A1 WO 2013001746A1 JP 2012003997 W JP2012003997 W JP 2012003997W WO 2013001746 A1 WO2013001746 A1 WO 2013001746A1
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Prior art keywords
voltage
switch
sine wave
inverter
gradation
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PCT/JP2012/003997
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English (en)
Japanese (ja)
Inventor
高野　洋
英之 長屋
敬輔 渡邉
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三洋電機株式会社
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Publication of WO2013001746A1 publication Critical patent/WO2013001746A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels

Definitions

  • the present invention relates to an inverter that mutually converts a direct-current voltage and an alternating-current voltage, and a power conversion device equipped with the inverter.
  • This system includes a photovoltaic power generation module, a storage battery, and a control unit.
  • the DC power generated by the solar module is converted into AC power by an inverter mounted on the control unit and supplied to the home.
  • the electric power excessively generated by the solar power generation module is stored in the storage battery.
  • the storage battery also has a function of storing inexpensive nighttime electric power and supplying it to the home in the daytime. For this reason, the converter which converts the alternating current power supplied from a system
  • a distributed power generation / storage system combining a solar power generation system and a power storage system requires a bidirectional inverter that can efficiently and alternately convert AC power and DC power.
  • the present invention has been made in view of such circumstances, and an object thereof is to provide a technique for improving the power conversion efficiency of an inverter by further reducing loss.
  • an inverter is a gradation control type inverter for generating a pseudo sine wave, and includes a first mode for converting DC to AC, and AC to DC. And a second mode for conversion.
  • the power conversion efficiency of the inverter can be improved.
  • FIG. 1 It is a figure which shows the power converter device which concerns on Embodiment 1 of this invention. It is a figure which shows the inverter which concerns on Embodiment 1 of this invention.
  • 3 is a diagram showing a pseudo sine wave generated by the inverter according to Embodiment 1.
  • FIG. It is a figure which shows the ON / OFF state of the switch at the time of producing
  • FIG. 3 is a diagram in which an applied voltage level is added to a diagram illustrating an on / off state of a switch when seven types of gradation levels are generated by the inverter illustrated in FIG. 2. It is a figure which shows the result of having produced
  • FIG. 6 is a diagram showing a power conversion device according to a third embodiment. 6 is a diagram illustrating a specific circuit configuration example of a power supply system according to Embodiment 3. FIG.
  • FIG. 1 is a diagram showing a power conversion device 10 according to Embodiment 1 of the present invention.
  • FIG. 1 also shows a DC power supply unit 100, a load 300, and an AC power supply 400, but these are not included in the components of the power conversion device 10.
  • the DC power supply unit 100 includes a power generation device such as a solar battery and a secondary battery such as a lithium ion battery.
  • the power converter 10 is configured to be able to switch between a first mode for converting DC power to AC power and a second mode for converting AC power to DC power.
  • the power conversion device 10 converts DC power from the DC power supply unit 100 into AC power and supplies the AC power to the load 300.
  • the power conversion device 10 converts AC power from the AC power supply 400 into DC power and supplies the DC power to the DC power supply unit 100. That is, the DC power supply unit 100 is charged with the power from the AC power supply 400.
  • the above is the outline of the power conversion device 10.
  • the power conversion apparatus 10 includes a direct current bidirectional converter 120, a power supply system 140, an inverter 200, and a switching unit 220.
  • the direct current bidirectional converter 120 is composed of a general direct current bidirectional converter. In the first mode, DC bidirectional converter 120 receives a DC voltage from DC power supply unit 100 on the primary side and outputs a DC voltage from the secondary side. In the second mode, DC bidirectional converter 120 receives the DC voltage from inverter 200 on the secondary side, and supplies the DC voltage to DC power supply unit 100 connected to the primary side to charge the DC voltage.
  • the power supply system 140 generates a plurality of types of DC voltages based on one type of DC voltage supplied from the DC power supply unit 100 supplied via a DC bidirectional converter.
  • the power supply system 140 includes a path 102 that directly outputs a DC voltage from the DC power supply unit 100, and a first power supply device 104 and a second power supply device 106 that convert the DC voltage into two different voltage levels.
  • the first power supply device 104 and the second power supply device 106 include a step-up or step-down DC-DC converter (also referred to as a step-up chopper).
  • the DC voltage output from the path 102 is the first DC voltage E1
  • the DC power output from the first power supply device, and the DC power output from the second power supply device are the second DC voltage E2 and the third DC, respectively.
  • This is called voltage E3.
  • the first DC voltage E1 is set to 96V
  • the second DC voltage E2 is set to 82V
  • the third DC voltage E3 is set to 32V.
  • the voltage value of the DC voltage is not particularly limited.
  • the inverter 200 converts a plurality of DC voltages from the power supply system 140 into AC power using pseudo sine waves by gradation control, and supplies the AC power to the load 300. Further, in the second mode, the inverter 200 converts AC power from the AC power supply 400 into DC power by the H bridge circuit 40 included in the inverter 200 and supplies the DC power to the DC power supply unit 100. Details of the inverter 200 will be described later.
  • the switching unit 220 switches the connection destination of the inverter 200 between the AC power source and the load. Specifically, in the first mode, inverter 200 is connected to load 300, and in the second mode, inverter 200 is connected to AC power supply 400.
  • FIG. 2 is a diagram showing a circuit configuration of inverter 200 according to Embodiment 1 of the present invention.
  • FIG. 2 also shows a load 300, an AC power supply 400, and a switching unit 220, but these are not included in the components of the inverter 200.
  • the inverter 200 converts a plurality of DC voltages from the power supply system 140 in the previous stage into an AC voltage using a pseudo sine wave and supplies the AC voltage to the load 300 connected via the switching unit 220.
  • the inverter 200 converts the AC voltage from the AC power source 400 connected via the switching unit 220 into a DC voltage, and the DC power source via the path 102 of the power system 140 and the DC bidirectional converter 120. To the unit 100.
  • the inverter 200 includes a control unit 20, an H bridge circuit 40, a first switch S11, a second switch S12, a first switch S21, a second switch S22, an input terminal 60, and an input terminal 80.
  • the H bridge circuit 40 includes four switches SW0 to SW3.
  • the first DC voltage E1 is applied to the high potential side terminal 42 of the H-bridge circuit 40 in the first mode.
  • the first output terminal 44 and the second output terminal 46 of the H bridge circuit 40 are connected to the load 300 or the AC power supply 400 via the switching unit 220.
  • an AC voltage from the AC power supply 400 is applied between the two output terminals of the H-bridge circuit 40.
  • the second DC voltage E2 and the third DC voltage E3 having levels different from the first DC voltage E1 are applied to the input terminal 60 and the input terminal 80, respectively.
  • the first switch and the second switch are provided for each input terminal.
  • the first switches S11 and S21 are respectively connected between the corresponding input terminal and the first output terminal 44 of the H bridge circuit.
  • the second switches S12 and S22 are respectively connected between the corresponding input terminal and the second output terminal 46 of the H bridge circuit.
  • the control unit 20 controls the switching elements included in the H-bridge circuit 40, the first switch S11, the second switch S12, the first switch S21, and the second switch S22 to turn on and off the DC voltage and the AC voltage. Convert.
  • a first DC voltage is applied to the high potential side terminal 42 of the H bridge circuit
  • a second DC voltage different from the first DC voltage is applied to the input terminal
  • the control unit generates a pseudo sine wave between the first output terminal 44 and the second output terminal 46 by controlling the H bridge circuit, the first switch, and the second switch.
  • an AC voltage is applied between the first output terminal 44 and the second output terminal 46, and the control unit turns off the first switch and the second switch in the state where the first switch and the second switch are turned off.
  • a DC voltage is generated between the high potential side terminal 42 of the H bridge and the low potential side terminal connected to the ground.
  • the first switch S11 includes switches SW4 and SW5
  • the second switch S12 includes switches SW6 and SW7.
  • the first switch S21 includes switches SW8 and SW9
  • the second switch S22 includes switches SW10 and SW11.
  • Switching elements included in the H-bridge circuit 40, the first switch S11, the second switch S12, the first switch S21, and the second switch S22 include a power MOSFET (Metal-Oxide-Semiconductor-Field-Effect-Transistor) and an IGBT (Insulated), respectively.
  • MOSFET Metal-Oxide-Semiconductor-Field-Effect-Transistor
  • IGBT Insulated
  • Gate-bipolar transistor, TRIAC (triode AC switch), GaN transistor, SiC-FET can be employed.
  • all the switching elements are power MOSFETs unless otherwise specified.
  • each of the first switch S11, the second switch S12, the first switch S21, and the second switch S22 includes two switching elements. This is because current flows in these switches in both directions, and two unidirectional power MOSFETs are arranged in series to form one bidirectional switching element. Therefore, these switches may be configured using power MOSFETs, IGBTs, TRIACs, GaN transistors, and SiC-FETs that are compatible with both directions.
  • the first output terminal 44 and the second output terminal 46 are connected to the load 300 via the switching unit 220.
  • the first output terminal 44 is referred to as a positive terminal
  • the second output terminal 46 is referred to as a negative terminal.
  • the control unit 20 controls the H bridge circuit 40 to supply the first DC voltage E1 to the load 300.
  • the switch SW0 and the switch SW3 are turned on, and the switch SW1 and the switch SW2 are turned off.
  • the switch SW1 and the switch SW2 are turned on, and the switch SW0 and the switch SW3 are turned off.
  • control unit 20 controls the first switch S11 and the second switch S12 and the H bridge circuit 40 to supply the second DC voltage E2 to the load 300.
  • the switch SW3 and the switch SW5 are turned on, and the switches SW0, SW1, SW2, SW4, SW6, and SW7 are turned off.
  • the switch SW1 and the switch SW7 are turned on, and the switches SW0, SW2, SW3, SW4, SW5, and SW6 are turned off.
  • control unit 20 controls the first switch S21 and the second switch S22 and the H bridge circuit 40 to supply the third DC voltage E3 to the load 300.
  • the switch SW3 and the switch SW9 are turned on, and the switches SW0, SW1, SW2, SW8, SW10, and SW11 are turned off.
  • the switch SW1 and the switch SW11 are turned on, and the switches SW0, SW2, SW3, SW8, SW9, and SW10 are turned off.
  • the first output terminal 44 and the second output terminal 46 are connected to the first DC voltage according to the switch state. Any one of the voltage E1, the second DC voltage E2, the third DC voltage E3, or the ground voltage (zero voltage) can be selectively generated.
  • the voltage applied across the load is given by a combination of voltages at each output terminal, and there are a total of thirteen patterns (including polarity reversal).
  • the control unit 20 supplies the potential difference (E1-E2) between the first DC voltage and the second DC voltage to the load 300 by controlling the H bridge circuit 40 and the first switch S11 and the second switch S12. Can do.
  • E1-E2 potential difference between the first DC voltage and the second DC voltage
  • the switch SW0 and the switch SW6 are turned on, and the switches SW1, SW2, SW3, SW4, SW5, and SW7 are turned off.
  • the switches SW2 and SW4 are turned on, and the switches SW0, SW1, SW3, SW5, SW6, and SW7 are turned off.
  • control unit 20 controls the H bridge circuit 40 and the first switch S21 and the second switch S22 to supply the load 300 with a potential difference (E1-E3) between the first DC voltage and the third DC voltage. can do.
  • a forward voltage is applied to the load 300
  • the switch SW0 and the switch SW10 are turned on, and the switches SW1, SW2, SW3, SW8, SW9, and SW11 are turned off.
  • the switch SW2 and the switch SW8 are turned on, and the switches SW0, SW1, SW3, SW9, SW10, and SW11 are turned off.
  • control unit 20 controls the first switch S11 and the second switch S12, and the first switch S21 and the second switch S22, whereby a potential difference (E2 ⁇ ) between the second DC voltage E2 and the third DC voltage E3. E3) can be supplied to the load 300.
  • a potential difference (E2 ⁇ ) between the second DC voltage E2 and the third DC voltage E3. E3) can be supplied to the load 300.
  • the switch SW5 and the switch SW10 are turned on, and the switches SW4, SW6, SW7, SW8, SW9, and SW11 are turned off.
  • the switches SW7 and SW8 are turned on, and the switches SW4, SW5, SW6, SW9, SW10, and SW11 are turned off.
  • the controller 20 controls the first potential difference (E1 ⁇ E1) between the first DC voltage E1, the second DC voltage E2, the third DC voltage E3, and the first DC voltage E1 and the second DC voltage E2. E2), the second potential difference (E1-E3) between the first DC voltage and the third DC voltage, and the third potential difference (E2-E3) between the second DC voltage and the third DC voltage.
  • E1 ⁇ E1 first DC voltage
  • E2 second DC voltage
  • E1-E3 between the first DC voltage and the third DC voltage
  • E2-E3 the third potential difference
  • FIG. 3 is a diagram illustrating a pseudo sine wave generated by the inverter 200 according to the first embodiment.
  • the control unit 20 includes a zero voltage, the first potential difference (E1-E2) (positive), the third DC voltage E3 (positive), the third potential difference (E2-E3) (positive), and the second potential difference (E1- E3) (positive), second DC voltage E2 (positive), first DC voltage E1 (positive), second DC voltage E2 (positive), second potential difference (E1-E3) (positive), third potential difference (E2-E3) (positive), third DC voltage E3 (positive), first potential difference (E1-E2) (positive), zero voltage, first potential difference (E1-E2) (negative), third DC Voltage E3 (negative), third potential difference (E2-E3) (negative), second potential difference (E1-E3) (negative), second DC voltage E2 (negative), first DC voltage E1 (negative), Second DC voltage E2 (negative), second potential difference (E1-E3) (negative), third potential difference (E2-E3) (negative), third DC voltage E3 (
  • FIG. 4 is a diagram illustrating an on / off state of the switch when the inverter 200 according to Embodiment 1 generates thirteen types of gradation levels.
  • Gradation level 0 is the zero voltage
  • gradation level 1 is the first potential difference (E1-E2) (positive)
  • gradation level 2 is the third DC voltage E3 (positive)
  • gradation level 3 is the third potential difference.
  • E2-E3) positive
  • gradation level 4 is the second potential difference (E1-E3) (positive)
  • gradation level 5 is the second DC voltage E2 (positive)
  • gradation level 6 is the first DC voltage.
  • gradation level-1 is the first potential difference (E1-E2) (negative)
  • gradation level-2 is the third DC voltage E3 (negative)
  • gradation level-3 is the third potential difference ( E2-E3) (negative)
  • gradation level-4 is the second potential difference (E1-E3) (negative)
  • gradation level-5 is the second DC voltage E2 (negative)
  • gradation level-6 is the first.
  • Each corresponds to the DC voltage E1 (negative).
  • the control unit 20 performs on / off control of the switches SW0 to SW11.
  • the number of DC voltages used in the inverter 200 is set to three has been described.
  • the number of DC voltages can be set to two, or four or more.
  • the control unit 20 controls all the switching elements included in the first switch S11, the second switch S12, the first switch S21, and the second switch S22 to be turned off, and converts each switching element of the H bridge circuit to a DC voltage. Control is performed to convert the voltage to a voltage, and the voltage is converted to a DC voltage at the upper end voltage of the H-bridge circuit.
  • the AC voltage is full-wave rectified by a diode bridge circuit formed by a body diode (flywheel diode) of each switch of the H bridge circuit.
  • FIG. 5 is a diagram showing a power conversion device 15 according to a comparative example to be compared with the first embodiment of the present invention.
  • the power conversion device 15 includes a direct current bidirectional converter 125, a bridge circuit 45, a filter 35, and a switching unit 225.
  • FIG. 5 also shows the DC power supply unit 100, the load 300, and the AC power supply 400, but these are not included in the components of the power conversion device 15.
  • DC power from the DC power supply unit 100 is converted into AC power by the bridge circuit 45.
  • a pseudo sine wave is generated by a PWM (Pulse Width Modulation) method.
  • AC power from the AC power supply 400 is converted to DC by the bridge circuit 45 and supplied to the DC power supply unit 100. That is, the DC power supply unit 100 is charged with the power from the AC power supply 400.
  • the effects of the first embodiment will be described based on this.
  • the switching amplitude is compared with the conventional PWM method as in the comparative example.
  • the switching loss can be reduced.
  • the power conversion efficiency of the inverter can be improved.
  • a large-scale filter for smoothing is required between the output and the load (AC power supply).
  • the power converter can be reduced in size and cost. it can.
  • power consumption in the output filter can be reduced, and the amount of heat generated can be reduced.
  • the fan for heat dissipation and the fin for heat dissipation can be simplified or they can be omitted.
  • the second embodiment is an example in which the gradation control of the first embodiment is combined with PWM control.
  • the configuration and the gradation control operation are the same as those in the first embodiment.
  • the inverter of the second embodiment also has the configuration shown in FIG. The operation of PWM control will be described below.
  • the control unit 20 generates an PWM signal that generates at least one gray level constituting the pseudo sine wave with a voltage of the gray level and a voltage of the adjacent gray level being high level and low level. Supply to each switch.
  • FIG. 6A and 6B are diagrams showing simulation results when a pseudo sine wave (without using a PWM signal) is generated by using the mounting circuit of the inverter 200 shown in FIG.
  • FIG. 6A shows time axis data
  • FIG. 6B shows frequency axis data.
  • a pseudo sine wave is generated using thirteen types of gradation levels.
  • the 39th harmonic distortion occupying the signal was 4.84%.
  • FIGS. 7A and 7B are diagrams showing simulation results when a pseudo sine wave (with use of a PWM signal) is generated using the mounting circuit of the inverter 200 shown in FIG.
  • FIG. 7A shows time axis data
  • FIG. 7B shows frequency axis data.
  • the 39th harmonic distortion occupying the signal was 0.11%.
  • FIG. 8 is a diagram for explaining PWM waveform data necessary for generating a pseudo sine wave (with use of a PWM signal) using the mounting circuit of the inverter 200 shown in FIG.
  • Six types of PWM waveform data (AF) are required to generate a pseudo sine wave using thirteen types of gradation levels.
  • the zero voltage and the six types of PWM waveform data are switched in the order of the PWM waveform data F to the PWM waveform data A after using the zero voltage. use.
  • the left and right of the six types of PWM waveform data (AF) are inverted, and the PWM waveform data A ′ to the PWM waveform data F ′ are switched in order.
  • phase ⁇ to (3/2) ⁇ the upper and lower sides of the six types of PWM waveform data (AF) are inverted, and the PWM waveform data F to the PWM waveform data A are switched in order.
  • phase (3/2) ⁇ to 2 ⁇ the upper and lower sides and the left and right sides of the six types of PWM waveform data (AF) are inverted, and the PWM waveform data A ′ to the PWM waveform data F ′ are switched in order.
  • a table (not shown) is provided outside or inside the control unit 20, and PWM waveform data is held in the table in units of gradations constituting a pseudo sine wave.
  • the PWM waveform data for each gradation is designed to have a waveform with the smallest high frequency distortion using an existing optimization algorithm.
  • the control unit 20 generates a PWM signal for generating a pseudo sine wave using the PWM waveform data held in the table.
  • the PWM waveform data is inverted vertically and / or horizontally to generate a PWM signal.
  • FIG. 9 is a diagram in which the applied voltage level is added to the diagram showing the on / off state of the switch when the inverter 200 shown in FIG. 2 generates seven types of gradation levels.
  • a PWM signal can be generated by reciprocating between applied voltages of adjacent gradations, such as between 1 gradation and 2 gradations, between 2 gradations and 3 gradations.
  • the first DC voltage E1 is referred to as a high voltage HV
  • the second DC voltage E2 is referred to as a medium voltage MV
  • the third DC voltage E3 is referred to as a low voltage LV.
  • FIG. 10 is a diagram showing a result of generating a PWM signal using the switching pattern shown in FIG.
  • A”-“F” in the graph indicate switching patterns for generating the PWM waveform data (AF) in FIG.
  • “/ A”-“/ F” in the graph is a pattern in which the positive and negative of “A”-“F” are reversed.
  • SW3 and SW9 are “ ⁇ ” in FIG. 9 and “E” in FIG.
  • SW0 and SW6 are “ ⁇ ”.
  • SW0 and SW6 are “/ E”.
  • SW3 and SW9 are turned on when the PWM pattern of “E” is high level, and “/ E” is high level when the PWM pattern of “E” is low level. Therefore, SW0 and SW6 are turned on. Thereby, the reciprocating operation of “1 gradation” and “2 gradations” in FIG. 9 can be realized.
  • FIG. 11 shows the relationship between an ideal sine wave quarter cycle to be generated and the gradation voltage.
  • the vertical axis y is voltage
  • the horizontal axis x is time.
  • the control unit 20 performs PWM for setting one gradation voltage and the other gradation voltage to a low level and a high level, respectively, within a time range in which the sine wave voltage becomes two gradation voltages.
  • a signal is generated to generate a pseudo sine wave.
  • the time during which the sine wave voltage becomes the gradation voltage during a quarter cycle of the AC output (sine wave output) is x0 to x6.
  • a PWM signal is generated in which one gradation voltage is set to a low level and the other gradation voltage is set to a high level.
  • control unit 20 generates a pseudo sine wave by generating a PWM signal within a time range in which adjacent gradation voltages are obtained.
  • the combinations of times for adjacent gradation voltages are x0 and x1, x1 and x2, x2 and x3, x3 and x4, x4 and x5, and x5 and x6.
  • FIG. 12 is a diagram for explaining PWM control by the control unit 20.
  • adjacent grayscale voltages and the time at which the sine wave voltage becomes each grayscale voltage are connected by a frame line.
  • a region surrounded by the frame line is expressed as a window. To do.
  • the control unit 20 since there are seven gradation voltages (y0 to y6) in the quarter period of the sine wave, six windows 30a to 30f are formed.
  • the control unit 20 generates a PWM signal in each window 30 to generate a pseudo sine wave.
  • the underline represents the low level of the PWM signal
  • the upper line represents the high level of the PWM signal
  • the left line represents the start time of the PWM control in the window 30
  • the right line represents the end of the PWM control.
  • the switching timing of the level of the PWM signal is determined by generating a triangular wave with the one gradation voltage and the other gradation voltage being low level and high level in the window 30 and using the intersection of the triangle wave and sine wave, respectively. .
  • the switching timing of the PWM signal may be dynamically determined, but may be determined in advance and stored in a table.
  • FIG. 13A shows a state in which a triangular wave is virtually generated in the window 30.
  • the time when the triangular wave and the sine wave intersect is extracted, and that time is determined as the voltage switching timing of the PWM signal.
  • FIG. 13A shows a state in which a triangular wave is generated in the window 30e.
  • the time when the triangular wave and the sine wave intersect is extracted and used as the voltage switching timing of the PWM signal. Is set.
  • FIG. 13B shows low-level and high-level output voltages by PWM control in the window 30e.
  • This output voltage constitutes a pseudo sine wave in the time range of the window 30e.
  • the control unit 20 outputs a low-level gradation voltage when the triangular wave voltage is higher than the sine wave voltage, and when the sine wave voltage is higher than the triangular wave voltage.
  • the PWM voltage is generated so as to output a high level gradation voltage.
  • the control unit 20 performs PWM control voltage switching at the intersection of the triangular wave and the sine wave. By doing so, it is possible to make the average voltage within the time range of the window 30 the same as the average voltage of the sine wave.
  • the window 30e has been described, but the voltage switching timing in the PWM control is similarly determined for the other windows 30.
  • the control unit 20 outputs the sine wave amplitude at the maximum gradation voltage and outputs a pseudo sine wave with reduced harmonic distortion. Is possible.
  • FIG. 14 shows a modified example of the window to be generated.
  • the windows 30a and 30b are collectively referred to as a window 30g
  • the windows 30c and 30d are collectively referred to as a window 30h.
  • PWM control can be simplified by increasing the time width of the window 30 to some extent, and stable PWM control can be realized while reducing switching loss.
  • the harmonic component can be greatly reduced by performing the PWM control in the plurality of windows 30 in the quarter cycle of the AC output.
  • the voltage switching pattern of each window 30 of PWM control may be created in advance and held in a table.
  • control unit 20 refers to the voltage pattern in the table and performs on / off control of each SW.
  • Do. 12 and 14 show the 0 to 1/4 cycle of the AC output, but the voltage switching pattern of each window is similarly derived and held in the table between the 1/4 cycle and 1 cycle. Is done.
  • FIG. 15 is a diagram showing a simulation result when the gradation control and the PWM control are combined.
  • a dotted line indicates a sine wave
  • a solid line indicates a pseudo sine wave generated by the inverter 200.
  • the 39th harmonic distortion occupying the signal is 1.52% and the conversion efficiency is 98.1%, and it is confirmed that the harmonic component in the pseudo sine wave is reduced. It was done.
  • FIG. 16 is a diagram showing the power conversion device 10 according to the third embodiment of the present invention.
  • the case where there are three DC voltages is shown, but here, the case where there are two DC voltages is shown.
  • symbol is attached
  • the power conversion device 10 includes a DC bidirectional converter 120, a power supply system 140, an inverter 200, and a switching unit 220, as in the first embodiment.
  • the power supply system 140 includes a path 102 that directly outputs a DC voltage from the DC power supply unit 100, and a first power supply device 104 that includes a comparator CP1 and a step-up DC-DC converter 142.
  • a high DC voltage output from the path 102 is referred to as a first DC voltage E1
  • a low DC voltage generated by the first power supply device 104 is referred to as a second DC voltage E2.
  • the comparator CP1 compares the voltage of the node through which current flows from the path 102 with the reference voltage Vref for maintaining the node at the second DC voltage E2.
  • the comparator CP1 is composed of an operational amplifier, the voltage of the node is applied to its non-inverting input terminal, and the reference voltage Vref is applied to its inverting input terminal. A high level signal is output when the voltage of the node exceeds the reference voltage Vref, and a low level signal is output when the voltage does not exceed the reference voltage Vref.
  • the step-up DC-DC converter 142 receives the voltage of the node input to the comparator CP1, boosts the voltage to a voltage higher than the first DC voltage E1, and applies it to the node of the path 102.
  • the boost DC-DC converter 142 enables the boost function when the voltage of the node is higher than the reference voltage Vref, and disables the boost function when the voltage of the node is equal to or lower than the reference voltage Vref.
  • the boost function of the boost DC-DC converter 142 is enabled, and when a low level signal is input, it is disabled.
  • the step-up DC-DC converter 142 Since the output terminal of the step-up DC-DC converter 142 is connected to the path 102, the charge accumulated at the node to be maintained at the second DC voltage E2 can be returned to the system of the first DC voltage E1. .
  • the step-up DC-DC converter 142 needs to step up to a voltage exceeding the first DC voltage E1, and a current needs to flow from the step-up DC-DC converter 142 to the path 102.
  • FIG. 17 is a diagram illustrating a specific configuration example of the first power supply device 104.
  • the first power supply device 104 includes a comparator CP1, a variable resistor VR, a step-up DC-DC converter 142, a pulse generator 144, an AND gate 146, and a photocoupler 148.
  • the reference voltage Vref applied to the inverting input terminal of the comparator CP1 is generated by resistance division (not shown) of the power supply voltage (for example, 5 V) having the circuit configuration shown in FIG. For example, it is set to 2.5V.
  • the second DC voltage E2 is resistance-divided by the variable resistor VR and applied to the non-inverting input terminal of the comparator CP1.
  • the variable resistor VR divides the resistance so that it matches the reference voltage Vref when the second DC voltage E2 is an ideal value.
  • the pulse generator 144 (for example, a function generator) generates a pulse signal.
  • the AND gate 146 receives the pulse signal generated by the pulse generator 144 and the comparison result signal (used as an enable signal) output from the comparator CP1.
  • the AND gate 146 outputs the output signal of the pulse generator 144 as it is when the output signal of the comparator CP1 is high level, and outputs the low level when the output signal of the comparator CP1 is low level.
  • the output signal of the AND gate 146 is input to the switching element M1 described later via the photocoupler 148.
  • the AND gate 146 supplies the pulse signal to the switching element M1 when the voltage of the node (more precisely, the low voltage VL divided by the variable resistor VR) is higher than the reference voltage Vref, and the node When the voltage of is lower than the reference voltage Vref, an off signal (low level) is supplied to the switching element M1.
  • the step-up DC-DC converter 142 includes an inductor L1, a diode D1, a switching element M1, a first capacitor C1, and a second capacitor C2.
  • the series circuit of the inductor L1 and the diode D1 includes an input terminal connected to a node into which current flows (controlled to maintain the second DC voltage E2), and a medium voltage HV system through which current flows. Provided between the connected output terminals.
  • the switching element M1 (configured by a power MOSFET in FIG. 17) is provided between the connection point of the inductor L1 and the diode D1 and a predetermined fixed potential (ground in FIG. 17).
  • a pulse signal is input to the switching element M1 (in FIG. 17, the gate terminal of the power MOSFET)
  • the step-up DC-DC converter 142 starts a step-up operation and stops when an off signal is input.
  • the first capacitor C1 is provided between the input terminal of the step-up DC-DC converter 142 and the fixed potential, and smoothes the voltage at the input terminal.
  • the second capacitor C2 is provided with the output terminal of the step-up DC-DC converter 142 and the fixed potential, and smoothes the voltage at the output terminal.
  • the first power supply device 104 uses the input side of the step-up DC-DC converter to keep the voltage of the node into which the current flows constant, and discharges excess charges using the step-up function. It is possible to suppress the generation of useless power consumption by returning to the original.
  • the first DC voltage E1 and the second DC voltage are applied to the first output terminal 44 and the second output terminal 46 according to the state of the switch.
  • Either voltage E2 or ground voltage (zero voltage) can be selectively generated.
  • the voltage applied across the load is given by a combination of voltages at each output terminal, and there are a total of seven types (including polarity reversal). Since the voltage generation method is the same as that of the first embodiment, the description thereof is omitted.
  • the pseudo sine wave is generated by switching the voltage supplied to the load 300.
  • the control unit 20 controls the zero voltage, the first potential difference (E1-E2) (positive), the second DC voltage E2 (positive), the first DC voltage E1 (positive), and the second DC voltage E2 ( Positive), the first potential difference (E1-E2) (positive), zero voltage, the first potential difference (E1-E2) (negative), the second DC voltage E2 (negative), the first DC voltage E1 (negative),
  • a pseudo sine wave is generated by switching the voltage supplied to the load 300 in the order of the second DC voltage E2 (negative) and the first potential difference (E1-E2) (negative).
  • At least one gray level constituting the pseudo sine wave is a PWM signal in which the voltage of the gray level and the voltage of the adjacent gray level are set to the high level and the low level.
  • the gradation can be expressed by a PWM signal. Since the method is the same as that of the second embodiment, description thereof is omitted.
  • the present invention has been described based on the embodiments.
  • This embodiment is an exemplification, and it will be understood by those skilled in the art that various modifications can be made to combinations of the respective constituent elements and processing processes, and such modifications are also within the scope of the present invention.
  • the first power supply device of the third embodiment may be applied to the first power supply device or the second power supply device of the first embodiment. According to this modification, an effect obtained by combining the first embodiment and the second embodiment can be obtained.
  • a gradation control type inverter for generating a pseudo sine wave An inverter having a first mode for converting from direct current to alternating current and a second mode for converting from alternating current to direct current.
  • the switching loss when converting from direct current to alternating current can be reduced as compared with the case where the conventional PWM method is used.
  • the PWM system since the PWM system is not used, a smooth AC output waveform can be obtained without requiring a large-scale output filter. Therefore, it is possible to reduce the size and cost of the power conversion device.
  • power consumption in the output filter can be reduced, and the amount of heat generated can be reduced. Thereby, the fan for heat dissipation and the fin for heat dissipation can be simplified or they can be omitted. Further, if a large-scale output filter is not required, it is not necessary to pass through the output filter when converting from AC to DC, so that the conversion efficiency is improved.
  • an H bridge circuit having a high potential side terminal, a low potential side terminal, and a plurality of switches provided therebetween; An input terminal to which a DC voltage is applied; A first switch connected between the input terminal and a first output terminal of the H-bridge circuit; A second switch connected between the input terminal and a second output terminal of the H-bridge circuit; A controller that controls the H-bridge circuit, the first switch, and the second switch; In the first mode, a first DC voltage is applied to a high potential side terminal of the H bridge circuit, a second DC voltage different from the first DC voltage is applied to the input terminal, and the control unit By controlling the H bridge circuit, the first switch and the second switch, a pseudo sine wave is generated between the first output terminal and the second output terminal, In the second mode, an AC voltage is applied between the first output terminal and the second output terminal, and the control unit operates the H bridge circuit with the first switch and the second switch turned off.
  • the inverter according to (2) wherein the inverter is configured to generate a DC voltage between a high potential side terminal
  • the control unit is a PWM (Pulse Width Modulation) signal that sets at least one gradation constituting the pseudo sine wave as a high level and a low level as a voltage of the gradation and a voltage of the adjacent gradation.
  • PWM Pulse Width Modulation
  • the pseudo sine wave can be smoothed without increasing the number of gradations.
  • the control unit generates a pseudo sine wave by generating a PWM signal within a time range in which the sine wave voltage becomes an adjacent gradation voltage (3) or (4) The inverter described in.
  • the pseudo sine wave can be smoothed more effectively without increasing the number of gradations.
  • the switching timing of the PWM signal generates a triangular wave in which one gradation voltage and the other gradation voltage are set to a low level and a high level, respectively, within a time range in which the sine wave voltage becomes two gradation voltages.
  • the inverter according to (7) which is determined by using an intersection of the triangular wave and the sine wave.
  • a power conversion device comprising: a switching unit that switches a connection destination of the first output terminal and the second output terminal of the inverter between an AC power supply and a load.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)

Abstract

L'invention concerne un onduleur (200) qui convertit une pluralité de tensions en courant continu en des tensions en courant alternatif quasi-sinusoïdales par une commande à gradation, et distribue les tensions converties à une charge (300) qui est connectée par l'intermédiaire d'une unité de commutation (220). L'onduleur (200) convertit une tension en courant alternatif provenant d'une alimentation électrique en courant alternatif (400) connectée par l'intermédiaire de l'unité de commutation (220), en une tension en courant continu par utilisation d'un circuit en pont en H (40) compris dans l'onduleur (200), et distribue la tension en courant continu à une unité d'alimentation électrique en courant continu (100) par l'intermédiaire d'un convertisseur bidirectionnel à courant continu (120) et d'un canal (102) d'un système d'alimentation électrique (140).
PCT/JP2012/003997 2011-06-30 2012-06-20 Onduleur et dispositif de conversion électrique équipé de celui-ci WO2013001746A1 (fr)

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Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US9463358B2 (en) 2014-04-23 2016-10-11 Shimano Inc. Pedaling state detecting apparatus

Families Citing this family (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP6346542B2 (ja) * 2014-10-21 2018-06-20 公立大学法人 滋賀県立大学 可搬型太陽光発電給電システム
KR101697855B1 (ko) * 2015-03-30 2017-01-19 숭실대학교산학협력단 H-브리지 멀티 레벨 인버터
JP6327419B2 (ja) * 2015-03-31 2018-05-23 公益財団法人鉄道総合技術研究所 電力変換用回路、電力変換装置及び電力変換方法

Citations (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH06261414A (ja) * 1993-03-03 1994-09-16 Yaskawa Electric Corp ソーラカードライブシステムにおける発電装置および発電方法
JPH08182343A (ja) * 1994-12-22 1996-07-12 Toshiba Corp 太陽光発電システム
JPH11122820A (ja) * 1997-10-14 1999-04-30 Nissin Electric Co Ltd 太陽光発電装置
JP2001224142A (ja) * 2000-02-08 2001-08-17 Nissin Electric Co Ltd 太陽光発電装置
JP2008193817A (ja) * 2007-02-06 2008-08-21 Tokyo Institute Of Technology 磁気エネルギー回生スイッチを用いた交流／直流電力変換装置
JP2010094024A (ja) * 2010-01-29 2010-04-22 Mitsubishi Electric Corp 電力変換装置
JP2011041457A (ja) * 2009-07-14 2011-02-24 Yaskawa Electric Corp 直流−交流電力変換装置およびその電力変換回路
WO2011025029A1 (fr) * 2009-08-31 2011-03-03 三洋電機株式会社 Onduleur et convertisseur de puissance possédant un onduleur
WO2011065278A1 (fr) * 2009-11-30 2011-06-03 三洋電機株式会社 Appareil de raccordement au réseau

Patent Citations (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH06261414A (ja) * 1993-03-03 1994-09-16 Yaskawa Electric Corp ソーラカードライブシステムにおける発電装置および発電方法
JPH08182343A (ja) * 1994-12-22 1996-07-12 Toshiba Corp 太陽光発電システム
JPH11122820A (ja) * 1997-10-14 1999-04-30 Nissin Electric Co Ltd 太陽光発電装置
JP2001224142A (ja) * 2000-02-08 2001-08-17 Nissin Electric Co Ltd 太陽光発電装置
JP2008193817A (ja) * 2007-02-06 2008-08-21 Tokyo Institute Of Technology 磁気エネルギー回生スイッチを用いた交流／直流電力変換装置
JP2011041457A (ja) * 2009-07-14 2011-02-24 Yaskawa Electric Corp 直流−交流電力変換装置およびその電力変換回路
WO2011025029A1 (fr) * 2009-08-31 2011-03-03 三洋電機株式会社 Onduleur et convertisseur de puissance possédant un onduleur
WO2011065278A1 (fr) * 2009-11-30 2011-06-03 三洋電機株式会社 Appareil de raccordement au réseau
JP2010094024A (ja) * 2010-01-29 2010-04-22 Mitsubishi Electric Corp 電力変換装置

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US9463358B2 (en) 2014-04-23 2016-10-11 Shimano Inc. Pedaling state detecting apparatus

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