WO2011093269A1 - Dispositif de conversion électrique - Google Patents

Dispositif de conversion électrique Download PDF

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Publication number
WO2011093269A1
WO2011093269A1 PCT/JP2011/051319 JP2011051319W WO2011093269A1 WO 2011093269 A1 WO2011093269 A1 WO 2011093269A1 JP 2011051319 W JP2011051319 W JP 2011051319W WO 2011093269 A1 WO2011093269 A1 WO 2011093269A1
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Prior art keywords
voltage
output
inverter
period
phase inverter
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PCT/JP2011/051319
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English (en)
Japanese (ja)
Inventor
賢司 藤原
達也 奥田
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三菱電機株式会社
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Priority to JP2011551849A priority Critical patent/JP5410551B2/ja
Publication of WO2011093269A1 publication Critical patent/WO2011093269A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels
    • H02M7/49—Combination of the output voltage waveforms of a plurality of converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0095—Hybrid converter topologies, e.g. NPC mixed with flying capacitor, thyristor converter mixed with MMC or charge pump mixed with buck
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels
    • H02M7/4835—Converters with outputs that each can have more than two voltages levels comprising two or more cells, each including a switchable capacitor, the capacitors having a nominal charge voltage which corresponds to a given fraction of the input voltage, and the capacitors being selectively connected in series to determine the instantaneous output voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels
    • H02M7/487—Neutral point clamped inverters

Definitions

  • the present invention relates to a power conversion device that converts direct-current power into alternating-current power, for example, a power conversion device that uses a solar power generation device as a power conditioner linked to a power system.
  • the AC output terminal of the second inverter is connected in series to one of the AC output terminals of the single-phase first single-phase inverter, and the AC output terminal of the third inverter is connected in series to the other. Some are connected to obtain an AC output voltage as a sum.
  • the first single-phase inverter is connected to a first DC source having a first DC voltage obtained by boosting the DC voltage of the solar cell with a chopper circuit, and the second inverter is converted from the first DC source by the former converter.
  • the third inverter is connected to the third DC source having the third DC voltage converted from the first DC source by the second converter. , Each receiving power supply.
  • the output is a pulse waveform at the commercial frequency
  • the output voltage waveform of the power converter is a sine wave AC and the first sine wave AC.
  • the second and third inverters output the difference from the output of the single-phase inverter (see, for example, Patent Document 1).
  • the conventional power converter is configured as described above, and the first single-phase inverter performs pulse output, and the power output by the first single-phase inverter during the output period becomes the output power of the power converter. If this condition is satisfied, the power balance of the second and third inverters becomes zero and the voltage is maintained. However, it is necessary to give the second and third inverters an AC output command value that can be output by the DC bus voltage, while the first single-phase inverter outputs the output by receiving the limitation. Depending on the conditions, there is a shortage in the power balance. The shortage is compensated by the second and third inverters.
  • the second and third inverters are configured to receive power supply via the first and second converters connected to the first DC source. Yes.
  • a conversion device such as the former and the second converter leads to an increase in cost and loss.
  • the present invention has been made to solve the above-described problems, and an object thereof is to obtain a power conversion device that is inexpensive and has low power loss.
  • a power conversion device including a first inverter, a second inverter, and a control device
  • the first inverter is connected between the positive and negative terminals of a DC power source, converts the power of the DC power source into AC and outputs it through an AC output line
  • the second inverter has a capacitor and a single-phase inverter circuit, the DC side of the single-phase inverter circuit is connected to the capacitor, and the AC side is connected in series to the AC output line
  • the control device rises when the sine wave AC output voltage command becomes larger than a predetermined value, and outputs a pulse of one pulse that falls when the sine wave AC voltage command becomes less than the predetermined value at every half cycle of the AC output voltage command
  • the first inverter is controlled by transmitting a main voltage pulse command so that the first output is output as the first voltage, and the first voltage based on the compensation voltage command issued based on the AC output voltage command and the output voltage of the first inverter.
  • the output voltage of the inverter 2 is subjected to pulse width modulation control to output the sum of the output voltages of the first and second inverters as a sine wave AC voltage, and the voltage of the capacitor in response to the compensation voltage command If the first period, which is a period during which the output voltage of the second inverter is insufficient, is present before and after the period during which the main voltage pulse is to be output. During the first period, the output voltage of the first inverter is output by pulse width modulation control to compensate for the insufficient output voltage and the second period during the period in which the main voltage pulse is to be output. The power energy supplied from the first inverter in the first period is reduced by reducing the power energy output from the first inverter by performing pulse width modulation control on the output voltage of the first inverter. It was designed to offset.
  • a power conversion device including a first inverter, a second inverter, and a control device
  • the first inverter is connected between the positive and negative terminals of a DC power source, converts the power of the DC power source into AC and outputs it through an AC output line
  • the second inverter has a capacitor and a single-phase inverter circuit, the DC side of the single-phase inverter circuit is connected to the capacitor, and the AC side is connected in series to the AC output line
  • the control device rises when the sine wave AC output voltage command becomes larger than a predetermined value, and outputs a pulse of one pulse that falls when the sine wave AC voltage command becomes less than the predetermined value at every half cycle of the AC output voltage command.
  • the first inverter is controlled by transmitting a main voltage pulse command so that the first output is output as the first voltage, and the first voltage based on the compensation voltage command issued based on the AC output voltage command and the output voltage of the first inverter.
  • the output voltage of the inverter 2 is subjected to pulse width modulation control to output the sum of the output voltages of the first and second inverters as a sine wave AC voltage, and the voltage of the capacitor in response to the compensation voltage command If the first period, which is a period during which the output voltage of the second inverter is insufficient, is present before and after the period during which the main voltage pulse is to be output.
  • the output voltage of the first inverter is output by pulse width modulation control to compensate for the insufficient output voltage and the second period during the period in which the main voltage pulse is to be output.
  • the power energy supplied from the first inverter in the first period is reduced by reducing the power energy output from the first inverter by performing pulse width modulation control on the output voltage of the first inverter. Because it was designed to offset An inexpensive and low-power-conversion power converter can be obtained.
  • FIG. 6 is a configuration diagram of a power conversion device according to a third embodiment. It is explanatory drawing for demonstrating operation
  • FIG. 6 is a configuration diagram of a power conversion device according to a third embodiment. It is explanatory drawing for demonstrating operation
  • FIG. 20 is a PAD diagram of the control device of FIG. 19.
  • FIG. 10 is a configuration diagram of a power conversion device according to a fifth embodiment. It is a wave form diagram for demonstrating the effect at the time of shifting the phase of the triangular wave carrier of a 1st and 2nd single phase inverter 180 degree
  • FIG. 10 is a configuration diagram of a power conversion device according to a sixth embodiment. It is a block diagram of the modification of the power converter device which is Embodiment 6.
  • FIG. It is a block diagram of the other modification of the power converter device which is Embodiment 6.
  • FIG. 1 to 10 show a first embodiment for carrying out the present invention.
  • FIG. 1 is a configuration diagram showing a configuration of a power converter
  • FIG. 2 is a diagram of first and second single-phase inverters.
  • FIG. 3 is a waveform diagram showing a change in power energy in and out of the second single-phase inverter.
  • 4 to 9 are explanatory diagrams for explaining the operation of the power converter
  • FIG. 10 is a PAD diagram (PROBLEM ANALYSIS DIAGRAM) of the control device of FIG.
  • a first single-phase inverter 3 as a first inverter has a single-phase full-bridge circuit 3b and AC output lines 3c and 3d.
  • the full bridge circuit 3b is composed of four field effect transistors (FETs) 3a which are switching means.
  • the second single-phase inverter 4 as the second inverter includes a single-phase full bridge circuit 4 b and a capacitor 5.
  • the single-phase full bridge circuit 4b is composed of four field effect transistors (FETs) 4a as switching means.
  • the switching means not only the FET but also a semiconductor element having a self-extinguishing capability such as an IGBT or the like can be appropriately used.
  • the capacitor 5 functions as a DC power source on the single-phase inverter side that accumulates electric charges.
  • a capacitor 2 is connected to a DC power source 1 such as a solar battery, and DC power is supplied to the first single-phase inverter 3.
  • Capacitor 2 smoothes the voltage of the DC bus.
  • the AC output side of the second single-phase inverter 4 is connected in series to one AC output line 3 c of the first single-phase inverter 3.
  • the control device 10 includes a threshold voltage adjusting device 11 and a processing device 12 and controls the first single-phase inverter 3 and the second single-phase inverter 4.
  • the threshold voltage adjusting device 11 includes a subtractor 111 and a PI control device 112.
  • a DSP DIGITAL SIGNAL PROCESSOR
  • FPGA FIELD PROGRAMMABLE GATE ARRAY
  • the power conversion device 100 is configured as described above. Then, a sine wave single-phase AC output voltage Vo is applied from the power conversion device 100 to a load 7 such as a power system through the smoothing filter 6.
  • the waveform of the output voltage V1 of the first single-phase inverter 3 is a pulse waveform that rises at time t1 and falls at time t2, as shown in FIG.
  • the control device 10 transmits a pulse-like target voltage command V1REF (FIG. 2A) as a main voltage pulse command to the first inverter 3.
  • the target voltage command V1REF has a main voltage pulse rise command S1 and a fall command S1.
  • the rise command S1 of the main voltage pulse is the main output voltage V1 at the time point t1 when the sine wave AC output voltage command VoREF becomes equal to or higher than a first threshold voltage VTHB1 (constant or variable, which will be described later) as a predetermined value.
  • the falling command S2 is transmitted so that the main voltage pulse falls at the time t2 when the AC output voltage command VoREF becomes smaller than the first threshold voltage VTH1.
  • the first inverter 3 outputs the output voltage V1 as the main voltage pulse at a rate of one pulse with respect to the half cycle of the sinusoidal AC output voltage command VoREF in response to the target voltage command V1REF.
  • the period from when the main voltage pulse rising command S1 is transmitted until the falling command S2 is transmitted is a period during which the main voltage pulse should be output in the present invention.
  • the first threshold voltage VTHB1 can be obtained from the voltage VC1 of the capacitor 2 that is the DC power supply on the single-phase inverter side and the effective value VoRMS of the AC output voltage Vo of the power converter 100.
  • the output power factor is 1, the power Pmain output from the first single-phase inverter 3 only needs to match the total output power Po of the power converter. Therefore, the AC voltage value at the phase ⁇ th where the following equation (1) holds is the threshold voltage VTHB1.
  • Vp is the peak voltage of the sine wave AC voltage
  • Ip is the peak current of the sine wave AC current.
  • the control device 10 gives an output voltage command V2REF as a compensation voltage command to the second single-phase inverter 4 so that the AC output voltage Vo of the power conversion device 100 becomes a sine wave, as shown in FIG.
  • Output voltage V2 is output by the PWM control method.
  • the output voltage command V2REF is a command for the voltage to be output from the second single-phase inverter 4.
  • the output voltage command V2REF is output to the second single-phase inverter 4 so as to correct the difference based on the difference between the sinusoidal AC output voltage command VoREF and the output voltage V1 of the first single-phase inverter 3. Is done.
  • the AC side of the second single-phase inverter 4 is connected in series to the AC output line 3 c of the first single-phase inverter 3.
  • the output voltage command V2REF may be output based on the difference between the sinusoidal AC output voltage command VoREF and the target voltage command V1REF of the first single-phase inverter 3, and there is substantially no difference.
  • the second single-phase inverter 4 is different from a general PWM inverter having only positive power.
  • the output power P1 of the second single-phase inverter 4 has a positive polarity and a negative polarity.
  • the capacitor 5 of the second single-phase inverter 4 is discharged and electric energy is released.
  • it is negative power energy is supplied and charged.
  • the electrical characteristics of the direct-current power source 1 such as a solar cell that is an input and the electrical characteristics of the load 7 represented by the power system that is an output are not always the same, and the threshold voltage VTHB1 also changes depending on the conditions.
  • the threshold voltage VTHB1 also changes depending on the conditions. For example, as shown in FIG. 4A, consider an operation at a time point t1 when the AC voltage is positive and is the rising point of the main voltage pulse output of the first single-phase inverter 3.
  • the time point t1 is a time point at which the rising command S1 of the main voltage pulse of the target voltage command V1REF should be transmitted to the first single-phase inverter 3, and is also a time point at which the main voltage pulse should rise.
  • the output voltage command V2REF of the second single-phase inverter 4 is higher than the voltage VC2 between the terminals of the capacitor 5, and a period Ta during which the second single-phase inverter 4 cannot output may occur before time t1. .
  • the control device 10 performs control so that the first single-phase inverter 3 partially performs high-frequency switching operation by PWM control as shown in FIG. Compensates for output voltage.
  • the first single-phase inverter 3 compensates for the output voltage that is insufficient in the period Ta, so that the power conversion apparatus 100 outputs the sine wave-shaped AC output voltage Vo.
  • the period Ta is a first period in which the voltage of the capacitor 5 is insufficient with respect to the compensation voltage command V2REF in the present invention and the output voltage V2 of the second inverter 4 is insufficient.
  • the period Ta is also an output impossible period in which the output voltage of the second single-phase inverter 4 is insufficient.
  • the first single-phase inverter 3 outputs power energy in the period Ta in which the normal output is not performed. For this reason, the output becomes excessive, and the capacitor 5 of the second single-phase inverter 4 is charged excessively. Therefore, as shown in FIG. 6A, the first single-phase inverter 3 performs high-frequency switching control by PWM control during the period Tb (details will be described later) to reduce the output, It adjusts so that the electric power energy which a 1st single phase inverter outputs becomes the output electric power required for a power converter device, and prevents excessive output.
  • the period Tb is the second period of the present invention.
  • the period Tb is a period after the time point t1, is a period during which the first inverter 3 was supposed to output the main voltage pulse, and is also a power adjustment PWM period for decreasing the output.
  • the start point of the period Tb is a time point t1 (see FIG. 5A) when the AC output voltage command VoREF for the first single-phase inverter 3 becomes larger than the first threshold voltage VTHB1. This time is also the end point of the period Ta.
  • the period Tb is set as follows. Due to the switching operation of the first single-phase inverter 3 in the period Ta (see FIG. 5A), the power energy output from the first single-phase inverter 3 becomes excessive, and the voltage VC2 of the capacitor 5 becomes the predetermined capacitor voltage. When the target voltage VC2REF is exceeded, a second threshold voltage VTHB2 that is higher than the reference first threshold voltage VTHB1 by a control amount ⁇ as a predetermined control amount is obtained. A method for obtaining the control amount ⁇ (see FIG. 6A) will be described later. When the AC output voltage command VoREF becomes larger than the second threshold voltage VTHB2, the first single-phase inverter 3 starts outputting the main voltage pulse as usual. This time is the end point of the period Tb. Note that this period Tb is originally an initial part of the rise of the main voltage pulse, and PWM control is performed in this initial part.
  • a difference Dp (a negative value) between the power energy (power amount) when the first single-phase inverter 3 is switched by PWM control in the period Tb and the power energy when the first single-phase inverter 3 is not switched is a negative value in the period Ta.
  • the process ends when the power energy Pg supplied from the first single-phase inverter 3 becomes the same. That is, the process ends when the power energy difference Dp and the power energy Pg are offset.
  • the operation of the second single-phase inverter 4 is stopped during the period Ta and the period Tb, and the supply of voltage is not performed. not going.
  • the threshold voltage is set to the first threshold voltage VTHB1 regardless of the above. And the capacitor 5 of the second single-phase inverter 4 may be charged.
  • the operation at the time t2 when the main voltage pulse falls is the same. That is, as shown in FIG. 4B, after the time point t2, when the period Ta1 in which the output voltage command V2REF of the second single-phase inverter 4 is higher than the voltage VC2 of the capacitor 5 occurs, the period Ta1 In FIG. 5, the control device 10 performs control for partially performing high-frequency switching by PWM control on the first single-phase inverter 3 as shown in FIG.
  • the control device 10 causes the first single-phase inverter 3 to partially perform a high-frequency switching operation by PWM control to compensate for an output voltage that is insufficient in the period Ta1, and the power conversion device 100 has a sinusoidal AC output.
  • the voltage Vo is output.
  • the control device 10 PWM-controls the output voltage of the first inverter only during a period Tb1 (details will be described later) as a second period before the time t2. Reduce the output power energy.
  • the controller 10 cancels the amount of power energy supplied from the first inverter 3 in the period Ta1 by reducing the power energy output by PWM control of the output voltage of the first inverter.
  • the time point t2 is a time point at which a falling command of the main voltage pulse of the target voltage command V1REF should be transmitted to the first single-phase inverter 3, and also a time point at which the main voltage pulse should fall (FIG. 2 ( a)).
  • the period Ta1 is a period during which the second single-phase inverter 4 cannot output because the output voltage command V2REF is higher than the voltage VC2 between the terminals of the capacitor 5 and the output voltage of the second single-phase inverter 4 is insufficient. .
  • the period Ta1 is a first period in which the voltage of the capacitor 5 is insufficient with respect to the compensation voltage command V2REF in the present invention and the output voltage V2 of the second inverter 4 is insufficient.
  • the period Tb is also a period during which the first single-phase inverter 3 should have continued to output the main voltage pulse.
  • the setting of the period Tb1 which is the power adjustment PWM period, is performed by the same method as the setting of the period Tb in FIG.
  • a difference Dp2 (a negative value) between the power energy when the first single-phase inverter 3 is switched by PWM control in the period Tb1 and the power energy when the first single-phase inverter 3 is not switched is a first single value in the period Ta1.
  • the power energy Pg2 supplied from the phase inverter 3 is set to be the same. That is, the difference Dp2 and the power energy Pg2 are set so as to cancel each other.
  • the difference Dp2 and the power energy Pg2 are set so as to cancel each other.
  • the operation of the second single-phase inverter 4 is stopped, and the voltage supply is performed. Not. If the DC voltage VC2 of the second single-phase inverter 4 is lower than the target voltage VC2REF for some reason, such as a load change, the threshold voltage is set higher than the first threshold voltage VTHB1 regardless of the above. And the capacitor 5 of the second single-phase inverter 4 may be charged.
  • the control device 10 needs to perform PWM control on the output voltage of the first single-phase inverter 3 to compensate (supply) the voltage.
  • the control device 10 indicates that the output AC voltage command value VoREF (the output voltage V2 of the second single-phase inverter 4) is The first single-phase inverter 3 starts PWM control when it becomes higher than a third threshold voltage VTHB3 (described later) as in 9 (a).
  • This point is the start point of the PWM control period Td (FIG. 9A) for power adjustment as the third period.
  • the third threshold voltage VTHB3 is a value lower than the first threshold voltage VTHB1 by the control amount ⁇ (described above).
  • the power energy supplied by the switching of the first single-phase inverter 3 in the period Td cancels the power energy that has become insufficient due to the switching of the first single-phase inverter 3 in the period Tc.
  • the control device 10 performs control for causing the first single-phase inverter 3 to partially perform a high-frequency switching operation by PWM control as shown in FIG. 8B, and outputs that are insufficient in the period Tc1. Compensate for voltage.
  • the control device 10 compensates for the insufficient output voltage so that the power conversion device 100 outputs the AC output voltage Vo having a sine wave shape.
  • the output energy is reduced because the first single-phase inverter 3 performs a high-frequency switching operation by PWM control in the period Tc1 for normal output.
  • the first single-phase inverter 3 performs PWM control on the output voltage of the first inverter only for the period Td1 as the fifth period after the time point t2.
  • the decrease in the power energy supplied from the first inverter 3 in the period Tc1 is offset by increasing the output power energy.
  • the period Tc1 is a first period in which the voltage of the capacitor 5 is insufficient with respect to the compensation voltage command V2REF in the present invention and the absolute value of the output voltage V2 of the second inverter 4 is insufficient.
  • the setting of the period Td1 is performed in the same manner as the setting of the period Td in FIG. In the period Td1, the difference between the power energy when the first single-phase inverter 3 is switched by PWM control in the period Tc1 and the power energy when the first single-phase inverter 3 is not switched is supplied from the first single-phase inverter 3 in the period Td1. Set to be the same as the power energy.
  • the operation of the second single-phase inverter 4 is stopped during the period Tc1 and the period Td1, and the voltage supply is performed.
  • the threshold voltage is set to the first threshold voltage VTHB1 regardless of the above. And the capacitor 5 of the second single-phase inverter 4 may be charged.
  • the second single-phase inverter 4 is stopped while the first single-phase inverter 3 is performing high-frequency switching by PWM control. For this reason, the output voltage V1 of the first single-phase inverter 3 becomes the AC output voltage Vo of the power conversion device 100 as it is, and instead of the second single-phase inverter 4, the first single-phase inverter 3 to the power conversion device 100 Voltage is output.
  • Control such as P control and PI control may be used to determine the control amount ⁇ of the threshold voltage VTHB1.
  • PI control is performed using the threshold voltage adjustment device 11 shown in FIG. In FIG.
  • the voltage VC2 of the capacitor 5 of the second single-phase inverter 4 and the target voltage VC2REF of the capacitor 5 are input to the subtractor 111, and the deviation ⁇ is input to the PI controller 112.
  • the PI control device 112 determines the control amount ⁇ of the threshold voltage based on the deviation ⁇ , and calculates the second threshold voltage VTHB2 and the third threshold voltage VTHB3 by adjusting ⁇ from the first threshold voltage VTHB1.
  • FIG. 10 The PAD figure of the said control is shown in FIG.
  • PWM1 ON indicates that the first single-phase inverter 3 operates by PWM control
  • PWM1 OFF indicates that PWM control operation is not performed.
  • the first single-phase inverter 3 is partially operated by PWM control, so that the shortage of voltage during the period Ta during which the second single-phase inverter 4 cannot output can be compensated, and thereby the second single-phase inverter 3 Since the operation is performed even when the voltage of the capacitor 5 of the inverter 4 is set to be low, switching means such as a low breakdown voltage semiconductor element can be used for the second single-phase inverter 4 and the cost is reduced.
  • FIG. 11 to 14 show the second embodiment.
  • FIG. 11 is a configuration diagram of the power converter
  • FIGS. 12 and 13 are waveform diagrams for explaining the operation
  • FIG. 14 is a PAD diagram of the controller.
  • the power conversion device 200 includes a control device 20.
  • the control device 20 has a processing device 22. Since other configurations are the same as those of the first embodiment shown in FIG. 1, the corresponding components are denoted by the same reference numerals and description thereof is omitted.
  • the processing device 22 does not operate only the first single-phase inverter 3 in the period Ta, but, as shown in FIG. 12, the first single-phase inverter 3 and the second single-phase inverter 3 in the period Ta.
  • Control is performed so that the single-phase inverter 4 outputs power energy (voltage).
  • the second single-phase inverter 4 can output a voltage up to the DC bus voltage of the second single-phase inverter 4, that is, the voltage VC ⁇ b> 2 of the capacitor 5.
  • the PWM control period Tb of the first single-phase inverter 3 can be shortened.
  • the first single-phase inverter 3 needs to perform PWM control during the period Tc to be normally output as the main voltage pulse, the second single-phase inverter 3 also corresponds to the output voltage command V2REF in the period Tc. If the voltage VC2 of the capacitor 5 of the single-phase inverter 4 is continuously output, the PWM control period for adjusting the electric power of the first single-phase inverter 3 as shown in FIG. Td can be shortened.
  • the control device 20 performs the control described above.
  • FIG. 14 shows a PAD diagram of the control.
  • FIG. FIGS. 15 to 18 show the third embodiment
  • FIG. 15 is a configuration diagram of the power converter
  • FIGS. 16 and 17 are waveform diagrams for explaining the operation
  • FIG. 18 is a PAD diagram of the controller.
  • the power conversion device 300 includes a control device 30.
  • the control device 30 includes a PWM output amount adjustment device 31 and a processing device 32.
  • the PWM output amount adjustment device 31 includes a subtractor 311 and a PI control device 312. Since other configurations are the same as those of the first embodiment shown in FIG. 1, the corresponding components are denoted by the same reference numerals and description thereof is omitted.
  • the control device 30 operates as follows, and FIG. 18 shows a PAD diagram.
  • the control device 30 gives the output voltage command V2REF of the second single-phase inverter 4 in the partial PWM control period as a variable instead of being fixed, and controls the voltage VC2 of the capacitor 5 of the second single-phase inverter 4.
  • the control amount ⁇ (FIG. 16 (b) shown in FIG. 16B is used as the output voltage command V2REF of the second single-phase inverter 4 as a predetermined control amount. ))
  • the output power of the first single-phase inverter 3 becomes larger than the power to be output by the power converter, and the surplus power is charged in the capacitor 5 of the second single-phase inverter 4.
  • VC2 rises.
  • the target output command V1REF in FIG. 16 indicates a command waveform in the partial PWM control period.
  • the output voltage command V2REF of the second single-phase inverter 4 is increased by the control amount ⁇ (FIG. 17B).
  • the increased amount is compensated by lowering the target output command V1REF of the first single-phase inverter 3.
  • the output power of the first single-phase inverter 3 becomes smaller than the power to be output by the power converter, and the insufficient power is supplied from the capacitor 5 of the second single-phase inverter 4.
  • VC2 decreases.
  • the target output command V1REF in FIG. 17 indicates a command waveform in the partial PWM control period.
  • a threshold control device such as P control or PI control may be used to determine the control amount ⁇ .
  • the PWM output amount adjusting device 31 performs PI control. Note that the absolute value of the output voltage command V2REF of the second single-phase inverter 4 varies from 0 to the voltage VC2 of the capacitor 5 of the second single-phase inverter 4.
  • the voltage of the capacitor 5 of the second single-phase inverter 4 can be controlled and an overvoltage can be prevented, so that a capacitor having an appropriate voltage can be used. Further, overvoltage can be prevented even if the voltage of the DC power supply 1 changes suddenly due to disturbance such as power flow.
  • FIG. 19 and 20 show the fourth embodiment.
  • FIG. 19 is a configuration diagram of the power conversion device
  • FIG. 20 is a PAD diagram of the control device.
  • the power conversion device 400 includes a control device 40.
  • the control device 40 includes a PWM output amount adjustment device 41 and a processing device 42.
  • the PWM output amount adjustment device 41 includes a subtracter 411 and a PI control device 412. Since other configurations are the same as those of the first embodiment shown in FIG. 1, the corresponding components are denoted by the same reference numerals and description thereof is omitted.
  • the control device 40 operates as described below, and FIG. 20 shows a PAD diagram.
  • the power factor is not 1 and the case where the output voltage and the output current are out of phase can be handled.
  • the power conversion device 400 When the output current phase shifts, the power conversion device 400 generates a period in which the polarity of the output power energy is negative. In the above period, adding and subtracting the control amount has an adverse effect, so the control amount needs to be reversed.
  • the correction direction of the control amount is determined by the power energy polarity PREF of the power converter.
  • the power energy polarity PREF is positive if the output current is positive, and the power energy polarity PREF is negative if the output current is negative.
  • the power energy polarity PREF is negative if the output current is positive
  • the power energy polarity PREF is positive if the output current is negative.
  • the power energy polarity PREF is positive and the voltage VC2 of the capacitor 5 of the second single-phase inverter 4 is lower than the target voltage VC2REF.
  • the output voltage command V2REF of the second single-phase inverter 4 is changed so as to decrease by a control amount ⁇ (described later in detail) as a predetermined control amount.
  • the output voltage command V2REF of the second single-phase inverter 4 is changed to increase by ⁇ .
  • the output voltage command V2REF of the second single-phase inverter 4 is increased by ⁇ To change.
  • the output voltage command V2REF of the second single-phase inverter 4 is changed in the direction of decreasing by ⁇ .
  • a control device such as P control or PI control may be used to determine the control amount ⁇ that raises or lowers the output voltage command V2REF.
  • the PWM output amount adjusting device 41 performs PI control.
  • the controllable range of the absolute value of the output voltage command V2REF is from 0 to the voltage VC2 of the capacitor 5 of the second single-phase inverter 4.
  • the present invention can be applied even when the power factor of the load is not 1.
  • FIG. FIGS. 21 and 22 show the fifth embodiment
  • FIG. 21 is a configuration diagram of the power converter
  • FIG. 22 is a case where the phases of the triangular wave carriers of the first and second single-phase inverters are shifted by 180 degrees. It is a wave form diagram for demonstrating the effect of this.
  • the power conversion device 500 includes a control device 50.
  • the control device 50 includes a processing device 52. Since other configurations are the same as those of the third embodiment shown in FIG. 15, the corresponding components are denoted by the same reference numerals and description thereof is omitted.
  • the control device 50 operates as described below.
  • the present embodiment is based on the third embodiment or the fourth embodiment.
  • the first single-phase inverter 3 is partially PWM-controlled in the same manner as in the third and fourth embodiments.
  • the second single-phase inverter 4 is also PWM controlled.
  • the triangular wave comparison method when the phases of the triangular wave carriers in the first single-phase inverter 3 and the second single-phase inverter 4 are the same, the first single-phase inverter 3 and the second single-phase inverter 3 The center of each pulse of the single-phase inverter 4 coincides. For this reason, when the second single-phase inverter 4 outputs positive, the voltage output at the time of one switching increases and the current ripple increases.
  • FIG. 22 shows that the voltage ratio of the voltage VC1 of the capacitor 2 of the first single-phase inverter 3 and the voltage VC2 of the capacitor 5 of the second single-phase inverter 4 is 2 to 1, and the output of the second single-phase inverter 4 is It is positive and shows a comparison of ripple currents when the phases of two triangular wave carriers (waveform c1 and waveform c2) in the first single-phase inverter 3 and the second single-phase inverter 4 are shifted by 180 degrees. is there.
  • FIG. 22A shows a ripple current waveform W1 when the phases of two triangular wave carriers (waveform c1 and waveform c2) are the same.
  • 22B shows a ripple current waveform W2 when the phases of two triangular wave carriers (waveform c1 and waveform c2) are shifted by 180 degrees.
  • the waveform a1 is the PWM output of the first single-phase inverter 3
  • the waveform a2 is the PWM output of the second single-phase inverter 4.
  • FIG. FIGS. 23 to 25 show the sixth embodiment
  • FIG. 23 is a configuration diagram of a power conversion device
  • FIG. 24 is a configuration diagram of another power conversion device which is a modification
  • FIG. 25 is another modification. It is a block diagram of the other power converter device which is.
  • the power conversion device 600 includes capacitors 2 a and 2 b connected in series, a first single-phase inverter 603 as a first inverter of three levels, and a control device 60.
  • the first single-phase inverter 603 has AC output lines 603c and 603d.
  • the AC output side of the second single-phase inverter 4 is connected in series to one AC output line 603 c of the first single-phase inverter 603.
  • the control device 60 operates in the same manner as the control device 10 in the first embodiment.
  • the operation of the power conversion device 600 differs only in the configuration of the first single-phase inverter, and the power shown in FIG. This is the same as the conversion device 100.
  • the power conversion device 700 includes a three-phase inverter 703 as a first inverter, a second single-phase inverter 704 as a second inverter, and a control device 70.
  • the AC output side of the second single-phase inverter 704 is connected in series to the three AC output lines 703c, 703d, and 703e of the three-phase inverter 703, respectively.
  • the control device 70 operates in the same manner as the control device 10 in the first embodiment, and the operation of the power conversion device 700 is the same as that of the power conversion device 100 shown in FIG. It is.
  • the power converter device 800 can also be comprised.
  • the second single-phase inverter as the second inverter may be divided into two second single-phase inverters 804, and a control device 80 for controlling them may be provided.
  • Control device 80 operates in the same manner as control device 10 in the first embodiment, and operation of power conversion device 800 is the same as that of power conversion device 100 shown in FIG. 1 except for the configuration of the inverter.
  • the first inverter may be a single-phase inverter or a three-phase inverter.
  • the second single-phase inverter can be configured as three or more single-phase inverters 804.
  • control devices 60, 70, 80 instead of the control devices 60, 70, 80 in this embodiment, a control device that operates in the same manner as the control devices 20, 30, 40, 50 shown in the second to fifth embodiments can be used. Needless to say, the power converters having various characteristics can be configured by appropriately combining the individual configurations shown in the above embodiments.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
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Abstract

L'invention concerne un onduleur monophasé (3) qui produit une unique impulsion principale de tension à chaque demi-cycle d'une instruction de tension de sortie alternative sinusoïdale. Un onduleur monophasé (4) réalise une commande de modulation PWM sur la tension d'un condensateur (5) et produit une tension destinée à compenser la différence entre l'instruction de tension de sortie alternative et l'impulsion principale de tension et les côtés alternatifs de chacun des deux onduleurs monophasés (3, 4) sont connectés en série. La tension de sortie (Vo) qui constitue la sortie totale est conçue pour être une onde sinusoïdale; cependant, lorsque l'onduleur monophasé (4) doit produire la tension de compensation, la compensation ne peut pas se faire si la tension du condensateur (5) est basse. L'insuffisance de tension doit donc être compensée par une commande de la modulation PWM de l'onduleur monophasé (3); par contre, si l'onduleur monophasé (3) compense l'insuffisance de tension, la quantité d'énergie fournie devient excessive et la tension du condensateur (5) est élevée. L'énergie produite est donc réduite par réalisation d'une modulation PWM pendant la période de sortie de l'impulsion principale de tension, si bien que l'on évite l'élévation de la tension. Il devient donc inutile d'avoir un dispositif fournissant une alimentation à l'onduleur monophasé (4), ce qui permet de réduire le coût et la perte d'énergie.
PCT/JP2011/051319 2010-01-26 2011-01-25 Dispositif de conversion électrique WO2011093269A1 (fr)

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US20190260306A1 (en) * 2017-01-11 2019-08-22 Murata Manufacturing Co., Ltd. Power converter
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JP2013240203A (ja) * 2012-05-15 2013-11-28 Omron Corp インバータ装置および太陽光発電システム
US9425679B2 (en) 2012-05-15 2016-08-23 Omron Corporation Inverter apparatus and solar power generation system
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US11742777B2 (en) 2013-03-14 2023-08-29 Solaredge Technologies Ltd. High frequency multi-level inverter
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US11296590B2 (en) 2014-03-26 2022-04-05 Solaredge Technologies Ltd. Multi-level inverter
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US20190260306A1 (en) * 2017-01-11 2019-08-22 Murata Manufacturing Co., Ltd. Power converter
US20230261563A1 (en) * 2020-08-04 2023-08-17 Mitsubishi Electric Corporation Power conversion device
US12107487B2 (en) * 2020-08-04 2024-10-01 Mitsubishi Electric Corporation Power conversion device
JP2022119256A (ja) * 2021-02-04 2022-08-17 三菱電機株式会社 電力変換装置
JP7466476B2 (ja) 2021-02-04 2024-04-12 三菱電機株式会社 電力変換装置
US12136890B2 (en) 2023-11-14 2024-11-05 Solaredge Technologies Ltd. Multi-level inverter

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