WO2009131110A1 - 無線通信システム、送信装置、受信装置、無線通信方法、送信方法、受信方法 - Google Patents

無線通信システム、送信装置、受信装置、無線通信方法、送信方法、受信方法 Download PDF

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Publication number
WO2009131110A1
WO2009131110A1 PCT/JP2009/057904 JP2009057904W WO2009131110A1 WO 2009131110 A1 WO2009131110 A1 WO 2009131110A1 JP 2009057904 W JP2009057904 W JP 2009057904W WO 2009131110 A1 WO2009131110 A1 WO 2009131110A1
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Prior art keywords
frequency offset
frequency
unit
physical quantity
training
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PCT/JP2009/057904
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English (en)
French (fr)
Japanese (ja)
Inventor
洋輔 藤野
大誠 内田
藤田　隆史
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日本電信電話株式会社
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Application filed by 日本電信電話株式会社 filed Critical 日本電信電話株式会社
Priority to ES09734275.2T priority Critical patent/ES2689945T3/es
Priority to JP2010509181A priority patent/JP5286576B2/ja
Priority to EP09734275.2A priority patent/EP2270993B1/en
Priority to US12/988,417 priority patent/US8644766B2/en
Priority to CN2009801139292A priority patent/CN102007700B/zh
Publication of WO2009131110A1 publication Critical patent/WO2009131110A1/ja

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H04L27/38—Demodulator circuits; Receiver circuits
    • H04L27/3845—Demodulator circuits; Receiver circuits using non - coherent demodulation, i.e. not using a phase synchronous carrier
    • H04L27/3854—Demodulator circuits; Receiver circuits using non - coherent demodulation, i.e. not using a phase synchronous carrier using a non - coherent carrier, including systems with baseband correction for phase or frequency offset
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/0014—Carrier regulation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/0014—Carrier regulation
    • H04L2027/0024—Carrier regulation at the receiver end
    • H04L2027/0026—Correction of carrier offset
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/0014—Carrier regulation
    • H04L2027/0024—Carrier regulation at the receiver end
    • H04L2027/0026—Correction of carrier offset
    • H04L2027/0038—Correction of carrier offset using an equaliser
    • H04L2027/0042—Correction of carrier offset using an equaliser the equaliser providing the offset correction per se
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/0014—Carrier regulation
    • H04L2027/0044—Control loops for carrier regulation
    • H04L2027/0063—Elements of loops
    • H04L2027/0067—Phase error detectors
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/0014—Carrier regulation
    • H04L2027/0083—Signalling arrangements
    • H04L2027/0089—In-band signals
    • H04L2027/0093—Intermittant signals
    • H04L2027/0095—Intermittant signals in a preamble or similar structure

Definitions

  • the present invention relates to a wireless communication system, a transmission device, a reception device, a wireless communication method, a transmission method, and a reception method.
  • Digital radio communication systems use modulation schemes such as PSK (Phase Shift Keying) and QAM (Quadrature Amplitude Modulation) in order to improve frequency utilization and transmission characteristics.
  • modulation schemes such as PSK (Phase Shift Keying) and QAM (Quadrature Amplitude Modulation)
  • PSK Phase Shift Keying
  • QAM Quadrature Amplitude Modulation
  • information is modulated on the phase. Therefore, in the presence of a carrier frequency offset due to a frequency difference between the transmitter and the transmitter on the transmission side, the transmission characteristics are greatly degraded due to phase rotation due to the carrier frequency offset.
  • Methods for estimating the carrier frequency offset include a method using a predetermined series of training signals and a blind method that does not require a training signal.
  • the latter blind method does not require a training signal, and thus can achieve high transmission efficiency.
  • the carrier frequency offset cannot be estimated in a short time. Therefore, in a wireless communication system that performs burst transmission that needs to estimate a carrier frequency offset in a short time, a method of estimating a carrier frequency offset using a predetermined series of training signals is used (Non-Patent Document 1).
  • FIG. 15 is a diagram illustrating the transmission device 5 and the reception device 6 in the wireless communication system 300.
  • a radio communication system 300 that uses a technique for estimating a carrier frequency offset using a known series of training signals shown in Non-Patent Document 1 will be described with reference to FIG.
  • the wireless communication system 300 includes a transmission device 5 and a reception device 6.
  • the transmission device 5 includes a training signal sequence generation unit 51, a radio unit 52, and a transmission antenna 53.
  • the training signal sequence generation unit 51 generates a predetermined sequence of training signals.
  • the radio unit 52 performs analog conversion and frequency conversion on the training signal generated by the training signal sequence generation unit 51 and transmits the training signal from the transmission antenna 53 to the reception device 6.
  • the reception device 6 includes a reception antenna 61, a radio unit 62, a phase difference detection unit 63, an averaging unit 64, and a frequency estimation unit 65.
  • the reception antenna 61 receives a radio signal transmitted from the transmission device 5.
  • the radio unit 62 performs frequency conversion and digital conversion on the radio signal received by the reception antenna 61 to generate a reception signal.
  • the phase difference detection unit 63 compares the received signal with a training signal based on a predetermined sequence, and detects a physical quantity that is obtained according to the phase transition amount for a certain time and includes the influence of noise.
  • a training signal is a signal sequence that is repeated at intervals of 0.8 ⁇ s, and a physical quantity that is a function of a phase transition amount between 0.8 ⁇ s is detected by delaying a received signal by 0.8 ⁇ s. ing.
  • the averaging unit 64 averages the physical quantities detected by the phase difference detection unit 63 in order to avoid the influence of noise.
  • the frequency estimation unit 65 estimates the carrier frequency offset from the physical quantity averaged by the averaging unit 64.
  • n be the sample number
  • the training signal generated by the training signal sequence generation unit 51 be s (n).
  • a received signal y (n) that is received by the receiving antenna 61, frequency-converted and digital-converted by the radio unit 62, and generated as a result thereof is expressed by Expression (1).
  • h is a complex amplitude response between the transmission antenna 53 and the reception antenna 61.
  • ⁇ f is a carrier frequency offset between the transmission device 5 and the reception device 6.
  • f s is a sampling frequency.
  • ⁇ (n) is noise that is uncorrelated for each sample and follows a complex Gaussian distribution with an average power amount of 1. For the sake of simplicity, hereinafter, it is assumed that the magnitude (
  • the phase difference detection unit 63, the averaging unit 64, and the frequency estimation unit 65 receive the radio signal and the received signal y (n) and the training signal s (n) generated by the training signal sequence generation unit 51. Are used to estimate the carrier frequency offset ⁇ f.
  • the training signal s (n) is a training signal based on a predetermined signal sequence.
  • delay detection type phase difference detection is used in the phase difference detection unit 63, that is, the delay detection result in the time difference ⁇ sample of the received signal y (n) and the delay detection result in the time difference ⁇ sample of the training signal s (n).
  • a physical quantity z (n) which is a function of the phase transition amount in the time difference ⁇ sample, is expressed by Expression (2).
  • Equation (2) ⁇ (n) is represented by equation (3).
  • the averaged physical quantity ⁇ can be expressed by the following equation when the number of samples N is larger than the value of the time difference ⁇ samples (phase difference N> ⁇ ). 4).
  • Equation (4) Re [•] represents a real number.
  • the averaged physical quantity ⁇ is expressed by Expression (5).
  • the frequency estimation unit 65 calculates an estimated value f est of the carrier frequency offset based on the equation (6).
  • Im [•] represents an imaginary number.
  • ⁇ r and ⁇ i indicating noise are variables that follow a Gaussian distribution with a variance of 1.
  • ⁇ r and ⁇ i indicating noise are variables that follow a Gaussian distribution with a variance of 1.
  • a case will be described in which the sum of the powers of the received signals used for estimation of the carrier frequency offset is sufficiently higher than the noise power, that is, a case represented by Expression (9).
  • the estimated value f est of the carrier frequency offset calculated by the frequency estimation unit 65 is tan ⁇ when ⁇ takes a value sufficiently smaller than 1 ( ⁇ ⁇ 1). Use relationships. At this time, when N> ⁇ , the estimated value f est of the carrier frequency offset can be approximated by Expression (10).
  • Equation (11) the estimated carrier frequency offset value f est can be approximated by Equation (11).
  • ⁇ ⁇ representing noise is a variable that follows a Gaussian distribution with a variance of 1.
  • the pull-in range in which the carrier frequency offset can be estimated is defined by, for example, Expression (12).
  • the sampling rate is slower, the time of the time difference ⁇ sample is longer, the reception level
  • the sampling rate f s and the time difference ⁇ sample are limited in the range that can be set by the pull-in range of the carrier frequency offset shown in Expression (12). Therefore, in the conventional frequency offset estimation system, the sampling rate f s and the value of the time difference ⁇ sample are determined from the required carrier frequency offset pull-in range. Thereafter, the number N of samples is determined from the allowable estimation error and the assumed reception level
  • the reception level greatly decreases with a certain probability.
  • the instantaneous reception level is 20 dB or more lower than the average reception level.
  • This Rayleigh fading environment is a general model of a multipath environment. Therefore, when a conventional carrier frequency offset estimation system is used in a multipath fading environment, the average number of samples is defined by CNR (Carrier-to-Noise Ratio) in order to avoid an increase in estimation error due to a decrease in reception level.
  • CNR Carrier-to-Noise Ratio
  • the present invention has been made in consideration of the above-described circumstances, and an object of the present invention is to provide a radio communication system, a transmission apparatus, and a reception apparatus that accurately estimate a carrier frequency offset with a small number of averaged samples even in a multipath environment. It is to provide a wireless communication method, a transmission method, and a reception method.
  • a wireless communication system uses a transmission apparatus that transmits a plurality of radio signals, a plurality of radio signals from the transmission apparatus, and a carrier frequency and a reception that the transmission apparatus transmits. And a receiving apparatus that estimates a difference from a reference reception frequency as a carrier frequency offset, branching a predetermined first sequence of training signals, and branching a plurality of first sequences A transmitting apparatus that transmits the radio signal modulated at a frequency by the carrier frequency offset having regularity with respect to each of the training signals, and the first sequence included in the radio signal transmitted from the transmitting apparatus According to the phase transition amount obtained from the training signal of the first sequence and the training signal of the first sequence determined in advance. And a receiving device for estimating the carrier frequency offset.
  • the phase difference detection of the training signal is facilitated by the function of the frequency offset added to the first series of training signals transmitted by a plurality of radio signals. Therefore, the carrier frequency offset can be estimated with high accuracy with a short training signal length or a smaller transmission power.
  • a wireless communication system includes a transmission device that transmits a plurality of wireless signals from a plurality of transmission antennas, and a plurality of wireless signals from the transmission device that are received by a reception antenna.
  • a wireless communication system comprising: a reception device that estimates a difference between a carrier frequency to be transmitted and a reference reception frequency used for reception as a carrier frequency offset, wherein the transmission device includes a predetermined first series of training signals An integer multiple of the frequency f 1 for each frequency assigned to the training signal of the first sequence branched to the same number as the number of the plurality of transmission antennas.
  • a first frequency offset applying unit for applying a frequency offset, and the first frequency offset applying unit.
  • a transmission unit that transmits the radio signal including the first series of training signals having the frequency offset to the reception device through the transmission antenna, and the reception device transmits the transmission device through the reception antenna.
  • a first phase difference detection unit that detects a first physical quantity corresponding to a phase transition amount at a time difference T 1 that is a natural number times the time represented by the reciprocal of the frequency f 1 , and averages the first physical quantity
  • a first averaging unit that calculates a first averaged physical quantity, and a frequency estimation unit that estimates a carrier frequency offset based on the first averaged physical quantity.
  • a steady drop in the reception level can be avoided by the action of the frequency offset added to the predetermined series of training signals transmitted by the plurality of radio signals from the plurality of transmission antennas.
  • a carrier frequency offset can be estimated with high accuracy with a short training signal length or smaller transmission power even in a multipath fading environment.
  • the transmission device further includes a second training signal sequence generation unit that generates a predetermined second sequence of training signals, and the plurality of transmissions.
  • a frequency offset in which the absolute value of all frequency offsets is smaller than half of the reciprocal of the time difference T 1 is assigned to each frequency assigned to the training signal of the second series branched as many as the number of antennas.
  • the wireless signal is transmitted to the reception device through the transmission antenna, and the reception device further includes a second series of training signals included in the wireless signal transmitted from the transmission device, and a predetermined second sequence.
  • a second phase difference detection unit for detecting a second physical quantity corresponding to a phase transition amount at a time difference T 2 shorter than the time difference T 1 , and averaging the second physical quantity based on the training signal of
  • a second averaging unit that calculates a second averaged physical quantity, wherein the frequency estimation unit is configured to calculate the carrier frequency offset based on the first averaged physical quantity and the second averaged physical quantity. May be estimated.
  • a wide pull-in range and a short pull-in time can be realized by performing phase difference detection using the second series of training signals.
  • the estimation accuracy is set within the pull-in range of phase difference detection using the first series of training signals.
  • the second frequency offset imparting section the absolute value of the difference of all the frequency offset to be granted, the frequency to be an integral multiple of the frequency f 2 grant offset, the second averaging unit, the second physical quantity in a range of a natural number times the reciprocal of the frequency f 2 may be averaged. Accordingly, the carrier frequency offset can be estimated with high accuracy by using the delay detection type phase difference detection in the second phase difference detection unit.
  • a transmission apparatus is a transmission apparatus that transmits a plurality of radio signals from a plurality of transmission antennas, and generates a first training signal that is determined in advance.
  • a sequence generator and a first frequency offset that is an integer multiple of the frequency f 1 is assigned to each frequency allocated to the training signal of the first sequence branched to the same number as the plurality of transmission antennas. And transmitting the radio signal including the first series of training signals having the frequency offset assigned by the first frequency offset assigning unit to the receiving device through the transmission antenna.
  • the transmission device further includes a second training signal sequence generation unit that generates a predetermined second sequence of training signals, and the plurality of transmission antennas. For each frequency allocated to the training signal of the second series branched to the same number as the number of the frequency offset, a frequency offset in which the absolute value of all the frequency offsets is smaller than half the reciprocal of the time difference T 1 is given.
  • a second frequency offset assignment unit wherein the transmission unit has the first series of training signals having the frequency offset assigned by the first frequency offset assignment unit, and the second frequency offset.
  • the second frequency offset imparting section the absolute value of the difference of all the frequency offset to be granted, the frequency to be an integral multiple of the frequency f 2 Offset May be given.
  • a receiving apparatus assigns a frequency offset that is an integer multiple of the frequency f 1 to each of the frequencies allocated to the branched first sequence of training signals, and a plurality of radios Communicating with a transmitting device that transmits signals from a plurality of transmitting antennas, receiving a plurality of radio signals from the transmitting device by a receiving antenna, and a difference between a carrier frequency transmitted by the transmitting device and a reference receiving frequency used for reception As a carrier frequency offset, the receiving unit receiving the radio signal from the transmitting device through the receiving antenna, and the first sequence included in the radio signal transmitted from the transmitting device and training signals, based on the training signals of the first series predetermined time represented by the reciprocal of the frequency f 1 Calculating a first phase difference detecting unit for detecting a first averaging physical quantity by averaging the first physical quantity natural first physical quantity corresponding to the phase shift amount in the time difference T 1 of the number of times A first averaging unit; and a frequency estimation unit that estimates
  • the absolute values of all frequency offsets are half the reciprocal of the time difference T 1 for each frequency assigned to the branched second series of training signals.
  • the second sequence of training signals having a frequency offset smaller than the value and the first sequence of training signals communicate with a transmitting device that transmits the multiplexed signals, and the receiving device further transmits from the transmitting device.
  • the second sequence corresponding to the phase transition amount at the time difference T 2 shorter than the time difference T 1 based on the second sequence training signal included in the generated radio signal and the predetermined second sequence training signal.
  • a second phase difference detection unit that detects the physical quantity of the second physical quantity, and a second averaging unit that calculates the second averaged physical quantity by averaging the second physical quantity.
  • the frequency estimation unit may estimate the carrier frequency offset based on the first average physical quantity and the second average physical quantity.
  • the communication device communicates with the transmission device that assigns the frequency offset so that the absolute value of the difference between all the applied frequency offsets is an integer multiple of the frequency f 2 .
  • the averaging unit 2 may be averaged in a range of a natural number multiple of the time of the second physical quantity the inverse of the frequency f 2.
  • the first phase difference detection unit, the time difference T 1 of the training signals of the first sequence included in a radio signal transmitted from the transmitting device The first physical quantity may be calculated by subtracting the phase transition quantity in the time difference of the predetermined first series of training signals from the phase transition quantity.
  • the first phase difference detection unit may be configured to use the first sequence training signal included in the radio signal transmitted from the transmission device in the time difference T 1 .
  • the first physical quantity may be calculated by multiplying the delay detection result and the conjugate complex of the delay detection result in the time difference between the predetermined first series of training signals. Accordingly, the carrier frequency offset can be estimated with high accuracy by using the delay detection type phase difference detection in the first phase difference detection unit.
  • the first averaging unit the average range of a natural number times the time represented the first physical quantity by the reciprocal of the frequency f 1
  • the first average physical quantity may be calculated by converting to Thereby, the physical quantity Z 1 (n) for N 1 samples, which is a natural number multiple of fs / f 1 sample, is averaged in the first averaging unit. Therefore, it is possible to obtain the carrier frequency offset estimation accuracy corresponding to the averaging sample number N 1.
  • the second phase difference detection unit may include a time difference T 2 of the second series of training signals included in the radio signal transmitted from the transmission device.
  • the second physical quantity may be calculated by subtracting the phase transition quantity at the time difference of the predetermined second series of training signals from the phase transition quantity.
  • the second phase difference detection unit is configured to use the second sequence training signal included in the radio signal transmitted from the transmission device in the time difference T 2 .
  • the second physical quantity may be calculated from the delay detection result by multiplying a conjugate complex of the delay detection result in the time difference between the second series of training signals determined in advance.
  • the absolute value of a difference between all frequency offsets assigned by the second frequency offset supply portion imparts a frequency offset so as to be an integral multiple of the frequency f 2.
  • the second averaging unit averages the physical quantity for N 2 samples, which is a natural number multiple of the sample of f s / f 2 . Thereby, the carrier frequency offset estimation accuracy according to the averaged sample number N 2 can be obtained.
  • the receiving device includes a plurality of at least one of the receiving unit, the first phase difference detecting unit, the first averaging unit, and the frequency estimating unit, and at least 1 A signal selection / synthesis unit that selects or synthesizes and outputs a plurality of signals output by the reception unit, the first phase difference detection unit, the first averaging unit, and the frequency estimation unit. You may prepare.
  • a wireless communication method uses a transmission device that transmits a plurality of wireless signals, a plurality of wireless signals from the transmission device, and a carrier frequency and a reception that the transmission device transmits.
  • a phase transition amount obtained from the first series of training signals included in and a predetermined first series of training signals Estimating a carrier frequency offset between the transmission device.
  • a wireless communication method includes: a transmission device that transmits a plurality of radio signals from a plurality of transmission antennas; a plurality of radio signals from the transmission device that are received by a reception antenna; A wireless communication method using a receiving apparatus that estimates a difference between a carrier frequency to be transmitted and a reference receiving frequency used for reception as a carrier frequency offset, wherein the transmitting apparatus performs a predetermined first sequence training.
  • An integer multiple of the frequency f 1 for the first training signal sequence generation process for generating a signal and each frequency assigned to the training signal of the first sequence branched to the same number as the plurality of transmission antennas
  • a first frequency offset applying process for applying a frequency offset, and before the first frequency offset applying process.
  • a first phase difference detection process for detecting a first physical quantity corresponding to a phase transition amount at a time difference T 1 that is a natural number times the time represented by the reciprocal of the frequency f 1 and the first physical quantity are averaged.
  • a first averaging process for calculating a first averaged physical quantity, and a frequency estimation process for estimating a carrier frequency offset based on the first averaged physical quantity, Having.
  • the transmission apparatus further generates a second training signal sequence generation process for generating a predetermined second sequence of training signals, and the plurality of transmissions. for each frequency allocated to the training signal of the second series the number of which is split into the same number of antennas, applying a frequency offset absolute value is less than half the value of the reciprocal of the time difference T 1 of the all frequency offset
  • a second frequency offset assigning step wherein in the transmission step, the first sequence of training signals having the frequency offset assigned in the first frequency offset assigning step, and the second Multiplexing the second series of training signals having the frequency offset applied in the frequency offset applying process
  • a radio signal is transmitted to the reception device through the transmission antenna, and the reception device further includes a second sequence of training signals included in the radio signal transmitted from the transmission device, and a predetermined second sequence of A second phase difference detection process for detecting a second physical quantity corresponding to a phase transition amount at a time difference T 2 shorter than the time difference T 1 based on a training signal, and
  • the absolute value of a difference between all frequency offsets granted, the frequency to be an integral multiple of the frequency f 2 grant offset, in the second averaging process, the second physical quantity in a range of a natural number times the reciprocal of the frequency f 2 may be averaged.
  • a transmission method is a transmission method using a transmission device that transmits a plurality of radio signals from a plurality of transmission antennas, and generates a predetermined first sequence of training signals.
  • a frequency offset that is an integral multiple of the frequency f 1 for the first training signal sequence generation process and each frequency assigned to the training signal of the first sequence branched to the same number as the plurality of transmission antennas.
  • receiving the radio signal including the training signal of the first sequence having the frequency offset assigned in the first frequency offset granting process through the transmitting antenna. Transmitting to the device.
  • a plurality of radios are provided by assigning a frequency offset that is an integer multiple of the frequency f 1 to each frequency allocated to the branched first sequence training signal.
  • Communicating with a transmitting device that transmits signals from a plurality of transmitting antennas, receiving a plurality of radio signals from the transmitting device by a receiving antenna, and a difference between a carrier frequency transmitted by the transmitting device and a reference receiving frequency used for reception A reception method using a receiving device that estimates a carrier frequency offset as a carrier frequency offset, the receiving method receiving the wireless signal from the transmitting device through the receiving antenna, and the wireless signal transmitted from the transmitting device and training signals of the first series, on the basis of the training signals of the first sequence predetermined for the frequency f 1
  • the radio communication system, transmission apparatus, reception apparatus, radio communication method, transmission method, and reception method of the present invention can estimate a carrier frequency offset with high accuracy with a small number of averaged samples even in a multipath environment.
  • 1 is a block diagram showing a wireless communication system 100 according to a first embodiment of the present invention. It is the graph which compared the estimation error characteristic of the carrier frequency offset in the technique of 1st Embodiment of this invention, and a prior art. It is the graph which compared the estimation error characteristic of the carrier frequency offset in the technique of 1st Embodiment of this invention, and a prior art. It is a flowchart which shows the process of the transmitter 1 by 1st Embodiment of this invention. It is a flowchart which shows the process of the receiver 2 by 1st Embodiment of this invention. It is a block diagram which shows the radio
  • FIG. 1 is a schematic block diagram showing a wireless communication system 100 according to the present embodiment.
  • a radio communication system 100 that estimates a carrier frequency offset using a predetermined sequence of training signals will be described with reference to FIG.
  • the transmission apparatus 1 includes a transmission device 1 and a reception device 2.
  • the transmission apparatus 1 includes a training signal sequence generation unit 11, frequency offset assignment units 12-1 to 12-M, radio units 13-1 to 13-M, and transmission antennas 14-1 to 14-M.
  • M is an integer of 2 or more.
  • the training signal sequence generation unit 11 generates a predetermined sequence of training signals and outputs the training signals to the frequency offset assignment units 12-1 to 12-M.
  • the frequency offset assigning units 12-1 to 12-M add a frequency offset that is an arbitrary integral multiple of an arbitrary frequency f 1 to the training signal generated by the training signal sequence generating unit 11, respectively, and the radio unit 13- Output to 1 to 13-M.
  • the radio units 13-1 to 13-M perform analog conversion and frequency conversion on the training signals generated by the training signal sequence generation unit 11 and given the frequency offset by the frequency offset applying units 12-1 to 12-M, Output as radio signals to the transmitting antennas 14-1 to 14-M.
  • the transmitting antennas 14-1 to 14-M transmit radio signals output from the connected radio units 13-1 to 13-M to the receiving device 2.
  • the training signal sequence generation unit 11 has an output terminal connected to an input terminal of each of the frequency offset assignment units 12-1 to 12-M.
  • the training signal sequence generation unit 11 branches the generated training signal and outputs the branched training signals to the frequency offset addition units 12-1 to 12-M.
  • the frequency offset assignment units 12-1 to 12-M have an input terminal connected to the output terminal of the training signal sequence generation unit 11, and an output terminal connected to the input terminals of the radio units 13-1 to 13-M on a one-to-one basis. Has been.
  • the frequency offset assigning units 12-1 to 12-M add frequency offsets to the input training signals, and output them to the radio units 13-1 to 13-M.
  • the radio units 13-1 to 13-M are connected to the output terminals of the frequency offset applying units 12-1 to 12-M on a one-to-one basis, and the output terminals are input terminals of the transmission antennas 14-1 to 14-M. Are connected one to one.
  • the radio units 13-1 to 13-M convert training signals, which are input signals and given frequency offsets, respectively, generate radio signals, and transmit the signals via the transmission antennas 14-1 to 14-M.
  • the wireless signal is transmitted to the receiving device 2.
  • the receiving device 2 includes a receiving antenna 21, a radio unit 22, a phase difference detecting unit 23, an averaging unit 24, and a frequency estimating unit 25.
  • the reception antenna 21 receives the radio signal transmitted from the transmission device 1 and outputs it to the radio unit 22.
  • the radio unit 22 performs frequency conversion and digital conversion on the radio signal received by the reception antenna 21, generates a reception signal, and outputs the received signal to the phase difference detection unit 23.
  • the phase difference detection unit 23 compares the reception signal generated by the radio unit 22 with a predetermined series of training signals. Then, the phase difference detection unit 23 detects a physical quantity indicated by a function of the phase transition amount at a time difference T 1 that is an arbitrary natural number times the time represented by the reciprocal of the frequency f 1 , and outputs the detected physical quantity to the averaging unit 24. .
  • the averaging unit 24 averages the physical quantity output from the phase difference detection unit 23 in order to avoid the influence of noise, and outputs the averaged physical quantity to the frequency estimation unit 25.
  • the frequency estimation unit 25 estimates the carrier frequency offset based on the averaged physical quantity averaged by the averaging unit 24.
  • the output terminal of the receiving antenna 21 is connected to the input terminal of the wireless unit 22.
  • the receiving antenna 21 outputs the received radio signal to the radio unit 22.
  • the radio unit 22 has an input terminal connected to the output terminal of the receiving antenna 21, and an output terminal connected to the input terminal of the phase difference detection unit 23.
  • the radio unit 22 outputs a reception signal generated from the radio signal received by the reception antenna 21 to the phase difference detection unit 23.
  • the phase difference detection unit 23 has an input terminal connected to the output terminal of the radio unit 22 and an output terminal connected to the averaging unit 24.
  • the phase difference detection unit 23 extracts a training signal portion included in the received signal input from the radio unit 22, and averages a physical quantity indicated by a function of a phase transition amount obtained by comparison with a predetermined series of training signals.
  • the averaging unit 24 has an input terminal connected to the output terminal of the phase difference detection unit 23, and an output terminal connected to the frequency estimation unit 25.
  • the averaging unit 24 outputs the averaged physical quantity obtained by performing the averaging process on the physical quantity input from the phase difference detecting unit 23 to the frequency estimating unit 25.
  • the frequency estimation unit 25 has an input terminal connected to the output terminal of the averaging unit 24.
  • the frequency estimation unit 25 estimates the carrier frequency offset based on the input averaged physical quantity and outputs the result.
  • n is a sample number.
  • s 1 (n) be the training signal generated by the training signal sequence generation unit 11.
  • the first training signal x 1m (n) given the frequency offset by the frequency offset assigning unit 12-m can be expressed by Expression (13) when the frequency offset is given at equal intervals.
  • m represents a natural number from 1 to M.
  • f s is the sampling frequency.
  • the frequency f 1 when the frequency offset is applied at equal intervals needs to satisfy the relationship of Expression (14). .
  • the received signal y 1 produced by the result (n) can be represented by the formula (15).
  • h m is a complex amplitude response between the transmitting antenna 14-m (m is a natural number from 1 to M) and the receiving antenna 21.
  • ⁇ f is a carrier frequency offset between the transmission device 1 and the reception device 2.
  • f s is a sampling frequency.
  • ⁇ 1 (n) indicates noise that is uncorrelated for each sample and follows a complex Gaussian distribution with an average power amount of 1.
  • Expression (15) is an expression in which the phase amplitude response h in Expression (1) is replaced with a variable ⁇ 1 (n) that varies with time.
  • ⁇ 1 (n) can be considered as a variable corresponding to the phase amplitude response, and can be represented by Expression (16).
  • the phase difference detection unit 23, the averaging unit 24, and the frequency estimation unit 25 receive and generate the received signal y 1 (n) and the training signal s 1 (preliminary training signal generated by the training signal sequence generation unit 11). n) is used to estimate the carrier frequency offset ⁇ f.
  • the physical quantity z 1 (n) which is a function of the phase transition amount in the time difference ⁇ 1 sample, can be expressed by Expression (17).
  • ⁇ 1 (n) is represented by formula (18).
  • the conversion physical quantity ⁇ 1 can be expressed by Expression (20).
  • the frequency estimation unit 25 calculates an estimated value f est of the carrier frequency offset.
  • a calculation formula for obtaining the estimated value f est of the carrier frequency offset is shown in Formula (22).
  • Noise ⁇ 1 (n) for each sample and stochastically uncorrelated follow a complex Gaussian distribution. Therefore, using the properties of the Gaussian distribution and Equation (22), the average physical quantity ⁇ 1 when the number of samples N 1 in Equation (20) is larger than the value of the time difference ⁇ 1 sample (N 1 > ⁇ 1 ) is , Can be expressed as equation (25).
  • a property of the Gaussian distribution there is a property that when two independent variables according to the Gaussian distribution are linearly calculated, a Gaussian distribution having a variance obtained by linearly calculating the variance of both variables can be approximated.
  • the average physical quantity ⁇ 1 when the number of samples N 1 in Expression (21) is equal to or less than the value of the time difference ⁇ 1 sample (N 1 ⁇ ⁇ 1 ) can be expressed as Expression (26).
  • Noises ⁇ r and ⁇ i are variables that follow a Gaussian distribution with a variance of 1.
  • Equation (26) the case where the sum of the received signal power used for estimating the carrier frequency offset is sufficiently higher than the noise power, that is, the case represented by Equation (27) will be described.
  • the estimated value f est of the carrier frequency offset calculated by the frequency estimation unit 25 is calculated when the number of samples N 1 is larger than the value of the time difference ⁇ 1 sample (N 1 > ⁇ 1 ). It can be approximated by (28). Note that when ⁇ takes a value sufficiently smaller than 1 ( ⁇ ⁇ 1), a relationship of tan ⁇ is used.
  • ⁇ ⁇ is a variable that follows a Gaussian distribution with a variance of 1. Note that the pull-in range in which the carrier frequency offset can be estimated can be defined by, for example, Expression (30).
  • Expression (28) and (29) represent
  • the expression is replaced by
  • the reception level drops with a certain probability.
  • the probability that the reception level from all transmission antennas will be low is low. Therefore, the probability that ⁇
  • the method for estimating the carrier frequency offset in the first embodiment of the present invention reduces the estimation error with the same training signal length and the same transmission power as compared with the conventional method of estimating the carrier frequency offset in a multipath fading environment. it can. Further, the estimated value can be obtained with the same estimation error with a shorter training signal length or lower transmission power.
  • FIG. 2 and FIG. 3 show a comparison of carrier frequency offset estimation error characteristics between the technology of the first embodiment of the present invention and the conventional technology.
  • the estimation error behaves stochastically, it was evaluated by RMS (Root Mean Square).
  • the modulation speed was 9600baud, and the interval of phase difference detection was 8 symbols.
  • the number of transmission antennas is two.
  • independent single-wave Rayleigh fading is assumed for each antenna as a propagation path.
  • the horizontal axis indicates CNR [dB].
  • the vertical axis indicates the carrier frequency offset estimation error [Hz].
  • a curve g11 indicates the characteristics when the technique of the first embodiment is used.
  • a curve g12 shows the characteristics when the conventional technique is used.
  • the CNR is fixed at 10 dB, the training signal length is changed, and the estimation error characteristic is evaluated. Comparing the required training signal length at which the estimation error is 10 Hz, the conventional technique required about 10,000 symbols, whereas the first embodiment uses about 30 symbols.
  • the carrier frequency offset estimation error is 10 [Hz]
  • the training signal length can be reduced to about 1/300 compared to the conventional technique by using the technique of the first embodiment.
  • the horizontal axis indicates the training signal length [symbol].
  • the vertical axis indicates the carrier frequency offset estimation error [Hz].
  • a curve g13 shows the characteristics when the technique of the first embodiment is used.
  • a curve g14 shows the characteristics when the conventional technique is used.
  • the estimation error characteristic was evaluated by fixing the training signal length to 54 symbols and changing the CNR. Comparing the required CNR with an estimation error of 10 [Hz], the conventional technique required about 23 dB, whereas the first embodiment uses about 8 dB. That is, when the carrier frequency offset estimation error is 10 [Hz], the transmission power can be reduced to about 1/30 compared to the conventional technique by using the technique of the first embodiment.
  • two or more of the plurality of frequency offset assigning units 12-1 to 12-M may assign the same frequency offset. Even in such a case, the system of the present embodiment can operate normally. However, when all the frequency offset assigning units 12-1 to 12-M assign the same frequency, only the same effect as the conventional one can be obtained. Therefore, it is desirable that the frequency offset assigning units 12-1 to 12-M assign two or more frequency offsets.
  • the received signal y 1 (n) is less affected by noise as the absolute value of the variable ⁇ 1 (n) is larger. Therefore, the phase difference detection unit 23 can detect the phase difference with higher accuracy as the absolute value of the variable ⁇ 1 (n) is larger. Further, the variable ⁇ 1 (n) varies due to the frequency offset imparted by the frequency offset imparting units 12-1 to 12-M, and the variation pattern is not uniquely determined. For this reason, when an inappropriate averaging sample number N 1 is set in the averaging unit 24, only the phase difference detected from the received signal having a small absolute value of the variable ⁇ 1 (n) is averaged. Therefore, there may not be obtained accuracy of estimating the carrier frequency offset corresponding to the averaging sample number N 1 in the frequency estimation unit 25.
  • the frequency offset giving unit 12-1 ⁇ 12-M when applying the frequency offset to be an integral multiple of the frequency f 1, the variable beta 1 of variation cycle always f s / f 1 samples (n) cycle It becomes. Accordingly, the averaging unit 24 averages the physical quantity z 1 (n) for N 1 samples, which is an arbitrary natural number multiple of f s / f 1 sample, which is one cycle of the variable ⁇ 1 (n). The physical quantity with high accuracy is always included and averaged.
  • the frequency estimation unit 25 can obtain the accuracy of estimating the carrier frequency offset corresponding to the averaging sample number N 1.
  • delay detection type phase difference detection is used in the phase difference detection unit 23
  • the magnitude of the physical quantity z 1 (n) indicates the square of the absolute value, that is, the probability of the detected phase difference. Therefore, by using the delay detection type phase difference detection in the phase difference detection unit 23, the averaging unit 24 automatically performs appropriate averaging according to the detection accuracy of the phase difference. Therefore, the carrier frequency offset can be estimated with high accuracy in the frequency estimation unit 25.
  • Frequency offset supply portion 12-1 ⁇ 12-M all the frequency offset to be applied may be given a frequency offset to be any integer multiple of the arbitrary frequency f 1.
  • phase difference detection unit 23 may use any phase difference detection unit that detects a physical quantity that is a function of the phase transition amount in the time difference ⁇ 1 sample.
  • phase difference detection means for detecting the phase difference itself by subtracting the phase transition amount in the time difference of the training signal from the phase transition amount in the time difference ⁇ 1 sample of the received signal in the portion where the training signal exists is used. May be.
  • averaging unit 24 averages the physical quantity z 1 (n) for N 1 samples that is an arbitrary natural number multiple of the delay sample number ⁇ 1 .
  • the present invention is not limited thereto. Is not to be done.
  • Averaging sample number N 1 can be any value.
  • a band filter may be provided in the previous stage of the phase difference detection unit 23.
  • FIG. 4 is a flowchart showing processing of the transmission device 1 according to the first embodiment of the present invention.
  • the training signal sequence generation unit 11 generates a training signal predetermined by the transmission device 1 (step S11).
  • the frequency offset giving unit 12-1 ⁇ 12-M is for each frequency allocated to the number of branched training signals into the same number of a plurality of transmitting antennas 14-1 ⁇ 14-M, the frequency f 1 A frequency offset that is an integral multiple is applied (step S12).
  • the radio units 13-1 to 13-M transmit radio signals including a training signal having the frequency offset assigned by the frequency offset assigning units 12-1 to 12-M to the transmission antennas 14-1 to 14-M.
  • the data is transmitted to the receiving device 2 (step S13).
  • FIG. 5 is a flowchart showing processing of the receiving device 2 according to the first embodiment of the present invention.
  • the radio unit 22 receives a radio signal from the transmission device 1 through the reception antenna 21 (step S21).
  • the phase difference detection unit 23 is represented by the reciprocal of the frequency f 1 based on the training signal included in the radio signal transmitted from the transmission device 1 and the training signal predetermined by the reception device 2. detecting a physical quantity corresponding to the phase shift amount in the natural number times the time difference T 1 of the time (step S22).
  • the averaging unit 24 calculates the averaged physical quantity by averaging the physical quantities detected in Step S22 (Step S23).
  • the frequency estimation unit 25 estimates a carrier frequency offset based on the averaged physical quantity (step S24).
  • FIG. 6 is a schematic block diagram showing the wireless communication system 200 according to the present embodiment.
  • FIG. 7 is a diagram illustrating an example of a transmission signal format in the wireless communication system 200.
  • a wireless communication system 200 illustrated in FIG. 6 includes a transmission device 3 and a reception device 4.
  • the transmission apparatus 3 includes a first training signal sequence generation unit 31, first frequency offset addition units 32-1 to 32-M, a second training signal sequence generation unit 33, and a second frequency offset addition unit 34-1.
  • 34-M radio units 35-1 to 35-M, and transmission antennas 36-1 to 36-M.
  • M is an integer of 2 or more.
  • the first training signal sequence generation unit 31 generates a predetermined first sequence of training signals and outputs the training signal to the first frequency offset assignment units 32-1 to 32-M.
  • the first frequency offset assigning units 32-1 to 32-M have an arbitrary integer multiple of an arbitrary frequency f 1 in the first sequence of training signals generated by the first training signal sequence generating unit 31. Each frequency offset is assigned and output to the radio units 35-1 to 35-M.
  • the second training signal sequence generation unit 33 generates a predetermined second sequence of training signals and outputs the training signals to the second frequency offset assignment units 34-1 to 34-M.
  • the second frequency offset assigning units 34-1 to 34-M add the absolute values of all frequency offsets to the time difference T 1 to the second sequence training signal generated by the second training signal sequence generating unit 33.
  • a frequency offset smaller than half of the reciprocal value is assigned and output to the radio units 35-1 to 35-M.
  • the radio units 35-1 to 35-M are trained in the first sequence generated by the first training signal sequence generating unit 31 and having the frequency offset added by the first frequency offset adding units 32-1 to 32-M.
  • the signal and the second series of training signals generated by the second training signal sequence generation unit 33 and provided with the frequency offset by the second frequency offset applying units 34-1 to 34-M are time-division multiplexed. After that, analog conversion and frequency conversion are performed and output to the transmission antennas 36-1 to 36-M.
  • the transmitting antennas 36-1 to 36-M transmit the radio signals output from the radio units 35-1 to 35-M to the receiving device 4. For example, as in the transmission signal format shown in FIG.
  • the first sequence training signal 50 and the second sequence training signal 60 have a data portion 70 so that the signals do not overlap each other in time. Is sent continuously before sending.
  • the horizontal axis indicates the time axis.
  • the transmission signal format shown in FIG. 7 shows a signal format transmitted in the order of the first series of training signals 50, the second series of training signals 60, and the information of the data unit 70.
  • the first training signal sequence generation unit 31 has an output terminal connected to an input terminal of each of the first frequency offset applying units 32-1 to 32-M.
  • the first training signal sequence generation unit 31 branches the generated first sequence training signals and outputs the branched training signals to the first frequency offset assignment units 32-1 to 32-M.
  • the first frequency offset assigning units 32-1 to 32-M have their input terminals connected to the output terminals of the first training signal sequence generation unit 31, and their output terminals as the first of the radio units 33-1 to 33-M. Are connected to the input terminals in a one-to-one relationship.
  • the first frequency offset assigning units 32-1 to 32-M assign frequency offsets to the input first series of training signals, and output them to the radio units 35-1 to 35-M.
  • the output terminal of the second training signal sequence generation unit 33 is connected to the input terminals of the second frequency offset assignment units 34-1 to 34-M.
  • the second training signal sequence generation unit 33 branches the generated second sequence of training signals and outputs the branched training signals to the second frequency offset assignment units 34-1 to 34-M.
  • the second frequency offset assignment units 34-1 to 34-M have input terminals connected to the output terminals of the second training signal sequence generation unit 33, and output terminals connected to the second units of the radio units 35-1 to 35-M. Are connected to the input terminals in a one-to-one relationship.
  • the second frequency offset assigning units 34-1 to 34-M add frequency offsets to the input second series of training signals, respectively, and output them to the radio units 35-1 to 35-M.
  • the first input terminals are connected to the output terminals of the frequency offset applying units 32-1 to 32-M, and the second input terminals are frequency offset applying units 34-1 to 34. -Connected to the output terminal of M.
  • the radio units 35-1 to 35-M have output terminals connected one-to-one to the input terminals of the transmission antennas 36-1 to 36-M.
  • the radio units 35-1 to 35-M convert the input training signals to which the respective frequency offsets are added, generate radio signals, and receive the radio signals via the transmission antennas 36-1 to 36-M. Transmit to device 4.
  • the reception device 4 includes a reception antenna 41, a radio unit 42, a first phase difference detection unit 43, a first averaging unit 44, a second phase difference detection unit 45, a second averaging unit 46, and a frequency estimation unit. 47 is provided.
  • the reception antenna 41 receives the radio signal transmitted from the transmission device 3 and outputs it to the radio unit 42.
  • the radio unit 42 performs frequency conversion and digital conversion on the radio signal received by the reception antenna 41, generates a reception signal, and outputs the received signal to the first phase difference detection unit 43 and the second phase difference detection unit 45.
  • the first phase difference detection unit 43 compares the received signal input from the radio unit 42, a training signal of the first series are predetermined, which is a function of phase shift amounts in a time difference T 1 second 1 physical quantity is detected and output to the first averaging unit 44.
  • the first averaging unit 44 averages the input first physical quantity and outputs the first averaged physical quantity to the frequency estimation unit 47 in order to avoid the influence of noise.
  • the second phase difference detection unit 45 compares the received signal input from the radio unit 42 with a predetermined second series of training signals, and the phase transition amount at the time difference T 2 shorter than the time difference T 1. Is detected and output to the second averaging unit 46.
  • the second averaging unit 46 averages the input second physical quantity and outputs the second averaged physical quantity to the frequency estimation unit 47 in order to avoid the influence of noise.
  • the frequency estimation unit 47 calculates a carrier frequency offset from the first averaged physical quantity averaged by the first averaging unit 44 and the second averaged physical quantity averaged by the second averaging unit 46. presume.
  • the receiving antenna 41 has an output terminal connected to an input terminal of the wireless unit 42.
  • the receiving antenna 41 outputs the received radio signal to the radio unit 42.
  • the radio unit 42 has an input terminal connected to the output terminal of the receiving antenna 41, and an output terminal connected to the input terminal of the first phase difference detection unit 43 and the input terminal of the second phase difference detection unit 45.
  • the radio unit 42 outputs a reception signal generated from the radio signal received by the reception antenna 21 to the first phase difference detection unit 43 and the first phase difference detection unit 45.
  • the first phase difference detection unit 43 has an input terminal connected to the output terminal of the radio unit 42 and an output terminal connected to the first averaging unit 44.
  • the first phase difference detection unit 43 extracts a part of the first series of training signals included in the reception signal input from the radio unit 42 and compares it with a predetermined first series of training signals.
  • the physical quantity indicated by the function of the phase transition amount obtained in this way is output to the first averaging unit 44.
  • the first averaging unit 44 has an input terminal connected to the output terminal of the first phase difference detection unit 43, and an output terminal connected to the first input terminal of the frequency estimation unit 47.
  • the first averaging unit 44 outputs the averaged physical quantity obtained by performing the averaging process on the physical quantity input from the first phase difference detecting unit 43 to the frequency estimating unit 47.
  • the second phase difference detection unit 45 has an input terminal connected to the output terminal of the radio unit 42 and an output terminal connected to the second averaging unit 46.
  • the second phase difference detection unit 45 extracts a part of the second series of training signals included in the reception signal input from the radio unit 42, and compares it with a predetermined second series of training signals.
  • the physical quantity indicated by the function of the phase transition amount obtained in this way is output to the second averaging unit 46.
  • the second averaging unit 46 has an input terminal connected to the output terminal of the second phase difference detection unit 45, and an output terminal connected to the second input terminal of the frequency estimation unit 47.
  • the second averaging unit 46 outputs the averaged physical quantity obtained by performing the averaging process on the physical quantity input from the second phase difference detecting unit 45 to the frequency estimating unit 47.
  • the frequency estimation unit 47 has a first input terminal connected to the output terminal of the first averaging unit 44 and a second input terminal connected to the output terminal of the second averaging unit 46.
  • the frequency estimation unit 47 estimates the carrier frequency offset based on the input averaged physical quantity and outputs the result.
  • the second training signal sequence generation unit 33 and the generated second training signal sequence are included in the transmission device 3.
  • the receiving device 4 also includes a second phase difference detection unit 45 that detects the second phase transition amount with a small number of delay samples using the second series of training signals, and the detected second phase transition.
  • a second averaging unit 46 that averages the quantities is further provided.
  • the first training signal sequence generation unit 31 performs the same operation as the training signal sequence generation unit 11.
  • the first frequency offset assigning units 32-1 to 32-M perform the same operation as the frequency offset assigning units 12-1 to 12-M.
  • the first phase difference detection unit 43 performs the same operation as the phase difference detection unit 23.
  • the first averaging unit 44 performs the same operation as the averaging unit 24. Therefore, in the second embodiment, the first average physical quantity ⁇ 1 represented by the formula (20), the formula (21), the formula (25), and the formula (26) shown in the first embodiment is obtained.
  • n be the sample number.
  • the second series of training signals generated by the second training signal series generation unit 33 is s 2 (n).
  • the second training signal x 2m (n) given the frequency offset by the frequency offset assigning unit 34-m has the frequency offset so that the given frequency offset is arranged at equal intervals at the interval indicated by the frequency f 2.
  • m represents a natural number from 1 to M.
  • f s is the sampling frequency.
  • the reception signal y 2 (n) received by the reception antenna 41 and subjected to frequency conversion and digital conversion by the radio unit 42 and generated as a result thereof can be expressed by Expression (32).
  • h m is a complex amplitude response between the transmitting antenna 36-m (m is a natural number from 1 to M) and the receiving antenna 41.
  • ⁇ f is a carrier frequency offset between the transmission device 3 and the reception device 4.
  • f s is a sampling frequency.
  • ⁇ 2 (n) is noise that is uncorrelated for each sample and follows a complex Gaussian distribution with an average power of 1.
  • Expression (32) is an expression in which the phase amplitude response h in Expression (1) is replaced with a variable ⁇ 2 (n) that varies with time.
  • ⁇ 2 (n) can be considered as a variable corresponding to the phase amplitude response, and can be expressed as Equation (33).
  • the second phase difference detection unit 45, the second averaging unit 46, and the frequency estimation unit 47 calculate a carrier frequency offset rough estimation value f ′ est . Thereafter, the first phase difference detection unit 43, the first averaging unit 44, and the frequency estimation unit 47 further estimate the carrier frequency offset remaining after removing the influence of the rough carrier frequency offset estimation value f ′ est .
  • the second phase difference detection unit 45, the second averaging unit 46, and the frequency estimation unit 47 include a reception signal y 2 (n) generated by receiving a radio signal and a predetermined second training signal sequence Using the second series of training signals s 2 (n) generated by the generation unit 33, a rough carrier frequency offset estimated value f ′ est is calculated. Thereafter, the frequency estimation unit 47 uses the obtained carrier frequency offset rough estimation value f ′ est and the first averaged physical quantity ⁇ 1 to calculate the carrier frequency offset estimation value f est based on Expression (34). obtain.
  • variable ⁇ ′ 1 is an average of the physical quantities of the phase transition amount in the time difference ⁇ 1 sample remaining after correcting the phase transition amount corresponding to the rough estimated carrier frequency offset value f ′ est . That is, the variable ⁇ ′ 1 can be expressed by Expression (35).
  • the rough estimated carrier frequency offset value f ′ est causes an error due to the influence of the frequency offset given to the second series of training signals and the influence of noise ⁇ 2 (n).
  • the influence of the noise ⁇ 2 (n) is ignored, and an estimation error due only to the influence of the frequency offset is considered.
  • the second averaging unit 46 averages the second physical quantity z 2 (n) for N 2 samples, which is an arbitrary natural number multiple of f s / f 2 samples, which is one cycle of the variable ⁇ 2 (n). And the second average physical quantity ⁇ 2 is calculated.
  • Second averaging physical quantity phi 2 may be represented by the formula (37).
  • the frequency estimation unit 47 calculates a carrier frequency offset rough estimation value f ′ est based on the equation (38).
  • the pull-in range of the rough estimated carrier frequency offset value f ′ est represented by Expression (39) is the pull-in range of the carrier frequency offset estimating unit 25 in the first embodiment represented by Expression (30). To make it wider than the range, ⁇ 2 > ⁇ 1 is set.
  • the number of antennas M is large. However, a small value can be used for the delay sample number ⁇ 2 . Therefore, the pull-in range shown in Expression (39) can be sufficiently expanded.
  • the carrier frequency offset estimation accuracy in the second embodiment of the present invention is the same as in the first embodiment. That is, even when the second embodiment is used, the same effect as that of the first embodiment described with reference to FIGS. 2 and 3 can be obtained.
  • two or more of the plurality of second frequency offset assigning units 34-1 to 34-M may assign the same frequency offset. Even in that case, the system of this embodiment can operate normally. However, if all the second frequency offset assigning units 34-1 to 34-M assign the same frequency, only the same effect as that of the first embodiment can be obtained. Therefore, it is desirable that the second frequency offset assigning units 34-1 to 34-M assign two or more frequency offsets.
  • equation (34), the equation (36), the estimation error of f 'est if the reception level h M is sufficiently larger than the other reception levels h 1 ⁇ h M-1 is maximum.
  • the estimation error at that time is M ⁇ f 2 . That is, the absolute value of the frequency offset given by the second frequency offset assigning units 34-1 to 34-M is the maximum value. Therefore, all the frequency offsets assigned by the second frequency offset assigning units 34-1 to 34-M are included in the pull-in range of the carrier frequency offset estimation using the first average physical quantity ⁇ 1 in the first embodiment.
  • a frequency offset is added so as to fit. That is, the frequency offset is applied so that the absolute values of all the applied frequency offsets are smaller than f s / 2 ⁇ 1 . Thereby, it is possible to achieve both a wide pull-in range and high estimation accuracy.
  • the frequency estimation unit 47 can improve the accuracy of estimating the carrier frequency offset corresponding to the averaging sample number N 2.
  • the phase component of the physical quantity z 2 (n) indicates the detected phase difference.
  • the amplitude component indicates the square of the absolute value of the variable ⁇ 2 (n), that is, the probability of the detected phase difference. Therefore, by using the delay detection type phase difference detection in the second phase difference detection unit 45, the second averaging unit 46 automatically performs appropriate averaging according to the detection accuracy of the phase difference. . Therefore, the frequency estimation unit 47 can estimate the carrier frequency offset with high accuracy.
  • the second phase difference detection unit 45 may use any means for detecting a second physical quantity that is a function of the phase transition amount in the time difference ⁇ 2 samples.
  • the phase difference itself is obtained by subtracting the phase transition amount in the time difference of the second series of training signals from the phase transition amount in the time difference ⁇ 2 samples of the received signal in the portion where the second series of training signals exists.
  • Phase difference detecting means for obtaining the above may be used. When such a phase difference detection means is used, the calculation for the phase difference detection is only addition / subtraction, so that the circuit configuration can be simplified.
  • the second averaging unit 46 uses the second physical quantity z 2 (N 2 samples corresponding to an arbitrary natural number multiple of f s / f 2 samples, which is one cycle of the variable ⁇ 2 (n). Although the case where n) is averaged was demonstrated, it is not limited to this. Averaging sample number N 2 may be any value.
  • a band limiting filter may be provided before the first phase difference detection unit 43 and the second phase difference detection unit 45.
  • the first series of training signals 50 and the second series of training signals 60 are transmitted before the data unit 70 is transmitted so that the signals do not overlap with each other in time.
  • the case of continuous transmission has been described, but the present invention is not limited to this.
  • the first series of training signals 50 and the second series of training signals 60 may be assigned at any time as long as the signals do not overlap in time.
  • the first series of training signals 50 and the second series of training signals 60 are time-division multiplexed has been described, but the present invention is not limited to this.
  • the first series of training signals 50 and the second series of training signals 60 may be multiplexed using frequency division multiplexing, code division multiplexing, or the like.
  • FIG. 8 is a flowchart showing processing of the transmission device 3 according to the second embodiment of the present invention.
  • the first training signal sequence generation unit 31 generates a first sequence of training signals predetermined by the transmission device 3 (step S31).
  • the second training signal sequence generation unit 33 generates a second sequence of training signals predetermined by the transmission device 3 (step S32).
  • the first frequency offset assigning units 32-1 to 32-M correspond to the frequencies assigned to the first series of training signals branched in the same number as the number of the plurality of transmission antennas 36-1 to 36-M.
  • a frequency offset that is an integral multiple of the frequency f 1 is applied (step S33).
  • the second frequency offset assigning units 34-1 to 34-M assign the respective frequencies assigned to the second series of training signals branched in the same number as the plurality of transmission antennas 36-1 to 36-M. against imparts frequency offset absolute value is less than half the value of the reciprocal of the time difference T 1 of the all frequency offset (step S34).
  • the radio units 35-1 to 35-M include the first series of training signals having the frequency offset assigned by the first frequency offset assigning units 32-1 to 32-M and the second frequency offset.
  • the second series of training signals having frequency offsets assigned by the assigning units 34-1 to 34-M are time-division multiplexed and transmitted as radio signals to the receiving apparatus 4 through the transmitting antennas 36-1 to 36-M. Transmit (step S35).
  • step S35 Transmit
  • step S31 may be performed after the process of step S32, and the process of step S33 may be performed after the process of step S34.
  • the process of step S31 and the process of step S32 may be performed simultaneously, and the process of step S33 and the process of step S34 may be performed simultaneously.
  • FIG. 9 is a flowchart showing processing of the receiving device 4 according to the second embodiment of the present invention.
  • the radio unit 42 receives a radio signal from the transmission device 3 through the reception antenna 41 (step S41).
  • the first phase difference detection unit 43 includes a first series of training signals included in the radio signal transmitted from the transmission apparatus 3, and a first series of training signals predetermined by the reception apparatus 4.
  • the second phase difference detection unit 45 includes a second series of training signals included in the radio signal transmitted from the transmission apparatus 3, and a second series of training signals predetermined by the reception apparatus 4. based on, for detecting a second physical quantity corresponding to the phase transition amount in a short time difference T 2 than the time difference T 1 (step S43).
  • the first averaging unit 44 calculates the first average physical quantity by averaging the first physical quantity detected in step S42 (step S44).
  • the second averaging unit 46 calculates the second average physical quantity by averaging the second physical quantity detected in Step S43 (Step S45). Specifically, the second averaging unit 46 averages a range of natural number times the reciprocal of the frequency f 2 of the second physical quantity.
  • the frequency estimation unit 47 estimates a carrier frequency offset based on the first averaged physical quantity calculated in step S44 and the second averaged physical quantity calculated in step S45 (step S46).
  • step S42 may be performed after step S43
  • step S44 may be performed after step S45
  • the process of step S42 and the process of step S43 may be performed simultaneously
  • the process of step S44 and the process of step S45 may be performed simultaneously.
  • FIG. 10 is a schematic block diagram showing a receiving device 7 according to the third embodiment of the present invention.
  • the transmitting device that communicates with the receiving device 7 is the same as the transmitting device 1 (FIG. 1) in the first embodiment, and the components, the connection of the components, and the signal flow are the same as in the first embodiment.
  • the reception device 7 includes reception antennas 71-1 to 71-L 1 , radio units 72-1 to 72-L 2 , phase difference detection units 73-1 to 73-L 3 , and averaging units 74-1 to 74-L. 4.
  • Frequency estimators 75-1 to 75-L 5 and signal selectors / synthesizers 76-1 to 76-5 are provided.
  • Receiving antennas 71-1 to 71-L 1 receive the radio signal transmitted from transmitting apparatus 1 and output it to signal selecting / combining section 76-1.
  • Signal selection and combining unit 76-1 in order to avoid the influence of noise by the reception diversity effect, select or synthesize radio signals received by the receiving antennas 71-1 ⁇ 71-L 1, radio units 72-1 to 72 and outputs to -L 2.
  • the radio units 72-1 to 72-L 2 perform frequency conversion and digital conversion on the radio signal output from the signal selection / synthesis unit 76-1, generate a reception signal, and generate a signal selection / synthesis unit 76-2. Output to.
  • the signal selection / combination unit 76-2 selects or synthesizes the reception signals generated by the radio units 72-1 to 72-L 2 in order to avoid the influence of noise by the reception diversity effect, and the phase difference detection unit 73- and outputs it to the 1 ⁇ 73-L 3.
  • Phase difference detecting unit 73-1 ⁇ 73-L 3 compares the received signal generated by the signal selection and combining unit 76-1, and a training signal sequence is predetermined, the reciprocal of the frequency f 1 A physical quantity indicated by a function of the phase transition amount at a time difference T 1 that is an arbitrary natural number times the represented time is detected and output to the signal selection / synthesis unit 76-3.
  • the signal selection / combination unit 76-3 selects or combines the physical quantities output from the phase difference detection units 73-1 to 73-L 3 to avoid the influence of noise due to the reception diversity effect, and averages 74-1. and outputs it to the ⁇ 74-L 4.
  • the averaging units 74-1 to 74-L 4 average the physical quantities output from the signal selection / synthesis unit 76-3 to avoid the influence of noise, and the averaged physical quantities are sent to the signal selection / synthesis unit 76-4. Output.
  • Signal selection and combining unit 76-4 in order to avoid the influence of noise by the reception diversity effect, select or synthesize averaging physical amounts output from the averaging 74-1 ⁇ 74-L 4, the frequency estimation unit 75- and outputs it to the 1 ⁇ 75-L 5.
  • the frequency estimation units 75-1 to 75-L 5 estimate the carrier frequency offset based on the averaged physical quantity output from the signal selection / synthesis unit 76-4, and output the carrier frequency offset to the signal selection / synthesis unit 76-5. .
  • Signal selection and combining unit 76-5 in order to avoid the influence of noise by the reception diversity effect, selecting or combining the carrier frequency offset estimated by the frequency estimation unit 75-1 ⁇ 75-L 5.
  • the signal selection / combination unit 76. -1 when the number of reception antennas L 1 is 1, or when the number of reception antennas L 1 and the number of radio units L 2 are the same, the signal selection / combination unit 76. -1 can be omitted.
  • the number L 2 of the radio unit if it is 1, or, if the number L 3 having L 2 and the phase difference detecting unit of the wireless unit is equal, the signal selection and combining unit 76-2 Can be omitted.
  • the number L 3 of the phase difference detecting section when it is 1, or, if the number L 4 of the averaging unit and the number L 3 of the phase difference detecting unit is equal, the signal selection and combining unit 76 -3 can be omitted.
  • the signal selection / synthesis unit 76-4 Can be omitted.
  • the number L 5 of the frequency estimation unit if it is 1, it is possible to omit the signal selection and combining unit 76-5.
  • the signal selectors 76-1 to 76-5 select and output three high-level signals from the five input signals, divide the six input signals into two, and synthesize each To output three signals.
  • a plurality of receiving antennas are provided as compared with the first embodiment. Also includes a signal selection and combining unit 76-1 for selecting or combining a plurality of radio signals received by a plurality of receiving antennas 71-1 ⁇ 71-L 1. Further, a signal selecting / synthesizing unit 76-2 for selecting or synthesizing a plurality of received signals generated from radio signals is provided.
  • a signal selection / synthesis unit 76-3 for selecting or synthesizing a plurality of physical quantities indicated by a function of the phase transition amount calculated from the received signal is provided. Further, a signal selecting / synthesizing unit 76-4 for selecting or synthesizing a plurality of averaged physical quantities obtained by averaging the physical quantities indicated by the phase transition amount function is provided. Further, a signal selection / synthesis unit 76-5 for selecting or combining a plurality of carrier frequency offsets estimated from the averaged physical quantity is provided. As a result, the carrier frequency offset can be estimated with higher accuracy by the reception diversity effect.
  • the operation principle of the carrier frequency offset estimation system in the third embodiment of the present invention will be described using mathematical expressions.
  • the number of reception antennas L 1 , the number of radio units L 2 , the number of phase difference detection units L 3 , and the number of averaging units L 4 are L, respectively.
  • a case where the number L 5 is 1 will be described.
  • a configuration in which the signal selection / combination units 76-1, 76-2, 76-3, and 76-5 are omitted will be described.
  • the receiving device 7a having such a configuration will be described with reference to FIG.
  • FIG. 11 is a schematic block diagram showing the receiving device 7a.
  • the case where the signal selecting / combining unit 76-4 performs simple combining using the averaging physical quantity ⁇ 1l calculated by the averaging unit 74-1 (l is a natural number from 1 to L) as the weighting factor 1 will be described.
  • the receiving antennas 71-1 to 71-L perform the same operation as the receiving antenna 21, respectively.
  • the radio units 72-1 to 72-L perform the same operation as the radio unit 22, respectively.
  • the phase difference detection units 73-1 to 73-L operate in the same manner as the phase difference detection unit 23.
  • the averaging units 74-1 to 74-L each perform the same operation as the averaging unit 24. Therefore, the average physical quantity ⁇ 1l calculated by the averaging unit 74-1 (l is a natural number from 1 to L) is expressed by the equations (40) and (41) as in the equations (25) and (26). Can be shown as
  • h ml represents a transmission antenna 14-m (m represents a natural number from 1 to M) and a reception antenna 71-l (l represents a natural number from 1 to L).
  • the signal selection / synthesizing unit 76-4 simply synthesizes the average physical quantity ⁇ 1l calculated by the averaging unit 74-1 (l is a natural number from 1 to L) as the weighting factor 1. Therefore, the synthesized average physical quantity ⁇ 1l is expressed by Expression (42) and Expression (43), respectively.
  • the frequency estimation unit 75-1 performs the same operation as the frequency estimation unit 25. Therefore, the estimated value f est of the carrier frequency offset calculated by the frequency estimator 75-1 is calculated by the equations (44) and (4) when the sum of the received power used for the estimation of the carrier frequency offset is sufficiently higher than the noise power, respectively. (45) can be approximated.
  • Expressions (42) and (43) are expressions in which ⁇
  • the complex amplitude response between the transmitting antenna and the receiving antenna changes independently. Therefore, the probability that ⁇
  • This effect is generally referred to as a reception diversity effect. Therefore, the method for estimating the carrier frequency offset in the third embodiment of the present invention is estimated with the same training signal length and the same transmission power as compared with the method for estimating the carrier frequency offset in the first embodiment in a multipath fading environment. The error can be reduced. In addition, an estimated value can be obtained with the same estimation error with a shorter training signal length or lower transmission power.
  • FIG. 12 and FIG. 13 show a comparison of carrier frequency offset estimation error characteristics between the technique of the third embodiment of the present invention and the conventional technique.
  • the estimation error behaves stochastically. Therefore, it evaluated by RMS.
  • the modulation speed was 9600baud, and the interval of phase difference detection was 8 symbols.
  • the number of transmission antennas is 2, and the number of reception antennas is 2.
  • independent single-wave Rayleigh fading is assumed for each antenna as a propagation path.
  • the horizontal axis indicates CNR [dB].
  • the vertical axis indicates the carrier frequency offset estimation error [Hz].
  • a curve g31 indicates characteristics when the technique of the third embodiment is used.
  • a curve g32 shows the characteristics when the conventional technique is used.
  • the estimation error characteristic was evaluated by fixing the CNR to 10 dB and changing the training signal length. Comparing the required training signal length at which the estimation error is 10 Hz, the conventional technique required about 10,000 symbols, whereas the third embodiment uses about 20 symbols. That is, when the carrier frequency offset estimation error is 10 [Hz], the training signal length can be shortened to about 1/500 compared to the conventional technique by using the technique of the third embodiment. Note that the technique of the third embodiment can shorten the training signal length to about 2/3 as compared with the technique of the first embodiment.
  • the horizontal axis indicates the training signal length [symbol].
  • the vertical axis indicates the carrier frequency offset estimation error [Hz].
  • a curve g33 shows the characteristics when the technique of the third embodiment is used.
  • a curve g34 shows the characteristics when the conventional technique is used.
  • the training signal length is fixed to 54 symbols, the CNR is changed, and the estimation error characteristic is evaluated. Comparing the required CNR with an estimation error of 10 [Hz], it was about 23 dB in the prior art, whereas it was about 2 dB when using the technique of the third embodiment. That is, when the carrier frequency offset estimation error is 10 [Hz], the transmission power can be reduced to about 1/120 compared to the conventional technique by using the technique of the third embodiment. Note that the technique of the third embodiment can reduce the transmission power to about 1 ⁇ 4 compared to the technique of the first embodiment.
  • FIG. 14 is a schematic block diagram showing a receiving device 8 according to the fourth embodiment of the present invention.
  • the transmission device that communicates with the reception device 8 is the same as the transmission device 3 in the second embodiment, and the components, the connection of the components, and the signal flow are the same as those in the second embodiment.
  • the reception device 8 includes reception antennas 81-1 to 81-L 1 , radio units 82-1 to 82-L 2 , first phase difference detection units 83-1 to 83-L 3 , and first averaging unit 84.
  • the receiving antennas 81-1 to 81-L 1 receive the radio signal transmitted from the transmitting apparatus 3 and output it to the signal selection / synthesis unit 88-1.
  • Signal selection and combining unit 88-1 in order to avoid the influence of noise by the reception diversity effect, select or synthesize radio signals received by the receiving antennas 81-1 ⁇ 81-L 1, radio units 82-1 to 82 and outputs to -L 2.
  • the radio units 82-1 to 82-L 2 perform frequency conversion and digital conversion on the radio signal output from the signal selection / synthesis unit 88-1, generate a reception signal, and generate a signal selection / synthesis unit 88-2. Output to.
  • the signal selection / synthesizing unit 88-2 selects or synthesizes the reception signals generated by the radio units 82-1 to 82-L 2 in order to avoid the influence of noise by the reception diversity effect, and detects the first phase difference. parts 83-1 ⁇ 83-L 3, and outputs the second phase difference detecting unit 85-1 ⁇ 85-L 6.
  • the first phase difference detection units 83-1 to 83-L 3 compare the reception signal generated by the signal selection / synthesis unit 88-1 with a predetermined first series of training signals, A physical quantity indicated by a function of the phase transition amount at the time difference T 1 is detected and output to the signal selection / synthesis unit 88-3.
  • Signal selection and combining unit 88-3 in order to avoid the influence of noise by the reception diversity effect, the first physical quantity selected or synthesized to output from the first phase difference detecting unit 83-1 ⁇ 83-L 3 , and outputs it to the first averaging unit 84-1 ⁇ 74-L 4.
  • the first averaging units 84-1 to 74-L 4 average the first physical quantity output from the signal selection / synthesis unit 88-3 to avoid the influence of noise, and the first averaging physical quantity Is output to the signal selection / synthesis unit 88-4.
  • Signal selection and combining unit 88-4 in order to avoid the influence of noise by the reception diversity effect, select or synthesize first averaging physical amounts output from the first averaging unit 84-1 ⁇ 84-L 4 , and it outputs the frequency estimation unit 75-1 ⁇ 75-L 5.
  • Second phase difference detectors 85-1 to 85-L 6 compare the received signal generated by signal selector / synthesizer 88-1 with a predetermined second series of training signals, The second physical quantity indicated by the function of the phase transition amount at the time difference T 2 shorter than the time difference T 1 is detected and output to the signal selection / synthesis unit 88-5.
  • the signal selector / synthesizer 88-5 selects or synthesizes the second physical quantity output from the second phase difference detectors 85-1 to 85-L 6 in order to avoid the influence of noise due to the reception diversity effect.
  • the second averaging units 86-1 to 86 -L 7 are used.
  • the second averaging units 86-1 to 86 -L 7 average the second physical quantity output from the signal selection / synthesizing unit 88-5 to avoid the influence of noise, and the second averaging physical quantity Is output to the signal selection / synthesis unit 88-6.
  • Signal selection and combining unit 88-6 in order to avoid the influence of noise by the reception diversity effect, select or synthesize second averaging physical amounts output from the second averaging unit 86-1 ⁇ 86-L 7 , and it outputs the frequency estimation unit 75-1 ⁇ 75-L 5.
  • the frequency estimation units 75-1 to 75-L 5 receive the first averaged physical quantity output from the signal selection / synthesis unit 88-4 and the second averaged output from the signal selection / synthesis unit 88-6. the physical quantity estimates the carrier frequency offset on the basis of outputs to the frequency estimation unit 75-1 ⁇ 75-L 5.
  • Signal selection and combining unit 88-7 in order to avoid the influence of noise by the reception diversity effect, selecting or combining the carrier frequency offset estimated by the frequency estimation unit 75-1 ⁇ 75-L 5.
  • the signal selection / combination unit 88-1 can be omitted.
  • the number L 2 of the radio unit if it is 1, or, and the number L 6 having L 3 and the second phase difference detection unit number L 2 and the first phase difference detecting unit of the radio unit, If the number is the same, the signal selection / synthesis unit 88-2 can be omitted.
  • the number L 3 of first phase difference detection units is 1, or the number L 3 of first phase difference detection units and the number L 4 of first averaging units are the same number.
  • the signal selection / synthesis unit 88-3 can be omitted.
  • the number of first averaging units L 4 is 1, or when the number of first averaging units L 4 and the number of frequency estimation units L 5 are the same, signal selection The synthesis unit 88-4 can be omitted.
  • the signal selection / synthesis unit 88-5 can be omitted.
  • the number L 7 of the second averaging unit if it is 1, or, if the number L 5 having L 7 and the frequency estimation unit of the second averaging unit is equal, the signal selection The synthesis unit 88-6 can be omitted.
  • the number L 5 of the frequency estimation unit if it is 1, it is possible to omit the signal selection and combining unit 88-7.
  • a plurality of receiving antennas are provided as compared with the second embodiment. Also includes a signal selection and combining unit 88-1 for selecting or combining a plurality of radio signals received by the receiving antennas 81-1 ⁇ 81-L 1. Further, a signal selection / synthesis unit 88-2 for selecting or combining a plurality of reception signals generated from the radio signal is provided. Further, signal selection / synthesis units 88-3 and 88-5 are provided for selecting or synthesizing a plurality of first physical quantities indicated by a function of the phase transition amount calculated from the received signal.
  • signal selection / synthesis units 84-1 and 86-1 are provided that select or synthesize a plurality of first averaged physical quantities obtained by averaging the first physical quantities indicated by the phase transition amount function. Further, a plurality of second physical quantities represented by a function of the phase transition amount calculated from the received signal and a plurality of second averaged physical quantities obtained by averaging the second physical quantities represented by the function of the phase transition amount are selected or Signal selection / synthesis units 88-4 and 88-6 for synthesis are provided. Further, a signal selecting / synthesizing unit 88-7 for selecting or synthesizing a plurality of carrier frequency offsets estimated from the first average physical quantity and the second average physical quantity is provided.
  • the carrier frequency offset can be estimated with higher accuracy by the reception diversity effect as in the third embodiment.
  • the estimation accuracy of the carrier frequency offset in the second embodiment of the present invention is the same as that in the third embodiment.
  • a frequency offset is appropriately given to a training signal based on a predetermined signal sequence transmitted from a plurality of transmission antennas.
  • a decrease in reception level can be avoided.
  • the carrier frequency offset can be estimated with high accuracy with a small number of averaged samples.
  • the present invention is not limited to the above embodiments, and can be modified without departing from the spirit of the present invention.
  • the transmission antenna of the transmission apparatus is independent for each wireless signal.
  • the present invention can also be applied to a wireless communication system that transmits a plurality of wireless signals generated by a plurality of wireless units (transmitting units) from the same transmission antenna. In that case, a plurality of radio signals pass from the transmitting antenna to the receiving antenna. If the propagation characteristics including the antenna are not the propagation characteristics having the same condition for all of the plurality of radio signals transmitted from the same transmitting antenna, the effect of the present invention can be expected.
  • the transmission device of the present invention corresponds to the transmission device 1 and the transmission device 3.
  • the first training signal sequence generation unit of the present invention corresponds to the training signal sequence generation unit 11 and the first training signal sequence generation unit 31.
  • the first frequency offset applying unit of the present invention corresponds to the frequency offset applying units 12-1 to 12-M and the first frequency offset applying units 32-1 to 32-M.
  • the transmission unit of the present invention corresponds to the radio units 13-1 to 13-M and the radio units 35-1 to 35-M.
  • the transmission antenna of the present invention corresponds to the transmission antennas 14-1 to 14-M and the transmission antennas 36-1 to 36-M.
  • the first series of training signals of the present invention corresponds to the predetermined series of training signals in the first embodiment and the first series of training signals in the second embodiment.
  • the first physical quantity of the present invention corresponds to the physical quantity in the first embodiment and the first physical quantity in the second embodiment.
  • the first averaged physical quantity of the present invention corresponds to the averaged physical quantity in the first embodiment and the first averaged physical quantity in the second embodiment.
  • the receiving device of the present invention corresponds to the receiving device 2 and the receiving device 4.
  • the receiving antenna of the present invention corresponds to the receiving antenna 21 and the receiving antenna 41.
  • the receiving unit of the present invention corresponds to the radio unit 22 and the radio unit 42.
  • the first phase difference detection unit of the present invention corresponds to the phase difference detection unit 23 and the first phase difference detection unit 43.
  • the first averaging unit of the present invention corresponds to the averaging unit 24 and the first averaging unit 44.
  • the second phase difference detection unit of the present invention corresponds to the second phase difference detection unit 45.
  • the second averaging unit of the present invention corresponds to the second averaging unit 46.
  • the frequency estimation unit of the present invention corresponds to the frequency estimation unit 25 and the frequency estimation unit 47.
  • the signal selection / synthesis unit of the present invention corresponds to the signal selection / synthesis units 76-1 to 76-5 and the signal selection / synthesis units 88-1 to 88-7.
  • the present invention can be applied to a wireless communication system, a transmission device, a reception device, a wireless communication method, a transmission method, a reception method, and the like that accurately estimate a carrier frequency offset with a small number of averaged samples even in a multipath environment.
  • Second training signal sequence generating unit 34-1 to 34-M ... second frequency offset applying unit , 35-1 to 35-M... Wireless unit, 36-1 to 36-M. ⁇
  • Receiving antenna 42... Radio unit, 43... First phase difference detection unit, 44... First averaging unit, 45.
  • Reception antenna 82-1 to 82-L 2 ... Radio unit, 83-1 to 83-L 3 . , 84-1 to 84-L 4 ... First averaging unit, 85-1 to 85-L 6 ... Second phase difference detection unit, 86-1 to 86-L 7. Second averaging unit, 75- 1 to 75-L 5: Frequency estimation unit, 88-1 to 88-7 ... Signal selection / synthesis unit, 100 ... Radio communication system, 200 ... Radio communication system

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  • Digital Transmission Methods That Use Modulated Carrier Waves (AREA)
PCT/JP2009/057904 2008-04-21 2009-04-21 無線通信システム、送信装置、受信装置、無線通信方法、送信方法、受信方法 WO2009131110A1 (ja)

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EP09734275.2A EP2270993B1 (en) 2008-04-21 2009-04-21 Radio communication system and radio communication method
US12/988,417 US8644766B2 (en) 2008-04-21 2009-04-21 Radio communication system, transmission device, reception device, radio communication method, transmission method, reception method
CN2009801139292A CN102007700B (zh) 2008-04-21 2009-04-21 无线电通信系统、发送装置、接收装置、无线电通信方法、发送方法、接收方法

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