WO2008080503A1 - Filtre à haute fréquence avec couplage de circuit de verrouillage - Google Patents

Filtre à haute fréquence avec couplage de circuit de verrouillage Download PDF

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Publication number
WO2008080503A1
WO2008080503A1 PCT/EP2007/010634 EP2007010634W WO2008080503A1 WO 2008080503 A1 WO2008080503 A1 WO 2008080503A1 EP 2007010634 W EP2007010634 W EP 2007010634W WO 2008080503 A1 WO2008080503 A1 WO 2008080503A1
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WO
WIPO (PCT)
Prior art keywords
coupling
frequency
frequency filter
inner conductor
filter according
Prior art date
Application number
PCT/EP2007/010634
Other languages
German (de)
English (en)
Inventor
Wilhelm Weitzenberger
Original Assignee
Kathrein-Werke Kg
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Kathrein-Werke Kg filed Critical Kathrein-Werke Kg
Priority to EP07856439A priority Critical patent/EP2095459A1/fr
Priority to CN200780047099.9A priority patent/CN101563809B/zh
Priority to KR1020097012217A priority patent/KR101484934B1/ko
Priority to AU2007341704A priority patent/AU2007341704B2/en
Publication of WO2008080503A1 publication Critical patent/WO2008080503A1/fr

Links

Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/201—Filters for transverse electromagnetic waves
    • H01P1/205—Comb or interdigital filters; Cascaded coaxial cavities
    • H01P1/2053—Comb or interdigital filters; Cascaded coaxial cavities the coaxial cavity resonators being disposed parall to each other
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/213—Frequency-selective devices, e.g. filters combining or separating two or more different frequencies
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/201—Filters for transverse electromagnetic waves
    • H01P1/205—Comb or interdigital filters; Cascaded coaxial cavities
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/213—Frequency-selective devices, e.g. filters combining or separating two or more different frequencies
    • H01P1/2136—Frequency-selective devices, e.g. filters combining or separating two or more different frequencies using comb or interdigital filters; using cascaded coaxial cavities

Definitions

  • the invention relates to a high-frequency filter with blocking circuit coupling according to the preamble of claim 1.
  • High frequency filters are used in a wide range.
  • the mobile subscriber's communication with the base station is handled by transmit-receive antennas provided in the base station. It is desirable to use only a common antenna for the transmit and receive signals.
  • Transmit and receive signals use different frequency ranges.
  • the antenna used must be capable of transmitting and receiving in both frequency ranges.
  • a suitable frequency filtering is required, which ensures that on the one hand, the transmission signals from the transmitter only to the antenna (and not in the direction of the receiver) and on the other the received signals from the antenna are only forwarded to the receiver.
  • a pair of high-frequency filters can be used, both of which pass through a specific, namely the respectively desired frequency band (bandpass filter).
  • bandpass filter a specific frequency band
  • band-stop filters One speaks here of band-stop filters.
  • a pair of high-frequency filters consisting of a first filter that passes frequencies below a frequency lying between the transmit and receive band and the overlying areas blocks (low-pass filter), and a second filter, which frequencies below this between the transmit and receive band frequency blocks and passes the higher frequencies. It is then a so-called high-pass filter.
  • Other combinations of the mentioned filter types can be used.
  • the transmission-Empfangsbandaufsplittung within the base station is performed in this case usually with duplex switches, which have the mentioned task, the transmission-reception path as possible without interference on the common antenna together.
  • the duplexer consists of two interconnected bandpass filters, namely the so-called transmit bandpass (TX bandpass) and the Empfangsband- pass (RX bandpass), with separate connections for the receiving branch, the transmitting branch and the jointly connected antenna are provided.
  • the bandpasses used inside the duplexer must be On the one hand, therefore, they have the selection (ie the necessary stop attenuation) necessary for the interconnection of the transmitting and receiving bandpass filters (TX / RX) and, on the other hand, they are intended to attenuate the useful signals as little as possible in their respective passband.
  • the bandpass structures used in duplex switches are predominantly composed of coaxial resonators in the common mobile radio frequency ranges (e.g., GSM / UMTS).
  • bandpasses (so-called Cauer bandpasses) which have transmission zeros (so-called blocking poles) in the stopband.
  • This type of filter is very often realized in conjunction with coaxial resonators by so-called cross-coupling.
  • non-adjacent resonators ie, in the course of the signal not directly consecutive resonators
  • a bandpass structure such capacitive or inductive coupled together that arise due signal splitting with subsequent phase-shifted merge amplitude cancellations (transmission zeros or blocking points) in the transmission characteristic.
  • Such a cross-coupling technique is described, for example, in IEEE Transactions on Microwave Theory and Techniques, Vol. 4, April 2003 "Cross-Coupling in Coaxial Cavity Filters - A tutorial Overview", J. Brian Thomas, pages 1368-1376. - A -
  • a generic high-frequency filter with blocking circuit coupling in particular in the form of a duplexer, can generally be taken as known from WO 2004/100305 A1. It is a high-frequency filter with a plurality of resonators, which are arranged between three terminals, namely between a terminal for a transmitting branch, a connection for the receiving branch and a connection for the common antenna.
  • the doubly coupled resonators oscillate in the coupled state in two mutually different coupling resonance frequencies which are different from the resonant frequency, which strongly strengthens the two Coupled resonators considered individually in each case in the frequency range between the transmitting and receiving band have or tuned to the resonators.
  • coupling tuning elements are provided on a separating wall located between two inner conductors of two adjacent coaxial resonators, above which a coupling window is formed to the upper waveguide wall, which can be adjusted in order to change the coupling.
  • JP 09-199906 A describes the use of adjusting loops between two resonators in order to change the coupling.
  • each resonator can be additionally adjusted by screws similar to the aforementioned prior art.
  • the resonators are inductively or capacitively coupled to each other, wherein the inductive or capacitive coupling can be adjusted primarily by varying the ratio between the distance between the shafts and the distance between the heads of the inner conductors. For fine adjustment also serve screws between the individual resonators.
  • Object of the present invention is in contrast to provide an improved high-frequency filter, the one improved passage and / or blocking effect for predetermined frequencies or frequency ranges, with restrictions on the filter topology should not be possible.
  • the improvement over the prior art is achieved essentially by the fact that the high-frequency filter comprising electromagnetically coupled coaxial resonators, with respect to at least one selected coaxial resonator pair whose two coaxial resonators are immediately adjacent to one another in the transmission path, can be specifically preselected and / or presettable Coupling impedance is assigned, which is dimensioned so that due to the combination of capacitive and inductive coupling results in a coupling impedance resonance with a defined stop frequency. Since this type of coupling generates a blocking point in the transmission behavior of the high-frequency filter, it is also referred to below as blocking-circuit coupling.
  • this blocking circuit coupling so the blocking frequency, so that it lies on the one hand outside the passband of the RF filter, and on the other hand within the stop band of an RF filter.
  • the blocking frequency can be predefined primarily by changing and / or setting and / or preselecting two variables which essentially influence or determine the blocking frequency.
  • a defined capacitive coupling takes place.
  • the defined inductive coupling may be e.g. be set over the distance of the resonators to be coupled.
  • the required capacitive coupling can be contrasted, for example, realized by an elongated extension at the top of the resonators to be coupled.
  • the desired coupling of adjacent resonators can be set so changed by specifying the inductive and capacitive coupling that the desired attenuation outside of the passband of a RF filter and within a stopband of an RF filter.
  • the distance between two inner conductors can be reduced by providing them with radial extensions on their upper side. This can also be used to reduce the overall height of the filter.
  • FIG. 1 The schematic structure of a high-frequency filter in the case of a duplex switch in a schematic basic representation
  • FIG. 2 shows a schematic top view of a high-frequency filter with a signal path
  • Figure 3 is a schematic axial section along the line III-III in Figure 2;
  • Figure 4 is a Ersat zschaltsent with respect to the embodiment of Figures 2 and 3;
  • FIG. 5 shows a diagram for the reproduction of the transmission and attenuation behavior of a bandpass filter according to the invention for a duplexer
  • FIGS. 6a to 6f show different views of different settings of a coupling capacitance or coupling inductance.
  • the RF filter 1 shows a schematic diagram of a high-frequency filter in the form of a duplexer 3, wherein the RF filter 1 comprises three terminals 5, 7 and 9, namely a terminal TX, RX and a terminal for the antenna port AP, so that transmission signals via a first signal path from the transmitting terminal 5 coming from the antenna port AP (from there the common antenna) and vice versa, the received signals from the antenna via the antenna port AP (terminal 9) the receiving terminal 7 can be supplied.
  • the duplexer 3 comprises in the two signal paths a corresponding bandpass filter 11 or 13, which have the necessary selection (ie stop attenuation), thus From the transmission terminal no signals can get into the reception branch.
  • the pass-bands for the useful signals should be damped as little as possible.
  • a high-frequency filter 1 with a signal path 10 is shown, for example, from a connection 5 to a connection 9, that is, from a transmission connection to an antenna port connection (ie, only the shows a branch of a duplexer) and thereby comprises six coaxial resonators 15.
  • the coaxial resonators 15 are arranged in a conductive housing 17 with a plurality of resonator chambers 19, where in the embodiment shown in the middle or rather in the central region perpendicular to the housing bottom 17a each have a conductive inner conductor 21 extends - as is apparent from the illustration in Figure 3 - the at a suitable distance below an attachable to the housing 17 electrically conductive housing cover 17b ends.
  • Each coaxial resonator 15 thus has a circumferential housing wall 17c, wherein along the signal path coupling openings 23, so-called apertures are provided in the respective housing wall 17c, whereby windows are formed, through which the electromagnetic waves can propagate.
  • FIG. 3 shows only a schematic sectional illustration, for example, through a section for the bandpass filter 11 provided for the transmitting branch, whereby the signal path for the second reception branch of the duplex divider not shown in FIG could connect.
  • the corresponding equivalent circuit diagram is reproduced in FIG. 4, namely with the signal path 10 from the connection 5 to the connection 9, wherein the six resonators 11 are represented as parallel resonant circuits 111 whose one output is grounded and the opposite output is in the corresponding sequence is connected to the signal path 10.
  • the parallel resonant circuits 24 are characterized in a known manner by a capacitor and an inductance.
  • the distances between the connection points 25 of the individual parallel resonant circuits 24 can also be described by inductances 27, as far as conventional couplings between Coaxial resonators, so not to the below-explained coupling of the invention.
  • connection between two mutually parallel adjacent parallel resonant circuits can not be described by an inductive coupling, but by a blocking circuit coupling in the form of a parallel resonant circuit with a capacitance and an inductance, as shown in Figure 4 .
  • a capacitive cross-coupling using a capacitor C is additionally realized (see FIG. 2 and FIG. 4).
  • a coupling according to the invention is realized between the first and the second coaxial resonators 15.1 and 15.2 as well as between the second and third coaxial resonators 15.2 and 15.3 as well as the third and fourth coaxial resonators 15.3 and 15.4.
  • a conventional coupling (cross-coupling) between the first and the fifth coaxial resonators 15.1 and 15.5 is shown, which is also discussed below.
  • This capacitive coupling is shown, for example, between inner conductor sections 21a on the two inner conductors 21 of the two first coaxial resonators 15.1 and 15.2 in FIG. 3, by correspondingly drawn E-field vectors 121 '(FIG. 2).
  • the inductive coupling is ultimately preselected and / or adjusted accordingly.
  • the inductive coupling can be preset or selected differently by other alternative or supplementary, ie additional measures.
  • the coupling capacitances and coupling inductances necessary for setting the blocking circuit coupling can be set by known coupling setup variants.
  • the coupling diaphragms ie the passage openings between two adjacent coaxial resonators in the height and / or width can be set differently, whereby the degree of coupling changes).
  • coupling pins can be provided between the resonators, coupling loops or coupling webs.
  • the coupling webs would extend, for example, in a partial height between two inner conductors, ie also extend parallel to the inner conductors (preferably perpendicular to the bottom wall) and thereby be electrically connected to the bottom of the coupling resonators.
  • the Coupling loops can be electrically and mechanically connected in the manner of an inverted U-bracket between two inner conductors on the ground. It is also possible for a coupling loop to be positioned in a vertical orientation (ie lying in a vertical plane) or in a plane slightly inclined thereto via a vertical axis of rotation with respect to the ground and can thereby be rotated in the circumferential direction. The larger the area penetrated by the magnetic surfaces, the greater the coupling effect.
  • the mentioned effects can also be used in combination or parts thereof in combination in order to implement and implement the desired coupling setting options accordingly.
  • FIG. 6b On the basis of Figure 6b is shown in plan view that along the connecting line of two adjacent inner conductor 21 is provided from the ground uplifting web, which extends there against the height of the inner nenleiter in a partial height. This is a so-called coupling web 307.
  • This coupling web 307 is electrically connected to the bottom 17a of the housing 17 of the RF filter.
  • a first window opening 303 (coupling diaphragm) between the coaxial resonator 15.1 and 15.2 is significantly reduced and, on the other hand, a further coupling diaphragm 303 between the resonator 15.2 and 15.3 becomes clear is enlarged, so that the coupling aperture in any case has a greater width parallel to the bottom or top surface.
  • a coupling loop 305 for changing the coupling inductance which is positioned in the bottom in the manner of an inverted "U" is shown.
  • a coupling loop is shown with reference to FIG. 6f, which can be rotated about its vertical axis 305 ', so that the magnetic field strength passing through the loop changes, whereby the coupling inductance can be changed and set differently.
  • the desired blocking position can be generated with a defined blocking frequency outside the passband of an HF filter. It is crucial that in addition to the aforementioned defined inductive resonator coupling a defined capacitive coupling is present.
  • the aforementioned inductive coupling can be adjusted by the distance 321 of the resonators to be coupled (position of the inner conductor 21 of the relevant resonator), whereas the capacitive coupling is adjusted via the clear distance 121 between two adjacent inner conductors 21 of two adjacent resonators, the size of which can be predetermined by the clear distance of the mentioned elongated (radially protruding) inner conductor extensions 21.
  • the second inner conductor of the second Koaxialresonators 15.2 is formed in the manner of a T-shaped, namely with another, usually parallel to the ground and thus transversely or radially to the inner conductor protruding, opposite réelleleitererwei- sion 21 a.
  • the third inner conductor 21 of the third coaxial resonator 15.3 to be coupled therewith could also be provided with a corresponding inner conductor extension 21a, the distance between these two adjacent inner conductor extensions 21a being much greater than the distance between the first and second coaxial resonators.
  • an additional bridging member 221 is further provided for this purpose, which is held and positioned in isolation with respect to the housing.
  • the sum distance formed from the two individual distances 121a and 121b gives the size which is decisive for the specification of the desired defined capacitance coupling.
  • the additional inner conductor 21 does not see two inner conductor extensions 180 'opposite each other (as the second inner conductor 21 of the second coaxial resonator 15.2 does) due to the further coupling between the third and fourth coaxial resonators 15.3 and 15.4 ), but has two inner conductor extensions 21a, which are arranged at a 90 ° angle to each other, namely according to the signal path of the electromagnetic waves angled at 90 ° .
  • the fact that the two inner conductors 21 are positioned more densely with respect to the second and third resonators 15.2 and 15.3 results from the illustration of Figure 2 in plan view.
  • a bandpass filter can be realized, as reproduced in FIG. 4, with one or more blocking frequencies f s , ie one or more so-called blocking poles.
  • This transmission characteristic shows that, in accordance with the number of coaxial resonators coupled within the scope of the invention, the plurality of blocking poles (blocking frequencies) can be generated such that these blocking frequencies lie, for example, in the passband (frequency range) of an adjacent bandpass filter which is offset.
  • another coupling according to the invention may also be implemented at any other arbitrary point, that is to say, for example, between the fourth and fifth and / or fifth and sixth coaxial resonators.
  • n-coaxial resonators therefore, five, namely n-1 coupling impedances can be dimensioned such that a coupling impedance results in each case with a defined frequency f s due to the communication of capacitive and inductive coupling, ie a blocking point by the type of coupling in the transmission behavior of the high-frequency filter at the at least one or more mutually offset frequencies f sl , f s2 , f s3 , etc. to f Sn results, which may be referred to as blocking circuit coupling.
  • a conventional coupling is additionally realized, which can also be additionally provided in the case of the HF filter according to the invention.
  • This conventional coupling (cross-coupling) is also shown in the equivalent circuit diagram according to FIG. 4, namely there via the connecting path 131 with the capacitor C provided there.
  • a coupling element 31 which acts between the first and fifth coaxial resonators and is usually formed by an electrically conductive coupling element projecting into the respective cavity of the associated resonator and having a "bone-shaped" side view Generated by its enlarged opposite conclusion with the associated inner conductor in the respective coaxial resonator capacitive coupling.
  • This is also included in the equivalent circuit diagram. characterized, namely by the capacitive coupling path 131.
  • FIG. 5 a diagram of the bandpass behavior of a bandpass filter 11 for a transmission branch and for a bandpass filter 13 for a reception branch (in dashed lines) is reproduced.
  • This shows the number of blocking poles f RS / f ⁇ s , depending on the number of blocking circuit couplings used.
  • the increasing frequency F is reproduced on the X-axis and the damping D on the Y-axis.
  • the at least one or more blocking poles can be laid so that they lie, for example, in a frequency range of an adjacent bandpass offset from the passband of the relevant bandpass.
  • the one or more blocking poles are arranged, in whole or in part, at least in such a way that they lie outside the actual passband of the bandpass filter in a frequency range which differs from the center frequency of the relevant bandpass filter. less than ⁇ 50%, in particular less than ⁇ 40%, ⁇
  • the advantages of the invention can still be realized to a sufficient extent, if at least one or more of the Sperrpole (blocking points) of a respective bandpass filter Considered by appropriate choice of suitable coupling capacitances and coupling inductances is so laid or be that this at least one Sperrpol in a frequency range is generated, not more than five times the duplex spacing (ie the frequency center distance of two adjacent band passes) of the center frequency the relevant bandpass away.
  • the blocking poles viewed from a bandpass filter, should be arranged outside the passband of the bandpass filter such that the blocking poles are not more than five times, in particular not more than four times, three times, twice or even less than the duplex spacing (ie the second frequency spacing second) neighboring bandpasses).
  • one or more of the blocking poles can also be positioned in a frequency range of the adjacent bandpass.
  • the inductive or the capacitive coupling can be determined whether the respective Sperrpol below a Bandpass filter or above a bandpass filter (ie with the bandpass filter lower frequency or higher frequency) is formed. This is achieved by selecting the coupling capacitance and coupling inductance of the trap coupling so that the resulting resonant frequency is either below or above the bandpass passband as needed.

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  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Control Of Motors That Do Not Use Commutators (AREA)

Abstract

L'invention concerne un filtre à haute fréquence amélioré présentant les caractéristiques suivantes : le filtre à haute fréquence présente un comportement de transmission avec une résonance d'impédance de couplage avec au moins un emplacement de blocage à une fréquence (fs), l'emplacement de blocage pouvant être réglé avec cette fréquence (fs) grâce à la spécification et/ou présélection d'un couplage capacitif (12/') et inductif (12/'') défini entre deux résonateurs coaxiaux (15) se suivant directement sur une voie de signalisation (10).
PCT/EP2007/010634 2006-12-22 2007-12-06 Filtre à haute fréquence avec couplage de circuit de verrouillage WO2008080503A1 (fr)

Priority Applications (4)

Application Number Priority Date Filing Date Title
EP07856439A EP2095459A1 (fr) 2006-12-22 2007-12-06 Filtre à haute fréquence avec couplage de circuit de verrouillage
CN200780047099.9A CN101563809B (zh) 2006-12-22 2007-12-06 具有带阻滤波回路耦合的高频滤波器
KR1020097012217A KR101484934B1 (ko) 2006-12-22 2007-12-06 폐쇄 회로 커플링을 구비한 고주파 필터
AU2007341704A AU2007341704B2 (en) 2006-12-22 2007-12-06 High frequency filter with closed circuit coupling

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102006061141.1A DE102006061141B4 (de) 2006-12-22 2006-12-22 Hochfrequenzfilter mit Sperrkreiskopplung
DE102006061141.1 2006-12-22

Publications (1)

Publication Number Publication Date
WO2008080503A1 true WO2008080503A1 (fr) 2008-07-10

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Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/EP2007/010634 WO2008080503A1 (fr) 2006-12-22 2007-12-06 Filtre à haute fréquence avec couplage de circuit de verrouillage

Country Status (6)

Country Link
EP (1) EP2095459A1 (fr)
KR (1) KR101484934B1 (fr)
CN (1) CN101563809B (fr)
AU (1) AU2007341704B2 (fr)
DE (1) DE102006061141B4 (fr)
WO (1) WO2008080503A1 (fr)

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ES2401083T3 (es) 2000-11-08 2013-04-16 Institut Straumann Ag Procedimiento para la colocación de prótesis dentales
FI125596B (en) 2010-11-12 2015-12-15 Intel Corp Customizable resonator filter
KR101194971B1 (ko) * 2011-05-19 2012-10-25 주식회사 에이스테크놀로지 광대역을 실현하는 다중 모드 필터
GB201303027D0 (en) * 2013-02-21 2013-04-03 Mesaplexx Pty Ltd Filter
US9509031B2 (en) * 2013-05-23 2016-11-29 Com Dev International Ltd. Coaxial filter with elongated resonator
EP2814111B1 (fr) * 2013-06-13 2020-03-18 Alcatel Lucent Ensemble de résonance
EP2814112A1 (fr) * 2013-06-13 2014-12-17 Alcatel Lucent Ensemble de résonance
WO2015008150A2 (fr) * 2013-06-25 2015-01-22 Powerwave Technologies S.A.R.L. Agencement de couplage entre résonateurs de filtre à cavité
CN104701592B (zh) * 2015-04-01 2017-11-21 河南理工大学 Tm模介质腔体滤波器
KR101677950B1 (ko) 2015-04-13 2016-11-21 주식회사 에이스테크놀로지 크로스 커플링을 이용하는 캐비티 필터
DE102015005523B4 (de) * 2015-04-30 2018-03-29 Kathrein-Werke Kg Hochfrequenzfilter mit dielektrischen Substraten zur Übertragung von TM-Moden in transversaler Richtung
DE102016117415B4 (de) 2016-09-15 2019-10-31 Kathrein Mobilcom Austria Gmbh Hochfrequenzfilter mit verbesserter Signaleinkopplung bzw. Signalauskopplung
CN113675561A (zh) * 2020-05-14 2021-11-19 大富科技(安徽)股份有限公司 一种滤波器及通信设备

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US5528204A (en) * 1994-04-29 1996-06-18 Motorola, Inc. Method of tuning a ceramic duplex filter using an averaging step
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Publication number Priority date Publication date Assignee Title
US3736536A (en) * 1971-04-14 1973-05-29 Bendix Corp Microwave filter
US5528204A (en) * 1994-04-29 1996-06-18 Motorola, Inc. Method of tuning a ceramic duplex filter using an averaging step
WO1999030383A2 (fr) * 1997-12-11 1999-06-17 Lk-Products Oy Structure de resonateur

Also Published As

Publication number Publication date
CN101563809A (zh) 2009-10-21
EP2095459A1 (fr) 2009-09-02
KR20090098822A (ko) 2009-09-17
DE102006061141B4 (de) 2014-12-11
KR101484934B1 (ko) 2015-01-21
CN101563809B (zh) 2014-09-17
AU2007341704B2 (en) 2012-08-09
DE102006061141A1 (de) 2008-06-26
AU2007341704A1 (en) 2008-07-10

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