WO2007114391A1 - 誘電体導波路デバイス、これを備える移相器、高周波スイッチおよび減衰器、ならびに高周波送信器、高周波受信器、高周波送受信器およびレーダ装置、アレイアンテナ装置、誘電体導波路デバイスの製造方法 - Google Patents
誘電体導波路デバイス、これを備える移相器、高周波スイッチおよび減衰器、ならびに高周波送信器、高周波受信器、高周波送受信器およびレーダ装置、アレイアンテナ装置、誘電体導波路デバイスの製造方法 Download PDFInfo
- Publication number
- WO2007114391A1 WO2007114391A1 PCT/JP2007/057287 JP2007057287W WO2007114391A1 WO 2007114391 A1 WO2007114391 A1 WO 2007114391A1 JP 2007057287 W JP2007057287 W JP 2007057287W WO 2007114391 A1 WO2007114391 A1 WO 2007114391A1
- Authority
- WO
- WIPO (PCT)
- Prior art keywords
- frequency
- dielectric
- terminal
- transmission line
- frequency signal
- Prior art date
Links
- 238000004519 manufacturing process Methods 0.000 title claims description 20
- 230000005540 biological transmission Effects 0.000 claims abstract description 324
- 230000005684 electric field Effects 0.000 claims abstract description 116
- 239000004020 conductor Substances 0.000 claims description 299
- 230000008859 change Effects 0.000 claims description 110
- 230000001902 propagating effect Effects 0.000 claims description 89
- 238000001514 detection method Methods 0.000 claims description 18
- 238000000034 method Methods 0.000 claims description 18
- 239000000758 substrate Substances 0.000 claims description 11
- 230000008569 process Effects 0.000 claims description 9
- 238000011144 upstream manufacturing Methods 0.000 claims description 9
- 238000003475 lamination Methods 0.000 claims description 7
- 230000010363 phase shift Effects 0.000 claims description 6
- 238000010030 laminating Methods 0.000 claims description 5
- 239000010408 film Substances 0.000 description 78
- 239000000463 material Substances 0.000 description 44
- 230000000694 effects Effects 0.000 description 25
- 238000003780 insertion Methods 0.000 description 21
- 230000037431 insertion Effects 0.000 description 21
- 230000008054 signal transmission Effects 0.000 description 20
- 238000010586 diagram Methods 0.000 description 18
- 229910052751 metal Inorganic materials 0.000 description 16
- 239000002184 metal Substances 0.000 description 16
- 230000005672 electromagnetic field Effects 0.000 description 13
- BASFCYQUMIYNBI-UHFFFAOYSA-N platinum Chemical compound [Pt] BASFCYQUMIYNBI-UHFFFAOYSA-N 0.000 description 12
- KDLHZDBZIXYQEI-UHFFFAOYSA-N Palladium Chemical compound [Pd] KDLHZDBZIXYQEI-UHFFFAOYSA-N 0.000 description 10
- 230000000644 propagated effect Effects 0.000 description 10
- 239000010936 titanium Substances 0.000 description 9
- 239000010949 copper Substances 0.000 description 8
- 238000009826 distribution Methods 0.000 description 8
- 239000010931 gold Substances 0.000 description 8
- 230000005855 radiation Effects 0.000 description 8
- 230000002238 attenuated effect Effects 0.000 description 7
- 239000011651 chromium Substances 0.000 description 7
- 239000000919 ceramic Substances 0.000 description 6
- 239000013078 crystal Substances 0.000 description 6
- 239000003989 dielectric material Substances 0.000 description 6
- 229920005989 resin Polymers 0.000 description 6
- 239000011347 resin Substances 0.000 description 6
- 239000000126 substance Substances 0.000 description 6
- 239000010409 thin film Substances 0.000 description 6
- 229910052782 aluminium Inorganic materials 0.000 description 5
- XAGFODPZIPBFFR-UHFFFAOYSA-N aluminium Chemical compound [Al] XAGFODPZIPBFFR-UHFFFAOYSA-N 0.000 description 5
- 230000015572 biosynthetic process Effects 0.000 description 5
- 238000005516 engineering process Methods 0.000 description 5
- 230000010355 oscillation Effects 0.000 description 5
- 229910052719 titanium Inorganic materials 0.000 description 5
- 239000011701 zinc Substances 0.000 description 5
- VYZAMTAEIAYCRO-UHFFFAOYSA-N Chromium Chemical compound [Cr] VYZAMTAEIAYCRO-UHFFFAOYSA-N 0.000 description 4
- RYGMFSIKBFXOCR-UHFFFAOYSA-N Copper Chemical compound [Cu] RYGMFSIKBFXOCR-UHFFFAOYSA-N 0.000 description 4
- BQCADISMDOOEFD-UHFFFAOYSA-N Silver Chemical compound [Ag] BQCADISMDOOEFD-UHFFFAOYSA-N 0.000 description 4
- RTAQQCXQSZGOHL-UHFFFAOYSA-N Titanium Chemical compound [Ti] RTAQQCXQSZGOHL-UHFFFAOYSA-N 0.000 description 4
- 229910045601 alloy Inorganic materials 0.000 description 4
- 239000000956 alloy Substances 0.000 description 4
- 229910052802 copper Inorganic materials 0.000 description 4
- 230000007423 decrease Effects 0.000 description 4
- 238000005530 etching Methods 0.000 description 4
- 239000000945 filler Substances 0.000 description 4
- 239000011521 glass Substances 0.000 description 4
- PCHJSUWPFVWCPO-UHFFFAOYSA-N gold Chemical compound [Au] PCHJSUWPFVWCPO-UHFFFAOYSA-N 0.000 description 4
- 229910052737 gold Inorganic materials 0.000 description 4
- 229910052697 platinum Inorganic materials 0.000 description 4
- 239000004065 semiconductor Substances 0.000 description 4
- 229910052709 silver Inorganic materials 0.000 description 4
- 239000004332 silver Substances 0.000 description 4
- 238000013459 approach Methods 0.000 description 3
- 229910052804 chromium Inorganic materials 0.000 description 3
- 238000005259 measurement Methods 0.000 description 3
- 229910052763 palladium Inorganic materials 0.000 description 3
- JBQYATWDVHIOAR-UHFFFAOYSA-N tellanylidenegermanium Chemical compound [Te]=[Ge] JBQYATWDVHIOAR-UHFFFAOYSA-N 0.000 description 3
- 230000007704 transition Effects 0.000 description 3
- VYPSYNLAJGMNEJ-UHFFFAOYSA-N Silicium dioxide Chemical compound O=[Si]=O VYPSYNLAJGMNEJ-UHFFFAOYSA-N 0.000 description 2
- XUIMIQQOPSSXEZ-UHFFFAOYSA-N Silicon Chemical compound [Si] XUIMIQQOPSSXEZ-UHFFFAOYSA-N 0.000 description 2
- XLOMVQKBTHCTTD-UHFFFAOYSA-N Zinc monoxide Chemical compound [Zn]=O XLOMVQKBTHCTTD-UHFFFAOYSA-N 0.000 description 2
- 238000004458 analytical method Methods 0.000 description 2
- 239000011230 binding agent Substances 0.000 description 2
- 230000000903 blocking effect Effects 0.000 description 2
- 238000005229 chemical vapour deposition Methods 0.000 description 2
- VNNRSPGTAMTISX-UHFFFAOYSA-N chromium nickel Chemical compound [Cr].[Ni] VNNRSPGTAMTISX-UHFFFAOYSA-N 0.000 description 2
- RDYMFSUJUZBWLH-UHFFFAOYSA-N endosulfan Chemical compound C12COS(=O)OCC2C2(Cl)C(Cl)=C(Cl)C1(Cl)C2(Cl)Cl RDYMFSUJUZBWLH-UHFFFAOYSA-N 0.000 description 2
- 229910052732 germanium Inorganic materials 0.000 description 2
- GNPVGFCGXDBREM-UHFFFAOYSA-N germanium atom Chemical compound [Ge] GNPVGFCGXDBREM-UHFFFAOYSA-N 0.000 description 2
- AMGQUBHHOARCQH-UHFFFAOYSA-N indium;oxotin Chemical compound [In].[Sn]=O AMGQUBHHOARCQH-UHFFFAOYSA-N 0.000 description 2
- 150000002739 metals Chemical class 0.000 description 2
- 238000012986 modification Methods 0.000 description 2
- 230000004048 modification Effects 0.000 description 2
- 229910001120 nichrome Inorganic materials 0.000 description 2
- 230000035699 permeability Effects 0.000 description 2
- 229910052710 silicon Inorganic materials 0.000 description 2
- 239000010703 silicon Substances 0.000 description 2
- 229910000679 solder Inorganic materials 0.000 description 2
- MZLGASXMSKOWSE-UHFFFAOYSA-N tantalum nitride Chemical compound [Ta]#N MZLGASXMSKOWSE-UHFFFAOYSA-N 0.000 description 2
- WFKWXMTUELFFGS-UHFFFAOYSA-N tungsten Chemical compound [W] WFKWXMTUELFFGS-UHFFFAOYSA-N 0.000 description 2
- 229910052721 tungsten Inorganic materials 0.000 description 2
- 239000010937 tungsten Substances 0.000 description 2
- WURBVZBTWMNKQT-UHFFFAOYSA-N 1-(4-chlorophenoxy)-3,3-dimethyl-1-(1,2,4-triazol-1-yl)butan-2-one Chemical compound C1=NC=NN1C(C(=O)C(C)(C)C)OC1=CC=C(Cl)C=C1 WURBVZBTWMNKQT-UHFFFAOYSA-N 0.000 description 1
- JBRZTFJDHDCESZ-UHFFFAOYSA-N AsGa Chemical compound [As]#[Ga] JBRZTFJDHDCESZ-UHFFFAOYSA-N 0.000 description 1
- YCKRFDGAMUMZLT-UHFFFAOYSA-N Fluorine atom Chemical compound [F] YCKRFDGAMUMZLT-UHFFFAOYSA-N 0.000 description 1
- GYHNNYVSQQEPJS-UHFFFAOYSA-N Gallium Chemical compound [Ga] GYHNNYVSQQEPJS-UHFFFAOYSA-N 0.000 description 1
- 229920000106 Liquid crystal polymer Polymers 0.000 description 1
- 239000004977 Liquid-crystal polymers (LCPs) Substances 0.000 description 1
- 229910004121 SrRuO Inorganic materials 0.000 description 1
- HCHKCACWOHOZIP-UHFFFAOYSA-N Zinc Chemical compound [Zn] HCHKCACWOHOZIP-UHFFFAOYSA-N 0.000 description 1
- 230000000052 comparative effect Effects 0.000 description 1
- PMHQVHHXPFUNSP-UHFFFAOYSA-M copper(1+);methylsulfanylmethane;bromide Chemical compound Br[Cu].CSC PMHQVHHXPFUNSP-UHFFFAOYSA-M 0.000 description 1
- 229910052878 cordierite Inorganic materials 0.000 description 1
- 238000005520 cutting process Methods 0.000 description 1
- 230000003247 decreasing effect Effects 0.000 description 1
- JSKIRARMQDRGJZ-UHFFFAOYSA-N dimagnesium dioxido-bis[(1-oxido-3-oxo-2,4,6,8,9-pentaoxa-1,3-disila-5,7-dialuminabicyclo[3.3.1]nonan-7-yl)oxy]silane Chemical compound [Mg++].[Mg++].[O-][Si]([O-])(O[Al]1O[Al]2O[Si](=O)O[Si]([O-])(O1)O2)O[Al]1O[Al]2O[Si](=O)O[Si]([O-])(O1)O2 JSKIRARMQDRGJZ-UHFFFAOYSA-N 0.000 description 1
- HTXDPTMKBJXEOW-UHFFFAOYSA-N dioxoiridium Chemical compound O=[Ir]=O HTXDPTMKBJXEOW-UHFFFAOYSA-N 0.000 description 1
- 238000006073 displacement reaction Methods 0.000 description 1
- 238000001312 dry etching Methods 0.000 description 1
- 239000003822 epoxy resin Substances 0.000 description 1
- 230000005669 field effect Effects 0.000 description 1
- 229910052731 fluorine Inorganic materials 0.000 description 1
- 239000011737 fluorine Substances 0.000 description 1
- 229910052839 forsterite Inorganic materials 0.000 description 1
- 229910052733 gallium Inorganic materials 0.000 description 1
- 230000012447 hatching Effects 0.000 description 1
- 229910000457 iridium oxide Inorganic materials 0.000 description 1
- 230000001788 irregular Effects 0.000 description 1
- HCWCAKKEBCNQJP-UHFFFAOYSA-N magnesium orthosilicate Chemical compound [Mg+2].[Mg+2].[O-][Si]([O-])([O-])[O-] HCWCAKKEBCNQJP-UHFFFAOYSA-N 0.000 description 1
- 239000000395 magnesium oxide Substances 0.000 description 1
- 230000002093 peripheral effect Effects 0.000 description 1
- 238000001020 plasma etching Methods 0.000 description 1
- 229920000647 polyepoxide Polymers 0.000 description 1
- 239000010453 quartz Substances 0.000 description 1
- 229910052705 radium Inorganic materials 0.000 description 1
- HCWPIIXVSYCSAN-UHFFFAOYSA-N radium atom Chemical compound [Ra] HCWPIIXVSYCSAN-UHFFFAOYSA-N 0.000 description 1
- 239000010980 sapphire Substances 0.000 description 1
- 229910052594 sapphire Inorganic materials 0.000 description 1
- 239000007787 solid Substances 0.000 description 1
- 239000011343 solid material Substances 0.000 description 1
- 238000004544 sputter deposition Methods 0.000 description 1
- XOLBLPGZBRYERU-UHFFFAOYSA-N tin dioxide Chemical compound O=[Sn]=O XOLBLPGZBRYERU-UHFFFAOYSA-N 0.000 description 1
- 229910001887 tin oxide Inorganic materials 0.000 description 1
- 238000012546 transfer Methods 0.000 description 1
- 238000001771 vacuum deposition Methods 0.000 description 1
- 238000001039 wet etching Methods 0.000 description 1
- 229910052725 zinc Inorganic materials 0.000 description 1
- 239000011787 zinc oxide Substances 0.000 description 1
- 229910052726 zirconium Inorganic materials 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P1/00—Auxiliary devices
- H01P1/18—Phase-shifters
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
- G01S7/03—Details of HF subsystems specially adapted therefor, e.g. common to transmitter and receiver
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P3/00—Waveguides; Transmission lines of the waveguide type
- H01P3/16—Dielectric waveguides, i.e. without a longitudinal conductor
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P3/00—Waveguides; Transmission lines of the waveguide type
- H01P3/16—Dielectric waveguides, i.e. without a longitudinal conductor
- H01P3/165—Non-radiating dielectric waveguides
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
- Y10T—TECHNICAL SUBJECTS COVERED BY FORMER US CLASSIFICATION
- Y10T29/00—Metal working
- Y10T29/49—Method of mechanical manufacture
- Y10T29/49002—Electrical device making
- Y10T29/49117—Conductor or circuit manufacturing
- Y10T29/49124—On flat or curved insulated base, e.g., printed circuit, etc.
- Y10T29/49155—Manufacturing circuit on or in base
Definitions
- Dielectric waveguide device including the same, high-frequency switch and attenuator, and high-frequency transmitter, high-frequency receiver, high-frequency transceiver and radar device, array antenna device, and method for manufacturing dielectric waveguide device
- the present invention relates to a dielectric waveguide device used in a high frequency band such as a microwave, a quasi-millimeter wave band, and a millimeter wave band, a phase shifter that controls the phase of an electromagnetic wave in the high frequency band, a high frequency switch, and
- the present invention relates to an attenuator, and a high frequency transmitter, a high frequency receiver, a high frequency transmitter / receiver radar device, an array antenna device, and a dielectric waveguide device manufacturing method.
- phase shifter that is one of the first conventional dielectric waveguide devices
- a coplanar waveguide is formed on a ferroelectric thin film, and a voltage is applied to the ferroelectric thin film. Therefore, the phase of the electromagnetic wave is changed (see, for example, JP 2003-508942)
- a ferroelectric material is loaded in the phase shifter, which is one of the dielectric waveguide devices of the second prior art. It has a parallel plate structure (for example, M. Cohn and AF Eikenberg, "Ferro electric Phase Shifters for VHF and UHF," IRE Trans, on Microwave Theory and Techniciques, Vol. MTT-10, pp. 536-548 ( 1962)).
- the phase is controlled by controlling the dielectric constant of a part of the dielectric of the non-radiative dielectric line (see, for example, the publication of JP-A-8-102604). ).
- the use of a dielectric having a variable dielectric constant in the dielectric waveguide has attempted to obtain a phase change.
- the thickness of the dielectric waveguide has increased. For example, a voltage as high as 4000V must be applied. There is a problem.
- the conventional technology has a problem that it is difficult to realize a small dielectric waveguide device that operates at a low voltage by using a dielectric whose dielectric constant varies depending on the magnitude of an applied electric field. .
- an object of the present invention is to provide a dielectric waveguide device that is small and operates at a low voltage, a phase shifter including the dielectric waveguide device, a high-frequency switch and an attenuator, and a high-frequency transmitter, a high-frequency receiver, a high-frequency transceiver, A radar device, an array antenna device, and a dielectric waveguide device manufacturing method are provided.
- the dielectric waveguide device of the present invention has a dielectric part including a change part in which at least one of the dielectric constant and dimensions changes according to an applied electric field, and a transmission line that propagates electromagnetic waves,
- It is formed thinner than the skin thickness with respect to the frequency of the electromagnetic wave propagating through the transmission line, and includes an electrode embedded in the dielectric part and for applying an electric field to the change part.
- the present invention it is possible to change at least one of the dielectric constant and the dimension of the change portion by applying an electric field to the change portion by the electrode, and thereby, for example, an electromagnetic wave propagating through the transmission line.
- the transmission line has a cutoff characteristic, the cutoff frequency can be changed or the electromagnetic wave propagating through the transmission line can be attenuated.
- the dimension of the changing portion changes, the dimension mainly changes in the voltage application direction, that is, the thickness changes in the voltage application direction.
- the electrode is embedded in the dielectric portion and is formed thinner than the skin thickness with respect to the frequency of the electromagnetic wave propagating through the transmission line.
- the electromagnetic wave propagating through the transmission path can pass through the electrode, so that the electromagnetic wave is not cut off.
- An electric field having a large electric field strength can be applied to the changed part by the electrode in a state in which transmission loss due to the embedding of the electrode is suppressed, and at least the dielectric constant and dimensions of the changed part are shifted.
- the electric power applied to the electrode to apply an electric field to the changing part Even if the pressure is reduced, an electric field with a large electric field strength is given to the changing part, and even if the transmission line length is short, an electric field with a large electric field strength is given to the changing part.
- Dielectric waveguide devices such as phase shifters, high frequency switches and attenuators that can be operated can be realized.
- the dielectric part is provided so as to sandwich the change part, and has a lower dielectric constant than the change part, and includes a second dielectric part,
- the transmission line is a pair of flat plate conductors that sandwich the dielectric part in a direction perpendicular to the lamination direction of the change part and the second dielectric part and the propagation direction of the electromagnetic wave propagating through the transmission line.
- the electrode is provided between the changing portion and the second dielectric portion.
- the transmission line includes an H guide and an NRD guide. Since the electrode is provided between the changing portion and the second dielectric portion, an electric field can be effectively applied to the changing portion, and even if applied to these transmission lines, the waveguide mode of electromagnetic waves is affected. None give.
- the second dielectric portion functions as a support member that supports the flat conductor portion
- the flat conductor portion can be manufactured using a thin film forming technique, a thick film printing technique, a sheet-like ceramic technique, or the like.
- a dielectric waveguide device suitable for miniaturization in manufacturing it is possible to realize a dielectric waveguide device suitable for miniaturization in manufacturing.
- the second dielectric part is the most of the changing parts when the electric field is applied to the changing part and when the electric field is applied to the changing part!
- the dielectric constant is low, lower than the dielectric constant of the part!
- the dielectric constant is higher than that of air, and the dielectric constant is higher than that of air.
- the dielectric waveguide device is embedded in the change portion, and is perpendicular to the stacking direction of the change portion and the flat conductor portion and the propagation direction of the electromagnetic wave propagating through the transmission line.
- the transmission line has a pair of flat conductor portions sandwiching the dielectric portion, and the electrodes adjacent to each other are connected to different flat conductor portions of the pair of flat conductor portions. It is a characteristic.
- the transmission line includes an H guide and an NRD guide. Since the electrode is embedded in the changing portion, an electric field can be effectively applied to the changing portion, and by increasing the distance between the electrodes, a larger electric field strength can be given to the changing portion. A small dielectric waveguide device that operates at a low voltage can be realized.
- the electrodes adjacent to each other are connected to different plate conductors of the pair of plate conductors, applying a voltage to the pair of plate conductors causes a potential difference between the adjacent electrodes, An electric field can be applied to the changing portion. Even if a large number of electrodes are formed, it is possible to apply a voltage to the electrodes adjacent to each other simply by applying a voltage to the flat plate conductor, and to individually form a wiring for applying a voltage to each electrode. There is no need.
- the dielectric part has a dielectric constant lower than that of the change part, the stacking direction of the change part and the plate conductor part, and the transmission line And a second dielectric part sandwiching the change part in a direction perpendicular to the propagation direction of the electromagnetic wave propagating through the electromagnetic wave.
- the second dielectric portion functions as a support member that supports the flat conductor portion
- the flat conductor portion is manufactured using a thin film forming technique, a thick film printing technique, a sheet-like ceramic technique, or the like. Therefore, it is possible to realize a dielectric waveguide device suitable for miniaturization in manufacturing.
- the second dielectric portion has the lowest dielectric constant among the changing portions when an electric field is applied to the changing portion and when the electric field is applied to the changing portion and when no electric field is applied. Since it is made of a dielectric material having a dielectric constant lower than that of the part and having a dielectric constant higher than that of air, the wavelength of the propagating electromagnetic wave can be further reduced.
- the dielectric waveguide device can be miniaturized.
- the dielectric waveguide device of the present invention is characterized in that the distance between the pair of flat plate conductor portions is selected to be equal to or less than half of the wavelength of the electromagnetic wave propagating in the second dielectric portion. To do.
- the transmission line constitutes a non-radiative dielectric line (NRD guide)
- NORD guide non-radiative dielectric line
- radiation of electromagnetic waves to the outside is suppressed from the region sandwiched between the pair of flat conductor portions, and the transmission line Insertion loss when a phase shifter is inserted can be reduced.
- a dielectric waveguide device can be realized that can effectively apply an electric field to the dielectric part with little loss to the LSE mode high-frequency signal propagating to the dielectric part.
- the dielectric waveguide device of the present invention includes a changing portion in which at least one of a dielectric constant and a dimension changes in accordance with an applied electric field, and an electric field is applied to the changing portion through which the electromagnetic wave propagates. And a conductor part that surrounds the dielectric part and forms a waveguide.
- the phase of the electromagnetic wave propagating through the dielectric portion can be changed according to the voltage applied to the pair of electrodes.
- the dimensions mainly change in the voltage application direction, that is, the thickness changes in the voltage application direction.
- a conductor part including a pair of electrodes surrounds the dielectric part, forms a waveguide, and a transmission line having a cutoff characteristic by the conductor part and the dielectric part, that is, having a cutoff frequency. It is formed.
- the conductor portion may be formed with a predetermined distance around the axis to form the waveguide. Since the conductor part forming the waveguide includes a pair of electrodes
- the electric field applied to the dielectric constant changing part can be controlled stably even if the frequency of the electromagnetic wave propagating through the dielectric part is selected to be close to the cutoff frequency. Therefore, it is possible to operate stably near the cutoff frequency. As a result, the frequency of the electromagnetic wave propagating through the dielectric part can be selected to be close to the cutoff frequency, and a large phase change can be obtained even near a short line length near the cutoff frequency. If used as a phase shifter, the phase shifter can be formed in a small size.
- the dimension of the cross section perpendicular to the propagation direction of the electromagnetic wave in the dielectric part is also reduced, and the distance between the pair of electrodes is reduced.
- a large electric field can be applied to the dielectric part at a low voltage, and it is small and stable with a large phase change at a low voltage.
- An obtainable dielectric waveguide device can be realized.
- the dielectric waveguide device of the present invention includes a first dielectric part including a change part in which at least one of the dielectric constant and the dimension changes according to the applied electric field, and the dielectric constant is the first dielectric part.
- a pair of electrodes for applying an electric field to the change portion provided in the stacking direction with a gap smaller than the gap between the pair of flat plate conductor portions and sandwiching the dielectric portion; It is characterized by including.
- a transmission line having a cutoff characteristic that is, having a cutoff frequency is formed by the first dielectric part and the pair of flat conductor parts.
- the change part included in the first dielectric part changes at least one of the dielectric constant and the dimension according to the magnitude of the applied electric field, that is, according to the voltage applied to the pair of electrodes.
- the phase of the electromagnetic wave propagating through the dielectric part can be changed.
- the dimensions change, the dimensions mainly change in the voltage application direction, that is, the thickness changes in the voltage application direction.
- the electromagnetic wave propagates mainly through the first dielectric part sandwiched between the pair of flat conductor parts and the second dielectric part.
- the influence of the change of the dielectric part of the change part on the change of the phase of the electromagnetic wave should be increased, and the line length for obtaining the required phase change should be shortened. And the phase shifter can be formed in a small size.
- the pair of electrodes sandwich the dielectric portion in the stacking direction, an electric field can be applied to the changing portion by applying a voltage to the pair of electrodes. Since the distance between the pair of electrodes is smaller than the distance between the pair of flat conductor portions, it is possible to apply a larger electric field to the changing portion than to apply the electric field to the changing portion by the pair of flat plate conductor portions. A large electric field can be applied to the change part by voltage.
- the second dielectric part having a dielectric constant smaller than the dielectric constant of the first dielectric part is interposed between the first dielectric part and the electrode, the electromagnetic wave at the electrode part is sufficiently attenuated and enters a cutoff state. It can be avoided.
- the second dielectric part has a dielectric constant lower than that of the lowest dielectric part of the first dielectric part.
- an electrode is provided and an electric field is applied to the changing portion, so that the phase shifter can be stably operated near the cutoff frequency, and thereby the frequency of the electromagnetic wave propagating through the dielectric portion can be reduced. It becomes possible to select so as to be in the vicinity of the cutoff frequency. Since the phase shift is short near the cutoff frequency and a large phase change can be obtained even with the line length, the phase shifter can be formed in a small size.
- the frequency of the electromagnetic wave propagating through the dielectric part so that it is close to the force cutoff frequency, the dimension of the cross section perpendicular to the propagation direction of the electromagnetic wave in the dielectric part is also reduced, and the distance between the pair of electrodes approaches. Therefore, a large electric field can be applied to the dielectric portion at a low voltage, and a small phase shifter capable of stably obtaining a large phase change at a low voltage can be realized.
- the distance between the pair of flat plate conductor portions is selected to be less than or equal to half the wavelength of the electromagnetic wave propagating in the second dielectric portion. To do.
- the nonradiative dielectric line is formed by the dielectric portion and the flat conductor portion.
- the phase shifter of the present invention comprises the dielectric waveguide device or the dielectric waveguide device,
- the phase of the electromagnetic wave propagating through the transmission line is changed by changing at least one of a dielectric constant and a dimension of the changing part according to an electric field applied to the changing part.
- the present invention even if the voltage applied to the electrode to apply the electric field to the changing portion is reduced, an electric field having a large electric field strength is given to the changing portion, and even if the transmission line length is short, the transmission portion is Since the phase change can be obtained, it is possible to realize a small phase shifter that can be operated at a low voltage. In addition, since there is no mechanical drive part, a highly reliable and highly reliable phase shifter can be realized.
- phase shifter of the present invention when a predetermined frequency is applied to the pair of electrodes, fc is a cutoff frequency, and f is a frequency of an electromagnetic wave propagating through the dielectric waveguide, fc and f Is selected to satisfy 1.03 ⁇ f / fc ⁇ l.5.
- the phase shifter since it is used near the cutoff frequency where the phase change is large, a large phase change can be obtained even with a short line length, and the phase shifter can be made compact. At the same time, since the cross-sectional dimension of the dielectric portion in the direction perpendicular to the propagation direction of the electromagnetic wave is reduced, the pair of electrodes can be brought close to each other, and a large electric field strength can be obtained with a small voltage.
- the phase shifter can be operated at a low voltage.
- the high frequency switch of the present invention comprises the dielectric waveguide device
- the transmission line has a cutoff characteristic
- the cut-off frequency force in the transmission line becomes lower than the frequency of the electromagnetic wave propagating through the transmission line by changing at least one of the dielectric constant and the dimension of the changing part according to the electric field applied to the changing part. It is characterized by being able to switch between the propagation state and the higher cutoff state.
- the propagation state and the cutoff state can be easily switched by changing the voltage applied to the electrode.
- the switching mode is in the OFF state
- the cutoff state is entered, so that an essentially high ONZOFF ratio can be obtained.
- a highly reliable high-frequency switch with excellent durability can be realized. Even if the voltage applied to the electrode is reduced to apply an electric field to the changing part, an electric field with a large electric field strength is given to the changing part, and even if the transmission line length is short, the cutoff state realizes the OFF state. Therefore, a high ONZOFF ratio can be obtained, so that a high-frequency switch that can be operated at a low voltage with a small size can be realized. In addition, since there is no mechanical drive part, it is possible to realize a highly reliable V and high frequency switch with excellent durability.
- the attenuator of the present invention comprises a dielectric waveguide device
- the electromagnetic wave propagating through the transmission line is attenuated by changing at least one of a dielectric constant and a dimension of the changing part according to an electric field applied to the changing part.
- an electric field having a large electric field strength is given to the changing portion, and attenuation near the cutoff frequency is used.
- Sufficient attenuation can be obtained even if the length of the transmission line is short, so that an attenuator that is small and can be operated at a low voltage can be realized.
- since there is no mechanical drive part it is possible to realize a highly reliable attenuator with excellent durability.
- the high frequency transmitter of the present invention is a high frequency oscillator that generates a high frequency signal, a high frequency transmission line that is connected to the high frequency oscillator and transmits a high frequency signal from the high frequency transmitter,
- An antenna connected to the high-frequency transmission line and emitting a high-frequency signal
- phase shifter inserted into the high-frequency transmission line so that a high-frequency signal passes through the dielectric part
- the phase shifter is inserted so that the electromagnetic wave of the high frequency signal transmitted through the high frequency transmission line passes through the dielectric part, for example, a wire or bump for connecting a high frequency oscillator
- the phase shift caused by the high-frequency transmission line can be individually adjusted and matched due to variations in the shape of the wiring and the wiring width of the high-frequency transmission line, providing stable oscillation characteristics and insertion loss. Since it is kept small, a high-frequency transmitter with high transmission output can be realized.
- the phase shifter can be operated at a low voltage with a small size as described above, a high frequency transmitter can be formed in a small size even if a phase shifter is provided, and a voltage is applied to the phase shifter. Therefore, it is possible to suppress the complicated configuration.
- the high frequency receiver of the present invention includes an antenna that captures a high frequency signal
- a high-frequency transmission line connected to the antenna and transmitting a high-frequency signal captured by the antenna
- a high-frequency detector connected to the high-frequency transmission line and detecting a high-frequency signal transmitted to the high-frequency transmission line;
- the phase shifter inserted into the high-frequency transmission line so that a high-frequency signal passes through the dielectric part;
- the phase shifter is inserted so that the electromagnetic wave of the high frequency signal transmitted through the high frequency transmission line passes through the dielectric part, for example, a wire or bump for connecting a high frequency oscillator
- the phase shift caused by the high-frequency transmission line can be individually adjusted to achieve matching due to variations in the shape of the wiring and the wiring width of the high-frequency transmission line. Therefore, a high-frequency receiver with high detection output can be realized.
- the phase shifter can be operated at a low voltage with a small size as described above, a high frequency receiver can be formed in a small size even if a phase shifter is provided, and a voltage can be applied to the phase shifter. It is possible to suppress the complexity of the configuration for giving.
- the high-frequency transmitter / receiver of the present invention includes a high-frequency oscillator that generates a high-frequency signal, a first high-frequency transmission line that is connected to the high-frequency oscillator and transmits a high-frequency signal, and first, second, and third terminals, A branching device having a first terminal connected to the first high-frequency transmission line and selectively outputting a high-frequency signal applied to the first terminal to the second terminal or the third terminal;
- a second high-frequency transmission line connected to the second terminal and transmitting a high-frequency signal applied from the second terminal;
- a high-frequency signal having fourth, fifth and sixth terminals which outputs a high-frequency signal given to the fourth terminal via the second high-frequency transmission line to the fifth terminal and given to the fifth terminal
- a duplexer that outputs to the sixth terminal
- a third high-frequency transmission line connected to the fifth terminal, transmitting a high-frequency signal output from the fifth terminal, and transmitting a high-frequency signal to the fifth terminal;
- An antenna connected to the third high-frequency transmission line for radiating and capturing high-frequency signals
- a fourth terminal connected to the third terminal and transmitting a high-frequency signal output from the third terminal;
- a fifth high-frequency transmission line connected to the sixth terminal and transmitting a high-frequency signal output from the sixth terminal;
- a mixer connected to the fourth and fifth high-frequency transmission lines, for mixing the high-frequency signals applied to the fourth and fifth high-frequency transmission lines, and outputting an intermediate frequency signal; and the high-frequency signal passes through the dielectric portion
- the phase shifter is inserted into at least one of the first to fifth high-frequency transmission lines.
- Adjusts the phase of the undesired high-frequency signal due to the high-frequency transmission line for example, to realize a high-frequency transmitter / receiver with stable oscillation characteristics and high transmission output due to low insertion loss
- a high-frequency transmitter / receiver having a stable detection characteristic and a high detection output because the insertion loss force is suppressed, and an intermediate signal generated by a mixer, for example.
- the reliability of the frequency signal can be improved. Since the phase shifter is small and can be operated at a low voltage as described above, a high frequency transmitter / receiver can be formed in a small size even if a phase shifter is provided. It is possible to prevent the configuration for applying the voltage from becoming complicated.
- the high frequency transmitter of the present invention includes a high frequency oscillator that generates a high frequency signal, a high frequency transmission line that is connected to the high frequency oscillator and transmits a high frequency signal from the high frequency oscillator,
- An antenna connected to the high-frequency transmission line and emitting a high-frequency signal
- the high-frequency signal inserted into the high-frequency transmission line and transmitting the high-frequency signal transmitted to the high-frequency transmission line by setting the propagation state, and the high-frequency signal transmitted to the high-frequency transmission line by setting the cutoff state Including the high-frequency switch for blocking.
- the high frequency switch when the high frequency switch is in a propagation state, the high frequency signal generated by the high frequency oscillator is transmitted through the high frequency switch, so that the antenna is transmitted through the high frequency transmission line. Given to Na and radiated as radio waves.
- the high frequency switch when the high frequency switch is in the cut-off state, the high frequency signal generated by the high frequency oscillator does not pass through the high frequency switch, so that the antenna force is not radiated.
- a pulse signal wave can be radiated from the antenna.
- a large ONZO FF ratio can be obtained, and a highly reliable high frequency transmitter can be realized by using a highly reliable high frequency switch with excellent durability.
- the high-frequency transmitter / receiver of the present invention includes a high-frequency oscillator that generates a high-frequency signal, a first high-frequency transmission line that is connected to the high-frequency oscillator and transmits a high-frequency signal, and first, second, and third terminals, A branching device having a first terminal connected to the first high-frequency transmission line and selectively outputting a high-frequency signal applied to the first terminal to the second terminal or the third terminal;
- a second high-frequency transmission line connected to the second terminal and transmitting a high-frequency signal applied from the second terminal;
- a high-frequency signal having fourth, fifth and sixth terminals which outputs a high-frequency signal given to the fourth terminal via the second high-frequency transmission line to the fifth terminal and given to the fifth terminal
- a duplexer that outputs to the sixth terminal
- a third high-frequency transmission line connected to the fifth terminal, transmitting a high-frequency signal output from the fifth terminal, and transmitting a high-frequency signal to the fifth terminal;
- An antenna connected to the third high-frequency transmission line for radiating and capturing high-frequency signals
- a fourth high-frequency transmission line connected to the third terminal and transmitting a high-frequency signal output from the third terminal;
- a fifth high-frequency transmission line connected to the sixth terminal and transmitting a high-frequency signal output from the sixth terminal;
- a mixer connected to the fourth and fifth high-frequency transmission lines and mixing the high-frequency signals applied to the fourth and fifth high-frequency transmission lines and outputting an intermediate frequency signal.
- the duplexer includes the high-frequency switch. And the third high-frequency switch By setting the state, the high frequency signal is transmitted between the fourth terminal and the fifth terminal, and by setting the cutoff state, the high frequency signal is blocked between the fourth terminal and the fifth terminal, (4)
- the high frequency switch transmits the high frequency signal between the fifth terminal and the sixth terminal by setting the propagation state, and between the fifth terminal and the sixth terminal by setting the cutoff state. It is characterized by blocking high-frequency signals.
- the branching device includes the two high-frequency switches, and the first high-frequency switch transmits the high-frequency signal between the first terminal and the second terminal by being in the propagation state, and is in the cut-off state. Accordingly, the high-frequency signal is blocked between the first terminal and the second terminal, and the second high-frequency switch transmits the high-frequency signal between the first terminal and the third terminal by being in the propagation state. In addition, the high-frequency signal is cut off between the first terminal and the third terminal by setting the cut-off state. When the first high-frequency switch is in the propagation state, the second high-frequency switch is in the cut-off state, and when the first high-frequency switch is in the cut-off state, the second high-frequency switch is in the propagation state.
- the second and third terminal forces can be selectively output from the high-frequency signal input from.
- a large ONZOFF ratio can be obtained, and a highly reliable and high-frequency transmitter / receiver can be realized by configuring a branching unit using a highly reliable V ⁇ high-frequency switch with excellent durability. .
- the high-frequency transmitter / receiver of the present invention includes a high-frequency oscillator that generates a high-frequency signal, a first high-frequency transmission line that is connected to the high-frequency oscillator and transmits a high-frequency signal, and first, second, and third terminals, A branching device having a first terminal connected to the first high-frequency transmission line and selectively outputting a high-frequency signal applied to the first terminal to the second terminal or the third terminal;
- a second high-frequency transmission line connected to the second terminal and transmitting a high-frequency signal applied from the second terminal;
- a high-frequency signal having fourth, fifth and sixth terminals which outputs a high-frequency signal given to the fourth terminal via the second high-frequency transmission line to the fifth terminal and given to the fifth terminal
- a duplexer that outputs to the sixth terminal,
- a third high-frequency transmission line connected to the fifth terminal, transmitting a high-frequency signal output from the fifth terminal, and transmitting a high-frequency signal to the fifth terminal;
- An antenna connected to the third high-frequency transmission line for radiating and capturing high-frequency signals
- a fourth high-frequency transmission line connected to the third terminal and transmitting a high-frequency signal output from the third terminal;
- a fifth high-frequency transmission line connected to the sixth terminal and transmitting a high-frequency signal output from the sixth terminal;
- a mixer connected to the fourth and fifth high-frequency transmission lines and mixing the high-frequency signals applied to the fourth and fifth high-frequency transmission lines and outputting an intermediate frequency signal.
- the duplexer includes the high-frequency switch.
- the third high-frequency switch transmits the high-frequency signal between the fourth terminal and the fifth terminal by setting the propagation state, and the fourth terminal and the The high-frequency signal is blocked between the fifth terminals, and the fourth high-frequency switch transmits the high-frequency signal between the fifth terminal and the sixth terminal by setting the propagation state, and sets the cutoff state. The high frequency signal is cut off between the fifth terminal and the sixth terminal.
- the duplexer includes the two high-frequency switches, and the third high-frequency switch transmits the high-frequency signal between the fourth terminal and the fifth terminal by setting the propagation state.
- the high-frequency signal is cut off between the fourth terminal and the fifth terminal by setting the cut-off state, and the fourth high-frequency switch has the fifth terminal and the sixth sixth switch by setting the propagation state.
- a high-frequency signal is transmitted between the terminals, and the high-frequency signal is blocked between the fifth terminal and the sixth terminal by setting the cut-off state.
- the fourth high-frequency switch When the third high-frequency switch is in the propagation state, the fourth high-frequency switch is in the cutoff state, and when the third high-frequency switch force S is in the cutoff state, the fourth high-frequency switch is in the propagation state, so that the fourth terminal
- the high frequency signal input from the fifth terminal can be output from the fifth terminal, and the high frequency signal input from the fifth terminal force can be output to the sixth terminal. Big ONZ An OFF ratio can be obtained, and a highly reliable high-frequency transmitter / receiver can be realized by configuring a branching device using a highly reliable high-frequency switch with excellent durability.
- the high-frequency transmitter / receiver of the present invention includes a high-frequency oscillator that generates a high-frequency signal, a first high-frequency transmission line that is connected to the high-frequency oscillator and transmits a high-frequency signal, and first, second, and third terminals, A branching device having a first terminal connected to the first high-frequency transmission line and selectively outputting a high-frequency signal applied to the first terminal to the second terminal or the third terminal;
- a second high-frequency transmission line connected to the second terminal and transmitting a high-frequency signal applied from the second terminal;
- a high-frequency signal having fourth, fifth and sixth terminals which outputs a high-frequency signal given to the fourth terminal via the second high-frequency transmission line to the fifth terminal and given to the fifth terminal
- a duplexer that outputs to the sixth terminal
- a third high-frequency transmission line connected to the fifth terminal, transmitting a high-frequency signal output from the fifth terminal, and transmitting a high-frequency signal to the fifth terminal;
- An antenna connected to the third high-frequency transmission line for radiating and capturing high-frequency signals
- a fourth high-frequency transmission line connected to the third terminal and transmitting a high-frequency signal output from the third terminal;
- a fifth high-frequency transmission line connected to the sixth terminal and transmitting a high-frequency signal output from the sixth terminal;
- a mixer that is connected to the fourth and fifth high-frequency transmission lines, mixes the high-frequency signals applied to the fourth and fifth high-frequency transmission lines, and outputs an intermediate frequency signal;
- the high-frequency switch inserted into at least one of the first to third transmission lines so as to pass through the dielectric part.
- the high frequency oscillator is generated by setting all of the high frequency switches inserted into at least one of the first to third high frequency transmission lines to a propagation state.
- the high frequency signal transmitted to the first high frequency transmission line is applied to the first terminal of the branching device, the second terminal force of the branching device is applied to the second high frequency transmission line, and is applied to the fourth terminal of the branching filter.
- the fifth terminal force of the duplexer is applied to the third high-frequency transmission line and radiated as an antenna force.
- the high-frequency signal generated by the high-frequency oscillator does not pass through the high-frequency switch and is blocked.
- the high-frequency signal received by the antenna is given to the third high-frequency transmission line, given to the fifth terminal of the duplexer, given from the sixth terminal of the duplexer to the fifth high-frequency transmission line, and sent to the mixer.
- the mixer receives the high-frequency signal generated by the high-frequency oscillator from the third terminal of the branching device via the fourth high-frequency transmission line as a local signal.
- the mixer mixes the high-frequency signal generated by the high-frequency oscillator and the high-frequency signal received by the antenna, and outputs an intermediate frequency signal, thereby obtaining information contained in the received high-frequency signal.
- the high-frequency transmitter / receiver of the present invention includes a high-frequency oscillator that generates a high-frequency signal, a first high-frequency transmission line that is connected to the high-frequency oscillator and transmits a high-frequency signal, and first, second, and third terminals, A branching device having a first terminal connected to the first high-frequency transmission line and selectively outputting a high-frequency signal applied to the first terminal to the second terminal or the third terminal;
- a second high-frequency transmission line connected to the second terminal and transmitting a high-frequency signal applied from the second terminal;
- a high-frequency signal having fourth, fifth and sixth terminals which outputs a high-frequency signal given to the fourth terminal via the second high-frequency transmission line to the fifth terminal and given to the fifth terminal
- a duplexer that outputs to the sixth terminal
- a third high-frequency transmission line connected to the fifth terminal, transmitting a high-frequency signal output from the fifth terminal, and transmitting a high-frequency signal to the fifth terminal;
- An antenna connected to the third high-frequency transmission line for radiating and capturing high-frequency signals;
- a fourth high-frequency transmission line connected to the third terminal and transmitting a high-frequency signal output from the third terminal;
- a fifth high-frequency transmission line connected to the sixth terminal and transmitting a high-frequency signal output from the sixth terminal;
- a mixer connected to the fourth and fifth high-frequency transmission lines, for mixing the high-frequency signals applied to the fourth and fifth high-frequency transmission lines, and outputting an intermediate frequency signal; and the high-frequency signal passes through the dielectric portion
- the attenuator is inserted into at least one of the first to fifth high-frequency transmission lines.
- the attenuator is inserted into at least one of the first to fifth high-frequency transmission lines so that a high-frequency signal passes through the dielectric part.
- amplitude modulation can be performed by changing the amplitude of the high-frequency signal.
- a small and stable high-frequency transmitter / receiver can be realized. Since the attenuator is small and can be operated at a low voltage as described above, a high-frequency transmitter / receiver can be made small even if an attenuator is provided, and a configuration for applying voltage to the attenuator. Can be prevented from becoming complicated.
- the duplexer is formed by a hybrid circuit or a circulator.
- the duplexer may be formed by a hybrid circuit or a circulator.
- the hybrid circuit is a directional coupler that can be realized by Magic T, hybrid ring or rat race.
- the radar apparatus of the present invention includes the high frequency transmitter / receiver,
- a distance detector for detecting a distance from the high-frequency transmitter / receiver to the detection object based on the intermediate frequency signal from the high-frequency transmitter / receiver.
- the radar apparatus since the distance detector detects the distance from the high frequency transmitter / receiver to the detection object based on the intermediate frequency signal from the high frequency transmitter / receiver, The radar apparatus can accurately detect the distance to the object.
- the array antenna apparatus of the present invention is characterized in that a plurality of antennas with phase shifters each having an antenna element and the phase shifter are arranged side by side.
- the phase of the high frequency signal supplied to the antenna element is shifted by the phase shifter added to each antenna element, thereby adjusting the phase of the radio wave radiated by each antenna element force and
- the beam can be tilted in a predetermined direction from the front of the array antenna. Since the phase shifter is small and can be operated at a low voltage, the array antenna device does not increase in size. Further, the array antenna apparatus can change the direction of the radiation beam as described above by providing the phase shifter, and thereby, the direction of the radiation beam without mechanically operating the antenna element can be changed. It can be changed and convenience can be improved.
- the radar apparatus of the present invention includes the array antenna apparatus,
- a high-frequency transmitter / receiver connected to the array antenna device, for supplying a high-frequency signal to the array antenna device and for receiving a high-frequency signal captured by the array antenna device.
- a method of manufacturing a waveguide device includes a step of forming a first dielectric film made of a dielectric material having a predetermined dielectric constant, laminated on a substrate,
- the first dielectric film, the stacked body, and the third dielectric film are etched to form a front end from a first end face of a pair of end faces facing each other in a direction perpendicular to the stacking direction.
- the electrode film formed near the first direction in the predetermined direction is exposed, and formed from the second end face of the pair of end faces facing each other toward the second direction in the predetermined direction. Forming a protrusion from which the electrode film is exposed;
- the above-described phase shifter in which the even-numbered electrode film and the odd-numbered electrode film in the stacking direction are connected to different flat plate conductor portions in the stacking direction is implemented. Can appear.
- the stacked electrode films can be accurately and reliably drawn out to the first and second end faces, and the manufacturing method is suitable for semiconductor processes that have been used in the past.
- a stable dielectric waveguide device can be manufactured with high productivity. Dielectric waveguide devices include phase shifters, high frequency switches and attenuators.
- FIG. 1 is a perspective view schematically showing a phase shifter 20 according to an embodiment of the present invention.
- FIG. 2 is a cross-sectional view schematically showing a phase shifter 30 according to another embodiment of the present invention.
- FIG. 3 is a flowchart showing the manufacturing process of the phase shifter 30.
- FIG. 4A to 4C are schematic diagrams showing the manufacturing process of the phase shifter 30.
- FIG. 4A to 4C are schematic diagrams showing the manufacturing process of the phase shifter 30.
- FIG. 5 is a plan view showing a state in which a plurality of electrode films 33 and second dielectric films 34 are stacked in step s3.
- FIG. 6 is a perspective view schematically showing a phase shifter 40 according to still another embodiment of the present invention.
- FIG. 7 schematically shows a phase shifter 50 according to still another embodiment of the present invention.
- FIG. 8 is a perspective view schematically showing a phase shifter 60 according to still another embodiment of the present invention.
- FIG. 9 is a perspective view schematically showing a phase shifter 70 according to still another embodiment of the present invention.
- FIG. 10 schematically shows a phase shifter 80 according to still another embodiment of the present invention.
- FIG. 11 is a perspective view schematically showing a phase shifter 90 according to still another embodiment of the present invention.
- FIG. 12 is a perspective view schematically showing a phase shifter 100 according to still another embodiment of the present invention.
- FIG. 13 is a perspective view schematically showing a phase shifter 110 according to still another embodiment of the present invention.
- FIG. 14 is a perspective view schematically showing a phase shifter 120 according to still another embodiment of the present invention.
- FIG. 15 is a cross-sectional view schematically showing a phase shifter 130 according to still another embodiment of the present invention.
- FIG. 16 is a graph showing the relationship between fZfc and ⁇ .
- FIG. 17 shows the relationship between fZfc and ⁇ jS Z amaxZV.
- FIG. 18 is a cross-sectional view schematically showing a phase shifter 140 according to still another embodiment of the present invention.
- FIG. 19 is a perspective view schematically showing a phase shifter 150 according to still another embodiment of the present invention.
- FIG. 20 is a perspective view schematically showing a phase shifter 160 according to still another embodiment of the present invention.
- FIG. 21 is a cross-sectional view schematically showing a phase shifter 170 according to still another embodiment of the present invention.
- FIG. 22 is a perspective view schematically showing a connection structure 230 between the phase shifter 20 and the microstrip line 231.
- Figure 23 shows a hypothesis perpendicular to the thickness direction Z, including the axis A2 along the propagation direction X of the phase shifter 20.
- 3 is a cross-sectional view of a connection structure 230 in one plane.
- FIG. 24 is a cross-sectional view of connection structure 230 in a virtual plane including axis A2 along propagation direction X of phase shifter 20 and perpendicular to width direction Y.
- FIG. 25 is a perspective view schematically showing a connection structure 250 between the phase shifter 20 and the strip line 251.
- FIG. 26 is a cross-sectional view of the connection structure 250 in a virtual plane including the axis A2 along the propagation direction X of the phase shifter 20 and perpendicular to the thickness direction Z.
- FIG. 27 is a cross-sectional view of connection structure 250 in a virtual plane including axis A2 along propagation direction X of phase shifter 20 and perpendicular to width direction Y.
- FIG. 28 is a cross-sectional view taken along section line ⁇ - ⁇ in FIG.
- FIG. 29 is a perspective view schematically showing a connection structure 330 between the phase shifter 170 and the microstrip line 231.
- FIG. 29 is a perspective view schematically showing a connection structure 330 between the phase shifter 170 and the microstrip line 231.
- FIG. 30 is a cross-sectional view of the connection structure 330 in a virtual plane including the axis A2 along the propagation direction X of the phase shifter 170 and perpendicular to the thickness direction Z.
- FIG. 31 is a cross-sectional view of connection structure 330 in a virtual plane that includes axis A2 along propagation direction X of phase shifter 170 and is perpendicular to width direction Y.
- FIG. 32 is a perspective view schematically showing a connection structure 350 between the phase shifter 170 and the strip line 251.
- FIG. 32 is a perspective view schematically showing a connection structure 350 between the phase shifter 170 and the strip line 251.
- FIG. 33 is a cross-sectional view of connection structure 350 in a virtual plane that includes axis A2 along propagation direction X of phase shifter 170 and is perpendicular to thickness direction Z.
- connection structure 350 is a cross-sectional view of connection structure 350 in a virtual plane that includes axis A2 along propagation direction X of phase shifter 170 and is perpendicular to width direction Y.
- FIG. 34 is a cross-sectional view of connection structure 350 in a virtual plane that includes axis A2 along propagation direction X of phase shifter 170 and is perpendicular to width direction Y.
- FIG. 35 is a sectional view taken along section line XII-XII in FIGS.
- FIG. 36 is a schematic diagram showing a configuration of a high-frequency transmitter 260 according to an embodiment of the present invention.
- FIG. 37 is a schematic diagram showing a configuration of a high-frequency receiver 270 according to an embodiment of the present invention.
- the radar apparatus 290 includes the high-frequency transceiver 280 according to the embodiment of the present invention. It is a schematic diagram which shows the structure of these.
- FIG. 39 is a schematic diagram showing a configuration of a radar apparatus 400 including an array antenna apparatus 399 including the phase shifter 20 according to the embodiment of the present invention.
- FIG. 40 is a schematic diagram showing a configuration of a high-frequency transmitter 360 according to another embodiment of the present invention.
- FIG. 41 is a schematic diagram showing a configuration of a radar apparatus 390 including a high-frequency transceiver 380 according to another embodiment of the present invention.
- FIG. 42 is a schematic diagram showing a configuration of a branching device 286 constituted by the switch 361.
- FIG. 43 is a schematic diagram showing a configuration of a duplexer 287 including the switch 361.
- FIG. 1 is a perspective view schematically showing a phase shifter 20 according to an embodiment of the present invention.
- the phase shifter 20 includes a dielectric portion 22, a pair of first and second plate conductor portions 23a and 23b, a pair of first and second electrodes 24a and 24b, and a voltage applying means 19. Is done.
- the phase shifter 20 according to the embodiment of the present invention is formed in a substantially rectangular parallelepiped shape.
- the cross section perpendicular to the propagation direction X of the electromagnetic wave in the phase shifter 20 has the same shape as the end face of the phase shifter 20 in the propagation direction X.
- the dielectric part 22 is made of a dielectric material,
- the first dielectric part 25 including the changing part whose rate changes and the second dielectric part 26 are configured.
- the dielectric part 22 has a first input / output terminal 22a for receiving an electromagnetic wave and a second input / output terminal 22b for outputting an electromagnetic wave.
- the first input / output end 22a and the second input / output end 22b are respectively formed on the upstream side and the downstream side in the propagation direction X along the propagation direction (line extending direction) X in which electromagnetic waves propagate.
- the dielectric portion 22 is formed in a rectangular parallelepiped shape, and the first input / output end 22a and the second input / output end 22b are formed by a plane perpendicular to the propagation direction X and face each other. Provided.
- the cross section perpendicular to the propagation direction X of the dielectric portion 22 is rectangular.
- width direction Y is the longitudinal direction of the first dielectric part 25 included in the dielectric part 22 in the cross section perpendicular to the propagation direction X.
- thickness direction Z is the short direction in the cross section perpendicular to the propagation direction X of the first dielectric part 25 included in the dielectric part 22.
- the first dielectric part 25 also has a changing part force, for example, Ba Sr
- the first dielectric portion 25 is formed in a rectangular parallelepiped shape, and is formed between both end portions in the propagation direction X of the dielectric portion 22 and between both end portions in the width direction Y.
- the second dielectric part 26 is laminated on both sides of the first dielectric part 25 with the first dielectric part 25 interposed therebetween.
- the second dielectric part 26 is formed symmetrically across the first dielectric part 25.
- the second dielectric part 26 is provided on both sides of the first dielectric part 25 in the thickness direction Z.
- the second dielectric portion 26 has a substantially rectangular parallelepiped shape.
- the second dielectric part 26 is formed of a material whose dielectric constant is lower than that of the first dielectric part 25.
- the dielectric constant of the second dielectric part 26 is selected to be less than the dielectric constant of the first dielectric part 25 when the dielectric constant of the first dielectric part 25 changes and the dielectric constant becomes the smallest.
- the second dielectric part 26 is formed of glass, single crystal, ceramics or resin.
- glass quartz glass, crystallized glass, or the like is used.
- single crystal crystal, sapphire, MgO or LaAlO is used.
- ceramics aluminum
- the second dielectric portion 26 may be formed of air, but the first dielectric portion 25 can be mechanically held and is formed of the above-described solid material having a dielectric constant higher than that of air. Is preferred.
- the electromagnetic wave propagating through the first dielectric part 22 among the parts sandwiched between the first and second flat plate conductor parts 23a and 23b.
- the wavelength in the portion excluding the first dielectric portion 25 can be shortened as compared with the wavelength in the air, whereby the phase shifter 20 can be formed in a small size.
- the first and second flat plate conductor portions 23a and 23b are mechanically supported by the second dielectric portion 26, the mechanical strength can be improved, and the first and second flat plate conductors can be improved.
- Part 23a and 23b can be manufactured using thin film formation technology, thick film printing technology, or sheet-like ceramic technology, and a phase shifter suitable for miniaturization can be realized.
- the first and second flat plate conductor portions 23a and 23b are arranged in the direction of propagation X of the electromagnetic wave in the dielectric portion 22 and the thickness direction Z that is the stacking direction of the first and second dielectric portions 25 and 26, respectively.
- the dielectric portion 22 is provided in close contact with the dielectric portion 22, that is, provided on both sides of the first and second dielectric portions 25, 26.
- the first and second flat plate conductor portions 23a and 23b have conductivity, are formed in a plate shape, and surfaces facing the dielectric portion 22 are provided in parallel to each other.
- the first and second flat plate conductor portions 23a and 23b are respectively laminated on the end face in the width direction Y of the dielectric portion 22, and are formed over the entire end face in the width direction Y.
- the first and second flat plate conductor portions 23a and 23b are formed of a low resistivity metal, a metal that can be fired simultaneously with the dielectric portion 22 at a high temperature, solder, or a conductive paste.
- Low V ⁇ resistivity metals include gold (Au), copper (Cu), aluminum (A1), platinum (Pt), titanium (Ti), silver (Ag), palladium (Pd), zinc (Zn) and A group power that also has chrome (Cr) power is selected.
- the first and second plate conductor parts 23a, 23b are made of gold (Au), copper (Cu), aluminum (A1), platinum (Pt), titanium (Ti), silver (Ag), palladium (Pd), zinc Any one of the group forces consisting of (Zn) and chromium (Cr) may be selected, or an alloy including at least two or a laminate thereof may be used. Tungsten (W) or the like is used as the metal that can be fired simultaneously with the dielectric portion 22 at a high temperature.
- a paste containing a metal filler and a binder resin that binds the metal filler is used as the conductive paste.
- the first and second flat plate conductor portions 23a and 23b may be formed of an oxide conductor such as ITO (Indium Tin Oxide), tin oxide, iridium oxide, or SrRuO.
- a and 23b are preferably formed of a low resistivity metal.
- the thickness of the first and second flat plate conductor portions 23a and 23b, that is, the thickness in the width direction Y is selected to be larger than the skin thickness with respect to the frequency of the electromagnetic wave propagating through the dielectric portion 22.
- the distance L1 between the first and second flat plate conductor portions 23a and 23b is selected according to the wavelength of the electromagnetic wave to be propagated through the dielectric portion 22, and the wavelength of the electromagnetic wave propagating through the second dielectric portion 26. Is chosen to be less than half of By selecting the distance L1 in this way, the dielectric part 22 and the first and second plate conductor parts 23a and 23b constitute a non-radiative dielectric line (NRD guide) that is a transmission line, and the first Loss can be reduced because the electromagnetic wave propagating through the dielectric portion 25 becomes non-radiating without leaking between the first and second flat plate conductor portions 23a and 23b.
- NTD guide non-radiative dielectric line
- the first and second electrodes 24a and 24b are embedded in the dielectric portion 22.
- the first and second electrodes 24 a and 24 b are provided between the first dielectric part 25 and the second dielectric part 26.
- the first and second electrodes 24a and 24b are provided in plane symmetry with respect to a virtual plane perpendicular to the thickness direction Z.
- the first and second electrodes 24a and 24b sandwich the first dielectric part 25 and are provided on both end surfaces in the thickness direction Z of the first dielectric part 25, respectively.
- the first and second electrodes 24a and 24b are provided across both ends of the first dielectric part 25 in the propagation direction X, and are provided separately from the first and second flat plate conductor parts 23a and 23b, respectively. .
- the first and second electrodes 24a and 24b are formed in a rectangular parallelepiped shape, and are stacked on the first dielectric portion 25 except for both ends of the dielectric portion 22 in the width direction Y.
- the first and second electrodes 24 a and 24 b are electrodes for applying an electric field to the first dielectric portion 25.
- the first and second electrodes 24a and 24b are formed by the force formed by the same material as the first and second plate conductor portions 23a and 23b described above, or by silicon (Si), germanium (Ge), and ⁇ Semiconductor materials such as gallium (GaAs) or high resistance materials such as tantalum nitride and NiCr alloys.
- the thickness L3 of the first and second electrodes 24a, 24b is selected to be less than the skin thickness with respect to the frequency of the electromagnetic wave to be propagated through the first dielectric part 25.
- the skin thickness is “ ⁇ ”
- the magnetic permeability is “”
- the conductivity is “ ⁇ ”
- the angular frequency is “ ⁇ ”
- the amplitude becomes lZe at the skin thickness.
- the phase shifter 20 can be driven with a low voltage.
- First and second electrodes 24a in this embodiment, the volume resistivity of 24b is, 10 _5 ⁇ ⁇ ⁇ above, is preferably selected more than 10 _4 ⁇ ⁇ ⁇ .
- the electric charges move and become stiff in the first and second electrodes 24a and 24b, and uniform throughout the first and second electrodes 24a and 24b. Therefore, the electric field can be uniformly applied over the entire first and second electrodes 24a and 24b without hindering the movement of charges in the first and second electrodes 24a and 24b.
- Such a predetermined thickness or more is formed.
- the resistivity of the first and second electrodes 24a, 24b embedded in the second dielectric portion 22 is preferably selected to be 10 " 5 ⁇ ⁇ m or more and 10 8 ⁇ ⁇ ⁇ or less.
- First and second When the electrodes 24a, 24b of the resistivity is less than 10 _5 ⁇ ⁇ ⁇ , attenuation of electromagnetic waves in the electrode is increased, the loss is large Kunatsute undesirable.
- the first and second electrodes 24a, 24b of the resistivity of 10 If it becomes smaller than _5 ⁇ ⁇ ⁇ , the desired mode will be cut off and will not propagate, but the resistivity of the first and second electrodes 24a, 24b will be larger than 10 8 ⁇ 'm. If it becomes too large, the difference in resistivity from the dielectric sandwiched between the first and second electrodes 24a, 24b becomes small, and a desired voltage cannot be applied to the dielectric due to a voltage drop.
- the thickness of the first and second electrodes 24a and 24b is determined by the resistivity of the material used for the first and second electrodes 24a and 24b. If the thickness is too thick, the loss increases. It turns off and no longer transmits. If it is too thin, the desired voltage cannot be applied to the dielectric due to the voltage drop.
- the first and second electrodes 24a and 24b have a resistivity of 1 ⁇ 10 _4 ( ⁇ ⁇ ⁇ ) (assuming TaN is used as the material) and a resistivity of 1 X 10 _3 ( ⁇ ⁇ ⁇ ) Table 1 shows the loss due to the electrode per lmm for the 77 GHz electromagnetic wave when the electromagnetic field analysis is performed.
- the electrode thickness is practically 30 nm or less when the electrode resistivity is 1 X 10 " 4 (Qm). In the case where the resistivity of the electrode is 1 X 10 _3 ( ⁇ ⁇ ⁇ ), it is preferable to set the electrode to 320 nm or less for practical use.
- the phase shifter 20 further includes a voltage applying unit 19.
- the voltage applying means 19 is realized by an electric circuit that applies a voltage in a predetermined range between the pair of first and second electrodes 24a and 24b.
- the voltage applying means 19 is connected to the first and second electrodes 24a, 24b, applies a predetermined potential to each electrode, and applies a voltage between the first and second electrodes 24a, 24b.
- an electric field is applied to the first dielectric portion 25 sandwiched between the first and second electrodes 24a, 24b.
- the voltage applying means 19 is configured to include, for example, a voltage divider, and applies the voltage divided by the voltage divider to the first and second electrodes 24a and 24b.
- the voltage applying means 19 can apply a plurality of stages of voltages to the first and second electrodes 24a, 24b.
- the voltage applying means 19 applies an alternating voltage having a frequency lower than the frequency of the propagating electromagnetic wave or a direct voltage to the first and second electrodes 24a, 24b.
- the voltage applying means 19 applies a voltage corresponding to the phase amount to be shifted to the first and second electrodes 24a, 24b.
- the voltage application means 19 applies a voltage between the first and second electrodes 24a and 24b, and changes the magnitude of the applied voltage within a predetermined range, thereby allowing the phase of the electromagnetic wave guided through the dielectric portion 22 to vary. Can be changed according to the magnitude of the applied voltage, that is, the magnitude of the applied electric field.
- the dielectric forming the first dielectric part 25 has a lower dielectric constant when the applied electric field is increased, and this can change the phase of the electromagnetic wave guided through the dielectric part 22.
- the cut-off frequency fc of the nonradiative dielectric line formed by the dielectric part 22 and the first and second plate conductor parts 23a and 23b is the dielectric that forms the first dielectric part 25.
- the dielectric constant of the body and the size of the first dielectric part 25 (the dimension of the cross section perpendicular to the propagation direction X), the distance L4 between the first and second electrodes 24a, 24b, the distance L1 between the plate conductor parts 23a, 23b Ll
- the size of the first dielectric portion 25 is selected so that the cut-off frequency is less than the frequency of the electromagnetic wave to be propagated (use frequency).
- the cut-off frequency is fc
- the use frequency that is, the dielectric part 22 propagates.
- the frequency of the electromagnetic wave to be applied is f, 1. 03 ⁇ f / fc ⁇ 1.5, preferably 1. 03 ⁇ f / fc ⁇ l.
- the size of 5, the distance L4 between the first and second electrodes 24a, 24b, the distance L1 between the first and second flat plate conductor parts 23a, 23b, and the dielectric forming the second dielectric part 26 are set.
- the dielectric material forming the first dielectric part 25 and the dielectric material forming the second dielectric part 26 are determined, and then the first and second flat plate conductor parts After determining the distance L1 between 23a and 23b, the size of the first dielectric part 25 is determined, and the distance L4 between the first and second electrodes 24a and 24b is determined accordingly.
- the length L5 of the propagation direction X of the first dielectric part 25 to which an electric field is applied by the first and second electrodes 24a, 24b is selected to be a length that can provide the necessary phase change.
- the electromagnetic wave propagates mainly through the first dielectric portion 25 sandwiched between the first and second flat plate conductor portions 23a and 23b and the second dielectric portion 26.
- the dielectric constant of the first dielectric part 25 By changing the dielectric constant of the first dielectric part 25, the influence on the phase change of the electromagnetic wave can be increased, and the line length for obtaining the required phase change can be shortened. Can be formed into a small size.
- a highly reliable and highly reliable phase shifter can be realized.
- the first and second electrodes 24 a and 24 b are embedded in the dielectric portion 22 and are formed thinner than the skin thickness with respect to the frequency of the electromagnetic wave propagating through the first dielectric portion 25. As a result, even if the first and second electrodes 24a and 24b are provided in contact with the first dielectric portion 25, the propagating electromagnetic wave can pass through the first and second electrodes 24a and 24b. The electromagnetic wave can be propagated without being cut off, and the guided mode is not affected. In addition, an electric field having a large electric field strength can be applied to the first dielectric portion 25 by the first and second electrodes 24a and 24b in a state where transmission loss due to the embedding of the first and second electrodes 24a and 24b is suppressed.
- the phase of the electromagnetic wave can be changed stably. Therefore, even if the voltage applied to the first and second electrodes 24a and 24b to apply an electric field to the first dielectric part 25 is reduced, an electric field having a large electric field strength is applied to the first dielectric part 25. Even if the length of the transmission line is short, an electric field with a large electric field strength is applied to the first dielectric portion 25. Therefore, the amount of phase change per unit length of the transmission line is increased, and the size is reduced. In addition, the phase shifter 20 that can be operated at a low voltage can be realized.
- phase shifter 20 by selecting the frequency of the electromagnetic wave propagating through the dielectric part 22 near the cutoff frequency, a large phase change can be obtained near the cutoff frequency even with a short line length. It can be formed in a small size.
- the interval between the first and second flat plate conductor portions 23a, 23b is set to half or less of the wavelength of the electromagnetic wave propagating in the second dielectric portion 26.
- the distance between the first and second flat plate conductor portions 23a and 23b may be larger than half of the wavelength of the electromagnetic wave propagating in the second dielectric portion 26.
- the first and The second flat plate conductor portions 23a and 23b and the dielectric portion 22 constitute an H guide, and the transmission loss is larger than that of the phase shifter 20 of the embodiment shown in FIG. Can do.
- the first and second electrodes 24a, 24b are formed from the first input / output end 22a to the second input / output end 22b in the propagation direction X, but the first and second electrodes 24a , 24b may be formed discontinuously in the propagation direction X.
- the first dielectric part 25 is made of a material whose dielectric constant changes.
- the first dielectric part 25 is Any structure including a changing portion made of a substance whose dielectric constant changes may be used.
- the change part is preferably formed in a part where the electric field strength is high, for example, in the center part in the width direction Y and the thickness direction Z. With such a configuration, the phase shifter has the same size depending on the proportion of the first dielectric portion 25 occupied by the changed portion and the area of the first dielectric portion 25 where the changed portion is formed.
- the amount of phase change obtained at the time of fabrication is determined, and the amount of phase change is smaller than when the entire first dielectric portion 25 is made of a material whose dielectric constant changes, but in the same manner as in the previous embodiment.
- a small phase shifter can be provided.
- FIG. 2 is a cross-sectional view schematically showing a phase shifter 30 according to another embodiment of the present invention.
- the phase shifter 30 includes a dielectric portion 22, a pair of first and second flat plate conductor portions 23a and 23b, a pair of first and second electrodes 24a and 24b, and a voltage applying means 19. Is done.
- the phase shifter 30 according to the embodiment of the present invention is formed in a substantially rectangular parallelepiped shape.
- a cross section perpendicular to the propagation direction X of the electromagnetic wave in the phase shifter 30 has the same shape over both ends of the propagation direction X of the phase shifter 30.
- the phase shifter 30 of the present embodiment is similar to the phase shifter 20 shown in FIG. 1 described above, and differs only in the configuration of the electrodes and the positions where the electrodes are provided.
- the components are denoted by the same reference numerals, and the description thereof is omitted.
- the phase shifter 30 includes a dielectric portion 22, first and second flat plate conductor portions 23a, 23b, a plurality of electrodes Tl, T2, ..., Tn-1, ⁇ , and a voltage applying means 19. It is comprised including.
- the first dielectric part 25 has a plurality of Electrodes Tl, T2, ⁇ , Tn-1, ⁇ (symbol ⁇ is a natural number of 2 or more) are embedded.
- the second dielectric part 26 sandwiches the first dielectric part 25, that is, is provided on both sides of the first dielectric part 25 in the thickness direction.
- the electrodes ⁇ are provided at intervals in the thickness direction ⁇ .
- the electrode thickness L7 is selected in the same manner as the first and second electrodes 24a and 24b.
- the electrode T is formed of the same shape and the same material as the first and second electrodes 24a and 24b described above.
- the electrode T is provided such that its thickness direction is parallel to the thickness direction Z.
- the electrodes T adjacent to each other in the thickness direction Z are connected to different flat conductor portions of the first and second flat conductor portions 23a and 23b. That is, among the electrodes T, the odd-numbered electrodes Tl, T3,..., Tm-2, Tm (the symbol m is a positive odd number) toward the first direction in the thickness direction Z are the first plate conductor portions.
- the even-numbered electrodes T 2, T4, ..., Tk-2, Tk (symbol k is a positive even number) connected to 23a and directed in the first direction in the thickness direction Z are the second plate conductors
- the voltage is applied to the first or second flat plate conductor portions 23a and 23b by connecting the electrode T to the first or second flat plate conductor portions 23a and 23b in this way, they are adjacent to each other.
- An electric potential difference is generated in the electrode T to be applied, and an electric field can be applied to the first dielectric portion 25.
- a voltage can be applied by the electrodes T adjacent to each other only by applying a voltage to the first and second plate conductor portions 23a and 23b. There is no need to form a separate wiring for applying voltage.
- the total thickness L7 of the electrode ridge is preferably 320 nm or less.
- the electrode T is connected to the first or second plate conductor portions 23a and 23b to which the electrode T is not connected. They are spaced apart.
- the electrode T is embedded in the first dielectric part 25, an electric field can be effectively applied to the first dielectric part 25, and the interval between the electrodes T can be further increased. By bringing them closer, it is possible to give a larger electric field strength to the first dielectric portion 25, and it is possible to operate with a smaller size and a lower voltage.
- the voltage can be applied by the electrodes T adjacent to each other only by applying a voltage to the first and second plate conductor portions 23a, 23b, and wiring for applying the voltage to each electrode T can be individually provided.
- the circuit board can be easily implemented.
- FIG. 3 is a flowchart showing the manufacturing process of the phase shifter 30, and FIGS. 4A to 4C are schematic diagrams showing the manufacturing process of the phase shifter 30.
- the process proceeds from step si to step s2.
- step s2 a first dielectric film 32 made of a dielectric having a predetermined dielectric constant is formed on the first surface 31a of the substrate 31, and the process proceeds to step s3.
- the substrate 31 is made of, for example, MgO single crystal.
- the dielectric constant is higher than that of the first dielectric film 32, which is laminated on the first dielectric film 32, and is thinner than the thickness of the skin film with respect to the predetermined frequency (operating frequency) of the electromagnetic wave.
- a laminated body 35 is formed by alternately laminating the second dielectric films 34 whose dielectric constant changes according to the magnitude of the applied voltage.
- the electrode films 33 that are adjacent to each other in the direction in which the electrode films 33 are laminated are formed so as to partially overlap each other.
- the electrode film 33 is formed using a semiconductor material such as silicon (Si), germanium (Ge) and gallium arsenide (GaAs), or a high resistance material such as tantalum nitride and NiCr alloy.
- the second dielectric film 34 is formed of, for example, Ba Sr TiO (abbreviation BST), Mg Ca TiO, Z
- FIG. 5 is a plan view showing a state in which a plurality of electrode films 33 and second dielectric films 34 are stacked in step s3.
- a metal mask having a rectangular through hole is used, and the electrode film 33 is deposited so that the electrode film 33 is attached only to a portion corresponding to the through hole.
- no-turn formation can be performed simultaneously with the formation of the electrode film 33.
- the second film is formed over the entire surface of the laminated portion covering the electrode film 33.
- a dielectric film 34 is formed and laminated on the second dielectric film 34 to form the electrode film 33 again.
- the electrode film 33 and the second dielectric film 34 are laminated so that the electrode films 33 adjacent to each other in the direction in which the electrode films 33 are laminated overlap each other.
- a predetermined direction F perpendicular to the direction the formation position is changed closer to the first direction F1 and closer to the second direction F2. Since the size of each electrode film 33 is equal, when the adjacent electrode film 33 is formed, the electrode mask 33 is formed by shifting the metal mask in the first direction F1 or the second direction F2 of the predetermined direction F. Thus, a plurality of electrode films 33 partially overlapping in the stacking direction can be formed. In FIG. 5, the portion where the electrode films 33 adjacent to each other overlap is indicated by hatching. Next, the process proceeds to step s4.
- a dielectric film 36 is formed.
- the third dielectric film 36 is formed of the same material as the first dielectric film 32, and is formed of glass, single crystal, ceramics or resin.
- the first dielectric film 32 and the third dielectric film 36 are formed to have the same film thickness.
- step s5 the first dielectric film 32, the stacked body 35, and the third dielectric film 36 are etched to form the convex portion 37 shown in FIG. 4B.
- the convex portion 37 is formed so as to include a part of the first dielectric film 32, the stacked body 35, and the third dielectric film 36.
- the convex portion 37 is a first direction F1 in a predetermined direction F from the first end surface 38a of the pair of end surfaces 38a, 38b facing each other in the direction in which the electrode film 33 and the second dielectric film 32 are laminated.
- the electrode film 33 formed near the second direction F2 in the predetermined direction F is exposed from the second end face 39b of the pair of end faces 38a, 38b facing each other.
- etching a known etching method such as chemical dry etching, reactive ion etching, or wet etching can be used.
- the material of the electrode film 33 and the material of the second dielectric film 34 are selected in advance so that the etching rate of the second dielectric film 34 is higher than that of the electrode film 33.
- the end portions of the electrode film 33 can be exposed at the first and second end faces 38a, 38b of the convex portion 37.
- the area outside the phantom line 39 in FIGS. 4A to 4C is removed by etching.
- an electrode Tb that is not exposed at the end face in the first direction Fl and is exposed at the end face in the second direction F2 is formed.
- step s6 first and second flat plate conductor portions 23a and 23b are formed on the first and second end faces 38a and 38b of the convex portion, as shown in FIG. 4C.
- a phase shifter 30 is formed.
- the first and second flat plate conductor portions 23a and 23b cover the convex portion 37 to form a conductive film, and the first and second end faces 38a, It is formed by removing the portion excluding 38b.
- step s6 is completed, the process proceeds to step s7 and the manufacturing process is terminated.
- a known thin film forming method such as vacuum deposition, sputtering, or CVD (Chemical Vapor Deposition) can be used for forming the electrode film 33.
- the phase shifter 30 in which the even-numbered electrodes T and the odd-numbered electrodes T are connected to different plate conductor portions in the stacking direction of the electrode film 33. .
- the laminated electrode film 33 can be accurately and surely drawn out to the first end surface 38a and the second end surface 38b, and the phase shifter is manufactured by a manufacturing method suitable for a semiconductor process in which conventional force is also used. 30 can be formed, so that a small and stable phase shifter with good accuracy can be manufactured with high productivity.
- phase shifters 30 can be formed on the substrate 31 by forming the electrode film 33 using a photomask in which a plurality of through holes are formed. Dicing the boundary of the substrate 31 between adjacent phase shifters 30 and cutting them individually!
- FIG. 6 is a perspective view schematically showing a phase shifter 40 according to still another embodiment of the present invention.
- the same reference numerals are given to the same configurations as those of the above-described embodiments, and the description thereof is omitted.
- the cross section of the phase shifter 40 perpendicular to the propagation direction X of the electromagnetic wave has the same shape as the end face of the phase shifter 40 in the propagation direction X.
- the phase shifter 40 forms a non-radiative dielectric line (NRD guide).
- the dielectric part 42, the first and second plate conductor parts 23 a and 23 b, the first and second electrodes 24 a and 24 b, and the voltage applying unit 19 are configured.
- the dielectric part 42 is formed in a rectangular parallelepiped shape.
- the dielectric part 42 includes a first dielectric part 44 and a second dielectric part 45, and is formed by embedding the first and second electrodes 24a and 24b.
- the first dielectric part 44 is the same as that described above.
- the second dielectric part 45 is formed of the same material as the second dielectric part 26 of the above-described embodiment.
- the dielectric portion 42 is provided so as to be sandwiched between the first and second flat plate conductor portions 23a and 23b.
- the dielectric portion 42 is the first and second flat plate conductors.
- the end forces of the portions 23a and 23b are also provided apart from each other.
- a first dielectric part 44 is provided at the center in the stacking direction Z. On both sides of the first dielectric part 44 in the stacking direction Z, the second dielectric part 45 is provided.
- the first and second electrodes 24a and 24b are provided by being laminated on both end faces in the thickness direction Z of the first dielectric part 44, and sandwich the first dielectric part 44 so as to sandwich the first and second dielectric parts 44. It is embedded between body parts 44 and 45.
- the first and second electrodes 24 a and 24 b are formed over both end faces of the first dielectric portion 44 in the thickness direction Z.
- the second dielectric part 46 is formed on the target with the first dielectric part 45 interposed therebetween, and the first and second electrodes 24a and 24b are formed on the target with the first dielectric part 45 interposed therebetween.
- a voltage applying means 19 is connected to the first and second electrodes 24a, 24b, and the phase of the electromagnetic wave propagating through the phase shifter 40 can be changed, which is the same as each phase shifter in the previous embodiment. The effect of can be achieved.
- FIG. 7 is a perspective view schematically showing a phase shifter 50 according to still another embodiment of the present invention.
- the same reference numerals are given to the same configurations as those of the above-described embodiments, and the description thereof is omitted.
- the cross section of the phase shifter 50 perpendicular to the propagation direction X of the electromagnetic wave has the same shape as the end face of the phase shifter 50 in the propagation direction X.
- the phase shifter 50 forms an image line.
- the phase shifter 50 includes a ground conductor plate 51, a dielectric part 52, and an electrode 53.
- the ground conductor plate 51 is formed in a rectangular parallelepiped shape, and the first surface 51a in the thickness direction Z is formed in a plane.
- Dielectric portions 52 are stacked on the first surface 51a.
- the dielectric portion 52 includes a first dielectric portion 54 and a second dielectric portion 55, and is formed by embedding the electrode 53.
- a first dielectric part 54 is laminated on the first surface 51 a
- an electrode 53 is laminated on the first dielectric part 25, and a second dielectric part 26 is laminated on the electrode 53.
- First dielectric part The laminated body 56 of the electrode 54, the electrode 53, and the second dielectric part 55 is formed in a rectangular parallelepiped shape, and is formed between both ends of the ground conductor plate 51 in the propagation direction X.
- the laminated body 56 is also provided so that the end force in the width direction Y of the ground conductor plate 51 is also separated.
- the first dielectric part 54 is formed of the same material as the first dielectric part 25 of the above-described embodiment, and the second dielectric part 55 is the same as the first dielectric part 25 of the above-described embodiment.
- the electrode 53 is formed of the same material as the first and second electrodes 24a and 24b of the above-described embodiment and has the same thickness.
- the ground conductor plate 51 is formed of the same material as the flat conductor portions 23a and 23b of the above-described embodiment.
- the dimension L11 in the thickness direction of the second dielectric part 55 is a cutoff frequency when a predetermined voltage is applied between the electrode 53 and the ground conductor plate 51 to reduce the dielectric constant of the first dielectric part 54.
- f is the operating frequency, that is, the frequency of the electromagnetic wave propagating through the dielectric part 52.
- a voltage applying means 19 is connected to the electrode 53 and the ground conductor plate 51, and the phase of the electromagnetic wave propagating through the phase shifter 40 can be changed, and the same effect as each phase shifter of the above-described embodiment. Can be achieved.
- FIG. 8 is a perspective view schematically showing a phase shifter 60 according to still another embodiment of the present invention.
- the same reference numerals are given to the same configurations as those of the above-described embodiments, and the description thereof is omitted.
- the cross section of the phase shifter 60 perpendicular to the propagation direction X of the electromagnetic wave has the same shape as the end face of the phase shifter 60 in the propagation direction X.
- the phase shifter 60 forms an image line.
- the phase shifter 60 includes a ground conductor plate 51, a dielectric part 61, and an electrode 63.
- the dielectric portion 61 is formed of the same material as the first dielectric portion 25 of the above-described embodiment, is formed in a rectangular parallelepiped shape, and is formed between both end portions of the ground conductor plate 51 in the propagation direction X.
- the dielectric portion 61 is also provided with an end force in the width direction Y of the ground conductor plate 51 spaced apart.
- An electrode 63 is embedded in the dielectric portion 61.
- the electrode 63 is arranged in the thickness direction Z
- the first electrode 63a and the second electrode 63b are formed with a predetermined interval L32.
- the predetermined interval L32 is selected, for example, from 0.1 ⁇ m to 50 ⁇ m. Smaller L32 is preferable because the electric field strength that can be applied to the dielectric portion 61 is increased and the phase change can be increased. However, if L32 is too small, the loss increases. If L32 is made too large, the electric field intensity that can be applied to the dielectric part 61 becomes small, the line length necessary to obtain the desired phase change becomes long, and the phase shifter becomes large.
- the dielectric portion 61 is formed in a rectangular parallelepiped shape and a plate shape, and is formed between both end portions in the propagation direction X of the dielectric portion 61.
- the thicknesses of the first electrode 63a and the second electrode 63b are selected in the same manner as the first and second electrodes 24a and 24b described above.
- the length of the first electrode 63a in the width direction Y is selected to be as large as possible without contacting the second electrode 63b.
- the dielectric part 61 is formed to extend in the thickness direction Z while meandering in the width direction Y in a cross section perpendicular to the propagation direction X.
- the end of the second electrode 63b on the ground conductor plate 51 side in the thickness direction Z is connected to the ground conductor plate 51.
- a voltage applying means 19 is connected to the first and second electrodes 63a, 63b, and the phase shifter 60 can change the phase of the propagating electromagnetic wave in the same manner as each phase shifter described above. An effect similar to that of each phase shifter of the embodiment can be achieved.
- FIG. 9 is a perspective view schematically showing a phase shifter 70 according to still another embodiment of the present invention.
- the same reference numerals are given to the same configurations as those of the above-described embodiments, and the description thereof is omitted.
- the cross section perpendicular to the propagation direction X of the electromagnetic wave in the phase shifter 70 has the same shape as the end face of the phase shifter 70 in the propagation direction X.
- the phase shifter 70 is formed in a rectangular parallelepiped shape.
- the phase shifter 70 forms a strip line.
- the phase shifter 70 includes a strip conductor portion 71, a dielectric portion 72, first and second electrodes 24a and 24b, and first and second flat plate conductor portions 23a and 23b.
- the strip conductor portion 71 is formed of a conductor and has a rectangular parallelepiped shape.
- the strip conductor portion 71 is made of the same material as the first and second plate conductor portions 23a and 23b described above. Formed.
- the strip conductor portion 71 is formed by being embedded in the dielectric portion 72.
- the dielectric part 72 is formed in a rectangular parallelepiped shape.
- the strip conductor portion 71 is embedded in the dielectric portion 72 in a state where both end portions in the extending direction of the strip conductor portion 71 are exposed from the end face of the dielectric portion 72. That is, the extending direction of the strip conductor portion 71 is the electromagnetic wave propagation direction X.
- the strip conductor part 71 is formed at the center of the dielectric part 72.
- First and second flat plate conductor portions 23a and 23b are provided on both end faces of the dielectric portion 72 in the thickness direction Z, respectively, and the dielectric portion 72 includes the first and second flat plate conductor portions 23a, It is sandwiched between 23b.
- the strip conductor portion 71 is formed in parallel with the first and second flat conductor portions 23a and 23b.
- the dimension in the thickness direction Z of the strip conductor portion 71 is formed smaller than the dimension in the width direction Y.
- the dielectric part 72 includes first and second dielectric parts 74 and 75.
- the first dielectric part 74 is formed of the same material as the first dielectric part 25 of the above-described embodiment, and the second dielectric part 75 is the same as the second dielectric part 26 of the above-described embodiment. Of similar material and thickness.
- the first dielectric parts 74 are provided on both sides of the strip conductor part 71 in the thickness direction Z, and are provided so as to sandwich the strip conductor part 71.
- the first dielectric part 74 is formed over the entire surface on both end faces in the thickness direction Z of the strip conductor part 71, and the multilayer body 76 of the first dielectric part 74 and the strip conductor part 71 is formed in a rectangular parallelepiped shape.
- the second dielectric part 75 is provided so as to surround the stacked body 76.
- the first and second electrodes 24a and 24b are embedded between the first and second dielectric parts 74 and 75, respectively.
- the first and second electrodes 24a and 24b are provided on both sides in the thickness direction Z of the multilayer body 76, respectively, and are sandwiched between the multilayer bodies 76.
- the first and second electrodes 24a and 24b are formed over the entire end surface of the laminate 76 in the thickness direction Z.
- FIG. 10 is a perspective view schematically showing a phase shifter 80 according to still another embodiment of the present invention.
- the same reference numerals are given to the same configurations as those of the above-described embodiments, and the description thereof is omitted.
- the phase shifter 80 is formed in a rectangular parallelepiped shape.
- the cross section of the phase shifter 80 perpendicular to the propagation direction X of the electromagnetic wave has the same shape as the end face of the phase shifter 80 in the propagation direction X.
- the phase shifter 80 is formed in a rectangular parallelepiped shape.
- the phase shifter 80 forms a strip line.
- the phase shifter 80 includes a strip conductor portion 71, a dielectric portion 82, first and second electrodes 24a and 24b, and first and second flat plate conductor portions 23a and 23b.
- the dielectric part 82 is formed in a rectangular parallelepiped shape.
- the strip conductor portion 71 is embedded in the dielectric portion 82 with both end portions in the extending direction of the strip conductor portion 71 exposed from the end face of the dielectric portion 82. That is, the extending direction of the strip conductor portion 71 is the electromagnetic wave propagation direction X.
- the strip conductor portion 71 is formed in the central portion of the dielectric portion 82.
- the first and second flat plate conductor portions 23a and 23b are respectively provided on both end faces in the thickness direction Z of the dielectric portion 82, and the dielectric portion 82 includes the first and second flat plate conductor portions 23a, It is sandwiched between 23b.
- the strip conductor portion 71 is formed in parallel with the first and second flat conductor portions 23a and 23b.
- the dimension in the thickness direction Z of the strip conductor portion 71 is formed smaller than the dimension in the width direction Y.
- the dielectric part 82 includes first and second dielectric parts 84 and 85.
- the first dielectric part 84 is formed of the same material as the first dielectric part 25 of the above-described embodiment, and the second dielectric part 85 is the same as the second dielectric part 26 of the above-described embodiment. It is formed by the substance.
- the first dielectric parts 84 are provided on both sides of the strip conductor part 71 in the thickness direction Z, respectively, spaced from the strip conductor part 71.
- the first dielectric portion 84 is formed across both end portions of the dielectric portion 82 in the width direction Y and the thickness direction Z.
- the first dielectric part 84 is provided at an equal distance in the thickness direction Z with respect to the strip conductor part 71, that is, formed in plane symmetry with respect to an imaginary plane that includes the axis of the strip conductor part 71 and is perpendicular to the thickness direction Z.
- the Each first dielectric part 84 is provided between the second dielectric parts 85.
- the first and second electrodes 24a and 24b are provided on both sides of the thickness direction Z of the first dielectric portions 84, respectively.
- the first dielectric part 84 is sandwiched, that is, provided on both sides of the first dielectric part 84, and embedded between the first and second dielectric parts 84 and 85.
- the first and second electrodes 24a and 24b are respectively formed over the entire end surface of the first dielectric portion 84 in the thickness direction Z.
- the dielectric portions 84 and 85 are arranged in the thickness direction Z between the strip conductor portion 71 and the first and second flat plate conductor portions 23a and 23b. It is provided at a close position.
- Each of the first and second electrodes 24a, 24b is connected to a voltage applying means 19, and can change the phase of the electromagnetic wave propagating through the phase shifter 80. Similar effects can be achieved.
- FIG. 11 is a perspective view schematically showing a phase shifter 90 according to still another embodiment of the present invention.
- the same reference numerals are given to the same configurations as those of the above-described embodiments, and the description thereof is omitted.
- the cross section perpendicular to the propagation direction X of the electromagnetic wave in the phase shifter 90 has the same shape as the end face of the phase shifter 90 in the propagation direction X.
- the phase shifter 90 forms a microstrip line.
- the phase shifter 90 includes a strip conductor portion 71, a ground conductor plate 51, a dielectric portion 92, and an electrode 93.
- the dielectric part 92 is formed in a rectangular parallelepiped shape.
- a strip conductor part 71 is laminated and provided on the first surface 92a in the thickness direction Z of the dielectric part 92.
- the strip conductor portion 71 is formed at the center in the width direction Y of the dielectric portion 92 across the both end portions of the dielectric portion 92 in the propagation direction X, and is separated from the end portions of the dielectric portion 92 in the width direction Y.
- the ground conductor plate 51 is laminated over the entire surface.
- the dielectric portion 92 includes a first dielectric portion 94 and a second dielectric portion 95, and is formed by embedding an electrode 93.
- the first dielectric part 94 is formed of the same material as the first dielectric part 25 of the above-described embodiment, and the second dielectric part 95 is the same as the second dielectric part 26 of the above-described embodiment.
- the electrode 93 is made of the same material as the first and second electrodes 24a and 24b of the above-described embodiment and has the same thickness.
- the strip conductor portion 71 of the first dielectric portion 94 is laminated in the thickness direction Z.
- the second end surface 94b opposite to the first end surface 94a is stacked and embedded between the first and second dielectric portions 94 and 95.
- the electrode 93 is formed by being laminated over the entire surface of the second end face 94b of the first dielectric part 94.
- the voltage application means 19 is connected to the electrode 93 and the strip conductor portion 71, and the phase of the electromagnetic wave propagating through the phase shifter 90 can be changed.
- the same effect as each phase shifter of the above-described embodiment Can be achieved.
- FIG. 12 is a perspective view schematically showing a phase shifter 100 according to still another embodiment of the present invention.
- the phase shifter 100 is formed in a rectangular parallelepiped shape.
- the cross section of the phase shifter 100 perpendicular to the propagation direction X of the electromagnetic wave has the same shape as the end face of the phase shifter 100 in the propagation direction X.
- the phase shifter 100 forms a microstrip line.
- the phase shifter 100 includes a strip conductor portion 71, a ground conductor plate 51, a dielectric portion 102, and first and second electrodes 24a and 24b.
- a strip conductor portion 71 is laminated and provided on the first surface 102a in the thickness direction Z of the dielectric portion 102.
- the strip conductor portion 71 is formed at the center in the width direction Y of the dielectric portion 102 across the both end portions of the dielectric portion 102 in the propagation direction X, and the end portion force in the width direction Y of the dielectric portion 102 is separated by a predetermined distance.
- a ground conductor plate 51 is laminated over the entire surface.
- the dielectric portion 102 includes a first dielectric portion 104 and a second dielectric portion 105, and is formed by embedding the first and second electrodes 24a and 24b.
- the first dielectric part 104 is formed of the same material as the first dielectric part 25 of the above-described embodiment, and the second dielectric part 105 is the same as the second dielectric part 26 of the above-described embodiment. It is formed by a similar material.
- the first dielectric portion 104 is provided between the strip conductor portion 71 and the ground conductor plate 51 so as to be separated from the strip conductor portion 71.
- the first dielectric portion 104 is formed between both end portions of the dielectric portion 102 in the width direction Y and the thickness direction Z.
- the first dielectric part 104 is provided between the second dielectric parts 105.
- the first and second electrodes 24a and 24b are disposed on both sides of the first dielectric portion 104 in the thickness direction Z, respectively.
- the first dielectric part 104 is sandwiched between the first and second dielectric parts 104 and 105, and is provided.
- the first and second electrodes 24a and 24b are respectively formed over the entire surface on the end face in the thickness direction Z of the first dielectric portion 105.
- the first dielectric portion 104 is provided in the thickness direction Z between the strip conductor portion 71 and the ground conductor plate 51 at a position near the strip conductor portion 71 where the electric field strength of the propagating electromagnetic wave is large.
- a voltage applying means 19 is connected to each of the first and second electrodes 24a and 24b, and the phase of the electromagnetic wave propagating through the phase shifter 100 can be changed, which is the same as each phase shifter in the above-described embodiment. The effect of can be achieved.
- FIG. 13 is a perspective view schematically showing a phase shifter 110 according to still another embodiment of the present invention.
- the same reference numerals are given to the same configurations as those in the above-described embodiments, and the description thereof will be omitted.
- the cross section perpendicular to the propagation direction X of the electromagnetic wave in the phase shifter 110 has the same shape as the end face of the phase shifter 110 in the propagation direction X.
- the phase shifter 110 forms a coplanar line.
- the phase shifter 110 includes a strip conductor portion 71, a ground conductor portion 111, a dielectric portion 112, and first and second electrodes 24a and 24b.
- the dielectric part 112 is formed in a rectangular parallelepiped shape.
- a strip conductor portion 71 is provided by being laminated.
- the strip conductor portion 71 is formed at the center in the width direction Y of the dielectric portion 112 across the both end portions of the dielectric portion 112 in the propagation direction X.
- the ground conductor portions 111 are formed on both sides of the strip conductor portion 71 in the width direction Y so as to be separated from the strip conductor portion 71, respectively.
- the ground conductor 111 is formed along the strip conductor 71.
- the ground conductor 111 is formed to have the same thickness as the strip conductor 71 and is formed across the end of the dielectric 112 in the width direction Y.
- the dielectric portion 112 includes a first dielectric portion 114 and a second dielectric portion 115, and is formed by embedding the first and second electrodes 24a and 24b.
- the first dielectric part 114 is formed of the same material as the first dielectric part 25 of the above-described embodiment, and the second dielectric part 115 is the same as the second dielectric part 26 of the above-described embodiment. It is formed by a similar material.
- the first dielectric portion 114 extends from the strip conductor portion 71 and the ground conductor portion 111 in the thickness direction Z. Are spaced apart from each other. The first dielectric portion 114 is formed across both end portions of the dielectric portion 102 in the width direction Y and the thickness direction Z. The first dielectric part 114 is provided between the second dielectric parts 115.
- the first and second electrodes 24a and 24b are respectively provided on both sides in the thickness direction Z of the first dielectric part 114, and are provided so as to sandwich the first dielectric part 114. It is buried between the body parts 114 and 115.
- the first and second electrodes 24a and 24b are respectively formed over the entire surface of the first dielectric portion 114 on the end surface in the thickness direction Z.
- the first dielectric part 114 is provided in the thickness direction Z as close as possible to the strip conductor part 71 and the ground conductor part 111 where the electric field intensity of the propagating electromagnetic wave is large.
- a voltage applying means 19 is connected to each of the first and second electrodes 24a and 24b, and the phase of the electromagnetic wave propagating through the phase shifter 110 can be changed, which is the same as each phase shifter in the above-described embodiment. The effect of can be achieved.
- the first dielectric part 45, 54, 74, 84, 94, 104, 114 in the thickness direction Z dimension L9, L10, L12, L13, L14, L15: L17 is, for example, 0.1 m to Selected as 50 m.
- Dimensions 9, L10, L12, L13, L14, L15, 17 If the force is greater than 50 / ⁇ ⁇ , the applied electric field strength decreases and the line length necessary to obtain the desired phase change becomes longer. The phaser grows big. Moreover, if the dimensions L9, L10, L12, L13, L14, L15, and L17 are increased and the electrodes are laminated as described above, the loss due to the electrodes will increase.
- FIG. 14 is a perspective view schematically showing a phase shifter 120 according to still another embodiment of the present invention.
- the same reference numerals are given to the same configurations as those in the above-described embodiments, and the description thereof will be omitted.
- the cross section perpendicular to the propagation direction X of the electromagnetic wave in the phase shifter 120 has the same shape as the end face of the phase shifter 120 in the propagation direction X.
- the phase shifter 120 forms a slot line.
- the phase shifter 20 includes a slot conductor portion 121, a dielectric portion 112, and first and second electrodes 24a and 24b.
- a slot conductor 121 is laminated on the first surface 112a in the thickness direction Z of the dielectric 112. Provided.
- the slot conductor 121 is formed of the same material as the strip conductor 71 described above, and has the same thickness.
- the slot conductor portion 121 is laminated on the dielectric portion 112 except for the central portion of the dielectric portion 112 in the width direction Y.
- the slot conductor 121 has a first slot conductor 121a and a second slot conductor 121b. The first slot conductor 121a and the second slot conductor 121b are provided apart from each other in the width direction Y.
- a voltage applying means 19 is connected to each of the first and second electrodes 24a and 24b, and the phase of the electromagnetic wave propagating through the phase shifter 20 can be changed, which is the same as each phase shifter in the above-described embodiment. The effect of can be achieved.
- FIG. 1 is a cross-sectional view schematically showing a phase shifter 130 according to still another embodiment of the present invention.
- the phase shifter 130 includes a dielectric part 2 through which electromagnetic waves propagate and a conductor part 3 that surrounds the dielectric part 2 and forms a waveguide.
- the phase shifter 130 according to the embodiment of the present invention is formed in a rectangular parallelepiped shape.
- the cross section perpendicular to the propagation direction X of the electromagnetic wave in the phase shifter 130 has the same shape as the end face of the phase shifter 130 in the propagation direction X.
- the dielectric portion 2 is made of a dielectric and is formed to include a changing portion whose dielectric constant changes according to the applied electric field.
- the dielectric part 2 includes a change part and is formed of the same material as that of the first dielectric part 25.
- the dielectric part 2 has first and second input / output terminals 2a and 2b through which electromagnetic waves are input and output.
- the first and second input / output terminals 2a and 2b are formed at the ends of the propagation direction X along the propagation direction X in which the electromagnetic waves propagate.
- the dielectric portion 2 is formed in a rectangular parallelepiped shape, and the first and second input / output ends 2a and 2b are formed by a plane perpendicular to the propagation direction X and are mutually connected. Opposed.
- the cross section perpendicular to the propagation direction X of the dielectric part 2 is rectangular.
- width direction Y is the short direction in the cross section perpendicular to the propagation direction X of the dielectric part 2
- thickness direction Z is the cross section of the dielectric part 2 perpendicular to the propagation direction X.
- longitudinal direction is the longitudinal direction.
- the conductor portion 3 is made of a conductor and includes a pair of first and second electrodes 4a and 4b for applying an electric field to the dielectric portion 2.
- the first and second electrodes 4a and 4b are provided by being laminated on the outer surface of the dielectric part 2.
- the conductor portion 3 has the first and And the second electrodes 4a and 4b, and the first and second electrodes 4a and 4b are in close contact with the dielectric portion 2 around the axis A1 along the propagation direction X of the dielectric portion 2 In a state where both end faces of the part 2 in the propagation direction X are exposed, a waveguide is formed surrounding the dielectric part 2 apart from the axis A1.
- the first and second electrodes 4a and 4b are provided independently, that is, provided in a non-contact manner.
- the first and second electrodes 4a and 4b are formed across both end portions of the dielectric portion 2 in the propagation direction X.
- the first and second electrodes 4a and 4b are formed rotationally symmetric with respect to the axis A1.
- the first and second electrodes 4a, 4b are formed in a substantially U-shaped cross section perpendicular to the propagation direction X.
- the first electrode 4a covers the first end 2c side force dielectric part 2 in the thickness direction Z of the dielectric part 2 and extends to the middle part in the thickness direction Z.
- the second electrode 4b is the dielectric part 2
- the dielectric part 2 is covered from the second end part 2d side in the thickness direction Z of the film and extends to the intermediate part in Z in the thickness direction.
- the first and second electrodes 4a and 4b do not touch each other! It is formed independently, and is formed around the axis A1 along the outer surface of the dielectric part 2 with a predetermined distance L18.
- the predetermined distance L18 is selected so as not to leak electromagnetic waves propagating through the dielectric portion 2 between the first and second electrodes 4a and 4b, and is formed by the first and second electrodes 4a and 4b. It is selected to be 1Z2 or less of the length a of the long side (size in the thickness direction Z) of the inner dimension of the wave tube.
- the first and second electrodes 4a and 4b are formed of a low resistivity metal, a metal capable of cofiring with the dielectric portion 2 at a high temperature, solder, or a conductive paste.
- Low resistivity metals include: gold (Au), copper (Cu), aluminum (A1), platinum (Pt), titanium (Ti), silver (Ag), no radium (Pd), zinc (Zn) And the group power of chromium (Cr) force is chosen.
- the first and second electrodes 4a and 4b are gold (Au), copper (Cu), aluminum (A1), platinum (Pt), titanium (Ti), silver (Ag), palladium (Pd), zinc (Zn) And the group power of chromium (Cr) power is also selected!
- first and second electrodes 4a and 4b may be formed of a transparent electrode body such as ITO (Indium Tin Oxide). First and second electrodes 4a and 4b are preferably formed of a low resistivity metal.
- the thicknesses of the first and second electrodes 4a and 4b are selected to be larger than the skin thickness with respect to the electromagnetic wave propagating through the dielectric part 2, and are selected to be 1 ⁇ m, for example.
- the dielectric part 2 is provided with insulating parts 5a and 5b formed integrally with the dielectric part 2.
- the insulating parts 5a and 5b are formed of the same material as that of the dielectric part 2.
- the insulating portions 5a and 5b are provided between the first and second electrodes 4a and 4b around the axis Al, and prevent the adjacent first and second electrodes 4a and 4b from coming into contact with each other.
- the insulating portions 5a and 5b are provided across both end portions in the propagation direction X of the dielectric portion 2, and are provided in contact with the first and second electrodes 4a and 4b, respectively.
- the insulating portions 5a and 5b protrude in the width direction Y from the surface of the dielectric portion 2 in a predetermined distance L19.
- the predetermined distance L19 is selected to be equal to the thickness in the width direction Y of the first and second electrodes 4a and 4b laminated on the dielectric portion 2.
- the predetermined distance L19 is selected to be (2 ⁇ -1) / 4 ( ⁇ is a natural number) of the wavelength of the plane wave propagating through the dielectric portion 2.
- the first and second electrodes 4a and 4b are separated around the axis A1, the first and second electrodes 4a and 4b are separated from each other. That is, leakage of electromagnetic waves propagating through the dielectric portion 2 can be prevented from the insulating portions 5a and 5b.
- the phase shifter 130 further includes a voltage applying means 19.
- the voltage applying means 19 is realized by an electric circuit that applies a voltage in a predetermined range between the pair of first and second electrodes 4a and 4b.
- the voltage applying means 19 is connected to the first and second electrodes 4a and 4b, applies a predetermined potential to each electrode, and applies a voltage between the first and second electrodes 4a and 4b.
- an electric field is applied to the dielectric portion 2 sandwiched between the first and second electrodes 4a and 4b.
- the voltage applying means 19 applies an AC voltage or a DC voltage having a frequency lower than the frequency of the propagating electromagnetic wave to the first and second electrodes 4a and 4b.
- the voltage applying means 19 applies a voltage corresponding to the phase amount to be shifted to the first and second electrodes 4a and 4b.
- the voltage application means 19 applies a voltage between the pair of electrodes 4a and 4b, and changes the magnitude of the applied voltage within a predetermined range, thereby changing the phase of the electromagnetic wave guided through the dielectric portion 2.
- Change according to the magnitude of the applied voltage that is, the magnitude of the applied electric field be able to.
- the dielectric forming the dielectric part 2 has a lower dielectric constant when the applied electric field is increased, and the phase of the electromagnetic wave guided through the dielectric part 2 can thereby be changed.
- the TE mode of the waveguide In order to propagate the electromagnetic wave in the TE mode of the waveguide,
- Phaser 130 is formed.
- the phase shifter 130 can be regarded as a dielectric waveguide. Therefore, the phase shifter 130 is described as a dielectric waveguide in which an dielectric is filled in the waveguide of the waveguide.
- the case where the relative permittivity ⁇ r of the dielectric forming the dielectric portion 2 varies between 800 and 760 according to the applied electric field will be described.
- the dielectric loss of the dielectric forming the dielectric part 2 is defined as tan ⁇ , and the length of the inner side of the waveguide formed by the first and second electrodes 4a and 4b (size in the thickness direction Z) is long.
- the electrical conductivity of the conductor forming the waveguide is ⁇
- the cutoff frequency of the waveguide is Assuming fc, fc is expressed by Equation 2.
- the cut-off frequency is a frequency at which a propagating high frequency signal is attenuated by 3 dB.
- Equation 2 is the permeability of vacuum and ⁇ is the permittivity of vacuum. Therefore,
- the cut-off frequency is determined by the length a.
- the TE mode orthogonal to the desired TE mode is not cut-off mode.
- phase change per unit length said a variation of phase constant j8 delta beta, that this value is the size Ihodo phase shifter small Show that you can.
- FIG. 16 is a graph showing the relationship between fZfc and ⁇ .
- the horizontal axis of the graph represents the frequency used (that is, the frequency f of the electromagnetic wave guided through the dielectric part 2) divided by the cutoff frequency fc (fZfc), and the vertical axis of the graph represents the amount of change in the phase constant j8.
- ⁇ represents.
- the operating frequency f is 77 GHz
- the long side a of the internal dimension of the waveguide is changed, the amount of change ⁇ ⁇ in the cutoff frequency fc and the phase constant
- 8 is calculated, and fZfc and ⁇
- FIG. 17 shows the relationship between fZfc and ⁇ iS / amaxZV.
- the horizontal axis of the graph represents fZfc, and the vertical axis of the graph represents the amount of phase change obtained under a certain loss obtained by dividing the change ⁇ of the phase constant j8 by the maximum attenuation constant a by the operating voltage. It represents the value (A ⁇ ⁇ max / V) obtained by dividing ( ⁇
- a ⁇ a maxZV is a performance index of the phase shifter.
- fZfc is 1.03 or less, it may cause a large phase change to electromagnetic waves with a short line length. Yes, but the loss increases as it approaches the cutoff state.
- the fZfc force is 1.5 or more, it is necessary to increase the line length and to apply a high voltage to the first and second electrodes 4a and 4b.
- f / fc as 1. 03 ⁇ f / fc ⁇ l. 5
- fZfc is preferably selected such that 1.03 ⁇ f / fc ⁇ l.2.
- ⁇ j8 Z a maxZV> 0.03 can be achieved, so that a phase shifter operating at a lower voltage can be realized.
- the cut-off frequency fc depends on the dielectric constant of the dielectric forming the dielectric portion 2 and the waveguide. It is determined by the length a of the long side of the dimension.
- the electric field strength required to change the relative permittivity ⁇ r of the dielectric forming the dielectric part 2 from 800 to 760 is 17 kVZcm.
- a voltage of 136 V may be applied between the first and second electrodes 4a and 4b.
- the phase change amount is 154 ° Zmm. Therefore, the length c necessary for obtaining the phase change of 360 °, that is, the length c in the propagation direction X of the dielectric part 2 to which the electric field is applied by the first and second electrodes 4a and 4b is 2.3 mm. is there.
- a 0.5 m thick BST film was formed on a MgO single crystal substrate with a relative dielectric constant of 9.5, and an electrode with a center conductor width of 50 ⁇ m and a gap of 25 ⁇ m was formed on it.
- the relative dielectric constant force of BST is changed from 00 force to 680, and the phase change at 77 GHz is 18 ° Zmm. Therefore, the length required to obtain a 360 ° phase change is 20 mm.
- the length c in the propagation direction X of the dielectric part 2 to which an electric field is applied by the first and second electrodes 4a and 4b is selected so as to obtain a necessary phase change.
- the phase shifter 130 since the conductor portion 3 forming the waveguide is formed by the first and second electrodes 4a and 4b, it is necessary to form an electrode separately from the waveguide. Nagu is easy to make. Since the first and second electrodes 4a and 4b are included in the waveguide, the frequency of the electromagnetic wave propagating through the dielectric part 2 is selected so as to be close to the cutoff frequency, and applied to the dielectric part 2. Therefore, the phase shifter 130 can be stably operated in the vicinity of the force cutoff frequency.
- the frequency of the electromagnetic wave propagating through the dielectric part 2 can be selected to be in the vicinity of the cutoff frequency, and a large phase change can be obtained in the vicinity of the cutoff frequency even with a short line length. Therefore, the phase shifter 130 can be formed in a small size. Further, by selecting the frequency of the electromagnetic wave propagating through the dielectric part 2 so as to be in the vicinity of the cutoff frequency, the size of the cross section perpendicular to the propagation direction of the electromagnetic wave of the dielectric part 2 is also reduced. 2 Since the distance between the electrodes 4a and 4b is close, a large electric field can be applied to the dielectric part 2 at a low voltage, and a large phase change can be stably obtained with a small voltage. A phase shifter 130 can be realized.
- fc is the cut-off frequency when voltage is applied to the first and second electrodes 4a and 4b
- f is the frequency of the electromagnetic wave propagating through the dielectric part
- fc and f are 1. 03 ⁇ f Since it is selected so as to satisfy /fc ⁇ l.5 and is used near the cutoff frequency where the phase change is large, a large phase change can be obtained even with a short line length, and the phase shifter 130 can be downsized.
- the first and second electrodes 4a and 4b can be brought close to each other, and a large voltage can be obtained with a small voltage.
- the phase shifter 130 can be operated at a low voltage.
- an electromagnetic wave near the cutoff frequency that is, an electromagnetic wave having a frequency satisfying 1.03 ⁇ f / fc ⁇ l.5
- the electromagnetic wave having a frequency far from the cutoff frequency that is, fZfc? L.
- the transmission loss per unit length is large, but the phase change per unit length is large. Therefore, the transmission line loss required by the phase shifter 130 can be reduced as a result.
- the dielectric portion 2 is formed in a rectangular parallelepiped shape.
- the shape of the cross section of the dielectric portion 2 perpendicular to the propagation direction X of the dielectric portion 2 may be circular, elliptical, polygonal, or other irregular shape. Even in such a shape, the same effect can be achieved.
- the dielectric part 2 also has a material force that changes the dielectric constant, but in still another embodiment of the present invention, the dielectric part 2 has a dielectric constant.
- Any structure may be used as long as it includes a changing portion consisting of a material force that changes.
- the changing portion is preferably formed in a portion where the electric field intensity of the propagating electromagnetic wave is high, for example, in the central portion in the thickness direction Z.
- the force electrode in which the first and second electrodes 4a and 4b are formed rotationally symmetrical around the axis A1 applies an electric field to the dielectric part 2.
- the number of electrodes is not limited to a pair, and a plurality of pairs may be formed. The same effect can be achieved if the electrodes are arranged so that an electric field can be applied to the dielectric portion 2.
- the waveguide is formed only by the first and second electrodes 4a and 4b.
- the first and second electrodes 4a and 4b and the conductor are used.
- a waveguide may be formed by the waveguide forming portion.
- the first and second electrodes 4a and 4b and the waveguide forming portion are formed with a predetermined distance L1 around the axis A1. Even if it forms in this way, the same effect can be achieved.
- the TE mode may be propagated.
- FIG. 18 is a cross-sectional view schematically showing a phase shifter 140 according to another embodiment of the present invention.
- the phase shifter 140 of the present embodiment is similar to the phase shifter 130 shown in FIG. 15 described above, and the same reference numerals are given to the same components as the phase shifter 130, and only different configurations will be described. However, the description of the same configuration is omitted.
- the cross section of the phase shifter 140 perpendicular to the propagation direction X of the electromagnetic wave has the same shape as the end face of the phase shifter 130 in the propagation direction X.
- the phase shifter 140 includes a dielectric part 2 and first and second electrodes 4a and 4b.
- the insulating portions 5a and 5b are formed by repeatedly connecting the first portion 12 and the second portion 13 whose dimension in the thickness direction Z is smaller than that of the first portion 12 in the width direction Y.
- the first and second electrodes 4a and 4b are provided in contact with the first and second portions 12 and 13, respectively, and constitute a choke structure.
- Second portions 13 are provided at both ends in the width direction Y of the insulating portions 5a and 5b.
- the absolute value of the difference between the dimension L24 in the thickness direction Z of the first portion 12 and the dimension L25 in the thickness direction Z of the second portion 13 is preferably as large as possible.
- the dimension L24 is selected to be equal to the length a, for example.
- the dimension L25 is selected as the above-mentioned predetermined distance L8.
- the dimensions L26 and L27 in the width direction Y of the first and second portions 12 and 13 are selected to be (2n-l) / 4 (n is a natural number) of the wavelength of the plane wave propagating through the dielectric portion 2, respectively. like this
- the high-frequency leakage that further propagates the dielectric portion 2 can be reduced. Can be suppressed.
- FIG. 19 is a perspective view schematically showing a phase shifter 150 according to still another embodiment of the present invention.
- the same reference numerals are given to the same configurations as those in the above-described embodiments, and the description thereof will be omitted.
- the cross section perpendicular to the propagation direction X of the electromagnetic wave in the phase shifter 150 has the same shape as the end face of the phase shifter 150 in the propagation direction X.
- the phase shifter 150 is similar to the phase shifter 130 of the above-described embodiment, and basically has a configuration in which an electrode T is added to the configuration of the phase shifter 130.
- the electrodes T are formed so as to be embedded in the dielectric portion 2 at intervals in the width direction Y.
- the electrode T is formed across both ends of the electromagnetic wave propagation direction X of the dielectric part 2.
- the electrodes T are formed in parallel to each other along the propagation direction X.
- the electrodes T adjacent to each other in the width direction Y are connected to different electrodes among the electrodes 4a and 4b which are the first and second waveguide forming portions. It is.
- a voltage applying means 19 is connected to each of the first and second electrodes 4a and 4b, and the phase of the electromagnetic wave propagating through the phase shifter 130 can be changed. Similar effects can be achieved.
- FIG. 20 is a perspective view schematically showing a phase shifter 160 according to still another embodiment of the present invention.
- the same reference numerals are given to the same configurations as those in the above-described embodiments, and the description thereof will be omitted.
- the cross section perpendicular to the propagation direction X of the electromagnetic wave in the phase shifter 160 has the same shape as the end face of the phase shifter 160 in the propagation direction X.
- the phase shifter 160 forms a dielectric waveguide.
- the phase shifter 160 includes a waveguide 141, a dielectric part 142, and first and second electrodes 24a and 24b.
- the waveguide 141 is formed of the same material as the first and second flat plate conductor portions 23a and 23b, and is formed in a cylindrical shape.
- the dielectric part 142 is surrounded by the waveguide 141 with both end faces in the propagation direction X exposed.
- the dielectric portion 142 and the inner peripheral surface of the waveguide 141 are in close contact with each other.
- the dielectric part 142 includes a first dielectric part 145 and a second dielectric part 146, and is formed by embedding the first and second electrodes 24a and 24b.
- the first dielectric part 145 is formed of the same material as the first dielectric part 25 of the above-described embodiment, and the second dielectric part 146 is the same as the second dielectric part 26 of the above-described embodiment. It is formed by a similar material.
- the first dielectric part 145 is formed at the central part in the thickness direction Z of the dielectric part 142, and is provided between the second dielectrics 146 in the thickness direction Z.
- the first dielectric part 145 is formed between both ends of the dielectric part 22 in the short direction Y along the short direction Y in the cross section perpendicular to the propagation direction X of the waveguide 141.
- the first and second electrodes 24a, 24b are provided on both end surfaces in the thickness direction Z of the first dielectric portion 145, and sandwich the first dielectric portion 145 to provide the first dielectric portion 145.
- the second dielectric portion 146 The first and second electrodes 24 a and 24 b are formed across both end portions of the dielectric portion 142 along the propagation direction X of the electromagnetic wave.
- the first and second electrodes 24a and 24b are provided apart from the waveguide 141 in the width direction Y.
- the dimension L20 in the thickness direction Z of the first dielectric portion 94 is the same reasoning force as that of the first dielectric rod 54, 74, 84, 94, 104, 114 of the above-described embodiment, for example, 0.1 ⁇ m. m-50 ⁇ m is selected.
- a voltage applying means 19 is connected to the first and second electrodes 24a and 24b, and the phase of the electromagnetic wave propagating through the phase shifter 160 can be changed, which is the same as each phase shifter in the previous embodiment. The effect of can be achieved.
- the phase shifters 30, 40, 50, 60, 130, 150, 160 having the cutoff frequency are first and second electrodes 24a, 24b! /
- the cutoff frequency when applying this voltage is fc
- each phase shifter 30, 40, 50, 60, 130, 140 is f and the frequency of the propagating electromagnetic wave is f, f is formed so that 1.03 ⁇ f / fc ⁇ l.5, preferably 1.03 ⁇ f / fc ⁇ l.2.
- FIG. 21 is a cross-sectional view schematically showing a phase shifter 170 according to still another embodiment of the present invention.
- the phase shifter 170 includes a dielectric portion 22, a pair of first and second flat plate conductor portions 23a and 23b, a pair of first and second electrodes 24a and 24b, and a voltage applying means 19. Is done.
- the phase shifter 170 according to the embodiment of the present invention is formed in a substantially rectangular parallelepiped shape.
- the cross section perpendicular to the propagation direction X of the electromagnetic wave in 170 mm of the phase shifter has the same shape as the end face of the phase shifter 21 in the propagation direction X.
- the same components as those of the phase shifter 20 shown in FIG. 1 described above are denoted by the same reference numerals, only different components will be described, and description of similar components may be omitted. is there.
- the dielectric portion 22 is made of a dielectric, and includes a first dielectric portion 25 including a changing portion whose dielectric constant changes according to an applied electric field, and a second dielectric portion 26.
- the dielectric part 22 has a first input / output terminal 22a for receiving an electromagnetic wave and a second input / output terminal 22b for outputting an electromagnetic wave.
- the first input / output end 22a and the second input / output end 22b are respectively formed on the upstream side and the downstream side in the propagation direction X along the propagation direction X in which the electromagnetic wave propagates.
- the dielectric portion 22 is formed in a rectangular parallelepiped shape, and the first input / output end 22a and the second input / output end 22b are formed by a plane perpendicular to the propagation direction X and face each other.
- the cross section perpendicular to the propagation direction X of the dielectric portion 22 is rectangular.
- the directions perpendicular to the propagation direction X and perpendicular to each other are referred to as “width direction Y” and “thickness direction Z”, respectively.
- the width direction ⁇ is the longitudinal direction in the cross section perpendicular to the propagation direction X of the dielectric part 22
- the thickness direction ⁇ is the propagation direction of the dielectric part 22.
- the first dielectric portion 25 is formed in a rectangular parallelepiped shape, and is formed between both end portions in the propagation direction X of the dielectric portion 22 and between both end portions in the width direction Y.
- the second dielectric part 26 is laminated on both sides of the first dielectric part 25 with the first dielectric part 25 interposed therebetween.
- the second dielectric part 26 is provided on both sides of the first dielectric part 25 in the thickness direction Z and is laminated on the first dielectric part 25, respectively.
- the second dielectric part 26 has a rectangular parallelepiped shape.
- the first and second flat plate conductor portions 23a and 23b are arranged in the direction of propagation X of the electromagnetic wave in the dielectric portion 22 and the thickness direction Z that is the stacking direction of the first and second dielectric portions 25 and 26, respectively.
- the width direction Y which is a vertical direction
- the dielectric portion 22 is sandwiched, that is, provided on both sides of the first and second dielectric portions 25 and 26.
- the first and second flat plate conductor portions 23a, 23b have conductivity, are formed in a plate shape, and surfaces facing the dielectric portion 22 are provided in parallel to each other.
- the first and second flat plate conductor portions 23a and 23b are respectively laminated on the end face in the width direction Y of the dielectric portion 22, and are formed over the entire end face in the width direction Y.
- the thickness of the first and second flat plate conductor portions 23a, 23b, that is, the thickness in the width direction Y is selected to be larger than the skin thickness with respect to the electromagnetic wave propagating through the dielectric portion 22.
- the distance L1 between the first and second plate conductor portions 23a and 23b is selected to be less than or equal to one half of the wavelength of the electromagnetic wave propagating through the second dielectric portion 26.
- the first and second electrodes 24 a and 24 b are provided with the dielectric portion 22 sandwiched in the thickness direction Z, that is, provided on both sides of the dielectric portion 22.
- the first and second electrodes 24a and 24b are provided symmetrically with respect to a virtual plane that is perpendicular to the thickness direction Z.
- the first and second electrodes 24a, 24b are provided on both end surfaces of the dielectric portion 22 in the thickness direction Z, respectively.
- the first and second electrodes 24a and 24b are provided between both end portions of the dielectric portion 22 in the propagation direction X, and are provided separately from the first and second flat plate conductor portions 23a and 23b, respectively.
- the first and second electrodes 24a, 24b are formed in a rectangular parallelepiped shape, and, for example, 1 ⁇ m from both end surfaces of the second dielectric part 26 in the width direction Y except for both end parts in the width direction Y of the dielectric part 22. It is laminated on the second dielectric part 26 except in the range of ⁇ to 50 / ⁇ m.
- the first and second electrodes 24a and 24b are formed in parallel to each other with the surface forces facing the dielectric portion 22, and the interval L4 is formed less than the interval L1.
- the first and second electrodes 24a, than the distance L1, 24b is close to the first dielectric part 25 at a lower voltage compared to the case where the dielectric constant of the first dielectric part 25 is changed by applying a voltage to the first and second plate conductor parts 23a, 23b.
- the dielectric constant of can be changed.
- the interval L4 is preferably selected to be at least 1/10 of the interval L1 and smaller than L1. Since the amount of change increases as the electric field strength increases, the voltage applied between the first and second electrodes 24a and 24b can be reduced by the voltage application means 19 in which the distance L4 is reduced.
- the distance L4 is preferably set to 1/10 or more of the distance L1. Further, by selecting the interval L4 to be smaller than the interval L1, it is possible to apply an electric field to the change portion more effectively than to apply an electric field between the first and second flat plate conductor portions 23a and 23b. it can.
- a voltage applying means 19 is connected to the first and second electrodes 24a, 24b.
- the cutoff frequency fc of the transmission line formed by the dielectric portion 22 and the first and second flat plate conductor portions 23a and 23b is the dielectric constant of the dielectric forming the first dielectric portion 25. And the size of the first dielectric portion 25, the interval L4, the interval Ll, and the dielectric constant of the dielectric forming the second dielectric portion 26.
- the cut-off frequency is fc, and the operating frequency, that is, the dielectric part 22 is propagated.
- the frequency of the electromagnetic wave to be applied is f, 1. 03 ⁇ f / fc ⁇ l.
- the length L5 of the propagation direction X of the first dielectric part 25 to which an electric field is applied by the first and second electrodes 24a and 24b is selected to a length that can provide the necessary phase change.
- the electromagnetic wave propagates mainly through the first dielectric portion 25 sandwiched between the first and second flat plate conductor portions 24a, 24b and the second dielectric portion 26.
- the dielectric constant of the first dielectric part 25 By changing the dielectric constant of the first dielectric part 25, the influence on the phase change of the electromagnetic wave can be increased, and the line length for obtaining the required phase change can be shortened. Small Can be formed.
- the distance L4 is smaller than the distance L1, a large electric field can be applied to the first dielectric part 25 at a low voltage.
- first dielectric part 25 is sandwiched between the first and second electrodes 24a and 24b, that is, if the first and second electrodes 24a and 24b are provided in contact with both sides of the first dielectric part 25, it is cut.
- the second dielectric part 26 having a dielectric constant smaller than the dielectric constant of the first dielectric part 25 is interposed between the first dielectric part 25 and the electrode. Therefore, the electromagnetic wave at the electrode part is attenuated, so that the cut-off state can be prevented.
- the first and second electrodes 24a and 24b are provided and an electric field is applied to the first dielectric portion 25, so that the phase shifter 170 can be stably operated near the cutoff frequency.
- the frequency of the electromagnetic wave propagating through the dielectric portion 22 can be selected to be close to the cutoff frequency. Since a large phase change can be obtained in the vicinity of the cutoff frequency even with a short line length, the phase shifter 170 can be formed in a small size. Further, by selecting the frequency of the electromagnetic wave propagating through the dielectric part 22 so as to be in the vicinity of the cutoff frequency, the dimension of the cross section perpendicular to the propagation direction of the electromagnetic wave of the dielectric part 2 is also reduced. Since the distance between the two electrodes 24a and 24b approaches, a large electric field can be applied to the dielectric part 2 at a low voltage, and a large phase change can be stably obtained with a small voltage.
- a phase shifter 170 can be realized.
- the interval between the first and second flat plate conductor portions 23a, 23b is set to half or less of the wavelength of the electromagnetic wave propagating in the second dielectric portion 26.
- the interval between the first and second flat plate conductor portions 23a and 23b may be larger than half of the wavelength in the second dielectric portion 26.
- the first and second plate conductor portions 23a, 23b and the dielectric portion 22 form an H guide, and the transmission loss is larger than that of the phase shifter 170 of the embodiment shown in FIG. Similar effects can be achieved.
- the first and second electrodes 24a, 24b are formed from the first input / output end 22a to the second input / output end 22b in the propagation direction X, but the first and second electrodes 24a , 24b may be formed continuously in the propagation direction X.
- the first dielectric portion 25 is made of a material whose dielectric constant changes.
- the first dielectric portion 25 may be configured to include a changing portion made of a substance whose dielectric constant changes. The changing portion is preferably formed in a portion where the electric field strength of the propagating electromagnetic wave is high, for example, in the central portion in the width direction Y and the thickness direction Z.
- phase shifter having the same size was produced according to the proportion of the dielectric part 2 occupied by the changed part and the region of the dielectric part 2 where the changed part is formed.
- the phase change amount sometimes obtained is determined, and the phase change amount is smaller than the case where the entire first dielectric portion 25 is made of a substance whose dielectric constant changes, but as in the above-described embodiment, A small phase shifter can be provided.
- FIG. 22 is a perspective view schematically showing a connection structure 230 between the phase shifter 20 and the microstrip line 231.
- connection structure 230 between the phase shifter 20 and the microstrip line 231 is simply referred to as a “connection structure 230”.
- 23 is a cross-sectional view of the connection structure 230 in a virtual plane that includes the axis A2 along the propagation direction X of the phase shifter 20 and is perpendicular to the thickness direction Z.
- FIG. 24 shows the propagation direction of the phase shifter 20.
- 6 is a cross-sectional view of the connection structure 230 in a virtual plane including an axis A2 along X and perpendicular to the width direction Y.
- the dimension of width direction Y and thickness direction Z of first dielectric part 25 is the ratio of the long side to the length of the short side in the cross section perpendicular to propagation direction X. Is increased until only the LSE mode propagates, and the LSE mode is selected to propagate near the cutoff. Further, the cutoff frequency of the LSE mode is selected to be lower than the frequency of the electromagnetic wave propagating through the first dielectric portion 25.
- the first and second electrodes 24a and 24b can be provided closer to each other. Therefore, the voltage required to obtain a predetermined phase change can be further reduced.
- a microstrip line 231 which is a planar line, is connected to at least one of the first input / output terminal 22 a and the second input / output terminal 22 b of the phase shifter 20.
- the microstrip line 231 is connected to the first input / output terminal 22a of the phase shifter 20.
- connection structure 230 the first end face in the propagation direction of the electromagnetic wave in phase shifter 20 and the first end face in the propagation direction of the electromagnetic wave in microstrip line 231 are abutted and connected.
- the microstrip line 231 includes a microstrip dielectric part 232, a strip conductor part 233 provided in the microstrip dielectric part 232, and a ground conductor part 234.
- the strip conductor portion 233 and the ground conductor portion 234 are provided with a space therebetween.
- the strip conductor portion 233 and the ground conductor portion 234 are formed of the same material as the first and second flat plate conductor portions 23a and 23b described above.
- the microstrip dielectric part 232 is formed of the same material as the second dielectric part 26 described above, and is formed of a dielectric having a dielectric constant equal to the dielectric constant of the second dielectric part 26. By forming the microstrip dielectric part 232 with a dielectric having a dielectric constant equal to the dielectric constant of the second dielectric part 26, a connection structure with low reflection can be obtained.
- the microstrip dielectric part 232 is formed in a plane on both sides in the thickness direction Z, and has a rectangular parallelepiped shape in the embodiment of the present invention.
- a strip conductor portion 233 is formed by laminating the central portion 236 in the width direction Y.
- the strip conductor portion 233 has a rectangular parallelepiped shape.
- the strip conductor portion 233 extends along the propagation direction X. The length in the width direction Y of the strip conductor portion 233 is selected to be less than the interval L1.
- a ground conductor portion 234 is formed on the second surface portion 238 in the thickness direction Z of the microstrip dielectric portion 232.
- the ground conductor portion 234 is formed over the entire surface of the second surface portion 238.
- the end surface 241 facing the phase shifter 20 and the first input / output end 22a A non-radiative dielectric line formed by the dielectric portion 22 and the first and second flat plate conductor portions 23a and 23b and the strip conductor portion 233 are brought into contact with the end surface 242 of the first dielectric portion 25.
- the microstrip line 231 is coupled to the LSE mode of the non-radiative dielectric line formed by the dielectric part 22 and the first and second flat conductor parts 23a and 23b.
- the phase shifter 20 of the strip conductor 233 The center of the end surface 241 is connected to the center of the end surface 242 of the first dielectric part 25.
- the dimension in the width direction Y of the microstrip dielectric part 232 is selected to be equal to the length between the outer surfaces of the first and second plate conductor parts 23a, 23b in the width direction Y of the phase shifter 20.
- the strip conductor part 233 and the microstrip are arranged so that the longitudinal direction in the cross section perpendicular to the propagation direction X of the strip conductor part 233 and the longitudinal direction in the cross section perpendicular to the propagation direction X of the first dielectric part 25 coincide.
- the strip conductor portion 233 and the first dielectric portion 25 are connected so that the lamination direction of the dielectric portion 232 and the ground conductor portion 234 and the lamination direction of the first and second dielectric portions 25 and 26 are aligned. As a result, the degree of freedom in designing the strip conductor portion 233 can be improved.
- the microstrip dielectric part 232 is provided in contact with the first input / output end 22a.
- the ground conductor 234 is provided in contact with the first and second flat conductor portions 23a and 23b.
- the ground conductor 234 is provided so as not to contact the first and second flat plate conductors 23a and 23b.
- the strip conductor portion 233 does not contact the first and second electrodes 24a and 24b.
- the length in the width direction Y and the thickness direction Z of the strip conductor part 233 is the characteristic impedance force of the microstrip line 231 and the nonradiative property formed by the dielectric part 22 and the first and second flat conductor parts 23a and 23b. It is chosen to match the characteristic impedance of the dielectric line.
- the high-frequency electromagnetic field distribution of the microstrip line 231 is the LSE of the non-radiative dielectric line formed by the dielectric part 22 and the first and second plate conductor parts 23a and 23b. Since it approximates the electromagnetic field distribution of the mode, the electromagnetic field smoothly transitions at the connection between the microstrip line 231 and the phase shifter 20. Therefore, the connection loss between the microstrip line 231 and the phase shifter 20 can be reduced. In addition, since a high-frequency signal in the LSE mode can be satisfactorily taken out to the microstrip line 231, an electrical connection between the phase shifter 20 and an electronic circuit that is mounted on the substrate and uses the high-frequency signal passing through the phase shifter 20 Connection reliability can be improved.
- the phase shifter 20 and the microstrip line 231 may be integrally formed to constitute a phase shifter with a microstrip line.
- phase shifters 30 and 40 are also microstrip. Connect to the cable 231.
- FIG. 25 is a perspective view schematically showing a connection structure 250 between the phase shifter 20 and the strip line 251.
- connection structure 250 between the phase shifter 20 and the strip line 251 is simply referred to as “connection structure 250”.
- 26 is a cross-sectional view of the connection structure 250 in a virtual plane perpendicular to the thickness direction Z, including the axis A2 along the propagation direction X of the phase shifter 20, and
- FIG. 10 is a cross-sectional view of the connection structure 250 in a virtual plane including an axis A2 along the direction X and perpendicular to the width direction Y.
- FIG. 28 is a cross-sectional view taken along section line ⁇ - ⁇ of FIG. Since the connection structure 250 is similar to the connection structure 230 shown in FIG. 22 and has the same configuration, the same parts are denoted by the same reference numerals, and the description thereof is omitted.
- a strip line 251 is connected to at least one of the first input / output terminal 22a and the second input / output terminal 22b of the phase shifter 20.
- the strip line 251 is connected to the first input / output terminal 22a of the phase shifter 20
- the strip line 251 is connected to the second input / output terminal 22b of the phase shifter 20.
- connection structure 250 the first end face in the propagation direction of the electromagnetic wave in phase shifter 20 and the first end face in the propagation direction of the electromagnetic wave in strip line 251 are abutted and connected.
- the strip line 251 includes a strip dielectric part 252, a strip conductor part 233 provided in the strip dielectric part 252, and a ground conductor part 254.
- the strip conductor portion 233 and the ground conductor portion 234 are provided with a space therebetween.
- the strip dielectric portion 252 is formed of the same material as the microstrip dielectric portion 232 described above, and the ground conductor portion 254 is formed of the same material as the above-described ground conductor portion 234.
- the strip dielectric part 252 has a rectangular parallelepiped shape.
- a ground conductor portion 254 is formed on the surface portion of the strip dielectric portion 252 in the thickness direction Z and the width direction Y.
- the ground conductor 254 surrounds the strip dielectric part 252 around the axis extending in the propagation direction X.
- the strip conductor part 233 is embedded in the center of the strip dielectric part 252 and is provided in the strip direction in the propagation direction X. It is formed between both ends of the body part 252.
- the strip conductor portion 233 has a protruding portion 256 that protrudes toward the phase shifter 20 relative to the end face 255 that contacts the phase shifter 20 of the strip dielectric portion 252.
- Strip line of first dielectric part 25 An insertion hole 258 into which the protrusion 256 is inserted is formed in the end 257 facing the path 251.
- the insertion hole 258 is formed in the same size as the protrusion 256.
- the length L22 in the direction along the propagation direction X of the protrusion 256 and the insertion hole 258 is selected to be approximately (2n-l) / 4 (n is a natural number) of the wavelength of the propagating electromagnetic wave at the protrusion 256.
- phase difference between the electromagnetic wave reflected at the interface between the strip line 251 and the electromagnetic wave reflected at the interface between the tip of the protrusion 256 and the first dielectric part 25 is ⁇ (rad) to cancel the reflected wave.
- the strip dielectric portion 252 and the first and second dielectric portions 25 and 26 are connected in contact with each other.
- the ground conductor 254 is provided in contact with the first and second flat conductor portions 23a and 23b.
- the ground conductor 254 is provided in non-contact with the first and second electrodes 24a and 24b.
- the strip line 251 is coupled to the LSE mode of the non-radiative dielectric line formed by the dielectric part 22 and the first and second flat conductor parts 23a and 23b.
- the strip conductor portion 233 and the first dielectric portion 25 are provided coaxially.
- the dimension in the width direction Y of the strip line 251 is selected to be equal to the length between the outer surfaces of the first and second plate conductor portions 23a and 23b in the width direction Y of the phase shifter 20, and the thickness of the strip line 251
- the dimension in direction Y is chosen to be equal to the length between the outer surfaces in the thickness direction Z of phase shifter 20.
- the strip conductor part 233 and the first conductor part 233 are aligned so that the longitudinal direction in the cross section perpendicular to the propagation direction X of the strip conductor part 233 and the longitudinal direction in the cross section perpendicular to the propagation direction X of the first dielectric part 25 coincide.
- the dielectric part 25 is connected.
- the length of the strip conductor portion 233 in the width direction Y and the thickness direction Z is determined by the characteristic impedance of the strip line 251 formed by the dielectric portion 22 and the first and second flat plate conductor portions 23a and 23b. If the above configuration is selected so as to match the characteristic impedance of the non-radiative dielectric line, the high-frequency electromagnetic field distribution of the strip line 251 has the dielectric part 22 and the first and second flat conductor parts 23a. , 23b, and the LSE mode electromagnetic field distribution of the nonradiative dielectric line, so that the stripline 251 and the phase shifter 20 Since the electromagnetic field smoothly transitions at the connecting portion, connection loss can be reduced.
- the phase shifter 20 is electrically connected to the electronic circuit that is mounted on the substrate and uses the high-frequency signal that passes through the phase shifter 20. Connection reliability can be improved.
- phase shifter 20 and the strip line 251 may be integrally formed to constitute a phase shifter with a strip line.
- phase shifters 30 and 40 described above may be used in connection with the strip line 251 as in the case of the phase shifter 20!
- the projecting portion 256 may be provided in the strip conductor portion 233, and the projecting portion 256 may be inserted into the insertion hole 258 provided in the first dielectric portion 25.
- FIG. 29 is a perspective view schematically showing a connection structure 330 between the phase shifter 170 and the microstrip line 31.
- connection structure 330 between the phase shifter 170 and the microstrip line 231 is simply referred to as a “connection structure 330”.
- Fig. 30 is a cross-sectional view of the connection structure 330 in a virtual plane that includes the axis A3 along the propagation direction X of the phase shifter 170 and is perpendicular to the thickness direction Z.
- Fig. 31 shows the propagation of the phase shifter 170.
- FIG. 10 is a cross-sectional view of the connection structure 330 in a virtual plane including the axis A3 along the direction X and perpendicular to the width direction Y.
- the dimension of width direction Y and thickness direction Z of first dielectric part 25 is the ratio of the long side to the short side length in the cross section perpendicular to propagation direction X, and the LSM mode is cut off. Is increased until only the LSE mode propagates, and the LSE mode is selected to propagate near the cutoff. Further, the cutoff frequency of the LSE mode is selected to be lower than the frequency of the electromagnetic wave propagating through the first dielectric portion 25.
- a microstrip line 231 that is a planar line is connected to at least one of the first input / output terminal 22a and the second input / output terminal 22b of the phase shifter 170.
- the case where the microstrip line 231 is connected to the first input / output terminal 22a of the phase shifter 170 is shown, but the case where the microstrip line 231 is connected to the second input / output terminal 22b of the phase shifter 170 is shown.
- connection structure 330 the first end face in the propagation direction of electromagnetic waves in phase shifter 170 and the first end face in the propagation direction of electromagnetic waves in microstrip line 231 are Butt and connect.
- the first dielectric portion 25 is selected so as not to contact the first and second electrodes 24a, 24b.
- the end face 241 facing the phase shifter 170 and the end face 242 of the first dielectric part 25 of the first input / output end 22a are brought into contact with each other to form a dielectric.
- the non-radiative dielectric line formed by the portion 22 and the first and second flat plate conductor portions 23a and 23b and the strip conductor portion 233 are coupled.
- the microstrip line 231 is coupled to the LSE mode of the non-radiative dielectric line formed by the dielectric part 22 and the first and second flat conductor parts 23a and 23b.
- the center of the end face 241 facing the phase shifter 170 of the strip conductor part 233 is connected to the center of the end face 242 of the first dielectric part 25.
- the dimension in the width direction Y of the microstrip dielectric part 232 is selected to be equal to the length between the outer surfaces of the first and second plate conductor parts 23a, 23b in the width direction Y of the phase shifter 170.
- the strip conductor part 233 and the microstrip are arranged so that the longitudinal direction in the cross section perpendicular to the propagation direction X of the strip conductor part 233 and the longitudinal direction in the cross section perpendicular to the propagation direction X of the first dielectric part 25 coincide.
- the strip conductor portion 233 and the first dielectric portion 25 are connected so that the lamination direction of the dielectric portion 232 and the ground conductor portion 234 and the lamination direction of the first and second dielectric portions 25 and 26 are aligned. As a result, the degree of freedom in designing the strip conductor portion 233 can be improved.
- the microstrip dielectric part 235 is provided in contact with the first input / output end 22a.
- the ground conductor portion 234 is provided continuously with the second electrode portion 24b.
- the ground conductor 234 is provided so as not to contact the first and second flat plate conductors 23a and 23b.
- the length in the width direction Y and the thickness direction Z of the strip conductor part 233 is the characteristic impedance force of the microstrip line 231 and the nonradiative property formed by the dielectric part 22 and the first and second flat conductor parts 23a and 23b. It is chosen to match the characteristic impedance of the dielectric line.
- the high-frequency electromagnetic field distribution of the microstrip line 231 is the LSE of the non-radiative dielectric line formed by the dielectric part 22 and the first and second plate conductor parts 23a and 23b. Since it approximates the electromagnetic field distribution of the mode, the electromagnetic field smoothly transitions at the connection between the microstrip line 231 and the phase shifter 170. Therefore, micro The connection loss between the strip line 231 and the phase shifter 170 can be reduced. In addition, since the high-frequency signal in the LSE mode can be satisfactorily taken out to the microstrip line 231, the electrical connection between the phase shifter 170 and an electronic circuit that is mounted on the substrate and uses the high-frequency signal that passes through the phase shifter 170. Connection reliability can be improved.
- phase shifter 170 and the microstrip line 231 may be integrally formed to constitute a phase shifter with a microstrip line.
- FIG. 32 is a perspective view schematically showing a connection structure 350 between the phase shifter 170 and the strip line 251.
- connection structure 350 between the phase shifter 170 and the strip line 251 is simply referred to as “connection structure 350”.
- Fig. 33 is a cross-sectional view of the connection structure 350 in a virtual plane including the axis A3 along the propagation direction X of the phase shifter 170 and perpendicular to the thickness direction Z.
- Fig. 34 shows the propagation direction of the phase shifter 170.
- FIG. 6 is a cross-sectional view of the connection structure 350 in a virtual plane including an axis A3 along X and perpendicular to the width direction Y.
- FIG. 35 is a sectional view taken along section line XII-II in FIGS. 33 and 34.
- connection structure 350 is similar to the connection structure 330 shown in FIG. 29 and has the same configuration. Therefore, the same parts are denoted by the same reference numerals, and the description thereof is omitted.
- a strip line 251 is connected to at least one of the first input / output terminal 22a and the second input / output terminal 22b of the phase shifter 170.
- the force shown when the strip line 251 is connected to the first input / output terminal 22a of the phase shifter 170 is also shown when the strip line 251 is connected to the second input / output terminal 22b of the phase shifter 170. It is the same.
- connection structure 350 the first end face in the propagation direction of the electromagnetic wave in phase shifter 170 and the first end face in the propagation direction of the electromagnetic wave in strip line 251 are abutted and connected.
- the strip conductor portion 233 has a protruding portion 256 that protrudes toward the phase shifter 170 rather than the end face 255 that contacts the phase shifter 170 of the strip dielectric portion 252.
- An insertion hole 258 into which the protruding portion 256 is inserted is formed in the end portion 257 of the first dielectric portion 25 facing the strip line 251.
- the insertion hole 258 is formed in the same size as the protrusion 256.
- the protrusion 256 is provided by being inserted into the insertion hole 258.
- the length of the protrusion 256 and the insertion hole 258 in the direction along the propagation direction X is selected in the same manner as the length L22 described above, thereby reducing loss. Can do.
- the strip dielectric portion 252 and the first and second dielectric portions 25 and 26 are connected in contact with each other.
- the ground conductor 254 is provided in contact with the first and second flat conductor portions 23a and 23b.
- the ground conductor 254 is provided in non-contact with the first and second electrodes 24a and 24b.
- the ground conductor 254 and the first and second electrodes 24a and 24b are provided, for example, 1 ⁇ m to 50 ⁇ m apart.
- the strip line 251 is coupled to the LSE mode of the non-radiative dielectric line formed by the dielectric part 22 and the first and second flat conductor parts 23a and 23b.
- the strip conductor portion 233 and the first dielectric portion 25 are provided coaxially.
- the dimension in the width direction Y of the strip line 251 is selected to be equal to the length between the outer surfaces of the first and second plate conductor portions 23a and 23b in the width direction Y of the phase shifter 170, and the thickness of the strip line 251
- the dimension in the direction Y is selected to be equal to the length between the outer surfaces of the first and second electrodes 24a and 24b in the thickness direction Z of the phase shifter 170.
- the strip conductor part 233 and the first conductor part 233 are aligned so that the longitudinal direction in the cross section perpendicular to the propagation direction X of the strip conductor part 233 and the longitudinal direction in the cross section perpendicular to the propagation direction X of the first dielectric part 25 coincide.
- the dielectric part 25 is connected.
- the length of the strip conductor portion 233 in the width direction Y and the thickness direction Z is determined by the characteristic impedance of the strip line 251 formed by the dielectric portion 22 and the first and second flat plate conductor portions 23a and 23b. If the above configuration is selected so as to match the characteristic impedance of the non-radiative dielectric line, the high-frequency electromagnetic field distribution of the strip line 251 has the dielectric part 22 and the first and second flat conductor parts 23a. , 23b, and the electromagnetic field distribution in the LSE mode of the nonradiative dielectric line formed by can do .
- phase shifter 170 and the strip line 251 may be integrally formed to constitute a phase shifter with a strip line.
- the protruding portion 256 may be provided in the strip conductor portion 233, and the protruding portion 256 may be inserted into the insertion hole 258 provided in the first dielectric portion 25.
- FIG. 36 is a schematic diagram showing the configuration of the high-frequency transmitter 260 according to the embodiment of the present invention.
- the high-frequency transmitter 260 includes the phase shifter 20, the high-frequency oscillator 261, the transmission line 262, the transmission antenna 263, and the stub 264 of the embodiment shown in FIG.
- the high-frequency transmission line is simply referred to as a transmission line.
- the high-frequency oscillator 261 includes a gun oscillator using a gun diode, an impatting oscillator using an impatt diode, or an MMIC (Microwave Monolithic Integrated Circuit) oscillator using an FET (Field Effect Transistor). Generate a signal.
- the transmission line 262 is configured by a microstrip line or a strip line.
- the first end 262 a of the transmission line 262 in the high-frequency signal transmission direction is connected to the high-frequency oscillator 261, and the second end 262 b of the transmission line 262 in the high-frequency signal transmission direction is connected to the transmitting antenna 263.
- the transmitting antenna 263 is realized by a notch antenna or a horn antenna.
- the transmission direction of the high frequency signal is the propagation direction of the electromagnetic wave.
- the phase shifter 20 is inserted into the transmission line 262 so that the high-frequency signal passes through the dielectric part 22 via the microstrip line 231 or the stripline 251 described above.
- the stub 264 is realized by an open stub, for example, and functions as a characteristic adjustment circuit of the high-frequency oscillator 261.
- the stub 264 is provided on the transmission line 262 on at least one of the upstream side and the downstream side of the phase shifter 20 in the high-frequency signal transmission direction.
- the transmission line 262 includes first and second transmission lines 268 and 269.
- the first end portion 268a in the high-frequency signal transmission direction of the first transmission line 268 is connected to the high-frequency oscillator 261, and the second end portion 268b in the high-frequency signal transmission direction of the first transmission line 268 is the phase shifter. It is connected to 20 first input / output terminals 22a.
- the first end 269a of the second transmission line 269 in the high-frequency signal transmission direction is connected to the second input / output of the phase shifter 20.
- the second end 269b of the second transmission line 269 in the high-frequency signal transmission direction is connected to the transmission antenna 263.
- the high-frequency signal generated by the high-frequency oscillator 261 passes through the first transmission line 268, the dielectric part 22 of the phase shifter 20, and the second transmission line 268, and is given to the transmitting antenna 263. From the transmitting antenna 263 Radiated as radio waves.
- a stub 264 is provided in the middle of the high-frequency oscillator 261 and the transmission antenna 263, and the connection portion of the high-frequency oscillator 261 to the transmission line 262 or the connection portion of the transmission antenna 263 to the transmission line 262 is provided.
- the inconsistency in can be matched. As a result, reflection at the connecting portion can be suppressed to a small level, and stable oscillation characteristics can be obtained, and insertion loss can be suppressed to a low level, so that a high transmission output can be obtained.
- the phase shifter 20 is inserted into the transmission line 262 so that the electromagnetic wave of the high-frequency signal transmitted through the transmission line 262 passes through the dielectric part 22, so that, for example, the high-frequency oscillator 261 It is possible to individually adjust the phase shift caused by the transmission line 262 due to variations in the shape of the wire and Z or bump to connect the wires, and the variation in the wiring width of the transmission line. Therefore, it is possible to realize a high-frequency transmitter 260 having a stable oscillation characteristic and a high transmission output since the insertion loss is suppressed to a low level. Further, since the phase shifter 20 is small and can be operated at a low voltage as described above, the high-frequency transmitter 260 can be made small even if the phase shifter 20 is provided. It is possible to prevent the configuration for applying a voltage to 20 from becoming complicated.
- the force using the phase shifter 20 is changed to the phase shifter 20, and the phase shifter 30 of the above-described embodiments, etc. ! /, One may be used. Even if comprised in this way, the same effect can be achieved.
- the transmission line 262 is realized by a coplanar line, a grounded coplanar line, a slot line, a waveguide, or a dielectric waveguide in addition to the microstrip line and the strip line. Also good.
- FIG. 37 is a schematic diagram showing the configuration of the high-frequency receiver 270 according to the embodiment of the present invention. The same configuration as that of the high-frequency transmitter 260 of the above-described embodiment shown in FIG. In some cases, the reference numerals are attached and the description thereof is omitted.
- the high-frequency receiver 270 includes the phase shifter 20, the high-frequency detector 271, the transmission line 262, the stub 264, and the receiving antenna 273 according to the above-described embodiment.
- the high-frequency detector 271 is realized by, for example, a Schottky Noria diode detector, a video detector, or a mixer MMIC.
- the first end 262a of the transmission line 262 in the high-frequency signal transmission direction is connected to the high-frequency detector 271 and the second end 262b of the transmission line 262 in the high-frequency signal transmission direction is connected to the receiving antenna 273.
- the receiving antenna 273 is realized by a patch antenna or a horn antenna.
- the phase shifter 20 is inserted into the transmission line 262 so that the high-frequency signal passes through the dielectric part 22.
- the stub 264 is provided on the transmission line 262 on at least one of the upstream side and the downstream side of the phase shifter 20 in the high-frequency signal transmission direction.
- the receiving antenna 273 When a radio wave arriving at an external force is captured by the receiving antenna 273, the receiving antenna 273 applies a high-frequency signal based on the radio wave to the transmission line 262, passes through the dielectric part 22 of the phase shifter 20, and enters the high-frequency detector 271. A received high frequency signal is provided.
- the high frequency detector 271 detects a high frequency signal and detects information included in the high frequency signal.
- the high frequency signal captured by the receiving antenna 273 is transmitted to the transmission line 262 and detected by the high frequency detector 271.
- a stub 264 is provided in the middle of the receiving antenna 27 3 and the high frequency detector 271 to match the mismatch at the connection of the high frequency detector 271 to the transmission line 262 and the connection of the receiving antenna 273 to the transmission line 262. I can do it.
- reflection at the connection portion can be suppressed to a low level, and stable detection characteristics can be obtained, and a high detection output can be obtained because the insertion loss is suppressed to a low level.
- the phase shifter 20 is inserted into the transmission line 262 so that the electromagnetic wave of the high-frequency signal transmitted through the transmission line 262 passes through the dielectric part 22.
- the phase shift caused by the transmission line 262 due to variations in the shape of the wire and Z or bump for connecting the high-frequency detector 271 and the wiring width of the transmission line, etc., is individually adjusted for matching. It is stable because of its stable detection characteristics and low insertion loss.
- a high-frequency receiver 270 having a high detection output can be realized.
- the phase shifter 20 is small and can be operated at a low voltage as described above, the high-frequency receiver 270 can be made small even if the phase shifter 20 is provided, and the phase shifter 20 It is possible to prevent the configuration for applying a voltage from being complicated.
- FIG. 38 is a schematic diagram showing a configuration of a radar apparatus 290 including the high-frequency transceiver 280 according to the embodiment of this invention.
- the radar device 290 includes a high frequency transceiver 280 and a distance detector 291.
- the high frequency transmitter / receiver 280 includes the phase shifter 20, the high frequency oscillator 261, the first to fifth transmission lines 281, 282, 283, 284, 285, the branching unit 286, and the branching unit 287 of the above-described embodiment.
- the transmitting / receiving antenna 288 is realized by a notch antenna or a horn antenna.
- the first to fifth transmission lines 281, 282, 283, 284, 285 have the same configuration as the transmission line 262 described above.
- the first end 281a of the first transmission line 281 in the high-frequency signal transmission direction is connected to the high-frequency oscillator 261, and the second end 281b of the first transmission line 281 in the high-frequency signal transmission direction is the branch 286.
- the phase shifter 20 is inserted into the first transmission line 281 so that the high-frequency signal passes through the dielectric part 22.
- the stub 264 is provided in the first transmission line 281 on at least one of the upstream side and the downstream side of the phase shifter 20 in the high-frequency signal transmission direction.
- the branching device (switching device) 286 has first, second, and third terminals 286a, 286b, and 286c. A high-frequency signal supplied to the first terminal 286a is selectively applied to the second terminal 286b and the third terminal 286c. Output to.
- the branching device 286 is realized by, for example, a high frequency switch element.
- the branching device 286 is supplied with a control signal from a control unit (not shown) and based on the control signal, Selectively connect 1 terminal 286a and 2nd terminal 286b, or 1st terminal 286a and 3rd terminal 286c.
- the branching unit 286 is realized by a directional coupler, for example.
- the radar device 290 is realized by a pulse radar.
- the controller connects the first terminal 286a and the second terminal 286b, outputs a pulsed high-frequency signal from the second terminal 286b, and then connects the first terminal 286a and the third terminal 286c.
- the high frequency signal is output from the third terminal 286c.
- a first end 282a of the second transmission line 282 in the transmission direction of the high-frequency signal is connected to the second terminal 286b.
- the third terminal 286c is connected to the first end 284a of the fourth transmission line 284 in the transmission direction of the high frequency signal.
- the duplexer 287 has fourth, fifth, and sixth terminals 287a, 287b, and 287c, outputs a high frequency signal applied to the fourth terminal 287a to the fifth terminal 287b, and is applied to the fifth terminal 287b. Output high frequency signal to terminal 6 287c.
- a second end 282b of the second transmission line 282 in the high-frequency signal transmission direction is connected to the fourth terminal 287a.
- a first end 283a of the third transmission line 283 in the high-frequency signal transmission direction is connected to the fifth terminal 287b.
- a second end 283 b of the third transmission line 283 in the high-frequency signal transmission direction is connected to the transmission / reception antenna 288.
- the sixth terminal 288c is connected to the first end portion 285a of the fifth transmission line 285 in the transmission direction of the high-frequency signal.
- the second end 284 b of the fourth transmission line 284 in the high-frequency signal transmission direction and the second end 285 b of the fifth transmission line 285 in the high-frequency signal transmission direction are connected to the mixer 289.
- the duplexer 287 is realized by a hybrid circuit.
- the hybrid circuit is a directional coupler, and is realized by magic T, micro, hybrid ring or rat race.
- the high-frequency signal generated by the high-frequency oscillator 261 passes through the first transmission line 281 and the dielectric part 22 of the phase shifter 20, and passes through the branching unit 286, the second transmission line 282, the duplexer 287, and the third transmission line 282. Is transmitted to the transmission / reception antenna 288 and radiated as radio waves from the transmission / reception antenna 288.
- the high-frequency signal generated by the high-frequency oscillator 261 passes through the first transmission line 281 and the dielectric part 22 of the phase shifter 20 and is supplied as a local signal to the mixer 289 via the branching unit 286 and the fourth transmission line 284. Given.
- the transmitting / receiving antenna 288 When radio waves arriving from external force are received by the transmitting / receiving antenna 288, the transmitting / receiving antenna The tenor 288 gives a high-frequency signal based on the radio wave to the third transmission line 283, and is given to the mixer 289 via the duplexer 287 and the fifth transmission line 285.
- the mixer 289 mixes the high frequency signals given from the fourth and fifth transmission lines 284 and 285 and outputs an intermediate frequency signal.
- the intermediate frequency signal output from the mixer 289 is supplied to the distance detector 291.
- the distance detector 291 includes the high frequency detector 271 described above, and is based on the intermediate frequency signal obtained by receiving the radio wave (echo) radiated from the high frequency transmitter / receiver 280 and reflected by the measurement object. Thus, the distance from the high-frequency transceiver 280 to the measurement object, for example, the distance between the transmission / reception antenna 288 and the measurement object is calculated.
- the distance detector 291 is realized by a microcomputer, for example.
- the phase shifter 20 is inserted into the first transmission line 281 so that a high frequency signal passes through the dielectric part 22, and for example, transmission is performed due to variation in wiring width.
- a high-frequency transceiver 280 having a stable oscillation characteristic and a high transmission output to suppress the insertion loss is realized.
- a high-frequency transceiver 280 having a stable detection characteristic and a high detection output due to a small insertion loss can be realized, and an intermediate frequency generated by a mixer 289, for example. The reliability of the signal can be improved.
- the phase shifter 20 is small and can be operated at a low voltage as described above, the high-frequency transmitter / receiver 280 can be formed small even if the phase shifter 20 is provided. It is possible to prevent the configuration for applying a voltage to 20 from becoming complicated.
- the distance detector since the distance detector detects the distance to the detection target based on the intermediate frequency signal from the high frequency transmitter / receiver 280, the distance to the detection target can be accurately detected.
- the branching device 286 is realized by a directional coupler in this embodiment, in this case, the high-frequency signal applied to the first terminal 286a is branched to the second terminal 286b and the third terminal 286c and output. Is done. In this case, compared with a branching device using a switch, which will be described later, the power branching device 286 that reduces the power of the radio wave output from the transmitting / receiving antenna 288 is controlled. Since it is not necessary to control, the control of the apparatus is simplified.
- the phase shifter 20 is inserted into the first transmission line 281.
- the phase shifter 20 includes at least one of the first to fifth transmission lines 281 to 285. Any one of them may be inserted so that a high-frequency signal passes through the dielectric part 22. Even with such a configuration, the same effect can be achieved.
- any one of the phase shifters of the above-described embodiments such as the phase shifter 30, is used instead of the force using the phase shifter 20. It's okay. Even if comprised in this way, the same effect can be achieved.
- FIG. 2 is a schematic diagram showing a configuration of a radar apparatus 400 including an array antenna apparatus 399 including a phase shifter 20 according to an embodiment of the present invention.
- the radar device 400 includes an array antenna device 399, a high frequency transmitter / receiver 409, and a distance detector 291.
- the array antenna device 399 includes an antenna array body 407 in which an antenna 405 with a phase shifter configured by an antenna element 401 and a phase shifter 20 added to the antenna element 401 is arranged, and each phase shifter attached.
- the plurality of antenna elements 401 are arranged in a line with their radiation directions aligned.
- the antenna elements 401 are provided at equal intervals along the arrangement direction R.
- the antenna element 401 is realized by, for example, a slot antenna, a microstrip antenna, a horn antenna, or a reflector antenna.
- antenna device 400 has eight antenna elements 401 and eight phase shifters 20.
- the transmission line 402 includes a branching unit 403, and a high frequency signal input from the input unit 404 is branched into a plurality of parts by the branching unit 403 and provided to the antenna 405 with a phase shifter.
- the transmission line 402 is realized in the same manner as the transmission line 262.
- the high frequency transmitter / receiver 409 may be configured by the high frequency transmitter / receiver 280 of each of the embodiments described above, or the high frequency transmitter / receiver 280 may not include a phase shifter. And a conventional high-frequency transmitter / receiver that receives a high-frequency signal captured by the array antenna device 399.
- the phase shifter 20 is provided between the transmission line 402 and the antenna element 401 of each antenna element 405 with a phase shifter.
- a high-frequency signal propagating through the transmission line 402 passes through the dielectric part 22 of the phase shifter 20 and is given to the antenna element 401.
- Each phase shifter 20 adjusts the phase of the radio wave radiated by each antenna element force by shifting the phase of the high-frequency signal, and the equiphase surface is arranged in the first direction R1 in the arrangement direction R as shown in FIG.
- the direction of the radiation beam 406 is changed from the front to the first direction of the arrangement direction R of the antenna element 401 by shifting the phase of the radio wave radiated from the adjacent antenna element 401 by ⁇ as it goes from the front to the second direction R2.
- the antenna device 400 Since the phase shifter 20 is small and can be operated at a low voltage, the antenna device 400 does not increase in size.
- the array antenna device 399 can change the direction of the radiation beam, and thereby change the direction of the radiation beam without mechanically operating the antenna element 401. It is possible to improve convenience.
- the radar apparatus 400 can be easily changed without increasing the size of the radar apparatus 400, so that the radar apparatus can be realized with high convenience.
- phase shifter 20 may be replaced with any one of the phase shifter 30 described above or the phase shifter of each of the embodiments described above.
- the high-frequency switch is a phase shifter having a cutoff characteristic among the phase shifters of the respective embodiments described above, that is, phase shifters 20, 30, 40, 50, 60, 130. , 14 0, 150, 160, 170 and the like.
- the “high frequency switch” is simply referred to as “switch”.
- the cutoff frequency in the dielectric portion 22 can be changed by applying a voltage to the first and second electrodes 24a and 24b.
- the voltage applying means 19 applies an alternating voltage having a frequency lower than the frequency of the propagating electromagnetic wave or a direct voltage to the first and second electrodes 24a, 24b.
- the voltage applying means 19 applies a voltage to the first and second electrodes 24a, 24b, the dielectric constant of the dielectric portion 22 is reduced, thereby increasing the cut-off frequency of the switch.
- the switch is configured such that the cut-off frequency of the switch is lower than the frequency of the electromagnetic wave to be propagated (operating frequency).
- the voltage applying means 19 can apply a voltage to the first and second electrodes 24a and 24b so that the cut-off frequency of the switch is equal to or higher than the use frequency.
- the switch has a propagation state in which the voltage application means 19 lowers the cutoff frequency force than the frequency of the electromagnetic wave propagating through the dielectric portion 22, and the cutoff frequency is higher than the frequency of the electromagnetic wave propagating through the dielectric portion 22.
- the cut-off state can be switched.
- the operating frequency is constant, and therefore ONZ OFF operation is possible by the above switching.
- the cutoff state in the dielectric part 22 is lower than the frequency of the electromagnetic wave propagating through the dielectric part 22, and the propagation state of the electromagnetic wave. Since the cutoff state higher than the frequency can be switched, the propagation state and the cutoff state can be easily switched by changing the voltage applied to the first and second electrodes 24a and 24b. .
- the switching mode is the OF F state
- the cutoff state is entered, so that an essentially high ONZOFF ratio can be obtained.
- there is no mechanical drive part it is possible to realize a highly reliable high-frequency switch with excellent durability.
- the above configuration can realize a switch that can change the cutoff frequency with a low voltage.
- the high-frequency signal in the LSE mode can be satisfactorily taken out to the planar line by the connection structure, it is possible to realize a high-frequency switch that has good mountability on the planar circuit board. Even if the voltage applied to the first and second electrodes 24a and 24b is reduced to apply an electric field to the dielectric part 22, an electric field having a large electric field strength is applied to the changed part, and the line of the dielectric part 22 Even if the length is short, a high ONZOFF ratio can be obtained because the cutoff state realizes the OFF state, thus realizing a switch that can be operated at a low voltage with a small size. can do. In addition, since there is no mechanical drive part, it is possible to realize a highly reliable V and switch with excellent durability.
- the attenuator according to the embodiment of the present invention includes the! / Slipping force of the phase shifters 20, 30, 40, 50, 60, 130, 140, 150, 160, 170, etc. according to the above-described embodiments. Has the same configuration.
- by applying a voltage to the first and second electrodes 24a, 24b it is possible to change the cutoff frequency in the dielectric portion 22 and change the propagation characteristics.
- the high frequency signal can be attenuated by changing the propagation characteristics in the dielectric portion 22 according to the electric field applied to the dielectric portion 22, and the LSE mode high frequency signal can be flattened by the connection structure.
- the attenuator is preferably 1.03 ⁇ f / fc ⁇ l.5 when the cutoff frequency is fc and the frequency used is f. It is formed so that 03 ⁇ f / fc ⁇ l. In such an attenuator, even if the voltage applied to the first and second electrodes 24a and 24b is reduced, an electric field having a large electric field strength is applied to the changing portion, and an attenuation characteristic near the cutoff frequency is used.
- the electromagnetic wave can be sufficiently attenuated even if the transmission line has a short line length, it is possible to realize a small attenuator that can be operated at a low voltage. In addition, since there is no mechanical drive part, a highly reliable attenuator with excellent durability can be realized.
- FIG. 40 is a schematic diagram showing a configuration of a high-frequency transmitter 360 according to another embodiment of the present invention.
- the high-frequency transmitter 360 has a configuration in which the high-frequency switch 361 is provided instead of the phase shifter 20 of the high-frequency transmitter 260 in FIG. 36 described above, and the stub 264 is omitted. The description is omitted.
- the switch 361 has the same configuration as the shift of the phase shifter of each embodiment described above.
- the switch 361 is inserted into the transmission line 262 via the above-described microstrip line 231 or the above-described strip line 71, and transmits a high-frequency signal transmitted to the transmission line 262 by setting the propagation state. As a result, the high-frequency signal transmitted to the transmission line 262 is blocked.
- the high-frequency signal generated by high-frequency oscillator 261 is It is transmitted to the transmission line 262, passes through the dielectric part 22 of the switch 361, is given to the transmitting antenna 263, and is radiated as a radio wave.
- the switch 361 is in the cut-off state, the high-frequency signal generated by the high-frequency oscillator 261 is not transmitted to the transmitting antenna 263 because it does not pass through the switch 361.
- a pulse signal wave can be radiated from the transmitting antenna 263.
- a high-reliability high-frequency transmitter 360 can be realized by using a high-reliability high-frequency switch with excellent durability and high ONZOFF ratio.
- the voltage applying means 19 applies a voltage to the switch 361 based on the predetermined information, and turns on / off the switch 361, thereby radiating a radio wave corresponding to the predetermined information from the transmitting antenna 263. Can do.
- the transmission line 262 may be realized by a coplanar line, a grounded coplanar line, a slot line, a waveguide, or a dielectric waveguide, in addition to the microstrip line and the strip line.
- FIG. 41 is a schematic diagram showing a configuration of a radar apparatus 390 including a high-frequency transceiver 380 according to another embodiment of the present invention.
- the high frequency transmitter / receiver 380 has a configuration in which a high frequency switch 361 is provided in place of the phase shifter 20 of the high frequency transmitter / receiver 280 of FIG. 38 described above, and thus the same reference numerals are given to the same configuration. The description is omitted.
- the high-frequency signal generated by the high-frequency oscillator 261 is transmitted to the first transmission line 281 and given to the first terminal 286a of the branching device 286.
- the signal is supplied from the second terminal 286b of the branching device 286 to the second transmission line 282, is supplied to the fourth terminal 287a of the branching filter 287, and is sent to the third transmission line 283 from the fifth terminal 287b of the branching device 287. And radiated from the transmitting / receiving antenna 288.
- the switch 361 inserted into the first transmission line 281 When the switch 361 inserted into the first transmission line 281 is cut off, the high-frequency signal generated by the high-frequency oscillator 260 is not transmitted through the switch 361 and is blocked and is not radiated from the transmitting / receiving antenna 288. By switching the propagation state and cut-off state of the switch 361, a pulse signal wave can be radiated from the transmitting / receiving antenna 288. A high ON / OFF ratio can be obtained and a highly reliable switch 361 with excellent durability can be used to realize a highly reliable high frequency transceiver.
- the force with which the switch 361 is inserted into the first transmission line 281 In yet another embodiment of the present invention, the switch 361 is applied to at least one of the first to third transmission lines 281 to 283.
- the branching device 286 constituting the high-frequency transmitter / receiver 280 may be configured by two switches 361 in the radar apparatus according to each of the above embodiments.
- FIG. 42 is a schematic diagram showing a configuration of a branching device 286 constituted by the switch 361.
- the two switches 361 are referred to as a first switch 361A and a second switch 361B.
- the first switch 361A transmits a high-frequency signal between the first terminal 286a and the second terminal 286b by setting the propagation state, and between the first terminal 286a and the second terminal 286b by setting the cutoff state. Cut off high frequency signals.
- the second switch 361B transmits a high-frequency signal between the first terminal 286a and the third terminal 286c by setting the propagation state, and between the first terminal 286a and the third terminal 286c by setting the cutoff state. Cut off high frequency signals.
- the first ends of the first and second switches 361A and 361B in the electromagnetic wave propagation direction X are connected to form a first terminal 286a.
- the second terminal 386 is the second end of the first switch 361A in the electromagnetic wave propagation direction X.
- the second terminal 386 is the second end in the electromagnetic wave propagation direction X of the second switch 361B.
- the first and second switches 361A and 361B are also supplied with a control signal (not shown), and when the first switch 361A is in a propagation state based on the control signal, the second switch 361B is cut off.
- the first switch 361A is in the cut-off state, the high frequency signal input from the first terminal 286a is selectively transmitted from the second and third terminals 286b and 286c by setting the second switch 36 1B to the propagation state. Can be output.
- the radar device 390 is realized by a Nord radar.
- the control unit includes first and second switches 361A, 3 61B is controlled, the first terminal 286a and the second terminal 286b are connected, and a pulsed high-frequency signal is output from the second terminal 286b, and then the first and second switches 361A and 361B are controlled.
- the first terminal 286a and the third terminal 286c are connected to output a high frequency signal from the third terminal 286c.
- a highly reliable V and high frequency transmitter / receiver can be realized by configuring the branching unit 286 using the highly reliable switch 361 that can obtain a large ONZOFF ratio and has excellent durability.
- the duplexer 287 constituting the high-frequency transmitter / receiver 380 may be configured by two switches 361 in the radar apparatus according to each of the above-described embodiments. .
- FIG. 43 is a schematic diagram showing a configuration of a duplexer 287 including the switch 361.
- the duplexer 287 includes two switches 361.
- the two switches 361 are referred to as a third switch 361C and a fourth switch 361D.
- the third switch 361C transmits a high-frequency signal between the fourth terminal 287a and the fifth terminal 287b by setting the propagation state, and the high-frequency signal between the fourth terminal 287a and the fifth terminal 287b by setting the cutoff state. Block the signal.
- the fourth switch 361D transmits a high-frequency signal between the fifth terminal 287b and the sixth terminal 287c by setting the propagation state, and transmits a high-frequency signal between the fifth terminal 287b and the sixth terminal 287c by setting the cutoff state. Shut off.
- the first end of the third switch 361C in the electromagnetic wave propagation direction X is the fourth terminal 287a. Further, the second ends of the third and fourth switches 361C and 361D in the electromagnetic wave propagation direction X are connected in common to form a fifth terminal 287b.
- the first end of the electromagnetic wave propagation direction X of the fourth switch 361D is the sixth terminal 287c.
- the third and fourth switches 361C and 361D are also supplied with a control signal (not shown), and when the third switch 361C is in a propagation state based on the control signal, the fourth switch 361D is cut off.
- the third switch 361C is in the cut-off state, the high-frequency signal input from the first terminal 287a is output from the second terminal 287b by setting the fourth switch 36 1D to the propagation state, and from the second terminal 287b.
- the high frequency signal that is input can be output to the third terminal 287c.
- the control unit controls the third and fourth switches 361C and 361D and connects the first terminal 287a and the second terminal 287b to generate a pulsed high-frequency signal.
- the third and fourth switches 361C and 361D are controlled to connect the second terminal 287b and the third terminal 287c, and the high frequency signal captured by the transmitting / receiving antenna 288 is connected to the third terminal. Output from 286c.
- the control unit is configured so that the first and third switches 361A and 361C are in the propagation state and the second and fourth switches 361B and 361D are in the force-off state, or the first and third switches 361A and 361C are The first to fourth switches 361A to 361D are controlled so that the second and fourth switches 361B and 361D are in the propagation state.
- the high-frequency transmitter / receiver realizes a high-frequency transmitter / receiver by replacing the phase shifter 20 with the attenuator described above in the high-frequency transmitter / receiver 280 of the embodiment shown in FIG. Is done.
- amplitude modulation can be performed by changing the amplitude of the high-frequency signal, which occurs due to frequency fluctuations and temperature fluctuations of the high-frequency signals.
- By adjusting the transmission output (transmitted high-frequency signal) and the fluctuation of the intermediate frequency signal it is possible to realize a stable high-frequency transceiver with little signal fluctuation.
- the attenuator is small and can be operated at a low voltage as described above, a high-frequency transmitter / receiver can be formed in a small size even if an attenuator is provided, and a voltage is applied to the attenuator. It is possible to prevent the configuration from becoming complicated.
- the same effect may be obtained by configuring a high-frequency transceiver by inserting an attenuator in the same manner at least one of the first to fifth transmission lines 281, 282, 283, 284, 285 and a displacement force. Can be achieved.
- the high-frequency transmitter / receiver may be configured by combining the high-frequency transmitter / receiver according to each of the above-described embodiments.
- a transmission line may include a phase shifter, a switch, and an attenuator.
- a phase shifter is provided in at least one of the first to fifth transmission lines 281 to 285, and the first to fifth transmission lines 281 to A switch may be provided for at least one of the powers 285, and an attenuator may be provided for at least one of the first to fifth transmission lines 281 to 285.
- the changing portion may be a piezoelectric element whose size changes according to the applied electric field.
- Piezoelectric elements include, for example, quartz, zinc oxide, aluminum nitride, Pb (Zr, Ti) 0, BaTiO, LiNbO
- phase shifter, switch, and attenuator in each of the above embodiments are a dielectric waveguide device or a dielectric waveguide device.
Abstract
Description
Claims
Priority Applications (4)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
CN200780011241.4A CN101411024B (zh) | 2006-03-31 | 2007-03-30 | 电介质波导设备、具备其的移相器、高频开关以及衰减器和高频发送器、高频接收器、高频接收发送器以及雷达装置、阵列天线装置、电介质波导设备的制造方法 |
US12/295,586 US8013694B2 (en) | 2006-03-31 | 2007-03-30 | Dielectric waveguide device, phase shifter, high frequency switch, and attenuator provided with dielectric waveguide device, high frequency transmitter, high frequency receiver, high frequency transceiver, radar device, array antenna, and method of manufacturing dielectric waveguide device |
KR1020087024771A KR101168608B1 (ko) | 2006-03-31 | 2007-03-30 | 유전체 도파로 디바이스와, 이것을 구비하는 이상기, 고주파 스위치 및 감쇠기와, 고주파 송신기, 고주파 수신기, 고주파 송수신기, 레이더 장치, 어레이 안테나 장치, 및 유전체 도파로 디바이스의 제조 방법 |
EP07740723.7A EP2009731B1 (en) | 2006-03-31 | 2007-03-30 | Dielectric waveguide device, phase shifter, high frequency switch, and attenuator provided with dielectric waveguide device, high frequency transmitter, high frequency receiver, high frequency transceiver, radar device, array antenna, and method of manufacturing dielectric waveguide device |
Applications Claiming Priority (4)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP2006-101040 | 2006-03-31 | ||
JP2006101040A JP4537339B2 (ja) | 2006-03-31 | 2006-03-31 | 移相器ならびにこれを備える高周波送信器、高周波受信器、高周波送受信器、レーダ装置およびアンテナ装置 |
JP2006127023A JP4376873B2 (ja) | 2006-04-28 | 2006-04-28 | 誘電体導波路デバイス、これを備える移相器、高周波スイッチおよび減衰器、ならびに高周波送信器、高周波受信器、高周波送受信器およびレーダ装置、アレイアンテナ装置、誘電体導波路デバイスの製造方法 |
JP2006-127023 | 2006-04-28 |
Publications (1)
Publication Number | Publication Date |
---|---|
WO2007114391A1 true WO2007114391A1 (ja) | 2007-10-11 |
Family
ID=38563658
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
PCT/JP2007/057287 WO2007114391A1 (ja) | 2006-03-31 | 2007-03-30 | 誘電体導波路デバイス、これを備える移相器、高周波スイッチおよび減衰器、ならびに高周波送信器、高周波受信器、高周波送受信器およびレーダ装置、アレイアンテナ装置、誘電体導波路デバイスの製造方法 |
Country Status (4)
Country | Link |
---|---|
US (1) | US8013694B2 (ja) |
EP (1) | EP2009731B1 (ja) |
KR (1) | KR101168608B1 (ja) |
WO (1) | WO2007114391A1 (ja) |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN111201667A (zh) * | 2017-08-30 | 2020-05-26 | 韦弗有限责任公司 | 液晶的多状态控制 |
US11387571B2 (en) | 2020-03-09 | 2022-07-12 | Fujitsu Limited | Slot antenna apparatus, communication system, and method for adjusting angle of radio waves emitted from slot antenna apparatus |
Families Citing this family (199)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
EP2489095B1 (de) * | 2009-10-14 | 2017-10-04 | Landis+Gyr AG | Antennenkoppler |
US8330651B2 (en) * | 2009-11-23 | 2012-12-11 | Honeywell International Inc. | Single-antenna FM/CW marine radar |
FR2964499B1 (fr) * | 2010-09-08 | 2013-09-13 | Univ Joseph Fourier | Ligne de transmission haute frequence accordable |
US9113347B2 (en) | 2012-12-05 | 2015-08-18 | At&T Intellectual Property I, Lp | Backhaul link for distributed antenna system |
US10009065B2 (en) | 2012-12-05 | 2018-06-26 | At&T Intellectual Property I, L.P. | Backhaul link for distributed antenna system |
DE102013202806A1 (de) * | 2013-01-31 | 2014-07-31 | Rohde & Schwarz Gmbh & Co. Kg | Schaltung auf dünnem Träger für den Einsatz in Hohlleitern und Herstellungsverfahren |
US9999038B2 (en) | 2013-05-31 | 2018-06-12 | At&T Intellectual Property I, L.P. | Remote distributed antenna system |
US9525524B2 (en) | 2013-05-31 | 2016-12-20 | At&T Intellectual Property I, L.P. | Remote distributed antenna system |
US8897697B1 (en) | 2013-11-06 | 2014-11-25 | At&T Intellectual Property I, Lp | Millimeter-wave surface-wave communications |
US9209902B2 (en) | 2013-12-10 | 2015-12-08 | At&T Intellectual Property I, L.P. | Quasi-optical coupler |
ES2856220T3 (es) * | 2014-02-19 | 2021-09-27 | Kymeta Corp | Polarización dinámica y control de acoplamiento para una antena holográfica alimentada de forma cilíndrica,orientable |
US10431899B2 (en) | 2014-02-19 | 2019-10-01 | Kymeta Corporation | Dynamic polarization and coupling control from a steerable, multi-layered cylindrically fed holographic antenna |
US9653819B1 (en) | 2014-08-04 | 2017-05-16 | Waymo Llc | Waveguide antenna fabrication |
US9711870B2 (en) | 2014-08-06 | 2017-07-18 | Waymo Llc | Folded radiation slots for short wall waveguide radiation |
US9766605B1 (en) | 2014-08-07 | 2017-09-19 | Waymo Llc | Methods and systems for synthesis of a waveguide array antenna |
US9612317B2 (en) | 2014-08-17 | 2017-04-04 | Google Inc. | Beam forming network for feeding short wall slotted waveguide arrays |
US9692101B2 (en) | 2014-08-26 | 2017-06-27 | At&T Intellectual Property I, L.P. | Guided wave couplers for coupling electromagnetic waves between a waveguide surface and a surface of a wire |
US9768833B2 (en) | 2014-09-15 | 2017-09-19 | At&T Intellectual Property I, L.P. | Method and apparatus for sensing a condition in a transmission medium of electromagnetic waves |
US10063280B2 (en) | 2014-09-17 | 2018-08-28 | At&T Intellectual Property I, L.P. | Monitoring and mitigating conditions in a communication network |
US9628854B2 (en) | 2014-09-29 | 2017-04-18 | At&T Intellectual Property I, L.P. | Method and apparatus for distributing content in a communication network |
US9615269B2 (en) | 2014-10-02 | 2017-04-04 | At&T Intellectual Property I, L.P. | Method and apparatus that provides fault tolerance in a communication network |
US9685992B2 (en) | 2014-10-03 | 2017-06-20 | At&T Intellectual Property I, L.P. | Circuit panel network and methods thereof |
US9503189B2 (en) | 2014-10-10 | 2016-11-22 | At&T Intellectual Property I, L.P. | Method and apparatus for arranging communication sessions in a communication system |
US9973299B2 (en) | 2014-10-14 | 2018-05-15 | At&T Intellectual Property I, L.P. | Method and apparatus for adjusting a mode of communication in a communication network |
US9762289B2 (en) | 2014-10-14 | 2017-09-12 | At&T Intellectual Property I, L.P. | Method and apparatus for transmitting or receiving signals in a transportation system |
US9312919B1 (en) | 2014-10-21 | 2016-04-12 | At&T Intellectual Property I, Lp | Transmission device with impairment compensation and methods for use therewith |
US9780834B2 (en) | 2014-10-21 | 2017-10-03 | At&T Intellectual Property I, L.P. | Method and apparatus for transmitting electromagnetic waves |
US9769020B2 (en) | 2014-10-21 | 2017-09-19 | At&T Intellectual Property I, L.P. | Method and apparatus for responding to events affecting communications in a communication network |
US9564947B2 (en) | 2014-10-21 | 2017-02-07 | At&T Intellectual Property I, L.P. | Guided-wave transmission device with diversity and methods for use therewith |
US9653770B2 (en) | 2014-10-21 | 2017-05-16 | At&T Intellectual Property I, L.P. | Guided wave coupler, coupling module and methods for use therewith |
US9577306B2 (en) | 2014-10-21 | 2017-02-21 | At&T Intellectual Property I, L.P. | Guided-wave transmission device and methods for use therewith |
US9520945B2 (en) | 2014-10-21 | 2016-12-13 | At&T Intellectual Property I, L.P. | Apparatus for providing communication services and methods thereof |
US9627768B2 (en) | 2014-10-21 | 2017-04-18 | At&T Intellectual Property I, L.P. | Guided-wave transmission device with non-fundamental mode propagation and methods for use therewith |
US9954287B2 (en) | 2014-11-20 | 2018-04-24 | At&T Intellectual Property I, L.P. | Apparatus for converting wireless signals and electromagnetic waves and methods thereof |
US9997819B2 (en) | 2015-06-09 | 2018-06-12 | At&T Intellectual Property I, L.P. | Transmission medium and method for facilitating propagation of electromagnetic waves via a core |
US10009067B2 (en) | 2014-12-04 | 2018-06-26 | At&T Intellectual Property I, L.P. | Method and apparatus for configuring a communication interface |
US10340573B2 (en) | 2016-10-26 | 2019-07-02 | At&T Intellectual Property I, L.P. | Launcher with cylindrical coupling device and methods for use therewith |
US10243784B2 (en) | 2014-11-20 | 2019-03-26 | At&T Intellectual Property I, L.P. | System for generating topology information and methods thereof |
US9544006B2 (en) | 2014-11-20 | 2017-01-10 | At&T Intellectual Property I, L.P. | Transmission device with mode division multiplexing and methods for use therewith |
US9461706B1 (en) | 2015-07-31 | 2016-10-04 | At&T Intellectual Property I, Lp | Method and apparatus for exchanging communication signals |
US9742462B2 (en) | 2014-12-04 | 2017-08-22 | At&T Intellectual Property I, L.P. | Transmission medium and communication interfaces and methods for use therewith |
US9800327B2 (en) | 2014-11-20 | 2017-10-24 | At&T Intellectual Property I, L.P. | Apparatus for controlling operations of a communication device and methods thereof |
US9654173B2 (en) | 2014-11-20 | 2017-05-16 | At&T Intellectual Property I, L.P. | Apparatus for powering a communication device and methods thereof |
US9680670B2 (en) | 2014-11-20 | 2017-06-13 | At&T Intellectual Property I, L.P. | Transmission device with channel equalization and control and methods for use therewith |
US10144036B2 (en) | 2015-01-30 | 2018-12-04 | At&T Intellectual Property I, L.P. | Method and apparatus for mitigating interference affecting a propagation of electromagnetic waves guided by a transmission medium |
US9876570B2 (en) | 2015-02-20 | 2018-01-23 | At&T Intellectual Property I, Lp | Guided-wave transmission device with non-fundamental mode propagation and methods for use therewith |
US9749013B2 (en) | 2015-03-17 | 2017-08-29 | At&T Intellectual Property I, L.P. | Method and apparatus for reducing attenuation of electromagnetic waves guided by a transmission medium |
US9876282B1 (en) | 2015-04-02 | 2018-01-23 | Waymo Llc | Integrated lens for power and phase setting of DOEWG antenna arrays |
US10224981B2 (en) | 2015-04-24 | 2019-03-05 | At&T Intellectual Property I, Lp | Passive electrical coupling device and methods for use therewith |
US9705561B2 (en) | 2015-04-24 | 2017-07-11 | At&T Intellectual Property I, L.P. | Directional coupling device and methods for use therewith |
US9948354B2 (en) | 2015-04-28 | 2018-04-17 | At&T Intellectual Property I, L.P. | Magnetic coupling device with reflective plate and methods for use therewith |
US9793954B2 (en) | 2015-04-28 | 2017-10-17 | At&T Intellectual Property I, L.P. | Magnetic coupling device and methods for use therewith |
US9490869B1 (en) | 2015-05-14 | 2016-11-08 | At&T Intellectual Property I, L.P. | Transmission medium having multiple cores and methods for use therewith |
US9871282B2 (en) | 2015-05-14 | 2018-01-16 | At&T Intellectual Property I, L.P. | At least one transmission medium having a dielectric surface that is covered at least in part by a second dielectric |
US9748626B2 (en) | 2015-05-14 | 2017-08-29 | At&T Intellectual Property I, L.P. | Plurality of cables having different cross-sectional shapes which are bundled together to form a transmission medium |
US10650940B2 (en) | 2015-05-15 | 2020-05-12 | At&T Intellectual Property I, L.P. | Transmission medium having a conductive material and methods for use therewith |
US10679767B2 (en) | 2015-05-15 | 2020-06-09 | At&T Intellectual Property I, L.P. | Transmission medium having a conductive material and methods for use therewith |
US9917341B2 (en) | 2015-05-27 | 2018-03-13 | At&T Intellectual Property I, L.P. | Apparatus and method for launching electromagnetic waves and for modifying radial dimensions of the propagating electromagnetic waves |
US10812174B2 (en) | 2015-06-03 | 2020-10-20 | At&T Intellectual Property I, L.P. | Client node device and methods for use therewith |
US10348391B2 (en) | 2015-06-03 | 2019-07-09 | At&T Intellectual Property I, L.P. | Client node device with frequency conversion and methods for use therewith |
US9912381B2 (en) | 2015-06-03 | 2018-03-06 | At&T Intellectual Property I, Lp | Network termination and methods for use therewith |
US10103801B2 (en) | 2015-06-03 | 2018-10-16 | At&T Intellectual Property I, L.P. | Host node device and methods for use therewith |
US10154493B2 (en) | 2015-06-03 | 2018-12-11 | At&T Intellectual Property I, L.P. | Network termination and methods for use therewith |
US9866309B2 (en) | 2015-06-03 | 2018-01-09 | At&T Intellectual Property I, Lp | Host node device and methods for use therewith |
US9913139B2 (en) | 2015-06-09 | 2018-03-06 | At&T Intellectual Property I, L.P. | Signal fingerprinting for authentication of communicating devices |
US10142086B2 (en) | 2015-06-11 | 2018-11-27 | At&T Intellectual Property I, L.P. | Repeater and methods for use therewith |
US9608692B2 (en) | 2015-06-11 | 2017-03-28 | At&T Intellectual Property I, L.P. | Repeater and methods for use therewith |
US9820146B2 (en) | 2015-06-12 | 2017-11-14 | At&T Intellectual Property I, L.P. | Method and apparatus for authentication and identity management of communicating devices |
US9667317B2 (en) | 2015-06-15 | 2017-05-30 | At&T Intellectual Property I, L.P. | Method and apparatus for providing security using network traffic adjustments |
US9640850B2 (en) | 2015-06-25 | 2017-05-02 | At&T Intellectual Property I, L.P. | Methods and apparatus for inducing a non-fundamental wave mode on a transmission medium |
US9865911B2 (en) | 2015-06-25 | 2018-01-09 | At&T Intellectual Property I, L.P. | Waveguide system for slot radiating first electromagnetic waves that are combined into a non-fundamental wave mode second electromagnetic wave on a transmission medium |
US9509415B1 (en) | 2015-06-25 | 2016-11-29 | At&T Intellectual Property I, L.P. | Methods and apparatus for inducing a fundamental wave mode on a transmission medium |
US9836957B2 (en) | 2015-07-14 | 2017-12-05 | At&T Intellectual Property I, L.P. | Method and apparatus for communicating with premises equipment |
US9628116B2 (en) | 2015-07-14 | 2017-04-18 | At&T Intellectual Property I, L.P. | Apparatus and methods for transmitting wireless signals |
US10148016B2 (en) | 2015-07-14 | 2018-12-04 | At&T Intellectual Property I, L.P. | Apparatus and methods for communicating utilizing an antenna array |
US10044409B2 (en) | 2015-07-14 | 2018-08-07 | At&T Intellectual Property I, L.P. | Transmission medium and methods for use therewith |
US9722318B2 (en) | 2015-07-14 | 2017-08-01 | At&T Intellectual Property I, L.P. | Method and apparatus for coupling an antenna to a device |
US10033108B2 (en) | 2015-07-14 | 2018-07-24 | At&T Intellectual Property I, L.P. | Apparatus and methods for generating an electromagnetic wave having a wave mode that mitigates interference |
US10320586B2 (en) | 2015-07-14 | 2019-06-11 | At&T Intellectual Property I, L.P. | Apparatus and methods for generating non-interfering electromagnetic waves on an insulated transmission medium |
US9853342B2 (en) | 2015-07-14 | 2017-12-26 | At&T Intellectual Property I, L.P. | Dielectric transmission medium connector and methods for use therewith |
US9882257B2 (en) | 2015-07-14 | 2018-01-30 | At&T Intellectual Property I, L.P. | Method and apparatus for launching a wave mode that mitigates interference |
US10033107B2 (en) | 2015-07-14 | 2018-07-24 | At&T Intellectual Property I, L.P. | Method and apparatus for coupling an antenna to a device |
US10205655B2 (en) | 2015-07-14 | 2019-02-12 | At&T Intellectual Property I, L.P. | Apparatus and methods for communicating utilizing an antenna array and multiple communication paths |
US10170840B2 (en) | 2015-07-14 | 2019-01-01 | At&T Intellectual Property I, L.P. | Apparatus and methods for sending or receiving electromagnetic signals |
US10341142B2 (en) | 2015-07-14 | 2019-07-02 | At&T Intellectual Property I, L.P. | Apparatus and methods for generating non-interfering electromagnetic waves on an uninsulated conductor |
US9847566B2 (en) | 2015-07-14 | 2017-12-19 | At&T Intellectual Property I, L.P. | Method and apparatus for adjusting a field of a signal to mitigate interference |
US9793951B2 (en) | 2015-07-15 | 2017-10-17 | At&T Intellectual Property I, L.P. | Method and apparatus for launching a wave mode that mitigates interference |
US9608740B2 (en) | 2015-07-15 | 2017-03-28 | At&T Intellectual Property I, L.P. | Method and apparatus for launching a wave mode that mitigates interference |
US10090606B2 (en) | 2015-07-15 | 2018-10-02 | At&T Intellectual Property I, L.P. | Antenna system with dielectric array and methods for use therewith |
US9749053B2 (en) | 2015-07-23 | 2017-08-29 | At&T Intellectual Property I, L.P. | Node device, repeater and methods for use therewith |
US9948333B2 (en) | 2015-07-23 | 2018-04-17 | At&T Intellectual Property I, L.P. | Method and apparatus for wireless communications to mitigate interference |
US10784670B2 (en) | 2015-07-23 | 2020-09-22 | At&T Intellectual Property I, L.P. | Antenna support for aligning an antenna |
US9871283B2 (en) | 2015-07-23 | 2018-01-16 | At&T Intellectual Property I, Lp | Transmission medium having a dielectric core comprised of plural members connected by a ball and socket configuration |
US9912027B2 (en) | 2015-07-23 | 2018-03-06 | At&T Intellectual Property I, L.P. | Method and apparatus for exchanging communication signals |
US9967173B2 (en) | 2015-07-31 | 2018-05-08 | At&T Intellectual Property I, L.P. | Method and apparatus for authentication and identity management of communicating devices |
US9735833B2 (en) | 2015-07-31 | 2017-08-15 | At&T Intellectual Property I, L.P. | Method and apparatus for communications management in a neighborhood network |
US10020587B2 (en) | 2015-07-31 | 2018-07-10 | At&T Intellectual Property I, L.P. | Radial antenna and methods for use therewith |
US10240947B2 (en) | 2015-08-24 | 2019-03-26 | Apple Inc. | Conductive cladding for waveguides |
US9904535B2 (en) | 2015-09-14 | 2018-02-27 | At&T Intellectual Property I, L.P. | Method and apparatus for distributing software |
US10136434B2 (en) | 2015-09-16 | 2018-11-20 | At&T Intellectual Property I, L.P. | Method and apparatus for use with a radio distributed antenna system having an ultra-wideband control channel |
US10009901B2 (en) | 2015-09-16 | 2018-06-26 | At&T Intellectual Property I, L.P. | Method, apparatus, and computer-readable storage medium for managing utilization of wireless resources between base stations |
US10051629B2 (en) | 2015-09-16 | 2018-08-14 | At&T Intellectual Property I, L.P. | Method and apparatus for use with a radio distributed antenna system having an in-band reference signal |
US9705571B2 (en) | 2015-09-16 | 2017-07-11 | At&T Intellectual Property I, L.P. | Method and apparatus for use with a radio distributed antenna system |
US10009063B2 (en) | 2015-09-16 | 2018-06-26 | At&T Intellectual Property I, L.P. | Method and apparatus for use with a radio distributed antenna system having an out-of-band reference signal |
US10079661B2 (en) | 2015-09-16 | 2018-09-18 | At&T Intellectual Property I, L.P. | Method and apparatus for use with a radio distributed antenna system having a clock reference |
US9769128B2 (en) | 2015-09-28 | 2017-09-19 | At&T Intellectual Property I, L.P. | Method and apparatus for encryption of communications over a network |
US9729197B2 (en) | 2015-10-01 | 2017-08-08 | At&T Intellectual Property I, L.P. | Method and apparatus for communicating network management traffic over a network |
US10074890B2 (en) | 2015-10-02 | 2018-09-11 | At&T Intellectual Property I, L.P. | Communication device and antenna with integrated light assembly |
US9876264B2 (en) | 2015-10-02 | 2018-01-23 | At&T Intellectual Property I, Lp | Communication system, guided wave switch and methods for use therewith |
US9882277B2 (en) | 2015-10-02 | 2018-01-30 | At&T Intellectual Property I, Lp | Communication device and antenna assembly with actuated gimbal mount |
US10051483B2 (en) | 2015-10-16 | 2018-08-14 | At&T Intellectual Property I, L.P. | Method and apparatus for directing wireless signals |
US10665942B2 (en) | 2015-10-16 | 2020-05-26 | At&T Intellectual Property I, L.P. | Method and apparatus for adjusting wireless communications |
US10355367B2 (en) | 2015-10-16 | 2019-07-16 | At&T Intellectual Property I, L.P. | Antenna structure for exchanging wireless signals |
US9912419B1 (en) | 2016-08-24 | 2018-03-06 | At&T Intellectual Property I, L.P. | Method and apparatus for managing a fault in a distributed antenna system |
US9860075B1 (en) | 2016-08-26 | 2018-01-02 | At&T Intellectual Property I, L.P. | Method and communication node for broadband distribution |
US10291311B2 (en) | 2016-09-09 | 2019-05-14 | At&T Intellectual Property I, L.P. | Method and apparatus for mitigating a fault in a distributed antenna system |
US11032819B2 (en) | 2016-09-15 | 2021-06-08 | At&T Intellectual Property I, L.P. | Method and apparatus for use with a radio distributed antenna system having a control channel reference signal |
US10340600B2 (en) | 2016-10-18 | 2019-07-02 | At&T Intellectual Property I, L.P. | Apparatus and methods for launching guided waves via plural waveguide systems |
US10135147B2 (en) | 2016-10-18 | 2018-11-20 | At&T Intellectual Property I, L.P. | Apparatus and methods for launching guided waves via an antenna |
US10135146B2 (en) | 2016-10-18 | 2018-11-20 | At&T Intellectual Property I, L.P. | Apparatus and methods for launching guided waves via circuits |
US10811767B2 (en) | 2016-10-21 | 2020-10-20 | At&T Intellectual Property I, L.P. | System and dielectric antenna with convex dielectric radome |
US10374316B2 (en) | 2016-10-21 | 2019-08-06 | At&T Intellectual Property I, L.P. | System and dielectric antenna with non-uniform dielectric |
US9876605B1 (en) | 2016-10-21 | 2018-01-23 | At&T Intellectual Property I, L.P. | Launcher and coupling system to support desired guided wave mode |
US9991580B2 (en) | 2016-10-21 | 2018-06-05 | At&T Intellectual Property I, L.P. | Launcher and coupling system for guided wave mode cancellation |
US10312567B2 (en) | 2016-10-26 | 2019-06-04 | At&T Intellectual Property I, L.P. | Launcher with planar strip antenna and methods for use therewith |
US10225025B2 (en) | 2016-11-03 | 2019-03-05 | At&T Intellectual Property I, L.P. | Method and apparatus for detecting a fault in a communication system |
US10224634B2 (en) | 2016-11-03 | 2019-03-05 | At&T Intellectual Property I, L.P. | Methods and apparatus for adjusting an operational characteristic of an antenna |
US10498044B2 (en) | 2016-11-03 | 2019-12-03 | At&T Intellectual Property I, L.P. | Apparatus for configuring a surface of an antenna |
US10291334B2 (en) | 2016-11-03 | 2019-05-14 | At&T Intellectual Property I, L.P. | System for detecting a fault in a communication system |
US10178445B2 (en) | 2016-11-23 | 2019-01-08 | At&T Intellectual Property I, L.P. | Methods, devices, and systems for load balancing between a plurality of waveguides |
US10090594B2 (en) | 2016-11-23 | 2018-10-02 | At&T Intellectual Property I, L.P. | Antenna system having structural configurations for assembly |
US10340603B2 (en) | 2016-11-23 | 2019-07-02 | At&T Intellectual Property I, L.P. | Antenna system having shielded structural configurations for assembly |
US10340601B2 (en) | 2016-11-23 | 2019-07-02 | At&T Intellectual Property I, L.P. | Multi-antenna system and methods for use therewith |
US10535928B2 (en) | 2016-11-23 | 2020-01-14 | At&T Intellectual Property I, L.P. | Antenna system and methods for use therewith |
US10361489B2 (en) | 2016-12-01 | 2019-07-23 | At&T Intellectual Property I, L.P. | Dielectric dish antenna system and methods for use therewith |
US10305190B2 (en) | 2016-12-01 | 2019-05-28 | At&T Intellectual Property I, L.P. | Reflecting dielectric antenna system and methods for use therewith |
US10637149B2 (en) | 2016-12-06 | 2020-04-28 | At&T Intellectual Property I, L.P. | Injection molded dielectric antenna and methods for use therewith |
US10135145B2 (en) | 2016-12-06 | 2018-11-20 | At&T Intellectual Property I, L.P. | Apparatus and methods for generating an electromagnetic wave along a transmission medium |
US10020844B2 (en) | 2016-12-06 | 2018-07-10 | T&T Intellectual Property I, L.P. | Method and apparatus for broadcast communication via guided waves |
US10382976B2 (en) | 2016-12-06 | 2019-08-13 | At&T Intellectual Property I, L.P. | Method and apparatus for managing wireless communications based on communication paths and network device positions |
US10727599B2 (en) | 2016-12-06 | 2020-07-28 | At&T Intellectual Property I, L.P. | Launcher with slot antenna and methods for use therewith |
US10439675B2 (en) | 2016-12-06 | 2019-10-08 | At&T Intellectual Property I, L.P. | Method and apparatus for repeating guided wave communication signals |
US9927517B1 (en) | 2016-12-06 | 2018-03-27 | At&T Intellectual Property I, L.P. | Apparatus and methods for sensing rainfall |
US10755542B2 (en) | 2016-12-06 | 2020-08-25 | At&T Intellectual Property I, L.P. | Method and apparatus for surveillance via guided wave communication |
US10694379B2 (en) | 2016-12-06 | 2020-06-23 | At&T Intellectual Property I, L.P. | Waveguide system with device-based authentication and methods for use therewith |
US10326494B2 (en) | 2016-12-06 | 2019-06-18 | At&T Intellectual Property I, L.P. | Apparatus for measurement de-embedding and methods for use therewith |
US10819035B2 (en) | 2016-12-06 | 2020-10-27 | At&T Intellectual Property I, L.P. | Launcher with helical antenna and methods for use therewith |
US10243270B2 (en) | 2016-12-07 | 2019-03-26 | At&T Intellectual Property I, L.P. | Beam adaptive multi-feed dielectric antenna system and methods for use therewith |
US10446936B2 (en) | 2016-12-07 | 2019-10-15 | At&T Intellectual Property I, L.P. | Multi-feed dielectric antenna system and methods for use therewith |
US10389029B2 (en) | 2016-12-07 | 2019-08-20 | At&T Intellectual Property I, L.P. | Multi-feed dielectric antenna system with core selection and methods for use therewith |
US10139820B2 (en) | 2016-12-07 | 2018-11-27 | At&T Intellectual Property I, L.P. | Method and apparatus for deploying equipment of a communication system |
US10547348B2 (en) | 2016-12-07 | 2020-01-28 | At&T Intellectual Property I, L.P. | Method and apparatus for switching transmission mediums in a communication system |
US9893795B1 (en) | 2016-12-07 | 2018-02-13 | At&T Intellectual Property I, Lp | Method and repeater for broadband distribution |
US10168695B2 (en) | 2016-12-07 | 2019-01-01 | At&T Intellectual Property I, L.P. | Method and apparatus for controlling an unmanned aircraft |
US10359749B2 (en) | 2016-12-07 | 2019-07-23 | At&T Intellectual Property I, L.P. | Method and apparatus for utilities management via guided wave communication |
US10027397B2 (en) | 2016-12-07 | 2018-07-17 | At&T Intellectual Property I, L.P. | Distributed antenna system and methods for use therewith |
US9911020B1 (en) | 2016-12-08 | 2018-03-06 | At&T Intellectual Property I, L.P. | Method and apparatus for tracking via a radio frequency identification device |
US10530505B2 (en) | 2016-12-08 | 2020-01-07 | At&T Intellectual Property I, L.P. | Apparatus and methods for launching electromagnetic waves along a transmission medium |
US10411356B2 (en) | 2016-12-08 | 2019-09-10 | At&T Intellectual Property I, L.P. | Apparatus and methods for selectively targeting communication devices with an antenna array |
US10601494B2 (en) | 2016-12-08 | 2020-03-24 | At&T Intellectual Property I, L.P. | Dual-band communication device and method for use therewith |
US10389037B2 (en) | 2016-12-08 | 2019-08-20 | At&T Intellectual Property I, L.P. | Apparatus and methods for selecting sections of an antenna array and use therewith |
US9998870B1 (en) | 2016-12-08 | 2018-06-12 | At&T Intellectual Property I, L.P. | Method and apparatus for proximity sensing |
US10916969B2 (en) | 2016-12-08 | 2021-02-09 | At&T Intellectual Property I, L.P. | Method and apparatus for providing power using an inductive coupling |
US10938108B2 (en) | 2016-12-08 | 2021-03-02 | At&T Intellectual Property I, L.P. | Frequency selective multi-feed dielectric antenna system and methods for use therewith |
US10326689B2 (en) | 2016-12-08 | 2019-06-18 | At&T Intellectual Property I, L.P. | Method and system for providing alternative communication paths |
US10777873B2 (en) | 2016-12-08 | 2020-09-15 | At&T Intellectual Property I, L.P. | Method and apparatus for mounting network devices |
US10103422B2 (en) | 2016-12-08 | 2018-10-16 | At&T Intellectual Property I, L.P. | Method and apparatus for mounting network devices |
US10069535B2 (en) | 2016-12-08 | 2018-09-04 | At&T Intellectual Property I, L.P. | Apparatus and methods for launching electromagnetic waves having a certain electric field structure |
US10340983B2 (en) | 2016-12-09 | 2019-07-02 | At&T Intellectual Property I, L.P. | Method and apparatus for surveying remote sites via guided wave communications |
US10264586B2 (en) | 2016-12-09 | 2019-04-16 | At&T Mobility Ii Llc | Cloud-based packet controller and methods for use therewith |
US9838896B1 (en) | 2016-12-09 | 2017-12-05 | At&T Intellectual Property I, L.P. | Method and apparatus for assessing network coverage |
AT519539B1 (de) * | 2016-12-29 | 2018-10-15 | Avl List Gmbh | Radarzielemulator mit einer Überblendungsvorrichtung und Verfahren zum Überblenden von Signalen |
RU2653084C1 (ru) * | 2017-01-31 | 2018-05-07 | Самсунг Электроникс Ко., Лтд. | Высокочастотное устройство на основе жидких кристаллов |
WO2018143536A1 (en) | 2017-01-31 | 2018-08-09 | Samsung Electronics Co., Ltd. | Liquid crystal-based high-frequency device and high-frequency switch |
US10468736B2 (en) | 2017-02-08 | 2019-11-05 | Aptiv Technologies Limited | Radar assembly with ultra wide band waveguide to substrate integrated waveguide transition |
US9973940B1 (en) | 2017-02-27 | 2018-05-15 | At&T Intellectual Property I, L.P. | Apparatus and methods for dynamic impedance matching of a guided wave launcher |
US10298293B2 (en) | 2017-03-13 | 2019-05-21 | At&T Intellectual Property I, L.P. | Apparatus of communication utilizing wireless network devices |
US10763566B2 (en) * | 2017-07-20 | 2020-09-01 | Apple Inc. | Millimeter wave transmission line structures |
US10892553B2 (en) | 2018-01-17 | 2021-01-12 | Kymeta Corporation | Broad tunable bandwidth radial line slot antenna |
GB2571943B (en) * | 2018-03-13 | 2022-11-23 | Bae Systems Plc | Improvements in and relating to impedance matching |
US11070188B2 (en) | 2018-03-13 | 2021-07-20 | Bae Systems Plc | Impedance matching |
US11527808B2 (en) | 2019-04-29 | 2022-12-13 | Aptiv Technologies Limited | Waveguide launcher |
CN114122649B (zh) | 2019-08-29 | 2023-12-22 | 京东方科技集团股份有限公司 | 移相器 |
WO2021094943A1 (en) * | 2019-11-12 | 2021-05-20 | Mehran Ahadi | Adjusting a cutoff frequency of an emnz metamaterial |
US11495868B2 (en) * | 2019-11-12 | 2022-11-08 | Amirkabir University of Tehran | EMNZ metamaterial configured to form a switch, a multiplexer, and a phase shifter |
US11362436B2 (en) | 2020-10-02 | 2022-06-14 | Aptiv Technologies Limited | Plastic air-waveguide antenna with conductive particles |
US11757166B2 (en) | 2020-11-10 | 2023-09-12 | Aptiv Technologies Limited | Surface-mount waveguide for vertical transitions of a printed circuit board |
US11626668B2 (en) | 2020-12-18 | 2023-04-11 | Aptiv Technologies Limited | Waveguide end array antenna to reduce grating lobes and cross-polarization |
US11502420B2 (en) | 2020-12-18 | 2022-11-15 | Aptiv Technologies Limited | Twin line fed dipole array antenna |
US11749883B2 (en) | 2020-12-18 | 2023-09-05 | Aptiv Technologies Limited | Waveguide with radiation slots and parasitic elements for asymmetrical coverage |
US11681015B2 (en) | 2020-12-18 | 2023-06-20 | Aptiv Technologies Limited | Waveguide with squint alteration |
US11901601B2 (en) | 2020-12-18 | 2024-02-13 | Aptiv Technologies Limited | Waveguide with a zigzag for suppressing grating lobes |
US11444364B2 (en) | 2020-12-22 | 2022-09-13 | Aptiv Technologies Limited | Folded waveguide for antenna |
US11668787B2 (en) | 2021-01-29 | 2023-06-06 | Aptiv Technologies Limited | Waveguide with lobe suppression |
US11721905B2 (en) | 2021-03-16 | 2023-08-08 | Aptiv Technologies Limited | Waveguide with a beam-forming feature with radiation slots |
US11616306B2 (en) | 2021-03-22 | 2023-03-28 | Aptiv Technologies Limited | Apparatus, method and system comprising an air waveguide antenna having a single layer material with air channels therein which is interfaced with a circuit board |
US11616282B2 (en) | 2021-08-03 | 2023-03-28 | Aptiv Technologies Limited | Transition between a single-ended port and differential ports having stubs that match with input impedances of the single-ended and differential ports |
WO2023054743A1 (ko) * | 2021-09-29 | 2023-04-06 | 엘지전자 주식회사 | 무선통신 시스템에서 신호의 전송 방법 및 장치 |
US20230402731A1 (en) * | 2022-02-22 | 2023-12-14 | Doty Scientific, Inc. | Rolled-laminate Terahertz waveguide |
Citations (9)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPH08102604A (ja) | 1994-10-03 | 1996-04-16 | Hitachi Ferrite Ltd | 非放射性誘電体線路及び位相制御方法 |
JPH11103201A (ja) * | 1997-09-29 | 1999-04-13 | Mitsui Chem Inc | 移相器、移相器アレイおよびフェーズドアレイアンテナ装置 |
JP2000315902A (ja) * | 1999-04-28 | 2000-11-14 | Nippon Hoso Kyokai <Nhk> | 可変移相器 |
JP2003508942A (ja) | 1999-08-24 | 2003-03-04 | パラテック マイクロウェーブ インコーポレイテッド | 電圧により調整可能なコプレーナ型移相器 |
JP2003110335A (ja) * | 2001-09-27 | 2003-04-11 | Fujitsu Ltd | アレーアンテナ装置及びグレーティング抑圧方法 |
JP2003218611A (ja) * | 2002-01-22 | 2003-07-31 | Matsushita Electric Ind Co Ltd | 可変分布定数回路 |
JP2004531907A (ja) * | 2001-06-28 | 2004-10-14 | ラム リサーチ コーポレーション | セラミック静電チャックアセンブリ及びその作製方法 |
JP2005257384A (ja) * | 2004-03-10 | 2005-09-22 | Mitsubishi Electric Corp | レーダ装置およびアンテナ装置 |
JP2005337864A (ja) * | 2004-05-26 | 2005-12-08 | Kyocera Corp | 高周波送受信器およびそれを具備するレーダ装置ならびにそれを搭載したレーダ装置搭載車両およびレーダ装置搭載小型船舶 |
Family Cites Families (10)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CA2222637C (en) * | 1990-07-13 | 1999-12-14 | Zdenek Adler | Monostatic radar system having a one-port impedance matching device |
JP3089666B2 (ja) * | 1993-08-27 | 2000-09-18 | 株式会社村田製作所 | 高周波伝送線路、高周波共振器、高周波フィルタ及び高周波帯域除去フィルタ |
SE506313C2 (sv) | 1995-06-13 | 1997-12-01 | Ericsson Telefon Ab L M | Avstämbara mikrovågsanordningar |
AU2001288387A1 (en) * | 2000-08-25 | 2002-03-04 | Microcoating Technologies, Inc. | Electronic and optical devices and methods of forming these devices |
JP2002171115A (ja) | 2000-12-04 | 2002-06-14 | Nec Corp | フェーズドアレイアンテナ装置及びフェーズドアレイアンテナのビーム指向方向校正方法 |
JP3473577B2 (ja) | 2000-12-19 | 2003-12-08 | 日本電気株式会社 | レーダー装置 |
JP4245823B2 (ja) | 2001-05-02 | 2009-04-02 | 日本放送協会 | 可変特性高周波伝送路 |
US20050110138A1 (en) * | 2003-11-25 | 2005-05-26 | Banpil Photonics, Inc. | High Speed Electrical On-Chip Interconnects and Method of Manufacturing |
JP4566572B2 (ja) * | 2004-02-04 | 2010-10-20 | 三菱電機株式会社 | 車載レーダ装置 |
US7054524B2 (en) * | 2004-08-30 | 2006-05-30 | Energy Conversion Devices, Inc. | Asymmetric photonic crystal waveguide element having symmetric mode fields |
-
2007
- 2007-03-30 WO PCT/JP2007/057287 patent/WO2007114391A1/ja active Application Filing
- 2007-03-30 EP EP07740723.7A patent/EP2009731B1/en not_active Expired - Fee Related
- 2007-03-30 KR KR1020087024771A patent/KR101168608B1/ko not_active IP Right Cessation
- 2007-03-30 US US12/295,586 patent/US8013694B2/en not_active Expired - Fee Related
Patent Citations (9)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPH08102604A (ja) | 1994-10-03 | 1996-04-16 | Hitachi Ferrite Ltd | 非放射性誘電体線路及び位相制御方法 |
JPH11103201A (ja) * | 1997-09-29 | 1999-04-13 | Mitsui Chem Inc | 移相器、移相器アレイおよびフェーズドアレイアンテナ装置 |
JP2000315902A (ja) * | 1999-04-28 | 2000-11-14 | Nippon Hoso Kyokai <Nhk> | 可変移相器 |
JP2003508942A (ja) | 1999-08-24 | 2003-03-04 | パラテック マイクロウェーブ インコーポレイテッド | 電圧により調整可能なコプレーナ型移相器 |
JP2004531907A (ja) * | 2001-06-28 | 2004-10-14 | ラム リサーチ コーポレーション | セラミック静電チャックアセンブリ及びその作製方法 |
JP2003110335A (ja) * | 2001-09-27 | 2003-04-11 | Fujitsu Ltd | アレーアンテナ装置及びグレーティング抑圧方法 |
JP2003218611A (ja) * | 2002-01-22 | 2003-07-31 | Matsushita Electric Ind Co Ltd | 可変分布定数回路 |
JP2005257384A (ja) * | 2004-03-10 | 2005-09-22 | Mitsubishi Electric Corp | レーダ装置およびアンテナ装置 |
JP2005337864A (ja) * | 2004-05-26 | 2005-12-08 | Kyocera Corp | 高周波送受信器およびそれを具備するレーダ装置ならびにそれを搭載したレーダ装置搭載車両およびレーダ装置搭載小型船舶 |
Non-Patent Citations (2)
Title |
---|
M. COHN; A. F. EIKENBERG: "Ferroelectric Phase Shifters for VHF and UHF", IRE TRANS. ON MICROWAVE THEORY AND TECHNIQUES, vol. MTT-10, 1962, pages 536 - 548 |
See also references of EP2009731A4 |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN111201667A (zh) * | 2017-08-30 | 2020-05-26 | 韦弗有限责任公司 | 液晶的多状态控制 |
US11387571B2 (en) | 2020-03-09 | 2022-07-12 | Fujitsu Limited | Slot antenna apparatus, communication system, and method for adjusting angle of radio waves emitted from slot antenna apparatus |
Also Published As
Publication number | Publication date |
---|---|
KR20080103595A (ko) | 2008-11-27 |
EP2009731A4 (en) | 2012-02-01 |
US20090174499A1 (en) | 2009-07-09 |
EP2009731B1 (en) | 2014-01-01 |
US8013694B2 (en) | 2011-09-06 |
KR101168608B1 (ko) | 2012-07-30 |
EP2009731A1 (en) | 2008-12-31 |
Similar Documents
Publication | Publication Date | Title |
---|---|---|
WO2007114391A1 (ja) | 誘電体導波路デバイス、これを備える移相器、高周波スイッチおよび減衰器、ならびに高周波送信器、高周波受信器、高周波送受信器およびレーダ装置、アレイアンテナ装置、誘電体導波路デバイスの製造方法 | |
US7154357B2 (en) | Voltage tunable reflective coplanar phase shifters | |
JP4537339B2 (ja) | 移相器ならびにこれを備える高周波送信器、高周波受信器、高周波送受信器、レーダ装置およびアンテナ装置 | |
JP5171819B2 (ja) | 直流阻止回路、ハイブリッド回路装置、送信器、受信器、送受信器およびレーダ装置 | |
US20030001692A1 (en) | Voltage tunable varactors and tunable devices including such varactors | |
US20100245155A1 (en) | High-Frequency Transmission Line Connection Structure, Circuit Board, High-Frequency Module, and Radar Apparatus | |
US10903568B2 (en) | Electrochromic reflectarray antenna | |
EA003712B1 (ru) | Фазированные антенные решетки с последовательным возбуждением и диэлектрическими фазовращателями | |
JPH10341108A (ja) | アンテナ装置およびレーダモジュール | |
US6380825B1 (en) | Branch tee dielectric waveguide line | |
US7839349B1 (en) | Tunable substrate phase scanned reflector antenna | |
US20020033744A1 (en) | Waveguide-finline tunable phase shifter | |
JP4376873B2 (ja) | 誘電体導波路デバイス、これを備える移相器、高周波スイッチおよび減衰器、ならびに高周波送信器、高周波受信器、高周波送受信器およびレーダ装置、アレイアンテナ装置、誘電体導波路デバイスの製造方法 | |
JP4615485B2 (ja) | 誘電体導波路デバイス、これを備える移相器、高周波スイッチおよび減衰器、ならびに高周波送信器、高周波受信器、高周波送受信器、レーダ装置およびアレイアンテナ装置 | |
JP2000244212A (ja) | 導波管・伝送線路変換器 | |
JP4615486B2 (ja) | 誘電体導波路デバイスならびにこれを備える高周波送信器、高周波受信器、高周波送受信器、レーダ装置、移相器、高周波スイッチおよび減衰器 | |
EP1530249B1 (en) | Voltage tunable coplanar phase shifters | |
JP4606367B2 (ja) | 高周波スイッチならびにこれを備える高周波送信器、高周波受信器、高周波送受信器およびレーダ装置 | |
JP4606378B2 (ja) | 誘電体導波路デバイス、これを備える移相器、高周波スイッチおよび減衰器、ならびに高周波送信器、高周波受信器、高周波送受信器、レーダ装置およびアレイアンテナ装置 | |
RU2796642C1 (ru) | Резонансная оконечная свч нагрузка, интегрированная в подложку печатной платы | |
JP3472490B2 (ja) | 誘電体線路モジュール | |
Kim | Wideband two-dimensional and multiple beam phased arrays and microwave applications using piezoelectric transducers |
Legal Events
Date | Code | Title | Description |
---|---|---|---|
121 | Ep: the epo has been informed by wipo that ep was designated in this application |
Ref document number: 07740723 Country of ref document: EP Kind code of ref document: A1 |
|
WWE | Wipo information: entry into national phase |
Ref document number: 200780011241.4 Country of ref document: CN |
|
NENP | Non-entry into the national phase |
Ref country code: DE |
|
WWE | Wipo information: entry into national phase |
Ref document number: 1020087024771 Country of ref document: KR |
|
WWE | Wipo information: entry into national phase |
Ref document number: 2007740723 Country of ref document: EP |
|
WWE | Wipo information: entry into national phase |
Ref document number: 12295586 Country of ref document: US |