WO2006069397A2 - Prevision de numero de niveau fondee sur la capacite pour une conception mimo - Google Patents

Prevision de numero de niveau fondee sur la capacite pour une conception mimo Download PDF

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Publication number
WO2006069397A2
WO2006069397A2 PCT/US2005/047643 US2005047643W WO2006069397A2 WO 2006069397 A2 WO2006069397 A2 WO 2006069397A2 US 2005047643 W US2005047643 W US 2005047643W WO 2006069397 A2 WO2006069397 A2 WO 2006069397A2
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Prior art keywords
cap
tone
rank
snrs
calculating
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PCT/US2005/047643
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English (en)
Inventor
Hemanth Sampath
Tamer Kadous
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Qualcomm Incorporated
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Application filed by Qualcomm Incorporated filed Critical Qualcomm Incorporated
Priority to JP2007548617A priority Critical patent/JP2008526137A/ja
Priority to EP05856106A priority patent/EP1832032A2/fr
Priority to NZ556045A priority patent/NZ556045A/en
Priority to MX2007007757A priority patent/MX2007007757A/es
Priority to CA002591609A priority patent/CA2591609A1/fr
Priority to BRPI0519539-0A priority patent/BRPI0519539A2/pt
Priority to AU2005318993A priority patent/AU2005318993B2/en
Publication of WO2006069397A2 publication Critical patent/WO2006069397A2/fr
Priority to IL183999A priority patent/IL183999A0/en
Priority to ZA200805129A priority patent/ZA200705129B/xx
Priority to NO20073178A priority patent/NO20073178L/no

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/003—Arrangements for allocating sub-channels of the transmission path
    • H04L5/0044—Arrangements for allocating sub-channels of the transmission path allocation of payload
    • H04L5/0046—Determination of how many bits are transmitted on different sub-channels
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B17/00—Monitoring; Testing
    • H04B17/30—Monitoring; Testing of propagation channels
    • H04B17/309—Measuring or estimating channel quality parameters
    • H04B17/336—Signal-to-interference ratio [SIR] or carrier-to-interference ratio [CIR]
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/0001—Systems modifying transmission characteristics according to link quality, e.g. power backoff
    • H04L1/0002—Systems modifying transmission characteristics according to link quality, e.g. power backoff by adapting the transmission rate
    • H04L1/0003—Systems modifying transmission characteristics according to link quality, e.g. power backoff by adapting the transmission rate by switching between different modulation schemes
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/0001—Systems modifying transmission characteristics according to link quality, e.g. power backoff
    • H04L1/0023—Systems modifying transmission characteristics according to link quality, e.g. power backoff characterised by the signalling
    • H04L1/0026—Transmission of channel quality indication
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/02—Arrangements for detecting or preventing errors in the information received by diversity reception
    • H04L1/06—Arrangements for detecting or preventing errors in the information received by diversity reception using space diversity
    • H04L1/0618—Space-time coding
    • H04L1/0637—Properties of the code
    • H04L1/065—Properties of the code by means of convolutional encoding
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/02—Arrangements for detecting or preventing errors in the information received by diversity reception
    • H04L1/06—Arrangements for detecting or preventing errors in the information received by diversity reception using space diversity
    • H04L1/0618—Space-time coding
    • H04L1/0637—Properties of the code
    • H04L1/0656—Cyclotomic systems, e.g. Bell Labs Layered Space-Time [BLAST]
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/0204—Channel estimation of multiple channels
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/024—Channel estimation channel estimation algorithms
    • H04L25/0242—Channel estimation channel estimation algorithms using matrix methods
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006—Arrangements for removing intersymbol interference
    • H04L25/03343—Arrangements at the transmitter end
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2626—Arrangements specific to the transmitter only
    • H04L27/26265—Arrangements for sidelobes suppression specially adapted to multicarrier systems, e.g. spectral precoding
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/003—Arrangements for allocating sub-channels of the transmission path
    • H04L5/0058—Allocation criteria
    • H04L5/006—Quality of the received signal, e.g. BER, SNR, water filling
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/0001—Systems modifying transmission characteristics according to link quality, e.g. power backoff
    • H04L1/0009—Systems modifying transmission characteristics according to link quality, e.g. power backoff by adapting the channel coding
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/004—Arrangements for detecting or preventing errors in the information received by using forward error control
    • H04L1/0056—Systems characterized by the type of code used
    • H04L1/0071—Use of interleaving
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L1/00—Arrangements for detecting or preventing errors in the information received
    • H04L1/12—Arrangements for detecting or preventing errors in the information received by using return channel
    • H04L1/16—Arrangements for detecting or preventing errors in the information received by using return channel in which the return channel carries supervisory signals, e.g. repetition request signals
    • H04L1/18—Automatic repetition systems, e.g. Van Duuren systems
    • H04L1/1812—Hybrid protocols; Hybrid automatic repeat request [HARQ]
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006—Arrangements for removing intersymbol interference
    • H04L2025/0335—Arrangements for removing intersymbol interference characterised by the type of transmission
    • H04L2025/03426—Arrangements for removing intersymbol interference characterised by the type of transmission transmission using multiple-input and multiple-output channels
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/0001—Arrangements for dividing the transmission path
    • H04L5/0014—Three-dimensional division
    • H04L5/0023—Time-frequency-space
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/02—Channels characterised by the type of signal
    • H04L5/023—Multiplexing of multicarrier modulation signals

Definitions

  • the present invention relates generally to communications, and more specifically to techniques for determining a distribution of a data stream to be transmitted via a multi-channel, e.g., a multiple-input multiple-output (MIMO), orthogonal frequency division multiplexing (OFDM) communication system.
  • MIMO multiple-input multiple-output
  • OFDM orthogonal frequency division multiplexing
  • an RF modulated signal from a transmitter may reach a receiver via a number of propagation paths.
  • the characteristics of the propagation paths typically vary over time due to a number of factors such as fading and multipath.
  • multiple transmit and receive antennas may be used. If the propagation paths between the transmit and receive antennas are linearly independent (i.e., a transmission on one path is not formed as a linear combination of the transmissions on the other paths), which is generally true to at least an extent, then the likelihood of correctly receiving a data transmission increases as the number of antennas increases. Generally, diversity increases and performance improves as the number of transmit and receive antennas increases.
  • a multiple-input multiple-output (MIMO) communication system employs multiple (N T ) transmit antennas and multiple (N R ) receive antennas for data transmission.
  • a MIMO channel formed by the N T transmit and N R receive antennas may be decomposed into Ns independent channels, with N s ⁇ min ⁇ N ⁇ , N R ⁇ .
  • Each of the Ns independent channels may also be referred to as a spatial subchannel (or a transmission channel) of the MIMO channel and corresponds to a dimension.
  • the MIMO system can provide improved performance (e.g., increased transmission capacity) if the additional dimensionalities created by the multiple transmit and receive antennas are utilized.
  • an independent data stream may be transmitted from each of the Nr transmit antennas.
  • the transmitted data streams may experience different channel conditions (e.g., different fading and multipath effects) and may achieve different signal-to-noise-and-interference ratios (SNRs) for a given amount of transmit power.
  • SNRs signal-to-noise-and-interference ratios
  • successive interference cancellation processing is used at the receiver to recover the transmitted data streams (described below)
  • SNRs may be achieved for the data streams depending on the specific order in which the data streams are recovered. Consequently, different data rates may be supported by different data streams, depending on their achieved SNRs. Since the channel conditions typically vary with time, the data rate supported by each data stream also varies with time.
  • the MIMO design has two modes of operation - the single code word (SCW) and multiple-code word (MCW).
  • SCW single code word
  • MCW multiple-code word
  • the transmitter can encode the data transmitted on each spatial layer independently, possibly with different rates.
  • the receiver employs a successive interference cancellation (SIC) algorithm which works as follows: Decode the first layer, and then subtract its contribution from the received signal after re- encoding and multiplying the encoded first layer with an "estimated channel,” then decode the second layer and so on.
  • SIC successive interference cancellation
  • This "onion-peeling" approach means that each successively decoded layer sees increasing signal-to-noise (SNR) and hence can support higher rates.
  • SNR signal-to-noise
  • MCW design with SIC achieves capacity.
  • the transmitter encodes the data transmitted on each spatial layer with "identical data rates.”
  • the receiver can employ a low complexity linear receiver such as a Minimum Mean Square Solution (MMSE) or Zero Frequency (ZF) receiver, or non-linear receivers such as QRM, for each tone.
  • MMSE Minimum Mean Square Solution
  • ZF Zero Frequency
  • QRM non-linear receivers
  • the SCW design overcomes the above mentioned implementation hassles of the MCW design.
  • the drawback is that the SCW mode cannot support the MCW rates in spatially correlated channels or line-of-sight (LOS) channels with a high K-factor. Both of these scenarios lead to a loss in channel rank or increase in channel condition number and increased inter-layer interference. This dramatically lowers the effective SNR for each spatial layer. Hence, the data rate supported by each layer is lowered, which lowers the overall data rate.
  • LOS line-of-sight
  • K-factor is the ratio of the LOS channel power to the non-LOS channel power.
  • Rank is the number of eigen-modes in the channel with non-zero energy.
  • Condition Number is the ratio of the largest eigenvalue to the smallest eigen-value of the MIMO channel.
  • a method of rank prediction comprises calculating MIMO channel matrices corresponding to layer transmissions for each tone, calculating signal-to-noise ratios (SNRs) for each tone based on the MIMO channel matrices, mapping the SNR for each tone to generate effective SNRs for each layer transmission, calculating additive white Gaussian noise (AWGN) capacities corresponding to the effective SNRs and denoted as C ⁇ [Pl ' CaPl ' Caf>3 ' Cap ⁇ selecting an absolute highest Cap of the highest Caps, and selecting a rank based on the selected absolute highest Cap.
  • SNRs signal-to-noise ratios
  • a wireless communications device comprises means for calculating MIMO channel matrices corresponding to layer transmissions for each tone, means for calculating signal-to-noise ratios (SNRs) for each tone based on the MIMO channel matrices, means for mapping the SNR for each tone to generate effective SNRs for each layer transmission, means for calculating additive white Gaussian noise (AWGN) capacities corresponding to the effective SNRs and denoted as CaPx ' CaPl ' CaPi ' Cap * , means for selecting an absolute highest Cap of the highest Caps, and means for selecting a rank based on the selected absolute highest Cap.
  • SNRs signal-to-noise ratios
  • a processor is programmed to execute a method of rank prediction, the method comprising calculating MBVIO channel matrices corresponding to layer transmissions for each tone, calculating signal-to-noise ratios (SNRs) for each tone based on the MIMO channel matrices, mapping the SNR for each tone to generate effective SNRs for each layer transmission, calculating additive white Gaussian noise (AWGN) capacities corresponding to the effective SNRs and denoted as Cap ⁇ , Cap 2 , Cap - 3 , Cap, ⁇ selecting m absolute highest Cap of the highest Caps; and selecting a rank based on the selected absolute highest Cap.
  • SNRs signal-to-noise ratios
  • a computer readable media embodying a method of rank prediction comprises calculating MHvIO channel matrices corresponding to layer transmissions for each tone, calculating signal-to-noise ratios (SNRs) for each tone based on the MEvIO channel matrices, mapping the SNR for each tone to generate effective SNRs for each layer transmission, calculating additive white Gaussian noise (AWGN) capacities corresponding to the effective SNRs and denoted as Ca P ⁇ » Ca P2> Ca Pi' Ca P ⁇ selecting an absolute highest Cap of the highest Caps, and selecting a rank based on the selected absolute highest Cap.
  • SNRs signal-to-noise ratios
  • FIG. 1 shows a conventional SCW transmitter
  • FIG. 2 shows an SCW transmitter with rank prediction in accordance with an embodiment
  • FIG. 5 shows a block diagram for capacity based rank prediction in accordance with an embodiment.
  • the techniques described herein for performance based rank prediction may be used for various communication systems such as a Code Division Multiple Access (CDMA) system, a Wideband CDMA (WCDMA) system, a direct sequence CDMA (DS-CDMA) system, a Time Division Multiple Access (TDMA) system, a Frequency Division Multiple Access (FDMA) system, a High Speed Downlink Packet Access (HSDPA) system, an orthogonal frequency division multiplexing (OFDM)-based system, an Orthogonal Frequency Division Multiple Access (OFDMA) system, a single- input single-output (SISO) system, a multiple-input multiple-output (MIMO) system, and so on.
  • CDMA Code Division Multiple Access
  • WCDMA Wideband CDMA
  • DS-CDMA direct sequence CDMA
  • TDMA Time Division Multiple Access
  • FDMA Frequency Division Multiple Access
  • HSDPA High Speed Downlink Packet Access
  • OFDM orthogonal frequency division multiplexing
  • OFDMA Orthogonal Fre
  • OFDM is a multi-carrier modulation technique that effectively partitions the overall system bandwidth into multiple (NF) orthogonal subbands. These subbands are also referred to as tones, subca ⁇ ers, bins, and frequency channels. With OFDM, each subband is associated with a respective subcarrier that may be modulated with data. Up to NF modulation symbols may be transmitted on the NF subbands in each OFDM symbol period. Prior to transmission, these modulation symbols are transformed to the time-domain using an NF-point inverse fast Fourier transform (IFFT) to obtain a "transformed" symbol that contains NF chips.
  • IFFT inverse fast Fourier transform
  • the SCW design overcomes the drawbacks of MCW design.
  • SCW mode cannot support the MCW rates in spatially correlated channels or line-of- sight (LOS) channels with a high K-factor. Both of these scenarios lead to a loss in channel rank or increase in channel condition number and increased inter-layer interference. This dramatically lowers the effective SNR for each spatial layer. Hence, the data rate supported by each layer is lowered, which lowers the overall data rate.
  • Effective SNR is (approximately) proportional to the geometric mean of the SNRs averaged over all tones.
  • One way to reduce interlayer interference is to lower the number of spatial layers transmitted in low-rank channels, and trade-off inter-layer interference and MIMO gains. For example, lowering the number of layers transmitted from four to three, i.e., decreasing the rank from four to three, can dramatically increase the effective SNRs for the three layers and hence the data rate supported by each layer. The net- effect is that a three-layer transmission can in-fact have a higher spectral efficiency compared to a four-layer transmission.
  • the SCW design effectively trades off the interlayer interference and MMO gains to maximize overall spectral efficiency. This is achieved via rank prediction, where the receiver feeds back an optimal number of layers for transmission in addition to a Carrier-Quality-to-Interference (CQI) to match the channel rank.
  • CQI Carrier-Quality-to-Interference
  • FIG. 1 shows a conventional SCW transmitter 100.
  • the bits 102 are turbo- encoded 104 and QAM mapped 106 depending on the packet format (PF) 108, 110, specified by a rate prediction algorithm 112.
  • the encoding is identical to a single-in- single-out (SISO) design.
  • the coded symbols are then de-multiplexed 114 to ⁇ layers 116, which are then spatially mapped 118 to ⁇ OFDM modulators 120 and antennas 122.
  • the OFDM processing for each transmit antenna proceeds then in an identical fashion as the SISO, after which the signals are launched into a MIMO wireless channel.
  • the rate prediction algorithm uses a 4-bit CQI feedback 124 from receiver 126 every 5 msec.
  • the CQI is a measure of the effective SNR /spatial layer, measured at the receiver.
  • the spatial mapping is done in manner to ensure that the SNR for each layer are similar. As explained before, the performance of this design suffers in low rank channels.
  • SCW single code word
  • MCW Multiple Code Word
  • SIC Multiple Code Word
  • SCW is better than MCW since MCQ is more sensitive to channel estimation errors.
  • the performance degradation at high SNRs is lowered to 1-2 dB, by employing dual polarized antennas.
  • the SCW design is within two dB of MCW design even at high SNRs.
  • the performance of MCW is worse than SCW at SNR ⁇ 15 dB, due to increased sensitivity of SIC to channel estimation errors.
  • Figure 2 shows an SCW transmitter with rank prediction in accordance with an embodiment.
  • the bits 202 are turbo-encoded 204 and QAM mapped 206 depending on the packet format (PF) 208, 210, specified by a rate prediction algorithm 212.
  • PF packet format
  • the coded symbols are then de-multiplexed 214 to
  • M streams 216 or layers ( ⁇ ⁇ M ⁇ M r), where M 228 is a 2-bit integer l ⁇ M ⁇ M ⁇ specified by the receiver 226 feedback every 5 m-sec, in addition to a 5 -bit CQI 224.
  • the M streams 216 are then spatially mapped 218 to M ⁇ OFDM modulators 220 and M ⁇ antennas 222.
  • the spatial mapper (precoder) 218 is a M t x M matrix ⁇ *) that maps M symbols on to ⁇ antennas, for each OFDM tone, * ⁇
  • the precoder matrices can be chosen so that the equivalent channel matrix " W ' " ⁇ k) has improved frequency selectivity compared to ⁇ ' . The increased frequency selectivity can be exploited by the decoder to obtain frequency diversity gains.
  • a precoder matrix is the following permutation matrix:
  • M ⁇ ⁇ ⁇ ⁇ g ⁇ B ⁇ s a parameter to control the frequency selectivity of the equivalent channel.
  • the vertical axis 406 represents antennas.
  • the horizontal axis 408 represents tones.
  • Circular multiplexing improves frequency diversity regardless of the channel delay spread.
  • the performance of CM (with
  • STTD Space-Time transmit diversity
  • a precoder matrix is the following generalized delay diversity matrix:
  • the parameter ⁇ i s the delay-parameter, which also controls the frequency selectivity of the channel, and N is the number of OFDM tones.
  • the performance of delay diversity is strictly worse than circular multiplexing (and STTD), and has poor performance in LOS channel conditions for high PF.
  • the only advantage of using delay diversity is that it benefits from improved SISO channel estimation gains at very low SNRs (SNR ⁇ -5 dB) and for high mobility (> 120 kmph). In these channel scenarios, circular multiplexing cannot benefit from SISO channel estimation gains.
  • a current SISO design uses 7 PFs with spectral efficiencies [0.5, 1, 1.5, 2.0, 2.5, 3.0, 4.0] bps/Hz.
  • this granularity in spectral efficiency (SE) should be sufficient.
  • SE spectral efficiency
  • all four layers are used for transmission, this translates to spectral efficiencies of [2,4,6,8,10,12,16] bps/Hz, with a SE granularity on the order of 2-4 bps/Hz.
  • a consequence of this coarse granularity is a loss in data rate, since these users are constrained to transmit at a much lower data rate than their attainable SE.
  • MCW design with SIC does not have this granularity problem, since the rate in each layer can be adjusted independently, resulting in an overall finer spectral efficiency granularity.
  • Table 1 Packet Format for SCW Design with Rank Prediction
  • Table 1 shows the packet format for SCW design with rank prediction in accordance with an embodiment.
  • Table 1 shows the PFs with SEs targeting the first to sixth transmission. 16 PFs are provisioned with SE-per-layer ranging from 0.5 bps/Hz/layer to 4.25 bps/Hz/layer with 0.25 bps/Hz/layer increments targeting the first transmission.
  • the maximum attainable SE-per- layer is 1.42 bps/Hz/layer.
  • the SE between 1.42 bps/Hz/layer and 2.13 bps/Hz/layer can be achieved by targeting the second transmission and SE greater than 2.13 bps/Hz/layer can be achieved by targeting the first transmission, where HARQ benefits diminish.
  • more PF#s may be added with SE/layer > 4.25 bps/Hz so that higher SE can be achieved by targeting the third transmission, and benefit from HARQ gains, hi such a case, a 6-bit CQI may be needed to ensure that the PF granularity is captured.
  • FIG. 5 shows a block diagram for a capacity based rank prediction in accordance with an embodiment.
  • H(k)P 4 (k) 502 through HCk)P 1 Ck) 508 are input into MMSE 512 through MMSE 518, respectively.
  • MMSE 512 through MMSE 518 produce SNR 4 Ck) 522 through SNR 1 Ck) 528, respectively.
  • SNR 4 Ck) 522 through SNR 1 Ck) 528 are input into Cap Mapper 532 through Cap Mapper 538, respectively.
  • Cap Mapper 532 through Cap Mapper 538 produces Ef-SNR 4 542 through Ef-SNR 1 548, respectively, and Cap 4 552 through Cap ! 558, respectively.
  • Cap 4 552 through Cap ! 558 are input into a decision unit 570.
  • Decision unit 570 produces a rank 572.
  • EfCSNR 1 542 through Ef[SNR 4 548 and the rank 572 are input into a select & quantize unit 574.
  • the select & quantize unit 574 produces a five-bit CQI 576.
  • the capacity based rank prediction algorithm works as follows:
  • AWGN additive white Gaussian noise
  • the processing units used to perform interference control may be implemented within one or more application specific integrated circuits (ASICs), digital signal processors (DSPs), digital signal processing devices (DSPDs), programmable logic devices (PLDs), field programmable gate arrays (FPGAs), processors, controllers, micro-controllers, microprocessors, other electronic units designed to perform the functions described herein, or a combination thereof.
  • ASICs application specific integrated circuits
  • DSPs digital signal processors
  • DSPDs digital signal processing devices
  • PLDs programmable logic devices
  • FPGAs field programmable gate arrays
  • processors controllers, micro-controllers, microprocessors, other electronic units designed to perform the functions described herein, or a combination thereof.
  • the interference control techniques may be implemented with modules (e.g., procedures, functions, and so on) that perform the functions described herein.
  • the software codes may be stored in a memory unit and executed by a processor.
  • the memory unit may be implemented within the processor or external to the processor, in which case it can be communicatively coupled to the processor via various means as is known in the art.

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PCT/US2005/047643 2004-12-22 2005-12-22 Prevision de numero de niveau fondee sur la capacite pour une conception mimo WO2006069397A2 (fr)

Priority Applications (10)

Application Number Priority Date Filing Date Title
JP2007548617A JP2008526137A (ja) 2004-12-22 2005-12-22 Ｍｉｍｏ設計用の容量ベースのランク予測
EP05856106A EP1832032A2 (fr) 2004-12-22 2005-12-22 Prevision de numero de niveau fondee sur la capacite pour une conception mimo
NZ556045A NZ556045A (en) 2004-12-22 2005-12-22 Capacity based rank prediction for MIMO design
MX2007007757A MX2007007757A (es) 2004-12-22 2005-12-22 Pronostico de clasificacion basado en capacidad para diseno de mimo.
CA002591609A CA2591609A1 (fr) 2004-12-22 2005-12-22 Prevision de numero de niveau fondee sur la capacite pour une conception mimo
BRPI0519539-0A BRPI0519539A2 (pt) 2004-12-22 2005-12-22 prediÇço de classificaÇço com base em capacidade para projeto mimo
AU2005318993A AU2005318993B2 (en) 2004-12-22 2005-12-22 Capacity based rank prediction for MIMO design
IL183999A IL183999A0 (en) 2004-12-22 2007-06-17 Capacity based rank prediction for mimo design
ZA200805129A ZA200705129B (en) 2004-12-22 2007-06-20 Capacity based rank prediction for mimo design
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AU2005318993A1 (en) 2006-06-29
UA90495C2 (ru) 2010-05-11
CN101124759A (zh) 2008-02-13
US20060018397A1 (en) 2006-01-26
KR100940466B1 (ko) 2010-02-04
NZ556045A (en) 2010-12-24
BRPI0519539A2 (pt) 2009-02-17
RU2378767C2 (ru) 2010-01-10
NO20073178L (no) 2007-09-18
IL183999A0 (en) 2007-10-31
JP2008526137A (ja) 2008-07-17
MX2007007757A (es) 2007-11-09
AU2005318993B2 (en) 2009-10-29
ZA200705129B (en) 2009-09-30
US7567621B2 (en) 2009-07-28
RU2007128046A (ru) 2009-01-27
KR20070094006A (ko) 2007-09-19
EP1832032A2 (fr) 2007-09-12

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