WO2002071429A1 - Circuit electrique permettant d'eviter la formation d'un arc electrique au-dessus d'un contact electrique - Google Patents

Circuit electrique permettant d'eviter la formation d'un arc electrique au-dessus d'un contact electrique Download PDF

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Publication number
WO2002071429A1
WO2002071429A1 PCT/EP2002/001071 EP0201071W WO02071429A1 WO 2002071429 A1 WO2002071429 A1 WO 2002071429A1 EP 0201071 W EP0201071 W EP 0201071W WO 02071429 A1 WO02071429 A1 WO 02071429A1
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WO
WIPO (PCT)
Prior art keywords
contact
transistor
electrical circuit
voltage
circuit according
Prior art date
Application number
PCT/EP2002/001071
Other languages
German (de)
English (en)
Inventor
Jürgen Bruck
Jörg SCHULTHEISS
Original Assignee
Tyco Electronics Amp Gmbh
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Tyco Electronics Amp Gmbh filed Critical Tyco Electronics Amp Gmbh
Priority to DE50208415T priority Critical patent/DE50208415D1/de
Priority to DE10290874T priority patent/DE10290874D2/de
Priority to EP02708324A priority patent/EP1366502B1/fr
Publication of WO2002071429A1 publication Critical patent/WO2002071429A1/fr

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Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01H—ELECTRIC SWITCHES; RELAYS; SELECTORS; EMERGENCY PROTECTIVE DEVICES
    • H01H9/00—Details of switching devices, not covered by groups H01H1/00 - H01H7/00
    • H01H9/54—Circuit arrangements not adapted to a particular application of the switching device and for which no provision exists elsewhere
    • H01H9/541—Contacts shunted by semiconductor devices
    • H01H9/542—Contacts shunted by static switch means
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01H—ELECTRIC SWITCHES; RELAYS; SELECTORS; EMERGENCY PROTECTIVE DEVICES
    • H01H9/00—Details of switching devices, not covered by groups H01H1/00 - H01H7/00
    • H01H9/54—Circuit arrangements not adapted to a particular application of the switching device and for which no provision exists elsewhere
    • H01H9/541—Contacts shunted by semiconductor devices
    • H01H9/542—Contacts shunted by static switch means
    • H01H2009/543—Contacts shunted by static switch means third parallel branch comprising an energy absorber, e.g. MOV, PTC, Zener
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01H—ELECTRIC SWITCHES; RELAYS; SELECTORS; EMERGENCY PROTECTIVE DEVICES
    • H01H9/00—Details of switching devices, not covered by groups H01H1/00 - H01H7/00
    • H01H9/54—Circuit arrangements not adapted to a particular application of the switching device and for which no provision exists elsewhere
    • H01H9/541—Contacts shunted by semiconductor devices
    • H01H9/542—Contacts shunted by static switch means
    • H01H2009/544—Contacts shunted by static switch means the static switching means being an insulated gate bipolar transistor, e.g. IGBT, Darlington configuration of FET and bipolar transistor
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01H—ELECTRIC SWITCHES; RELAYS; SELECTORS; EMERGENCY PROTECTIVE DEVICES
    • H01H9/00—Details of switching devices, not covered by groups H01H1/00 - H01H7/00
    • H01H9/54—Circuit arrangements not adapted to a particular application of the switching device and for which no provision exists elsewhere
    • H01H9/541—Contacts shunted by semiconductor devices
    • H01H9/542—Contacts shunted by static switch means
    • H01H2009/546—Contacts shunted by static switch means the static switching means being triggered by the voltage over the mechanical switch contacts

Definitions

  • the present invention relates to an electrical circuit for avoiding an arc over an electrical contact when the contact is opened according to the preamble of patent claim 1.
  • an arc can occur over the opening switch contact as a result of a current impression by the inductive component, via which the current flow is maintained at least for a short time.
  • Such an arc can greatly reduce the service life of the switch contact or - at higher voltages than a stationary arc
  • FIG. 19 An alternative to the conventional RC circuit shown in FIG. 18 is the additional use of a voltage-limiting element (for example a Zener diode or a varistor) shown in FIG. 19, as a result of which the RC element is only a very small part of the Shutdown energy must take up and the main part is implemented by the Zener diode after reaching the Z voltage (80 V in the present example).
  • the capacitance C can be designed correspondingly lower: in the present example, 1 ⁇ F is sufficient instead of the 1000 ⁇ F used in FIG. All other components shown in FIG. 19 have the same reference numerals and have the same value as the corresponding components in FIG. 18.
  • the invention is based on the knowledge that the electronic device provided according to the invention in parallel with the electrical contact, even when switching off higher inductive loads, for example in direct current circuits with working voltages above 20 V, causes the voltage across the contact to rise suddenly to supercritical values after the opening of the Contact is prevented and thus an opening arc can be reliably avoided.
  • the electrical circuit according to the invention also does not require its own power supply and is only connected to a switch or relay via two electrical connections.
  • the electric circuit according to the invention can also be used to prevent the arc on a changeover switch for braking an electric motor from being braked or in the event of a polarity reversal.
  • a particular advantage of the electrical circuit according to the invention is the possibility of a very compact structure, which is of great advantage in automotive engineering, among other things.
  • the service life of the mechanical contacts can be increased significantly, since only a relatively low mechanical wear of the contacts occurs.
  • switching contacts with the electrical circuit according to the invention represent a particularly cost-effective solution, since single contacts with small contact thicknesses can be used, the dynamic properties of the switching contact do not have to be subjected to great demands, and other complex arc-quenching devices can be dispensed with entirely.
  • a discharge diode V1 is connected in parallel with the resistor R2 Cathode is connected to the capacitance C.
  • the diode V1 simultaneously protects the gate of the amplifier V3 against negative gate-source voltages.
  • Another resistor R1 which is connected between the capacitor C and the switch contact, limits the discharge current of the capacitor C and improves the dynamic properties of the circuit.
  • a voltage-limiting component V2 can be connected in parallel with the capacitor C to protect the amplifier.
  • a particularly simple and inexpensive solution for such a voltage-limiting component is a zener diode.
  • a voltage-limiting component V4 can also be connected in parallel with the amplifier V3 as overvoltage protection for the amplifier when an inductive load is switched off.
  • Zener diode is advantageous because it is a very inexpensive component.
  • a power MOSFET is used as amplifier V3.
  • the advantage of this solution is that MOS field effect transistors can be controlled with little power and the overall structure can be greatly miniaturized.
  • the MOSFET is operated, for example, in a source circuit, i. H. the source connection is connected to the connection of the resistor R102, which is connected to the switch contact, and the gate connection is connected to the common connection of capacitance C and resistor R102.
  • the capacitance C is in the feedback branch between the drain and gate connection.
  • This embodiment offers the advantage that the capacitance C can have a comparatively low value and nevertheless has the effect of a significantly larger capacitance (Miller effect).
  • the voltage across the opening contact can advantageously be kept below the minimum voltage for arcing for a certain time, in order then to be sufficient large contact distance to quickly rise to the value appropriate for demagnetizing the load circuit.
  • the time for which the voltage across the contact is at a constant Value kept below the minimum voltage is determined by the series connection of a resistor and a capacitor.
  • the Darlington transistor comprises two bipolar transistors.
  • the voltage across the opening contact can be kept at the value of the base-emitter voltage of the Darlington transistor for a certain adjustable time and then quickly increased to the voltage required to demagnetize the load inductance.
  • the adjustable time is determined by the charging of the capacity.
  • the Darlington transistor conducts the current of the direct current circuit, first at the lower voltage level, then at a higher voltage level.
  • the charging of the capacitance is essentially determined by the base-emitter voltage of the first transistor.
  • the Darlington transistor comprises a field effect transistor as the first transistor and a bipolar transistor as the second transistor.
  • the voltage of the opening contact can advantageously be kept at the value of the gate-source voltage, for example of the logic power MOSFET, and this can be increased again quickly after the adjustable time has elapsed.
  • the MOSFET carries the current of the DC circuit and the charging of the capacitance is determined by the gate-source voltage of the MOSFET.
  • the substrate diode of the MOSFET can take over the task of the freewheeling diode D1 according to FIG.
  • a voltage-limiting component can be connected in parallel with the output of the amplifier as overvoltage protection for the amplifier when an inductive load is switched off.
  • a particularly simple and inexpensive solution for such a voltage-limiting component is a Zener diode. Their breakdown voltage should be far above the operating voltage of the direct current circuit in order to enable the inductive load circuit to commute quickly.
  • the required Z-voltage can also be set by connecting a plurality of Z-diodes with a lower Z-voltage in series, so that the voltage-limiting element as a whole has a smaller differential resistance and also a lower temperature. receives the coefficient and can better dissipate a possible power loss through the division.
  • the base of the Darlington transistor is controlled in a particularly effective manner by a second amplifier T9, which has a line type complementary to the Darlington transistor.
  • transistor T10 In order to keep amplifier T9 saturated during the adjustable time, it is controlled by a third amplifier, transistor T10, which has the same conductivity type as the Darlington transistor.
  • a thyristor structure can be provided parallel to the input of the Darlington transistor.
  • the advantageous properties of the electrical circuit according to the invention can be used particularly effectively in an electromagnetic relay, the electrical circuit being connected in parallel with a normally open contact of the relay.
  • the electrical circuit according to the invention can advantageously be used in an electrical connector to avoid an arc when the plug connection is released.
  • FIG. 1 shows a switch contact with a DC voltage supply and an inductive load, to which an electrical circuit for avoiding an arc is connected in parallel in accordance with a first advantageous embodiment
  • Figure 2 shows the switch contact of Figure 1 with an electrical circuit to avoid an arc according to a second advantageous embodiment
  • FIG. 3 shows the typical time profile of contact voltage and load current for a switching contact equipped with the electrical circuit according to the invention
  • Figure 4 shows the application of the electrical circuit according to the invention for the braked shutdown of an electric motor
  • FIG. 5 shows the application of the electrical circuit according to the invention for motor pole circuits
  • FIG. 6 shows the application of the electrical circuit for connectors according to the invention
  • FIG. 7 shows a circuit diagram of an electrical circuit for avoiding an arc according to a third embodiment
  • Figure 8 is a circuit diagram of an electrical circuit to avoid an arc according to a fourth embodiment
  • FIG. 9 shows an equivalent circuit diagram of a relay with an electrical circuit for avoiding an arc according to a fifth embodiment
  • FIG. 10 shows a circuit diagram of a thyristor structure from an electrical circuit for avoiding an arc according to a sixth embodiment
  • FIG. 11 shows a time course of the voltage across a make contact, the current through a load inductance and the collector current of a first transistor during a switching process in the circuit according to the invention in accordance with the third embodiment
  • FIG. 12 shows an enlarged detail from the time diagram in FIG. 11;
  • FIG. 13 shows a time course of a switching process when using an electrical circuit according to a fourth embodiment
  • FIG. 14 shows a time diagram for the switching process in a circuit according to the fifth embodiment for an operating voltage of 60 V;
  • FIG. 15 shows a time diagram of a switching process in a circuit according to the fifth embodiment at an operating voltage of 42 V;
  • FIG. 16 shows a time diagram of a switching process in a circuit according to the fifth embodiment at an operating voltage of 24 V;
  • FIG. 17 shows a time diagram to explain the effect of a thyristor structure according to FIG. 9;
  • FIG. 18 shows a conventional RC contact circuit according to the prior art
  • Figure 19 shows another conventional RC contact circuit according to the prior art.
  • FIGS. 1 and 2 show schematically an equivalent circuit of such a circuit.
  • L_Last denotes the load inductance
  • R_Last the ohmic component of the load resistance
  • U_L the DC voltage supply.
  • the load circuit is to be interrupted by opening the switch contact 101. Without a suitable measure, a mechanical single contact would be destroyed in the existing loads by a very intense and possibly even permanently burning arc after a short operating time or immediately. Therefore, according to the invention, an electrical circuit for avoiding an arc over the contact, which is referred to below as circuit 100, is connected in parallel with the switching contact 101.
  • a first and a second advantageous embodiment which are shown in FIGS. 1 and 2
  • a sudden voltage rise at the switch contact 101 is prevented in order to avoid the arc and instead a linear voltage rise is forced.
  • the circuit 100 In addition to a series circuit comprising a capacitor C and a resistor R2, which is connected in parallel with the switch contact 101, the circuit 100 according to the invention has an N-channel enhancement MOSFET V3, which is operated in the source circuit.
  • the source and bulk connections are connected to one another and, like the resistor R2, are at the potential of the switch contact connection 1.
  • the drain connection of the MOSFET V3 is connected to the switch contact connection 2.
  • the gate connection is led to the connection point between the capacitance C and the resistor R2.
  • the active circuit 100 By using the active circuit 100 in the first or second embodiment, it is achieved that this sudden increase from a certain threshold voltage changes to an approximately linear increase due to the activation of the MOSFET V3.
  • the threshold voltage is given by the value of the resistor R1, which is connected between the capacitance C and the terminal 2 of the switching contact, and the gate-source threshold voltage of the MOSFET.
  • the rate of rise of the voltage across contact 101 essentially depends on the values of capacitance C, resistor R2 and gate-source threshold voltage MOSFET.
  • the circuit 100 By suitable dimensioning of the circuit 100, it can be achieved that the linear increase in the voltage across the contact 101 takes place so slowly during the opening phase of the contact 101 that the voltage is at all times safely below the minimum value required for the ignition of the arc.
  • the circuit must be dimensioned in such a way that the contact voltage increases quickly enough to ensure that the maximum voltage and thus the highest possible resistance of the drain is within the contact changeover time, which is in the region of approximately half a millisecond. Source path at MOSFET V3 is reached. As a result, a shutdown with as little loss of energy as possible can be ensured.
  • the capacitance C therefore preferably has a value of 10 nF to 30 nF, the resistor R2 a value of approximately 1 k ⁇ and the resistor R1 a value of 2 ⁇ .
  • a voltage surge can occur at contact 100, i.e. the voltage across the contact 100 rises to values above the operating voltage.
  • a Zener diode V2 a limitation to the maximum voltage determined by the diode V2 and the gate-source threshold voltage of the MOSFET is achieved, avalanche operation of the MOSFET V3 is thus prevented.
  • the loss of heat generated in the MOSFET when switching off can preferably be dissipated by thermal coupling with the mechanical structure of a switch or relay. If the switch contact 101 is closed, the capacitance C must very quickly, i. H. can be discharged within milliseconds so that rapid switching changes are possible. This is done via the resistor R1, which has a very small value in the range of approximately 2 ⁇ , and the diode V1, which is polarized in the direction of flow during discharge. Resistor R1 also dampens the tendency of the circuit to oscillate.
  • a Zener diode V4 can also be connected between the drain and the source connection of the MOSFET.
  • This additional suppressor diode is mainly used for particularly high inductive loads and, after reaching the maximum voltage, absorbs the main part of the remaining switch-off energy. The resulting heat loss should also be dissipated via a direct thermal coupling with the mechanical structure of the switch or relay.
  • FIG. 3 shows the typical time profile of contact voltage and load current when a switching contact is switched off, which is equipped with a circuit 100 according to the invention in accordance with the first or second embodiment.
  • the load inductance L_Last has a value of 10 mH, the maximum load current is 10 A, the load voltage is 42 V.
  • the maximum contact voltage is limited to 60 V, the time until the switch-off energy is fully implemented is approx. 3 milliseconds. An arc does not ignite.
  • the circuitry 100 according to the invention can also be used if the movable center contact 1 does not remain open after the make contact has opened, but is switched to ground by subsequent contact with the break contact, as occurs, for example, when an electric motor 118 is switched off when braking.
  • the corresponding structure is outlined in Figure 4.
  • FIG. 5 shows a polarity reversal circuit for an electric motor 118 as a further possibility of using the circuit 100 according to the invention.
  • Such polarity reversal circuits are always required when the direction of rotation of an electric motor 118 is to be changed, such as in the motor vehicle sector with window regulators or the like.
  • two changeover relays 101A, 101B each with a circuit 100A, 100B according to the invention, are connected between the center contact 1 and the make contact 2.
  • the two normally open contacts 2 of the switching contacts 101A and 101B are connected to one another and are at + U_L.
  • the break contacts 3 are also connected to one another and connected to ground.
  • the circuit 100 according to the present invention can, however, also be used for the arc-free disconnection of circuits in plug connectors.
  • FIG. 6 shows such a plug connector 120, which comprises a plug part 122 and a socket part 124.
  • the contact pin 126 and the contact socket 128 must be separated from one another.
  • an auxiliary contact 130 is provided in the socket part 124, and the circuit 100 according to the invention is connected between the auxiliary contact 130 and the contact socket 128.
  • the load circuit between contact socket 128 and contact pin 126 is first interrupted.
  • contact pin 126 still remains electrically connected to auxiliary contact 130.
  • the circuit 100 becomes active and takes over the controlled switching off of the load circuit. After the load circuit has been finally disconnected by the circuitry 100, the electrical connection between the contact pin 126 and the auxiliary contact 130 can be disconnected.
  • the in Load circuit contained inductive energy is converted into heat. It is necessary to ensure that the time difference between the disconnection of the contact pin 126 from the contact socket 128 and the disconnection of the contact pin 126 from the auxiliary contact 130 is large enough to ensure that the load circuit is switched off by the circuitry 100.
  • the distance between the contact socket 128 and the auxiliary contact 130 must be chosen to be sufficiently large.
  • FIG. 7 schematically shows a further equivalent circuit diagram of a circuit with a switch contact 101 and an inductive DC load.
  • the load circuit is in turn to be interrupted by opening the switching contact 101.
  • an electrical circuit 100 according to a third advantageous embodiment is connected in parallel with the switch contact 101.
  • the formation of an arc is prevented in that the voltage across the contact 101 is initially kept constant at a low level and only increases to its final value when the contact is opened so far is that no more arc ignites.
  • the electrical circuit 100 has a Darlington transistor which is formed by the transistors T1 and T2.
  • the base of this Darlington transistor is controlled by a transistor T9 with a conduction type complementary to the Darlington transistor.
  • the transistor T9 in turn is controlled by a transistor T10 with the same conductivity type as the Darlington transistor in such a way that the transistor T9 is kept in saturation for an adjustable time.
  • This adjustable time is determined by a timing element R10, C1, which is located in the emitter branch of the transistor T10. During this time, the Darlington transistor is fully conductive at the low voltage level.
  • the capacitor C1 is charged only by the difference in the base voltages of the Darlington transistor on the one hand and the transistor T10 on the other.
  • the voltage across the switch contact 101 remains at this level until the capacitor C1 is charged to the extent that the decaying collector current of the transistor T10 due to the difference voltage from the base-emitter voltage of T1 / 2 and the base-emitter voltage of T10 Transistor T9 can no longer maintain saturation. This is followed by a relatively steep rise in voltage, only slowed down by the Miller capacitors, until it is accepted by the Zener diode Z1. Since the respective collector base capacities decrease with increasing voltage, the voltage increase also takes place with increasing speed. At the high level determined by the Zener diode, the load inductance LL commutates and a damped oscillation follows, during which the parasitic energies are dissipated.
  • FIG. 8 shows a fourth embodiment in which the transistor T1 of the Darlington transistor is formed by a logic power MOSFET instead of a bipolar transistor, as shown in FIG. 7.
  • the characteristic base-emitter voltage of the Darlington transistor (approx. 1.5 V) essentially goes into the gate-source Voltage at the operating point of the MOSFET above (approx. 3.5 V).
  • the transistor T9 is initially saturated and thereby essentially connects the drain connection and the gate connection of the MOSFET via the base-emitter path of the transistor T2 until the capacitance C1 is charged. This is followed by the voltage increase, which is slowed down by the Miller effect, up to the Z voltage.
  • the breakdown voltage of the Zener diode should be far above the operating voltage of the DC circuit in order to enable the inductive load circuit to commutate quickly.
  • the required Z voltage can be set by connecting a plurality of Z diodes of smaller Z voltages in series, these having a smaller differential resistance and also a smaller temperature coefficient, and a better dissipation due to the division can dissipate.
  • This higher control voltage is used to ignite a thyristor structure, which is formed from the transistors T3 and T4 in connection with the transistor T8, so that the current supplied by the transistor T9 due to the lower operating voltage of the thyristor ( ⁇ 1 V) compared to the normal control voltage of the Darlington transistor (> 1, 2 V) or the MOSFET (> 3.5 V) is derived. Therefore, the current drops in the output stage T1, T2 and the voltage, only slowed down by the Miller capacitors, can rise to a maximum of the Z voltage.
  • a special design of the thyristor structure is shown in FIG.
  • This thyristor is made via the sum of the voltages of the transistors T6 and T7 connected as diodes as reference voltage in conjunction with the resistance R7 to the normal control Darlington transistor voltage adjusted. If a MOSFET is used instead of a bipolar transistor for the transistor T1, a higher reference voltage and therefore a Z-diode may also be required due to the higher control voltage.
  • FIG. 1 Another possible embodiment of the thyristor is shown in FIG. After the thyristor has been ignited, the current to be dissipated is conducted via the transistor T3, the Schottky diode DS and the transistor T4.
  • the capacitors Cv1 and Cv2 serve to equalize the charge in the starting phase of the circuit arrangement immediately after the normally open contact 101 is opened.
  • the diodes T6 and T7 again form the reference voltage and control the transistor T4 here.
  • FIG. 11 shows a complete demagnetization process: in the left part, the voltage above the make contact (curve 110) only remains at a low level, namely after the circuit arrangement has started, the base-emitter voltage of the Darlington transistor is less than 2 V. Im Time range after 50.05 ms you can see the rapid voltage rise to approx. 75 V, this value being essentially determined by the Z voltage. A voltage level then follows over time, during which the load inductance commutates. In the area of the commutation of the load inductance, the current I at the inductance (curve 112) decreases linearly to zero. This area is followed by a decaying oscillation in the course of the voltage across the normally open contact while the parasitic energy is being reduced.
  • Curve 110 in turn means the voltage across switch contact 101, curve 112 the current through the load inductance and curve 114 the current that flows into the electrical circuit according to the invention.
  • the plateau voltage in the low range here is approximately 5 V due to the use of the MOSFET.
  • the demagnetization curve is identical to the course shown in FIG.
  • FIGS. 14, 15 and 16 show the demagnetization curves for different operating voltages, namely 60 V, 42 V and 24 V.
  • the normally closed contact of a changeover switch closes and forces the circuit to a voltage which is below the Z voltage.
  • the load inductance is also demagnetized during the bounce time of the normally closed contact (as can be seen from the curve 112), but the circuit arrangement follows the voltage changes, only delayed by the Miller effect of the semiconductors.
  • the circuit arrangement is not reset until the capacitor C1 is discharged again. This takes place via the resistor R10 and the diode D2 when, for example, the normally open contact 101 closes. After reopening the normally open contact 101, the circuit arrangement reacts again in the manner shown above and delays the voltage rise.
  • FIG. 17 shows excerpts of the effect of the thyristor structure under changed load conditions.
  • curve 116 shows a takeover of the control current supplied by transistor T9 and, associated therewith, a rapid voltage rise at the emitter of the Transistor T1 (curve 110 to the right of the auxiliary line).
  • the further increase in the current in the Darlington transistor up to approx. 20 A is due to the Miller effect of the rapidly increasing voltage now starting.
  • transistor T10 is also actively blocked, so that only the Miller effect of transistor T9 is effective. This can be seen from the decreasing current in the thyristor (see curve 116 falling below 1 A). In the following, a positive feedback becomes effective due to the decreasing operating voltage of the thyristor structure.
  • FIGS. 7 to 10 can also be used for the applications shown in FIGS. 4 to 6.

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  • Electronic Switches (AREA)
  • Relay Circuits (AREA)
  • Arc-Extinguishing Devices That Are Switches (AREA)
  • Keying Circuit Devices (AREA)

Abstract

La présente invention concerne un circuit électrique permettant d'éviter la formation d'un arc électrique au-dessus d'un contact électrique lorsque ce contact est ouvert. Le circuit électrique comprend un relais temporisateur qui, comparé au contact non câblé, implique une augmentation chronologiquement retardée de la tension de contact. L'invention vise à produire un circuit électrique empêchant la formation d'un arc électrique au-dessus d'un contact électrique, c'est-à-dire un circuit qui permette d'empêcher très vraisemblablement la formation d'un arc électrique lorsque le contact de commutation est ouvert et qui, de plus, soit de production économique et puisse être miniaturisé. A cet effet, le circuit électrique selon l'invention présente également un transistor qui est monté parallèle au contact de commutation. Ce transistor comprend, par exemple, un transistor à effet de champ MOS de puissance qui fonctionne dans le circuit Source, ou bien un transistor Darlington constitué de deux transistors bipolaires ou d'un transistor bipolaire et d'un transistor à effet de champ.
PCT/EP2002/001071 2001-03-01 2002-02-01 Circuit electrique permettant d'eviter la formation d'un arc electrique au-dessus d'un contact electrique WO2002071429A1 (fr)

Priority Applications (3)

Application Number Priority Date Filing Date Title
DE50208415T DE50208415D1 (de) 2001-03-01 2002-02-01 Elektrische schaltung zur vermeidung eines lichtbogens über einem elektrischen kontakt
DE10290874T DE10290874D2 (de) 2001-03-01 2002-02-01 Elektrische Schaltung zur Vermeidung eines Lichtbogens über einem elektrischen Kontakt
EP02708324A EP1366502B1 (fr) 2001-03-01 2002-02-01 Circuit electrique permettant d'eviter la formation d'un arc electrique au-dessus d'un contact electrique

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE10109871 2001-03-01
DE10109871.5 2001-03-01

Publications (1)

Publication Number Publication Date
WO2002071429A1 true WO2002071429A1 (fr) 2002-09-12

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PCT/EP2002/001071 WO2002071429A1 (fr) 2001-03-01 2002-02-01 Circuit electrique permettant d'eviter la formation d'un arc electrique au-dessus d'un contact electrique

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EP (1) EP1366502B1 (fr)
AT (1) ATE342575T1 (fr)
DE (2) DE50208415D1 (fr)
WO (1) WO2002071429A1 (fr)

Cited By (8)

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WO2003056588A1 (fr) * 2001-12-27 2003-07-10 Lear Automotive (Eeds) Spain, S.L. Procede et systeme permettant d'eviter la formation d'un arc electrique dans un connecteur intercale dans une ligne d'alimentation d'une charge de puissance
DE102004023452A1 (de) * 2004-05-12 2005-12-08 Tyco Electronics Amp Gmbh Elektrische Schaltung zur Vermeidung eines Lichtbogens an einem sich öffnenden Kontakt
DE102007042903A1 (de) 2007-07-02 2009-01-08 Bammert, Jörg Elektrische Schaltung
WO2010108565A1 (fr) * 2009-03-25 2010-09-30 Ellenberger & Poensgen Gmbh Disjoncteur pour l'interruption galvanique du courant continu
WO2016062427A1 (fr) * 2014-10-24 2016-04-28 Ellenberger & Poensgen Gmbh Disjoncteur pour l'interruption galvanique de courants continus
FR3060226A1 (fr) * 2016-12-14 2018-06-15 Schneider Electric Industries Sas Appareil electrique de mise a la terre, comprenant une derivation isolante, et son procede de fermeture
EP3570309A4 (fr) * 2017-01-13 2020-01-01 Sony Corporation Dispositif de suppression d'arc
DE102019135122A1 (de) * 2019-12-19 2021-06-24 Phoenix Contact Gmbh & Co. Kg Technik zur Vermeidung eines Lichtbogens beim Trennen einer Gleichstromverbindung unter Verwendung einer Verlängerung eines Leitungsverbunds

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WO2003056588A1 (fr) * 2001-12-27 2003-07-10 Lear Automotive (Eeds) Spain, S.L. Procede et systeme permettant d'eviter la formation d'un arc electrique dans un connecteur intercale dans une ligne d'alimentation d'une charge de puissance
ES2190756A1 (es) * 2001-12-27 2003-08-01 Lear Automotive Edds Spain S L Metodo y sistema para evitar la formacion de un arco electrico en un conector intercalado en una linea de alimentacion de una carga de potencia.
DE102004023452A1 (de) * 2004-05-12 2005-12-08 Tyco Electronics Amp Gmbh Elektrische Schaltung zur Vermeidung eines Lichtbogens an einem sich öffnenden Kontakt
DE102004023452B4 (de) * 2004-05-12 2006-05-11 Tyco Electronics Amp Gmbh Elektrische Schaltung zur Vermeidung eines Lichtbogens an einem sich öffnenden Kontakt
DE102007042903A1 (de) 2007-07-02 2009-01-08 Bammert, Jörg Elektrische Schaltung
CN102349124A (zh) * 2009-03-25 2012-02-08 埃伦贝格尔及珀恩斯根有限公司 用于电切断直流电的断路开关
WO2010108565A1 (fr) * 2009-03-25 2010-09-30 Ellenberger & Poensgen Gmbh Disjoncteur pour l'interruption galvanique du courant continu
RU2482565C2 (ru) * 2009-03-25 2013-05-20 Элленбергер Унд Поенсген Гмбх Разъединитель для гальванического прерывания постоянного тока
US8742828B2 (en) 2009-03-25 2014-06-03 Ellenberger & Poensgen Gmbh Disconnector switch for galvanic direct current interruption
WO2016062427A1 (fr) * 2014-10-24 2016-04-28 Ellenberger & Poensgen Gmbh Disjoncteur pour l'interruption galvanique de courants continus
US10607792B2 (en) 2014-10-24 2020-03-31 Ellenberger & Poensgen Gmbh Disconnecting device for galvanic direct current interruption
FR3060226A1 (fr) * 2016-12-14 2018-06-15 Schneider Electric Industries Sas Appareil electrique de mise a la terre, comprenant une derivation isolante, et son procede de fermeture
EP3336871A1 (fr) * 2016-12-14 2018-06-20 Schneider Electric Industries SAS Appareil electrique de mise a la terre, comprenant une derivation isolante, et son procede de fermeture
EP3570309A4 (fr) * 2017-01-13 2020-01-01 Sony Corporation Dispositif de suppression d'arc
DE102019135122A1 (de) * 2019-12-19 2021-06-24 Phoenix Contact Gmbh & Co. Kg Technik zur Vermeidung eines Lichtbogens beim Trennen einer Gleichstromverbindung unter Verwendung einer Verlängerung eines Leitungsverbunds

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EP1366502B1 (fr) 2006-10-11
ATE342575T1 (de) 2006-11-15

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