WO2002041549A1 - Procede permettant d'ameliorer le degre de precision de l'estimation de canaux dans un systeme de communication sans fil - Google Patents

Procede permettant d'ameliorer le degre de precision de l'estimation de canaux dans un systeme de communication sans fil Download PDF

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Publication number
WO2002041549A1
WO2002041549A1 PCT/CN2001/001184 CN0101184W WO0241549A1 WO 2002041549 A1 WO2002041549 A1 WO 2002041549A1 CN 0101184 W CN0101184 W CN 0101184W WO 0241549 A1 WO0241549 A1 WO 0241549A1
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Prior art keywords
code
channel estimation
correlation window
zero correlation
pilot
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PCT/CN2001/001184
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English (en)
French (fr)
Inventor
Zhaohui Cai
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Huawei Technologies Co., Ltd.
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Application filed by Huawei Technologies Co., Ltd. filed Critical Huawei Technologies Co., Ltd.
Priority to AU2002223382A priority Critical patent/AU2002223382A1/en
Priority to EP01996939A priority patent/EP1328080A4/en
Publication of WO2002041549A1 publication Critical patent/WO2002041549A1/zh
Priority to US10/418,321 priority patent/US20040001529A1/en

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04J—MULTIPLEX COMMUNICATION
    • H04J13/00—Code division multiplex systems
    • H04J13/0007—Code type
    • H04J13/0055—ZCZ [zero correlation zone]
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/0224—Channel estimation using sounding signals
    • H04L25/0226—Channel estimation using sounding signals sounding signals per se
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/69—Spread spectrum techniques
    • H04B1/707—Spread spectrum techniques using direct sequence modulation
    • H04B1/7097—Interference-related aspects
    • H04B1/711—Interference-related aspects the interference being multi-path interference
    • H04B1/7115—Constructive combining of multi-path signals, i.e. RAKE receivers
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B2201/00—Indexing scheme relating to details of transmission systems not covered by a single group of H04B3/00 - H04B13/00
    • H04B2201/69—Orthogonal indexing scheme relating to spread spectrum techniques in general
    • H04B2201/707—Orthogonal indexing scheme relating to spread spectrum techniques in general relating to direct sequence modulation
    • H04B2201/70701—Orthogonal indexing scheme relating to spread spectrum techniques in general relating to direct sequence modulation featuring pilot assisted reception

Definitions

  • the present invention relates to the technical field of channel estimation in wireless communication systems, and in particular, to a method for improving the accuracy of channel estimation in a wireless communication system with uplink synchronization or downlink synchronization.
  • CDMA Code Division Multiple Access
  • TD-SCDMA Time Division Synchronous Code Division Multiple Access
  • the time slot structure is divided into a data part and a pilot part, that is, the time slots of each user are substantially the same.
  • the base station When arriving at the base station, the base station usually performs channel estimation on the pilot code, and then performs demodulation on the data part according to the channel estimation result, such as RAKE reception, multi-user detection, and so on.
  • the received pilot portion is a superimposed signal of multiple users, the pilot sequence of each user must be different.
  • multiple access interference similar to the spread spectrum system will also be generated.
  • the above CDMA system generally adopts a pilot structure similar to the GSM (Global System for Mobile Communications) pilot, which mainly uses a basic pilot code in a cell, and the pilot code of each user in the cell is based on the basic pilot. Code shift generation.
  • GSM Global System for Mobile Communications
  • Such a pilot structure makes the system easy to use unbiased channel estimation.
  • the channel estimation method is a method of least squares, and the channels of all users are estimated at one time by solving an equation.
  • the upper limit of the performance of the channel estimation depends on the number of users, the selection of the pilot basic code, and the noise ratio in the system.
  • the basic pilot code can use various pseudo-random sequences, such as m-sequence and Gold sequence, or various orthogonal codes.
  • the length of the pilot and the length of the actual channel delay may limit the number of users that can transmit in parallel in the same slot in the cell. For example, for a TD-SCDMA system, if the single user channel impulse response width is 8 chips, since the pilot code can be actually used for a length of 128 chips, the number of users that can be transmitted by a single slot and carrier at the same time can only be The number of users is limited to 16.
  • the invention provides a method for improving the channel estimation accuracy of a wireless communication system with uplink synchronization or downlink synchronization.
  • the method can improve the accuracy of system channel estimation, and can simultaneously suppress multiple access interference or reduction in system channel estimation. Its impact is small, and the number of simultaneous users in a single slot and a single carrier increases.
  • a method for improving channel estimation accuracy of a wireless communication system with uplink synchronization or downlink synchronization includes at least the following steps:
  • the pilot code of this system uses a code group with a zero correlation window or a code group with a zero correlation window to spread the pilot code.
  • the length of the code group with zero correlation window is determined such that the width of the zero correlation window window is larger than the maximum channel transmission impulse response length of the system, and the number of codes with zero correlation window is greater than the maximum number of users of the system.
  • the method further includes the following steps: Different numbers of users use code groups with different zero correlation window widths.
  • the present invention uses a code group with zero correlation window characteristics as the pilot code, or uses a code group with zero correlation window characteristics to spread the pilot code, the interference inherent in the channel estimation of the system is reduced, and the channel estimation efficiency of the system is improved. accuracy. At the same time, multiple-access interference of the system is suppressed, and the influence of other noises is reduced, thereby improving system performance.
  • the pilot code of the system By configuring the pilot code of the system, more users can be accommodated in the system. If a smart antenna is used, the arrival angle of the signal can be configured according to the position of the user, so that the configurations of users adjacent to the arrival angle are cross-correlated with a code sequence with a wide zero correlation window.
  • FIG. 1 is a schematic diagram of a time slot structure using an LS code as a pilot code.
  • '' Spreading codes commonly used in traditional spread-spectrum communications include various pseudo-random sequences, such as m-sequences, Gold sequences, etc., or various orthogonal codes, such as WALSH (Wash) codes.
  • WALSH Wi-Fi Protected Access
  • the requirements for a spreading code are generally that its autocorrelation characteristics are good, and its autocorrelation sidelobe is small and small. For multi-user systems, small cross-correlation functions between spreading codes are required.
  • Traditional spreading codes only meet this requirement to a certain extent. For example, the WALSH code is completely orthogonal when the code words are aligned, but its orthogonality is seriously damaged when it is not aligned, and it is relevant when the mobile channel delay exceeds one chip.
  • the autocorrelation function of a spreading code with a zero correlation window is zero everywhere except the origin, that is, it has the most ideal characteristics. From the perspective of orthogonality, the relative delay of each spreading code and its own division by zero Outside, it is completely orthogonal to any non-zero relative delay.
  • a cross-correlation function between spreading codes with a zero correlation window has a zero correlation window near the origin. From the perspective of orthogonality, the spreading codes are completely orthogonal when the relative delay is smaller than the width of the zero correlation window.
  • a spreading code with a zero correlation window has good autocorrelation characteristics, and its cross-correlation characteristics are also good. When the two spreading codes are aligned, the cross-correlation function value is 0, and the two spreading codes are staggered by several chips. At the same time, the value of the cross-correlation function can still be 0, and the number of chips that can be staggered is the width of the correlation window.
  • a spreading code with zero correlation window such as the LS code involved in the LAS (Large Area Synchronization) 2000 CDMA system proposed by Linkair
  • the generation method is as follows:
  • the spreading codes are divided into two groups, one group is called a C code, and the other group is called an S code.
  • the C code and the S code are used in pairs.
  • the codewords generated according to this method have good autocorrelation characteristics. If the C and S codes are completely separated, there are no sidelobes in their autocorrelation.
  • For the cross-correlation feature for codewords with a total length of C and S of 128, there are 64 codewords with zero correlation window (-1, 1), and codewords with zero phase window (-3, 3) are There are 32 codewords with a zero correlation window of (-7, 7). Among them, this code also has a feature, the zero correlation window is (-3, 3) among the 32 code words Contains two sets of codewords with zero correlation windows (-7, 7). That is, for a code group with a certain zero correlation window, it can be further divided into multiple groups of code groups with a wider zero correlation window.
  • the physical layer structure of the TD-SCDMA system adopts a burst structure (BURST) or a time slot structure (SLOT).
  • BURST burst structure
  • SLOT time slot structure
  • the uplink and downlink use the same frequency band through time division multiplexing, and use different spreading codes in the same burst.
  • the data of multiple users can be transmitted simultaneously in the structure or the time slot structure.
  • smart antenna technology is used during uplink reception and downlink transmission to perform spatial processing on signals.
  • an LS code with a zero correlation window of (-7, 7) can be used.
  • the number of codes that meet this condition in a single group is 16, and (-7, 7)
  • Zero correlation window codes which may provide an estimate of the channel impulse response with a maximum delay of 15 chips.
  • the channel delay is less than 8 in most cases, and no special adjustment of the pilot position is required.
  • the pilot code transmission time of the user can be offset relative to the pilot codes of other users, and the channel estimation is guaranteed to be within the range of the zero correlation window window width.
  • an LS code with a zero correlation window of (-3, 3) can be used. At this time, the number of LSs that meet the conditions is 32, because delay may be provided at this time. Channel estimation with a width of 7. For users whose delay is significantly greater than 4, the steps similar to 3 can also be adopted. 5. If the TD-CDMA system uses a smart antenna, this can allow the signals to reach the pilots of users with similar angular directions, and configure a cross-correlation LS code sequence with a wide zero correlation window. This makes the delay of channel estimation wider.
  • the performance of the system will be improved under 16 users. In the case of expansion to 32 users, it is also improved than the original system method.
  • a code group with a zero correlation window is used as a pilot code or a code group with a zero correlation window is used to spread the pilot code, which reduces the interference of the channel estimation inherent in the system and improves the accuracy of the channel estimation of the system.
  • multiple-access interference of the system is suppressed, and the influence of other noise is reduced, thereby improving the performance of the system.
  • By configuring the pilot code of the system more users can be accommodated in the system. Any modification, equivalent replacement, or improvement made within the spirit and principle of the present invention shall fall within the scope of the claims of the present invention.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Power Engineering (AREA)
  • Mobile Radio Communication Systems (AREA)

Description

提高无线通信系统信道估计准确度的方法
技术领域 本发明涉及无线通信系统的信道估计技术领域， 尤其是涉及一种提 高具有上行同步或下行同步的无线通信系统的信道估计准确度的方法。 发明背景
目前， 基于直接序列扩频的 CDMA (码分多址）通信系统已经得到 较为广泛的应用。 在这些系统中， 多个用户同时占用相同的无线频率， 通过不同的用户特征序列， 即不同的扩频码来区分。 对于第三代移动通 信系统， 其中有一类 CDMA系统， 例如 TD-SCDMA (时分同步码分多 址）蜂窝通信系统， 其时隙结构分成数据部分和导频部分， 即各用户的 时隙基本同时到达基站， 在基站端一般通过对导频码做信道估计， 然后 根据信道估计的结果对数据部分进行解调， 如 RAKE接收， 多用户检测 等等处理。
由于接收到的导频部分为多个用户的叠加信号， 故每个用户的导频 序列必须有所不同。 在对信道进行估计时同样会产生类似于扩频系统的 多址干扰， 要对其中某个用户进行信道估计必须考虑其它用户对其的影 响。 上述 CDMA系统一般采用类似于 GSM (全球移动通信）导频的导 频结构， 其主要是在一个小区内采用一个基本的导频码， 小区内的各用 户的导频码由该基本的导频码移位生成。 这样的导频结构使得系统易于 采用无偏的信道估计， 文献 "CDMA移动通信系统上行接收机中的低运 算量信道估计，， ( "Low Cost Channel Estimation in the Uplink Receiver of CDMA Mobile Radio Systems" Bernd Steiner and Paul Walter Baier. FREQUENZ 47(1993) 11-12. )提出的信道估计方法能够一次同时对所有 用户进行信道估计， 其信道估计方法为采用最小二乘法的方法， 通过解 方程的方法一次对所有用户的信道进行估计。 信道估计的性能的上限取 决于用户的数目和导频基本码的选取， 及系统中的噪声比。 基本的导频 码可以采用各种伪随机序列， 如 m序列和 Gold序列， 或各种正交码。
由于系统的各个导频码之间存在多址干扰， 使得系统信道估计接收 复杂或性能不佳。 采用上述方法还存在一些其它缺点， 如： 1、 不能同 时完全抑制多址干扰或使其影响最小。 2、 导频的长度和实际信道可能 延时的长度限制了小区内同时隙内可以并行传送的用户数。例如对于 TD - SCDMA系统， 若取单用户信道冲击响应宽度为 8个码片， 由于导频 码可以实际使用的长度为 128个码片， 故单时隙单载波同时可以传送的 用户数只可以为 16个， 限制了系统用户数的扩展。 发明内容
本发明提供了一种提高具有上行同步或下行同步的无线通信系统的 信道估计准确度的方法， 使用该方法能够提高系统信道估计的准确度， 能同时抑制系统信道估计中的多址干扰或减小其影响， 并使得单时隙单 载波同时存在的用户数目增大。
本发明一种提高具有上行同步或下行同步的无线通信系统信道估计 准确度的方法至少包括以下步骤：
该系统的导频码采用具有零相关窗的码組或采用具有零相关窗的码 组对导频码进行扩频。
所述的具有零相关窗的码组长度的确定是使其零相关窗窗口宽度大 于系统的最大信道传输沖击响应长度， 且具有零相关窗的码的个数大于 系统最大用户数目。
根据本发明技术方案， 进一步包括以下步骤： 根据系统中具体的用 户数目不同采用具有不同零相关窗口宽度的码组。
由于本发明采用具有零相关窗特性的码组作为导频码， 或采用具有 零相关窗特性的码组对导频码进行扩频， 减少了系统内在的信道估计的 干扰， 提高系统信道估计的准确性。 同时抑制系统的多址干扰、 减小其 它噪声的影响， 进而提高系统的性能。 通过配置系统的导频码， 还可以 在系统中容纳较多的用户。 若使用智能天线， 可以根据用户的位置， 信 号的到达角配置使到达角相邻的用户的配置互相关具有较宽零相关窗 的码序列。 附图简要说明
图 1是采用 LS码作为导频码的时隙结构示意图。 实施本发明的方式
下面结合附图对本发明进行详细描述。 ' 传统的扩频通信一般采用的扩频码有各种伪随机序列， 如 m序列， Gold序列等， 或各种正交码， 如 WALSH (沃什）码等。 对于扩频码的 要求一般是要求其自相关特性好， 要求其自相关旁瓣少而且小。 而对多 用户系统要求扩频码之间互相关函数小。 传统的扩频码仅仅是在一定程 度上满足这个要求， 如 WALSH码在码字对齐时完全正交， 但是在没有 对齐时其正交性严重破坏， 在移动信道延时超过一个码片时相关特性变 差。这些码在应用到移动多径传输信道中，多用户系统会产生多址干扰。 因此对于多用户的信道估计， 如果各用户的导频码自相关特性好和各用 户导频码的互相关特性好， 将能较大提高信道估计的精度。
具有零相关窗的扩频码的自相关函数除原点外处处为零， 即其具有 最理想的特性。 从正交性的观点来讲， 各扩频码与其自身除零相对时延 处外， 对任何非零相对时延都完全正交。 具有零相关窗的扩频码间的互 相关函数在原点附近存在一个零相关窗口。 从正交性观点来讲， 各扩频 码之间在相对时延小于该零相关窗口的宽度时是完全正交的。 具有零相 关窗的扩频码具有良好的自相关特性， 且其互相关特性也比较好， 在两 个扩频码对齐时其互相关函数值为 0， 两个扩频码错开几个码片时其互 相关函数值还能保持为 0， 可以错开的码片的个数为零相关窗窗口的宽 度。
对于具有零相关窗的扩频码， 如 Linkair公司所提出的 LAS (大区 域同步） 2000 CDMA系统中所涉及的 LS码， 就是一种具有零相关窗特 性的扩频码。 其生成的方式为： 把扩频码分成两组， 一组称为 C码， 一 组称为 S码， C码和 S码成对使用。 其中 C, S码的生成方式为， 首先 必须有最基本的两个 C码， 两个 S码， 如取 1,5 = 1， =-1。 然 后由下面公式就可以生成其它长度的 LS码:
LS
LS
+
LS
LS - (CM CM'SM SM)。
=l?253 i = 0, 1,2...,2M- 码， 其中—表示取反， +表示序号的增加。
按照这种方法生成的码字， 具有良好的自相关特性， 若 C， S码完 全分开的话， 则其自相关不存在旁瓣。 对于互相关特性， 则对于 C, S 总长为 128的码字， 则存在零相关窗为 （ - 1, 1) 的码字为 64个， 零 相窗为 （ -3， 3) 的码字为 32个， 零相关窗为 （ - 7, 7) 的码字为 16 个。 其中这种码还有一个特点， 零相关窗为 （ - 3, 3) 的 32个码字中 包含两组零相关窗为 （ - 7, 7 ) 的码字。 即对于一定零相关窗的码组， 都可以进一步分为多组具有更宽的零相关窗的码组。
下面以 TD-SCDMA系统为例， 对本发明作进一步的阐述。
本例 TD-SCDMA系统的物理层结构采用突发结构 （BURST )或时 隙结构 （SLOT ), 其中上下行通过时分复用使用同样的频段， 通过采用 不同的扩频码， 在同一个突发结构或时隙结构内可以同时传送多个用户 的数据， 其中在上行接收和下行发射时采用智能天线技术， 对信号进行 空域的处理。
1、 首先保持系统的原有时隙结构不变， 对中间长 144的 midamble (中间导频码）码进 4亍修改， 并采用长 128的 LS码作为导频码。 导频 的构造参考图 1, 其中时隙数据段与导频段可以设置一些 GAP, 即保护 的码片， 这些码片不发送信号。 若保持时隙的其它部分不变， GAP的总 长度为 16。 图中 （1 )、 （2 )、 （3 )分别示出了三种导频码位置示意。
2、 当系统内的用户数少于 16个， 可以使用零相关窗为 （ - 7， 7 ) 的 LS码， 单组符合这样条件的码的个数为 16个， （ - 7, 7 ) 的零相关 窗码， 最大可能提供延时为 15 ·个码片长度的信道冲击响应的估计。 一 般情况下， 根据 TD-CDMA系统的设置， 大部分情况信道的延时都小于 8, 不需要对导频的位置作特殊的调整。
3、 若系统中某用户的信道延时长度大于 8, 可以使该用户的导频码 发送时间相对于其它用户的导频码做相应的偏移， 保证信道估计是在零 相关窗窗口宽度范围内进行。
4、 当系统内的用户数多于 16个时， 可以使用零相关窗为（ - 3, 3 ) 的 LS码， 此时满足条件的 LS的个数为 32个， 由于此时可能提供延时 宽度为 7的信道估计。 对于延时明显大于 4的用户同样可以采用类似于 3的步骤。 5、 如果 TD-CDMA系统使用智能天线， 这样可以使信号到达角方 向相差不多的用户的导频， 配置互相关具有较宽零相关窗的 LS码序列。 使得信道估计的延时有所拓宽。
在使用采用 LS码做导频码的本发明后， 在 16个用户以下， 系统的 性能会得到改善。 在扩展到 32个用户的情况下， 比系统原来方法也有 所改善。 本发明采用具有零相关窗的码组作为导频码或釆用具有零相关窗的 码组对导频码进行扩频， 减少了系统内在的信道估计的干扰， 提高系统 信道估计的准确性。 同时抑制系统的多址干扰、 减小其它噪声的影响， 进而提高系统的性能。 通过配置系统的导频码， 还可以在系统中容纳较 多的用户。 凡在本发明的精神和原则之内， 所作的任何修改、等同替换、 改进等， 均应包含在本发明的权利要求范围之内。

Claims

权利要求书
1、 一种提高具有上行同步或下行同步的无线通信系统信道估计 准确度的方法， 其特征在于， 该方法至少包括以下步骤：
该系统的导频码采用具有零相关窗的码组或采用具有零相关窗的码 组对导频码进行扩频。
2、 根据权利要求 1 所述的提高信道估计准确度的方法， 其特征 在于：
所述具有零相关窗的码组长度的确定是使其零相关窗窗口宽度大于 系统的最大信道传输冲击响应长度， 且具有零相关窗的码的个数大于系 统最大用户数目。
3、 根据权利要求 1所述的信道估计准确度的方法， 其特征在于， 进一步包括以下步骤：
根据系统中具体的用户数目不同采用具有不同零相关窗口宽度的码 组。
4、 根据权利要求 1至 3任一所述的提高信道估计准确度的方法， 其特征在于， 所述具有零相关窗的码组为 LS码。
PCT/CN2001/001184 2000-10-20 2001-07-19 Procede permettant d'ameliorer le degre de precision de l'estimation de canaux dans un systeme de communication sans fil WO2002041549A1 (fr)

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