WO2001013466A1 - Procede d'elimination des interferences faisant appel a une antenne intelligente - Google Patents

Procede d'elimination des interferences faisant appel a une antenne intelligente Download PDF

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Publication number
WO2001013466A1
WO2001013466A1 PCT/CN2000/000170 CN0000170W WO0113466A1 WO 2001013466 A1 WO2001013466 A1 WO 2001013466A1 CN 0000170 W CN0000170 W CN 0000170W WO 0113466 A1 WO0113466 A1 WO 0113466A1
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WO
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Prior art keywords
smart antenna
signals
interference cancellation
interference
signal
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PCT/CN2000/000170
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English (en)
French (fr)
Inventor
Feng Li
Shihe Li
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China Academy Of Telecommunications Technology, Mii
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Application filed by China Academy Of Telecommunications Technology, Mii filed Critical China Academy Of Telecommunications Technology, Mii
Priority to MXPA02001465A priority Critical patent/MXPA02001465A/es
Priority to DE2000636485 priority patent/DE60036485T2/de
Priority to AU53873/00A priority patent/AU771268B2/en
Priority to JP2001517464A priority patent/JP4615170B2/ja
Priority to BRPI0013209A priority patent/BRPI0013209B1/pt
Priority to EP00938467A priority patent/EP1220355B1/en
Priority to CA 2381366 priority patent/CA2381366C/en
Publication of WO2001013466A1 publication Critical patent/WO2001013466A1/zh
Priority to US10/073,567 priority patent/US6639551B2/en

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/69—Spread spectrum techniques
    • H04B1/707—Spread spectrum techniques using direct sequence modulation
    • H04B1/7097—Interference-related aspects
    • H04B1/711—Interference-related aspects the interference being multi-path interference
    • H04B1/7113—Determination of path profile
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/2605—Array of radiating elements provided with a feedback control over the element weights, e.g. adaptive arrays
    • H01Q3/2611—Means for null steering; Adaptive interference nulling

Definitions

  • the present invention relates to a wireless communication technology, and more particularly, to a processing technology for canceling interference signals in a wireless base station or a user terminal using a smart antenna.
  • a base station structure of a wireless communication system using a modern smart antenna including An antenna array consisting of multiple antenna elements, a corresponding RF feeder cable, and a set of coherent RF transceivers.
  • the baseband signal processor obtains the spatial characteristic vector of the signal and the signal arrival direction (D0A), and uses the corresponding algorithm to realize the receiving antenna beam Shape.
  • Any one of the antenna elements, the corresponding RF feeder cable and the coherent RF transceiver is called a link.
  • the weight of each link obtained from the uplink receive beamforming is used for downlink transmit beamforming, and under the condition of symmetrical radio wave propagation, the full function of the smart antenna is achieved.
  • Mobile communication system is a Communication systems operating under changing mobile environments (refer to ITU Recommendation M1225), so the effects of severe time-varying and multipath propagation must be considered.
  • ITU Recommendation M1225) ITU Recommendation M12257
  • the research on beamforming algorithms for smart antennas is involved. The research conclusion is that the stronger the function, the more complicated the algorithm.
  • antenna beamforming must be completed in real time, and the time to complete the algorithm can only be calculated in L seconds. Limited by the level of modern microelectronic technology, in such a short period of time, digital signal processors (DSPs) or application-specific chips (ASICs) cannot achieve overly complex real-time processing.
  • DSPs digital signal processors
  • ASICs application-specific chips
  • a simple maximum power synthesis algorithm can be adopted for the CDMA mobile communication system.
  • the algorithm is not only simple, but also can solve the synthesis of multipath components whose delay is within the width of a chip.
  • modern code division multiple access mobile communication systems have large delays and high amplitudes of multipath propagation components in a mobile environment, and still cause severe interference. That is, in this mobile communication environment, the simple, real-time algorithm of smart antenna beamforming cannot solve the multipath propagation interference problem, nor can it completely solve the capacity problem of the CDMA mobile communication system.
  • Rake receivers and joint detection or multi-user detection technology have been studied in depth, and they are widely used in code In the multiplex mobile communication system, but for a mobile communication system that has used the smart antenna technology, it is not convenient to directly use the above-mentioned Rake receiver or multi-user detection technology.
  • the main reasons are: Based on the principle of Rake receiver or multi-user detection technology, they process CDMA signals of multiple code channels and synthesize or cancel the main multipath components. Smart antenna technology is targeted at each CDMA. Code channels are separately beamformed, and after channel estimation and matched filters, the matrix is used to find the inverse straight Then, the information of all user terminals is extracted at one time.
  • the two-dimensional smart antenna technology which is currently in the research stage, is not only immature, but also quite complicated.
  • Another method is to perform multi-user detection processing after using a smart antenna.
  • each code channel is separated, that is, each code channel must be separately subjected to multi-user detection processing, which not only fails to make full use of multi-user detection. Function, which also greatly increases the complexity of baseband signal processing.
  • the purpose of the present invention is to design an interference cancellation method based on a smart antenna, so that a code division multiple access mobile communication system or other mobile communication system can solve multipath propagation while using a smart antenna and using a simple maximum power synthesis algorithm. And other interference problems, and get good results.
  • a further object of the present invention is to provide a new digital signal processing method, which can be applied to a code division multiple access mobile communication system or other mobile communication systems, so that the mobile communication system can solve various problems while using a smart antenna. Interference such as multipath propagation.
  • a smart antenna-based interference method includes the following steps: A. Use the beamforming matrix obtained by the real-time beamforming algorithm to beamform the digital signals output by a smart antenna-based receiver to obtain a set of beamformed digital signals, expressed as NR k (m ), Where k represents a code channel and m represents a sampling point;
  • the digital signal output by the smart antenna-based receiver in step A is sampled.
  • the step A is completed in a baseband signal processor and includes: synchronizing and eliminating oversampling of digital signals output by a smart antenna-based receiver; performing descrambling and despreading, and separating into signals of each code channel; In the beamformer, a beamforming synthesis algorithm is used to shape the reception beam of each link, and the synthesis result is obtained.
  • the beamforming synthesis algorithm is a maximum power synthesis algorithm.
  • the step A further includes demodulating the digital signal output from the smart antenna output by the beamformer and detecting the signal-to-noise ratio of the training sequence. When the signal-to-noise ratio exceeds a threshold value, the received data is directly output and ended. If the ratio is lower than the threshold value, the subsequent steps are further performed.
  • the step B further includes: finding a main path of a signal in the shaped beam of the working code channel from other end users; spreading and scrambling the signal to restore the digital signal to the sampling level; Subtract the main path signals of other end users whose energy exceeds the threshold value from the digital signal NR k (m) to obtain the NS k (m).
  • the main path of the signals in the shaped beam of the working code channel from other end users is to find the signal levels of the other code channels in the working code channel beam.
  • the step C further comprises: moving the positions of the sampling points one by one within a symbol to obtain multiple sets of chip-level signals; correlating them with a known scrambling code to obtain multiple sets of outputs whose energy exceeds a threshold value; for these Add the known scrambling code to the output to recover multi-path interference at multiple sampling levels; subtract the multi-path interference from other users from the digital signal NS k (m) obtained in step B, and reduce the main path of the k-th code channel.
  • the multipath signal are superimposed in phase to obtain the sampling value of the k-th code channel after interference cancellation; performing descrambling, despreading and demodulation on the sample value of the k-th code channel to obtain the k-th code channel interference cancellation Signal, k takes any positive integer.
  • step C is performed only in one symbol, and the number of times required is equal to the number of samples in each chip multiplied by the spreading factor and then subtracted by one.
  • the step D further includes: subtracting the digital signal interference from other end users from the digital signal NS k (m) obtained in step B, and offsetting the multipath interference signal from other end users.
  • the step D is performed at the sampling level, and the signals involved are signals converted to the sampling level.
  • the step E further includes: canceling the main path and the multipath from other users Sampling the perturbed signal to obtain the value of each chip; after descrambling and despreading using the kth spreading code, the main path and multipath signals from the working end user are superimposed in phase to obtain interference cancellation Output signal after pin cancellation; Demodulation to obtain the required received data after interference cancellation.
  • the steps A, B, C, D, and E are interference cancellation for all code channels whose signal-to-noise ratio does not reach the threshold.
  • the steps A, B, C, D, and E are used for interference cancellation in a mobile communication base station; the steps C, D, and E are used for interference cancellation of a user terminal.
  • the method of the present invention is applicable to a CDMA mobile communication system in which a longer training sequence (pilot Pilot or Midamble) is not designed in the frame structure, or a longer training sequence (pilot Pilot or Midamble) is designed in the frame structure.
  • a longer training sequence pilot Pilot or Midamble
  • pilot Pilot or Midamble pilot Pilot or Midamble
  • the method of the present invention is required to eliminate multipath interference for each code channel to achieve the purpose of correct reception.
  • the method of the present invention proposes a simple maximum power synthesis algorithm, so that the smart antenna can perform beamforming at the symbol level to achieve the effect of real-time operation.
  • the new multi-path interference cancellation technology proposed by the present invention most of the multi-path interference from this channel and the multi-path interference from other channels can be cancelled. It is an integer multiple, but the probability of occurrence is very low), in order to minimize the influence of interference such as multipath propagation, and achieve the purpose of correct reception.
  • the method of the present invention has a limited amount of calculations, and can be completely implemented by using a currently commercially available digital signal processor (DSP).
  • DSP digital signal processor
  • CDMA code division multiple access
  • FDMA frequency division multiple access
  • TDMA time division multiple access
  • Figure 1 is a block diagram of the structure of a CDMA mobile communication base station using a smart antenna
  • Figure 2 is a principle block diagram of the signal-to-noise ratio detection and processing process on the output of the smart antenna in Figure 1.
  • FIG. 3 is a schematic block diagram of the interference cancellation method of the present invention.
  • Figure 4 is a block diagram of the structure of a mobile communication user terminal.
  • a base station structure in a typical wireless communication system such as a mobile communication system with a smart antenna or a wireless user loop system is shown. It mainly includes N identical antenna units 201A, 201B, 201N, N almost identical RF feeder cables 202A, 202B, ..., 202N, N radio frequency transceivers 203A, 203B, ..., 203N, and corresponding baseband signal processors 204. All radio frequency transceivers 203A, 203B, ..., 203N use the same local oscillator signal source 208 to ensure the coherent operation of each radio frequency transceiver of the base station.
  • All RF transceivers 203A, 203B, ..., 203N are provided with an analog-to-digital converter (ADC) and a digital-to-analog converter (DAC), so the input and output signals of the baseband signal processor 204 are both For digital signals, the radio frequency transceivers 203A, 203B, 203N and the baseband signal processor 204 are connected through a high-speed digital bus 209.
  • ADC analog-to-digital converter
  • DAC digital-to-analog converter
  • the basic working principle of the base station using the smart antenna and the working method of the smart antenna have been in the previous invention patent "Time Division Duplex Synchronous Code Division Multiple Access Wireless Communication System with Smart Antenna" (ZL 97 1 04039. 7) It is illustrated that the interference method of the present invention for receiving signals from smart antennas is also implemented in a base station of this structure.
  • the present invention does not change the working principle and characteristics of the smart antenna itself, and the present invention does not discuss the processing process of the transmitted signal, and only describes the interference cancellation method for the received signal.
  • the working mode of the smart antenna implemented by the baseband signal processor 204 under the base station structure shown in FIG. 1 is described. Assume that this code division multiple access wireless communication system has a total of K code channels.
  • the smart antenna system is composed of N antenna units, N radio frequency feeder cables, and N radio frequency transceivers, and will be described using the i-th receiving link.
  • the i-th radio frequency transceiver 203i outputs the digital signal after analog-to-digital conversion (ADC) and oversampling of the received signal from the antenna unit 201i, which is represented as S i (m), Where m is the m-th sampling point; step 302, the digital signal Si (m) passes through the box? After synchronizing and eliminating oversampling in 210, a chip-level digital signal is obtained, which is expressed as sli (n), where n represents the nth chip (chip); Step 303, the chip-level digital signal (n) passes through a box?
  • ADC analog-to-digital conversion
  • the descrambling code and despreading of 205 are separated into symbol-level signals of K code channels, which are represented as x ki (l), where 1 represents the first symbol;
  • Step 304 the symbol-level signals of the K code channels x ki (l) Form the receiving beam of the i-th link by using a certain beamforming synthesis algorithm through K beamformers 206, and obtain the synthesis result, which is expressed as:
  • k l, 2,..., K
  • w ik (l) is the beamforming coefficient of the k-th code channel on the i-th link.
  • x ki * (l) is a conjugate complex number of x ki (l), thereby obtaining a symbol-level beamforming matrix W k , where R k (l) is an output of the smart antenna system.
  • the weight of each link during uplink (base station reception) beamforming can be directly used for downlink (base station transmission) beamforming, fully obtaining the advantages of a smart antenna.
  • the received signal After processing the output Rk (l), the received signal can be obtained.
  • the interference that needs to be offset in the smart antenna CDMA wireless base station and the new signal processing method related to the present invention are shown.
  • step 306 the K demodulation units 207A, 207B, ⁇ , 207K and K signal-to-noise ratio (S / N) detection units 221A, 221B, ..., 221 are processed by the baseband signal processor 204.
  • the output R k (1) signal of the output smart antenna system is used to demodulate and detect the signal-to-noise ratio of its training sequence (the training sequence in any mobile communication system is known and can be obtained with only a comparison), If the signal-to-noise ratio of this output signal exceeds a preset threshold (step 307 in FIG. 3 and diamond box in FIG. 1), it means that the corresponding code channel has no errors or the number of errors is lower than a given value, then step 308 may be performed.
  • step 307 in FIG. 3 and diamond box in FIG. 2 Directly output the received signal, output the received data, and end the processing; if the signal-to-noise ratio of the output signal is lower than the threshold value (step 307 in FIG. 3 and diamond box in FIG. 2), go to step 305 and proceed to the next stage Signal processing (if the wireless communication system has no training sequence, it is not necessary to perform signal-to-noise detection in steps 306 and 307).
  • Step 305 Obtain the input digital signal NR k (m) after beamforming. This work is done in boxes (?) 222A, 222B, ⁇ ., 222. First, assuming that the processed code channel is a code channel used by the k-th user terminal, use the obtained beamforming matrix w ik (l) for the k-th code channel to directly beam-form the received data signal. Shape to form a new set of data NR k (m):
  • k l, 2, ... K;
  • w ik is the average value of the beamforming matrix of the k-th code channel in one frame, that is:
  • the multiple received CDMA signals are shown in Figure 1.
  • the obtained new data signal NR k (m) is sent to K multipath processors 223A, 223B, 223K, and processed by the new processing method of the present invention.
  • the processing process mainly includes steps 310 and 312.
  • the first step is a second step consisting of step 314, a third step consisting of step 316, and a fourth step consisting of step 318, as shown in FIG.
  • Step 1 Cancel the main path components contained in the signal level in the input digital signal NR k (m) k after beam shaping from other users.
  • the processing is as follows:
  • F v * (l) is the conjugate complex number of F v (l)
  • L is the number of symbols to be counted. Obviously, L should be less than or equal to the number of symbols in one frame.
  • the third step is to cancel the multipath signals, and to cancel the multipath signals from other users in NS k (m) to obtain SS k (m). Subtracting other interference data signals exceeding the threshold value from the input data signal NS k (m) obtained in the second step can offset multipath interference signals from other users:
  • the signal s3 kt (n) should be converted to the sampling level to form s3 kt (m).
  • each sample value can be considered to be uniformly distributed.
  • the fourth step is to obtain the output RS k (l) after interference cancellation.
  • the sampled value SS k (m) of the multipath interference signal from other users is canceled, and the chip-level digital signal value s4 k (n) is obtained, and the main path signal and the multipath signal of the kth code channel are made in phase.
  • the output signal RS k (1) after interference cancellation can be obtained.
  • step 320 After step 320 demodulation, the desired result after interference cancellation is finally obtained, and the data is output in step 308 and ends.
  • a structure of a CDMA user terminal using the method of the present invention includes: an antenna 401, a wireless transceiver 402, an analog-to-digital converter 403, a digital-to-analog converter 404, and a baseband signal processor 405.
  • the method of the invention will be implemented in the baseband signal processor 405 Medium implementation.
  • the output of the analog-to-digital converter 403 can be directly used for the above-mentioned input digital signal NR k (m), and then the interference cancellation is performed using the above-mentioned first to fourth steps.
  • these main path signals Fv (l) can be obtained by directly descrambling codes and despreading, without using the above formula (5), directly from the formula ( 6) Start.
  • the beamforming in the method of the present invention is performed at a base station.
  • the signal received by the user terminal itself is the digital signal NR k (m) after the beamforming, according to
  • the number k of code channels that the user terminal needs to receive can be used to cancel the interference of the K code channels using the aforementioned four steps.
  • the technical solution of the present invention is mainly directed to a code division multiple access mobile communication system, after simple changes, it can be applied to a frequency division multiple access and time division multiple access mobile communication system.
  • Any technician who is engaged in the research and development of wireless communication systems can understand the basic principles of smart antennas and the basic knowledge of digital signal processing, and can design high-quality smart antenna systems according to the method proposed by the present invention and use them in various High performance indicators in mobile communication or wireless user loop systems.
  • the method of the present invention is also a new set of digital signal processing methods, which can be used in a code division multiple access mobile communication system or other wireless communication systems, so that the system can solve various interferences such as multipath propagation while using a smart antenna. And get good results.

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Description

一种基于智能天线的干扰抵销方法
技术领域
本发明涉及一种无线通信技术， 更确切地说是涉及一种在使用智 能天线（Smart Antenna)的无线基站或用户终端中进行抵销干扰信号的 处理技术。 发明背景
在现代无线通信系统中， 特别是在码分多址（CDMA)无线通信系统 中， 为了提高系统容量和系统灵敏度， 及能在较低的发射功率下获得 较远的通信距离， 一般都使用智能天线技术。
在名称为 "具有智能天线的时分双工同步码分多址无线通信系统" 的发明专利中（ZL 97 1 04039. 7) , 公开了一种采用现代智能天线的无 线通信系统的基站结构， 包括由多个天线单元组成的天线阵列、 相应 的射频馈电电缆和一组相干的射频收发信机。 根据天线阵列中各天线 单元所接收到的、 来自用户终端的信号的不同反应， 由基带信号处理 器获得此信号的空间特征矢量和信号到达方向（D0A) , 并使用相应的算 法实现接收天线波束赋形。 其中任一个天线单元、 相应的射频馈电电 缆和相干的射频收发信机称为一条链路。 然后， 将从上行接收波束赋 形中获得的每一条链路的权重使用于下行发射波束赋形， 在对称的电 波传播条件下， 达到智能天线的全部功能。
现代无线通信的主体是移动通信。 移动通信系统是一种在复杂多 变的移动环境下工作的通信系统（参照 ITU建议 M1225 ), 因此必须考 虑严重的时变和多径传播的影响。 在上述专利及在许多公开发表的技 术文献中， 都涉及到对智能天线的波束赋形算法的研究， 其研究结论 是： 功能越强， 则算法越复杂。 由于在移动通信环境下， 天线波束赋 形是必须实时完成的， 且完成算法的时间只能以 L秒计算。 而受现代 微电子技术水平的限制， 在如此短的时间内， 数字信号处理器（DSP)或 专用芯片（ASIC)还不能实现过于复杂的实时处理。 面对上述矛盾， 可针对码分多址移动通信系统采用一种简单的最 大功率合成算法， 该算法不仅筒单， 还可解决时延在一个码片（Chip) 宽度内的多径分量的合成。 但现代的码分多址移动通信系统， 在移动 环境下的多径传播分量时延较大、 幅度较高， 仍然会造成严重的干扰。 即在此移动通信环境下， 智能天线波束赋形的简单、 实时的算法并不 能解决多径传播干扰问题， 也就不能彻底解决 CDMA移动通信系统的容 量问题。
另一方面，为解决多径传播产生的干扰问题，人们深入研究了 Rake接 收机和联合检测或称多用户检测技术（Joint Detect ion , Mul t i User Detect ion) , 并将其广泛地用于码分多址移动通信系统中， 但对于已经 使用了智能天线技术的移动通信系统来说， 却并不便于直接使用上述 Rake接收机或多用户检测技术。 其主要原因是： 基于 Rake接收机或多 用户检测技术的原理， 它们是对多码道的 CDMA信号进行处理， 对主要 的多径分量进行合成或抵销， 而智能天线技术是针对每一条 CDMA 的码 道分开进行波束赋形， 再经信道估值和匹配滤波器后， 通过矩阵求逆直 接将所有用户终端的信息一次解出。
目前正处于研究阶段的二维智能天线技术， 其算法不仅不成熟， 而 且相当复杂。
还有一种方法是在使用智能天线后进行多用户检测处理， 但由于此 时每一条码道已经分开， 即必须对每一条码道分别进行多用户检测处 理， 不仅不能充份发挥多用户检测的功能， 还大大增加了基带信号处理 的复杂度。 发明内容
为了使 CDMA 移动通信系统具有更高的容量和更好的性能， 必须找 到一种简单且实时工作又便于在基于智能天线的 CDMA 移动通信系统中 使用的干扰抵销方法。
本发明的目的是设计一种基于智能天线的干扰抵销方法， 使码分多 址移动通信系统或其它移动通信系统在使用智能天线、 使用简单的最大 功率合成算法的同时， 能解决多径传播等产生的干扰问题， 并获得良好 的效果。
本发明更进一步的目的是提供一套新的数字信号处理方法， 可应用 于码分多址移动通信系统或其它移动通信系统中， 使该移动通信系统能 在使用智能天线的同时， 解决各种多径传播等干扰。
本发明的目的是这样实现的： 一种基于智能天线的干扰^ <销方法， 包括以下步骤： A.用经实时波束赋形算法获得的波束赋形矩阵对基于智能天线的 某一接收机输出的数字信号进行波束赋形， 获得一组波束赋形后的数 字信号， 表示为 NRk (m) , 其中 k代表码道， m代表取样点；
B.将波束赋形后的一组数字信号 NRk (m)中所包含的来自其它用户 的主径信号抵销， 获得另一组仅包含所需信号和所有干扰的数字信号， 表示为 NSk (m) , 其中 k代表码道， m代表取样点；
C.在数字信号 NSk (m)中搜索， 并求出赋形波束方向上分布的所有 多径信号；
D.在数字信号 NSk (m)中抵销来自其它用户的多径干扰信号；
E.将工作的终端用户的主径与多径信号同相叠加， 获得干扰抵销 后的数字信号。
所述步骤 A 中的基于智能天线的接收机输出的数字信号是取样级 的。
所述步骤 A是在基带信号处理器中完成的， 包括： 对基于智能天 线的接收机输出的数字信号进行同步和消除过取样； 进行解扰码和解 扩频， 分离为各个码道的信号； 在波束赋形器中用波束赋形合成算法 对每条链路的接收波束赋形， 并求得合成结果。
所述的波束赋形合成算法是最大功率合成算法。
所述步骤 A还包括对波束赋形器输出的智能天线的输出数字信号 进行解调和检测训练序列的信噪比， 在信噪比超过门限值时直接输出 接收数据并结束， 在信噪比低于门限值则进一步执行后续步骤。 所述的步骤 B进一步包括： 求出来自其它终端用户的、 在工作码 道的赋形波束内的信号的主径； 对其进行扩频、 加扰码， 还原为取样 级的数字信号； 从所述的数字信号 NRk (m)中减去能量超过门限值的其 它终端用户的主径信号， 获得所述的 NSk (m)。
所述的求出来自其它终端用户的、 在工作码道的赋形波束内的信 号的主径是求出其它码道在工作码道波束内的信号电平。
所述步骤 C进一步包括： 在一个符号内逐个移动取样点的位置， 获得多组码片级别的信号； 用已知扰码对其求相关， 获得多组能量超 过门限值的输出； 对这些输出加上已知扰码， 恢复多组取样级别的多 径干扰； 从步骤 B所获得的数字信号 NSk (m)中减去来自其它用户的多 径干扰， 将第 k码道的主径和多径信号同相叠加， 获得消除干扰后的 第 k码道的取样值； 对第 k码道的取样值作解扰码、 解扩频和解调， 获得消除干扰后的第 k码道的信号， k取任意正整数。
所述步骤 C 的搜索只在一个符号内进行， 所需进行的次数等于每 码片内的取样数乘上扩频系数再减 1。
所述的步骤 D进一步包括： 从步骤 B所获得的数字信号 NSk (m)中 减去来自其它终端用户干扰的数字信号， 而抵销来自其它终端用户的 多径干扰信号。
所述的步骤 D是在取样级别上进行的， 所涉及的信号是转换到取 样级别上的信号。
所述的步骤 E进一步包括： 由抵销了来自其它用户的主径和多径 千扰信号的取样值， 获得各个码片的值； 通过解扰码及使用第 k 个扩 频码解扩频后， 将来自工作的终端用户的主径和多径信号同相叠加， 获得干扰抵销后的输出信号； 解调后获得干扰抵销后的所需接收数据。
所述的步骤 A、 B、 C, D、 E是对所有信噪比达不到门限值的码道 进行干扰抵销。
所述的步骤 A、 B、 C、 D、 E 用于移动通信基站中的干扰抵销； 所 述的步骤^ C、 D、 E用于用户终端的干扰 4氐销。
本发明的方法， 对在帧结构中设计有较长训练序列（导频 Pi lot或 Midamble)的 CDMA移动通信系统来说， 由于在实际的移动通信系统中， 并不是所有的工作码道都受到多径传播等干扰的严重影响， 故可以在 智能天线的输出端对信号质量进行预检测， 即检测所接收到的训练序 列（导频 Pi lot或 Midamble)中的信噪比（误码）， 对没有误码或误码数 量低于给定值的码道就可以不再作处理， 就可大大减少需要进行后续 处理的码道的数量， 大大降低基带信号处理的复杂度。
本发明的方法， 对在帧结构中没有设计较长训练序列（导频 Pi lot 或 Midamble) 的 CDMA移动通信系统， 或在帧结构中设计有较长训练序 列（导频 Pi lot或 Midamble)的 CDMA移动通信系统， 但存在严重干扰、 误码严重的码道， 则要 本发明的方法对每一条码道消除多径干扰， 以达到正确接收的目的。
本发明的方法， 提出了一种简单的最大功率合成算法， 使智能天 线能在符号级别进行波束赋形， 达到实时运行的效果。 使用本发明提出的新的多径干扰抵销技术， 可以将大多数来自本 信道的多径干扰和其它信道的多径干扰予以抵销 (未抵销的多径干扰， 时延是符号宽度的整数倍， 但出现概率很低）， 以最大限度地消除多径 传播等干扰的影响， 达到正确接收的目的。 本发明方法的计算量有限， 采用目前商用的数字信号处理器（DSP)就完全可以实现。
本发明的方法虽然是针对码分多址 （CDMA ) 的移动通信系统作出 的， 但经过简单改变后， 也完全可适用于频分多址（FDMA )或时分多 址（TDMA ) 的移动通信系统。 附图简要说明
图 1是使用智能天线的 CDMA移动通信基站结构原理框图
图 2是对图 1 中智能天线的输出进行信噪比检测和处理过程的原 理框图
图 3是本发明的干扰抵销方法流程示意框图
图 4是移动通信用户终端结构原理框图 实施本发明的方式
下面通过实施例及附图对本发明的技术进行详细说明。
参见图 1 , 图中示出一个典型的具有智能天线的移动通信系统或 无线用户环路系统等无线通信系统中的基站结构。 主要包括 N 个相同 的天线单元 201A， 201B, 201N, N条几乎全同的射频馈电电缆 202A, 202B, ... , 202N, N 个射频收发信机 203A, 203B, …， 203N, 和相应 的基带信号处理器 204。 所有的射频收发信机 203A, 203B, ... , 203N 都使用同一个本振信号源 208 , 以保证基站的各个射频收发信机相干工 作。
所有射频收发信机 203A， 203B, ... , 203N 中均设有模拟至数字的 变换器（ADC)和数字至模拟的变换器（DAC) , 因此基带信号处理器 204 的输入、 输出信号均为数字信号， 射频收发信机 203A, 203B, 203N 与基带信号处理器 204间通过一条高速数字总线 209连接。
该使用智能天线的基站的基本工作原理及智能天线的工作方法， 已在在先的发明专利 "具有智能天线的时分双工同步码分多址无线通 信系统" （ZL 97 1 04039. 7)中说明， 本发明对智能天线接受信号的干 扰 ·ί氏销方法也是在该结构的基站中实现的。 本发明并不改变智能天线 本身的工作原理及其特性， 且本发明并不讨论发信信号的处理过程， 只描述对收信信号的干扰抵销方法。
结合参见图 1及图 3中的步骤 301至 304 , 说明在图 1所示的基站 结构条件下， 基带信号处理器 204 实现智能天线的工作方式。 假设此 码分多址无线通信系统共有 Κ个码道， 智能天线系统由 Ν个天线单元、 Ν条射频馈电电缆和 Ν个射频收发信机组成， 并以第 i条接收链路进行 说明。
步骤 301， 第 i个射频收发信机 203i将来自天线单元 201 i的接收 信号经模拟至数字变换 (ADC)和过取样后输出数字信号， 表示为 S i (m)， 其中 m为第 m个取样点； 步骤 302, 数字信号 Si(m)经方框？ 210的同 步及消除过取样后， 获得码片级别数字信号， 表示为 sli(n)， 其中 n 表示第 n个码片（chip); 步骤 303， 码片级别数字信号 (n)经方框？ 205的解扰码和解扩频后分离为 K个码道的符号级信号，表示为 xki(l)， 其中 1表示第 1个符号； 步骤 304， 此 K个码道的符号级信号 xki(l)分 别通过 K个波束赋形器 206用一定的波束赋形合成算法对第 i条链路 的接收波束赋形， 并求得合成结果， 表示为：
Figure imgf000011_0001
式中， k=l， 2, …， K; wik(l)为第 k码道在第 i 链路的波束赋形 系数， 当使用最大功率合成算法时，
wik(l) =xki*(l) (2)
式中， xki*(l)是 xki(l)的共轭复数， 从而获得了符号级别的波束 赋形矩阵 Wk， 其中 Rk(l)是智能天线系统的输出。
在时分双工（TDD)系统中， 就可以将上行（基站接收）波束赋形时每 条链路的权重直接用于下行 (基站发射）波束赋形， 充分获得智能天线 的优势。 对上述输出 Rk(l)进行解调等处理后， 就可获得接收信号。
结合参见图 2、 图 3， 示出智能天线码分多址无线基站中需要抵销 的干扰及与本发明有关的新的信号处理方法。
步骤 306， 由 K个解调单元 207A， 207B, ·.., 207K和 K个信噪比 (S/N)检测单元 221A， 221B, ... , 221 , 对上述由基带信号处理器 204 输出的智能天线系统的输出 Rk (1)信号进行解调和检测其训练序列的信 噪比 （任何移动通信系统中的训练序列都是已知的， 只需作一下比较 就可获得）， 若此输出信号的信噪比超过预先设定的门限（图 3中步骤 307及图 1 中菱形框）， 说明相应码道没有误码或者误码数量低于给定 值， 就可执行步骤 308, 直接输出此接收信号， 输出接收数据并结束处 理； 若此输出信号的信噪比低于门限值 (图 3 中步骤 307及图 2 中菱 形框）， 则执行步骤 305， 进行下一阶段的信号处理 （如果无线通信系 统没有训练序列， 在步骤 306、 307中则不必要进行信噪比检测）。
步骤 305, 获得波束赋形后的输入数字信号 NRk(m)。 此项工作在框 (？ ) 222A, 222B, ··., 222 中完成。 首先， 假设所处理的码道是第 k个用户终端所使用的码道， 利用所获得的对第 k个码道的波束赋形矩 阵 wik(l)直接对接收到的数据信号进行波束赋形， 形成一组新的数据 NRk (m)：
Figure imgf000012_0001
式中， k= l， 2, ...K; wik为在一帧内对第 k码道的波束赋形矩阵的平 均值， 即：
Wik = · .(4)
V'=l-i J 式中， L为需要统计的符号数， 显然 L应当小于或等于一帧的符号 数； wik(l)的定义见式（1); Si (m)是第 i条链路所接收到的多路 CDMA信 号， 如图 1中所示。 所获得的新的数据信号 NRk(m)被送到 K 个多径处理器 223A, 223B, 223K 中， 用本发明的新的处理方法进行处理， 处理过程主 要包括由步骤 310、 312构成的第一步， 由步骤 314构成的第二步、 由 步骤 316构成的第三步和由步骤 318构成的第四步， 如图 3中所示。
第一步： 将波束赋形后的输入数字信号 NRk(m) k 波束内的信号电 平中所包含的、 来自其它用户的主径分量抵销， 其处理过程是：
1).求出第 k波束内的所有其它主径信号， 求出其它码道在工作码 道 k波束内的信号电平， 即计算
F 1)=∑ !)*w,k(l) (5) 式中， v-l， 2, …， K， 其它码道在第 k码道波束内的总功率为
Figure imgf000013_0001
式中， Fv*(l)是 Fv(l)的共轭复数， L 为需要统计的符号数， 显然 L应当小于或等于一帧的符号数。 然后， 将？ 和系统给定的门限值进 行比较， 若发现有 U个值超过门限， 称之为 U个需要抵销的信号， 即 U 个不可能用智能天线的空间滤波器进行消除的信号。 对第 1 个符号， 此信号的输出可表示为 Fu(l)。
对 Fu(l)用第 u个扩频码进行扩频， 得到扩频后的信号 fu(n), 求出 每个需要抵销的信号在第 k链路的平均幅度：
Figure imgf000014_0001
式中， Ru(l)已通过式（1)求出， u=l， 2, …， U。
再将此信号的扩频并加上已知的扰码， 复原出它的输入数字信号:
s2u (n) =u*fu (n) *pn_code (n) (8)
2) .在 NRk (m)中抵销其它主径信号， 获得 NSk (m)。 从总的波束赋形 后的输入数字信号中减去干扰， 则可得到仅包括所需码道（第 k码道) 和所有多径干扰的波束赋形后的输入数字信号
Figure imgf000014_0002
上述操作是在取样的级别上进行的， 信号 s2u(n)应转换到取样级 别上， 形成 s2u(m), 此处， 可以认为每个取样值是均匀分布的。
第二步， 在 NSk(m)中搜索并求出所有多径分量。 搜索在此赋形波 束方向上分布的多径分量， 该搜索在上述所形成的数字信号 NSk(m)中 进行， 每次移动一个取样点 m， 获得一组新的 slkj(n), 用已知的扰码 pn.code (n)在符号级别上获得相关 ykj (η) , 并计算其总能量：
Figure imgf000014_0003
式中， M， =M- 1, 而 M为被统计的 L个符号中的所有码片数。 上 式中仅保留能量超过门限值的共 T 个干扰， 然后对 ykt(n)用已知的 pn_code (n)加扰码， 获得第 t个干扰在输入数据中的值 s 3kt (n)： s3kt (n) =ykt (n) *pn_code (n) (11) 显然， 此搜索只需在一个符号内进行， 所需进行的次数等于每码 片内的取样数乘上 SF-1, 式中 SF为扩频系数。
第三步， 抵销多径信号， 在 NSk(m)中抵销来自其它用户的多径信 号， 获得 SSk(m)。 从在第二步中获得的输入数据信号 NSk(m)中减去其 它超过门限值的干扰数据信号， 就可以抵销来自其它用户的多径干扰 信号：
SSk(m) = NSk(m)一 s3k,(m) (12)
'=1-Γ
本操作是在取样的级别上进行的， 信号 s3kt(n)应转换到取样级别 上， 形成 s3kt(m)， 此处可认为每个取样值是均匀分布的。
第四步， 获得干扰抵销后的输出 RSk(l)。 由抵销了来自其它用户 多径干扰信号的取样值 SSk(m), 获得各个码片级数字信号值 s4k(n)， 再对第 k码道的主径信号和多径信号作同相叠加， 然后通过解扰码和 使用第 k个扩频码解扩频， 就可获得干扰抵销后的输出信号 RSk (1)。
再经过步骤 320 解调， 最终获得干扰 销后所需的结果， 并由步 骤 308输出数据后结束。
显然， 以上过程要对所有具有误码的码道进行， 即一共要进行 K 次（？信噪比高于门 P艮值）， 以达到对所有码道进行干扰抵销的目的。
参见图 4， 示出使用本发明方法的 CDMA用户终端结构。 包括： 天 线 401、 无线收发信机 402、 模拟至数字变换器 403、 数字至模拟变换 器 404和基带信号处理器 405。 本发明的方法将在基带信号处理器 405 中实施。
在此结构中， 模拟至数字变换器 403 的输出可直接用于上述的输 入数字信号 NRk (m) , 然后， 使用上述的第一步至第四步的过程进行干 扰抵销。 在第一步抵销来自其它用户的主径信号过程中， 这些主径信 号 Fv (l)可以从直接解扰码、 解扩频来获得， 无需使用上述的 （5 )式， 直接从式（6 )开始。
本发明方法中的波束赋形是在基站完成的， 在本发明的方法用于 用户终端时， 用户终端接收到的信号本身就是所述的波束赋形后的数 字信号 NRk (m)， 根据用户终端所需要接收的码道数 k， 就可使用前述的 四步对 K个码道进行干扰抵销。
虽然本发明的技术方案主要针对码分多址的移动通信系统， 但经过 简单改变后， 完全可以用于频分多址和时分多址移动通信系统。 任何 从事无线通信系统研究开发的技术人员， 通过了解智能天线的基本原 理及数字信号处理的基本知识， 就可以按本发明提出的方法来设计高 质量的智能天线系统， 并将其用于各种移动通信或无线用户环路系统 中， 而获得高性能指标。
本发明的方法也是一套新的数字信号处理方法， 可以用于码分多 址移动通信系统或其它无线通信系统， 使系统在使用智能天线的同时， 还可解决各种多径传播等干扰， 并获得良好的结果。
虽然这里对本发明的实施例进行了说明， 但很明显， 在不脱离本 发明精神和范围的情况下可对其进行多种变化。

Claims

权利要求书
1. 一种基于智能天线的干扰抵销方法， 其特征在于包括以下步 骤：
A.用经实时波束赋形算法获得的波束赋形矩阵对基于智能天线的 某一接收机输出的数字信号进行波束赋形， 获得一组波束赋形后的数 字信号， 表示为 NRk (m)， 其中 k代表码道， m代表取样点；
B.将波束赋形后的一组数字信号 NRk (m)中所包含的来自其它用户 的主径信号抵销， 获得另一组仅包含所需信号和所有干扰的数字信号， 表示为 NSk (m)， 其中 k代表码道， m代表取样点；
C.在数字信号 NSk (m)中搜索， 并求出赋形波束方向上分布的所有 多径信号；
D.在数字信号 NSk (m)中抵销来自其它用户的多径干扰信号；
E.将工作的终端用户的主径与多径信号同相叠加， 获得干扰抵销 后的数字信号。
2.根据权利要求 1 所述的基于智能天线的干扰抵销方法， 其特征 在于： 所述步骤 A 中的基于智能天线的接收机输出的数字信号是取样 级的。
3.根据权利要求 1 所述的基于智能天线的干扰抵销方法， 其特征 在于： 所述步骤 A是在基带信号处理器中完成的， 包括： 对基于智能 天线的接收机输出的数字信号进行同步和消除过取样； 进行解扰码和 解扩频， 分离为各个码道的信号； 在波束赋形器中用波束赋形合成算 法对每条链路的接收波束赋形， 并求得合成结果。
4.根据权利要求 3 所述的基于智能天线的干扰抵销方法， 其特征 在于： 所述的波束赋形合成算法是最大功率合成算法。
5.根据权利要求 1 或 3所述的基于智能天线的干扰抵销方法， 其 特征在于： 所述步骤 A还包括对波束赋形器输出的智能天线的输出数 字信号进行解调和检测训练序列的信噪比， 在信噪比超过门限值时直 接输出接收数据并结束， 在信噪比低于门 P艮值则进一步执行后续步骤。
6.根据权利要求 1 所述的基于智能天线的干扰抵销方法， 其特征 在于所述的步骤 B进一步包括： 求出来自其它终端用户的、 在工作码 道的赋形波束内的信号的主径； 对其进行扩频、 加扰码， 还原为取样 级的数字信号； 从所述的数字信号 NRk (m)中减去能量超过门限值的其 它终端用户的主径信号， 获得所述的 NSk (m)。
7.根据权利要求 1 所述的基于智能天线的干扰 4氏销方法， 其特征 在于： 所述的求出来自其它终端用户的、 在工作码道的赋形波束内的 信号的主径是求出其它码道在工作码道波束内的信号电平。
8.根据权利要求 1 所述的基于智能天线的干扰抵销方法， 其特征 在于： 所述步骤 B是在取样的级别上进行的。
9.根据权利要求 1 所述的基于智能天线的干扰抵销方法， 其特征 在于所述步骤 C进一步包括： 在一个符号内逐个移动取样点的位置， 获得多组码片级别的信号； 用已知扰码对其求相关， 获得多组能量超 过门限值的输出； 对这些输出加上已知扰码， 恢复多组取样级别的多 径干扰； 从步骤 B所获得的数字信号 NSk (m)中减去来自其它用户的多 径干扰， 将第 k码道的主径和多径信号同相叠加， 获得消除干扰后的 第 k码道的取样值； 对第 k码道的取样值作解扰码、 解扩频和解调， 获得消除干扰后的第 k码道的信号， k取任意正整数。
10.根据权利要求 1所述的基于智能天线的干扰抵销方法， 其特征 在于： 所述步骤 C 的搜索只在一个符号内进行， 所需进行的次数等于 每码片内的取样数乘上扩频系数再减 1。
11.根据权利要求 1所述的基于智能天线的干扰抵销方法， 其特征 在于所述的步骤 D进一步包括： 从步骤 B所获得的数字信号 NSk (m)中 减去来自其它终端用户干扰的数字信号， 而抵销来自其它终端用户的 多径干扰信号。
12.根据权利要求 1所述的基于智能天线的干扰抵销方法， 其特征 在于： 所述的步骤 D是在取样级别上进行的， 所涉及的信号是转换到 取样级别上的信号。
13.根据权利要求 1所述的基于智能天线的干扰抵销方法， 其特征 在于所述的步驟 E 进一步包括： 从抵销了来自其它终端用户的主径和 多径干扰信号的取样值， 获得各个码片的值； 通过解扰码及使用第 k个 扩频码解扩频后， 将来自工作用户的主径和多径信号同相叠加， 获得 干扰抵销后的输出信号； 解调后获得干扰抵销后的所需结果。
14.根据权利要求 1所述的基于智能天线的干扰抵销方法， 其特征 在于： 所述的步骤 A、 B、 C , D、 E 是对所有信噪比达不到门限值的码 道进行干扰抵销。
15.根据权利要求 1所述的基于智能天线的干扰抵销方法， 其特征 在于： 所述的步骤 A、 B、 C、 D、 E用于无线基站中的干扰 销。
16.根据权利要求 1所述的基于智能天线的干扰抵销方法， 其特征 在于： 所述的步骤 B、 C、 D、 E用于用户终端的干扰 4氐销。
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