WO1988001805A1 - Circuit interrupteur - Google Patents

Circuit interrupteur Download PDF

Info

Publication number
WO1988001805A1
WO1988001805A1 PCT/JP1987/000612 JP8700612W WO8801805A1 WO 1988001805 A1 WO1988001805 A1 WO 1988001805A1 JP 8700612 W JP8700612 W JP 8700612W WO 8801805 A1 WO8801805 A1 WO 8801805A1
Authority
WO
WIPO (PCT)
Prior art keywords
transistor
voltage
circuit
switching
switching circuit
Prior art date
Application number
PCT/JP1987/000612
Other languages
English (en)
Japanese (ja)
Inventor
Toshiyasu Suzuki
Original Assignee
Toshiyasu Suzuki
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Toshiyasu Suzuki filed Critical Toshiyasu Suzuki
Publication of WO1988001805A1 publication Critical patent/WO1988001805A1/fr

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/38—Means for preventing simultaneous conduction of switches
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/505—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means
    • H02M7/515—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only
    • H02M7/5152—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only with separate extinguishing means

Definitions

  • Nomenclature of the invention Switching circuit technology-This invention makes it easy to turn off or forcefully keep it off so that it does not turn on due to malfunction.
  • the present invention relates to a switching circuit having a self-holding function and a self-extinguishing function.
  • the present invention provides a G T ⁇ (gate-turn-off thyristor).
  • a power conversion circuit using a resonance circuit (: a series inverter> or a device that applies this power conversion circuit, if it is clean, an ignition device including an internal combustion engine ignition device, a high voltage generator, It is used in ozonizers, discharge lamp lighting devices, induction ripening devices, etc.
  • Background technology there is a GTO as a switching means having a self-holding function and a self-extinguishing function. The enlarged one is the switching method shown in Fig. 2. (Reference: Japanese Patent Publication No. 55-37178)
  • an overcurrent flows through the GTO, such as in a power short-circuit state or an overload state, it is difficult to turn off the GTO.
  • this switching means also has a disadvantage that it is difficult to turn on / off the transistor 1 or 2 when an overcurrent flows, such as in a power supply short-circuit state or an overload state.
  • one measure of the maximum value that the base current of the transistors 1 and 2 can reach is the value of both base currents when the product of the emitter DC current gains of the transistors 1 and 2 becomes 1.
  • Both switches are controlled so that when one is on, the other does not turn on.
  • the purpose is to prevent them from shorting the DC power supply 41 due to malfunction.
  • the base current of the transistor 51 passes from the DC power supply 41 through the switching means, the diode 48 and the resistor 50 during the ON period of the switching means which is located at the top of the figure.
  • the base current of the transistor 43 passes through the resistor 46, the diode 48, the switching means, and the DC power supply 41.
  • each current must be smaller than the respective holding current so that the current flowing through each diode 48 does not prevent the switching means from turning off.
  • Diode 48 and rectifier 49 prevent these currents and the main current of this arm pair from interfering with each other.
  • Diode 48 and rectifier 49 should preferably be of the fast-recovery type.
  • the two diodes 42 protect the emitter junctions of the transistors 43-45, 51, 52 from reverse surge voltages.
  • the transistors 51 and 52 turn off the lower switching means, and when the lower switching means is on.
  • the transistors 43 to 45 keep the switch off of the switch of However, for that purpose, the transistors 43 to 45 or 51, 52 must not lose as much as the base current of the transistors 1, 2 can reach. Turn 2 must be able to turn off.
  • transistors 1 and 2 can be forcibly kept off, which means that two sets of transistors 1, 2, 39 and 40 are likely to turn on simultaneously due to a malfunction caused by noise or the like. This means that even if an overcurrent flows through the bases of transistors 1 and 2, transistor 1 or 2 can be turned off.
  • One way to solve this is to use transistors with low current rating in transistors 1 and 2 in order to reduce the amount of base current that can reach transistors 1 and 2 in the switching means shown in FIG.
  • the use of a smaller transistor increases the number of transistors connected in Darlington and amplifies it.
  • increasing this has the disadvantage of increasing its on-state voltage.
  • the present invention relates to a circuit for detecting a voltage of a base-emitter of a bipolar transistor Q1 that is larger than a predetermined value.
  • the switching means that operates in accordance with the voltage detection means is a bipolar / switching circuit that connects the collector and base of the transistor Q1.
  • the bipolar transistor Q1 may be a Darlington-connected multiple bipolar transistor.
  • the switching means when the if switching means is on, it connects the collector to the base, so that part or all of the main current of the switching circuit flows to the base.
  • this main current is larger than the set value of the holding current of the switching circuit (this corresponds to the holding current of the thyristor, hereinafter, it will be referred to as), the voltage between the base and the emitter is maintained. The voltage is almost constant. Otherwise, this voltage will be less than that constant voltage, approaching zero cU.
  • the voltage detecting means detects that the base-emitter voltage is larger than the voltage set value corresponding to the set value of the holding current, the voltage detecting means keeps the switching means on. If not, the voltage detection means! ⁇ Keep the switching means off.
  • the entire operation of the present invention is positive feedback. If this positive feedback operation is prevented, the present invention can be easily turned off. Therefore, the present invention has a self-holding function and a self-extinguishing function.
  • the base and the emitter of the bipolar transistor Q1 convert the current into a voltage, and the voltage is detected by the voltage detecting means, so that the magnitude of the main current and the set value of the holding current are determined.
  • the main current of the present invention is larger than the setting current of the holding current, the base-emitter voltage is almost constant regardless of the magnitude.
  • the voltage detecting means operates according to the constant voltage, the operation is the same regardless of the magnitude of the main current. Therefore, even if the main current is large, the present invention is not particularly liable to be turned on and off, so that the turn-off is as easy as when the main current is small. This has the effect of the present invention.
  • the switching means since the switching means may be turned on and off in accordance with the voltage detection means, it may not be a bipolar transistor. Therefore, the present invention has an advantage that the switching means other than the bipolar transistor can be used as the switching means, which is more convenient than the prior art.
  • the present invention is the switching circuit according to claim 3
  • the constant voltage means described in the same claim the voltage detection means described in the same claim is the base-emitter of the bipolar transistor Q1 described in the same claim. Help detect the voltage between. Therefore, the present invention has an advantage that this voltage detecting means can be simply constituted by a transistor or the like. In the case where the present invention is applied to the switching circuit of claim 9, this advantage is obtained.
  • FIG. 1 are circuit diagrams of each embodiment of the present invention.
  • 2 to 5 are circuit diagrams of conventional switching means.
  • FIG. 16 is a circuit diagram of an arm pair using a conventional switching means.
  • FIG. 17 is a circuit diagram of an arm pair using an embodiment of the present invention.
  • FIG. 18 is a circuit diagram showing an embodiment of the present invention and a circuit of an ignition device using the same.
  • FIG. 19 is a circuit diagram showing two embodiments of the present invention and a circuit of an ignition device using the two embodiments. '
  • FIG. 20 is a circuit diagram showing a circuit of a bridge-type series inverter using the embodiment of the present invention.
  • FIGS. 21 (a) and 21 (b) are circuit diagrams showing a circuit of a prism type series inverter using an embodiment of the present invention.
  • FIG. 22 and FIG. 23 are circuit diagrams each showing a circuit of an ignition device using the embodiment of the present invention.
  • FIG. 24 and FIG. 25 are circuit diagrams of the circuit of the ignition device with the electronic distribution function using the kiyoshi according to the present invention.
  • BEST MODE FOR CARRYING OUT THE INVENTION will be described in more detail with reference to the accompanying drawings.
  • the transistor 7 corresponds to the above-mentioned bipolar transistor Q1
  • the comparator 3 corresponds to the above-described voltage detecting means
  • the transistor 6 corresponds to the above-mentioned switching means.
  • the magnitude V st of the reference voltage is set between the voltage terminal and the base-emitter voltage of the transistor 7 when the transistor 7 is turned on with reference to the emitter potential of the transistor 7.
  • the base-emitter voltage of the transistor 7 becomes substantially constant.
  • this voltage also approaches zero, so that it is possible to know from the magnitude of this voltage whether the main current is larger than a predetermined value.
  • the transistor 6 operating according to the comparator 3 via the transistor 5 connects the collector and base of the transistor 7; otherwise, the comparator 3 is connected via the transistor 5 Turn off transistors 6 and 7.
  • the role of the resistor 8 is important. Its role is to stabilize the voltage between the base and the emitter of the transistor 7 and detect the voltage of the comparator 3 In addition to helping to increase the turn-off speed of the transistor 7, it is useful in setting the magnitude of the holding current in this embodiment.
  • the resistor 8 has the effect that not only the setting becomes accurate, but also the range of setting values that can be selected is expanded.
  • the ON voltage in this embodiment is the sum of the voltage between the emitter and the collector of the transistor 6 and the voltage between the base and the emitter of the transistor 7, and this is referred to as the switching means in FIG.
  • the transistor 11 is the same as the switching transistor Q1 of the first embodiment
  • the transistor 10 is the same as the switching means of the first embodiment
  • the transistor 9 is the same as the switching means of the first embodiment.
  • a column circuit of rectifiers 12 and resistors 16 helps transistors 9 etc. detect the base-emitter voltage of transistor 11.
  • the present inventor added the voltage of the parallel circuit to the base-emitter voltage of the transistor 11 so that the transistor 9 and the like can detect the base-emitter voltage. There is no problem in voltage detection. This is because there is a one-to-one correspondence between the voltage across the base of the transistor 11 and the voltage between the base of the transistor 11 and the cathode of the rectifier 12.
  • the holding current value of this embodiment is the value of the resistances 13 to 16 and the base emitter of the transistor 9 when the transistor 9 is turned on.
  • the ON voltage of this embodiment is determined by the emitter of the transistor 10. -The collector-to-collector voltage and the transistor-to-base emitter voltage
  • the ON voltage of the switching means in FIG. 4 is the sum of both the voltage between the base and the emitter of the transistors 2 and 39 and the voltage between the emitter and the collector of the transistor i.
  • the sum of the voltages of the resistors 15 and 16 stabilizes before and after the double voltage, so that the base current of the transistor 9 becomes a small current having an upper limit, and the transistor 9 is turned on. ⁇ It is easy to turn off. Therefore, this embodiment can be easily turned off. Of course, even if the transistor 10 is used, the turn-off can be performed.
  • the resistor 16 may be omitted, but if it is provided, the set value of the holding current can be made accurate.
  • the parallel circuit of the resistor 17 and the rectifier 18 is connected to the base side of the transistor 11, and the role is the role of the resistor 16 and the rectifier 12 in FIG. Is the same as Thus, the current rating of rectifier 18 may be lower than that of rectifier l 12.
  • This implementation corresponds to the switching circuit of the eighth aspect of the present invention.
  • the resistor 17 may be omitted, but if it is present, the set value of the holding current can be made accurate.
  • Transistors 10 and 11 are connected in Darlington via fir parallel circuit Since the transistor ⁇ ⁇ ⁇ is turned on, it connects the collector and the base of the transistor 11 through this column circuit.
  • FIG. 8 The operation and effect of this embodiment are almost the same as those of FIG.
  • the embodiment of FIG. 8 is similar to the embodiment of FIG.
  • the latter transistor 9 has a common emitter, while the former has a common base. For this reason, the former saved one resistor compared to the latter.
  • the collector current of the transistor 9 is also almost constant, and the magnitude is determined by the constant voltage and the value of the resistor 19. . That is, in this embodiment, a constant current path in which a constant current flows through the collector of the transistor 9 is formed.
  • transistors 9 and 10 are similar to that of transistors 1 and 2 in FIG. 3, but the operation of both is different.
  • the ON voltage of this embodiment can be the same as that of the embodiment of FIG. 6, and the same as that of the switching means of FIG. Further, if the base of the transistor 9 and the mixer are short-circuited, this embodiment can be easily turned off.
  • the parallel circuit of the resistor 17 and the rectifier 18 is connected to the base ⁇ 3 ⁇ 4 of the transistor 11, but its role is the same as that of the resistor 16 and the rectifier 12 in FIG. Same as role.
  • the transistors 10 and 11 are Darlington connected through this column circuit, when turned on, the transistor 10 connects the base and the collector of the transistor 11 through this parallel circuit.
  • the transistors 22 and 23 connected in a Darlington connection are the bipolar transistor Q1 described in claim 1, and the transistor 21 is the switching transistor described in claim 1. It can be considered that the transistor 20 and the like correspond to the voltage detecting means described in the above item.
  • the transistor 23 expands the main current of the transistor 22 and the transistor 20 etc. is the base of the transistor 22. It can also be considered that the base-emitter voltage of the transistor 23 helps to detect the inter-electrode voltage.
  • the voltage between the base of the transistor 22 and the emitter of the transistor 23 is at a substantially constant predetermined value. This voltage is Keep the transistors 20 and 21 on and the transistors 22 and 23 turn on as their main currents increase.
  • the holding current of this embodiment is determined by the voltage between the base and the emitter of the transistor 20 when the transistor 20 is turned on and the value of the resistors 24 to 27.
  • the ON voltage of this embodiment is the sum of the base-emitter voltage of both the transistors 22 and 23 and the emitter-collector voltage of the transistor 21.
  • the ON voltage of the switching means in FIG. 4 is the sum of the base-emitter voltage of both transistors 2 and 39 and the emitter-collector ⁇ voltage of transistor 1.
  • this embodiment has the advantage that the on-voltage of this embodiment can be made the same as the on-voltage of the switching means in FIG.
  • the sum of the voltages of the resistors 26 and 27 stabilizes around 2 volts, so that the base current of the transistor 20 becomes a small current having an upper limit and the transistor 20 It is easy to turn off.
  • the base current of the transistor 21 is also smaller, it is easy to turn it off.
  • FIG. 11 is similar to the embodiment of FIG.
  • the latter transistor 20 has a common emitter, while the former has a common base. For this reason, the person saved one resistor compared to the latter.
  • the collector current of the transistor 20 is also almost constant, and the magnitude is determined by the constant voltage and the value of the resistor 28. Decided.
  • FIGS. 10 and 11 Comparing the switching means shown in FIGS. 10 and 11 with the switching means shown in FIG. 5, these embodiments have one or two more resistors in terms of the number of parts, but the ON voltage is higher. These embodiments have the effect that the pressure can be reduced by about 1 volt, and the forced turn-off and the maintenance of the forced off are easy. The present inventors will specifically describe this in the description of FIG. 17 described later. Fig. 12 and Fig. 13 are also possible. These are more advantageous in terms of on-voltage and off than the switching means of FIG. 5 in which the number of Darlington-connected transistors is increased by one stone. Note that each implementation of FIGS. 10 ⁇ to 13 is defined in claim 9 or 10. This corresponds to the switching circuit of the term tT ⁇ . In the embodiment shown in FIG. 14, the transistor 32 is the same as the bipolar transistor Q1 described in claim 1, the transistor 31 is the switching means described in the above item 1, the transistor 29 is the same as the transistor. These correspond to the voltage detection means described above.
  • Transistor 29 controls transistor 31 via transistor 30. Rectifiers 33 help detect the voltage of transistor 29 etc.
  • the transistor 38 is the same as the bipolar transistor Q1 of the first embodiment
  • the field-effect transistor 37 is the switching means of the first embodiment
  • the comparator 3 is the same as the switching device of the first embodiment. These correspond to the voltage detection means described in section-.
  • the transistors 34 to 36 drive the transistor 37 according to the comparator 3.
  • the reference voltage V st is based on the emitter potential of the transistor 38.
  • the circuit of FIG. 1.7 is an arm pair using two embodiments of FIG. 1.1. Each trigger signal is input from input terminal t3, input terminals t4 and t5.
  • Both switching circuits are controlled so that when one of them is on, the other does not turn on, so that they are prevented from shorting the DC power supply 41.
  • -Its basic operation is the same as that of the circuit of Fig. 16 described above.
  • transistor 54 keeps the lower switching circuit of FIG. 17 off, while when the lower switching circuit is on, Transistor 53 keeps its upper switching circuit off.
  • the circuit of FIG. 18 is a circuit of a series inverter type ignition device using another embodiment and a thyristor 60.
  • 55 is a three-terminal regulator
  • 56 is a DC-DC converter that outputs a negative voltage
  • 67 is a firing coil
  • 68 is a discharge gap for ignition.
  • This implementation is a switching composed of transistors 61 to 65, etc. Circuit.
  • the transistor 63 corresponds to the switching means described in claim 1
  • the transistor 64 corresponds to the voltage detecting means described in claim 1.
  • the transistors 61 and 62 correspond to the bipolar transistor Q1 described in the above item [2].
  • the transistor 62 corresponds to the transistor, the transistor 61 increases the main current of the transistor 62, and the transistors 64 and the like detect the voltage between the base and the emitter of the transistor 62. You may think that the base emitter voltage of 1 helps.
  • transistor 64 keeps transistor 63 on via transistor 65.
  • the on-voltage of this switching circuit is the sum of the base-emitter voltage of both transistors 616 and the emitter-collector voltage of transistor 63. Therefore, this embodiment has an effect that this voltage can be reduced to about the ON voltage of the switching means shown in FIG.
  • the main circuit is based on a DC power supply formed by a DC-DC converter 56 and a power supply capacitor 57, a switching circuit of the present invention, and a thyristor. W 8/1
  • Rectifiers 69, 70 limit the voltage on commutation capacitor 71 from zero voltage to the voltage on power supply capacitor 57. These actions are as follows. During the life of the thyristor 60, the thyristor 60 and the rectifiers 70 and 49 serve as a flywheel diode for the primary coil 67a. On the other hand, during the ON period of the switching circuit of the present invention, the switching circuit and the rectifiers 49 and 69 play the role.
  • this series inverter ignition system is different from the conventional one.
  • this igniter when one of the switching circuits and the thyristor 60 is turned off and the other is turned off so that the timing when the thyristor 60 turns on and off is automatically optimized, this turning off turns off the other. One turns on automatically.
  • one turn-off triggers the other turn'on.
  • the transistors 58 and the like detect the on / off of the switches of the present invention
  • the transistors 66 and the like detect the on / off of the thyristor 60.
  • the circuit configuration of this is basically the same as that of the circuit of Fig. 16 and Fig. 17.
  • each current is set smaller than each holding current value so that the current flowing through 8 does not prevent the switching circuit and the thyristor 60 from turning on and off.
  • the trigger of the thyristor 60 will be described.
  • the usage of the pulse-transformer 74 is different from the usual one, in which the saturation of the magnetic flux is positively used.
  • This minute time does not affect the time of the thyristor 60, which is determined by the current of the primary coil 67a, and the trigger power of the thyristor 60.
  • the present inventor has set the value of the resistor 75 and the characteristics of the pulse transformer 74 so that the above is sufficient.
  • the exciting inductance of the pulse transformer 74 is smaller than usual.
  • the magnetic energy of the pulse-transformer 74 is dissipated by the resistor 73 and the antenna diode 72, and the next trigger of the thyristor 60 is prepared.
  • the base potential of transistor 63 is set to 0.6 volts. The turn-on of the transistor 63 is prevented, and the capacitor 77 is also charged at the same time, and the trigger of the switching circuit is prepared.
  • transistor 66 When transistor 66 turns on together with thyristor 60, capacitor 77 discharges through resistor 79, the emitter, transistor, base, etc. of transistor 63, so that this switching circuit turns. Turn on.
  • the overall operation of the ignition device is as follows. When the ignition signal input to the input terminal t 6 rises, if the switching circuit and the transistor 58 of the present invention are off, the transistor 59 turns on and the pulse transistor 74 turns off. Trigger thyristor 60.
  • the transistor 66 is also turned off at the same time, so that the capacitor 77 triggers the switching circuit of the present invention.
  • transistors 58 When the star 59 is turned off, the magnetic energy of the pulse 'transformer 74 is released and the next trigger of the thyristor 60 is prepared.
  • transistor 59 turns on if the ignition signal is high-level. The same is repeated hereinafter. This repetition continues as long as the ignition signal is at a high level.
  • the transistor 59 remains off and the ignition device stops generating a spark.
  • the ignition device of the series inverter type generates a spark when charging and discharging the commutation capacitor 71.
  • the well-known CDI (capacitor discharge ignition) igniter generates a spark only when the capacitor is discharged.
  • the former ignition method will be referred to as a capacitor charge / discharge ignition method, or simply C CDT (Cond se nse r Char gea n d Diis ccha rge [gni t ⁇ on)), and the double CD [method].
  • C CDT Cond se nse r Char gea n d Diis ccha rge [gni t ⁇ on)
  • the circuit in FIG. 19 is also a circuit of a CCDI ignition system.
  • the control method is the turn-off-trigger method described above.
  • This circuit is a circuit using another embodiment of the present invention instead of the thyristor 60 in FIG. 18.
  • the implementation is performed by transistors 81 to 85 and the like. Composed
  • Transistors 81 and the like detect the voltage between the base of transistor 84 and the emitter of transistor 85.
  • Transistor 81 controls transistor 83 via transistor 82.
  • the transistor 58 keeps not only the transistor 59 but also the transistors 83 to 85 off. Therefore, the two kinds of switching circuits of the present invention are completely prevented from short-circuiting the DC-DC converter 56 and the power supply capacitor 57.
  • a switching circuit composed of transistors 61 to 65 and the like can be replaced with that shown in FIG. 10 or FIG.
  • the ignition device shown in FIGS. 18 and 19 becomes a high voltage generator that generates an alas and a negative high voltage if the ignition discharge gear 68 is *, and the ignition discharge gap 68 If you read in the discharge lamp instead of, the discharge lamp lighting device will be g.
  • these can be read as ozone generating discharge gears instead of ignition discharge gaps 68 to become intelligent zonizers, and instead of primary coils 67 a, inductive maturation coils can be connected.
  • Induction Become a mature device
  • the circuit shown in FIG. 20 is a bridge-type series inverter having a function of preventing a short circuit of the DC power supply 41 and using four switching circuits shown in FIG. Each switching circuit is formed by transistors 20 to 23 and the like.
  • This main circuit is composed of a DC power supply 41, these four switching circuits, four rectifiers 47, a commutation reactor 86, a commutation capacitor 87, and a load resistance 88.
  • the control method is the turn-off-trigger method described above.
  • the inverter When the inverter starts, when the start-stop signal input to the input terminal t8 falls, the transistor 100 is turned on. Then, the charging current of the capacitor 101 flows to the base and the emitter of the transistor 102, so that the transistor 1 and 2 trigger the switching circuit at the upper right of the figure. .
  • transistor 98 keeps the lower right switching circuit off, while transistor 93 keeps the lower left switching circuit on. Therefore, at this time, the transistor 95 keeps the switching circuit in the upper left of the drawing off, and the transistor 92 charges the capacitor 91.
  • transistor 93 keeps its lower left switching circuit on, so that the transistor /
  • the star 92 can detect both ON and OFF from the ON / OFF detection of the lower left switching circuit.
  • transistor 94 When its upper left switching circuit is on, transistor 94 keeps its lower left switching circuit off, while transistor 97 keeps its lower right switching circuit on.
  • the transistor 96 keeps the upper right switching circuit off, and the transistor 99 keeps the transistor 100 off to discharge the capacitor 101.
  • the transistor 97 keeps the lower right switching circuit on, so that the transistor 99 can turn on the lower right switching circuit. From the detection, both on and off can be detected.
  • the transistor 990 turns off together with its upper left and lower right switching circuits, if the start / stop signal is low, the transistor 100 turns on, and so on. Repeated . This repetition continues as long as the start / stop signal is at the ⁇ - ⁇ level. However, at the time of turn-off, if the start / stop signal is high-level, the transistor 100 remains active and the operation of the inverter stops.
  • the circuits shown in Fig. 21 (a) and (b>) are the -circuits of a bridge-type series inverter using four 11I switching circuits that have the function of preventing short-circuiting of the DC power supply 41. The same reference numerals are attached to the surrounding terminals ctl to ct 8, respectively.
  • These switching circuits are switching circuits 107 to 110, and the circuit configuration for preventing short-circuiting of the DC power supply 41 utilizes that of the arm pair shown in FIG.
  • the control method for this event is the turn-off trigger method described above.
  • the transistors 92, 104, etc., switch on and off the switching circuits 1, 8, 109, and the transistors 99, 105, etc. detect the on / off of the switching circuits 107, 110. Then, when the start / stop signal input to the input terminal t9 falls, or while this signal is at a low level, the switching circuit is activated and neither 07 nor 110 is turned on. L10, etc. trigger the switching circuits 108, 109 when the switch is turned on.
  • the 221st circuit is the circuit of the CCDI type ignition device described above, and its control method is the turn-off-trigger method described above. In addition, it plays the role of a flywheel diode against the primary coil 67a. The means to do this is in this circuit.
  • the rectifier 70 and the switching circuit 113 act on the primary coil 67a like a flywheel diode. Therefore, as long as the switching circuit 112 is on, the transistors 114 and the like continue to trigger the switching circuit 113.
  • the switching circuit 111 when the switching circuit 111 is on, the switching circuit 111 and the rectifiers 49, 69 act on the primary coil 67a like a flywheel-diode.
  • transistor 66 turns off switching circuit 111. To keep. Then, when the Sui Tsu quenching circuit 1 1 1 is on, the transistor 9 4 kept off the sweep rate Tsuchingu circuits 1 1 2, transistor 5 8 keep off the sweep rate Tsuchingu circuit 1 1 3 v
  • the transistors 66 and the like are turned on and off by detecting the on / off of the switching circuit 113. 1 1 3 Both ON and OFF can be detected.
  • the entire trigger operation is the same as that of the circuit of FIG.
  • the circuit of FIG. 23 is also the circuit of the above-described CCDI-type ignition device, and its control method is the turn-off-trigger method described in m.
  • the switching circuit 1 11 when the switching circuit 1 11 is on, the switching circuit 1 15 (the part surrounded by the dotted line) and the rectifier 69 are connected to the primary coil 67a. Acts like a flywheel or diode. Therefore, as long as the switching circuit 111 is on, the transistor 116 keeps triggering the switching circuit 115.
  • the transistors 58 and 94 can detect on / off of both the switching circuits 111 and 115 from the on / off detection of the switching circuit 115.
  • the circuit is the same as the circuit of FIG. Circuit of Figure 24, the two pairs of ignition coil 67 with ignition ⁇ electrostatic Giyappu 6 8 and, with the electron distribution function, the ⁇ the main circuit is a round Mainai ignition instrumentation g of the aforementioned CCD I type 18 The main circuit shown is used.
  • Switching switch 122 sets the spark at either ignition discharge gap 68. W 88/01805
  • the switching circuit 118 charges the commutation capacitor 71 via the primary coil 67a, and the switching circuit 119 charges the commutation capacitor 121 via the primary coil 67a. Then, the switching circuit 120 discharges the commutation capacitor 71 or 121 via one of the primary coils 67a.
  • transistor 99 keeps switching circuits 118, 11 off through transistors 128, 95, 96. At the same time, transistor 99 keeps transistor 100 off and discharges capacitor 101.
  • the circuit shown in FIG. 25 is also a circuit of the above-mentioned CCD I-type ignition device having two sets of ignition coil 67, ignition discharge gear 68, and electronic power distribution function. This main circuit uses the main circuit of FIG. Spark occurs in either ignition discharge gear 68 due to switching switch 122
  • the main circuit is as follows. >> The switching circuit 1 1 2 is the primary The charging capacitor 71 is charged through the coil 67a, and the switching circuit 130 charges the commutation capacitor 121 through the primary coil 67a. Then, the switching circuit 111 discharges the commutation capacitor 71 or 121 via one of the primary coils 67a.
  • the switching circuit 112 or 130 when the switching circuit 112 or 130 is on, the switching circuit 113 and the rectifier 70 or 131 act on each primary coil 67a like a flywheel diode. I do. To that end, the transistor 114 continues to trigger the switching circuit 113 as long as the switching circuit 112 or 130 is on.
  • Japanese Patent No. 62-5019 Japanese Patent No. 62-5019
  • the switching circuit according to the present invention was turned off or forcibly kept off so as not to turn on or off due to malfunction.
  • This is useful as a switching means having a self-holding function and a self-extinguishing function. Therefore, the present invention is useful not only as a substitute for GTO but also as a switching means that can be used in a power conversion circuit or the like in a new way.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Electronic Switches (AREA)

Abstract

Circuit interrupteur pouvant être mis aisément hors tension et maintenu obligatoirement dans cet état, présentant une fonction d'autorégulation et une fonction d'extinction d'arc automatique. Par exemple, lorsque le détecteur de tension (comparateur 3) détecte qu'une tension entre la base et l'émetteur d'un transistor bipolaire (7) dépasse une valeur prédéterminée, une organe commutateur (transistor 6) mis en fonction (via un transistor 5) par rapport au détecteur de tension relie le collecteur à la base dudit transistor bipolaire (7).
PCT/JP1987/000612 1986-08-25 1987-08-17 Circuit interrupteur WO1988001805A1 (fr)

Applications Claiming Priority (6)

Application Number Priority Date Filing Date Title
JP61/197349 1986-08-25
JP19734986 1986-08-25
JP62/005027 1987-01-14
JP502787 1987-01-14
JP18766587 1987-07-29
JP62/187665 1987-07-29

Publications (1)

Publication Number Publication Date
WO1988001805A1 true WO1988001805A1 (fr) 1988-03-10

Family

ID=27276562

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/JP1987/000612 WO1988001805A1 (fr) 1986-08-25 1987-08-17 Circuit interrupteur

Country Status (1)

Country Link
WO (1) WO1988001805A1 (fr)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO1997014216A1 (fr) * 1995-10-06 1997-04-17 Philips Electronics N.V. Tampon-commutateur entierement bipolaire a trois modes a grande vitesse et a vitesse de balayage elevee, et procede correspondant

Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS5161253A (ja) * 1974-11-25 1976-05-27 Nippon Electric Co Denshisuitsuchikairo
JPS57118438A (en) * 1980-11-21 1982-07-23 Thomson Csf Switch controllable in on or off with pulse

Patent Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS5161253A (ja) * 1974-11-25 1976-05-27 Nippon Electric Co Denshisuitsuchikairo
JPS57118438A (en) * 1980-11-21 1982-07-23 Thomson Csf Switch controllable in on or off with pulse

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO1997014216A1 (fr) * 1995-10-06 1997-04-17 Philips Electronics N.V. Tampon-commutateur entierement bipolaire a trois modes a grande vitesse et a vitesse de balayage elevee, et procede correspondant

Similar Documents

Publication Publication Date Title
US4104714A (en) Converter arrangements
US5200878A (en) Drive circuit for current sense igbt
US4464585A (en) Gate circuit of gate turn-off thyristor
JPS6121015B2 (fr)
WO1988001805A1 (fr) Circuit interrupteur
JP3187757B2 (ja) スイッチング手段の駆動回路
US3453492A (en) Capacitor discharge ignition system
SU520631A1 (ru) Устройство дл форсировки активноиндуктивной нагрузки
JP3521510B2 (ja) Ｄｃーｄｃコンバータ回路
JP2002044934A (ja) 半導体電力変換装置
SU484627A1 (ru) Релаксационный генератор двухступенчатых импульсов
JP2794064B2 (ja) 自己保持機能と自己ターン・オフ機能を持つスイッチング回路と自己発振型直列インバータ回路
JPS6321146Y2 (fr)
SU1203657A1 (ru) Транзисторный ключ
JP3667927B2 (ja) 同時オン防止手段
RU2029882C1 (ru) Система зажигания двигателя внутреннего сгорания
SU1742955A1 (ru) Преобразователь напр жени
SU746854A1 (ru) Тиристорный прерыватель посто нного тока
SU1480112A1 (ru) Транзисторный ключ
SU1723647A1 (ru) Преобразователь посто нного напр жени
SU1610560A1 (ru) Однотактный преобразователь посто нного напр жени
SU1192067A1 (ru) Однотактный преобразователь посто нного напр жени
JPS6033736Y2 (ja) ゲ−トタ−ンオフサイリスタのオフゲ−ト回路
SU1504751A2 (ru) Устройство дл управлени мощным высоковольтным транзисторным ключом
SU1252885A1 (ru) Преобразователь напр жени

Legal Events

Date Code Title Description
AK Designated states

Kind code of ref document: A1

Designated state(s): JP US

AL Designated countries for regional patents

Kind code of ref document: A1

Designated state(s): AT BE CH DE FR GB IT LU NL SE