US9030261B2 - Two mode power converter for audio amplifiers - Google Patents

Two mode power converter for audio amplifiers Download PDF

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Publication number
US9030261B2
US9030261B2 US14/115,371 US201214115371A US9030261B2 US 9030261 B2 US9030261 B2 US 9030261B2 US 201214115371 A US201214115371 A US 201214115371A US 9030261 B2 US9030261 B2 US 9030261B2
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Prior art keywords
supply rail
positive
output
drive mode
negative
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US14/115,371
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US20140077885A1 (en
Inventor
Mads Peter Frium
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ICEPower AS
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ICEPower AS
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/20—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers
    • H03F3/21—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers with semiconductor devices only
    • H03F3/217—Class D power amplifiers; Switching amplifiers
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/20—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers
    • H03F3/21—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers with semiconductor devices only
    • H03F3/217—Class D power amplifiers; Switching amplifiers
    • H03F3/2173—Class D power amplifiers; Switching amplifiers of the bridge type
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • H02M2001/0058—
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/01—Resonant DC/DC converters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
    • Y02B70/1491—

Definitions

  • This invention relates to a power converter for a single-ended class-D amplifier.
  • the power converter may also be used for a full bridge class D amplifier.
  • the two predominant topologies, known in prior art, and used for class-D amplifiers are the full-bridge- and the half-bridge topology.
  • the half-bridge topology has a distinct advantage over the full-bridge since only half the number of power switches, drivers and output inductors is needed. Even though the voltage rating of the power switches is doubled in the half-bridge topology, there is still a manufacturing and cost benefit due to the reduction of number of components. Since the speaker output terminals are referenced to ground, overload protection and output sensing becomes easier compared to the full-bridge topology.
  • the drawback of the half-bridge class-D topology is the need for a dual rail supply and the fact that this topology will pump current back to the opposite supply rail from where the power is being drained.
  • the consumer product market requires very efficient audio amplifiers with a high output power which at the same time consumes as little power as possible.
  • the positive and negative rail outputs can advantageously be used to drive a single ended class D amplifier.
  • the switching arrangement and the controller enable two different drive modes, so that the output voltages on the positive and negative rails can be generated at two different output voltage levels without changing the duty cycle or dead time of the control signals.
  • the selection of the one or another two different output levels can be made according to the amplifier voltage demanded by the front-end digital sound processor.
  • the power supply according to the present invention offers a great efficiency improvement for the total audio power solution during idle and at low output power.
  • the two drive modes may further be used to provide maximum voltage regulation without changing the switching frequency or dead-time.
  • the system is preferable arranged to run in resonant mode with zero voltage/zero current switching, by providing resonant tank capacitors, and by suitably selecting the switching frequency and dead time.
  • the pump reduction preferably occurs continuously cycle by cycle.
  • the power supply includes additional switches to provide an additional output. This output can be used to supply a full bridge class-D amplifier.
  • the converter does not include the positive and negative supply rail outputs, but only has a single supply rail output. In this case, the converter is thus intended to drive only a full bridge amplifier.
  • FIG. 1 is a block diagram of an embodiment of the present invention.
  • FIG. 2 is a block diagram of a converter in FIG. 1 connected to a single ended class D amplifier.
  • FIG. 3 is a block diagram of a converter in FIG. 1 connected to a full bridge class D amplifier.
  • FIG. 4 is a diagram illustrating the first and second control signals, Q and Q-neg.
  • FIG. 5 is a diagram illustrating voltage regulation.
  • FIG. 6 is a diagram illustrating resonant switching.
  • FIG. 7 is a diagram illustrating current pump cancelling.
  • FIG. 1 A block diagram of a power converter according to an embodiment of the present invention is shown in FIG. 1 .
  • the converter has a power supply input 6 , connected to a power source 10 (see FIGS. 2 and 3 ).
  • the output of the power source 10 is a DC-voltage (or almost) which means that in case of an AC-source input, means to rectify and stabilize the voltage is included in the source 10 , as well as means for safety insulation between the mains and the output.
  • the power source 10 is a DC battery (e.g. automotive, portable equipment), such as a 12 V battery.
  • the converter further has a positive supply rail output 7 and a negative supply rail output 8 , intended to driving a single ended class D amplifier 11 (see FIG. 2 ).
  • the converter also has a single supply rail output 9 , intended for driving a full bridge class D amplifier 12 (see FIG. 3 ).
  • the class D amplifier may be used to drive a load 13 such as an electro dynamic loudspeaker but can be any kind of transducer transforming the electrical signal from the amplifier to an acoustic signal.
  • the converter here comprises a transformer arrangement 2 having two primary windings W 1 and W 2 and two secondary windings W 3 and W 4 .
  • the windings W 1 and W 2 have a first number of turns n 1
  • the windings W 3 and W 4 have a second number of turns n 2 .
  • the transformer arrangement 2 can be implemented by a single magnetic structure.
  • the transformer arrangement is a planar transformer where the windings are formed on a printed circuit board (PCB). This makes the leakage inductance predefined within very narrow tolerances, which is important for the resonant tank behaviour which will be discussed below.
  • the converter in FIG. 1 has nine switches S 5 -S 13 , for example realized by MOSFET transistors.
  • the simple drive pattern of the MOSFETs also enables a simple way to implement soft-switching techniques of the switches.
  • the switches are controlled by a controller 3 .
  • the controller applies two control signals in the form of complementary square wave pulse trains, Q and Q-neg (see FIG. 4 ).
  • the control signals have a fixed pulse time (pt) and dead time (dt).
  • the supply pump reduction arrangement 4 works as a Supply Rail Mirror (SRM) which basically mirrors the voltage of the numerical smallest value to the other rail at any given time.
  • SRM Supply Rail Mirror
  • the SRM circuit will mirror the supply rails by redistributing the pumping charge in such a manner that supply rails will become essential equal numerically.
  • the positive supply rail output 7 , the negative supply rail output 8 and the single rail output 9 are connected to ground via capacitors C 14 , C 15 and C 16 , respectively.
  • C 14 , C 15 and C 16 By choosing the value of C 14 , C 15 and C 16 so that these capacitors together with the leakage inductance of the transformer form a resonant tank, Zero Voltage/Zero current switching (ZVS/ZCS) can be obtained for all switches.
  • the power converter 1 can be driven in two different drive modes, referred to as negate drive mode and boost drive mode.
  • the converter has a drive mode switch S 5 connected between the first common point and the positive supply rail 7 , and a boost drive mode switching arrangement comprising a first boost switch S 12 connected between a positive terminal of the second primary winding W 2 and ground, and a second boost switch S 13 connected between a negative terminal of the first primary winding W 1 and ground.
  • the switches S 5 , S 12 and S 13 are selectively controlled by the controller to provide two different output voltage levels on the positive and negative supply rail outputs 7 , 8 .
  • the difference is decided by the relationship between n 1 and n 2 , as will be discussed in further detail below.
  • Drive mode switch S 5 is set ON (closed) thereby connecting the power source 10 directly to the positive supply rail 7 .
  • Switches S 6 , S 8 and S 11 are driven by the Q pulse train, while S 7 , S 9 and S 10 are driven by the Q-neg pulse train.
  • the supply voltage is now transformed by the transformer arrangement 2 to the negative supply rail output 8 having the same magnitude but reversed polarity.
  • This mode is referred to as the negation state where the positive supply rail is negated to form a negative supply rail to obtain a +/ ⁇ voltage supply for a single ended class D amplifier.
  • the single supply rail output 9 is also provided with a voltage by the transformer arrangement 2 .
  • the negate action is bi-directional which means that any supply pumping from a class D amplifier connected to the dual rail output 7 , 8 will be redistributed to the opposite rail maintaining total rail balance regardless of load imbalance.
  • the circuit will cancel the supply pumping by mirroring the two supply rails on to each other.
  • the transistors S 6 and S 8 will be turned ON.
  • the positive supply rail across the capacitor C 14 will then be put across the transformer winding w 3 .
  • the negative supply rail voltage on the capacitor C 15 will be put across the transformer winding w 4 . Since the two windings are coupled to each other in a 1:1 ratio, any difference in the magnitude of the positive and negative rail voltage will cause a load current to migrate from the rail with the largest magnitude to the other rail.
  • the same operation is performed but now with transistor S 7 and S 9 turned ON. This action secures the balancing of the transformer 1 .
  • FIG. 7 showing the output voltages of the supply rails in an experimental realization of the system in FIG. 1 .
  • curve 25 is the positive supply rail voltage
  • curve 27 is the negative supply rail output
  • curve 26 is the output voltage swing across the amplifier load 13 . From FIG. 7 it is clear to see that when the output voltage swing 26 is at its positive peak the positive supply rail 25 sacks due to the peak power consumption. Looking at the negative supply rail voltage 27 at the same point in time this also sacks. This is because energy is being transformed from the negative supply rail 8 to the positive supply rail 7 by coupling between the transformer 2 windings W 4 and W 3 .
  • boost mode S 5 is set OFF (open) and the controller 3 applies the pulse trains Q and Q-neg also to S 12 and S 13 , respectively.
  • V positive supply rail V source ⁇ n 2/ n 1
  • V negativ supply rail ⁇ V source ⁇ n 2/ n 1
  • S 6 and S 7 acts as synchronous rectifiers for the positive supply rail and S 8 and S 9 acts as synchronous rectifiers for the negative supply rail.
  • boost mode it is possible to limit the maximum output voltage of the power converter without changing duty cycle or dead time. During such maximum output regulation zero voltage, zero current switching and pump cancellation on the positive and negative supply rails are maintained.
  • the boost switches S 12 and S 13 are enabled, and are driven by the pulse trains Q and Qneg, respectively.
  • the supply rail voltage increases with the charging of the output capacitors C 20 and C 22 .
  • the boost switches S 12 and S 13 are disabled, and during the following period T 2 the output voltage will decrease with the discharging of the output capacitors.
  • the switches are again enabled and the voltage will rise to the predefined level and then turn off again.
  • FIG. 6 depicts current and voltage signals obtained at the drain of switches S 12 and S 13 in an experimental realization of the system in FIG. 1 .
  • curve 21 is the current of the drain of the switch S 12
  • curve 22 is the voltage of the drain of the switch S 12
  • curve 23 is the current of the drain of the switch S 13
  • curve 24 is the voltage of the drain of the switch S 13 .
  • the curves 21 and 23 illustrate the resonant sinusoidal current waveform obtained by the switches. It is noted that all curves are free of any high frequency ringing which makes the topology very beneficial from an EMI point of view, important in many implementations.
  • the system as disclosed may be applied in any consumer product including means to provide audio to a user; such as, but not limited to, audio/video systems, multimedia players, audio/video appliances in automobiles, in boats and alike.
  • the switches may be of other kind than MOSFETs.
  • the transformer arrangement does not need to be a planar transformer on a PCB, but may be of a conventional transformer design.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Amplifiers (AREA)
  • Dc-Dc Converters (AREA)
US14/115,371 2011-06-15 2012-06-14 Two mode power converter for audio amplifiers Active 2032-08-25 US9030261B2 (en)

Applications Claiming Priority (4)

Application Number Priority Date Filing Date Title
EP11170024 2011-06-15
EP11170024.1A EP2536014B1 (de) 2011-06-15 2011-06-15 Umwandler mit zwei Modi für Audioverstärker
EP11170024.1 2011-06-15
PCT/EP2012/061334 WO2012172007A1 (en) 2011-06-15 2012-06-14 A two mode power converter for audio amplifiers

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US20140077885A1 US20140077885A1 (en) 2014-03-20
US9030261B2 true US9030261B2 (en) 2015-05-12

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US (1) US9030261B2 (de)
EP (1) EP2536014B1 (de)
CN (1) CN103597724B (de)
WO (1) WO2012172007A1 (de)

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US9509254B1 (en) * 2015-06-03 2016-11-29 Rockwell Collins, Inc. Bi-directional soft-switching class-D power amplifier
US10601373B2 (en) 2016-03-31 2020-03-24 Tymphany Hk Limited Booster circuit including dynamically sliding power supply unit
US12088203B2 (en) * 2022-05-03 2024-09-10 Infineon Technologies Austria Ag Partial power converters and split partial power conversion

Citations (9)

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US5903138A (en) * 1995-03-30 1999-05-11 Micro Linear Corporation Two-stage switching regulator having low power modes responsive to load power consumption
US5982639A (en) * 1997-11-04 1999-11-09 Power Integrations, Inc. Two switch off-line switching converter
US20040145930A1 (en) 2002-12-27 2004-07-29 Yamaha Corporation Power supply circuit
US20050017803A1 (en) * 2001-11-23 2005-01-27 Rudi Jonkman Switched mode power amplifier
WO2007096761A1 (en) 2006-02-24 2007-08-30 Bang & Olufsen Icepower A/S Audio power conversion system
US20090309658A1 (en) 2008-06-16 2009-12-17 Rgb Systems, Inc. Method and apparatus for power converter for class d audio power amplifiers
US7944296B1 (en) * 2010-03-12 2011-05-17 Samsung Electro-Mechanics Company Low power mode amplification with a transformer output matching and a virtual ground
US20110305049A1 (en) * 2010-06-10 2011-12-15 Carefusion 303, Inc. Phase-controlled uninterruptible power supply
US8760228B2 (en) * 2011-06-24 2014-06-24 Rf Micro Devices, Inc. Differential power management and power amplifier architecture

Patent Citations (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5903138A (en) * 1995-03-30 1999-05-11 Micro Linear Corporation Two-stage switching regulator having low power modes responsive to load power consumption
US5982639A (en) * 1997-11-04 1999-11-09 Power Integrations, Inc. Two switch off-line switching converter
US20050017803A1 (en) * 2001-11-23 2005-01-27 Rudi Jonkman Switched mode power amplifier
US20040145930A1 (en) 2002-12-27 2004-07-29 Yamaha Corporation Power supply circuit
WO2007096761A1 (en) 2006-02-24 2007-08-30 Bang & Olufsen Icepower A/S Audio power conversion system
US20090309658A1 (en) 2008-06-16 2009-12-17 Rgb Systems, Inc. Method and apparatus for power converter for class d audio power amplifiers
US7944296B1 (en) * 2010-03-12 2011-05-17 Samsung Electro-Mechanics Company Low power mode amplification with a transformer output matching and a virtual ground
US20110305049A1 (en) * 2010-06-10 2011-12-15 Carefusion 303, Inc. Phase-controlled uninterruptible power supply
US8760228B2 (en) * 2011-06-24 2014-06-24 Rf Micro Devices, Inc. Differential power management and power amplifier architecture

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
International Search Report from PCT/EP2012/061334 (now WO 2012/172007); dated Oct. 5, 2012; The instant application is a national phase of PCT/EP2012/061334; 3 pages.

Also Published As

Publication number Publication date
CN103597724A (zh) 2014-02-19
CN103597724B (zh) 2016-10-26
US20140077885A1 (en) 2014-03-20
EP2536014A1 (de) 2012-12-19
WO2012172007A1 (en) 2012-12-20
EP2536014B1 (de) 2016-12-28

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