US8937463B2 - Common-core power factor correction resonant converter - Google Patents

Common-core power factor correction resonant converter Download PDF

Info

Publication number
US8937463B2
US8937463B2 US13/714,754 US201213714754A US8937463B2 US 8937463 B2 US8937463 B2 US 8937463B2 US 201213714754 A US201213714754 A US 201213714754A US 8937463 B2 US8937463 B2 US 8937463B2
Authority
US
United States
Prior art keywords
terminal
energy
charge
storage capacitor
coupled
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Active, expires
Application number
US13/714,754
Other languages
English (en)
Other versions
US20140002035A1 (en
Inventor
Lon-Kou Chang
Yi-Wen Huang
Han-Hsiang Huang
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Macroblock Inc
Original Assignee
Macroblock Inc
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Macroblock Inc filed Critical Macroblock Inc
Assigned to MACROBLOCK, INC. reassignment MACROBLOCK, INC. ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: Chang, Lon-Kou, HUANG, HAN-HSIANG, HUANG, YI-WEN
Publication of US20140002035A1 publication Critical patent/US20140002035A1/en
Application granted granted Critical
Publication of US8937463B2 publication Critical patent/US8937463B2/en
Active legal-status Critical Current
Adjusted expiration legal-status Critical

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/06—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider
    • H02M3/07—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider using capacitors charged and discharged alternately by semiconductor devices with control electrode, e.g. charge pumps
    • G—PHYSICS
    • G05—CONTROLLING; REGULATING
    • G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
    • G05F1/00—Automatic systems in which deviations of an electric quantity from one or more predetermined values are detected at the output of the system and fed back to a device within the system to restore the detected quantity to its predetermined value or values, i.e. retroactive systems
    • G05F1/70—Regulating power factor; Regulating reactive current or power
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/125—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means
    • H02M3/135—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only
    • H02M3/137—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
    • Y02B70/1433—
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02P—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN THE PRODUCTION OR PROCESSING OF GOODS
    • Y02P80/00—Climate change mitigation technologies for sector-wide applications
    • Y02P80/10—Efficient use of energy, e.g. using compressed air or pressurized fluid as energy carrier

Definitions

  • the disclosure relates to a power factor correction convertor, and more particularly to a common-core power factor correction resonant converter.
  • the circuit structure of a power factor correction converter usually uses the inductors as energy storage devices.
  • the inductor further combines with the boost topology control architecture to achieve power factor correction effect such that the energy may be transferred to the loads.
  • the output voltage of this type of converter must be higher than the voltage of the line power source.
  • the circuit is not suitable for low-voltage output. Therefore, it is necessary to change the circuit to the step-down circuit type, such as the Forward Converter. However, this circuit can not provide high power factor function.
  • the boost converter requires complex control circuits, such as analog multiplier and other circuit elements to generate a high power factor and regulate the output, in order to achieve high power factor correction.
  • the aforementioned structure further requires circuits having functions of frequency jitter, a quasi resonant, or a valley switching in order to reduce the Electromagnetic Interference (EMI).
  • EMI Electromagnetic Interference
  • the output voltage is raised to a higher voltage level, such as 600V. Therefore, a relatively high Drain-Source withstand voltage element (for example, more than 600V power components) must be considered when choosing the switching elements in the framework.
  • the existing technology provides a power factor correction resonant converter, as shown FIG. 1 , in order to solve previous problems.
  • the Power Factor Correction resonant converter 100 uses the component 110 for soft switching, so that the input line voltage charges the capacitance CP to produce a charge-storage capacitor voltage VCP. Then the energy transferring operation is conducted by the soft switching operation through element 120 , such that the charge-storage capacitor voltage VCP is converted to an output power.
  • the charge-storage capacitor voltage VCP of the power factor correction resonant converter 100 is charged to the same voltage level as the input line voltage at most. Therefore, a relatively low withstand voltage element can be used.
  • the power factor correction resonant converter adopts two separate inductors (elements 110 and 120 , respectively), and is implemented by using five diodes, such that the cost and the volume of the circuit elements increase, and the component conduction loss also increase. Therefore, the power factor correction circuit still needs improvement.
  • the disclosure provides a common-core power factor correction resonant converter in order to reduce the cost and the volume of the circuit elements. Besides, a relatively low withstand voltage switch and capacitance elements can be chosen. And this circuit architecture can reduce the electromagnetic interference and possess a good power factor.
  • the disclosure provides a common-core power factor correction resonant converter comprising an energy-transforming circuit.
  • the energy circuit includes a first terminal, a second terminal, and a third terminal.
  • the first terminal of the energy-transforming circuit receives an input line voltage
  • the second terminal of the energy-transforming circuit is coupled to a ground
  • the third terminal of the energy-transforming circuit generates an output power.
  • the energy-transforming circuit includes a coupling inductor, a charge-storage capacitor, a switch, a first diode, and a second diode.
  • the energy-transforming circuit in response to a control signal, charges the input line voltage to the coupling inductor and the charge-storage capacitor by a switching operation of the energy-transforming circuit, so as to generate a charge-storage capacitor voltage. And then in accordance with the control signal, the energy-transforming circuit enables the coupling inductor and the charge-storage capacitor to discharge and to transfer energy to the output load through the switching operation of the coupling inductor, the charge-storage capacitor, the switch, the first diode, and the second diode of the energy-transforming circuit. Furthermore, a switching operation control can be utilized to provide the output voltage or current regulation.
  • the disclosure discloses a common-core power factor correction resonant converter. It activates different resonant circuit by the switching operation, in order to acquire input line power and conduct energy-transforming operation to output power. As a result, the disclosure reduces the voltage conversion loss, the cost and volume of the circuit elements. In addition, a relatively low withstand voltage element can be chosen. Furthermore, it maintains a better electromagnetic interference reducing effect and obtains a better power factor.
  • FIG. 1 is a schematic diagram of a power factor correction convertor according to the disclosure
  • FIG. 2 is a circuitry diagram of a common-core power factor correction resonant converter of the present disclosure
  • FIG. 3 is an embodiment of the detailed circuit diagram of the common-core power factor correction resonant converter in FIG. 2 ;
  • FIG. 4 is the waveform of the common-core power factor correction resonant converter in the present disclosure
  • FIG. 2 is a circuitry diagram of a common-core power factor correction resonant converter of the present disclosure.
  • FIG. 3 is an embodiment of the detailed circuit diagram of the common-core power factor correction resonant converter in FIG. 2 .
  • the common-core power factor correction resonant converter 200 may be referred as a coupling-inductor power factor correction resonant converter.
  • the common-core power factor correction resonant converter 200 includes an energy-transforming circuit 210 .
  • the energy-transforming circuit 210 includes a first terminal 211 , a second terminal 212 , and a third terminal 213 .
  • the first terminal 211 of the energy-transforming circuit 210 receives an input line voltage VIN
  • the second terminal 212 of the energy-transforming circuit 210 is coupled to a ground GND
  • the third terminal 213 of the energy-transforming circuit 210 generates an output power VO.
  • the energy-transforming circuit 210 includes a coupling inductor, a charge-storage capacitor, a switch, a first diode, and a second diode.
  • the coupling inductor, the charge-storage capacitor, the switch, the first diode, and the second diode of the energy-transforming circuit 210 are shown in the embodiments of FIG. 3 .
  • the volume of the charge-storage capacitor can be very small.
  • the energy-transforming circuit 210 operates a switching operation, the power-obtaining operation from the input line power, by the coupling inductor, the charge-storage capacitor, the switch, the first diode, and the second diode of the energy-transforming circuit 210 , such that the coupling inductor and the charge-storage capacitor constitute a resonant circuit. Accordingly, the input line voltage VIN is charged to the magnetizing inductance of the coupling inductor, and the charge-storage capacitor to store energy, so as to generate the charge-storage capacitor voltage VCP.
  • the energy-transforming circuit 210 enables the coupling inductor and the charge-storage capacitor to discharge and to transfer energy through the switching operation of the coupling inductor, the charge-storage capacitor, the switch, the first diode, and the second diode of the energy-transforming circuit 210 , such that the stored energy in the magnetizing inductance of the coupling inductor and the charge-storage capacitor voltage VCP is converted to the output power VO.
  • the operation mode for converting the input line power into the output power VO not only includes transferring the stored energy in the magnetizing inductance of coupling inductor element, but also discharging the charge-storage capacitor voltage VCP on the charge-storage capacitor element.
  • the voltage VCP is lowered down toward to 0V and clamped by the second diode while the charge-storage capacitor voltage VCP is converted into the output power VO through the energy conversion.
  • the input line voltage VIN can be alternating voltage (AC Voltage) or direct voltage (DC Voltage). The alternating voltage is more suitable for power factor correction.
  • This embodiment of the common-core power factor correction resonant converter 200 can be operated by the switching operation as previously mentioned. First of all, the embodiment acquires power and energy through the coupling inductor and the charge-storage capacitor of the energy-transforming circuit 210 , and then converts the acquired power to the output power VO by the energy conversion to provide a well output voltage or output current regulation and obtain a better power factor as well.
  • a common-core power factor correction resonant converter 300 includes an energy-transforming circuit 310 , a control unit 340 , a voltage-transforming unit 350 , and a load unit 360 .
  • the operation of the energy-transforming circuit 310 may refer to the implementation of the energy-transforming circuit 210 in FIG. 2 . Therefore, the explanations are not given again.
  • the energy-transforming circuit 310 includes a first terminal 311 , a second terminal 312 , and a third terminal 313 .
  • the energy-transforming circuit 310 includes a coupling inductor 320 (corresponding to the coupling inductor of the energy-transforming circuit 210 in FIG. 2 ), a charge-storage capacitor 330 (corresponding to the charge-storage capacitor of the energy-transforming circuit 210 in FIG. 2 ), the switch SW 1 (corresponding to the switch of the energy-transforming circuit 210 in FIG. 2 ), the diode D 1 (corresponding to the first diode of the energy-transforming circuit 210 in FIG. 2 ) and diode D 2 , (corresponding to the second diode of the energy-transforming circuit 210 in FIG. 2 ).
  • the coupling inductor 320 is a common-core transformer.
  • the coupling inductor 320 includes a primary side and a secondary side.
  • the first terminal of the primary side of the coupling inductor 320 is coupled to a first terminal of the coupling inductor 320 for receiving the input line voltage VIN, wherein the second terminal of the primary side and the first terminal of the secondary side of the coupling inductor 320 have the same polarity.
  • the primary side and the secondary side of the coupling inductor 320 have opposite polarity.
  • the coupling inductor 320 further includes a first coil L 1 and a second coil L 2 .
  • the first terminal of the first coil L 1 is the first terminal of the primary side of the coupling inductor 320 and the second terminal of the first coil L 1 is the second terminal of the primary side of the coupling inductor 320 .
  • the first terminal of the second coil L 2 is the first terminal of the secondary side of the coupling inductor 320 and the second terminal of the second coil L 2 is the second terminal of the secondary side of the coupling inductor 320 .
  • the first terminal of the switch SW 1 is coupled to the second terminal of the primary side of the coupling inductor 320 .
  • the second terminal of the switch SW 1 is coupled to the second terminal of the secondary side of the coupling inductor 320 and the first terminal of the charge-storage capacitor 330 .
  • the control terminal of the switch SW 1 receives the control signals CS 1 and is controlled by the control signal CS 1 to turn on or turn off.
  • the switch SW 1 can be implemented by a N-type transistor.
  • the drain of the N-type transistor is coupled to the second terminal of the primary side of the coupling inductor 320
  • the source of the N-type transistor is coupled to the second terminal of the secondary side of the coupling inductor 320
  • the gate of the N-type transistor receives control signals CS 1 for example.
  • the switch of the implementation is not limited to N-type transistor; it can also use P-type transistor or Insulated Gate Bipolar Transistor (IGBT) to for implementation.
  • the charge-storage capacitor 330 includes a capacitance CP.
  • the capacitance CP is implemented as the charge-storage capacitor 330 .
  • the anode of diode D 1 is coupled to the first terminal of the secondary side of the coupling inductor 320 , the cathode of the diode D 1 is coupled to the third terminal 313 of the energy-transforming circuit 310 to generate the output power VO.
  • the first terminal of the charge-storage capacitor 330 is coupled to the second terminal of the switch SW 1 , the first terminal of the charge-storage capacitor 330 generates the charge-storage capacitor voltage VCP, and the second terminal of the charge-storage capacitor component 330 is coupled to the ground GND.
  • the anode of the diode D 2 is coupled to the second terminal of the charge-storage capacitor component 330
  • the cathode of the diode D 2 is coupled to the first terminal of the charge-storage capacitor component 330 .
  • the control unit 340 is applied to receive the input line voltage VIN, the charge-storage capacitor voltage VCP, or the output power VO, so as to generate a control signal CS 1 according to the voltage level of the input line voltage VIN, the charge-storage capacitor voltage VCP, or the output power VO.
  • a control method may be taken for example.
  • the control unit 340 detects the voltage level of the charge-storage capacitor voltage VCP is 0V
  • the control signal CS 1 with a high logic level is provided to the switch SW 1 , such that the switch SW 1 turns on.
  • the control unit 340 detects the voltage level of the charge-storage capacitor voltage VCP equals to one half of the input line voltage VIN (ie (1/2)*VIN)
  • the control signal CS 1 with the low logic level is provided to the switch SW 1 , such that the switch SW 1 turns off.
  • the voltage-transforming unit 350 is coupled to the first terminal 311 of the energy-transforming circuit 310 for receiving the alternating voltage VAC and converting the alternating voltage VAC into the input line voltage VIN. Furthermore, the voltage-transforming unit 350 included, for example, a bridge rectifier and a filter, in order to rectify and filter the alternating voltage VAC through the bridge rectifier and the filter, so that the alternating voltage VAC is converted into the input line voltage VIN and then is outputted.
  • the first terminal of the load unit 360 is coupled to the third terminal 313 of the energy-transforming circuit 310 , and the second terminal of the load unit 360 is coupled to the ground terminal GND.
  • the load unit 360 includes a capacitor C 1 and a resistor R 1 .
  • the first terminal of the capacitor C 1 is coupled to the third terminal 313 of the energy-transforming circuit 310 , and the second terminal of the capacitor C 1 is coupled to the ground GND.
  • the first terminal of the resistor R 1 is coupled to the first terminal of the capacitor C 1 , and the second terminal of the resistor R 1 is coupled to the second terminal of the capacitor C 1 .
  • the coupling structure of the internal components of the common-core power factor correction resonant converter 300 is briefly illustrated.
  • the operation of the common-core power factor correction resonant converter 300 will be illustrated in the followings.
  • the alternating voltage VAC is transformed and rectified by the voltage-transforming unit 350 in order to generate the input line voltage VIN.
  • the control unit 340 detects a charge-storage capacitor voltage VCP is 0V, and then the control unit 340 generates a high logic level control signal CS 1 to conduct the switch SW 1 . Due to turn-on of the switch SW 1 , the first coil L 1 of the coupling inductor 320 and the capacitance CP of the charge-storage capacitor component 330 in energy-transforming circuit 310 constitute a resonant circuit, in order to charge the input line voltage VIN to the magnetizing inductance of the first coil L 1 and the capacitance CP of the charge-storage capacitor component 330 .
  • the voltage of the charge-storage capacitor voltage VCP continues to rise.
  • the switch SW 1 turns on, the input line voltage VIN charges the capacitance CP of the charge-storage capacitor component 330 through the magnetizing inductance of the primary side of the coupling inductor 320 .
  • control unit 340 When the control unit 340 detects the voltage level of the charge-storage capacitor reaching to a certain voltage, for example, one half of the input line voltage (ie (1/2)*the VIN), the control unit 340 generates a low logic level control signal CS 1 in order to disconnect the switch SW 1 .
  • the capacitance CP of the charge-storage capacitor component 330 and the second coil L 1 of the coupling inductor 320 constitute a resonant circuit, in order to discharge the magnetizing inductance of the second coil L 2 and the capacitance CP of the charge-storage capacitor component 330 , so that the magnetic energy in the magnetizing inductance of the second coil L 2 and the charge of the capacitance CP of the charge-storage capacitor component 330 conduct an energy transferring and convert into electrical energy for output power VO.
  • the energy is converted into the output power VO and the energy of the output power VO is transferred to the load 360 .
  • the switch SW 1 turns off, the polarity of the coupling inductor 320 reverses, making the current on the primary side of the coupling inductor 320 cut off.
  • the current on the secondary side of the coupling inductor 320 is generated, such that the magnetic energy in the magnetizing inductance of the second coil L 2 begins to release and the voltage on the capacitance CP of the charge-storage capacitor component 330 discharges and is transferred into the output power VO through the secondary side of the coupling inductor 320 .
  • the next switching cycle of the control switch SW 1 is waiting to turn on (in this case the voltage level of the charge-storage capacitor voltage VCP is 0V), and then the previous action mentioned above is repeated.
  • the switching operation of the aforementioned resonant circuit acquiring voltage and energy transfer respectively, it can provide the well output voltage or current regulation and obtain a better power factor as well.
  • the above charge-storage capacitor voltage VCP can be equal to one half of the input line voltage VIN 1/2 (ie (1/2)*VIN). However, the present disclosure is not limited to the example.
  • the voltage level of the charge-storage capacitor voltage VCP can be designed in any appropriate voltage level (i.e. the default voltage level).
  • I L ⁇ ⁇ 1 ⁇ ( t ) VIN ⁇ ( t ) - VCP ⁇ ( t ) L ⁇ ⁇ 1 ⁇ t ( 1 )
  • t ON is the conduction time of the switch SW 1 , which is the time for the voltage of the capacitance CP of the charge-storage capacitor component 330 charging from 0V to one half of the input line voltage VIN. It should be a fixed value and related to the resonant cycle of the resonant circuit.
  • VIN( t ) ⁇ square root over (2) ⁇ VAC ⁇ sin( ⁇ t ) (5)
  • Equation (6) is shown in the following:
  • F SW1 is the switching frequency of the switch SW 1
  • T SW1 is the switching cycle of the switch SW 1
  • F SW1 is the reciprocal of T SW1 , for example
  • curve S 1 is the input line voltage VIN
  • curve S 2 is the charge-storage capacitor voltage VCP
  • curve S 3 is the inductor current I L1 (t) passing through the first coil L 1 of the primary side of the coupling inductor 320 when the switch SW 1 turns on
  • the curve S 4 is the average input line current I in,avg (t) passing through the capacitance CP of the charge-storage capacitor 330 when the switch SW 1 turns.
  • the sinusoidal waveform of the average input line current I in,avg (t) (curve S 4 ) and the input line voltage VIN (curve S 1 ) are the same. Therefore, the common-core power factor correction resonant converter can obtain a good power factor.
  • the inductor current I L1 (t) of each cycle on the first coil L 1 is approximated to a parabola waveform instead of the traditional saw tooth waveform. It is expected to obtain a good reduction of the electromagnetic interference effect.
  • the on-off of the control switch SW 1 is controlled by a varying-frequency control mode, that is to say detecting the voltage level of the input line voltage VIN and the charge-storage capacitor voltage VCP in order to control the conducting of the switch SW 1 .
  • a varying-frequency control mode that is to say detecting the voltage level of the input line voltage VIN and the charge-storage capacitor voltage VCP in order to control the conducting of the switch SW 1 .
  • the pulse width modulation (PWM) fixed-frequency control method can also be used to control the conduction of the switch SW 1 , so as to control the conduction time t ON of the switch SW 1 .
  • An input line power P in (t) of the common-core power factor correction resonant converter 300 can be calculated by equation (7).
  • the approximated equation (7) is shown in the followings:
  • An output power P out (t) of the common-core power factor correction resonant converter 300 can be calculated by equation (8).
  • the approximated equation (8) is shown in the followings:
  • ⁇ is the efficiency between the input line power P in (t) and the output power P out (t).
  • the voltage level of the charge-storage capacitor voltage VCP of the charge-storage capacitor 330 on the capacitance CP is charged to one half of the input line voltage VIN (ie (1/2)*VIN) at most. Therefore, a relatively low withstand voltage capacitance CP can be implemented.
  • the input line voltage VIN applied in the disclosure is alternating voltage.
  • the present disclosure is not limited to the embodiment so that the input line voltage VIN can also use direct voltage.
  • the disclosure provides a common-core power factor correction resonant converter. It activates different resonant circuit by switching operations, in order to obtain power and conduct energy-transforming operation to output power. As a result, it can generate a well output voltage, current regulation and obtain a better power factor as well.
  • the voltage of the charge-storage capacitor is charged to one half of the input line voltage VIN at most, such that relatively low withstand voltage switching elements and capacitive elements can be implemented, and the cost and the volume of circuit elements can also be reduced.
  • the energy-transforming circuit of the disclosure is implemented by using a coupling inductor, a charge-storage capacitor, a switch, and two diodes. Comparing to the prior art of the power factor correction resonant converter, the disclosure can effectively reduce the volume of the circuit, and reduce the conduction losses from the components.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • General Physics & Mathematics (AREA)
  • Radar, Positioning & Navigation (AREA)
  • Automation & Control Theory (AREA)
  • Dc-Dc Converters (AREA)
  • Charge And Discharge Circuits For Batteries Or The Like (AREA)
US13/714,754 2012-06-27 2012-12-14 Common-core power factor correction resonant converter Active 2033-05-30 US8937463B2 (en)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
TW101123093 2012-06-27
TW101123093A 2012-06-27
TW101123093A TWI485961B (zh) 2012-06-27 2012-06-27 共鐵心式功率因數校正諧振轉換器

Publications (2)

Publication Number Publication Date
US20140002035A1 US20140002035A1 (en) 2014-01-02
US8937463B2 true US8937463B2 (en) 2015-01-20

Family

ID=47563118

Family Applications (1)

Application Number Title Priority Date Filing Date
US13/714,754 Active 2033-05-30 US8937463B2 (en) 2012-06-27 2012-12-14 Common-core power factor correction resonant converter

Country Status (6)

Country Link
US (1) US8937463B2 (ko)
EP (1) EP2680418B1 (ko)
JP (1) JP5599911B2 (ko)
KR (1) KR101456654B1 (ko)
CN (1) CN103516220B (ko)
TW (1) TWI485961B (ko)

Families Citing this family (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US10615692B2 (en) 2014-04-25 2020-04-07 Texas Instruments Incorporated Series capacitor buck converter having circuitry for precharging the series capacitor
KR102260299B1 (ko) 2014-11-12 2021-06-04 주식회사 솔루엠 전원장치 및 그의 구동방법
TWI645659B (zh) * 2018-01-05 2018-12-21 首利實業股份有限公司 LLC resonant converter efficiency improvement method and structure thereof

Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6690143B2 (en) * 2001-12-10 2004-02-10 Industrial Technology Research Institute Power factor correction circuit with resonant snubber

Family Cites Families (11)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5502357A (en) * 1994-10-03 1996-03-26 Durel Corporation Low cost inverter for EL lamp
JP3271581B2 (ja) * 1998-04-24 2002-04-02 株式会社村田製作所 偏向高圧一体型電源装置
US6081432A (en) * 1998-05-26 2000-06-27 Artesyn Technologies, Inc. Active reset forward converter employing synchronous rectifiers
JP4333295B2 (ja) * 2003-09-11 2009-09-16 横河電機株式会社 スイッチング電源
KR100834031B1 (ko) * 2006-10-17 2008-05-30 삼성전기주식회사 스너버회로를 이용한 역률개선회로
US7782027B2 (en) * 2006-12-30 2010-08-24 Advanced Analogic Technologies, Inc. High-efficiency DC/DC voltage converter including down inductive switching pre-regulator and capacitive switching post-converter
KR101445842B1 (ko) * 2008-05-29 2014-10-01 페어차일드코리아반도체 주식회사 컨버터
CN201422076Y (zh) * 2009-04-10 2010-03-10 东莞市冠佳电子设备有限公司 一种升压电路
TWM384460U (en) * 2010-03-01 2010-07-11 Welland Ind Co Ltd Electrical power conversion device with a power factor correction feature
TW201143267A (en) * 2010-05-31 2011-12-01 Univ Nat Cheng Kung Multi-winding high step-up DC-DC converter
US8767417B2 (en) * 2010-06-25 2014-07-01 System General Corp. Dual switches flyback power converter with wide input voltage range

Patent Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6690143B2 (en) * 2001-12-10 2004-02-10 Industrial Technology Research Institute Power factor correction circuit with resonant snubber

Also Published As

Publication number Publication date
JP5599911B2 (ja) 2014-10-01
KR101456654B1 (ko) 2014-11-04
CN103516220B (zh) 2015-08-19
US20140002035A1 (en) 2014-01-02
EP2680418B1 (en) 2018-09-12
KR20140001084A (ko) 2014-01-06
EP2680418A3 (en) 2014-09-03
TW201401737A (zh) 2014-01-01
CN103516220A (zh) 2014-01-15
JP2014011950A (ja) 2014-01-20
TWI485961B (zh) 2015-05-21
EP2680418A2 (en) 2014-01-01

Similar Documents

Publication Publication Date Title
US10833594B2 (en) System and method of controlling a power converter having an LC tank coupled between a switching network and a transformer winding
US9356526B2 (en) DC-DC power conversion apparatus and method
TWI542127B (zh) 降壓型主動式功因修正裝置
US9698671B2 (en) Single-stage AC-to-DC converter with variable duty cycle
US10103639B2 (en) Soft switching converter by steering the magnetizing current
US10566891B2 (en) Power supply device and control method thereof
WO2017012328A1 (zh) 一种单级功率因数校正的移相全桥拓扑电路
TW201541838A (zh) 返馳式主動箝位電源轉換器
WO2019102474A1 (en) Constant frequency dc/dc power converter
US8937463B2 (en) Common-core power factor correction resonant converter
KR101140336B1 (ko) 절연형 벅 부스트 ｄｃ?ｄｃ 컨버터
US20130250637A1 (en) Single-Stage Single-Switch Voltage Converter
TWI501527B (zh) 單輔助開關之交錯式高升壓比柔切式轉換器
JP6393962B2 (ja) スイッチング電源装置
TWI543513B (zh) 諧振轉換器
CN111049387B (zh) 一种tlcⅱ型谐振电路及其应用的电源变换器
Luewisuthichat et al. Analysis and implement DC-DC integrated boost-flyback converter with LED street light stand-by application
Lin et al. Analysis and implementation of a ZVS-PWM converter with series-connected transformers
CN108075669B (zh) 带集成级联结构的dc-dc变换器
TW201717532A (zh) 單級交流至直流轉換器
Chub et al. Sheppard-Taylor isolated high boost DC-DC converter
US9673716B2 (en) Resonant converter with three switches
TWI514739B (zh) 單級高功因返馳式轉換器
Bian et al. A high performance boost converter with voltage multiplier
Das et al. Analysis and design of a three-level DC-DC converter with load adaptive ZVS auxiliary circuit

Legal Events

Date Code Title Description
AS Assignment

Owner name: MACROBLOCK, INC., TAIWAN

Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNORS:CHANG, LON-KOU;HUANG, YI-WEN;HUANG, HAN-HSIANG;REEL/FRAME:029470/0114

Effective date: 20121206

FEPP Fee payment procedure

Free format text: PAYOR NUMBER ASSIGNED (ORIGINAL EVENT CODE: ASPN); ENTITY STATUS OF PATENT OWNER: SMALL ENTITY

Free format text: PAYER NUMBER DE-ASSIGNED (ORIGINAL EVENT CODE: RMPN); ENTITY STATUS OF PATENT OWNER: SMALL ENTITY

STCF Information on status: patent grant

Free format text: PATENTED CASE

MAFP Maintenance fee payment

Free format text: PAYMENT OF MAINTENANCE FEE, 4TH YR, SMALL ENTITY (ORIGINAL EVENT CODE: M2551)

Year of fee payment: 4

MAFP Maintenance fee payment

Free format text: PAYMENT OF MAINTENANCE FEE, 8TH YR, SMALL ENTITY (ORIGINAL EVENT CODE: M2552); ENTITY STATUS OF PATENT OWNER: SMALL ENTITY

Year of fee payment: 8