RU2699946C1 - Multibeam digital active phased antenna array with receiving-transmitting modules calibration device and calibration method - Google Patents

Abstract

FIELD: antenna equipment.

SUBSTANCE: invention relates to antenna engineering, particularly to the field of multibeam digital active phased arrays with polarization control during radiation and adaptation to electromagnetic wave polarization at reception and calibration method. Multibeam digital active phased array with polarization control can be used in radioelectronic systems (RES), such as communication systems, radar equipment, and enables to solve multifunctional tasks on the basis of one radioelectronic device.

EFFECT: technical result when using a multibeam digital active phased antenna array with controlled polarization of the emitted EMW and adaptation to polarization EMW at reception with an extended frequency application area, with calibration device of receiving-transmitting modules, consists in realization of compensation of frequency characteristics in digital form after digitization of oscillations, in provision of high antenna directivity, possibility of beams generation at frequencies, frequency distance between which exceeds working bands of DAC and ADC, and device for calibration of receiving and transmitting channels of multibeam digital active phased antenna array makes it possible to increase accuracy and reliability of measurements of their complex transmission coefficients.

4 cl, 14 dwg

Description

The invention relates to antenna technology, in particular, to the field of multipath digital active phased arrays with polarization control during radiation and adaptation to the polarization of the electromagnetic wave at the reception and calibration method.

A multi-beam digital active phased array with polarization control can be used in electronic systems (RES), such as communication systems, radar equipment, and allows you to solve multifunctional problems based on one RES.

For the formation of the required radiation pattern by the phased array, knowledge of the initial phase shifts and the amplitudes of the excitation of each channel is necessary. The process of obtaining these parameters is called calibration of transceiver modules (MRP).

The elements that make up each module are not absolutely identical and have deviations of parameters from the nominal value caused by manufacturing errors, temperature effects, aging, etc. Deviations of the parameters from the nominal value lead to the fact that the amplitudes and phases of the signals at the outputs of different SCMs will differ from the calculated values, this causes errors in the amplitude-phase distribution along the aperture of the active phased antenna array (AFAR) relative to the calculated values. Ultimately, this leads to a deterioration of the most important parameters of the AFAR, such as the coefficient of directional action, the efficiency of the AFAR and the level of the side lobes. Therefore, in order to maintain the calculated parameters of the AFAR during operation, it is necessary to periodically monitor the parameters of the multichannel transceiver path to restore the performance of the AFAR.

The preservation of the calculated parameters of the AFAR is provided by the introduction of digital-to-analog (DAC) and analog-to-digital (ADC) converters of devices for correcting the amplitude-phase characteristics of channels, the parameters of which are specified during the calibration process.

Known technical solutions for the construction of ILCAFAR (Svetlichny Yu.A. et al. Schemes and components of promising radio systems with digital phased antenna arrays. Materials of the scientific and technical conference of young scientists and specialists “Scientific Readings on the 90th Birthday of Academician V.P. Efremova ". M., 09/19/2016), in which the lattice consists of N transceiver modules connected to the processing module. After the analog-to-digital output of each transceiver module, a multi-frequency digital receiver is formed in the processing module, and the signal generated by the digital multi-frequency converter is fed to the digital-analog input of each transceiver module. The outputs of the processing module are connected to the inputs of the multichannel diagram-forming circuit, at the outputs of which beams (radiation patterns) are formed corresponding to the given frequencies. From the digital diagram-forming circuit, the inputs of multifrequency converters receive signals that, after conversion to analog form using the DAC and frequency conversion, amplification in the transceiver modules, form the amplitude-phase distribution of the electromagnetic field of the corresponding beam at the output of the emitters. The main disadvantages of the specified MLCAFAR:

- when receiving an electromagnetic wave, the width of the operating frequency range is limited by the operating frequency band at the input of the ADC;

- when emitting an electromagnetic wave, the width of the operating frequency range is limited by the operating frequency band at the input of the DAC;

- there is no control of the polarization of electromagnetic waves during radiation;

- there is no adaptation to the polarization of the received EMW.

There is a known method for calibrating AFAR, in which to determine the complex transmission coefficients of the AFAR channels, the signal from the control signal generator is fed through the divider to the input of each transmitting channel, a part of the transmitted signal branches off from the output of each transmitting channel and is summed in the control signal adder. Then the same signal through another divider of the control signal is fed to the input of each receiving channel AFAR. From the output of each receiving channel, the signal is summed in another adder and is fed to the input of the control signal detector. In this case, the signal at the detector input is a superposition of the reference signal, which is played by the total signal from the (N-1) AFAR channels, and one measured channel, and its phase shifter is switched one by one to each of L = 2 ^p (p is the number of bits of the phase shifter ) states. After measuring the signal level after the detector for each state of the phase shifter, an array of L values is obtained, based on which the transmission coefficient of the measured channel and the initial phase shift relative to the reference channel are determined (Rossels N.A., Shishlov A.V., Shitikov AM Active phased array antennas - some issues of setup and maintenance // Radio Engineering. No. 4/2009). The disadvantages of this method are:

- the ambiguity of measurements of the complex transmission coefficients of the AFAR channels, since the control signal sequentially passes first through the transmitting channels, and then through the receiving ones;

- limited scope of the method, due to the need to work simultaneously transmitting and receiving channels AFAR;

- the use of two dividers / adders of the control signal, which increases the mass, dimensions and cost of the calibration equipment; reduces the accuracy of measurements with increasing number of AFAR channels.

The closest analogue, prototype, is the technical solution described in US patent No. US 6545630 B1, 04/08/2003, G01S 7/38. In the prototype at the reception, the position of the beam and the polarization of the received electromagnetic wave (EMW) are controlled, and when the radiation is emitted, the polarization and direction of the antenna beam are controlled. The main disadvantages of this device are:

- lack of independent control of radiation patterns when receiving and emitting electromagnetic radiation;

- only one beam is formed;

- the technical complexity of the implementation of the PPM with identical parameters of the radio paths.

The technical result when using a multi-beam digital active phased antenna array with polarization control of the emitted electromagnetic wave and adaptation to the polarization of the electromagnetic wave at a reception with an extended range of applications in frequency, with a device for calibrating transceiver modules, consists in the implementation of digital frequency characteristics compensation after oscillation sampling, in ensuring a high directivity of the antenna, the possibility of the formation of rays at frequencies, the frequency distance between which exceeds the working field sy DAC and ADC, and the calibration device receiving and transmitting digital multi-channel active phased array antenna allows to improve the accuracy and reliability of measurements of their complex transmission coefficients.

For this, the multi-beam digital active phased antenna array (MLCAFAR) contains a system of antenna emitters with orthogonal polarizations connected to N transceiver modules (PPM) connected to an amplitude-phase correction (ROS) system associated with a digital beamforming (CDO) system, as well as a target designation device, a polarization control system and a synchronization system (SS), which synchronizes the operation of a multi-beam digital active phased antenna array. Moreover, an additional calibration device for a multipath digital active phased antenna array is included for periodically calibrating the receiving channels of the PMD according to the control signal generated by the transmitting channel of the reference PPM, and the transmitting channels of the MRP by the control signal generated by the transmitting channels of the PPM, the amplitude-phase correction system is configured to correct the parameters multichannel transceiver paths, and the digital chart formation system is made with the possibility of independent control directional patterns when receiving and transmitting signals, while the target designator is connected to a digital beamforming system for receiving and transmitting, connected to a polarization driver of the polarization control system during transmission and adaptation to polarization when receiving, while the signals are transmitted and received alternately.

In this case, each PPM contains the required number of digital-to-analog (DACs) during transmission and analog-to-digital (ADC) converters during reception, the number of which is determined by the number of generated beams at frequencies whose frequency spacing exceeds the passband at the input of the DAC and ADC.

The MLCAFAR calibration device for calibrating the receiving channels of the PPM by the control signal transmitted along the MLCAFAR receiving paths contains a reference PPM, a transmission path of the control signal, non-directional input of the control signal and microwave switches. The output of the transmitting channel of the reference PPM, through the switch for changing the direction of the control signal along the calibration path and the device for the non-directional input of the control signal into the receiving channel of the reference PPM, is connected to the microwave switch for selecting the PPM for calibration, connected to the input of the non-directional input of the control signal through which the control signal arrives at the input of the receiving calibrated channel, while the direction of the control signal along the transmission path between the receiving channel m reference MRP and MRP calibrated receiver finger paths in the opposite, the value of the control signal controlling the attenuation in the signal path between the receiving channels constant and the phase delay reverses sign. Further, by the signals at the outputs of the radio receiving channels of the reference PPM and the selected PPM, the deviations of the amplitude-phase characteristics of the receiving channel of the selected PPM from the amplitude-phase characteristics of the receiving channel of the reference PPM are determined. Based on the measurement results of these deviations, a differential difference in the transmit coefficient of the receive channel of the selected transceiver module from the transmit coefficient of the receive channel of the reference transceiver module is calculated, while the differential difference of the transmit coefficient of the receive channel of the selected PPM relative to the transmit coefficient of the receive reference PPM channel is calculated for two schemes for switching on the selected PPM: receiving channels of the selected PPM are connected to the antenna element, and receiving The selected channels of the selected MRP are connected through the non-directional input node to the control signal path.

In the method of calibrating MLCAFAR for calibrating the transmitting channels of the MRP according to the control signal transmitted along the paths of reception and transmission of MLCAFAR during the calibration of the transmitting channels of the PPM, the control signal generated by the transmitting channel of the reference PPM is input through the non-directional communication device into the receiving radio path of the reference PPM, and the control signal formed by the transmitting channel of the selected PPM, through an omnidirectional communication device is introduced into the receiving radio path of the selected PPM, and then, by the signals at the outputs of the radio receiving channels reference PPM and the selected receiving channel PPM, the deviations of the amplitude-phase characteristics of the receiving channel of the selected PPM from the amplitude-phase characteristics of the receiving channel of the reference transceiver module are determined. Based on the measurement results, taking into account the differential difference in the transmission coefficients of the receiving channels of the reference and selected transceiver modules of these deviations, the differential difference of the transmission channel gain of the selected PPM from the transmission coefficient of the transmission channel of the reference transceiver module is calculated.

MLCAFAR with polarization control of the emitted electromagnetic wave and adaptation to the polarization of the electromagnetic wave at a reception with an extended range of applications in frequency contains emitters with orthogonal polarizations having a common phase center. The outputs of the emitters are connected to the PPM, and each PPM contains the required number of DACs and ADCs, the number of which is more than one and is determined by the number of generated beams at the receive and transmit frequencies, the frequency distance between which exceeds the operating frequency bands of the DAC and ADC.

Ensuring the calibration of the MLCAFAR PPM is solved by the fact that the integrated MLCAFAR calibration device, consisting of the reference PPM, the control signal transmission path, the directional input devices of the control signal and switches, realizes the calibration of the PPM receiving channels by the control signal generated by the transmitting channel of the reference PPM, which is transmitted through the non-directional device communication is introduced into the receiving radio paths of the reference PPM and the selected receiving channel PPM. The direction of the control signal along the transmission path between the receiving channels in the paths is the opposite, while the attenuation of the control signal is constant, and the phase delay reverses its sign. Further, by the signals at the outputs of the radio receiving channels of the reference PPM and the selected PPM, the deviations of the amplitude-phase characteristics of the receiving channel of the selected PPM from the amplitude-phase characteristics of the receiving channel of the reference PPM are determined. Based on the measurement results of these deviations, the differential difference of the transmit channel gain of the selected PPM from the transmit coefficient of the receive channel of the reference PPM is calculated. In this case, measurements of the differential difference of the transmit channel gain of the selected PPM from the transmit coefficient of the receive channel of the reference PPM are performed for two switching schemes of the selected PPM: the receive channels of the selected PPM are connected to the antenna element, and the receive channels of the selected PPM are connected through the directional water node to the control signal path .

When calibrating the transmitting channels of the PPM, the control signal generated by the transmitting channel of the reference PPM is input through the non-directional communication device to the receiving radio path of the reference PPM, and the control signal generated by the transmitting channel of the selected PPM is transmitted through the device of non-directional communication to the receiving radio path of the selected PPM. Further, by the signals at the outputs of the radio receiving channels of the reference PPM and the selected receiving PPM channel, the deviations of the amplitude-phase characteristics of the receiving channel of the selected PPM from the amplitude-phase characteristics of the receiving channel of the reference PPM are determined. Based on the measurement results, taking into account the differential difference in the transmission coefficients of the receiving channels of the reference and selected PPM of these deviations, the differential difference of the gain of the transmitting channel of the selected PPM from the gain of the transmitting channel of the reference PPM is calculated.

Calibration of the receiving part of the transceiver channels is performed in the receiving mode, while the control signal is removed from the output of the receiving part of the transceiver channels. Calibration of the transmitting part of the transceiver channels is performed in the transmission mode, while for calibration use part of the signal power, branched from the output of the corresponding transceiver channel and passed through the receiving part of this channel. During the calibration, the phase shift and the difference in the amplitudes of the signal from the output of the calibrated channel relative to the reference are measured. The same channel is used as a reference for calibration of all channels, for example, the first one; a sinusoidal signal with a frequency in the operating AFAR frequency range is used for calibration.

The essence of the invention is illustrated by drawings.

In FIG. 1 shows a functional diagram of a digital AFAR with correction systems, CDO, polarization control during radiation and adaptation to the polarization of the received signal.

In FIG. Figure 2 shows a digital AFAR circuit with a calibration system, polarization control during EMF emission and adaptation to EMF polarization at reception.

In FIG. Figure 3 shows a functional diagram of an orthogonal polarization PPM (VH PPM) with correction of the amplitude-phase characteristics of the transceiver channels.

In FIG. 4 shows a functional diagram of the PMD for working on vertical / horizontal polarization, in which M _t channels for radiation and M _r channels for receiving electromagnetic waves, and time separation is provided by the use of microwave switches.

In FIG. Figure 5 shows a functional diagram of a multi-channel PPM with microwave switches for the temporary separation of the clock cycles of reception and transmission and connection of the control signal path.

In FIG. 6 and FIG. Figure 7 shows the switching options for the PPM microwave switches in the modes of receiving or transmitting electromagnetic waves and connecting the control signal path when calibrating these channels.

In FIG. Figure 8 shows the structural diagram of MLCAFAR with a calibration system.

In FIG. 9 shows the connection diagram of the MRP with index (number) i to the calibration system.

In FIG. 10 shows a pilot signal flow diagram at step L1 when calibrating the receiving channels of the MRP with the index (number) i when they are connected to the emitter.

In FIG. 11 shows a pilot signal flow diagram at the R1 calibration stage of the PPM receiving channels with index (number) i when they are connected to the emitter.

In FIG. 12 shows a pilot signal flow chart at the L2 calibration stage of the receiving channels of the MRP with index (number) i when they are connected to the pilot signal path.

In FIG. 13 shows a control signal transmission scheme at the calibration step R2 of the receiving PPM channels with index (number) i when they are connected to the control signal passage.

In FIG. 14 shows a signal flow diagram in step T during calibration of the transmission channels.

The claimed digital AFAR with a calibration system, polarization control during EMF emission and adaptation to EMF polarization at the reception contains:

1 - a system of antenna emitters on orthogonal polarizations;

2 - N transceiver modules;

3 - a system of amplitude-phase correction (ROS);

4 - a system of digital chart formation (CDO);

5 - target designation device;

6 - polarization control system;

7 - synchronization system;

8 - calibration device MLCAFAR for periodic calibration of the receiving channels of the PPM on the control signal generated by the transmitting channel 9 of the reference transceiver module;

9 - transmitting channel of the reference transceiver module;

10 - reference PPM;

11 - the receiving channel of the reference PPM;

12 - microwave switch M 2 × 2 (matrix of switches with two inputs and two outputs) changes the direction of passage of the control signal along the calibration path 8;

13 - matched load Z;

14 - microwave switches M PPM (matrix of switches with one input and N outputs) for connecting PPM 2 with index (number) i to the calibration path;

15 - nodes input calibration signal;

16 - unit for calculating calibration data;

17 - digital-to-analog converters radio paths PPM VH;

18 is a signal adder with the number of M _t inputs, forming a total signal;

19 is a multi-channel receiver on M _r channels;

20 - output amplifier PPM with index i;

21 - analog-to-digital converters;

22 - node input signal PPM with index i;

23 - switch the direction of the signal in the reference PPM;

24 - node input control signal reference PPM;

25 - output amplifier reference PPM;

26 - output amplifier PPM with index i.

The functional diagram (Fig. 1) of a digital AFAR with a device that implements the proposed calibration method, a correction system, a digital charting system, polarization control during EMF emission and adaptation to EMF polarization at the reception has the following notation:

H, V - emitters 1 on orthogonal polarizations;

- СВЧ переключатели для изменения тракта прохождения СВЧ сигналов в ППМ 2 с индексом (номером) i через узлы ввода сигналов.Miv

- Microwave switches for changing the path of the microwave signals in the MRP 2 with index (number) i through the signal input nodes.

Calculation data calculation block 16 implements the control algorithm of the MLCAFAR calibration process, measures the outputs of the receiving channels of the PMD forming MLCAFAR and calculates the calibration coefficients.

The control signal is generated by the transmitting channel of the reference PPM. The output of the transmitting channel of the reference PPM is connected to a microwave switch 12 M 2 × 2, which provides a change in the direction of passage of the control signal through the calibration path.

The input of the receiving channel of the reference PPM is connected to the path of the control signal through the omnidirectional communication node.

Using a set of microwave switches 14, the selected MRP with the index (number) i using input nodes 15 is connected to the calibration path 8.

Calculation data calculation unit 16 implements a calibration control process algorithm in which the receiving part of the transceiver channels of the selected PPM is calibrated in the receive mode, and the transmit part of the transceiver channels is calibrated in the transmission mode. During calibration, measurements are made of the phase difference and signal amplitudes from the output of the receiving channel of the selected PPM 2 relative to the receiving channel of the reference PPM 10.

With the proposed calibration method, there is no need to ensure that the control signal is in phase when calibrating the receiving and transmitting channels of the magnetic control.

The block diagram of MLCAFAR, which provides independent control of the beam during reception and emission of electromagnetic waves, control of the polarization of the emitted electromagnetic wave and adaptation to polarization of electromagnetic waves at the reception, as well as control of the parameters of the multi-channel transmit-receive path to restore the efficiency of the AFAR in FIG. 2 has the following notation:

ППМ VH № i - transceiver module 2 with index (number) i from 1 to N for radiation and reception of electromagnetic waves on orthogonal polarizations, which contains two channels connected to radiators on orthogonal polarizations, for radiation and two channels connected to radiators on orthogonal polarizations, for receiving EMW;

- комплексные коэффициенты амплитудно-фазовой коррекции передающих каналов ППМ VH с индексами (номерами) 1, 2, …, N при излучении ЭМВ на вертикальной поляризации.

- complex coefficients of the amplitude-phase correction of the transmitting channels of the PMH VH with indices (numbers) 1, 2, ..., N when emitting electromagnetic waves on vertical polarization.

- комплексные коэффициенты амплитудно-фазовой коррекции передающих каналов ППМ VH с индексами (номерами) 1, 2, …, N при излучении ЭМВ на горизонтальной поляризации.

- complex coefficients of the amplitude-phase correction of the transmitting channels of the PMH VH with indices (numbers) 1, 2, ..., N when emitting electromagnetic waves on horizontal polarization.

- комплексные коэффициенты амплитудно-фазовой коррекции приемных каналов ППМ VH с индексами (номерами) 1, 2, …, N при приеме ЭМВ на вертикальной поляризации.

- complex coefficients of the amplitude-phase correction of the receiving channels of the PMH VH with indices (numbers) 1, 2, ..., N when receiving EMW on vertical polarization.

- комплексные коэффициенты амплитудно-фазовой коррекции приемных каналов ППМ VH с индексами (номерами) 1, 2, …, N при приеме ЭМВ на горизонтальной поляризации.

- complex coefficients of the amplitude-phase correction of the receiving channels of the PMH VH with indices (numbers) 1, 2, ..., N when receiving EMW on horizontal polarization.

The work of MLCAFAR on reception and transmission is carried out by alternately changing the period of radiation and the period of reception of electromagnetic waves.

When emitting electromagnetic radiation, the initial data for the operation of MLCAFAR are:

- temporal parameters of the emitted signal: a sequence of quadrature components of the analytical signal I _tr , Q _tr ;

- polarization parameters of the emitted electromagnetic wave;

- the shape and spatial orientation of the bottom of the antenna system;

- carrier frequency of the emitted signal ƒ ₀ .

The operation of MLCAFAR during radiation is carried out as follows: the input of the polarization control system 6 MLCAFAR receives an analytical signal in quadratures I _tr , Q _tr , from which the polarization control system 6 generates quadrature signals I _trv , Q _trv and I _trv , Q _trh with specified polarization parameters for radiation at orthogonal polarizations of EMW components, for example, vertical and horizontal polarizations.

The quadrature signals I _trv , Q _trv and I _trv , Q _trv enter the _CDO system, in which the amplitude-phase distribution of the field at the aperture of the antenna system is calculated, which is required for the formation of MDs with the given parameters of spatial orientation and shape. The operation of the CDS system occurs by target designation from an external source, for example, on-board electronic equipment (avionics) of the facility on which the AFAR is installed.

корректирует амплитуду и фазу выходных квадратурных сигналов системы ЦДО 4, которые далее поступают в ЦАП 17 передающих радиотрактов ППМ VH.The elements forming the MLCAFAR transmitting radio paths are not completely identical. To eliminate the deviation of the amplitudes and phases of the signals at the outputs of the transmitting radio paths of the PPM VH from the calculated values, a correction system based on the data on the deviations of the amplitude-phase characteristics of the channels from the calculated values equal to

corrects the amplitude and phase of the output quadrature signals of the CDO 4 system, which then go to the DAC 17 of the transmitting radio paths of the VH PMP.

(представленных в комплексном описании), поступающих с соответствующих выходов системы коррекции.In the transmitting channels of the PMH VH connected to the emitters 1 of the spatially orthogonal components of the EMW, the modulation of the output signals corresponding to the components of the quadrature signals

(presented in the complex description) coming from the corresponding outputs of the correction system.

- аналитические цифровые входные сигналы (в комплексном представлении) передающих каналов ППМ VH с индексами (номерами) 1, 2, …, N для излучения ЭМВ на вертикальной поляризации.

- analytical digital input signals (in a complex representation) of the transmitting channels VHF VH with indices (numbers) 1, 2, ..., N for emitting electromagnetic waves on vertical polarization.

- аналитические цифровые входные сигналы (в комплексном представлении) передающих каналов ППМ VH с индексами (номерами) 1, 2, …, N для излучения ЭМВ на горизонтальной поляризации.

- analytical digital input signals (in a complex representation) of the transmitting channels VHF VH with indices (numbers) 1, 2, ..., N for EMW radiation on horizontal polarization.

- аналитические цифровые выходные сигналы (в комплексном представлении) приемных каналов ППМ VH с индексами (номерами) 1, 2, …, N при приеме ЭМВ на вертикальной поляризации.

- analytical digital output signals (in a complex representation) of the receiving channels of the VHF program with indexes (numbers) 1, 2, ..., N when receiving EMW on vertical polarization.

The frequency plan of work of the transmitting channels of the PMH VH is set by the synchronization system 7, which determines the corresponding frequency conversion at which the electromagnetic wave is emitted at a given frequency ƒ ₀ .

As a result of these actions, MLCAFAR emits EMV into the space with given temporal and spatial characteristics.

When receiving EMV, the initial data for the operation of ILCAFAR are:

- the shape and spatial orientation of the bottom of the antenna system;

- carrier frequency of the received signal ƒ ₀ .

The operation of the MLCAFAR during reception is carried out as follows: the emitters of the VH 2 PPM receive the spatially orthogonal components of the EMW incident on the MLCAFAR opening. The signals received by the emitters 1 are fed to the input of the receiving channels 2 PPM VH. In the receiving channels, the input signals are converted in frequency and the digital values of the quadrature of the signals I _trv , Q _trv and I _trv , Q _trv corresponding to the orthogonal decomposition bases of the incident EMF emitters are generated at zero intermediate frequency 1. The frequency plan of the receiving channels of the VHF PPM is set by the synchronization system 7 , which determines the corresponding frequency conversion at which EMW is received at a given frequency ƒ ₀ .

корректирует амплитуду и фазу выходных квадратурных сигналов системы ЦДО 4, которые далее поступают в ЦАП передающих радиотрактов ППМ VH 2.Further, the signals from the outputs of the VH 2 PPM are fed to the inputs of the correction system 3. The need to use the correction system 3 is due to the fact that the elements forming the receiving radio paths of MLCAFAR are not identical, and this leads to erroneous results when calculating the signal at the output of MLCAFAR. To exclude the influence of amplitude and phase differences of the receiving paths on the quality of signal formation at the output of the MLCAFAR correction system 3, according to the data on the deviations of the amplitude-phase characteristics of the channels from the calculated values equal to

corrects the amplitude and phase of the output quadrature signals of the CDO 4 system, which are then fed to the DAC of the transmitting radio paths of the PPM VH 2.

After correction, the digital quadratures of the VH 2 MLCAFAR PPM signals are fed to the inputs of the CDO 4 system when receiving electromagnetic wave, which, in accordance with the required parameters for the formation of the antenna system’s receiving antenna, calculates the amplitude-phase distribution of the field. The operation of the CDO 4 system occurs by target designation 5 from an external source, for example, avionics.

The signals from the outputs of the CDO 4 system at reception enter the polarization control system 6, where adaptation is made to the polarization of the received electromagnetic wave. The essence of adaptation to the polarization of the received EME is the formation at the output of the analytical signal in quadratures I _rc , Q _rc by coherent addition of the received spatially orthogonal signals. During adaptation, the ellipticity parameters of the adopted electromagnetic wave are determined. As a result of these actions, MLCAFAR receives EMW at a given frequency ƒ ₀ for a given beam pattern, its spatial orientation, and generates a quadrature signal and its ellipticity parameters at its outputs.

MLCAFAR provides:

- the formation of the DN of a given form for reception and transmission, and their orientation in space;

- polarization control of the emitted electromagnetic wave;

- adaptation to the polarization of the received EMW.

In FIG. Figure 3 shows the functional diagram of the VH PMD from a digital AFAR for the reception and emission of EME components at orthogonal polarizations with elements of a correction system.

Here:

на вертикальной поляризации от системы ЦДО 4 при излучении компоненты ЭМВ с вертикальной поляризацией;I _trv , Q _trv - quadrature components of the analytical signal

on vertical polarization from the CDO 4 system when emitting a vertical polarized EMF component;

на вертикальной поляризации от системы ЦДО 4 при излучении компоненты ЭМВ на горизонтальной поляризации;I _trv , Q _trh - quadrature components of the analytical signal

on vertical polarization from the CDO 4 system when emitting an EMW component on horizontal polarization;

приемного канала, поступающие на систему ЦДО 4 вертикальной поляризации;I _rcv , Q _rcv - quadrature components of the analytical signal

the receiving channel, arriving at the system DAC 4 vertical polarization;

приемного канала, поступающие на систему ЦДО 4 горизонтальной поляризации;I _rch , Q _rch - quadrature components of the analytical signal

the receiving channel arriving at the CDO system 4 of horizontal polarization;

- комплексные коэффициенты АФК передающих каналов ППМ HV при излучении ЭМВ на вертикальной и горизонтальной поляризации;

- complex ROS coefficients of the transmitting channels of the HV PPM when emitting electromagnetic waves on the vertical and horizontal polarization;

- комплексные коэффициенты амплитудно-фазовой коррекции (АФК) приемных каналов ППМ HV при приеме ЭМВ на вертикальной и горизонтальной поляризации.

- complex coefficients of amplitude-phase correction (ROS) of the receiving channels of the HV PPM when receiving EMW on vertical and horizontal polarization.

Correction of the amplitude-phase characteristics of the MRP is carried out by multiplying the analytical signal by the complex coefficients of the ROS channels according to the rule of multiplication of complex quantities.

In FIG. 4 is a functional diagram of a transceiver module 2 on vertical / horizontal polarization, realizing the possibility of operating it in a multi-channel version, in which M _t channels for radiation and M _r receive channels EMF, while the frequency distance between the receiving and transmitting channels exceeds the working band of the ADC and DAC.

In FIG. 4 the following notation is accepted:

i is the index (number) of the transceiver module 2;

M _t is the number of digital inputs of the transceiver module 2;

M _r - the number of digital outputs of the transceiver module 2;

I _{tr (mt)} , Q _{tr (mr)} are the quadrature components of the analytical signal from the CDO 4 system, determined from the condition of the required amplitude-phase distribution (formation of the desired beam pattern) at the aperture of the antenna array when emitting the EMF channel, mt ∈ [1, ..., M _t ] transceiver module;

I _{rc (mr)} , Q _{rc (mr)} are the quadrature components of the analytical signal of the receiving channel mr ∈ [1, ..., M _r ] of the receiving-transmitting module 2, which are fed to the CDO system 4 to form the amplitude-phase distribution at the aperture of the antenna array at receiving EMV (the formation of DN during admission);

- сумматор 18 сигналов числом M_t входов, формирующий композитный сигнал;

- adder 18 signals by the number of M _t inputs, forming a composite signal;

- многоканальное приемное устройство 19 на M_r каналов.

- multi-channel receiving device 19 on M _r channels.

формирует аналоговый композитный сигнал на основе входных цифровых сигналов, число которых равно M_t, и который далее поступает на выходной усилитель 20. Многоканальное приемное устройство

имеет приемные каналы, по числу АЦП, равному M_r.In MRP multi-frequency driver

generates an analog composite signal based on digital input signals, the number of which is equal to M _t , and which then goes to the output amplifier 20. Multichannel receiving device

has receiving channels, according to the number of ADCs equal to M _r .

Technological errors in the implementation of PPM 2 radio circuits lead to inter-channel and quadrature non-identical characteristics of the receiving and transmitting channels of MLCAFAR. To maintain the calculated parameters of the digital AFAR during operation, it is necessary to periodically monitor the parameters of the CAFAR multi-channel transmit-receive path and calibrate it to restore the identity of all channels, which is eliminated by the introduction of amplitude-phase channel correction devices before the DAC and after the ADC.

When working with signals for which the operation of the ADC or DAC is inefficient (high frequency, insufficient bit depth of the existing ADC / DAC, their high power consumption, etc.), one or several intermediate frequency conversions using local oscillators can be performed in the MRP.

To ensure digital synthesis of the radiation pattern in reception mode, as well as the formation of a given distribution of the electromagnetic field in the aperture of the antenna array 1 in transmission mode, the CDO 4 system is used, which provides digital synthesis of the radiation pattern in reception mode, as well as the formation of a given distribution of the electromagnetic field in the aperture of the antenna array in transmission mode.

The CDO system consists of devices for the formation of MDs when emitting electromagnetic radiation and the formation of MDs when receiving electromagnetic waves.

The formation of the required parameters of EMW ellipticity during radiation is ensured by decomposing the analytical signal into two components with a given ratio of amplitudes and phases and emitted in the form of spatially orthogonal EMF components.

Adaptation to polarization of electromagnetic waves during reception is provided by matching the polarization basis of the antenna with the polarization of the received signal.

The formation of a grid of reference frequencies that ensure synchronous operation of all the components of the hardware and software complex of the CDO 4 system, the generation of the clock signal from the ADC and DAC, the output of the reference signal to an analog master oscillator, the generation of local oscillator frequencies, and the switching of the switching signal correction of the characteristics of the receiving and transmitting modules is provided by the synchronization system 7.

One of the most difficult tasks is to configure broadband MLCAFAR (phasing during reception and transmission) and to keep it in working condition. To solve this problem, the claimed invention proposes to introduce an internal calibration system into ILCAFAR, which, based on the deviation of the amplitude-phase characteristics of the ILCAFAR PMP from the amplitude-phase characteristics of the reference PPM, will allow calculating the amplitude-phase correction coefficients of the receiving and transmitting PPM channels.

To expand the instantaneous band of operating frequencies of MLCAFAR for reception and transmission by the claimed invention (Fig. 4), it is proposed to introduce additional DAC 17 and ADC 21 into the composition of the PMP, which allow the generation of beams at frequencies whose frequency spacing exceeds the working frequency band of DAC 17 and ADC 21. The output of each DAC 17 is connected to an analog adder 18, the output of which is formed by the total signal, then fed to the output amplifier 20 PPM with index i. The output of each ADC generates a digital signal, and each of them is connected to a separate receiving channel. The maximum instantaneous operating frequency band of MLCAFAR for radiation is equal to the sum of the operating bands at the input of all DACs 17, and the maximum instantaneous operating frequency band of MLCAFAR for radiation is equal to the sum of the operating bands at the input of all ADCs 21.

In FIG. 5 shows a functional diagram of a multi-channel PPM, in which the output of the antenna emitter 1, through the input node 15 of the signals, is connected to the receiving and transmitting channels, and the transmitting channel has M _tr digital inputs, the receiving channel has M _rc digital outputs. Microwave switches 24 of the control signal input node change the paths of the control signal and the connection of the receiving and transmitting channels to the emitter.

In FIG. 5 adopted the following notation:

П1i, П2i, ..., П6i - high-frequency switches 14 of the transceiver modules 2;

U1i - input node 22 (communication device) of the PPM calibration signal with index i;

- сумматор 18 ППМ с индексом (номером) i на M_tr входов, формирующий суммарный сигнал на основе входных цифровых сигналов, который далее поступает на выходной усилитель 20;

- the adder 18 PPM with the index (number) i on the M _tr inputs, forming a total signal based on the input digital signals, which is then fed to the output amplifier 20;

- формирователь 19 приемных каналов ППМ с индексом (номером) i, которые с помощью АЦП 21 формируют M_rc цифровых выходов ППМ.

- shaper 19 receive channels PPM with index (number) i, which using the ADC 21 form M _rc digital outputs PPM.

High-frequency switches П1i, П2i, ..., П6i ППМ provide the required configuration of the microwave signal path during calibration of the ППМ and during its operation in the modes of reception and transmission of electromagnetic waves.

The communication devices U1i, U2i of the microwave signal transmission paths of the type of loop connection are performed as identically as possible with a communication coefficient of -20 to -25 dB to reduce the degradation of the noise figure of the receiving channels.

In FIG. 6 and FIG. 7 shows the switching options of the microwave signal paths for connecting the emitter to the receiving and transmitting channels of the PPM with the index (number) i in the operating modes of receiving / transmitting electromagnetic waves and connecting the path of the control signal during calibration of these channels:

- Scheme a) corresponds to the position of the microwave switches of the input node when receiving electromagnetic waves by the receiving-transmitting module: we conventionally denote the operating mode of the PPM with the index (number) i at this position of the microwave switches “Receive”;

- Scheme b) corresponds to the position of the microwave switches of the input unit when emitting electromagnetic radiation by the receiving-transmitting module: we conventionally denote the operating mode of the PPM with the index (number) i at this position of the microwave switches "Transmission";

- Scheme c) corresponds to the position of the microwave switches of the input node when calibrating the receiving PPM channel with the index (number) i in the "Reception" mode: we will arbitrarily denote the position "Calibration Pr";

- Diagram d) corresponds to the position of the microwave switches of the input node when calibrating the receiving PPM channel with index (number) i in the "Transmission" mode: we will arbitrarily denote the position "Calibration P".

In FIG. 8 shows a detailed functional diagram of MLCAFAR with a system for calibrating the receiving and transmitting channels of the PMD with the index (number) i according to the control signal, where

- комплексные коэффициенты АФК канала т приемо-передающего модуля при излучении и при приеме ЭМВ;

- complex coefficients of the ROS channel t of the transceiver module during radiation and when receiving electromagnetic waves;

I _{tr, i (mt)} , Q _{tr, i (mt)} are the quadrature components of the analytical signal from the CDO system, determined from the condition of the required amplitude-phase distribution (formation of the desired beam pattern) at the aperture of antenna array 1 when EMF is emitted by the mt PPM channel 2 s index (number) i;

I _{rc, i (mr)} , Q _{rc, i (mr)} are the quadrature components of the analytical signal of the receiving channel mr PPM 2 with the index (number) i fed to the CDO system to form the amplitude-phase distribution at the aperture of the antenna array when receiving electromagnetic radiation (formation Nam when taking);

I _{tr, i (mt)} , Q _{tr, i (mt)} - quadrature components of the analytical signal emitted by the beam with the number mt;

I _{rc, i (mr)} , Q _{rc, i (mr)} - quadrature components of the analytical signal received by the mt beam;

- комплексный коэффициент управления амплитудно-фазовым значением канала mt ППМ 2 с индексом (номером) i при формировании ДП на излучение и комплексный коэффициент управления амплитудно-фазовым значением канала mr ППМ 2 с индексом (номером) i при формировании ДН при приеме;

- a complex coefficient of control of the amplitude-phase value of the channel mt PPM 2 with the index (number) i when generating a DP for radiation and a complex coefficient of control of the amplitude-phase value of the channel mt PPM 2 with the index (number) i when forming the beam when receiving;

U0 is a communication device 24 of the calibration signal transmission path with the input of the receiving channel of the reference PPM;

P0K, P1K, ..., P6K - high-frequency switches 23 that determine the path of the control signal of the reference PPM;

- сумматор 18 ППМ с индексом (номером) i на M_tr входов формирующий суммарный сигнал на основе входных цифровых сигналов, который далее поступает на выходной усилитель;

- the adder 18 PPM with the index (number) i on the M _tr inputs forming the total signal based on the input digital signals, which then goes to the output amplifier;

- формирователь 19 приемных каналов ППМ с индексом (номером) i, которые с помощью АЦП формируют M_rc цифровых выходов приемо-передающих модулей.

- shaper 19 receiving channels PPM with index (number) i, which using the ADC form M _rc digital outputs of the transceiver modules.

Let MLCAFAR have N PPM 2 emitting and receiving EMWs on two orthogonal polarizations (PPM VH) and, accordingly, 2N receiving-transmitting modules (PPM), each of which has M _tr digital inputs and M _rc digital outputs. MLCAFAR forms M _{tr of} various diagrams for EMF emission and M _{rc of} various diagrams when receiving EMF.

For simplicity of exposition of the ILCCAFAR functioning algorithm, we assume that the VHF PMPs have indices I ∈ [1, ..., N] and, accordingly, the MHPM indices of the VHM PMH with index (number) I connected to the emitters on the vertical polarization are i = 2I- 1, and the indices of the transceiver modules for the VH APM with index (number) I connected to the emitters on horizontal polarization are i = 2I.

The work of MLCAFAR is carried out in the modes of emitting electromagnetic waves (mode "Transmission"), receiving electromagnetic waves (mode "receiving") and calibration (modes "Calibration P", "Calibration Pr").

The calibration of the receiving and transmitting channels of the PPM with the index (number) i is performed by alternately comparing the output signals of the receiving channels of the PPM with the index (number) i of MLCAFAR with the output signal of the receiving channel of the reference PPM in the “Calibration P”, “Calibration Pr” and “Transmission” modes . The connection of the selected MRP with the index (number) i MLCFAR to the calibration system is performed using the switches P2, P4 for the PPM with vertical polarization and using the switches P3, P5 for the PPM with horizontal polarization.

Based on the results of the comparison, the deviations of the complex coefficients of the PPM channels with index (number) i are calculated relative to the amplitude-phase characteristics of the reference PPM channel and based on these deviations, the ROS coefficients of the PPM channels with index (number) i MLCAFAR are calculated. The calibration process of MLCAFAR consists in the formation of arrays of correction coefficients of the receiving and transmitting (emitting) channels for each of all MRPs included in MLCAFAR. These correction factors make it possible to eliminate the influence of the amplitude-phase differences of the receiving and transmitting channels when controlling the polarization and the formation of the pattern when receiving and emitting electromagnetic waves.

Calibration of the receiving channels of MLCAFAR can be defined as the measurement of a set of complex correction factors equal to the ratio of the complex transmission coefficients of the receiving PPM channels with index (number) i, i ∈ [1, 2, ..., 2N], to the value of the complex transmission coefficient of the receiving channel of the channel number mrc MRP with index (number)

здесь

here

- комплексный коэффициент коррекции приемного канала с номером mr, (mr ∈ [1, …, M_rc]) ППМ с индексом (номером) i, определенный относительно приемного канала с номером mrc, (mrc ∈ [1, M_rc]) приемо-передающего модуля с индексом (номером)

- the complex correction coefficient of the receiving channel with the number mr, (mr ∈ [1, ..., M _rc ]) the MRP with the index (number) i, defined relative to the receiving channel with the number mrc, (mrc ∈ [1, M _rc ]) transmitting module with index (number)

- комплексный коэффициент передачи приемного канала с номером mr приемо-передающего модуля с индексом (номером) i;

- the complex transmission coefficient of the receiving channel with the number mr of the transceiver module with index (number) i;

- комплексный коэффициент передачи приемного канала с номером mrc приемо-передающего модуля с индексом (номером)

- the complex transmission coefficient of the receiving channel with the mrc number of the transceiver module with the index (number)

может быть произвольным, очевидно что

.Rule of a choice of the channel of reception mrc MRP number with an index (number)

may be arbitrary, obviously

.

:Calibration of the transmitting channels MLCAFAR can be defined as the measurement of a set of complex correction factors equal to the ratio of the complex transmission coefficients of the EMC channels by the receiving-transmitting module with index (number) i (i ∈ [1, 2, ..., 2N]) to the value of the complex channel transfer coefficient radiation emitter with the number mtr from the transceiver module with index (number)

:

- комплексный коэффициент коррекции излучающего канала с номером mt, (mt ∈ [1, M_tr]) ППМ с индексом (номером) i, определенный относительно приемного канала с номером mtr, (mtr ∈ [1, …, M_tr]) приемо-передающего модуля с индексом (номером)

;

- the complex correction factor of the emitting channel with the number mt, (mt ∈ [1, M _tr ]) the PMD with the index (number) i, defined relative to the receiving channel with the number mtr, (mtr ∈ [1, ..., M _tr ]) transmitting module with index (number)

;

- комплексный коэффициент передачи приемного канала с номером mr приемо-передающего модуля с индексом (номером) i;

- the complex transmission coefficient of the receiving channel with the number mr of the transceiver module with index (number) i;

- комплексный коэффициент передачи приемного канала с номером mtr приемо-передающего модуля с индексом (номером)

.

- the complex transmission coefficient of the receiving channel with the mtr number of the transceiver module with the index (number)

.

может быть произвольным, очевидно что

.Rule for selection of the receive channel number mtr PPM with index (number)

may be arbitrary, obviously

.

,

:Calibration of the transmission coefficients of the receive paths for the control signals during monitoring of the transmitted signals with the index (number) i of signals, from the input point of the control signal U1i to the output of the ADC, can be defined as the measurement of a set of complex correction factors equal to the ratio of the complex corrections of the transmit coefficients of the receive channels for monitoring the emitted MRP of signals number j, j ∈ [1, ..., M _rc ], to the magnitude of the complex correction of the transmission coefficient of the channel receiving path number mrk, mrk ∈ [1, ..., M _rc ] MRP with index (number)

,

:

здесь

here

- комплексный коэффициент коррекции излучающего канала с номером j, (j ∈ [1, M_tr]) ППМ с индексом (номером) i, определенный относительно коэффициента передачи приемного канала с номером mrk, (mrk ∈ [1, M_tr]) ППМ с индексом (номером) mrk.

- the complex correction factor of the emitting channel with number j, (j ∈ [1, M _tr ]) the PMD with index (number) i, determined with respect to the transmission coefficient of the receiving channel with the number mrk, (mrk ∈ [1, M _tr ]) index (number) mrk.

может быть произвольным, очевидно что

.Rule for selection of the receive channel number MRK MRP with index (number)

may be arbitrary, obviously

.

A description of the MLCAFAR PPM calibration algorithm will be presented using the example of calibration of the PPM with index (number) i.

The calibration algorithm for the PMCA MLCAFAR at operating frequencies ƒ ₁ , ƒ ₂ , ..., ƒ _{k is} carried out by sequentially performing the following steps:

1. The frequency for which the MLCAFAR calibration is performed is set.

2. Calibration of the transceiver module is performed with the index (number) i at a given frequency.

Using high-frequency switches P1K, P6K, and P2K, P3K, P4K, P5K, the PPM with index (number) i is connected to the calibration system. The P1K, P6K switches provide the choice of PPM operating on vertical polarization or horizontal polarization, and the P2K, P3K, P4K, P5K switches provide the choice of the corresponding PPM.

In FIG. Figure 9 shows the connection diagram of the transceiver module with index (number) i to the calibration system.

The frequency at which the calibration of the receiving channels of the transceiver modules is set. A calibration calibration signal is generated by recording in the DAC of the transmitting channel the reference PPM of the quadrature components of the analytical signal.

2.1 Stage L1

The position of the switches П0К, П1, П1i, П2i, П6К is set so that the control signal from the output amplifier of the reference channel U0 25 of the reference PPM is distributed from the communication node U0 24 to the communication node U2i 22, and the high-frequency switches P1i, P2i, ..., П6i are received - transmitting module 2 with index (number) i are set to the position corresponding to the “Calibration Pr” mode.

, здесь индекс L1 соответствует наименованию этапа, для которого схема прохождения приведена на фиг. 10.The control signal through the communication node U0 enters the receiving channel of the reference PPM and through the communication node U1i to the receiving channels 1, 2, ..., M _rc , the selected PPM, the outputs of which are connected to the ADC. ADCs register in quadratures the output signals of the corresponding receiving channels equal to

, here the index L1 corresponds to the name of the stage for which the passage scheme is shown in FIG. 10.

2.2 Stage R1

The position of the P0K switch is set so that the control signal from the output amplifier of the reference channel U0 25 propagates from the communication node U2i to the communication node U0, and the high-frequency switches P1i, P2i, ..., P6i of the transceiver module 2 with the index (number) i are set to the position corresponding to the "Calibrate Pr" mode.

,

, а индекс R1 соответствует наименованию этапа, для которого схема прохождения контрольного сигнала приведена на фиг. 11.The control signal through the communication nodes U0 and U1i enters the receiving channel of the reference channel and the receiving channels 1, 2, ..., M _rc , the outputs of which are connected respectively to the ADC 21. The ADC registers the output signals of the corresponding receive channels in quadratures equal to

,

, and the index R1 corresponds to the name of the stage for which the control signal transmission scheme is shown in FIG. eleven.

2.3. Determination of the correction coefficients of the receiving channels of the transceiver module with the index (number) i for the "Reception" mode.

The calculation of deviations of the complex transmission coefficients of the receiving channel with the number j, j ∈ [1, ..., M _rc ] PPM with the index (number) i from the complex transmission coefficient of the reference receiving channel according to the formula:

и комплексного коэффициента передачи тракта прохождения контрольного сигнала от узла ввода U0 до узла U1i по формуле:

and the complex transmission coefficient of the control signal path from the input node U0 to the node U1i according to the formula:

, где

where

- комплексный коэффициент передачи узла связи U0;

- the complex transfer coefficient of the communication node U0;

- комплексный коэффициент передачи узла связи U1i;

- the complex transfer coefficient of the communication node U1i;

- комплексный коэффициент передачи приемного канала номер j, j ∈ [1, …, M_rc], ППМ с индексом (номером) i в режиме «Прием» от точки ввода контрольного сигнала через узел ввода U1i до соответствующего АЦП;

- the complex transmission coefficient of the receiving channel number j, j ∈ [1, ..., M _rc ], the transmitter with the index (number) i in the "Receive" mode from the input point of the control signal through the input node U1i to the corresponding ADC;

- отношение в квадратурах выходных значений АЦП на этапе L1;

- the ratio in quadratures of the output values of the ADC at step L1;

- отношение в квадратурах выходных значений АЦП на этапе R1.

- the ratio in quadratures of the output values of the ADC at step R1.

2.4 Stage L2.

The position of the switches П0К, П1, П1i, П2i, П6К is set so that the control signal from the output amplifier of the transmitting channel U0 25 of the reference PPM is distributed from the communication node U0 24 to the communication node U2i 22, and the high-frequency switches П1i, ..., П6i ППМ 2 с by index (number) i are set to the position corresponding to the Calibrate Pr mode.

и

, здесь индекс L2 соответствует заданному направлению распространения контрольного сигнала (фиг. 12).The control signal through the communication node U0 enters the receiving channel of the reference PPM and, through the communication node U2i, into the receiving channels 1, 2, ..., M _{rc of the} selected PPM, the outputs of which are connected to the ADC. ADCs register the output signals of the respective receive channels in quadratures

and

, here the index L2 corresponds to a given direction of propagation of the control signal (Fig. 12).

2.5 Stage R2.

The position of the П0К switch is set so that the control signal from the output amplifier U0 of the reference PPM is distributed from the communication node U2i to the communication node U0, and the high-frequency switches П1i, П2i, П6i ППМ 2 with the index (number) i are set to the position corresponding to the Calibration mode Etc".

,

, здесь индекс R2 соответствует заданному направлению распространения контрольного сигнала.The control signal through the communication nodes U0 and U2i enters the receiving channel of the reference PPM and receiving channels 1, 2, ..., M _{rc of the} transceiver module, the outputs of which are connected to the ADC. ADCs register in quadratures the output signals of the corresponding receiving channels equal to

,

, here the index R2 corresponds to a given direction of propagation of the control signal.

The pilot signal flow diagram is shown in FIG. 13.

2.6 Determination of the correction factors for the receiving channels of the MRP with the index (number) i for the "Transmission" mode.

The calculation of the deviations of the complex transmission coefficients of the receiving channel with number j, where j ∈ [1, ..., M _rc ] PPM with index (number) i, from the complex transmission coefficient of the reference receiving channel according to the formula:

and the complex transmission coefficient of the control signal path from the input node U0 to the input node U1i according to the formula:

, где

where

- комплексный коэффициент передачи узла связи U0;

- the complex transfer coefficient of the communication node U0;

- комплексный коэффициент передачи узла связи U2i;

- the complex transfer coefficient of the communication node U2i;

- комплексный коэффициент передачи приемного канала номер j, (j ∈ [1, …, M_rc]) ППМ с индексом (номером) i в режиме «Передача» от точки ввода контрольного сигнала через узел ввода U2i до соответствующего АЦП;

- the complex transmission coefficient of the receiving channel, number j, (j ∈ [1, ..., M _rc ]) MRP with index (number) i in the "Transmission" mode from the control signal input point through the input node U2i to the corresponding ADC;

- отношение в квадратурах выходных значений АЦП на этапе L2;

- ratio in quadratures of the output values of the ADC at step L2;

- отношение в квадратурах выходных значений АЦП на этапе R2.

- ratio in quadratures of the output values of the ADC at step R2.

2.7 Clauses 2.2 - 2.6 of the calibration of the receiving channels are performed for all MRP from the ILCAFAR. As a result, data is generated on the deviation of the transmission coefficients of the receiving channels of the PMD from the input points of the control signal through the input nodes U1i, U2i to the outputs of the corresponding ADCs relative to the complex transmission coefficient of the reference receiving channel.

2.8 Stage T

In the DAC of the transmitting channel of the reference PPM and transmitting channels with numbers 1, 2, ..., M _tr PPM with the index (number) i, equal quadrature signal components are recorded and signals of a given frequency are generated at the output of the transmitting channels.

.The position of the switches P0K, P1K is set so that the control signal from the output amplifier U0 of the transmitting channel of the reference PPM is distributed to the communication node U0 and, through the switch P1K, to the matched load. The control signal through the communication node U0 enters the receiving channel of the reference PPM, the output of which is connected to the ADC. The ADC registers in quadratures the output signal of the reference receiving channel equal to

.

High-frequency switches П1i, П2i, ..., П6i ППМ with index i are set to the position corresponding to the "Transmission" mode.

.The DAC of the transmitting channel with the number j, j ∈ [1, ..., M _tr ] PPM with the index (number) i generates a signal that is fed to the output amplifier 20 Yi and, further, to the emitter. The emitted signal through the communication node U1i is received by one of the reception channels, for example, whose number is n, n ∈ [1, ..., M _rc ]. The ADC of the receive channel n registers in quadratures the output signal of the receive channel equal to

.

The signal flow diagram for calibrating radiation paths is shown in FIG. fourteen.

According to the formula

, равной отношению в квадратурах выходного сигнала приемного канала номер n, n ∈ [1, …, M_rc] ППМ с индексом (номером) i, i ∈ [1, …, N] к выходному сигналу опорного приемного канала M_tr.calculating the value

equal to the ratio in quadratures of the output signal of the receiving channel number n, n ∈ [1, ..., M _rc ] PPM with index (number) i, i ∈ [1, ..., N] to the output signal of the reference receiving channel M _tr .

2.9 Clause 2.8 of the calibration of the transmitting channels is performed for all transceiver modules from the composition of MLCAFAR.

As a result, data are generated on the deviation of the complex transmission coefficients of the emitting channels of the transceiver modules relative to the complex transmission coefficient of the radiation channel of the reference channel.

3. The calculation of the correction coefficients of the receiving channels in the "Receive" mode.

, i ∈ [1, …, 2N] для режима «Прием» по формуле:The calculation of the complex correction coefficient of the amplitude-phase characteristic of the receiving channel with the number j, j ∈ [1, ..., M _rc ] PPM with the index (number) i, i ∈ [1, ..., 2N] relative to the complex transmission coefficient of the receiving channel with the number mrc, mrc ∈ [1, ..., M _rc ] MRP with index (number)

, i ∈ [1, ..., 2N] for the “Reception” mode according to the formula:

для всех (i,

) ∈ [1, …, Mrc]. В этом случае расчет комплексного коэффициента коррекции амплитудно-фазовой характеристики передающих каналов с номером j, j ∈ [1, …, M_tr] ППМ с индексом (номером) i, i ∈ [1, …, 2N] относительно комплексного коэффициента передачи излучающего канала mtr, mtr ∈ [1, …,M_tr] ППМ с индексом (номером)

осуществляется по формуле:The control signal input nodes are performed with the same transmission characteristics, i.e.

for all (i,

) ∈ [1, ..., Mrc]. In this case, the calculation of the complex correction coefficient of the amplitude-phase characteristic of the transmitting channels with the number j, j ∈ [1, ..., M _tr ] PPM with the index (number) i, i ∈ [1, ..., 2N] relative to the complex transmission coefficient of the emitting channel mtr, mtr ∈ [1, ..., M _tr ] MRP with index (number)

carried out by the formula:

4. Determination of the differential difference in the transmission coefficients of the PPM receiving channels in the "Transmission" mode relative to the "Reception" mode.

,

вычисляется по формуле:The differential difference in the transmission coefficients of the paths of the receiving channel of the PPM number j with index (number) i when changing the connection scheme is equal to the ratio of the transmission coefficients of the paths of the receiving channel number j, j ∈ [1, ..., M _rc ] PPM with index (number), i, i ∈ [1, ..., 2N] to the complex coefficient of matching the transmission coefficients of the paths on the receive channel number mkr, mkr ∈ [1, ..., M _rc ] of the transceiver module with index (number)

,

calculated by the formula:

;

для всех i ∈ [1, …, 2N], (j,

) ∈ [1, …, M_rc], дифференциальная разница коэффициентов передачи трактов приемного канала рассчитывается по формуле:Provided that the control signal input nodes are made with the most identical transfer characteristics, i.e.

;

for all i ∈ [1, ..., 2N], (j,

) ∈ [1, ..., M _rc ], the differential difference between the transmission coefficients of the paths of the receiving channel is calculated by the formula:

5. Formation of correction coefficients for the parameters of transceiver modules MLCAFAR.

Paragraphs 1-3 are repeated to determine the correction coefficients of the MLAFAR PPM at given frequencies ƒ ₁ , ƒ ₂ , ..., ƒ _k .

As a result, for each frequency rating:

, i ∈ [1, …, 2N]:1) Comprehensive correction coefficients of the amplitude-phase characteristics of the receiving channels of the PMD with indices (numbers) i, i ∈ [1, ..., 2N], relative to the amplitude-phase characteristics of the receiving channel with the number mrc, mrc ∈ [1, ..., M _rc ] MRP with index (number)

, i ∈ [1, ..., 2N]:

:2) The complex coefficients of the correction of the amplitude-phase characteristics of the transmitting channels of the PPM with indices (numbers) i, i ∈ [1, ..., 2N] relative to the complex transmission coefficient of the transmitting channel mtr, j ∈ [1, ..., M _tr ], the PPM with the index (number)

:

,

3) The complex coefficients of the differential difference in the transmission coefficients of the paths along the receive channel number j, j ∈ [1, ..., M _rc ] MRP with index (number) i, i ∈ [1, 2, ..., 2N], relative to the complex coefficient of coefficient matching transmit paths on the receive channel number mkr, mkr ∈ [1, ..., M _rc ] MRP with index (number)

,

Calibration of MLCAFAR should be carried out with a repetition period T _K , which is determined by the time the parameters of MLCAFAR devices change. The value of T _K depends on the used elemental base, circuit design, etc., and is determined on the prototype of the product.

The present invention allows us to expand the scope of application of MLCAFAR in frequency, realizing the possibility of forming rays at frequencies whose frequency distance exceeds the working bands of the DAC and ADC, and the calibration device for receiving and transmitting channels MLCAFAR improves the accuracy and reliability of measurements of their complex transmission coefficients.

Claims (4)

1. A multi-beam digital active phased antenna array (MLCAFAR) containing a system of antenna emitters with orthogonal polarizations connected to N transceiver modules (PPM) connected to an amplitude-phase correction (ROS) system associated with a digital beamforming system (CDO) as well as a target designation device, a polarization control system and a synchronization system (SS), synchronizing the operation of a multi-beam digital active phased array antenna, characterized in that it further includes a calibration device for a multi-beam digital active phased antenna array for periodic calibration of the reception channels of the PPM by the control signal generated by the transmitting channel of the reference PPM and transmitting channels of the PPM by the control signal generated by the transmitting channels of the PPM, the amplitude-phase correction system is configured to correct the parameters of multi-channel receivers -transmission paths, and the system of digital chart formation is made with the possibility of independent control of directional diagrams signal reception and transmission, while the target designation device is connected to a digital beamforming system for reception and transmission, connected to the polarization driver of the polarization control system during transmission and adaptation to polarization during reception, while the transmission and reception of signals is carried out alternately at the carrier frequencies. 2. MLCAFAR according to claim 1, characterized in that each transceiver module contains the required number of digital-to-analog (DAC) for transmission and analog-to-digital (ADC) converters for reception, the number of which is determined by the number of generated beams at the transmit and receive frequencies , the frequency spacing between which exceeds the passband at the input of the DAC and ADC. 3. The MLCAFAR calibration device for calibrating the receiving channels of the transmitting and receiving modules according to the control signal transmitted along the MLCAFAR receiving paths containing the reference PPM, the control signal transmission path, the directional input device of the control signal and microwave switches, characterized in that the output of the transmitting channel of the reference module MRP through the switch for changing the direction of the control signal along the calibration path and the device for the non-directional input of the control signal into the receiving channel the first control signal is connected to the microwave selector switch for calibration, connected to the input of the non-directional input of the control signal through which the control signal is fed to the input of the receiving calibrated channel, while the direction of the control signal along the transmission path between the receiving channel of the reference PPM and the receiving channel of the calibrated MRP in the paths is the opposite, while the amount of attenuation of the control signal in the transmission path of the control signal between the receiving channels is constant, and the phase the flip changes the sign to the opposite, and then the deviations of the amplitude-phase characteristics of the receiving channel of the selected transceiver module from the amplitude-phase characteristics of the receiving channel of the reference transceiver module are determined by the signals at the outputs of the radio reception channels of the reference transceiver module , and based on the measurement results of these deviations, the differential difference of the transmit channel coefficient of the received channel of the selected transceiver module from transmission coefficient of the receiving channel of the reference transceiver module, while measuring the differential difference of the transmission coefficient of the receiving channel of the selected transceiver module relative to the transmission coefficient of the reception channel of the reference transceiver module is performed for two switching circuits of the selected transceiver module: receiving channels of the selected transceiver module the transmitting module is connected to the antenna element, and the receiving channels of the selected transceiver module are connected through the node omnidirectional about the input to the path of the control signal. 4. Calibration method MLCAFAR for calibrating the transmitting channels of the transmitting and receiving modules by the control signal transmitted along the receiving and transmitting paths of MLCAFAR, characterized in that when calibrating the transmitting channels of the transmitting and transmitting modules, the control signal generated by the transmitting channel of the reference transmitting and transmitting module, through the omnidirectional communication device is introduced into the receiving radio path of the reference transceiver module, and the control signal generated by the transmission channel of the selected transceiver module, through the omnidirectional communication device is inserted into the receiving radio path of the selected transceiver module, and then, by the signals at the outputs of the radio receiving channels of the reference transceiver module and the selected receiving channel of the transceiver module, the deviations of the amplitude-phase characteristics of the receiving channel of the selected transceiver module from amplitude-phase characteristics of the receiving channel of the reference transceiver module, and based on the measurement results, taking into account the differential difference in the coefficient receiving transmission channel and reference the selected transceiver modules, these deviations, calculates the differential gain difference of the selected transmission channel transceiver module on the gain of the transmitting reference channel transceiver module.

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