CN109787671B - Hybrid beam forming device and method - Google Patents
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Abstract
The invention discloses a special arrayed hybrid beam forming device, which solves the problem that the existing hybrid beam forming device is high in calculation complexity and poor in time-varying characteristic. The device comprises a set of N array element array antennas, and is divided into M L array element sub-arrays according to a special arrangement mode, and each sub-array is correspondingly provided with a radio frequency-intermediate frequency-baseband signal processing channel. The L array element receiving signals of each subarray are subjected to radio frequency phase shifting and are combined into a signal, the signal is sent to a channel corresponding to the signal, M baseband complex signals are output to be subjected to adaptive digital beam forming, and weight vectors of the signals are subjected to adaptive iterative optimization, so that the signals are used for digital beam forming and simultaneously used for calculating the optimal phase shifting value of each radio frequency phase shifter in the subarray, and mixed beam forming is achieved. The gain improvement amount of the formed beam is approximately equal to N times, the hardware complexity of the beam is reduced by L times compared with the full-digital beam forming, and the calculation complexity of the beam is reduced by many times compared with the conventional hybrid beam forming; the method has important practical value in broadband satellite communication and ground-to-air communication.
Description
Technical Field
The invention belongs to the technical field of communication, relates to large-scale array antenna received signal processing, and particularly relates to a hybrid beam forming method based on a special array layout mode and sub-array grouping, which is applied to a receiving and transmitting antenna system forming a large-scale array.
Background
With the development of array antenna technology, large-scale array antennas capable of obtaining high gain have received much attention, however, with the expansion of the scale of array antennas, the hardware equipment complexity of pure digital beam forming methods may be too high to be acceptable, and hybrid beam forming is an effective method for solving this problem.
The Chinese patent of invention (application publication No. CN 105206934A) discloses a phased array receiving antenna system and an operation method thereof, the phased array receiving antenna system comprises a plurality of signal receiving units for receiving signals, a power combiner connected with the plurality of signal receiving units, a power calculating unit connected with the power combiner for calculating an output power value, and an adaptive beam forming module connected with the power calculating unit, wherein a phase shift value calculated by the adaptive beam forming module is input to the signal receiving units, so that an antenna beam points to an incoming wave direction. The phased array receiving antenna system provided by the invention solves the problem that the phased array antenna needs to work in combination with a receiver through the self-adaptive DOA estimation and wave beam output functions, and has the advantages of independent operation from the receiver and low cost. However, only the power value after the power combiner can be obtained, but the original receiving signal cannot be obtained, and when the array scale is enlarged, the parallel random gradient descent method has the advantages of high randomness of convergence performance and low DOA estimation precision.
In the document, "research and design of wireless communication system using intelligent antenna array" (doctor's academic paper author: Chenjie, university of electronic technology, west ampere) a combined structure and algorithm suitable for digital microwave beam switching and digital beam synthesis of planar antenna array is proposed, the radio frequency signal completes the microwave beam switching of pitching plane through digital microwave phase shift system, and the digital signal processing technology is adopted to form horizontal digital beam. The method combines microwave beam switching and digital beam synthesis, reduces hardware cost, is only suitable for a planar array, carries out beam forming on a pitch angle and a direction angle respectively, and has higher calculation complexity.
The hybrid beam forming method has the advantages of obtaining higher gain by using fewer radio frequency channels and greatly reducing the hardware cost, is not only suitable for large-scale array antennas, but also has important practical value for reducing the cost of array antenna systems with small scale. For example: the antenna is used for realizing a communication-in-motion user antenna in broadband satellite mobile communication or a ground station antenna which is used for rapidly tracking a plurality of aircraft targets in broadband ground-air communication.
How to design a hybrid beam forming system structure scheme is a critical problem of effectively reducing the computational complexity on the basis of controlling the hardware cost, and is also a main effort target of the invention.
Disclosure of Invention
The invention provides a hybrid beam forming device and a method based on a special array layout mode and a sub-array grouping method; the analog beamforming weight can be obtained by simple power calculation of the digital beamforming weight according to the relative position of the array elements, complete array processing gain can be obtained by beamforming, the calculation complexity is low, the method is suitable for various types of array models, and the main algorithm is the steepest gradient climbing self-adaptive iterative algorithm.
1. And (3) receiving end hybrid beam forming:
the receiving end of the hybrid beam forming device comprises a set of array antenna with N array elements, N radio frequency phase shifters, M radio frequency, intermediate frequency and baseband signal processing channels, M orthogonal down converters for generating baseband complex digital signals, a sampling quantization signal processing unit and a self-adaptive beam forming calculation unit.
The signal processing method and the steps of the receiving end hybrid beam forming are as follows:
(1-1) the N array element array antenna is divided into M sub-arrays, L array elements of each sub-array receive far-field signals respectively.
And (1-2) after signals received by the N array elements pass through the corresponding radio frequency phase shifters, the signals received by the L array elements of the same sub-array are merged and transmitted to a radio frequency receiving channel.
(1-3) the radio frequency signals obtained by the M sub-arrays correspond to M radio frequency, intermediate frequency and baseband signal processing channels, and are respectively sampled and quantized by an orthogonal down converter and an analog-to-digital converter to obtain M baseband complex digital signals X (k) ([ X ])1(k),X2(k)...,XM(k)]TAnd serves as an input signal for the adaptive beamforming calculation unit.
(1-4) the adaptive beamforming calculation unit inputs information according to the M dimensionNumber, for digital beamforming weight vector w (k) ═ w1(k),w2(k),…,wM(k)]Performing iterative update to obtain updated digital beam forming weight vector W (k +1) [ W ]1(k+1),w2(k+1),…,wM(k+1)]For synthesizing the beamformed output signals.
(1-5) combining with special array distribution rule, utilizing updated digital beam forming weight vector W (k +1) to simulate beam forming weight vector of L-dimensional sub-array
Updating, and correspondingly changing the phase shift parameters of the radio frequency phase shifter, wherein the analog beam forming weights of the corresponding positions of each sub array are the same.
2. And (3) transmitting end hybrid beam forming:
the transmitting end and the receiving end of the hybrid beam forming device share a set of array antenna with N array elements and N corresponding radio frequency phase shifters through a duplex coupler; the transmitting end also comprises M transmitting signal processing channels.
The signal processing method and the steps of the mixed beam forming at the transmitting end are as follows:
(2-1) multiplying the M-dimensional digital beam forming weight vector W (k) obtained by the self-adaptive iteration of the receiving end with a baseband complex signal u (k) to be sent to obtain an M-dimensional baseband complex signal V (k) ═ W (k)HU (k), wherein v (k) is represented by v (k) ═ v1(k),v2(k)...,vM(k)]T。
(2-2) converting vector v (k) to [ v [ ]1(k),v2(k)...,vM(k)]The M components are respectively sent to the input ends of M sending signal processing channels, and after each channel carries out quadrature carrier modulation on the baseband complex signal, the baseband complex signal is processed through a 1: l power dividers output L radio frequency signals respectively, and the total number of the radio frequency signals is N.
(2-3) the N radio frequency signals are connected with the radio frequency phase shifter through N duplex couplers and are transmitted by N antenna array elements; wherein the phase values in the radio frequency phase shifter have been formed during reception.
3. Special layout method of antenna array
The array antenna array layout mode and the sub-array grouping method in the device have the following characteristics:
(3-1) the number of the sub-arrays is not less than the number of the array elements in each sub-array;
(3-2) the number of each sub-array element is the same and the layout of the array elements is the same;
and (3-3) the layout of the center point of each subarray is similar to the layout of each array element in the subarray.
4. Method for realizing iterative updating of two beam forming parameters by using array distribution characteristics
The beam forming method of the invention is a mixed beam forming method based on a special array layout mode and a sub-array grouping method, and the signal processing steps are as follows:
(4-1) receiving signals by the array antenna:
assuming that an incident signal is a far-field narrow-band signal, N array elements of the array antenna respectively receive the incident signal, the received signal of each array element generates relative delay due to wave path difference, and the array received signal is X (t);
(4-2) initializing iteration ordinal number, analog beam forming weight and digital beam forming weight:
(4-2a) iteration ordinal initialization, k being 1;
(4-2b) setting the initial beam forming weight as the incoming wave direction phidAt 90 DEG, the vector value is oriented, i.e.
The initial L-dimensional sub-array analog beamforming weight vector is:
the initial M-dimensional digital beamforming weight vector is:
W(k)＝[w1(k),w2(k),…,wM(k)]|k＝1＝[1,1,…,1]；
the antenna array antenna comprises an array antenna, a plurality of antenna elements and a plurality of antenna elements, wherein N is ML, N is the number of the array antenna elements, M is the number of the array antenna radio frequency links, namely the number of sub-arrays, and L is the number of the array elements in the sub-arrays; the analog beam forming weights of the corresponding positions of each subarray are consistent; setting N analog phase shifter parameters according to the analog beam forming weight vector;
(4-3) obtaining a digital sampling signal:
sampling the sub-array receiving signals subjected to analog phase shift summation through the AD converters corresponding to the sub-arrays to obtain a digital sampling signal vector Xd(k)；
(4-4) calculating array output:
the array output is that each subarray digital sampling signal is weighted and summed according to the digital beam forming weight, namely the array output is: y (k) w (k) X (k), where y (k) is the hybrid beamforming output, w (k) is the digital beamforming weight vector, X (k) is the digital beamforming weight vectord(k) Is a vector of digitally sampled signals;
(4-5) updating the digital beam forming weight value:
judging whether an iteration cut-off condition is met, if so, making W (k +1) W (k), otherwise, iteratively updating the digital beam forming weight by adopting an adaptive digital beam forming method with amplitude constraint; obtaining updated digital beam forming weight W (k +1) [ W ]1(k+1),w2(k+1),…,wM(k+1)]Wherein | wi(k+1)|＝1，i＝1:M；
(4-6) updating the analog beam forming weight:
determining the relation between the analog beam forming weight and the digital beam forming weight according to the array layout, and calculating the analog beam forming weight according to the updated digital beam forming weight
Wherein d issubRepresenting the spacing of the elements of the sub-array, dDRepresenting the center point interval of each subarray, and correspondingly changing the phase shift parameters of the radio frequency phase shifter;
(4-7) changing the iteration number k to k +1, and turning to the step (4-3).
Compared with the prior art, the invention has the following advantages:
1. gains close to pure digital beamforming can be achieved: the hybrid beam forming method adopted by the invention can obtain gain close to pure digital beam forming, and the beam main lobe can be accurately aligned to an incident signal.
2. The hardware cost is low: the invention adopts the mode of combining analog beam forming and digital beam forming, only M radio frequency links and N radio frequency phase shifters are needed, the number of radio frequency and baseband signal processing channels including the number of AD converters is reduced, and the hardware cost is reduced.
3. The computational complexity is low: the invention can know the relation between the analog beam forming weight vector and the digital beam forming weight vector according to the array element layout, can calculate the analog beam forming weight vector by the digital beam forming weight vector only by simple power operation, and the power operation can be realized by a table look-up method when hardware is realized, so the calculation complexity is equivalent to that of the M array element digital beam forming method.
4. The method is suitable for various types of array element models: the hybrid beam forming method can be applied to various array models such as a uniform linear array model, an area array model, a circular array model and the like, and only the array layout accords with the characteristics.
Drawings
FIG. 1 is a schematic view of the apparatus of the present invention
FIG. 2 is a schematic diagram of an N-array-element uniform linear array model
FIG. 3 is a schematic diagram of a uniform circular array model with N array elements
FIG. 4 is a flow chart of the method of the present invention
Detailed Description
The present invention is described in further detail below with reference to the attached drawings.
Referring to fig. 1, a receiving end of the hybrid beam forming apparatus used in the present invention includes a set of array antenna with N array elements, N rf phase shifters, M rf, if, and baseband signal processing channels, M quadrature downconverters, a sampling quantization signal processing unit, and an adaptive beam forming calculation unit. The signal processing steps are as follows:
the method comprises the following steps: n array element array antennas are divided into M sub-arrays, L array elements of each sub-array, and N array elements receive far-field signals respectively.
Step two: after signals received by the N array elements pass through the corresponding radio frequency phase shifters, L array element receiving signals of the same sub-array are merged and transmitted to a radio frequency receiving channel.
Step three: the radio frequency signals obtained by the M sub-arrays correspond to M radio frequency, intermediate frequency and baseband signal processing channels, sampling and quantization are carried out through an orthogonal down converter and an analog-to-digital converter respectively, and M baseband complex digital signals X (k) are obtained and serve as input signals of the self-adaptive beam forming computing unit.
Step four: the adaptive beamforming calculation unit iteratively updates the M-dimensional digital beamforming weight vector W (k) according to the M-dimensional input signal to obtain an updated digital beamforming weight vector W (k +1) for synthesizing a beamforming output signal.
Step five: and (3) updating the L-dimensional sub-array analog beamforming weight vector F (k) by using the updated digital beamforming weight vector W (k +1) in combination with a special array arrangement rule, and correspondingly changing the phase shift parameters of the radio frequency phase shifter, wherein the analog beamforming weights at the corresponding positions of the sub-arrays are the same.
A transmitting end and a receiving end of the hybrid beam forming device share a set of array antenna with N array elements and N corresponding radio frequency phase shifters through a duplex coupler. The sending end also comprises M sending signal processing channels, and the signal processing process can be divided into the following steps:
the method comprises the following steps: multiplying an M-dimensional digital beam forming weight vector W (k) obtained by self-adaptive iteration of a receiving end by a baseband complex signal u (k) to be transmitted to obtain an M-dimensional baseband complex signal V (k) ═ W (k)H·u(k)。
Step two: respectively sending M components of the vector V (k) to input ends of M sending signal processing channels, carrying out quadrature carrier modulation on baseband complex signals by each channel, and carrying out 1: l power dividers respectively output L radio frequency signals, and N radio frequency signals are total.
Step three: n radio frequency signals are connected with a radio frequency phase shifter through N duplex couplers and are transmitted by N antenna array elements; wherein the phase values in the radio frequency phase shifter have been formed during reception.
The array layout mode and the sub-array grouping method have the following characteristics:
a) the number of the sub-arrays is not less than the number of the array elements in each sub-array
b) The number of each sub-array element is the same and the layout of the array elements is the same
c) The layout of the center point of each subarray is similar to the layout of each array element in the subarray
The array layout and sub-array grouping method of the present invention are further described below by two embodiments with reference to the accompanying drawings.
Example 1: the N array element uniform linear arrays are divided into M sub-arrays, each sub-array comprises L array elements, L is less than or equal to M, and a schematic diagram of an array model is shown in an attached figure 2. Where d is the array element spacing, typically half the wavelength of the incident signal. M sub-arrays in the model are equivalent to L array element uniform linear arrays with M array element intervals of M times d, and subarray central points can be equivalent to M array element uniform linear arrays with array element intervals of d. According to the calculation formula of the steering vector of the array antenna, the sub-array simulation beam forming weight vector F belongs to CL×1And digital beam forming weight vector W is belonged to CM×1The relationship of (1) is:
example 2: for the N-array element circular array model, the N-array element circular array model is divided into M sub-arrays, the sub-arrays are M-array element circular arrays (N ═ M × M), and a schematic diagram of the array model is shown in fig. 3, taking 25 array element circular arrays and 5 RF links as examples. The array elements with the same marking patterns are the same subarray, the equivalent is a five-array-element circular array with five array elements with 3-half-wavelength intervals, and the center point of the five-array-element circular array is equivalent to a five-array-element circular array with one array element with half-wavelength intervals. By using an array antenna steering vector calculation formula, under the array model, a subarray simulation beam forming weight vector F belongs to CM×1And digital beam forming weight vector W is belonged to CM×1The relationship of (1) is:
referring to fig. 3, the hybrid beamforming method based on the special array layout and the sub-array grouping method of the present invention includes the following steps:
step one, an array antenna receives a signal.
Assuming that the incident signal is a far-field narrowband signal, each array element of the array antenna receives the incident signal, and the received signal of each array element generates relative delay due to the wave path difference, the array received signal x (t) can be expressed as:
X(t)＝a(φd)s(t)+n(t)
wherein X (t) e CN×1A received signal vector, a (phi), representing N array elementsd)∈CN×1Representing the steering vector, phi, of the array antennadRepresenting the incoming wave direction of the incident signal, s (t) representing the far-field narrow-band incident signal, n (t) epsilon CN×1And the noise vectors of the N array elements are represented, and the noise of each array element is independent Gaussian white noise.
And step two, initializing the iteration ordinal number, the analog beam forming weight and the digital beam forming weight.
Initializing an iteration ordinal number, and enabling k to be 1;
setting initial beam forming weight as coming wave direction phidThe steering vector value when being 90 °, namely:
the initial L-dimensional sub-array analog beamforming weight vector is:
the initial M-dimensional digital beamforming weight vector is:
W(k)＝[w1(k),w2(k),…,wM(k)]|k＝1＝[1,1,…,1]；
the antenna array antenna comprises an array antenna, a plurality of antenna elements and a plurality of antenna elements, wherein N is ML, N is the number of the array antenna elements, M is the number of the array antenna radio frequency links, namely the number of sub-arrays, and L is the number of the array elements in the sub; the analog beam forming weights of the corresponding positions of each subarray are consistent;
setting N radio frequency phase shifter parameters according to the analog beam forming weight vector;
and step three, obtaining a digital sampling signal.
Sampling the sub-array receiving signals subjected to analog phase shift summation through the AD converters corresponding to the sub-arrays to obtain a digital sampling signal vector Xd(k)＝[Xd1(k),Xd2(k),...,XdM(k)]T。
And step four, calculating array output.
The array output is that each subarray digital sampling signal is weighted and summed according to the digital beam forming weight, namely the array output is: y (k) ═ w (k) · Xd(k) Where y (k) is the hybrid beamforming output, W (k) is a 1 xM dimensional digital beamforming weight vector, Xd(k) Is an M × 1-dimensional digitally sampled signal vector.
And step five, updating the digital beam forming weight.
Judging whether an iteration cut-off condition is met, if so, enabling W (k +1) to be W (k), otherwise, adopting an adaptive digital beam forming method with amplitude constraint to iteratively update the digital beam forming weight value, and obtaining the updated digital beam forming weight value W (k +1) to be [ W (k) ]1(k+1),w2(k+1),…,wM(k+1)]Wherein | wi(k+1)|＝1，i＝1:M；
And step six, updating the analog beam forming weight.
Determining the relation between the analog beam forming weight and the digital beam forming weight according to the array layout, and calculating the analog beam forming weight according to the updated digital beam forming weight
Wherein d issubRepresenting the spacing of the elements of the sub-array, dDAnd representing the center point interval of each subarray, and correspondingly changing the phase shift parameters of the radio frequency phase shifter.
And step seven, changing the iteration ordinal number k to k +1, and turning to the step three.
Claims (2)
1. A hybrid beamforming apparatus, characterized by:
1) the receiving end comprises a set of array antenna with N array elements, N radio frequency phase shifters, M radio frequency, intermediate frequency and baseband signal processing channels, M orthogonal down converters for generating baseband complex digital signals, a sampling quantization signal processing unit and a self-adaptive beam forming computing unit; dividing N antenna array elements and phase shifters into M antenna sub-arrays (N is ML) with L array elements and phase shifters, receiving signals of L array elements of each sub-array, combining the signals into one signal after radio frequency phase shifting, sending the signal to one of M radio frequency, intermediate frequency and baseband signal processing channels, and obtaining M baseband complex digital signals by sampling and quantizing an orthogonal down converter and an analog-to-digital converter; the signal processing steps are as follows:
(1a) the M baseband complex signals thus obtained are represented as a vector X (k) ═ X1(k),X2(k)...,XM(k)]TSending to an adaptive beam forming computing unit; wherein XM(k) Referring to a baseband complex signal vector of the Mth subarray of the kth iteration;
(1b) weight vector w (k) for digital beamforming in adaptive beamforming calculation unit1(k),w2(k),…,wM(k)]Carrying out self-adaptive iterative updating; w is aM(k) A digital beamforming weight vector referring to the Mth subarray of the kth iteration;
(1c) in the unit, L radio frequency shift phase values, namely vectors, used for each subarray analog beam forming are calculated by using the obtained weight vectors W (k) and an array arrangement rule
L elements of (a);
the analog beam forming weight vector of the Lth array element of the kth iteration of each subarray is referred to; the layout mode and the sub-array grouping method of the N-array element array antenna array are as follows:
(1) the number of the subarrays is not less than the number of the array elements in the subarrays, namely M is more than or equal to L;
(2) the number L of each sub-array element is the same, and the array element layout is the same;
(3) the layout of the center point of each subarray and the layout of each array element in each subarray are similar polygons;
(1d) hybrid beamforming is performed in this unit: sending the L phase values of F (k) to N radio frequency phase shifters according to an array layout mode, multiplying a weight vector W (k) by receiving signals X (k) obtained by M channels to obtain output signals y (k) W (k) X (k) of mixed beam forming;
2) the transmitting end and the receiving end share a set of array antenna with N array elements and N corresponding radio frequency phase shifters through a duplex coupler; the sending end also comprises M sending signal processing channels, and after each channel carries out quadrature carrier modulation on the baseband complex signal, the sending end is processed by the following steps of 1: l power dividers, each of which outputs L radio frequency signals; the output signal is connected to N radio frequency phase shifters through a duplex coupler and is transmitted by N array elements; the signal processing steps of the hybrid beamforming at the transmitting end are as follows:
(2a) multiplying a weight vector W (k) obtained by self-adaptive iteration of a receiving end by a baseband complex signal u (k) to be transmitted to obtain V (k) ═ W (k)HU (k), wherein v (k) is represented by v (k) ═ v1(k),v2(k)...,vM(k)]；vM(k) The weighted baseband complex signal vector of the Mth subarray of the kth iteration is referred to;
(2b) converting vector V (k) to [ v [ ]1(k),v2(k)...,vM(k)]To the input of M transmit signal processing channels, respectively, each channel being passed through 1: l power dividers are used for outputting L radio frequency signals respectively, N radio frequency signals in total are connected with the radio frequency phase shifter through N duplex couplers and are transmitted by N antenna array elements; wherein the phase values in the radio frequency phase shifter have been formed during reception.
2. A hybrid beam forming method based on a hybrid beam forming device comprises the following steps:
(1) beamforming weight vector initialization:
initializing an L-dimensional sub-array analog beamforming weight vector:
initialization of phase shift vectors for M-dimensional digital beamforming:
W(k)＝[w1(k),w2(k),…,wM(k)]|k＝1＝[1,1,…,1]；
the antenna array antenna comprises an array antenna, a plurality of antenna elements and a plurality of antenna elements, wherein N is ML, N is the number of the array antenna elements, M is the number of the array antenna radio frequency links, namely the number of sub-arrays, and L is the number of the array elements in the sub-arrays; the analog beam forming weights of the corresponding positions of each subarray are consistent;
(2) at time k, the quantized signal for the input M samples constitutes a received signal vector:
X(k)＝[X1(k),X2(k)...,XM(k)]T
the corresponding output signal y (k) ═ w (k) · x (k);
(3) iterative acquisition of updated digital beamforming phase-shift vector using adaptive digital beamforming with amplitude constraint
W(k+1)＝[w1(k+1),w2(k+1),…,wM(k+1)]
Wherein | wi(k+1)|＝1，i＝1:M；
(4) Calculating a weight vector F (k +1) of the updated analog beam forming according to the array layout mode and the updated digital beam forming phase shift vector W (k + 1):
wherein d issubRepresenting the spacing of the elements of the sub-array, dDRepresenting the center point interval of each subarray, and correspondingly changing the phase shift parameters of the radio frequency phase shifter;
(5) the iteration ordinal is updated, i.e., let k → k +1 go back to (2).
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| CN111628806B (en) * | 2020-05-12 | 2021-03-09 | 鹏城实验室 | Antenna beam pointing regulation and control method, device and readable storage medium |
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| CN113572503B (en) * | 2021-06-29 | 2022-09-02 | 西安电子科技大学 | Low-complexity improved mixed beam forming method based on GP |
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Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101867402A (en) * | 2010-05-04 | 2010-10-20 | 西安交通大学 | MIMO system and application method thereof for adaptive antenna selection |
| CN102082591A (en) * | 2010-12-13 | 2011-06-01 | 武汉滨湖电子有限责任公司 | Method for forming circular array antenna digital wave beams |
| CN107947838A (en) * | 2017-10-12 | 2018-04-20 | 北京邮电大学 | The mixed-beam figuration framework and encoder design of a kind of Hybrid connections |
| CN108633043A (en) * | 2017-03-24 | 2018-10-09 | 中兴通讯股份有限公司 | The processing method and processing device that wave beam restores |
-
2019
- 2019-03-07 CN CN201910173557.8A patent/CN109787671B/en active Active
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101867402A (en) * | 2010-05-04 | 2010-10-20 | 西安交通大学 | MIMO system and application method thereof for adaptive antenna selection |
| CN102082591A (en) * | 2010-12-13 | 2011-06-01 | 武汉滨湖电子有限责任公司 | Method for forming circular array antenna digital wave beams |
| CN108633043A (en) * | 2017-03-24 | 2018-10-09 | 中兴通讯股份有限公司 | The processing method and processing device that wave beam restores |
| CN107947838A (en) * | 2017-10-12 | 2018-04-20 | 北京邮电大学 | The mixed-beam figuration framework and encoder design of a kind of Hybrid connections |
Non-Patent Citations (2)
| Title |
|---|
| "A Novel Hybrid CFO Estimation Scheme for UFMC-Based Systems";Bin Tian 等;《IEEE COMMUNICATIONS LETTERS》;20170214;全文 * |
| "基于多波束GEO卫星的宽带移动通信系统";田斌等;《系统工程与电子技术》;20150916;全文 * |
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