JPH11215885A - Supply voltage variable current mode pwm driving device - Google Patents
Supply voltage variable current mode pwm driving deviceInfo
- Publication number
- JPH11215885A JPH11215885A JP10300544A JP30054498A JPH11215885A JP H11215885 A JPH11215885 A JP H11215885A JP 10300544 A JP10300544 A JP 10300544A JP 30054498 A JP30054498 A JP 30054498A JP H11215885 A JPH11215885 A JP H11215885A
- Authority
- JP
- Japan
- Prior art keywords
- current
- voltage
- resistor
- driving device
- amplifier
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
- H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
- H02P25/032—Reciprocating, oscillating or vibrating motors
- H02P25/034—Voice coil motors
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P7/00—Arrangements for regulating or controlling the speed or torque of electric DC motors
- H02P7/03—Arrangements for regulating or controlling the speed or torque of electric DC motors for controlling the direction of rotation of DC motors
- H02P7/04—Arrangements for regulating or controlling the speed or torque of electric DC motors for controlling the direction of rotation of DC motors by means of a H-bridge circuit
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Electronic Switches (AREA)
- Control Of Linear Motors (AREA)
Abstract
Description
【０００１】[0001]
【発明の属する技術分野】本発明は、集積回路のサイズ
や供給電圧を変更可能な電流モードＰＷＭ駆動装置に関
する。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a current mode PWM drive device capable of changing the size and supply voltage of an integrated circuit.
【０００２】[0002]
【従来の技術】バッテリ駆動式の携帯機器に用いられる
フレキシブルディスク、ＣＤ−ＲＯＭ、ＰＣ、ＣＤリー
ダなどの大容量記憶装置や、その他同様の回転機構を持
つ装置には、完全集積化された駆動装置により電気的に
切り換えられる電気モータが使われている。2. Description of the Related Art Fully integrated drive devices are used in large-capacity storage devices such as flexible disks, CD-ROMs, PCs, and CD readers used in battery-powered portable devices, and other devices having similar rotation mechanisms. Electric motors are used which are electrically switched by the device.
【０００３】図１は、一般的な電流モードのパルス幅変
調（ＰＷＭ）切換駆動装置の回路図であり、ボイスコイ
ルモータ（ＶＣＭ）と呼ばれるアクチュエータなどの外
部負荷を駆動するものである。FIG. 1 is a circuit diagram of a general current-mode pulse width modulation (PWM) switching driving device for driving an external load such as an actuator called a voice coil motor (VCM).
【０００４】電流制御ループは加算ノードＡで閉状態と
なっており、ノードＡでは、抵抗器Ｒ１を経て制御電圧
Ｖｄａｃにより印加される電流と、抵抗器Ｒ２を経て電
流検知部（Current Sense）を構成する電流センス増幅
器の出力電圧Ｖｓｅｎｓｅにより印加される電流とのバ
ランス操作が行われる。そのために、電流制御ループは
ノードＡの電圧と基準電圧Ｖｒｅｆとの差の誤差増幅器
を備えている。The current control loop is closed at the summing node A. At the node A, the current applied by the control voltage Vdac via the resistor R1 and the current sensing unit (Current Sense) via the resistor R2. A balance operation with the current applied by the output voltage Vsense of the current sense amplifier is performed. To this end, the current control loop comprises an error amplifier for the difference between the voltage at node A and the reference voltage Vref.
【０００５】電流制御ループにおけるフィードバック電
圧は、負荷ＶＣＭに直列に接続された検知抵抗器Ｒ３に
よる電圧降下に起因するものである。[0005] The feedback voltage in the current control loop is due to the voltage drop across the sensing resistor R3 connected in series with the load VCM.
【０００６】このような装置において、抵抗器Ｒ３の端
子間の電位差Ｖｉｎ１−Ｖｉｎ２が基準電圧Ｖｒｅｆと
同じである場合は、抵抗器ＲａとＲｂにほとんど電流が
流れないため、抵抗比率Ｒａ／Ｒａ’とＲｂ／Ｒｂ’間
の不一致による制御装置の検知精度低下は起こらない。In such a device, when the potential difference Vin1-Vin2 between the terminals of the resistor R3 is equal to the reference voltage Vref, almost no current flows through the resistors Ra and Rb, so that the resistance ratio Ra / Ra '. The detection accuracy of the control device does not decrease due to the mismatch between Rb and Rb / Rb '.
【０００７】しかし、検知抵抗器Ｒ３の端子間の電位差
が基準電圧Ｖｒｅｆと大きく異なる場合には、抵抗器Ｒ
ａとＲｂに電流が大きく流れるため、抵抗比率Ｒａ／Ｒ
ａ’とＲｂ／Ｒｂ’間の不一致により検知精度の低下が
起こる。However, if the potential difference between the terminals of the detection resistor R3 is significantly different from the reference voltage Vref, the resistor R3
a and Rb have a large current, so that the resistance ratio Ra / R
Mismatch between a ′ and Rb / Rb ′ causes a decrease in detection accuracy.
【０００８】図１に示す装置において、モータの巻線
は、シングルブリッジ部からの通常１２Ｖである供給電
圧で動作し、同様に制御ループも１２Ｖを供給されて動
作する。電流センス増幅器は、共通モードレンジ０〜１
２Ｖの信号を入力して、その供給電圧の半分を出力する
ようになっている。In the apparatus shown in FIG. 1, the windings of the motor operate at a supply voltage of typically 12 V from a single bridge section, and the control loop also operates with 12 V supplied. The current sense amplifier has common mode ranges 0-1.
A signal of 2 V is input, and half of the supply voltage is output.
【０００９】電流センス増幅器は、フィードバック演算
増幅器ＯＰを使って実現できる。この増幅器は、２入力
の差信号を１出力の出力信号Ｖｓｅｎｓｅへ変換する
が、その結果、基準電圧Ｖｒｅｆに対する出力オフセッ
トの問題が発生する。このような出力オフセットは、抵
抗値の不一致によりもたらされる。The current sense amplifier can be realized using a feedback operational amplifier OP. This amplifier converts a two-input difference signal into a one-output output signal Vsense. As a result, an output offset problem with respect to the reference voltage Vref occurs. Such an output offset is caused by a mismatch in resistance values.
【００１０】ここで、プラス端子における電圧をＶ＋と
すると、抵抗器Ｒｂの電流は下記のようになる。Here, assuming that the voltage at the plus terminal is V + , the current of the resistor Rb is as follows.
【数１】Ｉ＝（Ｖ＋−Ｖｒｅｆ）／ＲｂI = (V + -Vref) / Rb
【００１１】オフセットのない演算増幅器を使った場
合、マイナス端子における電圧も同じである。差入力信
号がないと、抵抗Ｒａ、Ｒａ’を流れる電流は同じとな
るので、出力電圧が下記のように示せる。When an operational amplifier without offset is used, the voltage at the minus terminal is the same. Without the difference input signal, the currents flowing through the resistors Ra and Ra 'are the same, so that the output voltage can be expressed as follows.
【数２】Ｖｏ＝Ｖ−−Ｉ×Ｒｂ’＝Ｖ＋−（Ｖ＋−Ｖｒ
ｅｆ）×（Ｒｂ’／Ｒｂ）Vo = V −− I × Rb ′ = V + − (V + −Vr)
ef) × (Rb ′ / Rb)
【００１２】抵抗値が完全に一致する場合には（Ｒｂ＝
Ｒｂ’）、出力電圧は基準電圧と全く同じになる。抵抗
値が一致しない場合には（Ｒｂ＝Ｒ、Ｒｂ’＝Ｒ＋△
Ｒ）、出力電圧は下記のようになる。When the resistance values completely match (Rb =
Rb ′), the output voltage becomes exactly the same as the reference voltage. If the resistance values do not match (Rb = R, Rb ′ = R + △
R), the output voltage is as follows.
【数３】Ｖｏ＝Ｖ−−Ｉ×Ｒｂ’＝Ｖ＋−（Ｖ＋−Ｖｒ
ｅｆ）×（１＋△Ｒ／Ｒ）Vo = V −− I × Rb ′ = V + − (V + −Vr
ef) × (1 + △ R / R)
【００１３】抵抗値のばらつきが１％以内で、ブリッジ
端子での共通モード信号と基準電圧との差が６Ｖである
ような最適例の場合、電圧Ｖｓｅｎｓｅのオフセット値
は約６０ｍＶとなる。In an optimal example in which the variation of the resistance value is within 1% and the difference between the common mode signal at the bridge terminal and the reference voltage is 6 V, the offset value of the voltage Vsense is about 60 mV.
【００１４】バッテリ駆動式機器の集積化装置の消費電
力削減やサイズ縮小には、装置全体の小型化と、供給電
圧を小さくすることが必要である。In order to reduce the power consumption and size of an integrated device of a battery-driven device, it is necessary to reduce the size of the entire device and the supply voltage.
【００１５】[0015]
【発明が解決しようとする課題】しかし小型化により、
電流センス増幅器の入力端における差電圧と基準電圧Ｖ
ｒｅｆとのレベル差が強調されることになり、図１のよ
うな一般的な制御装置ではブリッジ部での共通モード信
号と基準電圧との差が大きくなるため精度が低くなる。However, due to miniaturization,
The difference voltage at the input of the current sense amplifier and the reference voltage V
The level difference from ref is emphasized, and in a general control device as shown in FIG. 1, the difference between the common mode signal in the bridge section and the reference voltage increases, so that the accuracy decreases.
【００１６】本発明は上記の問題に鑑みて、小型化する
さいの不一致の問題点に対する効果的な電流モードＰＷ
Ｍ駆動装置を提案する。In view of the above problems, the present invention provides an effective current mode PW for solving the problem of inconsistency in miniaturization.
We propose an M drive.
【００１７】[0017]
【課題を解決するための手段】本発明によれば、１対の
相補制御信号で制御されるスイッチによりキャパシタを
操作し、バッファおよび電荷転送回路として動作する演
算増幅器と、サンプルホールド出力ステージと、から成
る切換式キャパシタ増幅器を電流センス増幅器として利
用することにより注目すべき結果が得られた。According to the present invention, an operational amplifier operates as a buffer and a charge transfer circuit by operating a capacitor by a switch controlled by a pair of complementary control signals, a sample and hold output stage, A remarkable result has been obtained by using a switched capacitor amplifier consisting of
【００１８】このような電流モードＰＷＭ駆動装置の構
成は、制御電圧（Ｖｄａｃ）により第１抵抗器（Ｒ１）
経由で印加される第１電流および電流検知抵抗器（Ｒ
３）の電圧降下分を入力とする電流センス増幅器（Curr
ent Sense）の出力電圧（Ｖｓｅｎｓｅ）により第２抵
抗器（Ｒ２）経由で印加される第２電流のバランスをと
る入力ノード（Ａ）の電圧と、基準電圧（Ｖｒｅｆ）と
を比較する誤差増幅器（Error Amplifier）の、前記入
力ノード（Ａ）で閉状態となる制御ループを備え、前記
基準電圧（Ｖｒｅｆ）が、前記電流検知抵抗器（Ｒ３）
による電圧降下量よりも小さい電流モードＰＷＭ駆動装
置であって、前記電流センス増幅器が、１対の相補制御
信号（Φ１、Φ２）により制御されるスイッチ（ｓｗ
Ａ、ｓｗＢ、ｓｗＣ、ｓｗ１）により、バッファ又は電
荷転送回路として動作する演算増幅器（ＯＰ）と、サン
プルホールド出力ステージとから構成される。The configuration of such a current mode PWM driving device is such that the first resistor (R1) is controlled by the control voltage (Vdac).
A first current and a current sensing resistor (R
3) Current sense amplifier (Curr)
ent Sense) and an error amplifier (Vref) that compares a voltage at an input node (A) that balances a second current applied through a second resistor (R2) with a reference voltage (Vref). Error Amplifier), the control loop being closed at the input node (A), wherein the reference voltage (Vref) is set to the current detection resistor (R3).
Wherein the current sense amplifier is controlled by a pair of complementary control signals (Φ1, Φ2).
A, swB, swC, sw1), an operational amplifier (OP) that operates as a buffer or a charge transfer circuit, and a sample-and-hold output stage.
【００１９】本装置はより簡単に制御できるため、切換
遷移時から適切な時間間隔おいた時点での差電圧（Ｖ１
−Ｖ２）のサンプリング操作を指定することが可能であ
る。このような方法では、集積化駆動装置の外部負荷に
直列に接続された電流検知抵抗器でモニタされる共通モ
ード信号の電圧低下に対して、制御ループが過剰反応し
なくなる。Since the present apparatus can be controlled more easily, the difference voltage (V1) at an appropriate time interval after the switching transition is performed.
-V2) sampling operation can be specified. In this way, the control loop does not over-react to a voltage drop of the common mode signal monitored by a current sensing resistor connected in series with the external load of the integrated drive.
【００２０】[0020]
【発明の実施の形態】図２に示すように、位相がΦ１の
とき、スイッチｓｗＡ、ｓｗＢ、ｓｗ１は閉となってお
り、検知抵抗器Ｒ３の端子電圧のサンプリングが行わ
れ、演算増幅器ＯＰはバッファとして動作する。この位
相では、電圧Ｖｓｅｎｓｅである出力値は基準電圧Ｖｒ
ｅｆに達し、Ｃ１はＶｉｎ１−Ｖｒｅｆで荷電され、Ｃ
２はＶｉｎ２−Ｖｒｅｆで荷電される。DESCRIPTION OF THE PREFERRED EMBODIMENTS As shown in FIG. 2, when the phase is Φ1, the switches swA, swB, and sw1 are closed, the terminal voltage of the detection resistor R3 is sampled, and the operational amplifier OP is turned on. Act as a buffer. In this phase, the output value of the voltage Vsense is equal to the reference voltage Vr.
ef, C1 is charged with Vin1-Vref and C1
2 is charged with Vin2-Vref.
【００２１】位相Φ２では、２個のキャパシタＣ１、Ｃ
２が直列接続されて、検知抵抗器Ｒ３の端子電圧がキャ
パシタＣ１、Ｃ２のそれぞれの端子に印加される。キャ
パシタＣ１、Ｃ２に充電される電荷は、下記のとおりで
ある。In the phase Φ2, two capacitors C1, C
2 are connected in series, and the terminal voltage of the detection resistor R3 is applied to the respective terminals of the capacitors C1 and C2. The charges charged in the capacitors C1 and C2 are as follows.
【数４】△Ｑ＝（Ｖｉｎ１−Ｖｉｎ２）×（１／Ｃ１＋
１／Ｃ２）△ Q = (Vin1-Vin2) × (1 / C1 +
1 / C2)
【００２２】演算増幅器ＯＰのフィードバックによりマ
イナス端子がＶｒｅｆになって、キャパシタＣ１、Ｃ２
の電荷がＣ３に移動する。この位相において、出力値Ｖ
ｓｅｎｓｅ’が下記の分だけ変動する。The negative terminal becomes Vref by the feedback of the operational amplifier OP, and the capacitors C1 and C2
Move to C3. In this phase, the output value V
Sense 'fluctuates by the following amount.
【数５】 △Ｖ＝△Ｑ／Ｃ３ ＝［（Ｖｉｎ１−Ｖｉｎ２）×（１／Ｃ１＋１／Ｃ２）］／Ｃ３ΔV = ΔQ / C3 = [(Vin1−Vin2) × (1 / C1 + 1 / C2)] / C3
【００２３】ここで、Ｃ１＝Ｃ２＝Ｃ、Ｃ３＝Ｃ／２と
すると、演算増幅器ＯＰの出力電圧は、検知抵抗器Ｒ３
の端子電圧によって変化することになる。Here, assuming that C1 = C2 = C and C3 = C / 2, the output voltage of the operational amplifier OP becomes the detection resistor R3
Will vary with the terminal voltage of
【００２４】電流センス増幅器の出力端におけるＶｓｅ
ｎｓｅ値を維持するには、いわゆるサンプルホールド機
能を備えたサンプルホールドステージを演算増幅器ＯＰ
にカスケード接続すればよい。Vse at the output of the current sense amplifier
To maintain the nse value, a sample-and-hold stage having a so-called sample-and-hold function is connected to the operational amplifier OP.
What is necessary is just to cascade connection.
【００２５】[0025]
【発明の効果】本発明による電流モードＰＷＭ駆動装置
は、電圧レベル差の増加による精度低下を起こすことな
く、ほぼ制限のない小型化が可能となる。また、切換式
キャパシタ技術を使った電流センス増幅器により、理論
的には無限の共通モードの阻止、つまり、不可避である
集積抵抗値の不一致によるオフセット障害をなくすこと
ができる。The current mode PWM driving apparatus according to the present invention can be reduced in size without any limitation without causing a decrease in accuracy due to an increase in voltage level difference. Also, current sense amplifiers using switched capacitor technology can prevent theoretically infinite common modes, i.e., eliminate unavoidable offset disturbances due to inconsistent integrated resistance values.
【図１】従来の電流モード切換駆動装置の回路図。FIG. 1 is a circuit diagram of a conventional current mode switching driving device.
【図２】本発明の電流モード切換駆動装置の回路図。FIG. 2 is a circuit diagram of a current mode switching driving device according to the present invention.
Claims (1)
（Ｒ１）経由で印加される第１電流および電流検知抵抗
器（Ｒ３）の電圧降下分を入力とする電流センス増幅器
（Current Sense）の出力電圧（Ｖｓｅｎｓｅ）により
第２抵抗器（Ｒ２）経由で印加される第２電流のバラン
スをとる入力ノード（Ａ）の電圧と、基準電圧（Ｖｒｅ
ｆ）とを比較する誤差増幅器（Error Amplifier）の、
前記入力ノード（Ａ）で閉状態となる制御ループを備
え、前記基準電圧（Ｖｒｅｆ）が、前記電流検知抵抗器
（Ｒ３）による電圧降下量よりも小さい電流モードＰＷ
Ｍ駆動装置であって、 前記電流センス増幅器が、１対の相補制御信号（Φ１、
Φ２）により制御されるスイッチ（ｓｗＡ、ｓｗＢ、ｓ
ｗＣ、ｓｗ１）により、バッファ又は電荷転送回路とし
て動作する演算増幅器（ＯＰ）と、サンプルホールド出
力ステージとから構成されることを特徴とする電流モー
ドＰＷＭ駆動装置。1. A current sense amplifier (Current Sense) having a first current applied through a first resistor (R1) by a control voltage (Vdac) and a voltage drop of a current sensing resistor (R3) as inputs. A voltage at the input node (A) that balances a second current applied through the second resistor (R2) by the output voltage (Vsense), and a reference voltage (Vre)
f) of the error amplifier comparing with
A current mode PW having a control loop that is closed at the input node (A), wherein the reference voltage (Vref) is smaller than the voltage drop by the current sensing resistor (R3).
M drive device, wherein the current sense amplifier comprises a pair of complementary control signals (Φ1,
Φ2) controlled switches (swA, swB, s)
wC, sw1), comprising: an operational amplifier (OP) operating as a buffer or a charge transfer circuit; and a sample-and-hold output stage.
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| IT97830533.2 | 1997-10-23 | ||
| EP97830533A EP0911954B1 (en) | 1997-10-23 | 1997-10-23 | PWM drive system in a current mode. |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| JPH11215885A true JPH11215885A (en) | 1999-08-06 |
Family
ID=8230817
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP10300544A Pending JPH11215885A (en) | 1997-10-23 | 1998-10-22 | Supply voltage variable current mode pwm driving device |
Country Status (4)
| Country | Link |
|---|---|
| US (1) | US6184665B1 (en) |
| EP (1) | EP0911954B1 (en) |
| JP (1) | JPH11215885A (en) |
| DE (1) | DE69704709T2 (en) |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US9209738B2 (en) | 2011-01-20 | 2015-12-08 | Panasonic Intellectual Property Management Co., Ltd. | Induction load driving system |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US6246220B1 (en) * | 1999-09-01 | 2001-06-12 | Intersil Corporation | Synchronous-rectified DC to DC converter with improved current sensing |
| US6577179B2 (en) * | 1999-11-15 | 2003-06-10 | Intel Corporation | Dynamic line termination with self-adjusting impedance |
| EP1207618B1 (en) * | 2000-11-20 | 2005-10-05 | STMicroelectronics S.r.l. | Circuit for the speed recovery of a direct current motor and method using said circuit |
| US6982559B2 (en) * | 2004-01-14 | 2006-01-03 | Kyocera Wireless Corp. | Accurate and efficient sensing circuit and method for bi-directional signals |
| US7207885B2 (en) | 2004-01-15 | 2007-04-24 | Espeed, Inc. | System and method for using a game controller device for electronic trading |
| US8170945B2 (en) * | 2004-01-15 | 2012-05-01 | Bgc Partners, Inc. | System and method for providing security to a game controller device for electronic trading |
| DE102005010899A1 (en) * | 2005-03-09 | 2006-09-21 | Siemens Ag | Control system with function monitoring for an electromechanical drive in a vehicle |
| US7112937B1 (en) * | 2005-10-31 | 2006-09-26 | Hewlett-Packard Development Company, Lp. | Device and method for driving a motor |
| US7522368B2 (en) * | 2006-04-10 | 2009-04-21 | Texas Instruments Incorporated | Differential voice coil motor control |
| US20080228618A1 (en) | 2007-03-15 | 2008-09-18 | Noviello Joseph C | System And Method For Providing An Operator Interface For Displaying Market Data, Trader Options, And Trader Input |
| US8525498B2 (en) * | 2008-07-31 | 2013-09-03 | Monolithic Power Systems, Inc. | Average input current limit method and apparatus thereof |
| US8208237B2 (en) | 2008-09-30 | 2012-06-26 | International Business Machines Corporation | Administering offset voltage error in a current sensing circuit |
| JP6489031B2 (en) * | 2016-01-27 | 2019-03-27 | 株式会社デンソー | Motor control device |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4066945A (en) * | 1976-03-31 | 1978-01-03 | The Bendix Corporation | Linear driving circuit for a d.c. motor with current feedback |
| US4436093A (en) * | 1980-11-04 | 1984-03-13 | Norland Corporation | Cardiac pacer having active notch filter system |
| US4596252A (en) * | 1985-05-06 | 1986-06-24 | Medtronic, Inc. | Pacer sense amplifier |
| FR2702104B1 (en) * | 1993-02-23 | 1995-06-30 | Aerospatiale | METHOD FOR DRIVING A REVERSIBLE ELECTRICAL APPARATUS. |
| US5361776A (en) * | 1993-08-06 | 1994-11-08 | Telectronics Pacing Systems, Inc. | Time domain reflectometer impedance sensor method of use and implantable cardiac stimulator using same |
-
1997
- 1997-10-23 DE DE69704709T patent/DE69704709T2/en not_active Expired - Fee Related
- 1997-10-23 EP EP97830533A patent/EP0911954B1/en not_active Expired - Lifetime
-
1998
- 1998-10-19 US US09/174,867 patent/US6184665B1/en not_active Expired - Lifetime
- 1998-10-22 JP JP10300544A patent/JPH11215885A/en active Pending
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US9209738B2 (en) | 2011-01-20 | 2015-12-08 | Panasonic Intellectual Property Management Co., Ltd. | Induction load driving system |
Also Published As
| Publication number | Publication date |
|---|---|
| US6184665B1 (en) | 2001-02-06 |
| DE69704709T2 (en) | 2001-08-09 |
| DE69704709D1 (en) | 2001-06-07 |
| EP0911954A1 (en) | 1999-04-28 |
| EP0911954B1 (en) | 2001-05-02 |
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