JPH10248262A - Power conversion device and its control method - Google Patents
Power conversion device and its control methodInfo
- Publication number
- JPH10248262A JPH10248262A JP10091220A JP9122098A JPH10248262A JP H10248262 A JPH10248262 A JP H10248262A JP 10091220 A JP10091220 A JP 10091220A JP 9122098 A JP9122098 A JP 9122098A JP H10248262 A JPH10248262 A JP H10248262A
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- Prior art keywords
- voltage command
- phase
- voltage
- value
- command
- Prior art date
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Abstract
Description
【０００１】[0001]
【発明の属する技術分野】本発明は交流電動機を駆動す
る電力変換装置とその制御方法及び電力変換装置を用い
た駆動システムに関する。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a power converter for driving an AC motor, a control method thereof, and a drive system using the power converter.
【０００２】[0002]
【従来の技術】従来、三相ブリッジ型インバータを用い
た電力変換装置は図８に示す構成となっている。また図
８において、インバータの電圧指令と搬送波及び三相の
出力電圧のうちＵ相とＶ相及びＵ−Ｖ線間電圧の波形を
図９に示す。2. Description of the Related Art Conventionally, a power converter using a three-phase bridge type inverter has a configuration shown in FIG. In FIG. 8, the voltage command of the inverter and the waveforms of the U-phase, the V-phase and the U-V line voltage among the carrier wave and the three-phase output voltage are shown in FIG.
【０００３】図８において、電圧指令手段５は、Ｕ，
Ｖ，Ｗ各相の電圧指令５０１，５０２，５０３を出力
し、搬送波発生手段７は前記電圧指令の基本波周期より
十分短かい周期の三角波状の波送波を出力する。比較器
８−ａ，８−ｂ，８−ｃでは前記各相の電圧指令５０
１，５０２，５０３と前記搬送波７０１とを比較し、得
られた信号８０１，８０２，８０３をインバータ３の対
応する相の制御信号としてドライブ回路９ａ〜９ｆを経
由してインバータ３の各スイッチング素子をオン・オフ
させ、前記電圧指令が搬送波より大きいときには、該当
相の出力電圧を正とし、小さいときには該当相の出力電
圧を負とする様に制御することにより、負荷に加わる電
圧を平均的に指令値に近づける。In FIG. 8, voltage command means 5 includes U,
The voltage commands 501, 502, and 503 for each of the V and W phases are output, and the carrier generation means 7 outputs a triangular wave transmission having a period sufficiently shorter than the fundamental period of the voltage command. In the comparators 8-a, 8-b, 8-c, the voltage command 50 of each phase is used.
1, 502, 503 and the carrier wave 701, and the obtained signals 801, 802, 803 are used as control signals for the corresponding phases of the inverter 3 and the respective switching elements of the inverter 3 are passed through the drive circuits 9a to 9f. ON / OFF, when the voltage command is larger than the carrier wave, the output voltage of the corresponding phase is set to be positive, and when the voltage command is smaller, the output voltage of the corresponding phase is set to be negative. Approach the value.
【０００４】前記従来技術によれば、電圧指令に応じた
高調波成分が小さい可変周波数可変振幅の電圧が得られ
る。According to the prior art, a voltage having a variable frequency and a variable amplitude with a small harmonic component according to a voltage command can be obtained.
【０００５】[0005]
【発明が解決しようとする課題】上記従来技術は、出力
電圧の高調波成分を小さくするために、各相の電圧指令
５０１〜５０３が常に搬送波７０１の振幅内にあること
が必要である。このため出力電圧の基本波成分を大きく
できないという問題があった。また、パルスパターンが
不規則なため、電動機を負荷とした場合に、発生トルク
の脈動が大きくなるという問題もある。In the above prior art, the voltage commands 501 to 503 of each phase must always be within the amplitude of the carrier wave 701 in order to reduce the harmonic components of the output voltage. For this reason, there is a problem that the fundamental wave component of the output voltage cannot be increased. In addition, since the pulse pattern is irregular, there is a problem that the pulsation of the generated torque increases when a load is applied to the electric motor.
【０００６】従来、出力電圧の基本波成分の最大値を大
きくするための方法として、各相の電圧指令値に基本波
の３倍の周波数の正弦波を加えて電圧指令値に基本波の
３倍の周波数の正弦波を加えて電圧指令のピーク値を小
さくする方法がある。しかし、前記方法では電圧指令手
段とは別に基本波の３倍の周波数の正弦波を発生させる
ための正弦波発生手段が必要となる。さらに、電圧指令
の基本波成分と３倍の周波数の正弦波を同期させる必要
があり、瞬時電圧制御を行う場合には制御回路が複雑に
なるという問題がある。また前記３倍の周波数を基本波
に加える方式でも発生トルク脈動が大きくなるという問
題がある。Conventionally, as a method for increasing the maximum value of the fundamental wave component of the output voltage, a sine wave having a frequency three times the fundamental wave is added to the voltage command value of each phase, and the voltage command value is increased by three times the fundamental wave. There is a method of adding a double frequency sine wave to reduce the peak value of the voltage command. However, in the above method, a sine wave generating means for generating a sine wave having a frequency three times the fundamental wave is required separately from the voltage command means. Further, it is necessary to synchronize a fundamental wave component of the voltage command with a sine wave having a frequency three times as high, and there is a problem that a control circuit becomes complicated when performing instantaneous voltage control. Further, even in the method of adding the triple frequency to the fundamental wave, there is a problem that the generated torque pulsation increases.
【０００７】本発明の目的は、出力電圧の高調波成分を
増加させることなく、簡単な制御回路で出力電圧の基本
波成分を大きくでき、しかも電動機駆動時のトルク脈動
を小さな電力変換装置を実現することにある。An object of the present invention is to realize a power converter which can increase the fundamental wave component of the output voltage with a simple control circuit without increasing the harmonic components of the output voltage, and which has a small torque pulsation when the motor is driven. Is to do.
【０００８】[0008]
【課題を解決するための手段】上記目的を達成するため
に、三相の電圧指令の大小を比較する比較器と、前記比
較器で最大値と最小値を除いた中間値を求め、前記中間
値を２分の１倍した値を各相電圧指令に加算する加算器
を設け、前記加算器の出力を新たに電圧指令値とするこ
とにより達成される。In order to achieve the above object, a comparator for comparing the magnitudes of three-phase voltage commands and an intermediate value excluding a maximum value and a minimum value are obtained by the comparator. This is achieved by providing an adder for adding a value obtained by halving the value to each phase voltage command, and newly using the output of the adder as a voltage command value.
【０００９】また、電圧指令として振幅指令と位相指令
が与えられる場合は、互に１２０°ずつ位相が異なる三
相の正弦波状の電圧指令に変換する変換手段を設け、前
記変換手段で変換した三相の電圧指令の大小を比較し、
その中間値の２分の１を変換した各相の電圧指令値に加
算した結果を新たな電圧指令値とすることによって上記
目的を達成できる。When an amplitude command and a phase command are given as voltage commands, a conversion means is provided for converting the voltage command into a three-phase sinusoidal voltage command having a phase different from each other by 120 °. Compare the magnitude of the phase voltage command,
The above object can be achieved by adding a result of adding one half of the intermediate value to the converted voltage command value of each phase as a new voltage command value.
【００１０】三相の電力変換器と負荷の間では、通常中
性点を接続しないので、電圧指令の与え方を変化させて
も、線間電圧さえ変化しなければ、負荷に加わる電圧は
変化しない。従って、各相の電圧指令に同じ値を加え
て、電圧指令の絶対値が最大となる相の電圧指令を小さ
くすることにより、負荷電圧を変化させることなく電圧
指令のピーク値を小さくすることができるため、電圧指
令を大きくすることによって、出力電圧の基本波成分の
最大値を大きくすることができる。[0010] Since a neutral point is not normally connected between the three-phase power converter and the load, the voltage applied to the load changes as long as the line voltage does not change even if the way of giving the voltage command is changed. do not do. Therefore, by adding the same value to the voltage command of each phase and reducing the voltage command of the phase in which the absolute value of the voltage command is maximum, the peak value of the voltage command can be reduced without changing the load voltage. Therefore, by increasing the voltage command, the maximum value of the fundamental wave component of the output voltage can be increased.
【００１１】さらに、三相の瞬時電圧指令の最大値と最
小値の絶対値を常に等しくなるように変換し、前記変換
した値を新たな電圧指令値とすることによって、線間電
圧を変化させずに前記電圧指令値を小さくすることがで
きるため、従来方法に比べ電圧指令を大きくすることが
可能となる。例えば、前記変換前の電圧指令が正弦波の
場合には、変換後の新たな電圧指令値の振幅は、変換前
の√３／２倍となるため、出力電圧の基本波成分は従来
に比べ２／√３≒１.１５ 倍に大きくできる。Further, the absolute value of the maximum value and the minimum value of the three-phase instantaneous voltage command are converted so as to always be equal, and the converted value is used as a new voltage command value, thereby changing the line voltage. Therefore, the voltage command value can be reduced without increasing the voltage command value as compared with the conventional method. For example, when the voltage command before the conversion is a sine wave, the amplitude of the new voltage command value after the conversion is √ / 2 times that before the conversion, so that the fundamental wave component of the output voltage is smaller than that of the conventional one. 2 / {3} 1.15 times larger.
【００１２】[0012]
【発明の実施の形態】図１に本発明第１の実施例を示
す。FIG. 1 shows a first embodiment of the present invention.
【００１３】交流電源１の電力をコンバータ２によって
直流に変換し、この直流を三相ブリッジ型インバータ３
により可変周波数可変電圧の交流電力に変換して負荷４
に供給する。The power of the AC power supply 1 is converted into DC by the converter 2 and this DC is converted into a three-phase bridge type inverter 3
The load 4
To supply.
【００１４】電圧指令手段５は正弦波状の三相瞬間電圧
指令５０１〜５０３を発生する。電圧指令比較手段６
は、前記三相瞬時電圧指令５０１〜５０３を互いに大小
比較し、それらの中から最大値６０１と最小値６０２を
除いた中間値６０３を出力する。前記電圧指令の中間値
６０３の２分の１を電圧指令補正信号６０５とし、これ
を前記各相の瞬時電圧指令５０１〜５０３の各々に加え
た値を新たな電圧指令６０６〜６０８とする。搬送波発
生手段７より出力される三角波状の搬送波701と、前記
各相の新たな電圧指令６０６〜６０８とを、それぞれ比
較器８ａ〜８ｃにより比較して、得られる信号をパルス
幅変調信号として、ドライブ回路９ａ〜９ｆを通じて三
相ブリッジ型インバータ３の各スイッチング素子をオン
・オフさせることにより負荷４に交流電力を供給する。The voltage command means 5 generates sinusoidal three-phase instantaneous voltage commands 501 to 503. Voltage command comparing means 6
Compares the three-phase instantaneous voltage commands 501 to 503 with each other, and outputs an intermediate value 603 excluding the maximum value 601 and the minimum value 602 from among them. One half of the intermediate value 603 of the voltage command is set as a voltage command correction signal 605, and a value obtained by adding this to each of the instantaneous voltage commands 501 to 503 of each phase is set as a new voltage command 606 to 608. The triangular carrier 701 output from the carrier generator 7 and the new voltage commands 606 to 608 of the respective phases are compared by comparators 8a to 8c, respectively, and the obtained signal is used as a pulse width modulation signal. AC power is supplied to the load 4 by turning on / off each switching element of the three-phase bridge type inverter 3 through the drive circuits 9a to 9f.
【００１５】図２に、図１に示す本発明第１の実施例に
おける各部の波形を示す。図２は、電圧指令手段５より
出力される各相の電圧指令５０１〜５０３が、互いに位
相が１２０°ずつ異なる正弦波である場合について示し
たものである。FIG. 2 shows waveforms at various points in the first embodiment of the present invention shown in FIG. FIG. 2 shows a case where the voltage commands 501 to 503 of each phase output from the voltage command means 5 are sine waves whose phases are different from each other by 120 °.
【００１６】Ｕ，Ｖ，Ｗ各相の電圧指令５０１〜５０３
をそれぞれＶU ，ＶV ，ＶW とする。各相の電圧指令は
通常零相分が零、即ち、Voltage commands 501 to 503 for each of U, V and W phases
Each and V U, V V, V W . The voltage command of each phase is usually zero for zero phase, that is,
【００１７】[0017]
【数１】 ＶU＋ＶV＋ＶW＝０ …（１） となるように得られる。例えばＶU≧ＶV≧ＶW である場
合について考えると、これらを互いに大小比較した中間
値はＶV であり、電圧指令補正信号６０５をＶmとする
と、（１）式よりV U + V V + V W = 0 (1) For example, considering the case of V U ≧ V V ≧ V W , an intermediate value obtained by comparing the magnitudes of these is V V , and if the voltage command correction signal 605 is V m , from the equation (1)
【００１８】[0018]
【数２】 (Equation 2)
【００１９】となる。このとき、変換後の新たな各相電
圧指令６０６〜６０８をＶU′，ＶV′，ＶW′ とし、そ
れぞれを求めると、## EQU1 ## At this time, the converted new phase voltage commands 606 to 608 are denoted by V U ′, V V ′, and V W ′, respectively.
【００２０】[0020]
【数３】 (Equation 3)
【００２１】となる。このとき、変換の前後で線間電圧
は変化していない。ＶU′，ＶV′，ＶW′ の中での最大
値はＶU′、最小値はＶW′であり、両者の絶対値は等し
い。ＶU ，ＶV ，ＶW の大小関係が異なる場合について
も同様に変換後の新たな電圧指令ＶU′，ＶV′，ＶW′
の中の最大値と最小値の絶対値は等しくなる。## EQU1 ## At this time, the line voltage has not changed before and after the conversion. The maximum value among V U ′, V V ′ and V W ′ is V U ′ and the minimum value is V W ′, and their absolute values are equal. Similarly, when the magnitude relations of V U , V V , and V W are different, new voltage commands V U ′, V V ′, V W ′ after conversion are obtained.
The absolute values of the maximum and minimum values in are equal.
【００２２】新たな電圧指令ＶU′，ＶV′，ＶW′ は図
２（ｃ）に示すような波形となり、その振幅は図２
（ａ）に示す変換前の電圧指令ＶU ，ＶV ，ＶW の振幅
より小さくなる。従って本実施例によれば、電圧指令の
振幅が搬送波の振幅を超えずに出力できる電圧の基本波
成分の最大値を従来よりも高くすることができる。The new voltage commands V U ′, V V ′, V W ′ have waveforms as shown in FIG.
It becomes smaller than the amplitudes of the voltage commands V U , V V , V W before conversion shown in FIG. Therefore, according to the present embodiment, the maximum value of the fundamental wave component of the voltage that can be output without the amplitude of the voltage command exceeding the amplitude of the carrier can be made higher than before.
【００２３】さらに、搬送波一周期間のパルスパターン
を詳細に見た場合、搬送波周期の始めと終わりに等しい
期間出力電圧が零となり、規則正しいパルスパターンと
なる。このため、電動機を駆動した場合に発生トルクの
脈動を小さくすることができる。Further, when the pulse pattern during one carrier wave period is viewed in detail, the output voltage becomes zero during a period equal to the beginning and end of the carrier wave period, and a regular pulse pattern is obtained. Therefore, the pulsation of the torque generated when the motor is driven can be reduced.
【００２４】図３に、本発明第２の実施例を示す。本実
施例は、電圧指令手段５′の出力として位相指令５０４
と振幅指令５０５が得られる場合についての実施例であ
る。電圧指令変換手段１０において、前記位相指令５０
４と前記振幅指令５０５を三相の電圧指令６０６′，６
０７′，６０８′に変換する。位相モード判定手段１０
１は位相指令５０４を入力し、６０°ごとの位相モード
１０３を出力する。関数発生手段１０２は、三相の電圧
指令６０６′〜６０８′の中の最大値と最小値の絶対値
が等しくかつ各線間電圧が正弦波なるような関数１０６
〜１０８を、位相指令５０４と位相モード１０３より求
め、振幅指令５０５を乗ずることにより、三相の電圧指
令６０６′〜６０８′が得られる。図６に位相指令と位
相モードおよび振幅指令に対する各相の電圧指令の関係
を示す。FIG. 3 shows a second embodiment of the present invention. In this embodiment, the phase command 504 is used as the output of the voltage command means 5 '.
This is an example of a case where the amplitude command 505 is obtained. In the voltage command conversion means 10, the phase command 50
4 and the amplitude command 505 are converted into three-phase voltage commands 606 ', 6
07 ', 608'. Phase mode determination means 10
1 inputs the phase command 504 and outputs the phase mode 103 every 60 °. The function generating means 102 generates a function 106 such that the absolute value of the maximum value and the minimum value of the three-phase voltage commands 606 'to 608' are equal and each line voltage becomes a sine wave.
To 108 are obtained from the phase command 504 and the phase mode 103 and multiplied by the amplitude command 505 to obtain three-phase voltage commands 606 'to 608'. FIG. 6 shows the relationship between the phase command, the phase mode, and the voltage command for each phase with respect to the amplitude command.
【００２５】前記各相の電圧指令６０６′〜６０８′
を、それぞれ比較器８ａ〜８ｃにおいて搬送波発生手段
７により出力される三角波状の搬送波７０１と比較し、
得られる信号をパルス幅変調信号として、ドライブ回路
９ａ〜９ｆを通じて三相ブリッジ型インバータ３の各ス
イッチング素子をオン・オフさせることにより、負荷４
に交流電力を供給する。The voltage commands 606 'to 608' for the respective phases
Is compared with a triangular carrier 701 output from the carrier generator 7 in the comparators 8a to 8c, respectively.
By turning on / off each switching element of the three-phase bridge type inverter 3 through the drive circuits 9a to 9f using the obtained signal as a pulse width modulation signal, the load 4
Supply AC power to
【００２６】本実施例によれば、電圧指令として位相指
令と振幅指令が得られる場合においても、出力電圧の基
本波成分の最大値を大きくすることができ、その際の演
算処理を簡単にすることができる。According to this embodiment, even when the phase command and the amplitude command are obtained as the voltage command, the maximum value of the fundamental wave component of the output voltage can be increased, and the calculation process at that time can be simplified. be able to.
【００２７】図５に本発明第３の実施例を示す。本実施
例は、交流電力を直流に変換する電力順変換装置に本発
明を適用した例である。FIG. 5 shows a third embodiment of the present invention. This embodiment is an example in which the present invention is applied to a power conversion device that converts AC power to DC.
【００２８】三相ブリッジ型コンバータ３′は交流リア
クトル２０を介して交流電源１に接続され、交流電力を
直流電力に変換して負荷４′に供給する。The three-phase bridge type converter 3 'is connected to the AC power supply 1 via the AC reactor 20, converts AC power into DC power, and supplies it to the load 4'.
【００２９】電圧制御器１２は直流電圧検出器より得ら
れる検出値と直流電圧指令との偏差によって働き、電流
振幅指令１２１を出力する。乗算器１５ａ〜１５ｃは電
圧検出器１３ａ〜１３ｃにより検出される各相の交流電
圧信号と前記電流振幅指令を乗算して、電圧と同位相の
交流電流指令を出力する。電流制御器１４ａ〜１４ｃは
電流検出器１６ａ〜１６ｃより得られる検出値と前記交
流電流指令との偏差によって働き、電圧指令５０１′〜
５０３′を出力する。電圧指令比較手段６は前記電圧指
令５０１′〜５０３′を互いに大小比較してその中での
中間値６０３′を出力する。得られた中間値６０３′の
２分の１を前記電圧指令５０１′〜５０３′に加え、そ
の和をそれぞれ比較器８ａ〜８ｃにおいて、搬送波発生
手段７より出力される三角波状の搬送波と比較し、得ら
れる信号をパルス幅変調信号としてドライブ回路９′ａ
〜９′ｆを介して三相ブリッジ型コンバータ３′の各ス
イッチング素子をオン・オフさせる。The voltage controller 12 operates according to the deviation between the detection value obtained from the DC voltage detector and the DC voltage command, and outputs a current amplitude command 121. The multipliers 15a to 15c multiply the AC voltage signals of each phase detected by the voltage detectors 13a to 13c by the current amplitude command, and output an AC current command having the same phase as the voltage. The current controllers 14a to 14c operate based on the deviation between the detection values obtained from the current detectors 16a to 16c and the AC current command, and the voltage commands 501 'to
503 'is output. The voltage command comparing means 6 compares the voltage commands 501 'to 503' with each other and outputs an intermediate value 603 '. One half of the obtained intermediate value 603 'is added to the voltage commands 501' to 503 ', and the sum is compared in comparators 8a to 8c with the triangular carrier outputted from the carrier generator 7. , The resulting signal as a pulse width modulation signal in drive circuit 9'a
The switching elements of the three-phase bridge type converter 3 'are turned on / off via .about.9'f.
【００３０】本実施例によれば、交流側の入力電流を力
率１でかつ正弦波に１つずつ直流側の出力電圧を制御す
る電力順変換装置において、直流側の出力電圧を従来よ
りも低くまで制御できるため、制御範囲が拡大し制御の
安定性が向上する。According to the present embodiment, in the power forward converter that controls the input current on the AC side at a power factor of 1 and controls the output voltage on the DC side one by one in a sine wave, the output voltage on the DC side is lower than in the prior art. Since the control can be performed to a low level, the control range is expanded and the stability of the control is improved.
【００３１】図５に示す実施例は図１に示すインバータ
を順変換装置に適用したものであるが、図３に示すイン
バータに適用しても、同様の効果が得られる。Although the embodiment shown in FIG. 5 applies the inverter shown in FIG. 1 to a forward converter, the same effect can be obtained by applying the inverter shown in FIG.
【００３２】さらに、本発明を順変換装置とインバータ
装置の両者に適用し、負荷の必要とする電力に応じて両
者の電圧指令を決定することにより変換装置全体の小型
化を図ることも可能となる。Furthermore, the present invention can be applied to both a forward converter and an inverter device, and the voltage command of both can be determined according to the power required by the load, thereby making it possible to reduce the size of the entire converter. Become.
【００３３】図６に本発明第４の実施例を示す。本実施
例は、本発明を多重インバータの制御に適用したもので
ある。FIG. 6 shows a fourth embodiment of the present invention. In this embodiment, the present invention is applied to control of a multiplex inverter.
【００３４】三相ブリッジ型インバータ３ａと３ｂは、
共に直流側は並列接続され、交流側は相間リアクトル１
６ａ〜１６ｃを介して接続されている。各相間リアクト
ルの中点を出力端として負荷に接続されている。The three-phase bridge type inverters 3a and 3b are:
In both cases, the DC side is connected in parallel, and the AC side is
6a to 16c are connected. The midpoint of each inter-phase reactor is connected to the load with the output terminal as the output terminal.
【００３５】電圧指令手段５は、正弦波状の三相の瞬時
電圧指令５０１〜５０３を発生する。電圧指令比較手段
６は前記三相の瞬時電圧指令５０１〜５０３を互いに大
小比較し、それらの中の中間値６０３を出力する。前記
電圧指令の中間値６０３の２分の１を電圧指令補正信号
６０５として、前記各相の電圧指令に加えた値を新たな
電圧指令６０６〜６０８とする。搬送波発生手段７は三
角波状の搬送波７０１とそれを反転した搬送波７０２を
出力する。比較器８ａ〜８ｃは新たな電圧指令６０６〜
６０８を搬送波７０１と比較して三相ブリッジ型インバ
ータ３ａの各スイッチング素子をオン・オフさせる信号
を作り、比較器８ｄ〜８ｆは新たな電圧指令６０６〜６
０８を搬送波７０２と比較して三相ブリッジ型インバー
タ３ｂの各スイッチング素子をオン・オフさせる信号を
作る。The voltage command means 5 generates sinusoidal three-phase instantaneous voltage commands 501 to 503. The voltage command comparing means 6 compares the three-phase instantaneous voltage commands 501 to 503 with each other and outputs an intermediate value 603 among them. One half of the intermediate value 603 of the voltage command is set as a voltage command correction signal 605, and the value added to the voltage command of each phase is set as new voltage commands 606 to 608. The carrier generator 7 outputs a triangular carrier 701 and a carrier 702 obtained by inverting the carrier 701. The comparators 8a to 8c output new voltage commands 606 to
608 is compared with the carrier 701 to generate a signal for turning on / off each switching element of the three-phase bridge type inverter 3a, and the comparators 8d to 8f output new voltage commands 606 to 6f.
08 is compared with the carrier 702 to generate a signal for turning on / off each switching element of the three-phase bridge inverter 3b.
【００３６】図７に、図６に示す本発明第４の実施例に
おける各部の波形を示す。インバータ３ａのＵ相出力電
圧３０１ａとインバータ３ｂのＵ相出力電圧３０１ｂで
は搬送波周波数成分の位相が異っているため、両者の合
成出力電圧３０１では搬送波周波数成分が低減されてい
る。したがって負荷に流れる電流の高調波成分が低減さ
れるので、電動機駆動に用いる場合には発生トルクの脈
動を低減することができる。FIG. 7 shows waveforms at various points in the fourth embodiment of the present invention shown in FIG. Since the phase of the carrier frequency component is different between the U-phase output voltage 301a of the inverter 3a and the U-phase output voltage 301b of the inverter 3b, the carrier frequency component is reduced in the combined output voltage 301 of both. Therefore, the harmonic component of the current flowing through the load is reduced, so that when used for driving an electric motor, the pulsation of the generated torque can be reduced.
【００３７】本実施例によれば、複数台のインバータを
並列接続した多数インバータにおいても、出力電圧の基
本波成分の最大値を大きくすることができる。According to this embodiment, the maximum value of the fundamental wave component of the output voltage can be increased even in a large number of inverters in which a plurality of inverters are connected in parallel.
【００３８】[0038]
【発明の効果】本発明によれば、小さな電圧指令で従来
方法と同じ大きさの相間出力電圧を得ることができるた
め、電圧指令値を従来方法に比べ大きく設定することが
可能になり、電圧の制御範囲を拡大できるという効果が
ある。According to the present invention, an inter-phase output voltage of the same magnitude as that of the conventional method can be obtained with a small voltage command, so that the voltage command value can be set larger than that of the conventional method. There is an effect that the control range of can be expanded.
【００３９】また、従来の出力電圧と同じ出力電圧を得
るための入力電圧を低くすることができるため、電力変
換装置の素子容量を小さくすることができ、さらに、装
置で発生する損失を小さくすることができる。Further, since the input voltage for obtaining the same output voltage as the conventional output voltage can be reduced, the element capacity of the power converter can be reduced, and the loss generated in the device can be reduced. be able to.
【００４０】本発明を順変換装置に適用した場合は、出
力する直流電圧は従来より低くまで制御できるので、制
御範囲を拡大することができる。When the present invention is applied to a forward conversion device, the output DC voltage can be controlled to a lower level than in the prior art, so that the control range can be expanded.
【００４１】さらに、本発明を順変換装置と逆変換装置
の両者に適用した電力変換装置とすると、入力の電圧電
流および出力の電圧電流の条件を従来とほぼ等しくした
場合の中間回路の直流電圧を従来より低くすることがで
きるので、平滑コンデンサ等の中間回路を小型化するこ
とができ、また中間回路で発生する損失を低減できる効
果がある。Further, if the present invention is applied to a power conversion device applied to both a forward conversion device and an inverse conversion device, the DC voltage of the intermediate circuit in the case where the conditions of the input voltage current and the output voltage current are substantially equal to those of the prior art. Can be reduced as compared with the prior art, so that an intermediate circuit such as a smoothing capacitor can be downsized, and the loss generated in the intermediate circuit can be reduced.
【００４２】さらに、本発明の電力変換装置を電動機の
駆動に適用した場合には、規則正しいパルスパターンを
発生することができるため、発生トルクの脈動を小さく
でき、機械的振動の発生を抑制できる。従って機械の安
定性を向上することができ、システム全体の長寿命化を
図ることができる他、騒音も低減でき効果がある。Furthermore, when the power converter of the present invention is applied to driving a motor, a regular pulse pattern can be generated, so that the pulsation of the generated torque can be reduced and the occurrence of mechanical vibration can be suppressed. Therefore, the stability of the machine can be improved, the service life of the entire system can be extended, and noise can be reduced.
【図１】本発明の第１の実施例の構成図。FIG. 1 is a configuration diagram of a first embodiment of the present invention.
【図２】第１の実施例における各部の波形を示す図。FIG. 2 is a diagram showing waveforms of respective units in the first embodiment.
【図３】本発明の第２の実施例の構成図。FIG. 3 is a configuration diagram of a second embodiment of the present invention.
【図４】図３の実施例における演算を説明する図。FIG. 4 is a view for explaining calculations in the embodiment of FIG. 3;
【図５】本発明の第３の実施例の構成図。FIG. 5 is a configuration diagram of a third embodiment of the present invention.
【図６】本発明の第４の実施例の構成図。FIG. 6 is a configuration diagram of a fourth embodiment of the present invention.
【図７】第４の実施例における各部の波形を示す図。FIG. 7 is a diagram showing waveforms at various points in a fourth embodiment.
【図８】従来技術の構成図。FIG. 8 is a configuration diagram of a conventional technique.
【図９】従来技術における各部の波形を示す図。FIG. 9 is a diagram showing waveforms of various parts according to the related art.
１…交流電源、２…コンバータ、３…三相ブリッジ型イ
ンバータ、４…負荷、５…電圧指令手段、６…電圧指令
比較手段、７…搬送波発生手段、８…比較器、１０…電
圧指令変更手段。DESCRIPTION OF SYMBOLS 1 ... AC power supply, 2 ... Converter, 3 ... Three-phase bridge type inverter, 4 ... Load, 5 ... Voltage command means, 6 ... Voltage command comparison means, 7 ... Carrier wave generation means, 8 ... Comparator, 10 ... Voltage command change means.
───────────────────────────────────────────────────── フロントページの続き (72)発明者 戸張 和明 茨城県日立市大みか町七丁目１番１号 株 式会社日立製作所日立研究所内 (72)発明者 神山 健三 茨城県日立市大みか町五丁目２番１号 株 式会社日立製作所大みか工場内 ──────────────────────────────────────────────────続 き Continuing on the front page (72) Inventor Kazuaki Tohari 7-1-1, Omika-cho, Hitachi City, Ibaraki Prefecture Inside Hitachi, Ltd. Hitachi Research Laboratory, Ltd. No. 2 In the Omika Plant of Hitachi, Ltd.
Claims (4)
ることにより直流あるいは交流の電力を可変周波数可変
電圧の電力に変換する三相の電力変換装置の制御方法に
おいて、各相の瞬時電圧指令値の中の最大値と最小値の
絶対値が等しくなるように、前記各相の瞬時電圧指令値
に等しい値を加えたものを新たな電圧指令とし、前記新
たな電圧指令に従って出力電力を制御することを特徴と
する電力変換装置の制御方法。In a control method of a three-phase power converter for converting DC or AC power to power of a variable frequency variable voltage by turning on / off a plurality of switching elements, an instantaneous voltage command value of each phase is controlled. A new voltage command is obtained by adding a value equal to the instantaneous voltage command value of each phase so that the absolute values of the maximum value and the minimum value are equal, and the output power is controlled according to the new voltage command. A method for controlling a power conversion device, comprising:
令値に加える値は、前記各相の瞬時電圧指令値の中間値
から求めるようにしたことを特徴とする電力変換装置の
制御方法。2. The method according to claim 1, wherein the value added to the instantaneous voltage command value of each phase is obtained from an intermediate value of the instantaneous voltage command values of each phase. .
ることにより直流あるいは交流の電力を可変周波数可変
電圧の電力に変換する三相の電力変換装置の制御方法に
おいて、各相の瞬時電圧指令値の中の最大値と最小値の
和が一定に成るように、前記各相の瞬時電圧指令値に等
しい値を加えたものを新たな電圧指令とし、前記新たな
電圧指令に従って出力電力を制御することを特徴とする
電力変換装置の制御方法。3. A control method of a three-phase power converter for converting a DC or AC power into a power of a variable frequency variable voltage by turning on / off a plurality of switching elements. A new voltage command is obtained by adding a value equal to the instantaneous voltage command value of each phase so that the sum of the maximum value and the minimum value becomes constant, and the output power is controlled according to the new voltage command. A method for controlling a power conversion device, comprising:
令値に加える値は、前記各相の瞬時電圧指令値の中間値
から求めるようにしたことを特徴とする電力変換装置の
制御方法。4. The method according to claim 3, wherein the value added to the instantaneous voltage command value of each phase is obtained from an intermediate value of the instantaneous voltage command values of each phase. .
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP09122098A JP3233097B2 (en) | 1998-04-03 | 1998-04-03 | Power converter and control method thereof |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP09122098A JP3233097B2 (en) | 1998-04-03 | 1998-04-03 | Power converter and control method thereof |
Related Parent Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP1242068A Division JPH0681514B2 (en) | 1989-09-20 | 1989-09-20 | Power converter and control method thereof |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPH10248262A true JPH10248262A (en) | 1998-09-14 |
| JP3233097B2 JP3233097B2 (en) | 2001-11-26 |
Family
ID=14020352
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP09122098A Expired - Lifetime JP3233097B2 (en) | 1998-04-03 | 1998-04-03 | Power converter and control method thereof |
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| Country | Link |
|---|---|
| JP (1) | JP3233097B2 (en) |
Cited By (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2006014447A (en) * | 2004-06-24 | 2006-01-12 | Toshiba Mitsubishi-Electric Industrial System Corp | Inverter device |
| EP2928070A1 (en) | 2014-04-03 | 2015-10-07 | Nidec Corporation | Motor control method and motor control apparatus |
| US9257934B2 (en) | 2012-01-12 | 2016-02-09 | Meidensha Corporation | Apparatus for parallel operation of pulse-width modulation power converters |
| US10574163B2 (en) | 2014-10-20 | 2020-02-25 | Meidensha Corporation | Three-phase neutral-point-clamped power conversion device |
| WO2020208829A1 (en) | 2019-04-12 | 2020-10-15 | 株式会社日立産機システム | Power conversion device and method for controlling same |
| WO2021224976A1 (en) | 2020-05-08 | 2021-11-11 | 株式会社日立産機システム | Power conversion device and control method thereof |
Families Citing this family (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP6303819B2 (en) * | 2014-05-29 | 2018-04-04 | 住友電気工業株式会社 | Power converter and three-phase AC power supply |
-
1998
- 1998-04-03 JP JP09122098A patent/JP3233097B2/en not_active Expired - Lifetime
Cited By (9)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2006014447A (en) * | 2004-06-24 | 2006-01-12 | Toshiba Mitsubishi-Electric Industrial System Corp | Inverter device |
| US9257934B2 (en) | 2012-01-12 | 2016-02-09 | Meidensha Corporation | Apparatus for parallel operation of pulse-width modulation power converters |
| EP2928070A1 (en) | 2014-04-03 | 2015-10-07 | Nidec Corporation | Motor control method and motor control apparatus |
| JP2015198546A (en) * | 2014-04-03 | 2015-11-09 | 日本電産株式会社 | Motor control method and motor control device |
| US9531307B2 (en) | 2014-04-03 | 2016-12-27 | Nidec Corporation | Motor control method and motor control apparatus |
| US10574163B2 (en) | 2014-10-20 | 2020-02-25 | Meidensha Corporation | Three-phase neutral-point-clamped power conversion device |
| WO2020208829A1 (en) | 2019-04-12 | 2020-10-15 | 株式会社日立産機システム | Power conversion device and method for controlling same |
| US11909341B2 (en) | 2019-04-12 | 2024-02-20 | Hitachi Industrial Equipment Systems Co., Ltd. | Power conversion device and method for controlling same |
| WO2021224976A1 (en) | 2020-05-08 | 2021-11-11 | 株式会社日立産機システム | Power conversion device and control method thereof |
Also Published As
| Publication number | Publication date |
|---|---|
| JP3233097B2 (en) | 2001-11-26 |
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