JP4893726B2 - Display device and driving method thereof - Google Patents

Description

The present invention relates to a display device of a type in which two adjacent pixels share one signal line and a driving method thereof .

  In recent years, matrix display devices such as active matrix liquid crystal display devices using thin film transistors (TFTs) as switching elements have been developed.

  This matrix display device has a scanning line driving circuit (hereinafter referred to as a gate driver) that generates a scanning signal for sequentially scanning each row of the pixel matrix. The gate driver has an operating frequency lower than that of a signal line driver circuit (hereinafter referred to as a source driver) that supplies a video signal to each column of the matrix. Therefore, the gate driver is integrally formed in the same process as the TFT that is an active element in the pixel matrix. It is also possible.

  Each pixel in such a matrix display device has a pixel electrode connected to the TFT and a common electrode to which a common voltage Vcom is applied, and is a deterioration phenomenon that occurs when an electric field in one direction is applied for a long time. In order to prevent this, inversion driving is generally performed to invert the polarity of the video signal Vsig from the source driver with respect to the common voltage Vcom for each frame, for each line, or for each dot.

  By the way, in the implementation of the matrix display device, the gate driver, the source driver, and the like are arranged around a display panel (display screen) in which a large number of pixels are arranged, and scanning lines (hereinafter referred to as gate lines) of the display panel and Wirings to signal lines (hereinafter referred to as source lines) are routed outside the display panel from each driver. It is strongly desired to reduce the wiring area of these wires, that is, to reduce the area other than the display panel (narrow frame) from the viewpoint of miniaturization of information equipment incorporating the matrix display device.

  For this reason, in particular, the area occupied by the source line can be reduced in response to the demand for narrowing the frame in the vertical direction of the display panel. Therefore, a pixel connection configuration in which the source line is halved is considered. (For example, FIG. 5 of patent document 1).

  FIG. 10 is a schematic diagram of a pixel connection example of a display panel considered as a technique for achieving such a narrow frame. In this case, one source line is shared by two adjacent pixels 100. In this case, the TFTs 102 of the two pixels 100 are connected to different gate lines. For example, in FIG. 10, the TFT 102 of the red (R) pixel 100 in the upper left is connected to the gate line G1 and the source line S1, and the TFT 102 of the green (G) pixel 100 adjacent to the right is connected to the gate line G2 and the source. Connected to line S1.

FIG. 11 is a diagram showing the order of writing the video signal Vsig to each pixel 100 in such pixel connection. In the above pixel connection, the writing of the video signal Vsig to each pixel 100 is performed in the order of the gate lines, and thus is as shown in FIG.
JP 2004-185006 A

  In the pixel connection in which the source line is halved as described above, there are a portion where the source line exists between the pixels and a portion where the source line does not exist. Largely exists. FIG. 12 is a diagram showing an equivalent circuit at this time. A voltage leak occurs between the pixels in which the inter-pixel parasitic capacitance 104 exists, so that the potential of the pixel 100 written earlier changes under the influence of the potential of the pixel 100 written later. This change in potential appears as display unevenness on the screen. Since the pixel writing order is fixed as shown in FIG. 11, display unevenness due to the occurrence of this leak always occurs at the same location.

FIG. 13 is a diagram showing an example of this display unevenness. The figure shows only the G pixel 100 for easy understanding. It is the same that the potential of the pixel 100 written earlier also changes in the black-colored pixels 100 of other colors. (Details will be described later.)
Hereinafter, the pixel potential fluctuation will be described in more detail. FIG. 14 is a diagram showing the configuration of each pixel when the display panel is a TFT LCD panel. Each pixel 100 has a liquid crystal (not shown) between a pixel electrode connected to the source line via a TFT 102 connected to the gate line and a common electrode (not shown) to which a common voltage Vcom is applied. It is sandwiched and configured. A corresponding display is realized by holding charges in the liquid crystal capacitor Clc for a field period (a frame period in the case of the non-interlace method). In order to prevent current leakage through the liquid crystal capacitor Clc and the TFT, an auxiliary capacitor Cs is provided in parallel with the liquid crystal capacitor Clc.

  FIG. 15A is a diagram showing a scanning timing chart of the gate lines G1 to G4 by the gate driver in FIG. 14, and FIG. 15B is a horizontal line that inverts the polarity of the common voltage Vcom every horizontal period. In the case of performing inversion driving, the green pixel F connected to, for example, S3 in FIG. 12 to be written first (hereinafter referred to as G-first pixel) and the red pixel to be written later in FIG. 12, for example, S2 It is a figure which shows the pixel electric potential waveform of L (henceforth the pixel after R).

  Hereinafter, a case of a normally white mode liquid crystal display device in which the transmittance is lowered (darkened) as the voltage applied to the pixel is increased will be described. In FIG. 15B, the amplitude of the common voltage Vcom is 5.0 V, the write voltage (video signal Vsig) of the pixel F ahead of G is 2.0 V (halftone) with respect to the common voltage Vcom, and after R The writing voltage (video signal Vsig) of the pixel L is 4.0 V (black, dark) with respect to the common voltage Vcom. Further, since the influence of the pull-in voltage (feedthrough voltage) ΔV generated when the TFT 102 is turned from on to off can be canceled by adjusting the common voltage Vcom (shifting Vcom downward by ΔV), FIG. This is not described in the waveform (the same applies to other pixel potential waveform diagrams described below).

  As shown in FIG. 15A, in each field, two gate lines are sequentially selected in one horizontal period, and the selected two gate lines are sequentially scanned in each horizontal period. Then, as shown in FIG. 15B, the TFT 102 connected to the selected gate line is turned on, and the video signal Vsig applied from the source line is written to the corresponding pixel 100. Accordingly, the write timing of the G-first pixel F is WG in FIG. 15B, and the write timing of the pixel L after R is WR. The pixel potential written at these write timings is maintained until it is rewritten in the next field.

  FIG. 15B shows a pixel potential waveform in an ideal state when the inter-pixel parasitic capacitance 104 is zero. However, as described above, the inter-pixel parasitic capacitance 104 exists in a place where there is no source line. FIG. 16A is a diagram showing a pixel potential waveform under the same voltage condition as FIG. 15B when the inter-pixel parasitic capacitance 104 is considered. In FIG. 16B, the common voltage Vcom has an amplitude of 5.0 V in consideration of the inter-pixel parasitic capacitance 104, and the write voltage of the pixel F ahead of the G is 2.0 V with respect to the common voltage Vcom. It is a figure which shows a pixel electric potential waveform in case the write-in voltage of the pixel L is 1.0V (white, light) with respect to the common voltage Vcom.

That is, as shown in FIGS. 16A and 16B, in the G-destination pixel F, the pixel potential written by the selection of the gate line G1 is the pixel L after the R by the selection of the gate line G2. Is written, Vc is shifted in a direction away from the common voltage Vcom (direction of darkening). The magnitude of this Vc is
Vc = (Vsig (Fn−1) + Vsig (Fn)) × Cpp / (Cs + Clc + Cpp) × α (1)
It can be expressed as In this equation (1), Vsig (Fn) is the write voltage of the pixel L after R in the current field, and Vsig (Fn−1) is the write voltage of the pixel L after R in the previous field. Accordingly, in the case of FIG. 16A, Vsig (Fn-1) + Vsig (Fn) = 8.0V, and in the case of FIG. 16B, Vsig (Fn-1) + Vsig (Fn) = 2.0V. Become. Cpp is the capacitance value of the inter-pixel parasitic capacitance 104, Cs is the capacitance value of the auxiliary capacitance Cs, Clc is the capacitance value of the liquid crystal capacitance Clc, and α is a proportional coefficient, which is a value determined by the panel structure and the like.

  Thus, as Vsig (Fn−1) + Vsig (Fn) is larger, the potential variation value Vc is larger and does not depend on the amplitude of Vcom.

  The above is the case of horizontal line inversion driving in which the polarity of the common voltage Vcom is inverted for each adjacent gate line, that is, between G2 and G3, between G4 and G5, and between G6 and G7 in FIG. For the polarity inversion of the common electrode Vcom, there is a driving method called dot inversion driving that inverts between adjacent pixels. In the pixel connection in which the source line is halved, between the G1 and G2 and between the G3 and G4 in FIG. 11 so that the polarity of the common voltage Vcom is inverted not between every adjacent gate line but between adjacent pixels. The polarity of the common voltage Vcom is inverted between G5 and G6 and between G7 and G8.

  When such dot inversion driving is performed, the results are as shown in FIGS. 17 (A) and 17 (B). Here, in FIG. 17A, the amplitude of the common voltage Vcom when the inter-pixel parasitic capacitance 104 is taken into consideration is 5.0 V, and the write voltage of the pixel F ahead of the G is 2.0 V (halftone) with respect to the common voltage Vcom. FIG. 17B is a diagram illustrating a pixel potential waveform when the write voltage of the pixel L after R is 4.0 V (black) with respect to the common voltage Vcom, and FIG. In this case, the amplitude of the common voltage Vcom is 5.0 V, the write voltage of the pixel F ahead of G is 2.0 V with respect to the common voltage Vcom, and the write voltage of the pixel L after R is 1.0 V with respect to the common voltage Vcom. It is a figure which shows a pixel electric potential waveform when it is set as (white).

  That is, as shown in FIGS. 17A and 17B, in the case of dot inversion driving, as in the case of performing the line inversion driving, in the G-destination pixel F, the gate line G1 is changed. The pixel potential written by selection is shifted by Vc when writing the pixel L after R by selection of the gate line G2, but in the case of dot inversion driving, the shifting direction is relative to the common voltage Vcom. The direction is closer (lighter).

  Also in this case, as Vsig (Fn−1) + Vsig (Fn) is larger, the potential variation value Vc is larger and is not dependent on the amplitude of Vcom, as in the case of horizontal line inversion driving. .

  Due to the above-described variation of Vc, the G-th pixel becomes darker than the actual display in the case of line inversion driving. In the case of dot inversion driving, it becomes brighter than the actual display. On the other hand, a normal voltage is written as the pixel potential of the pixel after G. Therefore, when displaying in the G raster, light and dark green are displayed every other line in the vertical direction in both inversion driving. Will end up.

  Similar fluctuations for Vc also occur in the R and B pixels.

In addition, the above is not limited to the case where the pixels 100 are arranged in a stripe arrangement , but the same applies when the pixels 100 are arranged in a delta arrangement .

  The method disclosed in Patent Document 1 cannot deal with the problem of display unevenness due to potential fluctuations that occur in pixels written earlier due to such interpixel parasitic capacitance 104.

The present invention has been made in view of the above points, and an object of the present invention is to provide a display device and a driving method thereof that can reduce display unevenness when an inter-pixel parasitic capacitance exists.

In the display device according to claim 1, the first pixel and the second pixel are arranged adjacent to each other in the row direction, and the first signal line is sandwiched in the row direction opposite to the second pixel. A third pixel adjacent to the first pixel is disposed, and a fourth pixel adjacent to the second pixel across the second signal line in a row direction opposite to the first pixel The first pixel and the third pixel share the first signal line, the second pixel and the fourth pixel share the second signal line, and And the fourth pixel are connected to a first scanning line, and the second pixel and the third pixel are connected to a second scanning line, the display device comprising: A correction circuit that outputs a signal in which a potential variation caused by the parasitic capacitance between the first pixel and the second pixel is corrected toward the pixel or the second pixel. Wherein the correction circuit, using at least a part of the gamma correction circuit that performs gamma correction of gradation, characterized in that to output said correction signal.

Display device according to claim 2, in the display device according to claim 1, wherein the correction circuit of said first pixel and the second pixel toward the pixel to be selected earlier A signal in which the potential variation is corrected is output, and a signal that does not correct the potential variation is output to a pixel to be selected later.

The display device according to claim 3, in the display device according to claim 1, wherein the correction circuit of said first pixel and the second pixel toward the pixel to be selected earlier A signal that does not correct the potential fluctuation is output, and a signal that corrects the potential fluctuation is output to a pixel to be selected later.

Display device according to claim 4, in the display device according to any one of claims 1 to 3, the correction amount of the corrected signal, and wherein Rukoto is set to a constant regardless of gradation To do.

The display device according to a fifth aspect is the display device according to any one of the first to third aspects, wherein the correction amount of the corrected signal is selectable.

The display device according to claim 6 is the display device according to any one of claims 1 to 3, wherein the correction direction of the corrected signal can be switched in accordance with a driving method. Features.

The display device according to claim 7 , wherein one signal line is arranged for every two pixels in the row direction, and two pixels adjacent to each other in the row direction across the signal line A display device that is shared and connected to different scanning lines via switching elements, and that is used to sequentially display a plurality of scanning lines, and to display information on the plurality of signal lines. A signal line driving circuit that outputs a signal in accordance with the signal line driving circuit, and a signal line driving circuit connected to a different signal line and adjacent to the pixel in the row direction. A correction circuit that outputs a signal in which a potential fluctuation due to parasitic capacitance is corrected, and the correction circuit outputs the corrected signal by using at least a part of a gamma correction circuit that performs gamma correction of gradation. is, the row direction Of the two pixels disposed adjacent, toward the pixel to be selected first, the corrected signal the potential variation, characterized in that to output to the signal line driver circuit.

The display device according to claim 8 , wherein one signal line is arranged for every two pixels in the row direction, and two pixels adjacent to each other in the row direction across the signal line are connected to the signal line. A display device that is shared and connected to different scanning lines via switching elements, and that is used to sequentially display a plurality of scanning lines, and to display information on the plurality of signal lines. A signal line driving circuit that outputs a signal in accordance with the signal line driving circuit, and a signal line driving circuit connected to a different signal line and adjacent to the pixel in the row direction. A correction circuit that outputs a signal in which a potential fluctuation due to parasitic capacitance is corrected, and the correction circuit outputs the corrected signal by using at least a part of a gamma correction circuit that performs gamma correction of gradation. is, the row direction Towards pixels to be selected for the two pixels disposed adjacent, later, the corrected signal the potential variation, characterized in that to output to the signal line driver circuit.

The display device according to claim 9 , wherein the first pixel column and the second pixel column are disposed adjacent to each other in the row direction, and the first signal line is disposed in the row direction opposite to the second pixel column. A third pixel column adjacent to the first pixel column is disposed across the first pixel column, and the second pixel column is disposed across the second signal line in a row direction opposite to the first pixel column. An adjacent fourth pixel column is disposed, the first pixel column and the third pixel column share the first signal line, and the second pixel column and the fourth pixel column are Sharing the second signal line, the first pixel column and the fourth pixel column are connected to a first scanning line corresponding to each pixel row for each pixel row, and the second pixel column And the third pixel column is different from the first scanning line for each pixel row and is connected to a second scanning line corresponding to each pixel row, the display device comprising: Picture For the column or the second pixel column, the potential variation caused by the parasitic capacitance generated between two pixels adjacent in the row direction in the first pixel column and the second pixel column a correction circuit for outputting the corrected signals, corresponding to different color components from each other between the two pixels in which each pixel in the first pixel row or the second row of pixels adjacent in the column direction, the correction The circuit is characterized in that the corrected signal is output using at least a part of a gamma correction circuit for performing gamma correction of gradation .

The display device according to claim 10 is the display device according to claim 9 , wherein color components of two pixels adjacent in the row direction between the first pixel column and the second pixel column. Are different from each other, and the combination of the different color components is equal every two pixel rows.

The display device driving method according to claim 11 , wherein the first pixel and the second pixel are arranged adjacent to each other in the row direction, and the first signal line is arranged in the row direction opposite to the second pixel. A third pixel adjacent to the first pixel is disposed across the first pixel, and a fourth pixel adjacent to the second pixel across the second signal line in a row direction opposite to the first pixel. Are arranged, the first pixel and the third pixel share the first signal line, the second pixel and the fourth pixel share the second signal line, A driving method of a display device in which the first pixel and the fourth pixel are connected to a first scanning line, and the second pixel and the third pixel are connected to a second scanning line. Te, using at least a part of the gamma correction circuit that performs gamma correction of gradation, toward the first pixel or the second pixel, the first pixel And outputting the corrected signal potential variation caused by the parasitic capacitance between the second pixel.

A display device driving method according to a twelfth aspect is the display device driving method according to the eleventh aspect , wherein a pixel to be selected first is selected from the two pixels adjacently arranged in the predetermined direction. A signal in which the potential variation is corrected is output toward the pixel, and a signal that does not correct the potential variation is output toward a pixel to be selected later.

A display device driving method according to a thirteenth aspect is the display device driving method according to the eleventh aspect , wherein a pixel to be selected first is selected from the two pixels adjacently arranged in the predetermined direction. A signal that does not correct the potential variation is output toward the pixel, and a signal that corrects the potential variation is output toward a pixel to be selected later.

According to the present invention, it is possible to reduce the write potential difference between pixels and reduce display unevenness.

  The best mode for carrying out the present invention will be described below with reference to the drawings.

[First Embodiment]
FIG. 1A is a schematic configuration diagram showing an overall configuration of the matrix display device according to the first embodiment of the present invention, and FIG. 1B is a diagram of pixel connection of the LCD panel in FIG. FIG.

  That is, as shown in FIG. 1A, the matrix display device according to this embodiment includes an LCD panel 10 in which a plurality of pixels are arranged, a driver circuit 12 that drives and controls each pixel of the LCD panel 10, And a Vcom circuit 14 for applying a common voltage Vcom to the LCD panel 10.

  As shown in FIG. 1B, the LCD panel 10 includes a plurality of source lines S1 to S480 and a plurality of gate lines X1 to X480 arranged in a matrix, and one source line is adjacent to two pixels 16. A plurality of pixels 16 are arranged so as to be shared. In this case, the TFTs 18 of the two pixels 16 are connected to different gate lines. For example, in FIG. 1B, the TFT 18 of the upper left R pixel 16 is connected to the gate line X1 and the source line S1, and the TFT 18 of the G pixel 16 adjacent to the right is connected to the gate line X2 and the source line S1. It is connected. Here, a case where the pixels 16 are arranged in a delta arrangement is shown.

  The plurality of source lines S1 to S480 and the plurality of gate lines X1 to X480 of the LCD panel 10 are connected to the driver circuit 12 by wirings 20 routed on a substrate (not shown) of the LCD panel 10.

  FIG. 2 is a block configuration diagram of the driver circuit in FIG. The driver circuit 12 includes a gate driver block 22, a source driver block 24, a level shifter circuit 26, a timing generator (hereinafter abbreviated as TG) logic circuit 28, and a gamma (hereinafter abbreviated as γ). ) It is composed of a circuit block 30, a charge pump / regulator block 32, an analog block 34, and other blocks.

  Here, the gate driver block 22 sequentially selects the plurality of gate lines X1 to X480 of the LCD panel 10, and the source driver block 24 should be displayed on the plurality of signal lines S1 to S480 of the LCD panel 10. The video signal Vsig according to the information is output.

  The level shifter circuit 26 shifts the level of an externally supplied signal to a predetermined level. The TG unit logic circuit 28 generates a necessary timing signal and control signal based on the signal shifted to a predetermined level by the level shifter circuit 26 and a signal supplied from the outside, and supplies it to each unit in the driver circuit 12. To do.

  The γ circuit block 30 is for performing γ correction so that the video signal Vsig output from the source driver block 24 has good gradation characteristics.

  The charge pump / regulator block 32 generates various voltages of a required logic level from an external power supply, and the analog block 34 further generates various voltages from the voltage generated by the charge pump / regulator block 32. Is. The Vcom circuit 14 generates the common voltage Vcom from the voltage VVCOM generated in the analog block 34. Since the other blocks are not directly related to the present invention, the description thereof is omitted.

  FIG. 3A is a diagram showing a configuration of the gate driver block 22 in FIG. For simplification of explanation and illustration, the description here assumes that there are eight gate lines. In this case, the gate driver block 22 includes a 3-bit counter 36, nine AND gates, two OR gates, three NOT gates, and one NAND gate.

  That is, a gate clock and an up / down (hereinafter abbreviated as U / D) signal are supplied from the TG unit logic circuit 28 to the 3-bit counter 36. The U / D signal is “1” at the time of non-inverted shift which is a normal display, and “0” at the time of upside-down inverted shift in which a vertically inverted display is performed. This is because the scanning direction of the gate line is reversed upside down in the non-inversion shift and the upside down shift, and as a result, the pixel written first and the pixel written later are opposite, and the operation is accordingly performed. This is because it is necessary to switch.

  The Q1 output of the 3-bit counter 36 is supplied to an AND gate for even-numbered gate lines X2, X4, X6, and X8 via an OR gate. An output signal of an AND gate that performs a logical operation between the U / D signal and a gate double (hereinafter referred to as GDOUBLE) signal supplied from the TG unit logic circuit 28 is supplied to the OR gate. Here, the GDOUBLE signal is “0” in the normal mode, which is a normal display state, and “2” in the gate double writing mode in which the display unevenness reduction driving (hereinafter referred to as “gate double writing driving”) according to this embodiment is performed. 1 ". The Q1 output of the 3-bit counter 36 is further supplied to an AND gate for odd-numbered gate lines X1, X3, X5, and X7 via a NAND gate. The NAND gate is supplied with an output signal of an OR gate gate that performs a logical operation of the U / D signal and a signal obtained by inverting the GDOUBLE signal at the NOT gate, and the output of the NAND gate is an odd number of gate lines X1, X3. , X5, and X7.

  The Q2 output of the 3-bit counter 36 is supplied to the AND gates for the gate lines X3, X4, X7, and X8, and via the NOT gate, the AND for the gate lines X1, X2, X5, and X6. Given to the gate.

  The Q3 output of the 3-bit counter 36 is supplied to the AND gates for the gate lines X5, X6, X7, and X8, and via the NOT gate, the AND for the gate lines X1, X2, X3, and X4. Given to the gate.

  FIG. 3B is a diagram showing a timing chart at the time of non-inversion shift in the gate double writing mode in the gate driver block 22 having such a configuration. FIG. 3C is also a timing chart at the time of upside down shift.

  At the time of non-inversion shift, as shown in FIG. 3B, the odd-numbered gate lines X1, X3, X5, and X7 have an even-numbered gate line X2, X4, X6 for a period corresponding to one gate clock. , X8, H signals are output in order for a period corresponding to two gate clocks. That is, in terms of timing, the gate lines X1 and X2 are in the selected state → the gate line X2 is in the selected state → the gate lines X3 and X4 are in the selected state → the gate line X4 is in the selected state → the gate lines X5 and X6 are in the selected state → the gate line X6 is selected → gate lines X7 and X8 are selected → gate line X8 is selected.

  At the time of upside down shift, as shown in FIG. 3C, the even-numbered gate lines X2, X4, X6, and X8 have a period corresponding to one generation of the gate clock, as shown in FIG. For X3, X5, and X7, H signals are sequentially output in the opposite directions during a period corresponding to two gate clocks. That is, in terms of timing, the gate lines X8 and X7 are selected → the gate line X7 is selected → the gate lines X6 and X5 are selected → the gate line X5 is selected → the gate lines X4 and X3 are selected → the gate line X3 is selected → gate lines X2 and X1 are selected → gate line X1 is selected.

  FIG. 4A is a diagram showing a scanning timing chart at the time of non-inversion shift in the gate double writing mode in this embodiment corresponding to FIG.

  FIGS. 4B and 4C show green lines connected to, for example, S3 in FIG. 1B written earlier when horizontal line inversion driving is performed to invert the polarity of the common voltage Vcom every horizontal period. FIG. 3 is a diagram showing pixel potential waveforms of a pixel Fg (hereinafter referred to as a G-first pixel) and a red pixel Lr (hereinafter referred to as a pixel after R) connected to, for example, S2 in FIG. It is.

  In this case, as will be described later, a blue pixel Fb (hereinafter referred to as a B-first pixel) connected to the same S2 as, for example, the red pixel Lr in FIG.

  At this time, since the gate lines are selected as described above, in each field, two gate lines corresponding to two adjacent pixels connected to different signal lines are simultaneously selected in one horizontal period. Thereafter, only one gate line corresponding to the pixel to be selected later is selected from the two pixels.

  FIG. 4B shows a case where the amplitude of the common voltage Vcom is 5.0 V and the write voltage (video signal) of the G-destination pixel Fg when horizontal line inversion driving is performed to invert the polarity of the common voltage Vcom every horizontal period. Vsig) is 2.0 V (halftone) with respect to the common voltage Vcom, the write voltage (video signal Vsig) of the pixel Lr after R is 4.0 V (black) with respect to the common voltage Vcom, and the B-th pixel FIG. 4C is a diagram showing a pixel potential waveform when the writing voltage of Fb (video signal Vsig) is 2.0 V (halftone) with respect to the common voltage Vcom, and FIG. 4C shows the amplitude of the common voltage Vcom. Is 5.0V, the write voltage of the pixel Fg ahead of G is 2.0V with respect to the common voltage Vcom, the write voltage of the pixel Lr after R is 1.0V (white) with respect to the common voltage Vcom, and B ahead Pixel F The write voltage (video signal Vsig) is a diagram showing a pixel potential waveform when the 2.0 V (halftone), with respect to the common voltage Vcom.

  In the present embodiment, by performing scanning of the gate line as shown in FIG. 4A, as shown in FIGS. 4B and 4C, the B pixel Fb and the R pixel Lr as shown in FIGS. Share a single source line S2 (signal line), so that the write potential of the B-destination pixel Fb is also applied to the post-R pixel Lr during the period in which the gate line X1 and the gate line X2 are selected simultaneously. This is applied and writing is also performed on the pixel Lr after the R, so that the same potential as that of the B-th pixel Fb is obtained. Then, when only the subsequent gate line X2 is selected, the write voltage of the post-R pixel Lr is output to the source line, and the voltage of the voltage that should originally be written to the post-R pixel Lr from the B-th pixel potential. Writing will be performed.

Also in this embodiment, since the inter-pixel parasitic capacitance Cpp exists as in the conventional case, in the G-destination pixel Fg, the pixel potential written by the selection of the gate line X1 is selected only for the gate line X2, When the voltage that should originally be written to the pixel Lr after R is written to the pixel Lr after R, the voltage shifts in a direction away from the common voltage Vcom (direction of darkening) by Vc. In the embodiment, the magnitude of this potential fluctuation Vc is
Vc = (Vsig (X2) −Vsig (X1)) × Cpp / (Cs + Clc + Cpp) × α (2)
It can be expressed as In this equation (2), Vsig (X2) is the write voltage of the pixel Lr after R when only X2 is selected, and Vsig (X1) is the write of the pixel Bb ahead of B when X1 and X2 are selected simultaneously Voltage. Others are the same as the above-mentioned formula (1).

  Therefore, in this embodiment, it is affected not only by the pixel potential of the previous field but by the potential of the pixel Fb of the adjacent pixel connected to the same signal line. In the case of FIG. 4B, Vsig (X2) −Vsig (X1) = 4.0−2.0 = 2.0V, and in the case of FIG. 4C, Vsig (X2) −Vsig (X1) = 1.0−2.0 = −1.0V. As a result, the absolute value of the potential fluctuation Vc due to the inter-pixel capacitance Cpp can be made smaller than before, and display unevenness can be reduced.

(The conventional case corresponds to FIGS. 15A and 15B and is 8.0 V and 2.0 V, respectively.)
Generally, when the pixel voltage with respect to the common voltage Vcom changes in the range of 1.0 V (white) to 4.0 V (black),
Vsig (Fn-1) + Vsig (Fn) in the formula (1) is in the range of 2.0V to 8.0V,
In the formula (2), Vsig (X2) −Vsig (X1) is in the range of −3.0V to 3.0V.

  As described above, according to the present embodiment, the absolute value of the Vc is small, so that the potential fluctuation Vc due to the inter-pixel parasitic capacitance Cpp can be made smaller than in the conventional case, and display unevenness can be reduced. Can do.

  When the potential difference between adjacent pixels connected to the same signal line is large, for example, the writing voltage of the G-destination pixel Fg is 4.0 V (black) with respect to the common voltage Vcom, and the writing of the pixel Lr after R If the voltage is 1.0 V (white) with respect to the common voltage Vcom and the write voltage of the B-th pixel Fb is 4.0 V (black) with respect to the common voltage Vcom, this embodiment In some cases, the potential fluctuation Vc is larger in the form than in the conventional example.

(Vsig (X2) −Vsig (X1) = 1.0−4.0 = −3.0V
Vsig (Fn-1) + Vsig (Fn) = 1.0 + 1.0 = 2.0V)
However, the G-destination pixel Fg affected in this case has a sufficiently saturated black level, and the potential fluctuation Vc cannot be visually recognized on the display, so that this does not cause a problem. Further, the pixel Lr after R which has an influence, the white level, and the pixel Fb ahead B are also at the black level. In this case, the screen display is an extremely bright R raster screen. The previous potential fluctuation is more difficult to see on the display. Therefore, the absolute value of the potential fluctuation Vc may be larger in the present embodiment than in the conventional example, but such a case is not a practical problem.

  Similarly, since the scanning direction is only reversed during the up / down inversion shift, similarly, the potential fluctuation Vc due to the inter-pixel parasitic capacitance Cpp can be made smaller than in the conventional case, and display unevenness can be reduced. it can.

  If necessary, the normal mode according to the conventional method and the gate double writing mode according to the present embodiment may be switched by the GDOUBLE signal.

  In that case, the case of the special display screen as described above can be appropriately handled.

  The above is the case of horizontal line inversion driving. Similarly, in the case of pseudo dot inversion driving (dot inversion driving in a delta arrangement corresponding to dot inversion driving in a stripe arrangement), the potential fluctuation Vc due to the inter-pixel parasitic capacitance Cpp is also the same. Can be made smaller than conventional ones, and display unevenness can be reduced.

  The same applies not only when the pixels 16 are arranged in a delta arrangement but also in a stripe arrangement.

  In the case where the pixels 16 are arranged in a delta arrangement, display unevenness (for example, vertical stripes corresponding to FIG. 13) meanders compared to the case where the pixels 16 are arranged in a stripe arrangement.

[Second Embodiment]
Next, a second embodiment of the present invention will be described.

  In the present embodiment, the potential variation Vc due to the inter-pixel parasitic capacitance Cpp is canceled out by correcting the potential variation Vc due to the inter-pixel parasitic capacitance Cpp in advance, thereby eliminating the display unevenness. is there.

  Here, a case where the γ circuit block 30 originally provided in the driver circuit 12 is used as a correction method is considered. A case of a still image in which unevenness is conspicuous will be described.

  As shown in FIG. 2, the driver circuit 12 includes a γ circuit block 30. FIG. 5 is a diagram showing a circuit configuration of the γ circuit block 30. As shown in the figure, the γ circuit block 30 includes a gamma curve resistor 38 and a tap switch (hereinafter referred to as TAPSW) 40. The gamma curve resistor 38 is tapped so that a potential corresponding to the γ curve is taken out, and a voltage value corresponding to the gradation of the pixel data is supplied to the source driver block 24 by the TAPSW 40. The source driver block 24 includes a digital / analog conversion circuit (hereinafter referred to as DAC) 42 and a source output amplifier 44. The DAC 42 converts a voltage value corresponding to the gradation of the pixel data into an analog signal, and a source output amplifier. A write voltage (video signal Vsig) is output to the corresponding source line of the LCD panel 10 via the display 44. The amplitude adjustment signals VRH1, VRH2, VRL1, and VRL2 that are inputs to the γ circuit block 30 are switched and supplied from the TG logic circuit 28 according to the polarity of POL (reverse of the common voltage Vcom).

  6A and 6B are diagrams showing a γ curve of the γ circuit block 30 when POL is L, that is, when the common voltage Vcom is H, and FIG. It is a figure which shows the gamma curve when the voltage Vcom is L. In these drawings, the “no correction” γ curve indicates the γ curve in the normal mode in which the correction of the potential fluctuation Vc according to the present embodiment is not performed. In contrast, in the present embodiment, a γ curve indicated as “with correction” can be selected in a mode for correcting the potential fluctuation Vc (hereinafter referred to as a data shift mode). This “corrected” γ curve is the same as the “uncorrected” γ curve in a direction where the output voltage is increased in FIG. In B), the output voltage is shifted by a certain value in the direction in which the output voltage decreases.

  This constant value is a value corresponding to Vc in the case of Vsig (Fn-1) = Vsig (Fn) in the equation (1) with respect to the gradation (halftone) where unevenness is easily noticeable.

  FIG. 6C is a diagram showing the relationship of the output voltage with respect to the amplitude adjustment signals VRH1, VRH2, VRL1, and VRL2 in the data shift mode, and FIG. 6D is a diagram showing the shift amount. FIG. 7A is a timing chart at the time of non-inversion shift, and FIG. 7B is a timing chart at the time of vertical inversion shift.

  Such a “corrected” γ curve can be created very simply because the voltage on the upper side and the lower side of the DAC 42 need only be shifted by a certain value.

  As shown in FIGS. 6C, 7A, and 7B, in this embodiment, two gate lines are sequentially selected in one horizontal period as in the prior art, and the selected gate lines are selected. A corresponding write voltage (video signal Vsig) is output. At that time, in the γ circuit block 30, the “uncorrected” γ curve is applied to the write voltage corresponding to one gate line, and the “corrected” γ curve is applied to the write voltage corresponding to the other gate line. To do. The γ circuit block 30 discriminates the switching timing of the gate line based on the G1STH signal, which is given from the TG unit logic circuit 28 and is H in the first half of the horizontal period and L in the second half.

  The data shift signal DSHIFT is input from the TG unit logic circuit 28 to the γ circuit block 30. As shown in FIG. 6D, the shift amount is set by the LSB2 bits of the data shift signal DSHIFT. This is to enable the driver circuit 12 to be applied to a plurality of LCD panels 10, and the shift amount is selected by the connected driver circuit 12. In addition, the MSB1 bit of the data shift signal DSHIFT sets whether to apply the “corrected” γ curve to the write voltage corresponding to the previous or subsequent gate line. This corresponds to the appearance of the potential fluctuation Vc due to the influence of the inter-pixel parasitic capacitance Cpp depending on the inversion driving method of the common electrode Vcom, and the contrast is reversed between the line inversion driving and the (pseudo) dot inversion driving. Because. Specifically, in the case of line inversion driving, a γ curve of “with correction” is applied to the previous writing voltage, and in the case of (pseudo) dot inversion driving, “with correction” is applied to the subsequent writing voltage. "Γ curve" is applied.

  FIG. 8A is a diagram showing a scanning timing chart at the time of non-inversion shift in the data shift mode in the present embodiment corresponding to FIG. At this time, as in FIG. 15A, in each field, two gate lines are sequentially selected in one horizontal period, and the selected two gate lines are sequentially scanned in each horizontal period.

  In FIG. 8B, in the case of performing horizontal line inversion driving, the amplitude of the common voltage Vcom is 5.0 V, and the write voltage (video signal Vsig) of the pixel Fg ahead G is 2.0 V (with respect to the common voltage Vcom). FIG. 6 is a diagram illustrating a pixel potential waveform when the write voltage (video signal Vsig) of the post-R pixel Lr is 4.0 V (black) with respect to the common voltage Vcom.

  In this case, the “corrected” γ curve is applied to the previous write voltage by the MSB1 bit of the data shift signal DSHIFT.

  Therefore, for the G-destination pixel Fg in the 1st field, since POL = H, that is, Vcom = L, the “corrected” γ curve of VRH2S is applied as VRH2 and VRL2S is applied as VRL2, and the G-destination pixel Fg is written. The voltage (video signal Vsig) is not 2.0V with respect to the common voltage Vcom, but is 2.0V-Vc. Then, for the post-R pixel Lr, the “no correction” γ curve of VRH2N as VRH2 and VRL2N as VRL2 is applied, and the write voltage (video signal Vsig) of the post-R pixel Lr is 4 with respect to the common voltage Vcom. 0.0V. When writing the pixel Lr after R, the potential of the pixel Fg ahead of G varies by Vc due to the inter-pixel parasitic capacitance Cpp, but becomes (2.0V−Vc) + Vc, and as a result, the common voltage Vcom is set. On the other hand, a desired pixel potential of 2.0V is obtained.

  In the 2nd field, since POL = L, that is, Vcom = H, for the G-destination pixel Fg, the “corrected” γ curve of VRH1S is applied as VRH1 and VRL1S is applied as VRL1, and the G-destination pixel Fg Write voltage (video signal Vsig) is not 2.0V with respect to the common voltage Vcom, but is 2.0V-Vc. Then, for the post-R pixel Lr, the “no correction” γ curve of VRH1N as VRH1 and VRL1N as VRL1 is applied, and the write voltage (video signal Vsig) of the post-R pixel Lr is 4 with respect to the common voltage Vcom. 0.0V. At the time of writing the pixel Lr after R, the potential of the pixel Fg ahead of the G varies by Vc due to the inter-pixel parasitic capacitance Vpp, but becomes (2.0V−Vc) + Vc, and as a result, the common voltage Vcom is set. On the other hand, a desired pixel potential of 2.0V is obtained.

  As described above, the pre-written pixel potential is corrected and written in advance by the potential variation Vc due to the inter-pixel parasitic capacitance Cpp, so that the potential variation Vc due to the inter-pixel parasitic capacitance Cpp can be offset and display unevenness can be eliminated. In addition, by using the γ circuit block 30 included in the driver circuit 12, a practical effect can be easily obtained without adding another circuit.

[Modification of Second Embodiment]
In the second embodiment, the potential variation Vc due to the inter-pixel parasitic capacitance Cpp is canceled by previously correcting and writing the pre-written pixel potential by the potential variation Vc due to the inter-pixel parasitic capacitance Cpp. The unevenness may be eliminated as shown in FIG.

  FIG. 9A is a diagram showing a scanning timing chart at the time of non-inversion shift in the data shift mode, as in FIG. 8A. FIG. 9B is a diagram in the case of performing horizontal line inversion driving. The amplitude of the common voltage Vcom is 5.0 V, the write voltage (video signal Vsig) of the pixel Fg ahead of G is 2.0 V (halftone) with respect to the common voltage Vcom, and the write voltage of the pixel Lr after R (video signal Vsig) ) Is a diagram showing a pixel potential waveform when the common voltage Vcom is 4.0 V (black).

In the modification of the second embodiment, as shown in FIG. 9B, the pixel potential of the subsequent writing is corrected and written by the potential variation Vc ′ due to the inter-pixel parasitic capacitance Cpp without correcting the writing of the previous writing. In this way, the potential of both adjacent pixels is changed by Vc ′ to eliminate display unevenness. (In this case, since the pixel potential of the later writing becomes larger by the amount of correction than in the case of the second embodiment, the actual correction value may be set slightly larger than the correction value of the second embodiment. Vc ′ is preferably 1 / (1− (Cpp / (Cs + Clc + Cpp) × α)) × Vc.)
In this case, the entire screen becomes an image shifted by the potential variation Vc ′ due to the inter-pixel parasitic capacitance Cpp. However, since the potential variation Vc ′ is a minute voltage that is about two orders of magnitude smaller than the write voltage Vsig in the first place, Even if the overall voltage is shifted, there is no practical problem.

  Also in this case, by using the γ circuit block 30 included in the driver circuit 12, a practical effect can be easily obtained without adding another circuit.

  The above is the case of horizontal line inversion driving. However, in the case of (pseudo) dot inversion driving, the MSB bit of the data shift signal DSHIFT is set to 1, so that “γ” is “corrected” with respect to the subsequent writing voltage. As in the case of the horizontal line inversion driving, a curve is applied, and the potential fluctuation Vc due to the inter-pixel parasitic capacitance Cpp can be made smaller than in the conventional case, and display unevenness can be reduced.

  As described above, if the correction value is corrected to a constant value for all the gradations in accordance with the gradation (halftone) of the portion where unevenness is easily noticeable, a sufficient effect can be obtained while simplifying the circuit. Obtainable.

  Furthermore, since the correction amount can be easily switched (as shown in FIG. 6D), it is possible to flexibly cope with liquid crystals having different inter-pixel parasitic capacitances.

  In addition, since the correction direction can be easily switched corresponding to the upside down mode (as shown in FIGS. 6 and 7), it can be applied to various drive modes including the polarity inversion mode. It can respond flexibly.

  In this way, the problem of display unevenness due to potential fluctuations generated in the pixels written earlier due to the inter-pixel parasitic capacitance is appropriately utilized by diverting a gamma correction circuit for gradation originally provided in the drive circuit. Since the problem is solved by outputting the corrected signal, it is not necessary to mount a new circuit, and it is possible to realize a good display without unevenness in a small space and at a low cost.

  Although the present invention has been described above based on the embodiments, the present invention is not limited to the above-described embodiments, and various modifications and applications are naturally possible within the scope of the gist of the present invention.

  For example, the technique based on the double gate writing in the first embodiment and the technique based on the data shift in the second embodiment may be combined.

  In the second embodiment, the γ circuit block is used to correct the potential fluctuation in advance, but it is needless to say that the correction may be performed by another circuit.

  In the second embodiment, the correction voltage is created so as to shift by a constant value regardless of the gradation. However, the correction amount corresponding to the equation (1) is calculated according to the gradation, and an appropriate correction voltage is set. You may make it create. In this case as well, it can be easily realized by using the γ circuit block 30 and switching the selection method of the TAPSW 40 of the gamma curve resistance according to the gradation.

  Further, for example, in order to cope with a moving image of Vsig (Fn−1) ≠ Vsig (Fn), it can be realized by using a circuit including a field memory.

  In the above, the case of normally white liquid crystal has been described. However, in the case of normally black liquid crystal in which the transmittance increases (becomes brighter) as the voltage applied to the pixel increases, the direction of light and darkness is merely reversed. Is applicable as well.

  Furthermore, it goes without saying that the switching element is not limited to a TFT but may be a diode or the like.

  Further, if the pixels of the matrix display device are not limited to liquid crystals but are capacitive elements, parasitic capacitance between the pixels is generated, and display unevenness can be similarly reduced by the present invention.

(A) is a schematic block diagram which shows the whole structure of the matrix display apparatus which concerns on 1st Embodiment of this invention, (B) is the schematic of the pixel connection of the LCD panel in (A). FIG. 2 is a block configuration diagram of a driver circuit in FIG. (A) is a figure which shows the structure of the gate driver block in FIG. 2, (B) is a figure which shows the timing chart at the time of the non-inversion shift in the gate double writing mode in the gate driver block of (A). (C) is a figure which similarly shows the timing chart at the time of a vertical inversion shift. 2A and 2B show waveforms according to the first embodiment of the present invention, in which FIG. 2A is a diagram showing a scanning timing chart at the time of non-inversion shift in the gate double writing mode, and FIG. When performing, the amplitude of the common voltage is 5.0 V, the write voltage of the G-first pixel is 2.0 V with respect to the common voltage, the write voltage of the pixel after R is 4.0 V with respect to the common voltage, and the B-point FIG. 6C is a diagram showing a pixel potential waveform when the pixel write voltage is 2.0 V with respect to the common voltage, and FIG. 6C is the common voltage amplitude of 5 V, and the G pixel write voltage is the common voltage. On the other hand, the pixel potential waveform is 2.0 V, the writing voltage of the pixel after R is 1.0 V with respect to the common voltage, and the writing voltage of the pixel ahead B is 2.0 V with respect to the common voltage. FIG. It is a figure which shows the circuit structure of (gamma) circuit block in the matrix display apparatus which concerns on 2nd Embodiment of this invention. (A) is a figure which shows the γ curve of the normal mode and data shift mode when POL is L in the γ circuit block, and (B) is also the γ curve of the normal mode and data shift mode when POL is H. (C) is a diagram showing the relationship of the output voltage with respect to the amplitude adjustment signal in the data shift mode, (D) is a diagram showing the shift amount. (A) is a figure which shows the timing chart at the time of non-inversion shift, (B) is a figure which shows the timing chart at the time of up-down inversion shift. FIG. 5A shows a waveform according to a second embodiment of the present invention, where FIG. 9A is a diagram showing a scanning timing chart during non-inversion shift in the data shift mode, and FIG. 5B is a case where horizontal line inversion driving is performed. Pixel potential waveform when the amplitude of the common voltage at 5.0 V is 2.0 V, the write voltage of the G-first pixel is 2.0 V with respect to the common voltage, and the write voltage of the pixel after R is 4.0 V with respect to the common voltage. FIG. FIG. 6A shows a waveform according to a modification of the second embodiment of the present invention, and FIG. 5A is a diagram showing a scanning timing chart at the time of non-inversion shift in the data shift mode, and FIG. In the case where the amplitude of the common voltage is 5.0 V, the write voltage of the G-first pixel is 2.0 V with respect to the common voltage, and the write voltage of the pixel after R is 4.0 V with respect to the common voltage. It is a figure which shows a pixel electric potential waveform. It is the schematic which shows the pixel connection of the display panel which halved the source line in the conventional matrix display apparatus. It is a figure which shows the order which writes a video signal in each pixel in the pixel connection of FIG. It is a figure which shows the equivalent circuit of the display panel of FIG. It is a figure which shows the example of the display nonuniformity in the display panel of FIG. It is a figure which shows the structure of each pixel at the time of using a display panel as a TFTLCD panel. (A) is a diagram showing a scanning timing chart, and (B) is a diagram showing a pixel potential waveform in horizontal line inversion driving when there is no inter-pixel parasitic capacitance. FIG. 6 is a diagram showing a pixel potential waveform in horizontal line inversion driving in consideration of the inter-pixel parasitic capacitance. In particular, (A) shows that the amplitude of the common voltage is 5.0 V, and the write voltage of the G ahead pixel is relative to the common voltage. FIG. 5B is a diagram illustrating a case where the writing voltage of the pixel after 2.0V is set to 4.0V with respect to the common voltage, and FIG. FIG. 5 is a diagram showing a pixel potential waveform when the common voltage is 2.0 V and the write voltage of the pixel after R is 1.0 V with respect to the common voltage. FIG. 6 is a diagram showing a pixel potential waveform in dot inversion driving in consideration of the inter-pixel parasitic capacitance, and in particular, (A) shows that the amplitude of the common voltage is 5.0 V, and the write voltage of the G-th pixel is relative to the common voltage FIG. 5B is a diagram illustrating a pixel potential waveform when a writing voltage of a pixel after 2.0 V and R is 4.0 V with respect to the common voltage, and FIG. FIG. 6 is a diagram illustrating a pixel potential waveform when the write voltage of 2.0 V is 2.0 V with respect to the common voltage and the write voltage of the pixel after R is 1.0 V with respect to the common voltage.

Explanation of symbols

    DESCRIPTION OF SYMBOLS 10 ... LCD panel, 12 ... Driver circuit, 14 ... Vcom circuit, 16 ... Pixel, 18 ... TFT, 20 ... Wiring, 22 ... Gate driver block, 24 ... Source driver block, 26 ... Level shifter circuit, 28 ... Timing generator (TG) ) Part logic circuit, 30 ... gamma (γ) circuit block, 32 ... regulator block, 34 ... analog block, 36 ... 3-bit counter, 38 ... gamma curve resistance, 40 ... tap switch (TAPSW), 42 ... digital / analog conversion Circuit (DAC) 44 ... Source output amplifier F ... G first pixel, L ... R post pixel, Fg ... G pre pixel, Lr ... R post pixel, Fb ... B pre pixel.

Claims (13)

A first pixel and a second pixel are arranged adjacent to each other in the row direction;
A third pixel adjacent to the first pixel is disposed in a row direction opposite to the second pixel with the first signal line interposed therebetween;
In the row direction opposite to the first pixel, a fourth pixel that is adjacent to the second pixel across the second signal line is disposed,
The first pixel and the third pixel share the first signal line;
The second pixel and the fourth pixel share the second signal line;
The first pixel and the fourth pixel are connected to a first scan line;
The display device in which the second pixel and the third pixel are connected to a second scanning line,
A correction circuit that outputs a signal in which a potential variation caused by a parasitic capacitance between the first pixel and the second pixel is corrected toward the first pixel or the second pixel ;
The display device , wherein the correction circuit outputs the corrected signal using at least a part of a gamma correction circuit that performs gamma correction of gradation . The correction circuit includes:
Of the first pixel and the second pixel, a signal in which the potential variation is corrected is output toward the pixel to be selected first, and the potential variation is directed toward the pixel to be selected later. The display device according to claim 1, wherein a signal without correcting the minute is output. The correction circuit includes:
Of the first pixel and the second pixel, a signal that does not correct the potential variation is output to a pixel to be selected first, and the pixel to be selected later is output. The display device according to claim 1, wherein a signal in which the potential variation is corrected is output. The correction amount of the correction signal, the display device according to any one of claims 1 to 3, wherein Rukoto is set to a constant regardless of gradation.   The display device according to claim 1, wherein the correction amount of the corrected signal is selectable.   The display device according to claim 1, wherein the correction direction of the corrected signal can be switched in accordance with a driving method. One signal line is arranged for every two pixels in the row direction,
Two pixels that are adjacent to each other in the row direction across the signal line share the signal line and are connected to different scanning lines via switching elements, respectively,
A scanning line driving circuit for sequentially selecting a plurality of the scanning lines;
A signal line driving circuit for outputting a signal according to information to be displayed to the plurality of signal lines;
To the signal line driving circuit, a signal in which potential fluctuation due to inter-pixel parasitic capacitance is corrected is output to one of two pixels connected to different signal lines and adjacently arranged in the row direction. A correction circuit for causing
The correction circuit outputs the corrected signal by using at least a part of a gamma correction circuit that performs gradation gamma correction, and is selected first from two pixels adjacently arranged in the row direction. A display device, wherein a signal in which the potential fluctuation is corrected is output to the signal line driver circuit toward a pixel to be processed. One signal line is arranged for every two pixels in the row direction,
Two pixels that are adjacent to each other in the row direction across the signal line share the signal line and are connected to different scanning lines via switching elements, respectively,
A scanning line driving circuit for sequentially selecting a plurality of the scanning lines;
A signal line driving circuit for outputting a signal according to information to be displayed to the plurality of signal lines;
To the signal line driving circuit, a signal in which potential fluctuation due to inter-pixel parasitic capacitance is corrected is output to one of two pixels connected to different signal lines and adjacently arranged in the row direction. A correction circuit for causing
The correction circuit outputs the corrected signal using at least a part of the gamma correction circuit that performs gradation gamma correction, and is selected later from two pixels adjacently arranged in the row direction. A display device, wherein a signal in which the potential fluctuation is corrected is output to the signal line driver circuit toward a power pixel. The first pixel column and the second pixel column are arranged adjacent to each other in the row direction,
A third pixel column that is adjacent to the first pixel column across the first signal line is disposed in a row direction opposite to the second pixel column,
In the row direction opposite to the first pixel column, a fourth pixel column adjacent to the second pixel column is disposed across the second signal line,
The first pixel column and the third pixel column share the first signal line;
The second pixel column and the fourth pixel column share the second signal line;
The first pixel column and the fourth pixel column are connected to a first scanning line corresponding to each pixel row for each pixel row,
In the display device, the second pixel column and the third pixel column are connected to a second scanning line that differs from the first scanning line and corresponds to each pixel row for each pixel row. And
Due to the parasitic capacitance generated between two pixels adjacent in the row direction in the first pixel column and the second pixel column toward the first pixel column or the second pixel column A correction circuit that outputs a signal that corrects the potential fluctuation
Each pixel in the first pixel column or the second pixel column corresponds to a different color component between two pixels adjacent in the column direction ,
The display device , wherein the correction circuit outputs the corrected signal using at least a part of a gamma correction circuit that performs gamma correction of gradation . The color components of two pixels adjacent in the row direction are different from each other between the first pixel column and the second pixel column, and the combination of the different color components is equal for every two pixel rows. The display device according to claim 9 , wherein A first pixel and a second pixel are arranged adjacent to each other in the row direction;
A third pixel adjacent to the first pixel is disposed in a row direction opposite to the second pixel with the first signal line interposed therebetween;
In the row direction opposite to the first pixel, a fourth pixel that is adjacent to the second pixel across the second signal line is disposed,
The first pixel and the third pixel share the first signal line;
The second pixel and the fourth pixel share the second signal line;
The first pixel and the fourth pixel are connected to a first scan line;
A driving method of a display device in which the second pixel and the third pixel are connected to a second scanning line,
Parasitic capacitance between the first pixel and the second pixel toward the first pixel or the second pixel using at least a part of a gamma correction circuit that performs gamma correction of gradation A method for driving a display device, comprising: outputting a signal in which an amount of potential fluctuation caused by the correction is corrected. Of the two pixels adjacently arranged in the predetermined direction, a signal in which the potential variation is corrected is output toward the pixel to be selected first, and the potential is applied to the pixel to be selected later. 12. The method of driving a display device according to claim 11 , wherein a signal that does not correct fluctuation is output. Of the two pixels arranged adjacent to each other in the predetermined direction, a signal that does not correct the potential variation is output toward the pixel to be selected first, and the pixel to be selected later is output. 12. The method of driving a display device according to claim 11 , wherein a signal in which the potential variation is corrected is output.

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