Classifications

• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
  • H02M3/00—Conversion of dc power input into dc power output
  • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
  • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
  • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
  • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
  • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
  • H02M3/337—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in push-pull configuration
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
  • H02M1/00—Details of apparatus for conversion
  • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
  • H02M1/083—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the ignition at the zero crossing of the voltage or the current
• • B—PERFORMING OPERATIONS; TRANSPORTING
  • B64—AIRCRAFT; AVIATION; COSMONAUTICS
  • B64D—EQUIPMENT FOR FITTING IN OR TO AIRCRAFT; FLIGHT SUITS; PARACHUTES; ARRANGEMENT OR MOUNTING OF POWER PLANTS OR PROPULSION TRANSMISSIONS IN AIRCRAFT
  • B64D13/00—Arrangements or adaptations of air-treatment apparatus for aircraft crew or passengers, or freight space, or structural parts of the aircraft
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
  • H02M1/00—Details of apparatus for conversion
  • H02M1/0048—Circuits or arrangements for reducing losses
  • H02M1/0054—Transistor switching losses
  • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
  • H02M1/00—Details of apparatus for conversion
  • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
  • H02M1/00—Details of apparatus for conversion
  • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
  • H02M1/007—Plural converter units in cascade
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
  • H02M1/00—Details of apparatus for conversion
  • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
  • H02M1/008—Plural converter units for generating at two or more independent and non-parallel outputs, e.g. systems with plural point of load switching regulators
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
  • H02M1/00—Details of apparatus for conversion
  • H02M1/38—Means for preventing simultaneous conduction of switches
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
  • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
  • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
  • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
  • H02M7/06—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode
  • H02M7/10—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode arranged for operation in series, e.g. for multiplication of voltage
  • H02M7/103—Containing passive elements (capacitively coupled) which are ordered in cascade on one source
• • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
  • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
  • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
  • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
  • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

• CONTINUOUS-CONTINUOUS CONVERTER FOR STEERING AN AIRCRAFT FAN INVERTER, CONTROL METHOD AND FAN THEREFOR
• the invention relates to the optimization of a structure of a DC-DC converter.
• the invention relates to a DC-DC converter for controlling a three-phase inverter, in particular a three-phase inverter driving a fan of a ventilation system of an aircraft.
• the ventilation systems for regulating the air circulation within an aircraft comprise at least one fan adapted to ensure air circulation in the aircraft, in particular in the cabin of the aircraft.
• Each fan is controlled by a three-phase inverter.
• the three-phase inverter comprises three supply arms, each of these arms comprising two isolated-gate bipolar transistors (IGBT for Insulated Gate Bipolar Transistor).
• IGBT Insulated Gate Bipolar Transistor
• the driving voltage requirements of the IGBT transistors are conventionally +15 V in positive bias voltage and -7.5 V in negative bias voltage. These voltages are provided by at least one DC-DC converter (DC-DC for Direct Current) and in general one IGBT transistor converter.
• the invention aims to overcome at least some of the disadvantages of known DC-DC converters.
• the invention aims to provide, in at least one embodiment of the invention, a DC-DC converter comprising a reduced number of components.
• the invention also aims to provide, in at least one embodiment of the invention, a DC-DC converter comprising few complex components.
• the invention also aims to provide, in at least one embodiment of the invention, a DC-DC converter having a footprint and a reduced weight.
• the invention also aims to provide, in at least one embodiment of the invention, a DC-DC converter having a high efficiency.
• the invention also aims to provide, in at least one embodiment of the invention, a DC-DC converter whose heating is reduced. 4. Presentation of the invention
• the invention relates to a DC-DC converter, adapted to be powered by a primary voltage source and to supply a control electronics of a three-phase inverter, said three-phase inverter being configured to drive a fan of a ventilation system of an aircraft, characterized in that it comprises:
• a transformer comprising two primary windings and at least one secondary winding
• a primary circuit comprising a supply input adapted to be connected to a first terminal of the primary voltage source, said supply input being connected to two switching loops each comprising one of the primary windings of the transformer and a controllable transistor comprising a parasitic capacitance and thus forming a symmetrical arrangement,
• At least one secondary circuit comprising a secondary winding of the transformer, said secondary winding comprising two terminals connected on the one hand to a capacitive rectification bridge, adapted to supply the inverter control electronics with an equal positive output voltage at twice the peak voltage across the secondary winding, and secondly to a branch of the circuit adapted to supply the inverter control electronics with a negative output voltage equal to the opposite of the voltage peak at the terminals of the secondary winding,
• controllable transistors are adapted to each be controlled by a driving signal between an on state and a off state, so that when a controllable transistor is in an on state, the other controllable transistor is in a state blocked and that when a controllable transistor is switched from the off state to the off state, the two controllable transistors are held in the off state for a dead time so as to perform a zero voltage switching.
• control voltage of a transistor designates the voltage between the gate and the source for a field effect transistor
• the output voltage at the terminals of a transistor indicates the voltage between the drain and the transistor.
• source for a field effect transistor and the current flowing through the transistor means the current between the drain and the source for a field effect transistor.
• the conducting state of the controllable transistors corresponds to a state in which a current flows through the transistor and the blocked state of the controllable transistors corresponds to a state in which the current flowing through the transistor is zero or negligible.
• the controllable transistors thus behave as controllable switches with parasitic capacitance in parallel, the on state corresponding to a closed switch and the off state corresponding to an open switch.
• a DC-DC converter according to the invention thus makes it possible to control a control electronics of a three-phase inverter with a reduced number of components.
• the primary circuit comprises a symmetrical mounting (also called push-pull assembly) comprising only two transistors instead of four transistors in frequently used full-bridge structures.
• the structure of the secondary circuit of the DC-DC converter makes it possible to obtain two voltages at the output of the secondary circuit with a single secondary winding.
• the DC-DC converter does not include magnetic components, which generally have a large footprint.
• the DC-DC converter according to the invention therefore has a smaller footprint than current solutions.
• the primary circuit comprises a symmetrical mounting controlled so as to perform a switching of the Zero Volt Switching transistors (or ZVS, for Zero Volt Switching in English).
• ZVS Zero Volt Switching in English
• each controllable transistor is alternately in an on or off state, but when a controllable transistor goes from the on state to the off state, the other controllable transistor remains in the off state for a dead time, then passes in the passing state.
• This dead time is a time interval which makes it possible to minimize the switching losses due, in the prior art, to a voltage-current switching with non-zero values.
• the dead time during which the two transistors are blocked allows voltage-current switching to very low values, resulting in very low switching losses.
• the efficiency of the DC-DC converter is improved and heating is reduced.
• Zero voltage switching is ensured during the dead time and by a particular combination of the primary windings and parasitic capacitances of the controllable transistors.
• a first controllable transistor is in the off state, the voltage at its terminals is at its maximum level and its parasitic capacitance is charged
• a second controllable transistor is in the on state, the voltage at its terminals is at its minimum level and its parasitic capacitance is discharged.
• the two transistors are in the off state and the primary windings are no longer supplied with current by the primary voltage source.
• a magnetizing current of the transformer makes it possible to discharge the parasitic capacitance of the first controllable transistor and to charge the parasitic capacitance of the second controllable transistor.
• the switching can be done without loss: in fact, the transistor comprises a diode which is spontaneously initiated during the dead time.
• the primary windings and the controllable transistors are thus chosen so that their characteristics allow the switching to zero voltage.
• the parasitic capacitances of the transistors, the magnetizing current and the duration of the dead time are chosen so as to obtain zero voltage switching without addition of components.
• the DC / DC converter according to the invention is therefore, in particular thanks to the combination of a push-pull arrangement, a capacitive rectification bridge and a zero voltage switching, perfectly adapted to the constraints of the new generations of Aircraft ventilation system fan, especially in terms of size, weight and thermal efficiency. In addition, its cost is reduced.
• the three-phase inverter comprising a plurality of insulated gate bipolar transistor
• the DC-DC electrical converter is characterized in that it comprises a plurality of secondary circuits each comprising a secondary winding of the transformer, each circuit secondary circuit being adapted to supply at least one insulated gate bipolar transistor of the control electronics of the three-phase inverter.
• the DC-DC converter supplies a plurality of insulated gate bipolar transistors of the three-phase inverter with a single primary power source.
• Each insulated gate bipolar transistor of the three-phase inverter requiring a secondary winding to obtain a positive and negative voltage, duplicate the number of secondary windings on the same transformer can drive a complete three-phase inverter, which allows a reduction of the size, weight and price of all DC-DC converters necessary for the control of a fan.
• controllable transistors are field effect transistors.
• controllable transistors of the DC-DC converter are metal oxide-oxide field effect transistors (also called MOSFETs for Metal Oxide Semiconductor Field Effect Transistors).
• MOSFETs Metal Oxide Semiconductor Field Effect Transistors
• Other components may also be used, provided that they are supplemented by a free-wheeling diode.
• the invention also relates to an aircraft system fan, characterized in that it is controlled by a three-phase inverter comprising a control electronics adapted to be powered by at least one DC-DC converter according to the invention.
• control electronics of the three-phase inverter comprises three supply arms, each arm being controlled by a DC-DC electrical converter according to the invention.
• control electronics of the three-phase inverter comprises three supply arms, and in that it comprises an electric converter according to the invention comprising six secondary circuits adapted to control the three arms of the three-phase inverter. food.
• the invention also relates to a control method of a DC-DC converter according to the invention, characterized in that it comprises controlling the two controllable transistors, said first controllable transistor and second controllable transistor, according to the following steps:
• a third step of controlling the second transistor controllable in the on state and the first transistor controllable in the off state a fourth step of transition of the second transistor controllable in the off state and the maintenance of the first transistor controllable in the state blocked during the timeout.
• the method according to the invention therefore allows control of the DC-DC converter comprising two transition stages in which the two transistors are in a locked state in order to allow a zero-switching of voltage.
• the invention also relates to a DC-DC converter, a fan and a control method characterized in combination by all or some of the characteristics mentioned above or below.
• FIG. 1 is a schematic view of a DC-DC electrical converter according to a first embodiment of the invention
• FIGS. 2a, 2b, 2c and 2d are diagrammatic views of a DC-DC converter according to the first embodiment of the invention during different stages of a method according to one embodiment of the invention
• FIG. 3 represents curves a, b, c respectively representing the control voltages of the controllable transistors, the voltages at the terminals of the controllable transistors and the intensities through the controllable transistors of a DC-DC converter according to the first embodiment of FIG. the invention
• FIG. 4 is a schematic view of a DC-DC converter according to a second embodiment of the invention.
• Figure 5 is a schematic view of a supply chain comprising three DC-DC converters according to the second embodiment of the invention and a fan according to one embodiment of the invention.
• FIG. 1 shows schematically a DC-DC converter 10 according to a first embodiment.
• the DC-DC converter comprises a primary circuit 12, a secondary circuit 14 and a transformer 16.
• the transformer 16 makes the connection between the primary circuit 12 and the secondary circuit 14.
• the transformer 16 comprises two perfectly coupled primary windings, a first primary winding L P1 and a second primary winding L P2 , and a secondary winding L s .
• the primary windings L P1 and L P2 form part of the primary circuit 12 and the secondary winding L s is part of the secondary circuit 14.
• the primary circuit 12 is powered by a primary voltage source whose terminals are respectively connected to a supply input V, N so as to supply the DC-DC converter.
• the supply input V, N is connected to two parallel switching loops, a first loop and a second loop.
• the first loop comprises the first primary winding L P1 and a first controllable transistor M 1
• the second loop comprises the second primary winding L P2 and a second controllable transistor M 2 .
• the two loops thus form a symmetrical assembly, also called push-pull assembly.
• the secondary winding L s recovers a ratio of the primary voltage present at the two primary windings.
• the secondary winding L s has a voltage V SE c at its terminals.
• the terminals of the secondary winding L s are connected on the one hand to a first branch comprising a capacitive rectification bridge, comprising two capacitors C s and C P and two diodes D x and D 3 forming a circuit called a Schenkel doubler and secondly to a second branch comprising a diode D 2 and a capacitor C N.
• Capacitor C s acts as a capacitive doubler.
• the first branch is adapted to provide a device, here represented by a resistor R 0U TI, a first output voltage V 0U TP equal to twice the peak voltage across the secondary winding L s .
• a device here represented by a resistor R 0U TI
• V 0U TP a first output voltage V 0U TP equal to twice the peak voltage across the secondary winding L s .
• the voltage V 0U TP is equal to the sum of the voltage V SEC , the voltage across the capacitor C s and the voltage across the diode Gold
• the voltage across the capacitor C s is equal to sum of the voltage V SEC and the voltage across the diode D 3 .
• V TP 0U 2xV SEC.
• the second branch is adapted to provide a device, here represented by a resistor 0 UT2, a second output voltage V 0 UTN equal to the opposite of the peak voltage across the secondary winding L s .
• a resistor 0 UT2 a second output voltage V 0 UTN equal to the opposite of the peak voltage across the secondary winding L s .
• the output voltage V 0 UTN is equal to the sum of the opposite of the voltage V SE c and the voltage across the diode D 2 .
• V SE c peak 7.5 V
• V 0 UTP 15V
• V 0 UTN -7.5 V
• FIGS. 2a, 2b, 2c, 2d show a DC-DC electrical converter according to the first embodiment of the invention during different steps of a method according to one embodiment of the invention. These figures make it possible to see in more detail the operation of the DC / DC converter according to different stages related to the states of the two controllable transistors Mi, M 2 .
• controllable transistors Mi, M 2 are each represented, for simplification and for the sake of clarity, by a closed switch (representing a transistor controllable in the on state) or open (representing a controllable transistor in the state blocked), at the terminals of which is connected in parallel a parasitic capacitance of each controllable transistor, respectively a first parasitic capacitance C DS1 of the first controllable transistor M 1 and a second parasitic capacitance C DS2 of the second controllable transistor M 2 .
• the method comprises the following steps:
• FIGS. 2a and 2c show the DC-DC converter during the first and third stages respectively, in which a controllable transistor is in the on state and the other controllable transistor is in the off state.
• the push-pull circuit of the primary circuit alternately feeds the first primary winding L P1 or the second primary winding L P2 .
• the current flowing in the secondary winding L s changes direction according to the primary winding supplied.
• the first primary winding L P1 is powered by the push-pull assembly when the first controllable transistor M 1 is in the on state and the second controllable transistor M 2 is in the off state, as shown with reference to FIG. 2a.
• the second primary winding L P2 is energized when the first controllable transistor Mi is in the off state and the second controllable transistor M 2 is in the on state, as shown with reference to FIG. 2c.
• a first charging current passing through the resistor 0 UTI and a second charging current passing through the resistor 0 UT2 are provided differently depending on the direction of the current flowing through the secondary winding L s .
• the capacitor C s charges up to V SEC C
• the capacitor C P supplies the first charging current
• the capacitor C N is charged up to V SEC crest and the secondary winding L s provides the second charging current.
• the capacitor C s discharges into the capacitor C P and supplies the first current of load
• the capacitor C N provides the second charging current.
• FIGS. 2b and 2d show the DC / DC converter during the second and fourth stages respectively, in which the two controllable transistors are in the off state.
• steps are transition steps, making it possible to obtain a zero-voltage switching by keeping the two controllable transistors in the off state during a dead time.
• the second step follows the first step in which the first controllable transistor Mi was conducting.
• the first parasitic capacitance C DS i of the first controllable transistor Mi is discharged and the output voltage across the first controllable transistor Mi is at its minimum level, that is to say close to zero.
• the second controllable transistor M 2 being blocked in the first and the second step, the second parasitic capacitance C of the second controllable transistor M 2 is charged and the output voltage across the second controllable transistor M 2 is at its maximum level.
• the two primary windings are no longer powered by the primary voltage source and a magnetizing current propagates in the direction indicated by the arrows on the two loops in Figure 2b.
• This magnetising current causes the charge of the first parasitic capacitance C DS1 and the discharge of the second parasitic capacitance C DS2 .
• the output voltage across the first controllable transistor M 1 increases gradually and the output voltage across the second controllable transistor M 2 decreases gradually.
• the parasitic capacitance consists only of that of the controllable transistor.
• the first parasitic capacitance C DS i discharges, the output voltage at the terminals of the first controllable transistor Mi gradually decreases, the second parasitic capacitance C DS2 is charged and the output voltage across the second controllable transistor M 2 increases gradually.
• the second step and the fourth step last during a predefined dead time depending on the characteristics of the primary windings and parasitic capacitors, so that the end of the dead time, the voltages across the transistors can reach the maximum value if the voltage increases during the step, or the minimum value if the voltage decreases during the step.
• FIG. 3 represents three curves a, b and c respectively representing, as a function of time, the control voltages V gs _ M1 and V gs _ M2 respectively of the first controllable transistor M 1 and the second controllable transistor M 2 (curves 30 and 32 ), the output voltages V ds _ M1 and V ds _ M2 across respectively the first controllable transistor M 1 and the second controllable transistor M 2 (curves 34 and 36), and the intensities l d _ M1 and l d _M2 respectively passing through the first controllable transistor M 1 and the second controllable transistor M 2 (curves 38 and 40) of a DC-DC converter according to the first embodiment of the invention.
• the curves 30, 34, 38 in solid lines are associated with the first controllable transistor Mi, and the curves 32, 36, 40 in dashed lines are associated with the second controllable transistor M 2 .
• Curve a thus represents the commands sent to the controllable transistors, the high level representing a control of the transistor that can be controlled in the on state and the low level representing a control of the controllable transistor in the off state.
• the commands are transmitted for example by a dedicated circuit (not shown), or by an already existing control card, for example an FPGA.
• the first controllable transistor M 1 is controlled in the on state: the output voltage V ds _ M1 at its terminals is therefore zero, and the intensity l d _ M1 of current passing through it non-zero.
• the second controllable transistor M 2 is controlled in the off state: the output voltage V ds _ M2 to its terminals is therefore non-zero and the intensity l d _ M2 of the current passing through it is zero (or negligible).
• the two controllable transistors are controlled in the off state: the output voltage V ds _ M1 across the first controllable transistor M 1 progressively increases because of the charge of the first parasitic capacitance C DS1 , and the output voltage across the second controllable transistor M 2 decreases due to the discharge of the second parasitic capacitance C DS 2.
• the intensities of the currents flowing through the transistors controllables are close to zero, corresponding to the magnetizing currents crossing parasitic capacitances.
• the intensity l d MI of the current flowing through the first controllable transistor Mi is brought to a zero or negligible value before the progressive increase of the output voltage V ds _ M1 across the first controllable transistor Mi. There are therefore no losses due to the switching of the first controllable transistor M 1 from the off state to the off state of the first step.
• the intensity l d _ M2 of the current flowing through the second controllable transistor M 2 is zero or negligible and the output voltage V ds _ M2 across the second controllable transistor M 2 has progressively reached a zero value. or negligible.
• the third and fourth steps are similar to the first and second steps, the role of the two controllable transistors being reversed.
• the efficiency of the DC-DC converter according to the invention is greater than 85% when the DC-DC converter is subjected to a temperature of between -50 ° C. and 115 ° C., which is superior to the converters of the prior art.
• FIG. 4 diagrammatically represents a DC / DC converter 10 'according to a second embodiment.
• the DC-DC converter comprises, identically to the first embodiment described previously, a primary circuit and a first secondary circuit 42 comprising a first secondary winding, providing voltages V 0U TP_HS and V 0U T N _HS-
• the DC-DC converter further comprises a second secondary circuit 44, identical to the first secondary circuit 42, comprising a second secondary winding.
• the transformer 16 'thus comprises the two primary windings described above, as well as the first secondary winding L S i and the second secondary winding L S 2-
• the second secondary circuit 44 makes it possible to obtain new output voltages, a voltage VO U TP_LS and a voltage V 0U T N _LS, with a single primary circuit and a single primary power source. A possible use of these new output voltages is described below with reference to FIG.
• FIG. 5 shows a supply chain comprising three DC-DC converters 10a, 10b, 10c according to the second embodiment of the invention and a fan 50 according to one embodiment of the invention.
• the fan 50 is powered by a three-phase inverter 52 comprising three supply arms 54a, 54b, 54c, the supply arms 54a, 54b, 54c forming a control electronics.
• Each power supply arm 54a, 54b, 54c comprises two IGBT transistors (not shown), a high-level IGBT transistor (HS) and a low-floor (LS) transistor. .
• each IGBT transistor of each branch had to be fed by a DC-DC converter, the three-phase inverter being fed by six DC-DC converters.
• the three low-floor IGBT transistors are powered by a single power supply, the three-phase inverter being fed by four DC-DC converters.
• the 10 'DC-DC converter according to the second embodiment previously described with reference to FIG. 4 makes it possible to simultaneously power a high-stage IGBT transistor, by virtue of the output voltages V 0U TP_HS and V 0U T N _HS, and a low stage IGBT transistor a feed arm, through the output voltages V and V 0U 0U TP_LS T N _LS-
• the three-phase inverter therefore requires only three converters 10a, 10b, 10c DC-DC.
• each supply arm 54a, 54b, 54c is powered by a converter 10a, 10b, 10c continuous, each converter 10a, 10b, 10c DC-DC being supplied by a source 56a, 56b, 56c primary power supply.
• the DC-DC converter comprises six secondary circuits, thus making it possible to supply all of the power supply arms of the control electronics of a three-phase inverter.

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• Engineering & Computer Science (AREA)
• Power Engineering (AREA)
• Dc-Dc Converters (AREA)
• Inverter Devices (AREA)
• Health & Medical Sciences (AREA)
• General Health & Medical Sciences (AREA)
• Pulmonology (AREA)
• Aviation & Aerospace Engineering (AREA)

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• 2015
  • 2015-06-11 FR FR1555330A patent/FR3037453B1/fr active Active
• 2016
  • 2016-06-07 WO PCT/FR2016/051361 patent/WO2016198783A1/fr active Application Filing
  • 2016-06-07 EP EP16731243.8A patent/EP3308455A1/fr not_active Withdrawn
  • 2016-06-07 CN CN201680038689.4A patent/CN107852097A/zh active Pending
  • 2016-06-07 US US15/580,155 patent/US10396650B2/en active Active

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