EP3206297B1 - Dispositif de conversion de puissance et son procédé de commande, et dispositif de commande de direction assistée électrique - Google Patents

Dispositif de conversion de puissance et son procédé de commande, et dispositif de commande de direction assistée électrique Download PDF

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Publication number
EP3206297B1
EP3206297B1 EP14903537.0A EP14903537A EP3206297B1 EP 3206297 B1 EP3206297 B1 EP 3206297B1 EP 14903537 A EP14903537 A EP 14903537A EP 3206297 B1 EP3206297 B1 EP 3206297B1
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EP
European Patent Office
Prior art keywords
voltage
current
rotating machine
phase
power
Prior art date
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Application number
EP14903537.0A
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German (de)
English (en)
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EP3206297A1 (fr
EP3206297A4 (fr
Inventor
Tatsuya Mori
Akira Furukawa
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Mitsubishi Electric Corp
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Mitsubishi Electric Corp
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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/22—Current control, e.g. using a current control loop
    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B62—LAND VEHICLES FOR TRAVELLING OTHERWISE THAN ON RAILS
    • B62D—MOTOR VEHICLES; TRAILERS
    • B62D5/00—Power-assisted or power-driven steering
    • B62D5/04—Power-assisted or power-driven steering electrical, e.g. using an electric servo-motor connected to, or forming part of, the steering gear
    • B62D5/0457—Power-assisted or power-driven steering electrical, e.g. using an electric servo-motor connected to, or forming part of, the steering gear characterised by control features of the drive means as such
    • B62D5/046—Controlling the motor
    • B62D5/0463—Controlling the motor calculating assisting torque from the motor based on driver input
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
    • H02M7/5395—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/14—Estimation or adaptation of machine parameters, e.g. flux, current or voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0009—Devices or circuits for detecting current in a converter

Definitions

  • the present invention relates to a power conversion device, and the like, and more particularly, to detection of a bus current during operation.
  • the motor control device is configured to perform drive control of a motor based on duty command values for respective PWM phases, and to detect a motor current in each phase of the motor with a one-shunt type current detector.
  • the motor control device includes a current detection correction part for calculating a current detection correction value based on a power supply voltage of an inverter, the duty command values for the respective phases, counter electromotive voltage information on the motor, the motor currents in the respective phases detected by the current detector, arrangement information on the PWM, and an electrical characteristic equation of the motor.
  • the current detection correction value is used to correct the motor currents in the respective phases detected by the current detector so as to acquire a motor average current, thereby performing drive control of the motor.
  • document JP 2008 219956 relates to a motor drive controller which drives an electric motor.
  • the motor drive controller is provided with first and second inverter units each generating an AC voltage from DC voltage of a AC-DC power transformer and outputting the AC voltage to an independent winding type motor and is further provided with control means for controlling the first and second inverter units so that the independent winding type motor can perform Y-wire connection equivalent operation or Delta-wire connection equivalent operation.
  • the control means controls the output voltages of the first and second inverter units so that the phase between the vector of a magnetic flux generated in the armature winding of the independent winding type motor and the vector of a composite voltage by the first and second inverter units may maintain a predetermined relation.
  • the European patent application publication EP3070835A1 falls under the conditions of Article 54(3) EPC and discloses an electric power steering device with two inverters connected in parallel to an electric motor, a voltage command calculation unit, a switching signal generation unit, and respective current detectors in the DC-bus lines of the inverters.
  • the current detection correction part is configured to calculate the current detection correction value based on the power supply voltage of the inverter, the duty command values for the respective phases, the counter electromotive voltage information on the motor, the motor currents in the respective phases detected by the current detector, the arrangement information on the PWM, and the electrical characteristic equation of the motor, and thus the calculation of the correction value requires a large amount of calculation, resulting in such a problem that implementation by using an inexpensive microcomputer is difficult. Further, temperature fluctuation of the motor causes fluctuation in the flux interlinkage number, which is proportional to a resistance R and a counter electromotive voltage EMF of the motor.
  • an inductance L of the motor fluctuates due to influence of magnetic saturation when a current is supplied to a winding of the motor.
  • the motor constants fluctuate in this way, and errors occur between the motor constants and motor constants stored in the current detection correction part, and an error occurs between a difference between the motor current in each phase detected by the current detector and the motor average current and the current detection correction value, resulting in such a problem that the motor currents in the respective phases detected by the current detector cannot be corrected to acquire the motor average current.
  • the present invention has been made in view of the above-mentioned problems. It is an object of the present invention to provide a power conversion device, and the like, relating to the control of detecting a bus current in operation, and capable of acquiring an average current through a small amount of calculation and being implemented by an inexpensive microcomputer.
  • a power conversion device including: an AC rotating machine having saliency, and including a multi-phase winding of three phases or more; a DC power supply configured to output a DC voltage; a voltage command calculation part configured to calculate voltage commands based on a control command from an outside for the AC rotating machine; a switching signal generation part configured to output switching signals corresponding to at least two voltage vectors on both sides of an axis having a larger inductance out of d and q axes of the AC rotating machine, and corresponding to the voltage commands; a power conversion part configured to carry out, based on the switching signals, one or both of an operation of converting the DC voltage from the DC power supply to an AC voltage and supplying the AC voltage to the AC rotating machine during a power running operation, and an operation of converting an electromotive force of the AC rotating machine to DC power and supplying the DC power to the DC power supply during a regeneration operation; a current detection part configured to detect a bus current, which is
  • the power conversion device, and the like relating to the control of detecting the bus current in operation, and capable of acquiring the average current through a small amount of calculation and being implemented by an inexpensive microcomputer.
  • a power conversion device, and the like, according to the present invention relate to control of detecting a bus current in operation, and fluctuation in a winding current flowing through a multi-phase winding of an AC rotating machine is small at a timing at which voltage vectors on both sides of an axis larger in an inductance of the AC rotating machine are output. A value close to an average of the winding current can be acquired by detecting the bus current at this timing.
  • a large amount of calculation e.g., calculation of a current detection correction value based on a power supply voltage of an inverter, duty command values for respective phases, counter electromotive voltage information on a motor, motor currents in the respective phase detected by a current detector, arrangement information on PWM, and an electrical characteristic equation of the motor is not necessary unlike a current detection correction part of the related art, and only a small amount of calculation is required for implementation.
  • application of an inexpensive microcomputer is facilitated. Further, the value close to the average of winding currents can be acquired while influence on variations in constants of the rotating machine is suppressed.
  • FIG. 1 is a diagram for illustrating an overall configuration of a power conversion device according to a first embodiment of the present invention.
  • An AC rotating machine 1 is constructed by a permanent magnet synchronous rotating machine including a three-phase winding (generally, multi-phase winding) C having three phases U, V, and W.
  • a three-phase winding generally, multi-phase winding
  • a DC power supply 2 is configured to output a DC voltage Vdc to a power conversion part 3.
  • This DC power supply 2 may include all devices that are configured to output a DC voltage, e.g., a battery, a DC-DC converter, a diode rectifier, and a PWM rectifier (which are not shown).
  • the power conversion part 3 is configured to turn on/off semiconductor switches Sup to Swn based on switching signals Qup to Qwn, thereby applying power conversion to the DC voltage Vdc input from the DC power supply 2, and applying AC voltages on a three-phase winding C having U, V and W phases of the AC rotating machine 1.
  • a semiconductor switching device e.g., an IGBT, a bipolar transistor, or a MOS power transistor and a diode connected to each other in an anti-parallel connection state are used.
  • the switching signals Qup, Qun, Qvp, Qvn, Qwp, and Qwn are switching signals for respectively turning on/off the semiconductor switches Sup, Sun, Svp, Svn, Swp, and Swn in the power conversion part 3.
  • a switching signal generation part 5 is configured to output the switching signals Qup to Qwn to which the pulse width modulation (PWM modulation) is applied in accordance with the voltage commands Vu, Vv, and Vw output from a voltage command calculation part 6.
  • the switching signals Qup to Qwn have pulse widths in accordance with the voltage commands Vu, Vv, and Vw.
  • the voltage conversion part 3 is configured to use the switching signals Qup to Qwn to carry out: an operation of converting the DC voltage from the DC power supply 2 to an AC voltage, and supplying the AC voltage to the AC rotating machine 1 during a power running operation; an operation of converting an electromotive force of the AC rotating machine 1 to DC power, and supplying the DC power to the DC power supply 2 during a regeneration operation; and both of the operation during the power running operation and the operation during the regeneration operation.
  • the switching signals Qup to Qwn are output to the power conversion part 3 as well as a current detection part 7 and a phase current calculation part 8 for the current detection, and the current detection part 7 and the phase current calculation part 8 are configured to respectively carry out the detection and the calculation in accordance with the switching signals Qup to Qwn. All the switching signals Qup to Qwn do not need to be output to the current detection part 7 and the phase current calculation part 8, and the same effect can be provided by using, for example, upper switching signals Qup, Qvp and Qwp or using another state variable that can represent states of the switching signals Qup to Qwn.
  • the voltage command calculation part 6 is configured to calculate the voltage commands Vu, Vv, and Vw for driving the AC rotating machine 1, and output the voltage commands Vu, Vv, and Vw to the switching signal generation part 5.
  • a calculation method for the voltage commands Vu, Vv, and Vw for example, there is given V/F control of setting a speed (frequency) command f for the AC rotating machine 1 as the control command of FIG. 1 to determine the amplitude of the voltage commands.
  • the V/F control is feedforward control, and does not require the three-phase currents lu, Iv, and Iw.
  • the input of the three-phase currents Iu, Iv, and Iw to the voltage command calculation part 6 is not essential in this case.
  • the current detection part 7 is configured to detect a bus current Idc, which is a current flowing between the DC power supply 2 and the power conversion part 3, and output a detection result to the phase current calculation part 8.
  • the current detection part 7 is constructed by a shunt resistor 7a and a sample-and-hold device 7b configured to sample and hold the current flowing through the shunt resistor 7a, thereby detecting the bus current Idc.
  • a current transformer (CT) may be used in place of the shunt resistor 7a, and in this case, an output voltage of the current transformer is sampled and held by the sample-and-hold device 7b, thereby detecting the bus current Idc.
  • FIG. 2 the relationship among the switching signals Qup to Qwn, the voltage vectors, the bus current, and the currents Iu, Iv, and Iw flowing through the three-phase winding is illustrated.
  • the value of one of Qup to Qwn is 1, one of the semiconductor switches Sup to Swn corresponding to the one of Qup to Qwn having the value of 1 is on.
  • the value of one of Qup to Qwn is 0, one of the semiconductor switches Sup to Swn corresponding to the one of Qup to Qwn having the value of 0 is off.
  • V1 to V6 are vectors different in the phase by 60 degrees from each other.
  • V1, V3, and V5 have U, V, W phase directions of the three-phase winding, respectively.
  • V0 and V7 are voltage vectors having the magnitude of zero.
  • the phase current calculation part 8 is configured to output lu, Iv, and Iw from the relationship shown in FIG. 2 based on the bus current Idc and the switching signals Qup to Qwn.
  • V0 and V7 cannot be used to detect the three-phase currents based on the bus current.
  • the voltage vector V1 is output to detect lu
  • the voltage vector V2 is output to detect -Iw.
  • There may be provided such a configuration that, based on the fact that a sum of the currents flowing through the three phases is zero in the three-phase three-line rotating machine, the acquired detected current values for the two phases are used to calculate a current of the remaining one phase. In other words, only such a configuration that appropriate voltage vectors are selected to detect the currents for at least two phases is necessary.
  • a position detector 100 is configured to output a phase ⁇ of the AC rotating machine 1 to the switching signal generation part 5.
  • FIG. 4 is a diagram for illustrating a basic structure of a rotor of the AC rotating machine 1, and showing such a structure that permanent magnets 41 to 44 are embedded inside an iron core. Flux barriers are provided on both ends of each of the permanent magnets 41 to 44.
  • a direction of a field pole generated by the permanent magnets is set to the d axis, and a direction advanced by 90 degrees in the electrical angle is set to the q axis.
  • a case of a four-pole machine is illustrated in FIG. 4 , and a direction advanced in 45 degrees in the mechanical angle with respect to the d axis is the q axis.
  • the rotating machine 1 having this rotor structure is referred to as interior magnet synchronous rotating machine and has saliency, and there is a relationship Ld ⁇ Lq between a d axis inductance Ld and a q axis inductance Lq.
  • the present invention can be applied to other AC rotating machines having a saliency, e.g., an inset permanent magnet synchronous rotating machine, a synchronous reluctance motor, and a switched reluctance motor.
  • AC rotating machines having a saliency e.g., an inset permanent magnet synchronous rotating machine, a synchronous reluctance motor, and a switched reluctance motor.
  • a description has been given of the rotor having four poles in FIG. 4 but the present invention can be applied to an AC rotating machine having an arbitrary number of poles as long as the number of poles is an even natural number (not including 0).
  • FIG. 5 is an operation explanatory diagram relating to a method of generating the switching signals Qup to Qwn in the switching signal generation part 5, and the detection timings of the bus current Idc in the current detection part 7 in a cycle Ts of the switching signals according to the first embodiment.
  • Qun, Qvn, and Qwn illustrated in FIG. 2 are respectively in an inverted relationship (0 for 1 and 1 for 0 except for a dead time period) with Qup, Qvp, and Qwp, and are thus not illustrated.
  • Qup is set to 1, and Qvp and Qwp are set to 0 at a time point t1(n), and this switching pattern is maintained until a time point t2(n) after an elapse of ⁇ t1 from the time point t1(n).
  • the voltage vector is V1 from the time point t1(n) to the time point t2(n).
  • a first bus current Idc is detected at a time point ts1-1(n) in the period from the time point t1(n) to the time point t2(n).
  • ⁇ t1 is set to a period longer than a sum of a dead time of the power conversion part 3 and a period for the current detection part 7 to detect the bus current Idc (such as a period required for settlement of ringing included in a detected waveform and a period required for the sampling and holding).
  • the voltage vector is V1 from the time point t1(n) to the time point t2(n), and the bus current Idc detected at the time point ts1-1(n) is equal to the current lu flowing through the U phase.
  • Qvp is set to 1 at the time point t2(n), and this switching pattern is maintained until a time point t3(n).
  • the voltage vector is V2 from the time point t2(n) to a time point t3(n).
  • the bus current Idc is again detected at a time point ts1-2(n) at this timing.
  • the bus current Idc detected at the time point ts1-2(n) is equal to a value -Iw acquired by inverting the sign of the current flowing through the W phase.
  • Qwp is set to 1 at the time point t3(n).
  • Pulse widths (periods in which the value 1 is maintained) of Qup to Qwp are determined by the voltage commands Vu, Vv, and Vw, and timings at which Qup to Qwp become 0 are thus determined in accordance with the pulse widths.
  • the two voltage vectors V1 and V2 are generated by setting Qup, Qvp, and Qwp to 1 in this sequence, and the bus current Idc is detected during the generations of those voltage vectors in this way.
  • the following five cases other than the example of FIG. 5 are conceivable by switching the sequence of setting the switching signals Qup to Qwp to 1.
  • the two voltage vectors V3 and V2 are generated by setting Qvp, Qup, and Qwp to 1 in this sequence, and the bus current Idc is detected during the generations of those voltage vectors.
  • the bus current Idc detected at the time point ts1-1(n) is equal to the current Iv flowing through the V phase
  • the bus current Idc detected at the time point ts1-2(n) is equal to a sign-inverted value -Iw of the current flowing through the W phase.
  • the two voltage vectors V3 and V4 are generated by setting Qvp, Qwp, and Qup to 1 in this sequence, and the bus current Idc is detected during the generations of those voltage vectors.
  • the bus current Idc detected at the time point ts1-1(n) is equal to the current Iv flowing through the V phase
  • the bus current Idc detected at the time point ts1-2(n) is equal to a sign-inverted value -Iu of the current flowing through the U phase.
  • the two voltage vectors V5 and V4 are generated by setting Qwp, Qvp, and Qup to 1 in this sequence, and the bus current Idc is detected during the generations of those voltage vectors.
  • the bus current Idc detected at the time point ts1-1(n) is equal to the current Iw flowing through the W phase
  • the bus current Idc detected at the time point ts1-2(n) is equal to the sign-inverted value -Iu of the current flowing through the U phase.
  • the two voltage vectors V5 and V6 are generated by setting Qwp, Qup, and Qvp to 1 in this sequence, and the bus current Idc is detected during the generations of those voltage vectors.
  • the bus current Idc detected at the time point ts1-1(n) is equal to the current Iw flowing through the W phase
  • the bus current Idc detected at the time point ts1-2(n) is equal to a sign-inverted value -Iv of the current flowing through the V phase.
  • the two voltage vectors V1 and V6 are generated by setting Qup, Qwp, and Qvp to 1 in this sequence, and the bus current Idc is detected during the generations of those voltage vectors.
  • the bus current Idc detected at the time point ts1-1(n) is equal to the current lu flowing through the U phase
  • the bus current Idc detected at the time point ts1-2(n) is equal to a sign-inverted value -Iv of the current flowing through the V phase.
  • the combinations (V1, V2”, “V3, V2”, “V3, V4", “V5, V4", “V5, V6”, and “V1, V6") of the two voltage vectors in the six patterns illustrated in FIG. 5 to FIG. 10 upon the bus current detections are switched to be output in accordance with the rotational position ⁇ of the AC rotating machine 1.
  • a reference phase (0 degrees) of ⁇ and ⁇ q is the U phase direction.
  • the two voltage vectors upon the bus current Idc detection are determined in accordance with the relationship of FIG. 11 . From FIG. 11 , for example, when ⁇ q is in a range of from 0 degrees to 60 degrees, voltage vectors V1 and V2 illustrated in FIG.
  • the switching signal generation part 5 outputs the switching signals Qup to Qwn to the power conversion part 3 so as to output the voltage vectors V1 and V2 (the same applies in the following).
  • the switching signal generation part 5 outputs the switching signals Qup to Qwn to the power conversion part 3 so as to output the voltage vectors V1 and V2 (the same applies in the following).
  • two voltage vectors are similarly generated in accordance with FIG. 11 .
  • FIG. 12 is a diagram for illustrating a dq axis coordinate and the q axis phase ⁇ q in addition to the diagram of FIG. 3 .
  • FIG. 12 is a diagram for illustrating a case where ⁇ q is in a range of from 0 degrees to 60 degrees. In this case, the two vectors on both sides of the q axis are V1 and V2.
  • the two vectors on both sides of the Q axis are "V3 and V2", “V3 and V4", “V5 and V4", “V5 and V6”, and “V1 and V6", respectively.
  • the two voltage vectors corresponding to ⁇ q of FIG. 11 are two voltage vectors on both sides of the q axis.
  • the AC rotating machine 1 has the relationship Ld ⁇ Lq, and, in this case, the selection of the two voltage vectors on both sides of the q axis is equal to selection of two voltage vectors on both sides of an axis having a larger inductance out of the d and q axes.
  • FIG. 13 is a diagram for illustrating the currents lu, Iv, and Iw flowing through the three-phase winding in addition to the diagram of FIG. 5 .
  • lu varies by amounts ⁇ lu_1 and ⁇ lu_2
  • Iw varies by amounts ⁇ lw_1 and ⁇ lw_2 during ⁇ 1 and ⁇ 2, respectively.
  • the average current of lu and the average current of Iw do not respectively match a detection value of lu and a detection value of Iw, resulting in generation of detection errors.
  • the current detection correction part uses the power supply voltage of the inverter, the duty command values for the respective phases, the counter electromotive voltage information on the motor, the motor currents in the respective phases detected by the current detector, the arrangement information on the PWM, and the electrical characteristic equation of the motor to calculate the current detection correction value, thereby correcting the detection error to acquire the average current.
  • the calculation of the correction value requires a large amount of calculation, resulting in such a problem that implementation by using an inexpensive microcomputer is difficult.
  • temperature fluctuation of the motor causes fluctuation in the flux interlinkage number, which is proportional to a resistance R and a counter electromotive voltage EMF of the motor.
  • an inductance L of the motor fluctuates due to influence of magnetic saturation when a current is supplied to the winding of the motor.
  • the motor constants fluctuate in this way, and errors occur between the motor constants and motor constants stored in the current detection correction part, and an error occurs between a difference between the motor current in each phase detected by the current detector and the motor average current and the current detection correction value, resulting in such a problem that the motor currents in the respective phases detected by the current detector cannot be corrected to acquire the motor average current.
  • a variation amount of the current during the output of the voltage vectors V1 to V6 other than V0 and V7 is inversely proportional to the inductance value in the direction of the voltage vector.
  • a voltage vector close to an axis having a large inductance only needs to be selected in order to decrease the variation amount of the current.
  • the AC rotating machine 1 having the relationship Lq>Ld when a voltage vector close to the q axis is selected, the inductance in the direction of the voltage vector becomes larger, and as a result, the current variation amount can be decreased.
  • FIG. 14 is a diagram for illustrating a phase-inductance characteristic when ⁇ q exists in a range of from 0 degrees to 180 degrees.
  • L(V1), L(V2), L(V3), and L(V4) are inductance values in directions of V1, V2, V3, and V4, respectively.
  • the inductance characteristic of the AC rotating machine 1 is a characteristic on a sinusoidal wave having the maximum value Lq, the minimum value Ld, and a cycle of 180 degrees. Thus, a phase closer to the q axis has a larger inductance value.
  • FIG. 14 is a diagram for illustrating a phase-inductance characteristic when ⁇ q exists in a range of from 0 degrees to 180 degrees.
  • L(V1), L(V2), L(V3), and L(V4) are inductance values in directions of V1, V2, V3, and V4, respectively.
  • the inductance characteristic of the AC rotating machine 1 is a characteristic on a sinusoidal wave having the maximum value Lq, the minimum
  • the inductances L(V1) and L(V2) corresponding to the V1 and V2 close in the phase to the q axis are values equal to or more than the other inductance values.
  • those two voltage vectors V1 and V2 close to the q axis are on both sides of the q axis.
  • the bus current Idc is detected when the two voltage vectors on both sides of the axis having a large inductance are output.
  • the variation amounts of the currents Iu, Iv, and Iw flowing through the three-phase winding can be decreased during the output of the two voltage vectors.
  • the calculation by the current detection correction part is not necessary as in the related art, and the currents Iu, Iv, and Iw flowing through the three-phase winding can precisely be acquired.
  • the bus current is detected when the two voltage vectors on both sides of the axis having a large inductance are output, and for example, in FIG. 13 , the variation values ⁇ lu_1 and ⁇ lu_2 of lu can be decreased, and further, the variation values ⁇ lw_1 and ⁇ lw_2 of Iw can be decreased through simple calculation.
  • the values respectively closer to the average current lu and the average current Iw can be acquired as a detection value of lu and a detection value of Iw.
  • two voltage vectors for supplying a current from the DC power supply 2 to the AC rotating machine 1 (hereinafter referred to as power running mode) upon the current detection in the power running operation state may be selected by the switching signal generation part 5. A description is now given of an effect obtained through this selection.
  • FIG. 17 is a diagram for illustrating an operation when the two voltage vectors V5 and V4 are generated by setting Qwp, Qvp, and Qup to 1 in this sequence, and the bus current Idc is detected during the generations of the voltage vectors.
  • the sum of the three-phase currents is zero, and when any one of the three-phase currents has a different value, the current in at least one phase has thus a negative value.
  • the bus current Idc detected at the time point ts1-1(n) is equal to the current Iw flowing through the W phase, the bus current Idc has a positive value, and the mode is in the power running mode in which the bus current Idc flows from the DC power supply 2 to the AC rotating machine 1.
  • the bus current Idc detected at the time point ts1-2(n) is equal to the sign-inverted value -lu of the current flowing through the U phase, the bus current Idc has a positive value, and the mode is in the power running mode in which the bus current Idc flows from the DC power supply 2 to the AC rotating machine 1.
  • FIG. 18 is a diagram for illustrating an operation when the two voltage vectors V1 and V2 are generated by setting Qup, Qvp, and Qwp to 1 in this sequence, and the bus current Idc is detected during the generations of the voltage vectors.
  • the bus current Idc detected at the time point ts1-1(n) is equal to the current lu flowing through the U phase, the bus current Idc has a negative value, and the mode is in the regeneration mode in which the bus current Idc flows from the DC power supply 2 to the AC rotating machine 1.
  • the bus current Idc detected at the time point ts1-2(n) is equal to the sign-inverted value -Iw flowing through the W phase, the bus current Idc has a negative value, and the mode is in the regeneration mode in which the bus current Idc flows from the DC power supply 2 to the AC rotating machine 1.
  • a power loss is acquired by a product of the square of the bus current Idc and an internal resistance R of the DC power supply 2.
  • a power loss is generated in portions in the power running mode other than regions in which the voltage vector is V0 or V7.
  • the period of the power running mode is increased by a period of the regeneration mode, and a power loss is generated even in the regeneration mode.
  • a power loss increases when the voltage vectors, which bring the mode into the regeneration mode in the power running operation state, are selected.
  • the switching signal generation part 5 outputs the two voltage vectors, which bring the mode into the power running mode upon the current detection in the power running operation state, thereby providing such an effect that a power loss can be decreased.
  • the phase angle ⁇ is 180 degrees and the phase ⁇ is 300 degrees as an example, but it should be understood that another combination is possible.
  • two voltage vectors for bringing the mode into the regeneration mode of supplying a current from the AC rotating machine 1 to the DC power supply 2 upon the current detection in the regeneration operation state may be selected by the switching signal generation part 5.
  • FIG. 19 is a diagram for illustrating an operation when the two voltage vectors V1 and V2 are generated by setting Qup, Qvp, and Qwp to 1 in this sequence, and the bus current Idc is detected during the generations of the voltage vectors when the AC rotating machine 1 is in the regeneration operation state.
  • the sum of the three-phase currents is zero, and when any one of the three-phase currents has a different value, the current in at least one phase has thus a positive value.
  • the bus current Idc detected at the time point ts1-1(n) is equal to the current lu flowing through the U phase, the bus current Idc has a negative value, and the mode is in the regeneration mode in which the bus current Idc flows from the AC rotating machine 1 to the DC power supply 2.
  • the bus current Idc detected at the time point ts1-2(n) is equal to the sign inverted value -Iw of the current flowing through the W phase, the bus current Idc has a negative value, and the mode is in the regeneration mode in which the bus current Idc flows from the AC rotating machine 1 to the DC power supply 2.
  • FIG. 20 is a diagram for illustrating a comparative example of an operation when the two voltage vectors V5 and V4 are generated by setting Qvp, Qup, and Qwp to 1 in this sequence, and the bus current Idc is detected during the generations of the voltage vectors.
  • the bus current Idc detected at the time point ts1-1(n) is equal to the current Iw flowing through the W phase, the bus current Idc has a positive value, and the mode is in the power running mode in which the bus current Idc flows from the DC power supply 2 to the AC rotating machine 1 .
  • the bus current Idc detected at the time point ts1-2(n) is equal to the sign inverted value -Iu of the current flowing through the U phase, the bus current Idc has a positive value, and the mode is in the power running mode in which the bus current Idc flows from the DC power supply 2 to the AC rotating machine 1.
  • a power loss is acquired by a product of the square of the bus current Idc and the internal resistance R of the DC power supply 2.
  • a power loss is generated in portions in the regeneration mode other than regions in which the voltage vector is V0 or V7.
  • the period of the regeneration mode is increased by a period of the power running mode, and a power loss is generated even in the power running mode.
  • a power loss increases when the voltage vectors, which bring the mode into the power running mode in the regeneration operation state, are selected.
  • the switching signal generation part 5 outputs the two voltage vectors, which bring the two voltage vectors into the regeneration mode upon the current detection in the regeneration operation state, thereby providing such an effect that a power loss can be decreased.
  • the two voltage vectors for the detection of the bus current may be selected based on a sequence in the amplitude of the voltage command or the voltage phase ⁇ v.
  • the voltage phase is an angle ⁇ v of a voltage command vector V* while the U1 phase direction is set as a reference.
  • the voltage command V* is represented as follows through the voltage commands Vu, Vv, and Vw of the first winding.
  • the selection of the two voltage vectors in accordance with the voltage phase ⁇ v or the sequence in the amplitude of the voltage commands is equivalent to selection of two voltage vectors neighboring the voltage command vector V*.
  • the power conversion device can be applied to an electric power steering in which a torque assisting a steering torque of a steering system is generated by the AC rotating machine 1, and as a result, an inexpensive microcomputer can be used to construct a steering system having a small steering torque ripple.
  • FIG. 31 An example of a configuration of a control device for the electric power steering according to the present invention is schematically illustrated in FIG. 31 .
  • the AC rotating machine 1 is attached to a steering shaft so as to apply the assist torque, and a power conversion unit PT is constructed by portions other than the AC rotating machine 1 of FIG. 1 , and the like.
  • FIG. 23 is a diagram for illustrating an overall configuration of a power conversion device according to a second embodiment of the present invention. A redundant description is not given of portions common to those of the first embodiment.
  • two systems of electric conversion parts 3a and 3b are connected between the DC power supply 2 and an AC rotating machine 1a.
  • a current detection part 10 and a phase current calculation part 8a are provided for the power conversion part 3a, and are supplied with the same switching signals Qup1 to Qwn1 from the switching signal generation part 5a as those to the power conversion part 3a.
  • a current detection part 11 and a phase current calculation part 8b are provided for the power conversion part 3b, and are supplied with the same switching signals Qup2 to Qwn2 as those to the power conversion part 3b.
  • the AC rotating machine 1a includes a first three-phase winding (generally, a multi-phase winding) C1 having U1, V1, and W1 phases, and a second three-phase winding (generally, a multi-phase winding) C2 having U2, V2, and W2 phases, and is, for example, a permanent magnet synchronous rotating machine having a phase difference of 30 degrees between the first three-phase winding C1 and the second three-phase winding C2.
  • the first power conversion part 3a is configured to turn on/off semiconductor switches Sup1 to Swn1 based on first switching signals Qup1 to Qwn1, thereby applying power conversion to the DC voltage Vdc input from the DC power supply 2, and applying AC voltages on the first three-phase winding C1 having U1, V1, and W1 phases of the AC rotating machine 1a.
  • a semiconductor switching device e.g., an IGBT, a bipolar transistor, or a MOS power transistor and a diode connected to each other in an anti-parallel connection state are used.
  • the first switching signals Qup1, Qun1, Qvp1, Qvn1, Qwp1, and Qwn1 are switching signals for respectively turning on/off the semiconductor switches Sup1, Sun1, Svp1, Svn1, Swp1, and Swn1 in the first power conversion part 3a.
  • the second power conversion part 3b is configured to turn on/off semiconductor switches Sup2 to Swn2 based on second switching signals Qup2 to Qwn2, thereby applying power conversion to the DC voltage Vdc input from the DC power supply 2, and applying AC voltages on the second three-phase winding C2 having U2, V2, and W2 phases of the AC rotating machine 1a.
  • a semiconductor switching device e.g., an IGBT, a bipolar transistor, or a MOS power transistor and a diode connected to each other in an anti-parallel connection state are used.
  • the second switching signals Qup2, Qun2, Qvp2, Qvn2, Qwp2, and Qwn2 are switching signals for respectively turning on/off the semiconductor switches Sup2, Sun2, Svp2, Svn2, Swp2, and Swn2 in the second power conversion part 3b.
  • the switching signal generation part 5a is configured to carry out pulse width modulation (PWM modulation) based on the first voltage commands Vu1, Vv1, and Vw1 output from the voltage command calculation part 6a, thereby outputting the switching signals Qup1 to Qwn1 having pulse widths in accordance with Vu1, Vv1, and Vw1, and to carry out pulse width modulation (PWM modulation) based on the second voltage commands Vu2, Vv2, and Vw2 output from the voltage command calculation part 6a, thereby outputting the switching signals Qup2 to Qwn2 having pulse widths in accordance with Vu2, Vv2, and Vw2.
  • PWM modulation pulse width modulation
  • the first current detection part 10 is configured to detect a first bus current Idc1, which is a current flowing between the DC power supply 2 and the power conversion part 3a, and output a detection result to a first phase current calculation part 8a.
  • the first current detection part 10 is constructed by a shunt resistor 10a and a sample-and-hold device 10b configured to sample and hold the current flowing through the shunt resistor 10a, thereby detecting the first bus current Idc1.
  • a current transformer (CT) may be used in place of the shunt resistor 10a, and in this case, an output voltage of the current transformer is sampled and held by the sample-and-hold device 10b, thereby detecting the first bus current Idc1.
  • the second current detection part 11 is configured to detect a second bus current Idc2, which is a current flowing between the DC power supply 2 and the second power conversion part 3b, and output a detection result to the second phase current calculation part 8b.
  • the second current detection part 11 is constructed by a shunt resistor 11a and a sample-and-hold device 11b configured to sample and hold the current flowing through the shunt resistor 11a, thereby detecting the second bus current Idc2.
  • a current transformer (CT) may be used in place of the shunt resistor 11a, and in this case, an output voltage of the current transformer is sampled and held by the sample-and-hold device 11b, thereby detecting the second bus current Idc2.
  • the voltage command calculation part 6a is configured to calculate the first voltage commands Vu1, Vv1, and Vw1 and the second voltage commands Vu2, Vv2, and Vw2 for driving the AC rotating machine 1a, and output the first voltage commands and the second voltage commands to the switching signal generation part 5a.
  • V/F control As a method of calculating the first voltage commands Vu1, Vv1, and Vw1 and the second voltage commands Vu2, Vv2, and Vw2, there exists V/F control of setting a speed (frequency) command f for the AC rotating machine 1a as a control command of FIG. 23 and then determining the amplitudes of the first voltage commands and the second voltage commands.
  • current feedback control or the like is used, which is control of setting current commands for the AC rotating machine 1a as the control commands, calculating, based on differences from the currents Iu1, Iv1, and Iw1 flowing through the first-three phase winding and output from the first phase current calculation part 8a, the first voltage commands Vu1, Vv1, and Vw1 so as to bring the differences to zero through the proportional-integral control, and simultaneously calculating, based on differences between the current commands and the currents Iu2, Iv2, and Iw2 flowing through the second three-phase winding output from the second phase current calculation part 8b, the second voltage commands Vu2, Vv2, and Vw2 so as to bring the differences to zero through the proportional-integral control.
  • the V/F control is feedforward control, and the first three-phase currents Iu1, Iv1, and Iw1 and the second three-phase current Iu2, Iv2, and Iw2 are not necessary.
  • the input of the first three-phase currents Iu1, Iv1, and Iw1 to the voltage command calculation part 6a, and the input of the second three-phase currents Iu2, Iv2, and Iw2 are not indispensable.
  • FIG. 24 is a table for showing the relationship among the first switching signals Qup1 to Qwn1, the first voltage vectors, the first bus current Idc1, and the currents Iu1, Iv1, and Iw1 flowing through the first three-phase winding.
  • FIG. 24 is basically the same as FIG. 2 .
  • a suffix (1) of the first voltage vector is assigned to denote the first voltage vector, and is assigned so as to be distinguished from second voltage vectors described later.
  • FIG. 25 is a table for showing the relationship among the second switching signals Qup2 to Qwn2, the second voltage vectors, the second bus current Idc2, and the currents Iu2, Iv2, and Iw2 flowing through the second three-phase winding.
  • FIG. 25 is basically the same as FIG. 2 .
  • a suffix (2) of the second voltage vector is assigned to denote the second voltage vector.
  • the first phase current calculation part 8a is configured to output Iu1, Iv1, and Iw1 from the relationship shown in FIG. 24 based on the first bus current Idc1 and the first switching signals Qup1 to Qwn1.
  • V0 and V7 cannot be used to detect the three-phase currents based on the bus current.
  • the voltage vector V1 is output to detect Iu1
  • the voltage vector V2 is output to detect -Iw1.
  • There may be provided such a configuration that, based on the fact that a sum of the currents flowing through the three phases is zero in the three-phase three-line rotating machine, the acquired detected current values in the two phases are used to calculate a current in the remaining one phase. In other words, only such a configuration that appropriate voltage vectors are selected, thereby detecting the currents for at least two phases is necessary.
  • the second phase current calculation part 8b outputs Iu2, Iv2, and Iw2 from the relationship shown in FIG. 25 based on the second bus current Idc2 and the second switching signals Qup2 to Qwn2.
  • V0 and V7 cannot be used to detect the three-phase currents based on the bus current.
  • the voltage vector V1 is output to detect Iu2
  • the voltage vector V2 is output to detect -Iw2.
  • FIG. 26 is an operation explanatory diagram in the cycle Ts of the switching signal relating to a method of generating the first switching signals Qup1 to Qwn1 and the second switching signals Qup2 to Qwn2 in the second switching signal generation part 5a, and detection timings of the first bus current Idc1 in the first current detection part 10 and the second bus current Idc2 in the second current detection part 11 according to the second embodiment. As shown in FIG. 24 and FIG.
  • Qun1, Qvn1, Qwn1, Qun2, Qvn2, and Qwn2 are in an inverted relationship with Qup1, Qvp1, Qwp1, Qup2, Qvp2, and Qwp2 (1 for 0 and 0 for 1 except for dead time periods), respectively, and are thus omitted.
  • Qup1 and Qup2 are set to 1, and Qvp1, Qwp1, Qvp2, and Qwp2 are set to 0 at the time point t1(n), and this switching pattern is maintained until the time point t2(n) at which ⁇ t1 has elapsed after the time point t1(n).
  • the first voltage vector is V1(1)
  • the second voltage vector is V1(2) from the time point t1(n) to the time point t2(n).
  • the first bus current Idc1 and the second bus current Idc2 are detected at the time point ts1-1(n) in the period from the time point t1(n) to the time point t2(n).
  • Qvp1 and Qvp2 are set to 1 at the time point t2(n), and this switching pattern is maintained until the time point t3(n).
  • the first bus current Idc1 and the second bus current Idc2 are again detected at the time point ts1-2(n) in the period.
  • Qwp1 and Qwp2 are set to 1 at the time point t3(n).
  • Pulse widths (periods in which the value 1 is maintained) of Qup1 to Qwp2 are determined by the first voltage commands Vu1, Vv1, and Vw1 and the second voltage commands Vu2, Vv2, and Vw2, and timings at which Qup1 to Qwp2 become 0 are thus determined in accordance with the pulse widths.
  • the stator windings (C1 and C2) have the phase difference of 30 degrees in the electrical angle between the U1 winding and the U2 winding, between the V1 winding and the V2 winding, and between the W1 winding and the W2 winding.
  • FIG. 29 winding directions of the three-phase winding (C1) having the U1, V1, and W1 phases represented by the dotted lines are superimposed on winding directions of the second three-phase winding (C2) having the U2, V2, and W2 phases represented by the solid lines.
  • U1, V1, and W1 may be referred to as first three-phase windings
  • U2, V2, and W2 may be referred to as second three-phase windings.
  • FIG. 28 is a diagram for illustrating the first voltage vectors, and is the same as that described in the first embodiment.
  • the second voltage vectors are represented by the solid lines, and the first voltage vectors are represented by the broken lines.
  • the vectors V0(2) and V(2) are represented by the black dots at the origin.
  • V0(1) and V7(1) similarly exist at the origin, but are omitted.
  • the AC rotating machine 1a according to the second embodiment has the phase difference of 30 degrees between the first three-phase winding C1 and the second three-phase winding C2.
  • V0(1), V0(2), V7(1), and V7(2) having no magnitude, all of
  • the reference phase (0 degrees) of ⁇ and ⁇ q is the U1 phase direction.
  • the two first voltage vectors are determined upon the detection of the first bus current Idc1 and the two second voltage vectors are determined upon the detection of the second bus current Idc2 in accordance with the relationship of FIG. 30 .
  • the d axis component thereof is denoted by Md
  • the q axis component thereof is denoted by Mq
  • the following setting may be provided.
  • the inductance is set as a sum of the respective self-inductances of the first three-phase winding C1 and the second three-phase winding C2, and the mutual inductance between the first three-phase winding C1 and the second three-phase winding C2.
  • the switching signal generation part 5a may be configured to output the two voltage vectors for bringing the mode to the power running mode upon the current detection in order to provide the effect of the decrease in the power loss in the power running operation state.
  • the switching signal generation part 5a may be configured to output the two voltage vectors for bringing the mode to the regeneration mode upon the current detection in order to provide the effect of the decrease in the power loss in the regeneration operation state.
  • the operation in the power running operation state and the operation in the regeneration operation state may be combined to be carried out.
  • the present invention can be applied to a device provided with an AC rotating machine including one or a plurality of multi-phase windings of four or more phases.
  • the power conversion device, and the like, according to the present invention can be applied to a power conversion device, and the like, in various fields.

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Claims (11)

  1. Dispositif de conversion de puissance, comprenant :
    une machine rotative à CA (1) à saillance, et incluant un enroulement polyphasé de trois phases ou plus ;
    une alimentation électrique CC (2) configurée pour délivrer une tension CC ;
    une partie de calcul d'instruction de tension (6) configurée pour calculer des instructions de tension sur la base d'une instruction de commande provenant d'un extérieur pour la machine rotative à CA ;
    une partie de génération de signal de commutation (5) configurée pour émettre des signaux de commutation correspondant à au moins deux vecteurs de tension sur les deux côtés d'un axe présentant une inductance plus importante parmi des axes d et q de la machine rotative à CA, et correspondant aux instructions de tension ;
    une partie de conversion de puissance (3) configurée pour réaliser, sur la base des signaux de commutation, une ou les deux d'une opération de conversion de la tension CC provenant de l'alimentation électrique CC en tension CA et d'amener de la tension CA à la machine rotative à CA pendant une opération de fonctionnement électrique, et une opération de conversion d'une force électromotrice de la machine rotative à CA en courant CC et d'amenée du courant CC à l'alimentation électrique CC pendant une opération de régénération ;
    une partie de détection de courant (7) configurée pour détecter un courant de bus, qui est un courant circulant entre l'alimentation électrique CC et la partie de conversion de puissance ; et
    une partie de calcul de courant de phase (8) configurée pour calculer, sur la base du courant de bus détecté, un courant de phase circulant à travers l'enroulement polyphasé de la machine rotative à CA,
    dans lequel la partie de détection de courant (7) est configurée pour détecter le courant de bus lorsque les signaux de commutation correspondant aux au moins deux vecteurs de tension sont émis.
  2. Dispositif de conversion de puissance selon la revendication 1, dans lequel la partie de génération de signal de commutation (5) est configurée pour émettre les signaux de commutation correspondant à un vecteur de tension lorsqu'un courant est amené de l'alimentation électrique CC (2) à la machine rotative à CA (1) à un moment auquel le courant de bus est détecté par la partie de détection de courant (7) dans un cas où la machine rotative à CA se trouve dans un état d'opération de fonctionnement électrique.
  3. Dispositif de conversion de puissance selon la revendication 1 ou 2, dans lequel la partie de génération de signal de commutation (5) est configurée pour émettre les signaux de commutation correspondant à un vecteur de tension lorsqu'un courant est amené de la machine rotative à CA (1) à l'alimentation électrique CC (2) à un moment auquel le courant de bus est détecté par la partie de détection de courant (7) dans un cas où la machine rotative à CA (1) est dans un état d'opération de régénération.
  4. Dispositif de conversion de puissance selon l'une quelconque des revendications 1 à 3, dans lequel la partie de détection de courant (7) est configurée pour détecter le courant de bus à un moment des signaux de commutation correspondant aux au moins deux vecteurs de tension sur les deux côtés d'un vecteur d'instruction de tension lorsqu'une amplitude des instructions de tension est supérieure à un seuil.
  5. Dispositif de conversion de puissance, comprenant :
    une machine rotative à CA (1a) à saillance, et incluant un premier enroulement polyphasé et un second enroulement polyphasé de trois phases ou plus ;
    une alimentation électrique CC (2) configurée pour délivrer une tension CC ;
    une partie de calcul d'instruction de tension (6a) destinée à calculer des premières instructions de tension et des secondes instructions de tension sur la base d'une instruction de commande provenant d'un extérieur pour la machine rotative à CA;
    une partie de génération de signal de commutation (5a) configurée pour émettre des premiers signaux de commutation correspondant à au moins deux premiers vecteurs de tension sur les deux côtés d'un axe présentant une inductance plus importante parmi des axes d et q du premier enroulement polyphasé de la machine rotative à CA (1a), et correspondant aux premières instructions de tension, et pour émettre des seconds signaux de commutation correspondant à au moins deux seconds vecteurs de tension sur les deux côtés d'un axe présentant une inductance plus importante parmi des axes d et q du second enroulement polyphasé de la machine rotative à CA, et correspondant aux secondes instructions de tension ;
    une première partie de conversion de puissance (3a) configurée pour réaliser, sur la base des premiers signaux de commutation, une ou les deux d'une opération de conversion de la tension CC provenant de l'alimentation électrique CC (2) en tension CA et d'amener de la tension CA au premier enroulement polyphasé de la machine rotative à CA (1a) pendant une opération de fonctionnement électrique, et une opération de conversion d'une force électromotrice du premier enroulement polyphasé de la machine rotative à CA (1a) en courant CC et d'amener du courant CC à l'alimentation électrique CC (2) pendant une opération de régénération ;
    une seconde partie de conversion de puissance (3b) configurée pour réaliser, sur la base des seconds signaux de commutation et en synchronisation avec la première partie de conversion de puissance (3a), une ou les deux d'une opération de conversion de la tension CC provenant de l'alimentation électrique CC (2) en tension CA et d'amener de la tension CA au second enroulement polyphasé de la machine rotative à CA (1a) pendant l'opération de fonctionnement électrique, et une opération de conversion d'une force électromotrice du second enroulement polyphasé de la machine rotative à CA (1a) en courant CC et d'amenée du courant CC à l'alimentation électrique CC (2) pendant l'opération de régénération ;
    une première partie de détection de courant (10) configurée pour détecter un premier courant de bus, qui est un courant circulant entre l'alimentation électrique CC (2) et la première partie de conversion de puissance (3a) ;
    une seconde partie de détection de courant (11) configurée pour détecter un second courant de bus, qui est un courant circulant entre l'alimentation électrique CC (2) et la seconde partie de conversion de puissance (3b) ;
    une première partie de calcul de courant de phase (8a) configurée pour calculer, sur la base du premier courant de bus détecté, un courant de phase circulant à travers le premier enroulement polyphasé de la machine rotative à CA (1a) ; et
    une seconde partie de calcul de courant de phase (8b) configurée pour calculer, sur la base du second courant de bus détecté, un courant de phase circulant à travers le second enroulement polyphasé de la machine rotative à CA (1a), dans lequel :
    la première partie de détection de courant (10) est configurée pour détecter le premier courant de bus lorsque les premiers signaux de commutation correspondant aux au moins deux premiers vecteurs de tension sont émis ; et
    la seconde partie de détection de courant (11) est configurée pour détecter le second courant de bus lorsque les seconds signaux de commutation correspondant aux au moins deux seconds vecteurs de tension sont émis.
  6. Dispositif de conversion de puissance selon la revendication 5, dans lequel l'inductance comprend une somme d'inductances propres respectives du premier enroulement polyphasé et du second enroulement polyphasé, et une inductance mutuelle entre le premier enroulement polyphasé et le second enroulement polyphasé.
  7. Dispositif de conversion de puissance selon la revendication 5 ou 6, dans lequel la partie de génération de signal de commutation (5a) est configurée pour émettre les premiers signaux de commutation et les seconds signaux de commutation correspondant à un vecteur de tension respectivement lorsqu'un courant est amené de l'alimentation électrique CC (2) à la machine rotative à CA (1a) aux moments respectifs auxquels le premier courant de bus et le second courant de bus sont détectés par la première partie de détection de courant (10) et la seconde partie de détection de courant (11) respectivement dans un cas où la machine rotative à CA (1a) est dans un état d'opération de fonctionnement électrique.
  8. Dispositif de conversion de puissance selon l'une quelconque des revendications 5 à 7, dans lequel la partie de génération de signal de commutation (5a) est configurée pour émettre les premiers signaux de commutation et les seconds signaux de commutation correspondant à un vecteur de tension respectivement lorsqu'un courant est amené de la machine rotative à CA (1a) à l'alimentation électrique CC (2) aux moments respectifs auxquels le premier courant de bus et le second courant de bus sont détectés par la première partie de détection de courant (10) et la seconde partie de détection de courant (11) respectivement dans un cas où la machine rotative à CA (1a) est dans un état d'opération de régénération.
  9. Dispositif de conversion de puissance selon l'une quelconque des revendications 5 à 8, dans lequel la première partie de détection de courant (10) et la seconde partie de détection de courant (11) sont configurées pour détecter le premier courant de bus et le second courant de bus respectivement à des moments respectifs du premier signal de commutation et du second signal de commutation correspondant aux au moins deux vecteurs de tension sur les deux côtés d'un vecteur d'instruction de tension lorsqu'une amplitude des instructions de tension est supérieure à un seuil.
  10. Dispositif de commande pour une direction assistée électrique, comprenant le dispositif de conversion de puissance selon l'une quelconque des revendications 1 à 9, de sorte que la machine rotative à CA (1a) génère un couple destiné à assister un couple de direction d'un système de direction.
  11. Procédé de commande pour un dispositif de conversion de puissance, comprenant :
    le calcul, par une partie de calcul d'instruction de tension (6), d'instructions de tension sur la base d'une instruction de commande provenant d'un extérieur pour une machine rotative à CA (1) à saillance, et incluant un enroulement polyphasé de trois phases ou plus ;
    l'émission, par une partie de génération de signal de commutation (5), de signaux de commutation correspondant à au moins deux vecteurs de tension sur les deux côtés d'un axe présentant une inductance plus importante parmi des axes d et q de la machine rotative à CA (1), et correspondant aux instructions de tension ;
    la réalisation, par une partie de conversion de puissance (3), sur la base des signaux de commutation, d'une ou des deux de conversion d'une tension CC provenant d'une alimentation électrique CC (2) en une tension CA et d'amenée de la tension CA à la machine rotative à CA (1) pendant une opération de fonctionnement électrique, et de conversion d'une force électromotrice de la machine rotative à CA (1) en courant CC et d'amenée du courant CC à l'alimentation électrique CC (2) pendant une opération de régénération ;
    de détection, par une partie de détection de courant (7), d'un courant de bus, qui est un courant circulant entre l'alimentation électrique CC (2) et la partie de conversion de puissance (3) ;
    de calcul, par une partie de calcul de courant de phase (8), sur la base du courant de bus, d'un courant de phase circulant à travers l'enroulement polyphasé de la machine rotative à CA (1) ; et
    de détection, par la partie de détection de courant (7), du courant de bus lorsque les signaux de commutation correspondant aux au moins deux vecteurs de tension sont émis.
EP14903537.0A 2014-10-08 2014-10-08 Dispositif de conversion de puissance et son procédé de commande, et dispositif de commande de direction assistée électrique Active EP3206297B1 (fr)

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PCT/JP2014/076936 WO2016056083A1 (fr) 2014-10-08 2014-10-08 Dispositif de conversion de puissance et son procédé de commande, et dispositif de commande de direction assistée électrique

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JP7245057B2 (ja) * 2019-01-22 2023-03-23 日立Astemo株式会社 モータ制御装置

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JP3675431B2 (ja) * 2002-10-01 2005-07-27 松下電器産業株式会社 電動機駆動装置
US6984948B2 (en) * 2002-12-12 2006-01-10 Matsushita Electric Industrial Co., Ltd. Motor control apparatus
JP4804381B2 (ja) * 2007-02-28 2011-11-02 三菱電機株式会社 電動機駆動制御装置及び電動機
JP5259303B2 (ja) * 2008-08-26 2013-08-07 株式会社東芝 インバータ装置
JP4746667B2 (ja) * 2008-11-26 2011-08-10 本田技研工業株式会社 電動機の相電流推定装置および電動機の磁極位置推定装置
JP2011015472A (ja) * 2009-06-30 2011-01-20 Sanyo Electric Co Ltd インバータ装置
JP5150585B2 (ja) * 2009-08-28 2013-02-20 株式会社日立産機システム 永久磁石同期電動機の駆動装置
JP5409422B2 (ja) * 2010-02-08 2014-02-05 三菱電機株式会社 同期電動機の磁極位置検出装置
US8339084B2 (en) * 2010-03-12 2012-12-25 GM Global Technology Operations LLC Systems and methods for monitoring current in an electric motor
JP5811438B2 (ja) * 2011-04-22 2015-11-11 株式会社リコー モータ駆動装置
JP5724776B2 (ja) 2011-09-12 2015-05-27 日本精工株式会社 モータ制御装置及び電動パワーステアリング装置
JP5993616B2 (ja) 2012-05-25 2016-09-14 日立オートモティブシステムズ株式会社 電動機の駆動制御装置
WO2015068300A1 (fr) * 2013-11-11 2015-05-14 三菱電機株式会社 Dispositif de conversion d'électricité
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CN107155394B (zh) 2019-06-11
US9935575B2 (en) 2018-04-03
JP6381662B2 (ja) 2018-08-29
JPWO2016056083A1 (ja) 2017-04-27
EP3206297A1 (fr) 2017-08-16
EP3206297A4 (fr) 2018-06-27
WO2016056083A1 (fr) 2016-04-14
US20170272019A1 (en) 2017-09-21
CN107155394A (zh) 2017-09-12

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