Classifications

• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
  • H02M1/00—Details of apparatus for conversion
  • H02M1/38—Means for preventing simultaneous conduction of switches
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
  • H02M3/00—Conversion of dc power input into dc power output
  • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
  • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
  • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
  • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
  • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
  • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
  • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
  • H02M3/1588—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load comprising at least one synchronous rectifier element
• • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
  • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
  • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
  • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
  • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

• the invention relates to a method and a device for determining and / or adjusting, in particular regulation and / or control of a dead time between the opening of a first switching element and the closing of a second switching element in a switching power supply with active freewheel.
• Switching power supplies for converting a DC input voltage into a supply voltage are often constructed with active freewheel, in which a first switching element is connected in series with a second switching element, wherein the second
• Switching element takes over the function of the active freewheel.
• the switching regulator is supplied with the DC input voltage.
• Parallel to the second switching element an inductor is connected in series with a capacitor.
• Over the second switching element an output voltage or measurement voltage is tapped.
• About the capacity of the supply voltage is tapped to supply a consumer.
• the first and the second switching element are periodically opened and closed, wherein always at least one of the switching elements is open. The ratio of the closing time of the first switching element to the total duration of closing duration and subsequent opening duration of the first
• Duty cycle is referred to as duty cycle.
• the duty cycle can be set to a given input DC voltage and a given, parallel to the capacitance connected electrical load a desired supply voltage.
• the person skilled in various forms of this basic form of a switching power supply with active freewheel are known, for example as a buck converter or step-down converter.
• Switching elements can be designed as transistors, for example as metal-oxide field-effect transistors (MOSFET). Due to the principle of such MOSFETs can not abrupt, so infinitesimally short switching operations implement, but require for the closing and opening a certain, dependent on the manufacture ⁇ technology and geometry time from a few tenths of a nanosecond up to a few nanoseconds. Furthermore, MOSFETs have technologically caused parasitic diodes between a drain and a source terminal. Such a parasitic diode of the second switching element acts in parallel to the series ⁇ circuit of the inductance and the capacitance across which the supply voltage is tapped.
• MOSFET metal-oxide field-effect transistors
• this parasitic inductance Due to the production, due to wire-like or at least elongated metallic connections between the components, such a switching regulator has a parasitic inductance. Due to the recovery behavior of the para-university ⁇ diode of the second switching element, this parasitic inductance can elements dependent on the switching speed of the switch, the input DC voltage and the electric
• the invention is based on the object to provide a method for determining and / or adjusting the dead time of a switching regulator with active freewheel in a switching power supply, which avoids overvoltage and / or destruction. Furthermore, the invention is based on the object to provide a device for carrying out the method.
• the object is achieved by the features of claim 1.
• the object is achieved by the features of claim 10.
• a measuring ⁇ voltage of the switching power supply via the second switching element are determined and based on the determined measurement voltage, a dead time is varied so that the deviation of the determined measurement voltage is minimized or limited by a desired value.
• the first and the second switching element in the switching regulator with active freewheel of the switching power supply are driven so that the second
• the inventive method can be embodied in the manner of a ge ⁇ closed regulation or control of the dead time by the dead time is determined several times in a loop and adjusted. In one embodiment of the method according to the invention, this comprises
• an initialization of a dead time in a first step, an initialization of a dead time, the initialization of a first overvoltage value of Measuring voltage with an overvoltage starting value greater than or equal to the maximum measurable overvoltage and the initialization of a positive correction direction for the change of the dead time,
• the process may be continued by repeating the sequence of the second to fifth steps.
• the dead time value is reduced by the dead time change; in the case of a positive correction direction, the dead time value is increased by the dead time change.
• the dead time change may be predetermined by a fixed dead time change step size.
• the dead time is set to an initial value that is at least chosen so that a short-circuit current is avoided by overlapping opening and closing of the first and second switching element. It is possible to initialize the dead time value with a standard dead time value for which it is known that in the case of typical loads connected to the switching regulator it will cause no or only slight overshoot of the measuring voltage, and thus also of the supply voltage.
• the correction direction is furthermore initialized as a positive correction direction, so that the dead time value is increased by the dead time change step width when an overvoltage occurs.
• the first overvoltage value is initialized with an overvoltage ⁇ start value.
• an overvoltage start value can be set, for example, as a maximum representable or maximum storable overvoltage value.
• the measured voltage measured with the current dead time setting is determined as the second overvoltage value in a measuring time window which is matched to the dead time.
• a circuit known to the person skilled in the art as a sample-and-hold element or instantaneous value sampling, which circuit can be operated with a trigger signal derived from the drive signals of the switching elements.
• the measurement voltage can be measured at a point in time approximately at the middle of the dead time.
• the second overvoltage value is compared with the first overvoltage value. If the second overvoltage value is below the first overvoltage value, the correction direction is maintained. Otherwise, the correction direction is reversed.
• the dead time is corrected according to the corrective ⁇ direction by the predetermined dead time change step size, that is increased at positive correction direction and reduced at negative correction direction.
• the second, ie the last measured, overvoltage value is assigned to the first overvoltage value and is thus available for comparison with a subsequent overvoltage value still to be measured in a subsequent pass of the second through fifth steps. If the third step is passed through for the first time, the second overvoltage value measured in the second step is never above the first overvoltage value, which was initialized in the first step with a maximum overvoltage starting value. Thus, for the first pass of the third step, it is ensured that the initialized positive correction direction is maintained.
• the correction direction from the previous pass is maintained exactly if this correction direction has caused a reduction of the overvoltage, thus improving the behavior of the switching regulator. In all other cases, the correction direction is changed.
• dead time values are determined with this method, which oscillate around an at least locally optimal dead time value, which is characterized by an at least locally minimum overvoltage value of the measuring voltage.
• dead time values outside, but in the immediate vicinity of the commutated dead time interval would lead to larger overvoltage values of the measurement voltage.
• the adverse overvoltage is minimized by the described method.
• a dead time is in a short-circuit current resul ⁇ advantage, and that in an optimal, namely compared to the setpoint of the measurement voltage not or only minimally increased measurement voltage during the switching of the first and second switching element results.
• the method leads to dead time values which are immediately around the optimum Float dead time, which leads to a minimum overvoltage value.
• Such changes generally require a modified optimal deadtime value to minimize the overvoltage.
• a modified optimal dead time value can be determined at least approximately.
• the second overvoltage value is determined as the maximum value of the measurement voltage over a complete switching cycle of the switching regulator, wherein such switching cycle is determined by the time between the beginning of a first closing of the first switching element and the beginning a subsequent second closing of the first switching element is determined.
• the third and fourth steps of the method are omitted when the second overvoltage value is less than or equal to a predetermined overvoltage limit.
• the at least approximately finding an at least locally optimal dead time value can no longer be guaranteed, but it is sufficient for many practical purposes, if a previously determined
• Overvoltage limit is not significantly exceeded.
• this embodiment represents an advantageously simplified method, since in this embodiment, the limitation of the measurement of the overvoltage profile to a predetermined, based on the current dead time measurement time window is omitted.
• advantageous manner ⁇ characterized a simpler arrangement may be used for the measurement of an overvoltage value.
• the overvoltage limit value is determined as a function of a predetermined desired value of the measurement voltage. In many significant applications, electrical loads can be supplied with supply voltages, which in a certain amount
• Corridor by a setpoint of a supply voltage For example, variations of plus or minus ten percent of the setpoint of the supply voltage from such electrical loads may be tolerated. It is therefore not necessary in these cases to limit the overvoltage at the measuring output of a switching power supply to a minimum, but only necessary to avoid exceeding the tolerated corridor of supply voltages. So it is for example possible to determine a surge limit corresponding to 1.05 times the nominal value of the measured voltage when it is known that consumers tolerate fluctuations in the supply voltage ⁇ 10 percent to a target value.
• a safe operation of consumers with minimal control effort for the dead time is possible.
• Dead time change determined from the difference between the first and the second overvoltage value.
• the Totzeit Sung influenced on the one hand the number of passes of the second to fifth steps that are required to bring a dead time in the vicinity of an optimal value ⁇ Tot. For a fast adaptation of the dead time value, therefore, a large dead time change is advantageous.
• the dead time change affects the width of the interval in which, under steady state conditions, the dead time value determined by the method oscillates around such an optimal dead time value.
• the dead time change may be determined from the product of the difference between the first and second overvoltage values with a predetermined positive factor. Far from the optimal dead time value sought, a change in the deadtime values results in a large change in the generated
• Dead time change step size a gain of at least one and a control deviation of the measurement voltage are formed, wherein the control deviation from the difference of the measured second overvoltage value and the predetermined setpoint value of the measurement voltage is formed. It is also possible to increase this error with an exponent of at least one. In an advantageous manner, the result is that a comparatively large dead time change is determined with comparatively large control deviations, while with comparatively small control deviations the dead time is changed only comparatively little.
• the load current consumed by the load changes over time.
• Such a change in the load current generally causes a control deviation of the measurement voltage.
• an adjustment of the dead time is necessary in order to limit undesirable over-voltage to avoid or ⁇ ver. Be gain factor and / or Exponent too small, the control deviation can not be compensated fast enough.
• the amplification factor and / or the exponent are chosen too large, it is possible to override the measurement voltage by changing the dead time too much.
• An override of the measuring voltage is also favored by a high capacitive impedance component of the consumer, which causes a temporal offset of the change in the measured voltage with respect to the change in the dead time.
• the gain factor and the exponent in the described embodiment of the method are adapted to the typical switching behavior of a connected consumer, in particular to the typical speed and the typical amplitude of a change in the recorded load current, and to the capacitive impedance component of the connected consumer.
• the adaptation is carried out in such a way that a gain factor and an exponent are determined for a specific load, which in the case of typical changes in the recorded load current does not yet cause an override of the measuring voltage, and thus of the supply voltage.
• the second overvoltage value is determined as the maximum value of the measuring voltage over a complete switching cycle of the switching regulator, wherein such a switching cycle is determined by the time between the beginning of a first closing of the first
• the third and fourth steps of the method are performed when the second overvoltage value is greater than a predetermined overvoltage limit. If, in a subsequent run of the method, the second overvoltage value is less than or equal to the predetermined one
• a modified fourth step is performed.
• the dead time in the correcting direction by a certain step number by a predetermined multiple of the Totzeit Sungs Colourweite is hereby amended ⁇ changed.
• a change in the dead time to the desired fall below the surge limit ge ⁇ leads, then in a subsequent pass of the method, the dead time is again changed in the same correcting direction by a predetermined multiple of the Totzeit Sungsuzeweite which the product of the Totzeit Sungs- increment with a step number.
• the third and fourth steps are omitted when the second overvoltage value is less than or equal to the predetermined overvoltage threshold. In other words, the dead time remains unchanged until an overrun of the overvoltage limit is detected again.
• the inventive device for determining and adjusting, in particular control or control of dead time comprises a measuring unit for measuring the measuring voltage of the switching power supply, a processing unit for calculating a dead time and a control unit for driving the first and second switching element in the switching regulator of the switching power supply.
• the measuring unit is connected to the processing unit and measures the measuring voltage across the second switching element. From this voltage measurement, the processing unit determines a change in the erfor ⁇ derliche Totzeitwerts by the inventive process.
• the processing unit is connected to the control unit and designed so that a control signal can be transmitted to the control unit via a connection, from which a required change in the dead time can be derived.
• the control unit is connected to the first and the second switching ⁇ element.
• the control unit sets HeidelbergZeitis for switching the first and the second switching element so that there is a dead time between the opening of the first switching ⁇ elements and the closing of the second switching element, which advantageously with the inventive device minimizing or at least limiting a Overvoltage at the measuring output of the switching power supply achieved.
• control unit is designed to drive MOSFETs.
• control unit is connected via electrical connections with switching elements designed as MOSFETs.
• FIG. 1 shows schematically the circuit structure of a switching power supply with an adaptation, for. As regulation, the dead time
• Figure 2 shows schematically the course of an overvoltage, caused by a too large dead time
• FIG. 3 schematically shows the course of an overvoltage, caused by too small a dead time
• Figure 5 shows schematically the course of an overvoltage at a
• FIG. 6 schematically shows a detailed view of the course of a
• FIG. 1 shows by way of example and schematically the circuit configuration of a switching power supply 1 with a measuring unit 2, a Ver ⁇ processing unit 3 and a controller 4.
• the input of the switching power supply 1 is formed by two input contacts 1.1, 1.2, which are powered by a DC input voltage U_IN.
• the measuring output of the switched-mode power supply 1 is formed by two measuring output contacts 1.3, 1.4, between which a measuring voltage U_out drops.
• the measuring voltage U_out should assume a desired setpoint U_soll, which lies below the input direct voltage U_in.
• a first switching element 1.5.1 and a second switching element 1.5.2 are designed as MOSFETs and connected in series.
• the measuring output contacts 1.3, 1.4 are arranged parallel to the second switching element 1.5.2. Furthermore, between the measuring output contacts 1.3, 1.4, and thus parallel to the second switching element 1.5.2, an inductance L and a capacitance C, which when closing the first switching element is loaded from the input DC voltage source U_ein on ⁇ , connected in series. Parallel with the capacitance C a consumer or load resistance X_L is supplied with the supply voltage ⁇ , which is discharged via the capacity C.
• the switching elements 1.5.1, 1.5.2 are periodically opened and closed by the control unit 4 in such a way that a dead time t_tot elapses between the opening of the first switching element 1.5.1 and the closing of the second switching element 1.5.2, while the two switching elements 1.5 .1, 1.5.2 are open.
• the measurement unit 2 is at the measurement output 1.3, 1.4 of the switching power supply 1 connected ⁇ and connected to the processing unit.
• the processing unit 3 is connected to the Steuerein ⁇ uniform. 4
• the control unit 4 controls the opening and closing of the switching elements 1.5.1, 1.5.2.
• the switching elements 1.5.1, 1.5.2 and the connections of the switching regulator 1.5 are electrically characterized by an ohmic resistance, a parasitic inductance and a parasitic capacitance.
• the parasitic inductances cause About ⁇ vibrate the measurement voltage U_OUT as t_schalt in Figure 2 for a switching time along the time axis t is illustrated within the switching regulator 1.5.
• t_mess 1.4 of the switching power supply 1 is effected by inducing vibration of the measuring voltage U_OUT, and thus exceeding the target value of the measurement voltage by the overvoltage U_Soll U_ueb the measuring ⁇ output 1.3.
• the setpoint value of the measuring voltage U_soll is set only after the oscillation has gradually decayed from the overvoltage U_ueb as the stationary value of the measuring voltage U_out. , n
• Figure 4 shows the flow chart for the inventive method by which minimizes the overvoltage U_ueb or at least re ⁇ is symbolized. The procedure starts at a starting point SO.
• the dead time will t_tot with a value t_tot_start, a first voltage value over ⁇ U_uebl with a surge start value ⁇ U_ueb_start and a compensation direction d with
• t_tot t_tot_start
• the method waits for the switching between the first switching element 1.5.1 and the second switching element 1.5.2, thus for a time or for a period of time at which or during which the first switching element 1.5.1 already open is and the second switching element 1.5.2 is not yet closed.
• the current value of the measuring voltage U_out is measured, and from this a second overvoltage value U_ueb2 is determined. For example, it is possible to determine a specific time from the control signals generated by the control unit 4 for the first switching element 1.5.1 and the second switching element 1.5.2. The second overvoltage value U_ueb2 can then be measured, for example, as the value of the measurement voltage U_out at this time.
• a subsequent first decision step El it is checked whether the second overvoltage value U_ueb2 is greater than or equal to the first overvoltage value U_uebl.
• the correction direction d is maintained and the fourth step S4 is executed immediately after the first decision step El along a negative drain path N.
• the dead time is t_tot in the corrective ⁇ turcardi a Totzeit Sung d_t_tot changed, expressed as the formula:
• t tot t tot + d * dt dead.
• the second overvoltage value U_ueb2 is assigned to the first overvoltage value U_uebl, expressed as a formula:
• a dead time t_tot is set by the described method, which leads to a minimum or approximately ⁇ approximately minimal second overvoltage value U_ueb2.
• the dead time t_tot oscillates around an optimum which is associated with a minimum overvoltage, ie with a minimum overshoot of the measuring voltage U_out, which sets the reference value of the Measuring voltage U_soll does not exceed, as shown in Figure 5.
• the measuring voltage U_out gradually adjusts to the setpoint value U setpoint and reaches it in steady-state steady state.
• FIG. 6 schematically illustrates the course of the overvoltage U_ueb and the course of the setpoint U_setpoint of the measuring voltage U_out, which sets in the stationary state, as a function of the set dead time t_tot. It can be clearly seen that a certain optimum value t_tot * of the dead time exists, in which the overvoltage U_ueb becomes minimal. It can also be clearly seen that the overvoltage U_ueb for this optimum value of the dead time t_tot * is below the setpoint U setpoint.
• FIG. 7 shows the flow chart for an embodiment of the method according to the invention, with which the overvoltage U_ueb is limited.
• the procedure starts at a starting point SO.
• the sequence of the first step S1 corresponds to the sequence shown in FIG.
• Switching cycle determined and the second overvoltage value ⁇ assigned wherein such a switching cycle is determined by the time between the beginning of a first closing of the first switching element and the beginning of a subsequent second closing of the first switching element.
• step E2 it is checked whether the determined in step S2 second surge ⁇ U_ueb2 voltage value less than or equal to a threshold-voltage is U_ueb_grenz. If the second overvoltage value U_ueb2 determined in the modified second step S2 'is less than or equal to the overvoltage limit value U_ueb_grenz, the fifth step S5 is processed along the positive sequence path J as the next step.
• the sequence of the first decision step El, optionally of the third step S3 and of the fourth step S4 is selected along the negative drain path, as already described in FIG :
• the fourth step S4 is executed. If the first overvoltage value U_uebl is greater than the second overvoltage value U_ueb2, the correction direction d is maintained and the fourth step S4 is executed immediately after the first decision step El along the negative drain path N.
• the dead time is t_tot in the corrective ⁇ d turoplasty a Totzeit Sungsuzeweite d_t_tot changed, expressed as the formula:
• t_tot t_tot + d * d_t_tot.
• this embodiment of the invention it is possible to carry out a comparatively large change in the dead time t_tot in the case of a large control deviation, and to carry out a comparatively smaller change in the dead time t_tot with a smaller control deviation.
• an approximately optimal dead time t_tot be set than in a method with a fixed step size, which remains constant regardless of the deviation of the last measured second overvoltage value U_ueb2 from the setpoint of the measurement voltage U_soll ,
• Concrete values for the amplification factor K and the exponent x are advantageously selected as a function of the impedance and the switching behavior of the connected load X_L. Comparatively large values for the gain factor K be ⁇ act a faster change of the dead time t tot and thus a faster reduction of the control deviation than comparatively low values for the amplification factor K. However, an overshoot of the measuring voltage U_out can be caused if the amplification factor K exceeds a certain limit value.
• a gain K in the range of about 1 to about 10 is chosen.
• the nonlinearity of the regulation of the measuring voltage U_off can be controlled.
• exponent x above 1 via a proportional change in the dead time ⁇ t_tot is effected with large control deviations.
• Verrin ⁇ delay the deviation is achieved in an advantageous manner as with an exponent x of 1.
• an overshoot of the measurement voltage U_OUT can be effected if the exponent x exceeds a certain limit.
• an exponent x in the range of about 1 to about 5 is chosen.
• the amplification factor K and the exponent x can initially be increased until an overshoot of the measurement voltage U_out is observed. Thereafter, the values thus found to be reduced by a predetermined amount in order to achieve a safe operation of the process without any overshoot of the measurement voltage U from ⁇ .
• the second surge voltage value ⁇ U_ueb2 is assigned to the first overvoltage value U_uebl, expressed as the formula:
• U uebl: U ueb2.
• the process is continued with any number of repetitions of the process from the second to the fifth step S2 to S5.
• a dead time t_tot such that an overvoltage limit U_ueb_grenz is not substantially exceeded.
• the dead time is ⁇ t_tot in the compensation direction d changed so that a decrease in measured second overvoltage value U_ueb2 occurs.
• the change in the dead time t_tot is set as soon as the overvoltage limit value U_ueb_grenz has been reached or fallen below and only resumed when the
• Overvoltage limit U_ueb_grenz is exceeded again.
• This embodiment of the method can thus be implemented with a lower expenditure on components such as comparators.
• FIG. 8 shows the flow chart for a further embodiment of the method in which the overvoltage U_ueb is limited.
• the procedure starts at a starting point SO.
• the first step Sl, the modified second step S2 'and the second decision-making step ⁇ E2 are run through in the same way as described by Figure 7 embodiment of the method. If the second overvoltage value U_ueb_limit determined in the modified second step S2 'is greater than the overvoltage limit value U_ueb_grenz, an iteration number Z is set to 0 along the negative flow path N in a subsequent sixth step S6, expressed as a formula:
• the iteration number Z describes how often the method has been run since the last time the predetermined overvoltage limit value U_ueb_grenz was exceeded. Subsequent to the sixth step S6, the flow of the first decision step El, optionally of the third
• the first decision step El is checked whether the second overvoltage value U_ueb2 is less than or equal to the first
• the correction direction d is maintained and the fourth step S4 is executed immediately after the first decision step El along the negative drain path N.
• the dead time is t_tot in the corrective ⁇ d turraum the Totzeit Sungs Colourweite d_t_tot changed, expressed as the formula:
• t_tot t_tot + d * d_t_tot.
• the fifth step S5 is executed as already described for FIG. 4, and subsequently the modified second step S2 'is continued.
• step S7 it is checked in a third decision step E3 whether the iteration number Z is greater than 1. If the iteration number Z is greater than 1, the fifth step S5 is processed along a positive flow path J as the next step, as already described for FIG. 4, and subsequently with the modified second one
• Step S2 continued.
• a modified fourth step S4 ' is processed along a negative flow path N as the next step.
• the dead time t_tot in the correction direction d is changed by the dead time change step size d_t_tot multiplied by a predetermined number of steps n, expressed as a formula:
• t_tot d * n * d_t_tot.
• a change in the dead time t_tot by a predetermined amount n * d_t_tot in the same direction is again carried out in the case of a passage following a change in the dead time t_tot in the fourth step S4.
• the fifth step S5 is executed as already described for FIG. 4 and subsequently with the modified second one
• Step S2 continued.
• Step S5 processed as already described for Figure 4 and subsequently proceeded ⁇ with the modified second step S2 '.
• the embodiment of the method illustrated in FIG. 8 permits a particularly rapid and stable reduction of a control deviation during a load change without continuous measurement of the measuring voltage U_out, if the switching behavior of a supplied consumer X_L can be determined in advance.
• particularly simple and stable switching power supplies can be developed, which by adjusting the gain K and / or the exponent x and / or the step number n easy for the supply of consumers X_L with different, but well-known

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• 2014
  • 2014-08-20 DE DE102014216551.2A patent/DE102014216551B4/de active Active
• 2015
  • 2015-06-10 US US15/504,346 patent/US10205382B2/en active Active
  • 2015-06-10 WO PCT/EP2015/062962 patent/WO2016026594A1/de active Application Filing
  • 2015-06-10 EP EP15728507.3A patent/EP3183806A1/de not_active Withdrawn
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