EP2777140A2 - Circuit de conversion de tension continue avec limitation de courant - Google Patents

Circuit de conversion de tension continue avec limitation de courant

Info

Publication number
EP2777140A2
EP2777140A2 EP12779022.8A EP12779022A EP2777140A2 EP 2777140 A2 EP2777140 A2 EP 2777140A2 EP 12779022 A EP12779022 A EP 12779022A EP 2777140 A2 EP2777140 A2 EP 2777140A2
Authority
EP
European Patent Office
Prior art keywords
signal
circuit
sum
correction
switching signal
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP12779022.8A
Other languages
German (de)
English (en)
Inventor
Manfred Lueger
Peter BLIEM
Christian Halper
Thomas Jessenig
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Ams Osram AG
Original Assignee
Ams AG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Ams AG filed Critical Ams AG
Publication of EP2777140A2 publication Critical patent/EP2777140A2/fr
Withdrawn legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0016—Control circuits providing compensation of output voltage deviations using feedforward of disturbance parameters
    • H02M1/0019—Control circuits providing compensation of output voltage deviations using feedforward of disturbance parameters the disturbance parameters being load current fluctuations
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1588—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load comprising at least one synchronous rectifier element

Definitions

  • the invention relates to a circuit for DC voltage conversion with current limitation, in which a level of a coil current of a DC-DC converter is limited.
  • a DC-DC converter converts the level of an input voltage into a higher or a lower level of an output voltage, depending on whether the DC-DC converter is implemented as a step-down or step-up converter.
  • a DC-DC converter has, for example, a coil which is connected to a controllable switch.
  • the controllable switch can be switched by activation with a switching signal in the conductive or blocking state, whereby a current through the coil is switched on or off.
  • the current limitation is activated, for example, if an excessive load on the DC-DC converter draws too much current or, for example if in one application, the circuit ei ⁇ ne output load transient takes too much power.
  • the current coil current can be measured with a simple control and compared with a threshold value. Depending on the comparison, the controllable switch is then switched on or off for the coil current.
  • a slope compensation circuit can be provided in the control. The edge compensation circuit is to ensure stable operation when the coil current is limited.
  • the edge compensation within the simple control has the consequence that the level of the coil current, at which the control circuit limits the coil current, is dependent on the ratio of the respective duration of the switch-on and switch-off (duty cycle) of the switching signal.
  • the level of the peak current at which current limiting is applied is not constant with ⁇ , but may be indirectly proportional to the length of the input and off cycling with which the controllable switch between the mitochondriahmigeren and the higher resistance state is switched.
  • a current limiting DC-DC circuit includes a DC-DC converter having a coil and a controllable switch switchable to a first and second state, wherein the controllable switch in the second state is higher-impedance than in the first state, a switching signal generating circuit for generating a switching signal for switching the controllable switch and a current limiter for generating a control ersignals for controlling the switching signal generating circuit.
  • the switching signal generating circuit is configured to generate a periodic sequence of the switching signal in dependence on the level of the control signal, which switches the controllable switch into the first and second state during a period of the switching signal, or to generate the switching signal such that the controllable switch during the period of the switching signal in the second state is switched ge ⁇ .
  • the current limiter further comprises a signal ⁇ generator circuit for generating a periodic signal and a correction circuit for generating a correction signal.
  • the current limiter is a measurement signal, the level of which depends on the size of the current through the coil, to ⁇ feasible.
  • the current limiter is designed to determine a sum of a level of the periodic signal and a level of the measurement signal.
  • the correction circuit generates the correction signal in response to the periodic signal or the switching signal.
  • the current limiter generates the control signal in dependence on the correction signal and the sum.
  • the switching signal generating circuit may be formed, for example, as a pulse width modulator.
  • the switching signal generated by the pulse width modulator is in this Ausges ⁇ taltungsform example, a pulse width modulated signal.
  • the DC-DC converter In response to the output signal, such as an output voltage, the DC-DC converter generates the
  • the switching signal as a periodic sequence of rectangular signals with under defenceli ⁇ chen ratios of a high level to a low level period of a period, so that the DC-DC converter generates a constant output voltage.
  • the switching signal generating circuit can, for example, have a signal generator circuit for generating a ramp-shaped periodic signal, for example a periodic sawtooth-shaped signal. For example, if the level of the ramp-shaped periodic signal is above a
  • Threshold is, the switching signal changes its state, so that the controllable switch of the DC-DC converter is controlled by a low-impedance to a high-impedance state.
  • a measurement signal which is dependent on a value of the coil current, are fed back to the switching signal generating circuit.
  • the current limiter is designed to limit the coil current to a predetermined value.
  • the actual coil current of the DC converter can ⁇ limiter is compared with a threshold value of the coil current in the electricity.
  • the coil current is measured and the measurement signal is he witnesses ⁇ a function of the coil current, the level of which depends on the measured coil current.
  • the measuring signal is supplied to the current limiter.
  • a level of the control signal generated by the current limiter is generated such that the switching signal generating circuit generates a periodic sequence of the switching signal, wherein the controllable switch is switched within ⁇ within a period between the first and second state.
  • the duty cycle of the switching signal is from the switching signal generating circuit is set in response to the output voltage and the coil current of the DC-DC converter.
  • the current limiter has an edge compensation circuit.
  • the edge compensation circuit may comprise, for example, the signal generator circuit and a summation circuit.
  • the signal generator circuit generates a periodic signal having a rising and falling edge within a period.
  • the edge of the perio ⁇ sized signal may be linear, quadratic or exponential increasing or linear, quadratic or exponential decreasing.
  • the signal generator may generate ramped signals, in particular sawtooth-shaped signals.
  • the periodic signal of the edge compensation ⁇ circuit for example, correspond to the periodic signal of the switching signal generating circuit.
  • the summing circuit of the edge compensation circuit determines a sum of the periodic signal and the measured ⁇ signal and generates a sum signal in dependence on the sum determined.
  • the sum signal can be compared with a reference value representing a threshold value of the coil current.
  • the control signal is generated by the current limiter at a level which causes the switching signal generating circuit to generate the switching signal at a level such that the controllable switch is switched to the second state at least during a period duration of the switching signal that the coil current is limited.
  • the periodic signal of the edge compensating circuit corresponds to the periodic signal of the switching signal generating circuit, the control results that, as the ratio of the on-time to the off-time of the switching increases
  • the Steuersig ⁇ nal is generated for controlling the switching signal generating circuit even at ever-smaller levels of the actual coil current having a level which interrupts the generation of the periodic sequence of the switching signal and instead the controllable switch for at least one entire period of the switching signal high impedance controls.
  • the current limitation thus begins as the level of the coil current decreases.
  • the current limiter on the correction circuit.
  • the correction circuit may play testify ER- a level of the correction signal in response to the switching signal, wherein ⁇ a function of the mean value, to the level of the switching signal aufeist over several periods.
  • the correction circuit may alternatively generate the correction signal in response to a sample of the periodic signal of the edge compensation circuit.
  • the current limiter generates the control signal for controlling the switching signal generating circuit in response to the sum of the periodic signal and the measurement signal, a pre- ⁇ passed reference signal whose level can indicate a threshold value of the coil current, and the correction signal.
  • the current limiter If the actual coil current is below a threshold value of the coil current, the current limiter generates the Steuersig ⁇ nal having a first level.
  • the first level causes the switching signal generating circuit to generate the periodic sequence of the switching signal so that the controllable switch of the DC-DC converter is turned off and on for at least one period of the switching signal.
  • the current limiter In the case of a boost converter is in the off state relationship ⁇ high-impedance state of the controllable switch, the coil to the reference voltage terminal of the DC-DC converter connected in high impedance. In the switched-on or in the low-impedance state of the controllable switch, the coil is connected to the reference voltage terminal low resistance.
  • the current limiter If, however, the actual coil current is above the threshold, the current limiter generates the second level control signal.
  • the second level of the control signal be ⁇ acts that the switching signal generating circuit generates the switching signal during the period of the switching signal with a state that switches the controllable switch of the DC
  • Circuit has less required test complexity when testing its function. In particular, it is not necessary to test the current limit for a specific duty cycle.
  • Figure 2 shows another embodiment of a circuit for
  • Figure 3 shows an embodiment of a correction circuit for generating a correction signal in response to a switching signal
  • Figure 4 shows an embodiment of a correction circuit for
  • Figure 5 shows a further embodiment of a correction scarf ⁇ processing for evaluating a signal generated by a pass compensation circuit periodic input signal of an edge compensation circuit
  • Figure 6 shows an embodiment of a buck converter.
  • FIGS. 1 and 2 show various embodiments of current-limiting DC-DC switching circuits each having a DC-DC converter 100, a switching signal generating circuit 200, and a current limiter 300. The two embodiments differ in the configuration of the current limiter circuit 300.
  • the DC-DC converter 100 can be used as an up-down converter relate hung example be carried out, which an output voltage he ⁇ evidence when an input voltage U j to an input terminal to an output terminal E100 A100.
  • the DC-DC converter 100 of the embodiment 1 and 2 for example, a current path 101 that is maral ⁇ tet between an input terminal E100 for applying a DC voltage and a reference voltage terminal M for applying a Be ⁇ karsschreib, for example, a ground potential comprise.
  • a coil 110th and a controllable switch 120 connected in series between the terminal for applying the input voltage U j and the reference voltage terminal M.
  • the controllable switch 120 may be formed, for example, as a transistor.
  • the controllable switch may be connected in a first, living relationship ⁇ conductive, and in a second, high-impedance Geren state in which opens the controllable switch Bezie ⁇ hung as is controlled locked.
  • the controllable switch 120 connects the coil 110 to the reference voltage terminal M in the first state at a lower level than in the second state.
  • a control terminal S100 of the DC-DC converter for applying a switching signal PWM to switch the controllable switch 120 in the first and second state is connected via ei ⁇ NEN driver 130 to a control terminal of the controllable switch 120th
  • DC voltage converter is connected via a switched Transis ⁇ tor or a diode 140 to the signal path 101.
  • the diode is connected between the coil 110 and the controllable switch 120. Between the diode 140 and the output ⁇ port A100, a capacitor 150 is connected to ground.
  • the DC-DC converter circuit 100 is configured as an up-converter.
  • the current-limiting DC-DC switching circuit shown in Figs. 1 and 2 is not limited to an up-converter.
  • the DC-DC converter circuit 100 may also, for example be implemented as a buck converter. A possible embodiment of a buck converter is shown in FIG.
  • the switching signal generating circuit 200 For generating the switching signal PWM for controlling the controllable switch 120 in the conducting and blocking states, the switching signal generating circuit 200 is provided in embodiments 1 and 2 of the current-limiting DC-DC switching circuit.
  • the switching signal generation circuit 200 comprises a signal generator 210 for generating a periodic signal I R.
  • the signal generator 210 is coupled to a summing circuit 220, whereby the periodic signal of the summation circuit 220 can be supplied on the input side. Furthermore, the summation circuit 220 on the input side, a measurement signal IsENSE 'whose level is dependent on a current 1 ⁇ through the coil 110, respectively.
  • the current through the coil which flows to the reference voltage connection, can be tapped directly on the coil itself or out of the current path 101.
  • the summation circuit 220 On the output side, the summation circuit 220 generates a summing signal IgO ', which indicates the sum of the periodic signal IR and the measurement signal IsE SE.
  • the switching signal generating circuit 200 includes a comparator circuit 250 which compares the output voltage generated by the DC-DC converter 100 with a reference voltage URE F. Depending on the comparison, the comparator circuit 250 generates a comparison ⁇ signal Ip on the output side. Furthermore, the switching signal generation Circuit 200, a comparator circuit 230 which compares the sum signal ⁇ so m with the comparison signal Ip. The comparator circuit 230 is coupled to the input side to an output of the comparator circuit 250 and to the signal generator 210. The comparator 230 generates in response to the comparison of the sum signal Igg w ith the comparison signal Ip output side the switching signal PWM.
  • the switching signal generating circuit 200 further includes a logic circuit 240 connected to an output side of the comparator circuit 230 at an input side and to the current limiter circuit 300 at another input side.
  • the logic circuit may include a flip-flop circuit. On the input side, the logic circuit is supplied with the switching signal PWM and a control signal I QC generated by the current limiter.
  • the logic circuit evaluates the state of the control signal I QC AU S and generates the switching signal PWM for controlling the controllable switch 120 of the DC-DC converter in response to the state of the control signal I QC at an output terminal A200 of the switching signal generating circuit 200.
  • the control signal I QC When the control signal I QC, for example, has a first state, generates the switching signal generating circuit 200 during a period of a periodic sequence of the switching signal PWM, wherein the controllable switch 120 is switched during a Perio ⁇ dendauer of the switching signal PWM in the first and second state. If the control signal I QC, for example ⁇ has the second state, the switching signal generating circuit generates the switching signal PWM during the period of the switching signal such that the controllable Schal ⁇ ter is switched to the time state during the entire period of the switching signal.
  • the switching signal generating circuit 200 for generating the switching signal PWM may be formed as a pulse width modulator. In this case, the switching signal PWM is a pulse width modulated signal.
  • the Siemenssig ⁇ nal PWM may be a square wave signal having a high and low pulse in a period of the switching signal.
  • the comparison signal Ip from the comparator 230 to the summation signal I 50 is compared.
  • the switching signal generating circuit 200 generates, for example, a high-pulse when the level of Ver ⁇ equal signal Ip is above the level of the summation signal I 50 and in the opposite case, the low-pulse.
  • the DC-DC converter 100 is designed to convert the level of the input voltage Up into the changed level of the output voltage UA ZU.
  • the level of the output voltage may be above or below the level of the input voltage Up, depending on whether the DC-DC converter is configured as an up or down converter.
  • controllable switch 120 Controlling the controllable switch 120, the coil 110 is never ⁇ or high-impedance connected to the reference voltage terminal M.
  • the controllable switch 120 may be configured such that a high-pulse causes a conductive and a low-pulse control of the controllable switch in the locked state.
  • the current limiter 300a has an edge compensation circuit 310a.
  • the edge compensation circuit 310a prevents the occurrence of subharmonic oscillations of the duty cycle of the switching signal PWM.
  • the edge compensation circuit 310a includes a signal generator circuit 311 for generating a periodic signal --SLOPE au f D it comprises further a cross ⁇ compensation circuit 310a, a summation formwork 312a.
  • the summing circuit 312a is coupled on the input side to the signal generator circuit 311 and the DC-DC converter 100.
  • the summation circuit 312a is the input side, the periodic see input signal IsLOPE and the measurement signal IsE SE feed ⁇ bar.
  • the summation circuit 312a forms a sum of the periodic input signal IsLOPE and the measurement signal IsE SE and generates on the output side as a function of the sum a sum signal Ig1.
  • the current limiter circuit 300a further comprises a correction circuit 320 for evaluating the switching signal PWM.
  • the correction circuit 320 on the input side, the switching signal ⁇ PWM fed. On the output side, the correction circuit 320 generates a correction signal I LO
  • the current limiting circuit 300a includes a summation ⁇ circuit 330, which is connected to the correction circuit 320, and a connection for applying a reference signal ⁇ LS.
  • the correction signal ⁇ LQ and the reference signal ⁇ LS can be fed to the summation circuit 330 on the input side.
  • the reference signal may indicate a threshold value of the coil current at which a current limitation is to take place.
  • the summation Circuit 330 forms a sum of the level of the reference signal ⁇ LS and the level of the correction signal ⁇ LQ and generates on the output side in dependence on the summation a summation signal Ig2 *
  • the current limiter circuit 300a further comprises a comparator circuit 340 for generating the control signal Ioc.
  • the comparator circuit 340 is connected on the input side to the summing circuit 312a and the summation circuit 330, so that the comparator circuit 340 can be supplied with the sum signal and the sum signal I52.
  • the comparator circuit 340 is designed to compare the sum signal with the sum signal I52 and to generate a level of the control signal IQC as a function of the comparison.
  • the comparator circuit can be designed to convert the control signal IQC, for example, as a digital signal having a "0 to generate "or" 1 "level.
  • Figure 2 shows an embodiment 2 of the circuit for
  • the DC-DC converter 100 and the switching signal generating circuit 200 are configured as in the embodiment 1 indicated in FIG.
  • the current limiter 300b includes an edge compensation circuit 310b having a signal generator circuit 311 and a summation circuit 312b.
  • the summation circuit 312b is connected to the signal generator circuit 311, the correction circuit 320 and the DC-DC converter 100.
  • Signal generator circuit 311 generates a periodic signal IgLOPE ' ⁇ as ⁇ he 312b summing circuit to a first input side a ⁇ is supplied.
  • the measurement signal SE supplied IsE ⁇ is supplied at a second entrance side.
  • the Summati ⁇ onsscrien 312b is the correction signal ⁇ LQ with a negative sign before ⁇ supplied.
  • the summation circuit 312b is configured to form a sum of a level of the measurement signal IsE SE and a level of the periodic signal IsLOPE and subtract a level of the correction signal ⁇ LQ ZU from it.
  • the summation circuit 312b generates the sum signal I ' sl on the output side.
  • the current limiter 300b further comprises akillerschal ⁇ tung 340 the sum signal and a reference signal I'sl ILS 'indicative of a threshold value of the coil current is fed to the input side.
  • the comparator 340 is connected to the input side of the summation circuit 312b and a connection for applying the reference signal ILS.
  • the comparator 340 generates the output side after comparing the level of the sum signal I'sl m it the level of the reference signal ILS the control signal Ioc- er level of Steu ⁇ ersignals I QC is the comparison of the level of Summensig ⁇ nals I'sl m it the level of the reference signal.
  • the control signal can be generated with a "0" or "1" level.
  • the signal generating circuit 210 may generate the periodic signal IR having edges between the individual periods.
  • the signal generator circuits 311a, 311b of the edge compensation circuits 310a, 310b may receive the periodic signal IsLOPE periodic signal with increasing time. generate falling or falling edges between successive periods.
  • the signal generator circuits 210 and 311a, 311b may generate, for example, a periodic signal with a sawtooth waveform, a periodic signal with an exponential waveform or a periodic signal with a quadratic waveform between successive periods, the level of the signal from period to period repeating from a level other than a "0" level drops to the "0" level or rises.
  • the current limiter generates the control signal I QC with a first state that causes the switching signal generation circuit 200 to generate a periodic sequence of a first and second state, for example, a high and low level state, of the switching signal PWM that the controllable switch 120 during a period of the
  • Switching signal is switched from the low-resistance or conductive in the high-resistance or blocking state when the level of the coil current ⁇ L is below a predefined threshold ⁇ L S.
  • the coil 110 is alternately low and high impedance connected to the reference voltage terminal M during a period of the switching signal.
  • control signal I QC may be from the
  • Current limiter 300 are output with a second state, which causes the switching signal generating circuit 200 generates the switching signal PWM during the entire period of the switching signal with the second state, so that the controllable switch 120 over the entire period of the switching signal or over several periods of the switching signal is locked.
  • the coil of the DC-DC converter is of the reference voltage connection. disconnects or connected to the reference voltage connection high-impedance. As a result, the coil current 1 ⁇ no longer increases, but is limited to a value.
  • the correction circuit 320 causes the current limiters 300a, 300b to generate the control signal I QC almost independently of the magnitude of the duty cycle of the switching signal PWM.
  • Switch-on / off-time ratio of the switching signal PWM ent ⁇ speaks, to the fact that the periodic signal IsLOPE 'example ⁇ , the amplitude of a sawtooth signal, has already risen far before a change of state takes place at the switching signal PWM.
  • the comparator circuit 340 only compared the sum of the periodic input signal IsLOPE and the measurement signal IsE SE with a constant level of a reference signal ⁇ LS, then with larger values of the duty cycle the control signal I QC would already be at relatively low levels of the measurement signal IsE SE unc ⁇ can thus be generated at low levels of the coil current ⁇ L with the second state switching the controllable switch 120 to the second state over several periods.
  • the high rise of the input signal IsLOPE can be compensated for a large duty cycle of the switching signal PWM.
  • the level of the coil current which is the triggering of the
  • FIG. 3 shows a first embodiment 320a of the correction circuit 320 of FIGS. 1 and 2.
  • the correction circuit has an input terminal E320a for applying the switching signal PWM and an output terminal A320a for outputting the correction signal ⁇ LQ.
  • the correction circuit 320a includes a low-pass filter 10 connected between the input and output terminals.
  • the low-pass filter 10 can be supplied with the switching signal applied to the input terminal E320a.
  • the low pass may include, for example, a resistor 11 and a capacitor 12, wherein the resistor 11 is connected between the input terminal and the output terminal and the capacitor is connected between the resistor and ground.
  • a buffer circuit 30 may be connected between the low-pass filter 10 and the output terminal A320a.
  • a buffer circuit 20 may be connected in front of the low-pass filter 10.
  • the correction circuit 320a shown in FIG. 3 is designed to determine an average value of the level of the switching signal PWM over a plurality of periods of the switching signal PWM and to provide this as a correction signal ⁇ LQ at the output terminal A320a.
  • FIG. 4 shows a further embodiment 320b of the correction circuit with an input terminal E320b for applying a periodic signal.
  • a ramp-shaped or sawtooth input voltage can be applied to the input terminal E320b.
  • the input terminal E320b may be connected to the signal generation circuit 311 for generating the periodic signal IsLOPE when the signal generation circuit 311 generates a periodic voltage.
  • the correction circuit 320b to an input terminal E320b 'for applying the switching signal PWM ⁇ .
  • the correction circuit At an output terminal A320b, the correction circuit generates the correction signal I LO ⁇ the correction
  • the circuit includes a low-pass filter 10 and a sampler 40 connected between the input terminal E320b and the output terminal A320b.
  • the low-pass filter 10 is arranged between the scanning unit 40 and the output terminal A320b.
  • the sampling unit 40 is connected between the low-pass filter 10 and the input terminal E320b.
  • the pickup 40 is adapted to sample the voltage applied to the input terminal E320b periodic input signal at specific time punk ⁇ th.
  • the sampling times are determined by the switching ⁇ signal PWM. For example, a sampling of the periodic signal waveform of the input signal can occur for each falling edge of the switching signal PWM.
  • the correction circuit 320c applies a periodic input signal in the form of a current to the input terminal E320c.
  • the input port may be connected E320C ⁇ example, with the signal generator circuit 311 for generating the periodic signal iSlope when the signal generating circuit 311 generates a periodic current.
  • the correction circuit 320c has a further input terminal E320c 'for applying the switching signal PWM.
  • the correction circuit further comprises an output terminal A320c for outputting the correction signal I LO
  • the correction circuit 320 includes the low-pass filter 10 and the sampling unit 40 connected between the input terminal E320c and the output connector A320c are switched. Furthermore, the correction circuit 320 c has a current / voltage converter 50 and a voltage / current converter 60.
  • the current / voltage converter 50 may be formed as a resistor connected between the input terminal E320c and the sampling unit 40.
  • the voltage / current converter 60 is connected between the low-pass filter 10 and the output terminal A320c.
  • the voltage / current converter comprises a controllable switch 61 and a Wi-resistor 62 connected between the output terminal and A320c ei ⁇ NEN reference voltage terminal M.
  • a control connection of the controllable switch 61 is connected to a Operati ⁇ onsverEntr 63rd
  • the non-inverting terminal of the operational amplifier 63 is connected to the low-pass filter 10.
  • the inverting terminal is connected between the steu ⁇ trollable switch 61 and the resistor 62nd
  • the output terminal A320c of the correction circuit 320c is connected to the controllable switch 61.
  • the periodic input signal IsLOPE may be sampled at sampling timings determined by the switching signal PWM.
  • the switching signal PWM can be game, a sequence of rectangular signals at ⁇ .
  • the exhaust sampling the periodic input signal iSlope can take place at ⁇ play, when the switching signal alternately a status, for example, has a transition from a high level to a low level.
  • the sampled input signal IgLOPE is then low-pass filtered.
  • the voltage / current converter 60 generates at the output terminal A320c the correction signal ⁇ L Q in the form of a current.
  • Figure 6 shows an embodiment of a DC wall ⁇ coupler 100, which is configured as a down converter, and generates an output voltage when an input voltage U j to an input terminal to an output terminal E100 A100.
  • the DC-DC converter 100 may comprise, for example, a current path 101, which is connected between the input terminal E100 for applying a DC voltage and a reference voltage terminal M for applying a reference voltage, for example a ground potential.
  • a controllable switch 120 is connected in series with a diode 140 between the terminal E100 for Anle ⁇ conditions of the input voltage U j and the reference voltage terminal M.
  • the diode 140 may also be formed as a transistor.
  • the controllable switch 120 may be formed beispielswei ⁇ se as a transistor.
  • the controllable scarf ⁇ ter can in a first Herohmigeren state in which the controllable switch is closed or conductive ge ⁇ is controlled, and be switched to a second, higher impedance state in which the controllable switch is controlled in open or closed.
  • a control terminal of S100 of the DC converter for turning on ⁇ place of the switching signal PWM for switching the controllable switch 120 in the first and second state is connected via ei ⁇ NEN driver 130 to a control terminal of the controllable switch 120th
  • the output terminal A100 of the DC-DC converter is connected to the signal path 101 via a coil 110.
  • Zvi ⁇ rule of the coil 110 and the output terminal A100 is connected a capacitor 150 to ground.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

Circuit de conversion de tension continue avec limitation de courant, comprenant un convertisseur de tension continue (100) pourvu d'une bobine (110) et d'un commutateur commandable (120) qui peut être commuté dans un état faiblement ohmique et un état fortement ohmique, et un limiteur de courant (300a, 300b) servant à produire un signal de commande (Ioc) pour commander l'état du commutateur commandable du convertisseur de tension continue (100). Le limiteur de courant (300a, 300b) est conçu de sorte que le courant (IL) traversant la bobine et subissant la limitation de courant est pratiquement indépendant du rapport des temps de mise en/hors circuit du commutateur commandable du convertisseur de tension continue (100).
EP12779022.8A 2011-11-07 2012-10-19 Circuit de conversion de tension continue avec limitation de courant Withdrawn EP2777140A2 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102011117814 2011-11-07
PCT/EP2012/070765 WO2013068226A2 (fr) 2011-11-07 2012-10-19 Circuit de conversion de tension continue avec limitation de courant

Publications (1)

Publication Number Publication Date
EP2777140A2 true EP2777140A2 (fr) 2014-09-17

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EP12779022.8A Withdrawn EP2777140A2 (fr) 2011-11-07 2012-10-19 Circuit de conversion de tension continue avec limitation de courant

Country Status (3)

Country Link
US (1) US9698679B2 (fr)
EP (1) EP2777140A2 (fr)
WO (1) WO2013068226A2 (fr)

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Publication number Priority date Publication date Assignee Title
TWI599870B (zh) * 2016-03-25 2017-09-21 威盛電子股份有限公司 操作系統及控制方法
CN109962607B (zh) * 2017-12-26 2020-10-02 维谛公司 一种限流控制调节方法和装置
FR3096152A1 (fr) * 2019-05-17 2020-11-20 STMicroelectronics (Grand Ouest) SAS DC-DC Converter with Steady State Current Limitation

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JP3351192B2 (ja) * 1995-07-12 2002-11-25 富士ゼロックス株式会社 画像読取信号処理装置
US7518348B1 (en) 2005-04-20 2009-04-14 National Semiconductor Corporation Adaptive error amplifier clamp circuit to improve transient response of DC/DC converter with current mode control
GB2437556B (en) 2006-04-26 2011-03-23 Wolfson Microelectronics Plc Improvements in switching regulator circuits
US8159204B2 (en) 2008-09-29 2012-04-17 Active-Semi, Inc. Regulating current output from a buck converter without external current sensing
US8138734B2 (en) 2009-04-06 2012-03-20 Monolithic Power Systems, Inc. Accurate current limit for peak current mode DC-DC converter
US8427123B2 (en) 2009-07-08 2013-04-23 Microchip Technology Incorporated System, method and apparatus to transition between pulse width modulation and pulse-frequency modulation in a switch mode power supply
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Also Published As

Publication number Publication date
WO2013068226A2 (fr) 2013-05-16
WO2013068226A3 (fr) 2014-03-20
US9698679B2 (en) 2017-07-04
US20140285174A1 (en) 2014-09-25

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