EP2462787A2 - Strahllagemonitor für elektronen-linearbeschleuniger - Google Patents
Strahllagemonitor für elektronen-linearbeschleunigerInfo
- Publication number
- EP2462787A2 EP2462787A2 EP10747017A EP10747017A EP2462787A2 EP 2462787 A2 EP2462787 A2 EP 2462787A2 EP 10747017 A EP10747017 A EP 10747017A EP 10747017 A EP10747017 A EP 10747017A EP 2462787 A2 EP2462787 A2 EP 2462787A2
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- European Patent Office
- Prior art keywords
- coupling
- frequency
- electron beam
- probes
- measuring device
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Classifications
-
- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05H—PLASMA TECHNIQUE; PRODUCTION OF ACCELERATED ELECTRICALLY-CHARGED PARTICLES OR OF NEUTRONS; PRODUCTION OR ACCELERATION OF NEUTRAL MOLECULAR OR ATOMIC BEAMS
- H05H7/00—Details of devices of the types covered by groups H05H9/00, H05H11/00, H05H13/00
- H05H7/22—Details of linear accelerators, e.g. drift tubes
Definitions
- This is understood to mean a robot arm, similar to that used in automobile production, only that the gripping hand is replaced by a special medical irradiation unit.
- the robot arm is movable about 6 axes and has a specified position accuracy of 0.2 mm.
- the movements of the patient during the irradiation, e.g. through breathing, are detected and compensated via cameras.
- 3-4 markers are mounted on the patient's chest, which send red light signals whose position is measured by the cameras.
- the so-called adiabatic displacements such as relaxation of the spine, cramping and pain are detected by two ceiling mounted X-ray machines and corrected by the positioning system of the robot.
- the healthy tissue that is irradiated in the beam path outside the point of intersection of the rays is not sustainably damaged by the single and therefore lower radiation dose.
- the advantages of this treatment method are manifold. Surgical intervention and anesthesia are not required. The treatment is carried out on an outpatient basis and the patient can resume his usual routine immediately after the treatment.
- the frequency of the RF acceleration field of electrons has become 2.988 GHz.
- the electron linear accelerator is operated in Cyberknife at a frequency of 9.3 GHz. This is an essential requirement for the mobility of the plant.
- the Cyberknife electron linear accelerator achieves a maximum acceleration energy of 6 MeV.
- only magnetrons can be used to generate the RF acceleration field.
- the electron beam at the exit of the accelerating tube must strike the photon target precisely. Deviations in the micrometer range already lead to particle loss or asymmetries in the applied dose profile. In this case, it can no longer be ensured that the patient is irradiated with the prescribed radiation dose and that the desired achieved success in therapy.
- Beam monitoring monitors The deposition of the electron beam from the ideal track is measured by means of so-called "beam monitoring monitors.” The determined deposit is then corrected by magnets or the irradiation is stopped, as with the Cyberknife, if a certain deviation is exceeded Beam condition monitors are examined, implemented and put into operation, whereby particular emphasis is placed on the selection of the technologies used in order to be able to produce industrially suitable systems later on.
- Fig. 1 shows the basic structure of an electron linear accelerator. Its main components are: electron beam source, high frequency source, accelerating tube, photon target.
- a classical electron beam source eg the electron gun, has a combination of thermal electron cathode and the beam optical elements, which allow a temporal and spatial bundling of the primary electrons.
- a circular waveguide is preferably used, and with the Eo 1 -.
- the HF source used is either a magnetron or a klystron, and after leaving the linac, the electrons strike a target of heavy metal, usually tungsten, with an energy of 6 to 23 MeV, which is the most common one for tumor irradiation
- a target of heavy metal usually tungsten
- the electromagnetic wave that accelerates the electron beam is usually generated or amplified by a magnetron or klystron with a transmission frequency of 2.998 GHz.
- the magnetron or klystron couples into a rectangular waveguide in Hio mode.
- the coupling from the rectangular waveguide into the Eoi mode of the round waveguide of the acceleration tube then takes place for reasons of adaptation via a slot, since the field configurations are the same at the coupling point.
- the extremely high RF power which is needed to accelerate the electrons to almost the speed of light, can only be provided by the magnetron or klystron in pulse mode for thermal reasons. Therefore, electron guns are in-phase fed into the accelerator tube by the electron gun.
- the bundles have a runtime of 5 ⁇ s and within this runtime individual pulses with a pulse duration of 30 ps and a repetition rate of 333 ps.
- the repetition rate corresponds to a frequency of 3 GHz. After that there is no signal for 5 to 20 ms. According to Fig. 2, the timing of the signals.
- the traveling wave and standing wave accelerators There are 2 types of electron linear accelerators: the traveling wave and standing wave accelerators.
- the traveling wave principle the electrons are accelerated at the correct phase infeed at the crest of the high-frequency wave.
- the speed of the electrons, which are just before the maximum of the wave, is thus continuously increased over the entire length of the acceleration tube.
- the electrons go along with the wave.
- standing wave accelerator the length of the acceleration tube is dimensioned so that at the end of the acceleration tube by reflection of the wave can form a standing wave in the pipe. Since the wave troughs would cause a negative acceleration of the electrons, the wave has experienced a phase shift, for example, by 180 degrees over the time course of the acceleration as soon as the accelerated electrons enter the respective next resonance chamber.
- the drift path tube of the electron beam between the resonators can be adapted to the needs of the beam optics and is an ideal place to measure the position of the electron beam via coupling probes and then to correct the filing via magnets along the accelerator tube.
- a method and a distance measuring device are specified, which makes it possible to measure the beam deposition of the electron beam in a drift tube of the electron linear accelerator.
- a frequency range is used which corresponds to a multiple of the frequency of the acceleration field in the resonance chamber.
- the functionality of the method has been demonstrated in the frequency range around 6 GHz.
- the evaluation of the frequency band around 5.98 GHz is referred to below as 6 GHz.
- This frequency corresponds to the 1st harmonic of the frequently used fundamental frequency of the acceleration field, which has a frequency of 2.99 GHz.
- the aim of the invention and the use of frequencies which correspond to a multiple of the fundamental frequency of the acceleration field is to achieve a higher accuracy in determining the position of the beam and thus to avoid spurious radiation that can destroy healthy tissue during radiotherapy.
- a Arrangement for decoupling the field of the electron beam and a reception concept for evaluating the beam deposition with high dynamics and sensitivity described.
- the beam position measurement within a drift tube has proven to be particularly advantageous, since there is exclusively the E-field of the electron beam and electromagnetic waves of the electron beam can be decoupled by a "ringing", depending on the size of the probe, which have pronounced frequencies which are multiples of Frequency of the alternating voltage which is coupled into the linear accelerator by a high-frequency generator for generating the acceleration field
- Analyzes of the field profile with CST Particle Studio have shown that in the drift tubes the electron beam has a field in the TEM mode
- the beam position is determined by 4 capacitive probes, each offset by 90 degrees, in the present case receiving concepts were investigated at 6 GHz and the results can also be transmitted to higher harmonics.
- a waveguide filter was developed with the help of CST Microwave Studio. This decouples the corresponding harmonic.
- the settling time should not be too high, so that the filter quickly finds itself in a stable state due to the high-energy pulses of the electron beam.
- a miniaturization of the waveguide filter can be achieved by introducing a dielectric.
- the concept with mixer and external logarithmic detector has proven to be advantageous.
- the mixed principle includes the evaluation of various higher harmonics, high frequency selectivity in the IF range, and the use of external housed detectors, which provide a wide range of detectors for different dynamic and frequency ranges, unlike the most ingene, RF-deployable detector chips.
- the distance between the external packaged detector and the VCO prevents sensitivity degradation due to crosstalk.
- the likewise analyzed diode detectors have the least hardware effort. This method fails because of the insensitivity and the reduced dynamics.
- the also analyzed sum and difference of the RF signal of two opposite channels has been found to be unsuitable for mass production due to their strong dependence on manufacturing tolerances of the acceleration tube.
- the signal processing concept of the DC voltages from the logarithmic detectors is based on an "oversampling" strategy in which the 5 ⁇ s pulse of the electron beam is 10 times oversampled and completely reconstructed in order to implement "state of the art” algorithms in a downstream digital signal evaluation can. Analyzes have shown that deposits of the electron beam from the ideal orbit with the mixing concept in the micrometer range can be measured if the component tolerances of the respective channels are measured and corrected in the digital signal processing.
- Figure 1 shows the basic structure of a linear accelerator, consisting of a high-frequency source, an electron beam source, an acceleration tube and a photon target.
- the electron beam is thereby accelerated by the E-field of the HF wave.
- FIG. 2 shows the time signal that is obtained during the decoupling of the electron beam carried by the electromagnetic field. This consists, for example, of single pulses which have a duration of 30 ps and a repetition time of 333 ps and are present within a pulse having a duration of 5 ⁇ s and a repetition time of 5 to 20 ms.
- Figure 3 shows the cross section of a standing wave resonator with outsourced coupling cavities for the RF acceleration field. Between the resonance chambers drift tubes are arranged, in which the electron beam reaches the next resonance spaces.
- Figure 4 shows a simulation design for the decoupling of an electron beam generated by a cathode and an anode. Two probe pairs with a probe diameter of 6 and 25 mm are simulated.
- Figure 5 shows the decoupled at the probe pair with 25 mm probe diameter time signals having slightly amplitude differences.
- FIG. 6 shows the frequency signals coupled to the probe pair with 25 mm probe diameter, which have slight amplitude differences, the largest amplitude difference being at 2.99 GHz and thus at a frequency which corresponds to the fundamental frequency of the acceleration field.
- FIG. 7 shows the time signals coupled out on the pair of probes with a diameter of 6 mm, which have amplitude differences which are more pronounced than with the probe pair with a probe diameter of 25 mm.
- FIG. 8 shows the frequency signals coupled to the pair of probes with a diameter of 6 mm which have amplitude differences which are more pronounced than those of the pair of probes with a probe diameter of 25 mm and where the largest amplitude difference is at 8.97 GHz and thus at one frequency. which corresponds to the 2nd harmonic of the fundamental frequency of the acceleration field.
- FIG. 9 shows a comparison of the time signals inside and outside a drift tube. Within the drift tube a "ringing" is recognizable, which requires a stronger characteristic of the 6 GHz component.
- FIG. 10 shows the signal difference of the 6 GHz component at the receiving probes when the electron beam position is varied. This results in signal differences even at slightly different distances to the electron beam.
- FIG. 11 shows a reception concept for RSSI measurement, comprising a waveguide filter with low attenuation in the heavy duty range, an LNA with specified noise figure and gain, an IF chain with specified bandwidth and an analog-to-digital converter with specified sampling frequency and video bandwidth.
- Figure 12 shows the block diagram of the logarithmic detection after mixing, consisting of the receiving probes, a waveguide filtering, an RF circuit in Kovargetude, a data acquisition using the principle of oversampling, a laptop and a control electronics.
- the components mentioned have the specified circuit structure.
- FIG. 13 shows the block diagram of the mixer. This includes a HF, an IF and an LO branch. In the central line structure, two diodes are arranged in neutral order and the LO signal is guided as a slotted wave, wherein the RF and the IF signal are guided as a coplanar wave.
- Figure 14 shows the block diagram of the receiver with external detector.
- the logarithmic detector is located outside the HF housing. Due to the initial state of development, the detector is being tested on an evaluation board.
- FIG. 15 shows the meter specifications of the receiver with external detector. This results in two almost identical curves, which show fairly linear behavior with an input power of -80 to -20 dBm.
- FIG. 16 shows the arrangement of the receiving probes within a drift tube. With this arrangement, both the electron beam can be received, as well as calibrated according to the described principle opposite receiving channels.
- FIG. 17 shows the transfer function of a probe calibration. In this case, a signal is fed in at Port 1 and received at Port 3 and Port 4 in order to calibrate it. This results in an isolation of about 40 dB between the send port and the receive ports.
- Figure 18 shows a favorable circuit arrangement for feeding the calibration concept, consisting of a VCO, components of an attenuator, an amplifier and a switch.
- the simulations with CST Particle Studio take place in a vacuum and only two opposing probes are considered. With an ideal electron beam position (no deposition from the ideal path of the electron beam), the two opposing probes have the same distance to the beam and thus the same signal level is present. The signal is influenced by the size of the probes.
- This can be simulated with the program CST Particle Studio in the simulation. For this purpose, a cathode and an anode must be defined for the electron beam. Then the type of source is specified.
- the particles are electrons which are distributed in a Gaussian shape within a Bunches.
- the exit velocity is given relativistically as the speed of light.
- the electric charge is in the range of pCoulomb. These values correspond approximately to the conditions prevailing at the LINAC.
- the next step is to define the probes. It is simulated with two different probe diameters of 6 or 25 mm. Above all, it should be noted that the coaxial outer conductor lying on ground does not touch the probe. Therefore, this is offset by 1 mm from the probe to the rear. Implemented in the simulation program then obtain the situation in Fig. 4. If the probes now have a different distance to the electron beam, so different signals result, which have both a phase difference and an amplitude difference. In the simulation one probe has a beam distance of 4 mm and the other a distance of 5 mm. The simulation time is 2 ns, so that 5 electron packets fit into the time span.
- the arrangement of the probe pairs with 25 mm diameter is simulated with CST Particle Studio.
- the time signals (FIG. 5) are obtained as a result, which are converted into the spectral range by a Fourier transformation (FIG. 6).
- the largest signal components are expected to be at the 3 GHz fundamental frequency.
- the amplitude difference between the two signals is 5.157 percent and 0.23 dB, respectively.
- the result of the time signal in FIG. 7 and the frequency signal in FIG. 8 are obtained.
- the largest signal component is at 9 GHz, the 2nd harmonic of the fundamental frequency.
- the amplitude difference is 10.65 percent and 0.49 dB, respectively, and the phase difference is 15.4 degrees.
- the amplitude difference is evaluated.
- the 6 GHz component is used, since smaller probes and components can be used for this than in the evaluation of the 3 GHz Proportions, disturbances by the fundamental frequency can be suppressed by a suitable bandpass filtering.
- the beam position measurement is to take place in operational mode within drift tubes in a standing wave resonator with outsorted coupling slots, as shown in Chapter 2 Fig. 3, take place.
- the drift tubes are located between resonators and are particularly well suited for a beam position measurement, as there only the E-FeId of the electron beam is present, while the RF signal takes the detour via coupling slots.
- the measuring probes are introduced radially from the outside into the drift tube with a radius in the centimeter range. Now a comparison of the time signals takes place (FIG. 9).
- the performance data of the external detector used in the preferred mixing concept and of the ADC (analog-to-digital converter) of the measurement data acquisition card are used to calculate the measurement accuracy.
- the detector used has a dynamic range of 95 dB, a DC output voltage range of 2.28 V.
- the minimum detectable power also determines the measurement accuracy of the beam condition monitor.
- 11 shows the basic circuit diagram of a simplified receiver for measuring the reception level, as it has been investigated in detail in the course of the work and has been favored over other concepts in multiple execution due to its superior system properties.
- Decisive for the minimum detectable reception power is the signal-to-noise ratio. From [4] follows for the noise power of a receiver:
- the noise figure is calculated according to [4]:
- the "oversampling" signal processing concept proposed in the course of the work demands an almost perfect reconstruction of the pulse, especially the pulse edges, which in turn are determined by the video bandwidth of the analog-to-digital converter (ADC)
- ADC analog-to-digital converter
- the proposed ADC has a video bandwidth of 10 MHz, ie an edge rise time of 0.1 ⁇ s, which is an acceptable value for pulse reconstruction in relation to the pulse length of 5 ⁇ s.
- Waveform Pulse length 5 ⁇ s; Pulse repetition frequency: 50 to 200 Hz
- the preferred circuit concepts are all based on parallelizing all receive channels, ensuring, through the choice of technology, that no inter-channel interference occurs and eliminating tunable components such as AGC (Automatic Gain Control) amplifiers.
- AGC Automatic Gain Control
- the large dynamic range of about 70 dB should be covered by broadband, logarithmic detectors. All non-linearities of the circuits are controlled by an automatic test station recorded and stored in the digital signal processing electronics, to be considered later in the calculation of the deposition of the electron beam from its ideal orbit. This is to ensure that a high measurement accuracy is achieved.
- Another strength of the concepts lies in the digital signal processing concept, which is designed so that a complete, digital reconstruction of the 5 ⁇ s pulse is possible. No information should be lost in the HF and IF circuits.
- the digital circuit consists of a microcontroller with corresponding peripherals. After oversampling the detector output voltage for pulse reconstruction, the data is sorted by pulse and gap and only the data stored in the pulse. Subsequently, the signal evaluation with algorithms such as threshold detection, pulse integration, plausibility calculations, a / ß - tracker, etc. The then calculated storage in x and y of the ideal track is provided via digital bus, such as CAN or Profibus the control electronics available. Subsequently, different reception concepts are compared with each other in an evaluative manner.
- the first RF component of the receiving circuit is always the bandpass filter in all circuit concepts. This is preferably carried out in waveguide technology to select the 6 GHz signal.
- the subsequent planar receiving circuit is implemented on a 0.635 mm thick aluminum oxide ceramic with unhoused chip components as active components.
- the RF circuit is mounted in a radiation-proof Kovar housing, which can be hermetically sealed.
- the signal evaluation takes place via a control and evaluation electronics on FR4 PCB.
- the received signal at the coupling probes is first filtered with a bandpass in waveguide technology in order to obtain a continuous 6 GHz signal during the 5 ⁇ s beam duration from the broadband, pulsed probe signal.
- a low-noise amplification with an LNA (Low Noise Amplifier).
- the LNA has the advantage that even the smallest signal components can be detected and, above all, that the noise figure of the entire system can be kept low. This is followed by an attenuation outside the useful band and a further amplification.
- the 6 GHz signal is mixed in the IF range of approximately 500 MHz.
- the advantages of the lower frequency are the lower line losses and the possibility to achieve very high frequency selectivity by filtering in the IF range.
- the IF signal can be led out of the housing and detected in an external, packaged, logarithmic detector on the circuit board.
- the LO signal is generated by a VCO controlled by a PLL (Phase-Locked Loop). This is initialized via the microcontroller and controlled with the quartz-precise nominal frequency.
- the actual frequency of the VCO is supplied to the PLL circuit by the VCO signal is coupled out and divided by frequency divider by a factor of 4.
- this signal is internally divided down again and compared its phase with the highly stable crystal signal.
- the VCO via a control voltage (V tune ), which is filtered with a low-pass, readjusted to 6.5 GHz.
- the mixed-down signal is again amplified by one GB to compensate for the conversion loss. This is followed by bandpass filtering in order to suppress the portions of the RF and LO signal that are greatly attenuated by insulation measures but still exist. This is followed by the conversion of the IF power into a DC voltage by means of the logarithmic detector.
- the further strategy is to over-sample the DC voltage, which is applied for 5 ⁇ s, with approximately 2 MHz. This results in 10 values in the pulse, which can be generated, for example, by means of a data acquisition card. talized and stored in the memory of the PC (personal computer) via USB bus. The database thus generated then serves for algorithm development and interpretation of the operational signal processing electronics.
- the circuit should be designed for a power range of at least -20 to -55 dBm. The level range at higher powers is limited by the saturation of the mixer and at lower power by the system noise.
- the active HF components are supplied with 6V.
- logarithmic direct detection After initial bandpass filtering and amplification, the signal is fed directly to the logarithmic detector at 6 GHz. Subsequently, just as in the mixing principle, an oversampling, data storage and digital signal evaluation takes place. Another possibility is the use of diode detectors. With this concept you would have the least amount of hardware. The method fails due to the insensitivity and the reduced dynamics of about 2O dB.
- An alternative concept is the sum and difference evaluation in the HF range.
- An I-Q mixer consists of two mixers that mix down the same signal, but with a LO signal shifted by 90 °. This phase shift and the division of the LO signal into two channels can be achieved either via a Pi / 2 hybrid or via a 3dB power divider, which has a ⁇ / 4 line delay on one channel.
- the position offset (P) is normalized to the radiant intensity with the formula:
- the technological implementation of logarithmic direct and IF detection are described below.
- the first component of the two RF circuits is in each case the bandpass filter. It is advantageous to use waveguide technology, since in the waveguide electromagnetic waves with frequencies below the specific cutoff frequency of the respective waveguide are not capable of propagation.
- By evaluating the 6 GHz component by means of a suitable choice of geometrical waveguide dimensions, it is possible to suppress the fundamental beam frequency of 3 GHz and to ensure that it does not cause interference in the receiving electronics. If one strives for a reduction of the waveguide, then one can fill it with dielectric, which has an ⁇ r > 1, without the transmission properties change significantly.
- the lower transmission losses are advantageous over a planar filter in stripline technology.
- the RF reception circuit is realized on alumina (A12O3) ceramic with an ⁇ r of 9.8. As a result, the reception structures become smaller with the factor f f ⁇ r .
- ceramic behaves heat dissipating and is therefore ideal for active components that convert their power loss into heat.
- the hardness of the ceramic material allows good bondability of the components.
- the ceramic substrate is protected by a Kovar housing, which has the same thermal expansion coefficient as the substrate. This ensures that the ceramic is not damaged by the housing during thermal propagation.
- the package protects the components that are "bare-faced" on the substrate with silver conductive adhesive and their bonded connections in an unhoused form.
- the bond connections are made with 17 ⁇ m gold wire.
- a request for use with the linear accelerator is an irradiation-resistant design. its hulls and hulls are hermetically sealed, a space-proven process using coplanar balanced stripline technology, where both the conductor and the ground plane are on one side of the substrate end advantage over the MSL are the lower couplings of the lines.
- two independent reception channels are required per axis, which, of course, must not cause any crosstalk on the other reception channel.
- An additional advantage over MSL is the simplified fabrication of ground contacts for lumped devices through simple bond connections.
- a waveguide filter was designed which decouples the harmonic at 6 GHz, has a bandwidth of about 145 MHz, the lowest possible losses in the passband and a high stopband attenuation.
- the bandwidth specification in the pass band is a compromise of narrowband and fast settling time. The settling time should not be too high for the filter to quickly stabilize due to the high energy pulses of the electron beam, thus allowing accurate evaluation.
- a filter with dazzling-coupled cavity resonators was selected due to the good manufacturing capabilities. This has in contrast to other filter arrangements resonators with uniform waveguide dimensions.
- the panels are designed inductively, so that you can produce two shells frästechnisch, which are then screwed together.
- the next development step is the design of the transition between waveguide and coaxial cable. This is necessary because the probes have an SMA output and the receiving circuit has an SMA input. This transition can be performed inductively or capacitively. Due to the simpler manufacturing, a capacitive transition was preferred here.
- the inner conductor of the SMA connector is simply extended, so that it protrudes into the waveguide.
- the distance to the waveguide wall in the longitudinal direction should be approximately ⁇ / 4, so that the existing short circuit on the waveguide wall at the location of the coupling causes an idle.
- the most favorable is the production of two half-shells, since there are the field-sensitive aperture not in the connection plane of the shells. In addition, no wall currents are crossed by this construction technique, which has a good effect on the avoidance of losses.
- the bolted waveguide filter was measured. It has a passband at 6 GHz with an adjustment better than -20 dB, but also other passbands such as at 8.3 GHz. These can be suppressed by adding a coaxial low-pass filter to the filter. In a series-compatible arrangement, the low-pass filter can be integrated into the capacitive coupling probe. In the present case, however, this step was omitted in the sense of a proof of function.
- the filter is reduced by introducing a dielectric.
- polyphenylene sulfide DIN abbreviation: PPSGF 40
- PPSGF 40 polyphenylene sulfide
- the first development step is to define the geometric dimensions of the circuit due to the practical realities of thin-film and package engineering. Subsequently, the structures are converted into a layout using the simulation program ADS (Advanced Design System). To produce the aluminum dioxide substrate in the thickness of 0.635 mm, a chrome mask is produced and the circuit is then processed in a thin-film laboratory. After the substrate has been fabricated, the chip components are glued with silver conductive adhesive, the assembled substrate is installed in the kovar housing, the connections of the chips to the substrate are bonded with gold wire and SMA plugs and connection pins are laser-welded into the kovar housing. All structures were drawn here with the drawing program AutoCAD.
- the central components are the two mixer structures. There arises by driving the non-linear characteristic of the diodes by the high-frequency LO signal and the applied RF signal relative to their frequency offset an IF signal. This is controlled by two diodes in balanced mode.
- a distinction between a LO and an RF branch, which in the layout within a structure is integrated. Starting from the LO line, which leads a coplanar wave, a slotted wave is excited via a bonding wire to ground.
- the slot shaft is short-circuited in the direction of the IF gate by a line interruption and in the direction of the HF gate by a ground bond across the line.
- the diodes are controlled, the LO signal suppressed outside of this wiring and thus isolated.
- the RF signal is fed to the diodes via an X- frequency inter-digital capacitor. In the direction of the ZF gate, isolation is provided by idling stubs.
- the stubs transform an open circuit into a short circuit at the point where the stubs hit the IF line.
- the RF wave is reflected at this point, forms a standing wave and generated by the ⁇ / 4 transmission line to the diodes, the idle condition.
- LO, HF and IF gate are isolated from each other by the line structures used.
- diodes Silicon Schottky diodes were selected. These have a low conversion loss due to their high cutoff frequency.
- the diodes are arranged so that one diode is on the line and bonded to ground while the other is grounded and bonded to the line. This corresponds to an arrangement for push-pull mixing.
- the cathode is always grounded.
- Rotation of the selected diode is not possible due to the "barrel-shaped" anode, so there is always a direction of flow at the diodes from top to bottom, during the mixing process the field in the slot is coupled through the bonding wire into the diodes.
- Fig. 15 shows the waveform of the two channels.
- a transmission signal of 20 dBm to at least -20 dBm must be generated in order to be able to cover the total dynamics of the receivers from approximately -20 to -60 dBm.
- the VCO from the operational receiver circuit is used with an output power of 13 dBm. Unlike the operational hardware, the VCO frequency is locked to 6 GHz.
- three attenuators which in practice have an attenuation of -4 to -20 dBm. After the Attenuators can amplify the signal well.
- Suitable for the application is the hmc 451 amplifier from Hittite. This is followed by an SPDT (Single Pole Double Throw Switch) switch that allows calibration of all four channels.
- a distance measuring device is provided with evaluation electronics for determining the position of an electron beam, which has at least two coupling probes for decoupling an electromagnetic wave of the electron beam and is characterized in that the decoupling of the electromagnetic wave takes place in at least one drift tube of an electron linear accelerator and in that the evaluation unit adapted to evaluate a frequency range of the decoupled electromagnetic wave, which has a center frequency which corresponds to a multiple of the frequency of the electromagnetic wave, which is fed from the high-frequency generator for generating the acceleration field in the linear accelerator.
- the packaging of the electrons within the linear accelerator tube has a favorable effect on the evaluation of the described frequency range.
- two coupling probes offset by 180 degrees at the cylinder edge of the drift tube or staggered by 90 degrees with 4 coupling probes, in order to determine the filing of the electron beam in the vertical and horizontal directions.
- the coupling probes are adapted in a 50 ⁇ system in the frequency range of the wave to be coupled out, have a low coupling factor in order to extract as little energy as possible from the electron beam and the coupling takes place capacitively or inductively or via slot coupling or a combination thereof.
- the field to be coupled out is preferably an electromagnetic wave in TEM mode with a frequency in the range 5 to 20 GHz.
- the frequency of the first harmonic preferably corresponds to the fundamental frequency of the acceleration field.
- each of the coupling probes is connected in each case via a waveguide in each case a receiver whose first coupling probe side receive channel component is designed as a narrowband RF band-pass filter whose center frequency corresponds to the decoupled electromagnetic wave.
- the bandpass filter is designed as a waveguide filter with or without dielectric filling or as a dielectric filter or preferably as a planar filter in order to achieve the most compact design.
- the respective receiver is a low-noise amplifier, then a mixer with local oscillator, preferably a voltage-controlled oscillator, then a narrow-band IF filter, then a logarithmic detector, then an analog / digital converter and then a digital signal processing unit.
- the bandwidth of the IF filter is preferably dimensioned, for example, at 10 MHz so that the reconstruction of the envelope of the pulse packets of the electron beam is possible, for example, for a duration of 5 ⁇ s.
- the video bandwidth of the analogue diode corresponds gitalwandlers at least the bandwidth of the IF filter.
- a signal via the respective coupling probe is fed into the drift tube for calibration of the receiver via a transmit / receive switch between RF band-pass filter and low-noise amplifier, which has the same frequency as the output shaft in the operational mode.
- the calibration signal is fed in via the middle coupling probe in each case and is received by the two adjacent coupling probes arranged offset by +/- 90 degrees.
- the determination of a distance, in particular using the distance measuring device according to the invention according to a method for determining a distance, in particular using the distance measuring device according to the invention, wherein the method identifies the steps:
- drift tube which has a decoupling region, wherein at least 4 by 90 degrees staggered coupling probes are connected via waveguides, each with an RF receiver, and
- an electromagnetic wave is fed via at least 1 coupling probe
- the calculation of the beam deposition takes place in an axis, e.g. vertically or horizontally by subtraction of the amplitude values of the received signals of two opposite coupling probes.
- the calibration signal fed in via a coupling probe is received in the two adjacent coupling probes and the amplitude difference of the two receiving channels is determined as a correction value, stored and offset in operational mode, when the electron beam is present, to determine the beam deposition.
- VCO Voltage Controlled Oscilltaor Voltage Controlled Oscillator
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- Physics & Mathematics (AREA)
- Engineering & Computer Science (AREA)
- Plasma & Fusion (AREA)
- Spectroscopy & Molecular Physics (AREA)
- Particle Accelerators (AREA)
- Radiation-Therapy Devices (AREA)
Abstract
Description
Claims
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
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DE102009028362A DE102009028362A1 (de) | 2009-08-07 | 2009-08-07 | Strahllagemonitor für Elektronen-Linearbeschleuniger |
PCT/EP2010/061376 WO2011015609A2 (de) | 2009-08-07 | 2010-08-04 | Strahllagemonitor für elektronen-linearbeschleuniger |
Publications (2)
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EP2462787A2 true EP2462787A2 (de) | 2012-06-13 |
EP2462787B1 EP2462787B1 (de) | 2017-07-19 |
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EP10747017.1A Active EP2462787B1 (de) | 2009-08-07 | 2010-08-04 | Strahllagemonitor für elektronen-linearbeschleuniger |
Country Status (4)
Country | Link |
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US (1) | US9736922B2 (de) |
EP (1) | EP2462787B1 (de) |
DE (1) | DE102009028362A1 (de) |
WO (1) | WO2011015609A2 (de) |
Families Citing this family (18)
Publication number | Priority date | Publication date | Assignee | Title |
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US8183801B2 (en) * | 2008-08-12 | 2012-05-22 | Varian Medical Systems, Inc. | Interlaced multi-energy radiation sources |
EP2823501B1 (de) | 2012-03-03 | 2019-05-01 | The Board of Trustees of The Leland Stanford Junior University | Pluridirektionale strahlentherapievorrichtungen mit sehr hoher elektronenenergie |
DE102012219726B3 (de) * | 2012-10-29 | 2014-03-13 | Friedrich-Alexander-Universität Erlangen-Nürnberg | Verfahren zum Betreiben eines Linearbeschleunigers und nach diesem Verfahren betriebener Linearbeschleuniger |
CN103068147A (zh) * | 2012-12-25 | 2013-04-24 | 江苏达胜加速器制造有限公司 | 一种设有导向线圈的加速管 |
KR20140102031A (ko) * | 2013-02-13 | 2014-08-21 | 한국원자력연구원 | 유연 및 회전연결 도파관을 이용한 다관절 방사선 치료기 |
EP3043864A4 (de) | 2013-09-11 | 2017-07-26 | The Board of Trustees of The Leland Stanford Junior University | Verfahren und systeme zur strahlenintensitätsmodulation zur aktivierung schneller radiotherapien |
WO2015102681A2 (en) | 2013-09-11 | 2015-07-09 | The Board Of Trustees Of The Leland Stanford Junior University | Methods and systems for rf power generation and distribution to facilitate rapid radiation therapies |
US9674026B1 (en) * | 2016-05-26 | 2017-06-06 | Jefferson Science Associates, Llc | Beam position monitor for energy recovered linac beams |
WO2018222839A1 (en) | 2017-06-01 | 2018-12-06 | Radiabeam Technologies, Llc | Split structure particle accelerators |
KR101993050B1 (ko) * | 2017-09-28 | 2019-06-25 | 고려대학교 세종산학협력단 | 빔 위치 모니터 신호처리 시스템 |
WO2020061204A1 (en) | 2018-09-21 | 2020-03-26 | Radiabeam Technologies, Llc | Modified split structure particle accelerators |
KR102182188B1 (ko) | 2018-11-21 | 2020-11-24 | 고려대학교 세종산학협력단 | 나노미터 수준의 빔 위치 분해능을 얻기 위한 공동형 빔 위치 모니터 신호처리 시스템 및 방법 |
JP2020165713A (ja) * | 2019-03-28 | 2020-10-08 | 株式会社デンソーテン | 検査データ出力装置、表示システムおよび検査データ出力方法 |
KR102185094B1 (ko) * | 2019-11-01 | 2020-12-01 | 에이트론(주) | 위성방송 수신용 저잡음 변환기 및 이를 포함하는 안테나 장치 |
US11483920B2 (en) * | 2019-12-13 | 2022-10-25 | Jefferson Science Associates, Llc | High efficiency normal conducting linac for environmental water remediation |
US11726174B1 (en) * | 2019-12-30 | 2023-08-15 | Waymo Llc | Methods and systems for removing transmit phase noise |
CN111208552B (zh) * | 2020-03-02 | 2024-06-18 | 中国工程物理研究院流体物理研究所 | 一种共振式在线束流位置探测器 |
CN113722871B (zh) * | 2021-11-03 | 2021-12-31 | 华中科技大学 | 一种x波段行波加速管的结构参数优化方法 |
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US2952795A (en) * | 1957-06-24 | 1960-09-13 | Gen Electric | Electron discharge device |
US3109146A (en) * | 1962-04-19 | 1963-10-29 | Bell Telephone Labor Inc | Cyclotron wave electron beam parametric amplifier |
-
2009
- 2009-08-07 DE DE102009028362A patent/DE102009028362A1/de not_active Withdrawn
-
2010
- 2010-08-04 WO PCT/EP2010/061376 patent/WO2011015609A2/de active Application Filing
- 2010-08-04 US US13/389,418 patent/US9736922B2/en active Active
- 2010-08-04 EP EP10747017.1A patent/EP2462787B1/de active Active
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Also Published As
Publication number | Publication date |
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US9736922B2 (en) | 2017-08-15 |
EP2462787B1 (de) | 2017-07-19 |
WO2011015609A2 (de) | 2011-02-10 |
WO2011015609A3 (de) | 2011-04-21 |
US20120262333A1 (en) | 2012-10-18 |
DE102009028362A1 (de) | 2011-02-10 |
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