EP2174408A1 - Onduleur - Google Patents

Onduleur

Info

Publication number
EP2174408A1
EP2174408A1 EP08758720A EP08758720A EP2174408A1 EP 2174408 A1 EP2174408 A1 EP 2174408A1 EP 08758720 A EP08758720 A EP 08758720A EP 08758720 A EP08758720 A EP 08758720A EP 2174408 A1 EP2174408 A1 EP 2174408A1
Authority
EP
European Patent Office
Prior art keywords
switch
voltage
inductance
inverter according
diode
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP08758720A
Other languages
German (de)
English (en)
Inventor
Heribert Schmidt
Bruno Burger
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Fraunhofer Gesellschaft zur Forderung der Angewandten Forschung eV
Original Assignee
Fraunhofer Gesellschaft zur Forderung der Angewandten Forschung eV
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Fraunhofer Gesellschaft zur Forderung der Angewandten Forschung eV filed Critical Fraunhofer Gesellschaft zur Forderung der Angewandten Forschung eV
Publication of EP2174408A1 publication Critical patent/EP2174408A1/fr
Withdrawn legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for ac mains or ac distribution networks
    • H02J3/38—Arrangements for parallely feeding a single network by two or more generators, converters or transformers
    • H02J3/381—Dispersed generators
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H02M1/34—Snubber circuits
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J2300/00—Systems for supplying or distributing electric power characterised by decentralized, dispersed, or local generation
    • H02J2300/20—The dispersed energy generation being of renewable origin
    • H02J2300/22—The renewable source being solar energy
    • H02J2300/24—The renewable source being solar energy of photovoltaic origin
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J2300/00—Systems for supplying or distributing electric power characterised by decentralized, dispersed, or local generation
    • H02J2300/30—The power source being a fuel cell
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H02M1/34—Snubber circuits
    • H02M1/342—Active non-dissipative snubbers
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
    • Y02E10/00—Energy generation through renewable energy sources
    • Y02E10/50—Photovoltaic [PV] energy
    • Y02E10/56—Power conversion systems, e.g. maximum power point trackers

Definitions

  • the invention relates to an inverter for converting a DC voltage into an AC voltage or an AC current according to the preamble of the main claim.
  • Inverters for converting a DC voltage to an AC voltage or AC are well known, and these inverters discriminate between inverters without galvanic isolation, ie, transformerless inverters and those with galvanic isolation, ie, transformer inverters.
  • the highest efficiencies are achieved with transformerless inverters in full bridge circuit without step-up converter. achieved, as described for example in DE 102 21 592 Al.
  • the potential of the source at mains frequency and half mains voltage varies from ground potential. Therefore, there is a limitation in the applicability of these concepts in sources with a high dissipation capacity to earth potential, as is the case for example with solar generators of certain technology, in particular thin-film modules.
  • the input voltage range is limited by the voltage required to supply at the level of the amplitude of the mains voltage, ie approximately 325 V with an effective value of 230 V, downwards.
  • transformerless concepts e.g. from DE 196 42 522 Cl and DE 197 32 218 Cl, in which a connection of the solar generator is fixedly connected to the neutral conductor and thus has a fixed potential to earth potential.
  • no leakage currents can flow, even with arbitrarily high leakage capacitances.
  • a choke coil in a first clock section via two switches to an input voltage which is buffered with an input capacitor, placed and stored energy in the inductor.
  • a plurality of switches are configured so that the energy stored in the choke coil can be delivered to the output via diodes and said switches.
  • Disadvantage of this known circuit arrangement is that the current flows through a plurality of semiconductor switches and diodes in the individual clock phases. In the first clock phase there are always two switches in the current path, in the second clock phase during the positive half cycle two switches and two diodes and in the negative two switches and one diode. This results in high losses and correspondingly poor efficiency.
  • the switches, together with the associated controls represent a considerable effort and reduce the reliability. These inverters are therefore characterized by high complexity and thus poor efficiency, high costs and reduced reliability.
  • the invention is therefore based on the object, an inverter for converting a DC voltage into an AC voltage or an AC current from a respect to a neutral unipolar
  • DC voltage source to provide that offers high efficiency and based on simple, inexpensive, reliable and control technology easily manageable structures.
  • a second inductance in close coupling is provided for the first inductance and the two inductors each emit their energy via a second two electronic switches to a lying parallel to the AC terminal filter capacitor, wherein a series circuit of a third clocked switch and a capacitor for receiving energy from stray inductances having transverse branch with the the first inductance and the series circuit of one of the second switch and the second inductor is connected, the number of semiconductor switches is reduced.
  • the current flows in the first clock phase only by a semiconductor switch, in the second clock phase during both half-waves by a respective semiconductor switch and a diode, whereby the efficiency and reliability increase.
  • the energy stored in the unavoidable leakage inductance of the first inductance can be absorbed and passed on in a targeted manner to the output, and there are no unnecessary losses associated with losses within the circuit.
  • This measure leads to a further noticeable increase in efficiency, one of the main goals in the development of inverters for photovoltaics.
  • the insertion of the switch into the shunt branch results in the capacitor not being charged to a high voltage in the half-wave in which the described function is not required. This would have the consequence that when changing the Netzpolartician briefly a high discharge current pulse would flow.
  • overvoltage limiting components such as varistors each with an inductance and a diode are connected, since they can absorb the energy stored in the inductors e energy, if in an emergency shutdown of the inverter, all switches are opened simultaneously. This avoids that, as a result of extreme overvoltages on the semiconductors, as in the prior art, these are destroyed. Since the overvoltage limiting components in the arrangement according to the invention are exposed to no pulse voltage, varistors can be used. However, the use of these inexpensive and robust components would be prohibited in clocked circuits, since varistors have a very high parasitic capacitance, which would have to be reloaded at each clock.
  • the prior art additionally uses decoupling diodes or so-called TVS diodes (transient voltage suppressor diodes (TransZorb diodes)), which however are more expensive.
  • TVS diodes transient voltage suppressor diodes (TransZorb diodes)
  • the circuit arrangement according to the invention can also be designed to be multi-phase, e.g. three-phase for feeding into the usual public three-phase network.
  • one or more solar generators, fuel cells, batteries or the like can be used as DC voltage source.
  • the circuit is designed to be complementary and the plus pole of the solar generator is connected to the neutral conductor, whereby all cells of the modules of the solar generator have a negative potential with respect to the ground potential. ben, which has an advantageous effect on the efficiency of certain solar cell types.
  • Fig. 2 diagrams of the switches at the
  • Fig. 3 shows timing diagrams on an enlarged scale of the first switch and the third switch, and a diagram for the current of the capacitor in the shunt branch.
  • the illustrated in Fig. 1 and designed as an inverter circuit arrangement has a DC voltage source, which is a solar generator 1 in the embodiment, which is located with its terminals on a positive line 2 and a neutral or ground conductor 3. This solar generator supplies a DC input voltage U SG .
  • an input capacitor C 0 is provided, which buffers the input voltage U SG . Between the lines 2, 3 is the
  • switch S 0 Series connection of a first inductor W 1 and a clocked by a control unit, not shown switch S 0 , which may be formed as a transistor, preferably as a MOS-FET or as an IGBT.
  • the diode D 0 is not required for the actual function of the circuit, but is in the case It is inherent to MOS FETs, IGBTs require additional installation and protect these components against negative voltages.
  • a second switch S N is connected, wherein a diode D N with the switching path of the switch S N is in series.
  • a diode D 1 In parallel with the switch is again a diode D 1 , wherein the same applies to the switch S N and the diode D 1 (also for the described below switch S p and the diode D 2 ), as for the switch S 0 and the diode D 0 .
  • the anode of the diode D N is connected to the output or filter capacitor C 2 .
  • Another diode D p is connected with its anode to the neutral conductor 3 and with its cathode to a further second switch S p with a parallel diode D 2 and a second inductance W 2 is connected in series with the switching path of the switch S p , wherein the winding start of the inductance W 2 is also connected to the output or filter capacitor C 2 .
  • the inductors W 1 and W 2 are coupled together.
  • a shunt branch is arranged, which consists of the series circuit of a switch S C1 and a capacitor C 1 , wherein a diode D C1 is connected in parallel with the switching path of the switch S C1 .
  • the inductors W 1 , W 2 feed via the switches S N and S p an output or filter capacitor C 2 , which is connected to a terminal on the neutral conductor 3 and is connected to the other terminal together with the second inductor W 2 and the diode D N with a smoothing or supply choke L 1 , whose other terminal is connected to one of the phases L of the network 4, in which an alternating current is to be fed , where the mains voltage is called U net .
  • the neutral conductor 3 marked N / PE also forms an AC output terminal.
  • the two coupled inductors W 1 , W 2 have energy storage properties, wherein the inductance W 1 is used twice, namely for storing the energy and for generating an in relation to the potential of the neutral conductor 3 inverted output voltage.
  • the winding of the inductors W 1 , W 2 are coupled to one another via a coupling factor k (0 ⁇ k ⁇ 1).
  • a first varistor VDR P is connected and a second varistor VDR N is connected to the cathode of the diode D N and the winding end of the second inductor W 2 connected.
  • the duty cycle of the switch S 0 is set via a control circuit, not shown, for example, a pulse width modulator PWM, so that in the output inductor L 1 adjusts a sinusoidal current, which is then fed into the public grid.
  • the clock period T clock of the clocked switch S 0 be 60 ⁇ s.
  • Way pulse-like output to the filter capacitor C 2 energy is there integrated into a capacitor voltage and fed via the smoothing inductor L 1 in the network 4.
  • the switches S p and S C1 are permanently open and the inductance W 2 is idle.
  • the switch S N is open and the switch S p is closed.
  • the energy stored in both inductances W 1 , W 2 leads to a positive current flow through the diode D p , through the switch S p and through the inductance W 2 in the capacitor C 2 and, as above, via the smoothing inductor L 1 in the network 4th
  • Fig. 3 the operation of the shunt arm with the switch S C1 , the diode D C1 and the capacitor C 1 is shown.
  • the capacitor C 1 has the task of receiving the energy stored in the W 1 unavoidable leakage inductance of the first inductance and to pass to the output.
  • the switch S C1 is closed shortly before the opening of the switch S 0 , ie, the delay time between the switching on of the third switch S cl and the switching off of the first switch S 0 is T D.
  • the turn-on time of the third switch is designated by T SC1 .
  • the capacitor C 1 forms a resonant circuit with the stray inductance of the first inductance W 1 , so that the current I C1 shown in FIG. 3 results.
  • the current flow direction in the capacitor C 1 reverses again after a defined time (zero crossing at T 01 ), and an energy flow takes place via the winding W 1 , the then conducting diode D C1 , the capacitor C 17 the switch S p and the second inductor W 2 in the output. It is essential that the switch S C1 is opened after the current direction has changed. has reversed and the current flows through the parallel diode D C1 .
  • Such a switch-off of the switch S C1 can be carried out either time-controlled by the control or regulating unit, not shown, because of the fixed time sequences, or else by detecting the current direction in the transverse path.
  • the duty cycle T SC1 In the case of a time-controlled activation of the third switch S C1 , the duty cycle T SC1 must be longer than the time T 01 until the first zero crossing of the capacitor current I C1 and shorter than the time T 02 until the second zero crossing. In a state-dependent control of the switch S C1 would be turned off by the first zero crossing T 01 .
  • the Umschwingvorgang ends at the next zero crossing T 02 of the current I C1 , since then the diode D C1 is in the reverse direction and the switch S C1 , as described, was opened.
  • the described timing ensures that the energy stored in the leakage inductance can be selectively passed on to the output and that no unnecessary losses associated with losses take place within the circuit. This measure leads to a noticeable increase in the efficiency.
  • the presence of the open in the negative half wave switch S C1 means that the capacitor C 1 in the negative half cycle is not charging via the diode D P to a high voltage. This would have the consequence that when changing the Netzpolartician, in which the switch S N is opened and the switch S p is closed, briefly a high discharging current pulse on the with the first inductor W 1 , the capacitor C 1 , the Switch S p , the second inductance W 2 and the capacitor C 2 formed circuit would flow.
  • the two varistors are connected between the respective inductance and the respective diode. These have the task to absorb the energy stored in the inductors, if an emergency shutdown of the inverter all switches are opened simultaneously. Unlike in many conventional inverter topologies, this arrangement does not have an inherent current path through which the inductance could output its energy in a controlled manner, eg via free-wheeling diodes into existing buffer capacitors. As a result, extreme overvoltages will be created on the semiconductors, which would typically destroy them. According to the circuit according to FIG. 1, in the event of an emergency shutdown, two paths result for the energy reduction.
  • the inexpensive and robust VDR resistors can be used since they are not exposed to any pulse voltage and the voltage across them changes relatively slowly at the mains frequency, ie 50 Hz.
  • the circuit of FIG. 1 can be constructed to be complementary.
  • the diodes D N and D p can also be embodied as electronic switches, the switch corresponding to the diode D N being in the negative half-cycle asynchronous with the first switch S 0 and that of the diode D p corresponding switches are driven in the positive half-wave. As a result, the efficiency can be further increased.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)

Abstract

La présente invention concerne un onduleur destiné à convertir une tension continue en une tension alternative ou un courant alternatif, comprenant un premier branchement série qui est relié aux bornes de tension continue et comprend au moins un premier commutateur électronique et une première inductance destinée à emmagasiner l'énergie de commutation et une pluralité de deuxièmes commutateurs électroniques destinés au transfert de l'énergie emmagasinée. Une deuxième inductance est couplée étroitement à la première inductance, les deux inductances fournissant leur énergie à un condensateur-filtre monté en parallèle de la borne de tension alternative, respectivement par l'intermédiaire d'un deuxième commutateur électronique. En outre, l'onduleur comprend une branche en dérivation qui comprend un branchement série d'un troisième commutateur cadencé et d'un condensateur destiné à emmagasiner l'énergie d'inductances de fuite, et qui est reliée à la première inductance et au branchement série de l'un des deuxièmes commutateurs et de la deuxième inductance. L'invention s'applique par ex. à un générateur solaire destiné à alimenter un réseau publique.
EP08758720A 2007-06-22 2008-05-20 Onduleur Withdrawn EP2174408A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102007029767A DE102007029767B3 (de) 2007-06-22 2007-06-22 Wechselrichter
PCT/EP2008/004124 WO2009000377A1 (fr) 2007-06-22 2008-05-20 Onduleur

Publications (1)

Publication Number Publication Date
EP2174408A1 true EP2174408A1 (fr) 2010-04-14

Family

ID=39702452

Family Applications (1)

Application Number Title Priority Date Filing Date
EP08758720A Withdrawn EP2174408A1 (fr) 2007-06-22 2008-05-20 Onduleur

Country Status (4)

Country Link
US (1) US20100289334A1 (fr)
EP (1) EP2174408A1 (fr)
DE (1) DE102007029767B3 (fr)
WO (1) WO2009000377A1 (fr)

Families Citing this family (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2009068698A1 (fr) * 2007-11-30 2009-06-04 Ingeteam Energy, S.A. Circuit électrique de conversion de courant continu en courant alternatif

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Also Published As

Publication number Publication date
DE102007029767B3 (de) 2008-12-24
US20100289334A1 (en) 2010-11-18
WO2009000377A1 (fr) 2008-12-31

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