EP2070189A1 - Récepteur radio - Google Patents

Récepteur radio

Info

Publication number
EP2070189A1
EP2070189A1 EP07802571A EP07802571A EP2070189A1 EP 2070189 A1 EP2070189 A1 EP 2070189A1 EP 07802571 A EP07802571 A EP 07802571A EP 07802571 A EP07802571 A EP 07802571A EP 2070189 A1 EP2070189 A1 EP 2070189A1
Authority
EP
European Patent Office
Prior art keywords
radio receiver
signals
frequency
signal
receiver according
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP07802571A
Other languages
German (de)
English (en)
Inventor
Gerhard Kottschlag
Jens Passoke
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Robert Bosch GmbH
Original Assignee
Robert Bosch GmbH
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Robert Bosch GmbH filed Critical Robert Bosch GmbH
Publication of EP2070189A1 publication Critical patent/EP2070189A1/fr
Withdrawn legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
    • H03D7/16—Multiple-frequency-changing
    • H03D7/165—Multiple-frequency-changing at least two frequency changers being located in different paths, e.g. in two paths with carriers in quadrature
    • H03D7/166—Multiple-frequency-changing at least two frequency changers being located in different paths, e.g. in two paths with carriers in quadrature using two or more quadrature frequency translation stages
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
    • H03D7/18—Modifications of frequency-changers for eliminating image frequencies

Definitions

  • the invention relates to a radio receiver.
  • the high intermediate frequency (IF) heterodyne receiver (e.g., JP 2006 174326).
  • IF intermediate frequency
  • JP 2006 174326 The high intermediate frequency (IF) heterodyne receiver
  • the heterodyne receiver with low intermediate frequency is known (for example DE 36 18 782 A1). It has the advantages that the IF filter has a large relative bandwidth and, with the low IF frequency, allows integration even in standard semiconductor processes, which can reduce component costs.
  • the disadvantage of this is the sensitivity to strong signals on the image frequency, since useful and image frequency are in the same frequency range and filtering in front of the mixer is hardly possible.
  • heterodyne receivers with an intermediate frequency of OHz are known, which are sometimes referred to as zero-IF-concept and subsequently also as direct heterodyne receivers or direct mix.
  • These have the advantages that due to the concept no image frequency is available and the IF filter can be integrated as a low-pass filter in standard semiconductor processes.
  • the disadvantage here however, that signal components are disturbed in the middle of the channel, as they fall in the mixture to the frequency OHz and would be fed as DC voltage to the subsequent stages.
  • the DC correction measures often required in these concepts all affect low IF frequency components, thereby preventing undistorted processing of those spectral components of the received signal transmitted close to the channel center frequency.
  • the object of the invention is to provide a radio receiver, which is less prone to interference and can be constructed as simply and inexpensively.
  • the object is achieved by a radio receiver in which the received signal is processed in parallel in at least two paths, wherein at a path a first local oscillator signal is an amount above the channel center and at a second path a second local oscillator signal is below the channel center Furthermore, spectral components can be filtered out by means of filters and then the signals are processed and / or combined in a suitable manner. This concept is referred to below as a segmented mixture or segmenting heterodyne receiver.
  • the signal components of the output signals of the mixers or signals derived therefrom can be digitized by means of analog-digital converters. It is also expedient if the individual stages, such as mixers, analog-to-digital converters and / or filters, can be integrated into a semiconductor. This can advantageously be created a cost-effective implementation.
  • a frequency offset of the local oscillator and / or the filter cutoff frequencies of the bandpasses at the mixer outputs can be varied as a function of the channel raster, the actual signal bandwidth and / or the (interference) signals in the adjacent channels.
  • VCO voltage-controlled oscillators
  • PLL phase-locked loops
  • VCO voltage-controlled oscillator
  • the first mixing process with a variable frequency, which is generated for example by a VCO, the second mixing process, however, not with another VCO, but with a fixed second mixing frequency.
  • Fig. 1 is a schematic representation of received and interference signals for different reception concepts
  • Fig. 2 is a schematic representation of a radio receiver according to the invention.
  • FIG. 1 with the subfigures 1 a to 1 e shows two reception concepts according to the prior art and illustrates the reception concept according to the invention schematically.
  • Figure 1a the composition of the received signal is sketched for illustration.
  • a useful signal 10 of the channel bandwidth BB is flanked by a plurality of interference signals S1, S2, S3, S4.
  • the subdivision A, B, C, D in the useful signal is used later to explain the receiving mechanisms, these blocks include, for example, spectral components of a common useful signal.
  • FIG. 1b shows a representation for heterodyne receivers with a low intermediate frequency. If in a heterodyne receiver a mixing oscillator is used, whose frequency is possibly well outside the receiving channel, the received signal is converted by the mixing process in a different frequency range. The signals applied to the image frequency are also transferred to the same frequency range. Since it is no longer possible to separate the useful signal from the image frequency signal, the reception capability on the image frequency must already be adequately suppressed by suitable measures, for example by prefiltering by means of a bandpass filter BPF, or by using a mirror frequency-suppressing mixer increases the interference immunity. However, the suppression capability of such mixers is typically significantly limited by the characteristics of the technology used. For concepts with a low IF for radio reception, both of the measures described above, even in combination, do not exhibit sufficient interference immunity in order to meet the customer expectations demanded by the good interference behavior of conventional receivers with reasonable effort.
  • FIG. 1 c shows a representation of the so-called direct superimposed receiver.
  • the receive band is mixed with an oscillator signal in the middle of the receive channel, it is called a direct-mix or zero-IF concept, which means that the center frequency of the IF band drops to 0 Hz. Since positive and negative frequencies do not differ with respect to their frequency, the signal components C and D fall above the oscillator frequency exactly on the signal components B and A, which were below the oscillator frequency in the receiving channel.
  • the direct heterodyne receiver exhibits the same image frequency problems as a low intermediate frequency heterodyne receiver.
  • a and B are the mirror to D and C and vice versa.
  • the mirror level is always just as large as the unsmoothed signal component, and thus about 3OdB to 4OdB mirror rejection are usually sufficient here.
  • the problem with the direct heterodyne receiver is the frequency ranges which are close to the frequency OHz, indicated by the dividing line 20. These spectral components of the blocks B and C, which are originally located in the middle of the channel of the useful signal, can be impaired during further processing, for example by Circuit parts of the receiver to compensate for a DC offset by signal components in the middle of the channel at the transition point between the blocks B and C or temperature drift of the receiver stages.
  • FIGS. 1 d and 1 e show the conditions occurring in the case of the segmented mixture according to the invention, in this case segmented direct mixture.
  • the radio receiver according to the invention uses two IQ mixers with then four mixing cells, so that the received signal is mixed with four different oscillator signals. Two frequencies are used, each with two phase angles shifted by 90 °. In the example shown, the two are shifted by +1/8 or -1/8 of the bandwidth (BB) of the user channel from the channel center frequency.
  • BB bandwidth
  • the radio receiver according to the invention is based on a heterodyne receiver or direct superimposed receiver, which is designed in several stages double or multiple and modified as described below.
  • the received signal is typically processed in parallel in at least two paths, with the local oscillator signal of the first path or the first local oscillator signal being a suitable fixed amount above the channel center and the local oscillator signal or the second local oscillator signal being the same fixed magnitude below the channel Channel center is located.
  • the offset is usually less than half the channel bandwidth, preferably about 1/8 Kanal- hand width.
  • the spectral components are filtered out, as for example by means of bandpass filters eliminated, which would be affected by DC correction measures.
  • this filtering also removes further spectral components that could be affected by the superposition of image frequency reception.
  • the remaining signal components of the different paths are then reassembled to give an undisturbed image of the complete signal spectrum in the receiving channel.
  • the optionally filtered output signals of the mixers are first digitized, so that the combining and possibly existing filtering can take place in the digital part.
  • the various signal components in the respective stages can be processed in time-division multiplexing.
  • the radio receiver device of the present invention can be cost effective since the required levels can be integrated into standard semiconductor technologies and possibly only low cost external ones Components are additionally required.
  • the radio receiver according to the invention has the advantage that all significant components can be integrated in standard semiconductor technologies. As a result, expensive external filters can possibly be avoided.
  • the affected spectral components can be discarded or substituted by the signal of the other path.
  • the 1 / f noise is lowered because the most affected low-frequency signal components of the baseband are filtered out as described and therefore no longer go into the output signal.
  • the mixer cell in the oscillator path it is likewise advantageous for the mixer cell in the oscillator path to generate weak interference signals at the input frequency and the respectively undesired mixing frequency, but the frequency position of these signals ensures that no strong interfering signals from adjacent channels are mixed into the useful signal.
  • FIG. 2 shows a schematic block diagram of a radio receiver 200 according to the invention.
  • the received signal of an antenna 201 is filtered by means of a downstream filter 202 and amplified by means of amplifier 203 connected downstream to the inputs 211a, 221a, 231a and 241a of four mixer cells 21 1, 221, 231, 241 passed.
  • the output signals of the mixers 211, 221, 231, 241 are preferably band-pass filtered by means of the downstream filters 212, 222, 232, 242, and then by means of the analogue Digital converter 213, 223, 233, 243 digitized and a digital signal processor DSP 251 supplied.
  • the digital signal processor 251 the four processed signals of the mixers are brought together in a suitable manner, then demodulated and further processed in a known manner.
  • the mixer drive signals for the mixer cells 211, 221, 231, 241 are generated from a voltage-controlled oscillator VCO 261 and a further oscillator 263.
  • the voltage controlled oscillator VCO 261 is controlled by a prior art phase-locked loop (PLL), not shown.
  • PLL phase-locked loop
  • the second oscillator 263 provides a contrast, lower frequency signal fi, as the output signal f 0 of the voltage-controlled oscillator VCO 261.
  • a divided down reference signal of the receiving system may optionally be fed, wherein the dividing factor can be changeable. This is particularly advantageous in order to be able to set or tune a suitable frequency offset.
  • the frequency of this signal results from the desired frequency offset ⁇ between the mixer drive signal of an IQ mixing path and the channel center frequency, eg 1/8 * BB, with BB equal to the bandwidth of the receive channel, and the split ratios in the signal chain between the oscillator and the mixer cells.
  • the divider 264 allows in a known manner the generation of two output signals with a phase shift of 90 °, these signals control two mixer cells 271, 281, in which the divided by the divider V, see block 262, VCO signal f 0 by ⁇ ⁇ is offset.
  • VCO signal f 0 by ⁇ ⁇ is offset.
  • the offset by 90 ° control of the two mixer cells 271, 281 is effected in a known manner that at the outputs of the summation 272 and subtractor 282 at one output the signal fo / V - ⁇ and at the other output the signal fo / V + ⁇ is present.
  • the signals required to drive the mixer cells 211, 221, 231, 241 are generated with a 90 ° phase offset.
  • the out of phase signals may also be generated by further divider stages, which may be similar to stage 264. The division factor would then be taken into account in the design of the oscillator signal chain.
  • processing is performed in a single path in time-division multiplexing. For example, this results in less wiring effort.
  • analog-to-digital conversion can not be performed with four separate analog-to-digital converters, but with an analog-to-digital converter in time division multiplex.
  • the frequency offset of the local oscillator and / or the filter cutoff frequencies of the bandpasses at the mixer outputs can be dependent on the channel raster, the actual signal bandwidth and / or the (interference) signals (for example level and / or bandwidth). be varied in the neighboring channels.
  • VCO voltage-controlled oscillators
  • PLL phase-locked loops
  • a voltage-controlled oscillator VCO can be operated on one of the two mixer drive frequencies or a multiple thereof, the derivative of the second mixer drive frequency in this case takes place by mixing with 2 * ⁇ or 2n * ⁇ in the case of splitting the oscillator signals Downsizing, by means of the division factor n, the mixer drive frequencies are generated.
  • the generation of the offset by 90 ° mixer drive signals by divider stages at the outputs of Summing or subtracting stages 272, 282 are made.
  • the division ratio can be chosen so high that the remaining at the outputs of the stages 272, 282 noise components are sufficiently lowered and thereby a sufficient immunity to interference can be achieved.
  • the harmonics of the local oscillator signals also contribute to the mixture and can lead to secondary reception points at integer multiples of the reception frequency.
  • this effect is counteracted by first mixing the received signal using a VCO to a fixed intermediate frequency, preferably far above the receiving frequency, where the unwanted mixing products of the harmonics and image frequency reception can be eliminated with simple filter measures, and Only then, in further processing stages, the above-described segmented mixture takes place at 0 Hz.
  • the second mixture does not require a second variable frequency oscillator corresponding to block 261, since the intermediate frequency remains constant, a fixed output frequency oscillator can be used and mixed with the signal of oscillator 263 in the manner previously described.
  • an adjustment of the oscillator mixer can be done by measuring the Störitati-level.
  • the mixer inputs are switched off, so that no received signal is passed through the mixing stages.
  • the oscillator residues and interference lines due to mirror carrier and VCO throughput are present at the mixer outputs. The strength of these signals can be detected and minimized by balancing the signal levels.
  • a compensation of the oscillator-mixer imbalance can be made.
  • the spurious signals resulting from residues of the mirror carrier and / or VCO throughput are preferably eliminated in the digital part by antiphase addition.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Superheterodyne Receivers (AREA)

Abstract

La présente invention concerne un récepteur radio (200), le signal de réception étant traité parallèlement dans au moins deux trajectoires, une première trajectoire se caractérisant par un premier signal d'oscillateur mixte de valeur supérieure au milieu de canal, et une seconde trajectoire se caractérisant par un second signal d'oscillateur mixte de valeur inférieure au milieu de canal. Selon l'invention, des filtres sont utilisés pour extraire par filtrage des composantes spectrales, puis les signaux sont traités et/ou rassemblés de manière appropriée.
EP07802571A 2006-09-25 2007-08-10 Récepteur radio Withdrawn EP2070189A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102006045160A DE102006045160A1 (de) 2006-09-25 2006-09-25 Funkempfänger
PCT/EP2007/058319 WO2008037539A1 (fr) 2006-09-25 2007-08-10 Récepteur radio

Publications (1)

Publication Number Publication Date
EP2070189A1 true EP2070189A1 (fr) 2009-06-17

Family

ID=38671023

Family Applications (1)

Application Number Title Priority Date Filing Date
EP07802571A Withdrawn EP2070189A1 (fr) 2006-09-25 2007-08-10 Récepteur radio

Country Status (7)

Country Link
US (1) US20100015940A1 (fr)
EP (1) EP2070189A1 (fr)
JP (1) JP2010504713A (fr)
CN (1) CN101517889B (fr)
DE (1) DE102006045160A1 (fr)
RU (1) RU2009115443A (fr)
WO (1) WO2008037539A1 (fr)

Families Citing this family (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN105245246B (zh) * 2014-07-08 2018-08-10 中国移动通信集团公司 一种全双工无线通信系统消除自干扰的方法与接收机
CN108362941B (zh) * 2018-03-29 2023-07-18 珠海迈科智能科技股份有限公司 一种测试Tuner模组晶振频偏的设备及方法
US10833711B2 (en) * 2018-12-19 2020-11-10 Silicon Laboratories Inc. System, apparatus and method for concurrent reception of multiple channels spaced physically in radio frequency spectrum

Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20010021234A1 (en) * 1997-05-13 2001-09-13 Matsushita Electric Industrial Co., Ltd. Portable radio device with direct conversion receiver including mixer down-converting incoming signal, and demodulator operating on downconverted signal

Family Cites Families (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE3618782A1 (de) * 1986-06-04 1987-12-10 Blaupunkt Werke Gmbh Hochfrequenzempfaenger mit einer digitalen anzeige der empfangsfrequenz
GB2214014A (en) * 1987-12-18 1989-08-23 Philips Electronic Associated Signal receiving arrangement
DE19525844C2 (de) * 1995-07-15 1998-08-13 Telefunken Microelectron Verfahren zur Frequenzumsetzung
US6574462B1 (en) * 1999-08-25 2003-06-03 Analog Devices, Inc. Local oscillator apparatus for radio frequency communication systems
DE60025458T2 (de) * 2000-10-30 2006-09-28 Texas Instruments Inc., Dallas Verfahren zur Schätzung und Entfernung eines zeitvarianten DC-Offsets
FR2843249A1 (fr) * 2002-07-31 2004-02-06 Koninkl Philips Electronics Nv Recepteur comportant des moyens de reception multiples en parallele.
DE60310569T2 (de) * 2002-08-08 2007-10-04 Koninklijke Philips Electronics N.V. Mischeranordnung unter verwendung von einigen oszillatoren und darauf basierenden systemen
US7583946B2 (en) * 2003-09-29 2009-09-01 Silicon Laboratories, Inc. Wireless communication system and method using clock swapping during image rejection calibration
JP4409423B2 (ja) * 2004-12-20 2010-02-03 ティーオーエー株式会社 Ａｍ受信機

Patent Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20010021234A1 (en) * 1997-05-13 2001-09-13 Matsushita Electric Industrial Co., Ltd. Portable radio device with direct conversion receiver including mixer down-converting incoming signal, and demodulator operating on downconverted signal

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
See also references of WO2008037539A1 *

Also Published As

Publication number Publication date
DE102006045160A1 (de) 2008-04-03
CN101517889B (zh) 2012-09-05
JP2010504713A (ja) 2010-02-12
CN101517889A (zh) 2009-08-26
RU2009115443A (ru) 2010-11-10
WO2008037539A1 (fr) 2008-04-03
US20100015940A1 (en) 2010-01-21

Similar Documents

Publication Publication Date Title
DE69834875T2 (de) Frequenzumsetzungsschaltung
DE2902952C2 (de) Direktmischendes Empfangssystem
EP0255553B1 (fr) Méthode pour la réception de signaux stéréo multiplex modulés en fréquence
DE4236546C1 (de) Homodynempfänger und Verfahren zur direkten Konvertierung
EP2286259A1 (fr) Récepteur à bande multifréquence
DE3784930T2 (de) Empfaenger mit zwei zweigen.
DE102021209433A1 (de) Signalempfänger, der Digitalbildsignaltrennung umfasst
DE102005015093A1 (de) Testsignal-Erzeugungsschaltung und Empfangsschaltung
EP1782085B1 (fr) Procede pour mesurer le bruit de phase d'un signal haute frequence et appareil de mesure permettant de mettre en oeuvre ce procede
WO1994010756A1 (fr) Recepteur homodyne et procede permettant de corriger le signal de reception converti
DE3779638T2 (de) Empfaenger mit parallelen signalstrecken.
DE3506778A1 (de) Mehrfachueberlagerungsempfaenger
DE2657170A1 (de) Schaltungsanordnung zum empfang eines der seitenbaender aus einem zweiseitenbandsignal
DE60315960T2 (de) Verfahren und vorrichtung zur analog-/digital-umsetzung
DE102005013497B4 (de) Steuerbare Frequenzteilerschaltung, Sende-Empfänger mit steuerbarer Frequenzteilerschaltung und Verfahren zur Durchführung eines Loop-Back-Tests
DE60206288T2 (de) Mischerschaltung mit spiegelfrequenzunterdrückung , und deren verwendung in einem direktkonversionsempfänger
WO2008037539A1 (fr) Récepteur radio
DE4306578C2 (de) Verfahren und Schaltungsanordnung zum Empfang von HF-Signalen unter Verwendung eines Doppelüberlagerungsempfängers
EP0755125B1 (fr) Procédé pour la réduction des postes supplémentaires de réception dans des récepteurs homodynes avec la fréquence porteuse variable en temps
DE10122830A1 (de) Abwärts-Mischeinrichtung
DE60217519T2 (de) Empfänger
EP0356555B1 (fr) Procédé et montage de circuit pour déterminer la présence ou non d'au moins une fréquence d'une valeur connue dans un signal d'entrée composé de plusieurs fréquences
DE3412191C2 (fr)
DE19523433C2 (de) Schaltungsanordnung zur Frequenzumsetzung
EP0185414B1 (fr) Récepteur FM stéréophonique

Legal Events

Date Code Title Description
PUAI Public reference made under article 153(3) epc to a published international application that has entered the european phase

Free format text: ORIGINAL CODE: 0009012

17P Request for examination filed

Effective date: 20090427

AK Designated contracting states

Kind code of ref document: A1

Designated state(s): AT BE BG CH CY CZ DE DK EE ES FI FR GB GR HU IE IS IT LI LT LU LV MC MT NL PL PT RO SE SI SK TR

AX Request for extension of the european patent

Extension state: AL BA HR MK RS

17Q First examination report despatched

Effective date: 20110210

DAX Request for extension of the european patent (deleted)
STAA Information on the status of an ep patent application or granted ep patent

Free format text: STATUS: THE APPLICATION IS DEEMED TO BE WITHDRAWN

18D Application deemed to be withdrawn

Effective date: 20180410