EP1916764B1 - Method and apparatus for compensating for mismatch occurring in radio frequency quadrature transceiver - Google Patents

Method and apparatus for compensating for mismatch occurring in radio frequency quadrature transceiver Download PDF

Info

Publication number
EP1916764B1
EP1916764B1 EP07108865.2A EP07108865A EP1916764B1 EP 1916764 B1 EP1916764 B1 EP 1916764B1 EP 07108865 A EP07108865 A EP 07108865A EP 1916764 B1 EP1916764 B1 EP 1916764B1
Authority
EP
European Patent Office
Prior art keywords
signal
baseband
module
phase
quadrature
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Fee Related
Application number
EP07108865.2A
Other languages
German (de)
English (en)
French (fr)
Other versions
EP1916764A3 (en
EP1916764A2 (en
Inventor
Pil-Soon Choi
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Samsung Electronics Co Ltd
Original Assignee
Samsung Electronics Co Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Samsung Electronics Co Ltd filed Critical Samsung Electronics Co Ltd
Publication of EP1916764A2 publication Critical patent/EP1916764A2/en
Publication of EP1916764A3 publication Critical patent/EP1916764A3/en
Application granted granted Critical
Publication of EP1916764B1 publication Critical patent/EP1916764B1/en
Expired - Fee Related legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
    • H03D3/00—Demodulation of angle-, frequency- or phase- modulated oscillations
    • H03D3/007—Demodulation of angle-, frequency- or phase- modulated oscillations by converting the oscillations into two quadrature related signals
    • H03D3/009—Compensating quadrature phase or amplitude imbalances
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/005—Control of transmission; Equalising
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
    • H04L27/20—Modulator circuits; Transmitter circuits
    • H04L27/2032—Modulator circuits; Transmitter circuits for discrete phase modulation, e.g. in which the phase of the carrier is modulated in a nominally instantaneous manner
    • H04L27/2053—Modulator circuits; Transmitter circuits for discrete phase modulation, e.g. in which the phase of the carrier is modulated in a nominally instantaneous manner using more than one carrier, e.g. carriers with different phases
    • H04L27/206—Modulator circuits; Transmitter circuits for discrete phase modulation, e.g. in which the phase of the carrier is modulated in a nominally instantaneous manner using more than one carrier, e.g. carriers with different phases using a pair of orthogonal carriers, e.g. quadrature carriers
    • H04L27/2067—Modulator circuits; Transmitter circuits for discrete phase modulation, e.g. in which the phase of the carrier is modulated in a nominally instantaneous manner using more than one carrier, e.g. carriers with different phases using a pair of orthogonal carriers, e.g. quadrature carriers with more than two phase states
    • H04L27/2089—Modulator circuits; Transmitter circuits for discrete phase modulation, e.g. in which the phase of the carrier is modulated in a nominally instantaneous manner using more than one carrier, e.g. carriers with different phases using a pair of orthogonal carriers, e.g. quadrature carriers with more than two phase states with unbalanced quadrature channels
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H04L27/36—Modulator circuits; Transmitter circuits
    • H04L27/362—Modulation using more than one carrier, e.g. with quadrature carriers, separately amplitude modulated
    • H04L27/364—Arrangements for overcoming imperfections in the modulator, e.g. quadrature error or unbalanced I and Q levels
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H04L27/38—Demodulator circuits; Receiver circuits
    • H04L27/3845—Demodulator circuits; Receiver circuits using non - coherent demodulation, i.e. not using a phase synchronous carrier
    • H04L27/3854—Demodulator circuits; Receiver circuits using non - coherent demodulation, i.e. not using a phase synchronous carrier using a non - coherent carrier, including systems with baseband correction for phase or frequency offset
    • H04L27/3863—Compensation for quadrature error in the received signal
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H04L27/38—Demodulator circuits; Receiver circuits
    • H04L27/3809—Amplitude regulation arrangements

Definitions

  • Methods and apparatuses consistent with the present invention relate to a radio frequency (RF) quadrature transceiver, and more particularly, to compensating for a mismatch occurring in an RF quadrature transceiver based on a direct-conversion scheme.
  • RF radio frequency
  • a direction conversion method not using an intermediate frequency band uses an in-phase carrier signal and a quadrature-phase carrier signal that have a phase difference of 90 degrees.
  • a phase difference between the two signals is not exactly 90 degrees, or a mismatch between the overall gains obtained by the paths of the two signals is generated, signal distortion can occur - see e.g. document US 2003/223480 . Accordingly, research into a method of efficiently and accurately compensating for a phase mismatch and a gain mismatch has been conducted.
  • Figures 1A and 1B are schematic diagrams illustrating structures of related art radio frequency (RF) quadrature transceivers.
  • Figure 1A illustrates a related art radio frequency integrated circuit (RFIC) manufactured by Athena Semiconductors, Inc., in which a feedback loop is established between a transmission module and a reception module, and thus a phase mismatch and a gain mismatch are compensated for by using a predetermined algorithm after a signal transmitted by the transmission module is directly received by the reception module.
  • the RFIC of Figure 1A must include a special envelope detector in order to achieve this mismatch compensation, and the reception module must perform a complicated digital signal processing operation using a signal received via the envelope detector.
  • Figure 1B illustrates a related art RFIC manufactured by Atheros Communications Inc.
  • This RFIC employs a 2-stage conversion scheme, such that signals having a phase difference of 90 degrees are not used in an RF band and a quadrature signal is generated in a frequency band (e.g., 1/4 of a carrier frequency band) lower than the RF band. Therefore, the 2-stage conversion scheme generates fewer phase errors and fewer gain errors than when employing the direct conversion scheme.
  • the compensation method of Figure 1B also cannot completely prevent generations of a phase mismatch and a gain mismatch. Rather, the use of an intermediate frequency causes an image frequency problem.
  • the 2-stage conversion scheme requires more mixers and more LO2 generation circuits than the other schemes. Accordingly, the RFIC employing the 2-stage conversion scheme consumes much power and has a large size.
  • Exemplary embodiments of the present invention overcome the above disadvantages and other disadvantages not described above. Also, the present invention is not required to overcome the disadvantages described above, and an exemplary embodiment of the present invention may not overcome any of the problems described above.
  • Exemplary embodiments of the present invention provide an apparatus and method of compensating for a phase mismatch and a gain mismatch, by which a radio frequency (RF) quadrature transceiver using a general direct-conversion scheme does not include an additional circuit and does not need to perform a complicated digital signal processing operation.
  • RF radio frequency
  • the signal processing method may further comprise setting amplification gain control signals for baseband signals of one of the reception module and the transmission module to be the same, and setting amplification gain control signals for baseband signals of the other module to be a first value; inputting identical signals to an in-phase input port and a quadrature input port of the transmission module and measuring amplitudes of baseband signals output from the reception module; setting the amplification gain control signals for the baseband signals of the other module to be a second value, re-inputting the identical signals to the in-phase input port and the quadrature input port of the transmission module, and measuring the amplitudes of baseband signals output from the reception module; calculating a gain mismatch between an in-phase path and a quadrature path of the one module on the basis of the amplitudes measured for the first value and the second value; and compensating for the gain mismatch of the one module on a basis of a result of the calculation.
  • the signal processing method may further comprise inputting identical signals to the in-phase input port and the quadrature input port of the transmission module, comparing the amplitudes of baseband signals output from the reception module, and compensating for a gain mismatch of the other module according to a result of the comparison.
  • Carrier signals used in the transmission module and the reception module may be generated by a frequency divider comprised of two cross-coupled latches. Compensating for the phase mismatch may comprise controlling a phase difference between the two carrier signals by independently controlling main currents of the latches of the frequency divider.
  • radio frequency quadrature transceiver according to Claim 7.
  • FIG. 2 is a flowchart of a method of compensating for a mismatch occurring in a radio frequency (RF) quadrature transceiver, according to an exemplary embodiment of the present invention.
  • RF radio frequency
  • a gain mismatch of a transmission (or reception) module is compensated for in operation 220, and a gain mismatch of the reception (or transmission) module is compensated for in operation 230.
  • a gain mismatch of the transmission and reception modules is compensated for in operation 220.
  • a gain mismatch of the reception (or transmission) module is compensated for in operation 230.
  • FIG. 3 is a block diagram of an RF quadrature transceiver according to an exemplary embodiment of the present invention.
  • the RF quadrature transceiver according to an exemplary embodiment of the present invention includes a reception module 310, a transmission module 320, a phase mismatch compensator 330, a local oscillator 340, and a gain mismatch compensator 350.
  • the reception module 310 converts an RF signal into a baseband signal
  • the transmission module 320 converts a baseband signal into an RF signal.
  • the reception module 310 and the transmission module 320 can independently control the amplification gains of a baseband in-phase signal and a baseband quadrature signal according to a gain control signal.
  • the local oscillator 340 generates an RF carrier signal. More specifically, the local oscillator 340 generates an RF signal with a frequency, which may be predetermined, and adjusts the frequency of the RF signal using a frequency divider (not shown) to thereby generate the RF carrier signal. This will be described in greater detail later with reference to Figures 9A through 9C .
  • the phase mismatch compensator 330 performs phase mismatch compensation by controlling the local oscillator 340.
  • the gain mismatch compensator 350 performs gain mismatch compensation by controlling the reception module 310 and the transmission module 320.
  • the phase mismatch compensator 330 and the gain mismatch compensator 350 establish a feedback path that allows the reception module 310 to directly receive a signal transmitted by the transmission module 320. To obtain this feedback path, an RF output port of the transmission module 320 and an RF input port of the reception module 310 are short-circuited. This will be described in greater detail later.
  • FIG 4 is a schematic diagram of a structure of an RF quadrature transceiver according to an exemplary embodiment of the present invention.
  • the RF quadrature transceiver according to an exemplary embodiment of the present invention is illustrated including a reception module 410 and a transmission module 420.
  • a phase mismatch compensator and a gain mismatch compensator are not illustrated, it will be understood by one of ordinary skill in the art that the RF quadrature transceiver of Figure 4 may be implemented in various forms according to the following description.
  • baseband signals I tx and Q tx pass through low pass filters (LPFs) in order to remove noise in other bands from the baseband signals I tx and Q tx .
  • the baseband signals I tx and Q tx are amplified by amplifiers and modulated by mixers using carrier signals LO_I and LO_Q, respectively, so as to be converted into RF signals.
  • the reception module 410 performs a process opposite to the process performed in the transmission module 420. In other words, in the reception module 410, received RF signals are demodulated by mixers so as to be converted into baseband signals, and the baseband signals pass through LPFs and are then amplified by variable gain amplifiers (VGAs).
  • VGAs variable gain amplifiers
  • amplification gains of the variable gain amplifiers that are respectively used on the paths of a baseband in-phase signal and a baseband quadrature signal can be controlled independently in each of the transmission and reception modules 420 and 410, and a phase mismatch and a gain mismatch are compensated for by using the amplification gains. This will now be described in greater detail.
  • FIG. 5 is a flowchart of a phase mismatch compensating method performed in the RF quadrature transceiver of Figure 4 , according to an exemplary embodiment of the present invention.
  • control signals for the variable amplifiers of the reception module 410 are set so as to be different, and an amplification gain G rx_q for a baseband quadrature signal Q rx is set so as to be much larger than an amplification gain G rx_i for a baseband in-phase signal I rx .
  • a switch SW for short-circuiting the RF output port of the transmission module 420 and the RF input port of the reception module 410 is closed so that the RF signals output from the transmission module 420 are input to the reception module 410, and the transmission module 420 only receives a baseband in-phase signal I tx . In other words, the transmission module 420 does not receive a baseband quadrature signal Qtx.
  • the reception module 410 estimates the baseband quadrature signal Q rx from the baseband in-phase signal I tx received in operation 520.
  • the phase mismatch is compensated for on the basis of the estimated amplitude of the baseband quadrature signal Q rx .
  • the baseband quadrature signal Q rx estimated in the reception module 410 is an amplification of noise generated only due to a phase mismatch, such that even a very small phase mismatch can be easily detected and compensated for, and the resolution of phase mismatch compensation can be increased. This will now be described in greater detail with reference to the following equations.
  • the baseband quadrature signal Q rx corresponds to noise generated due to a phase mismatch ⁇ . Since the control signal G rx_q is set to be larger than G rx_i in operation 510, even if the phase mismatch ⁇ is very small, the phase mismatch e is easily detected and compensated for because the phase mismatch ⁇ undergoes amplification. This effect is illustrated in Figures 6A and 6B .
  • Figures 6A and 6B are graphs illustrating an efficiency comparison between the method of Figure 5 and a related art phase mismatch compensating method.
  • Figures 6A and 6B illustrate the amplitudes of baseband signals estimated in reception modules when transmission modules only receive baseband in-phase signals as in the exemplary embodiment of Figure 5 .
  • Figure 6A corresponds to a related art case where G rx_q is set to be equal to G rx_i
  • Figure 6B corresponds to a case according to an exemplary embodiment of the present invention where G rx_q is set to be greater than G rx_i .
  • quadrature signals shown in Figures 6A and 6B correspond to noise generated due to phase mismatch.
  • FIG 7 is a flowchart of a gain mismatch compensating method performed in the RF quadrature transceiver of Figure 4 , according to an exemplary embodiment of the present invention.
  • the compensation of the gain mismatch according to an exemplary embodiment of the present invention may be performed after the compensation of the phase mismatch illustrated in Figure 5 is completed.
  • the baseband in-phase signal I tx whose phase mismatch has been compensated for and which is input to the transmission module 420 does not affect the quadrature signal Q rx output from the reception module 410.
  • the quadrature signal Q rx output from the reception module 410 does not affect the baseband in-phase signal I tx whose phase mismatch has been compensated for and which is input to the transmission module 420.
  • a gain mismatch compensator (not shown) of the RF quadrature transceiver of Figure 4 calculates a gain mismatch using the fact that, although a gain of an in-phase signal path and a gain of a quadrature signal path may be different at a specific value of a control signal, that is, a gain mismatch may occur, variation rates of the gains of the in-phase signal path and quadrature signal path according to a change of the control signal are identical.
  • a control signal for the amplification gain G tx_i for the baseband in-phase signal I tx of the transmission module 420 and a control signal for the amplification gain G tx_q for the baseband quadrature signal Q tx of the transmission module 420 are set to be the same.
  • a control signal for the amplification gain G rx_i of the baseband in-phase signal I rx of the reception module 410 and a control signal for the amplification gain G rx_q of the baseband quadrature signal Q rx of the reception module 410 are each set to a first value.
  • identical baseband signals I tx and Q tx are input to two input ports of the transmission module 420, and the baseband in-phase signal I rx and the baseband quadrature signal Q rx for the input baseband signals, which are output from the reception module 410, are measured.
  • control signal for the amplification gains G rx_i of the baseband in-phase signal I rx of the reception module 410 and the control signal for the amplification gain G rx_q of the baseband quadrature signal Q rx of the reception module 410 are each set to a second value.
  • the same baseband signals as the input signals used in operation 710 are input to the two input ports of the transmission module 420, and the baseband in-phase signal I rx and the baseband quadrature signal Q rx for the input baseband signals, which are output from the reception module 410, are further measured.
  • a gain mismatch between the baseband in-phase signal and the baseband quadrature signal generated in the transmission module 420 is calculated using the measured values of the baseband in-phase signal and baseband quadrature signal output from the reception module 410.
  • the gain mismatch is compensated for on a basis of a result of the calculation performed in operation 730. The calculation of the gain mismatch will now be described in greater detail.
  • I rx a - I rx b I tx ⁇ G tx_i ⁇ G rx_i a - G rx_i b
  • Q rx a - Q rx b Q tx ⁇ G tx_q ⁇ G rx_q a - G rx_q b
  • control signal for the amplification gain G tx_i for the baseband in-phase signal I tx of the transmission module 420 and the control signal for the amplification gain G tx_q for the baseband quadrature signal Q tx of the transmission module 420 have been set to be the same in operation 700, if k is not 1, then a gain mismatch has been generated.
  • the gain mismatch generated in the transmission module 420 is compensated for by suitably adjusting the gain control signals of the variable amplifiers of the transmission module 420 on the basis of the value k.
  • a gain mismatch of the reception module 410 can be simply compensated for in operations 731, 735, and 740.
  • identical baseband signals are input to the two input ports of the transmission module 420 in operation 731.
  • the same baseband signals as the signals input in operations 710 and 720 are input in operation 731.
  • arbitrary signals may be input in operation 731 as long as identical baseband signals are input to the two input ports of the transmission module 420.
  • the amplitudes of the baseband in-phase signal and baseband quadrature signal output from the reception module 410 are compared.
  • the gain control signals for the amplifiers of the reception module 410 are adequately controlled according to a result of the comparison.
  • the gain mismatch of the transmission module 420 is first compensated, and the gain mismatch of the reception module 410 is thereafter compensated.
  • the order of compensations may be switched. That is, the gain mismatch of the reception module 410 may be compensated for first, and then the gain mismatch of the transmission module 420 may be compensated.
  • Figures 8A through 8C are graphs illustrating an algorithm for estimating a value of a gain mismatch, according to an exemplary embodiment of the present invention.
  • Figure 8A illustrates a gain of an in-phase signal path and a gain of a quadrature signal path versus a change of a gain control signal applied to a variable gain amplifier.
  • the gains of the two paths may be different at a specific value of the gain control signal, but the variation rates of the gains, that is, the slopes of the straight lines representing the gain variations, are the same.
  • Figures 8B and 8C are graphs showing the amplitudes of the baseband signals I rx and Q rx , respectively, output from the reception module 410, according to variations of the gain control signals. As illustrated in Figures 8A and 8B , the two graphs have different slopes. However, the value of the gain mismatch can be obtained using the characteristic that the slopes of the graphs illustrating the gain variations are the same.
  • FIGS 9A through 9C are schematic diagrams of an apparatus for compensating for a phase mismatch, according to an exemplary embodiment of the present invention.
  • an oscillator VCO generates an RF signal
  • a frequency divider 900 generates carrier signals having frequencies corresponding a fraction of the RF signal.
  • the frequency divider 900 may generate carrier signals having frequencies corresponding to 1/2 the frequency of the RF signal.
  • Figure 9B illustrates the frequency divider 900, which includes cross-coupled latches 910, 920.
  • Figure 9C is a circuit diagram of one of the latches illustrated in Figure 9B .
  • a phase mismatch compensator according to an exemplary embodiment of the present invention controls the difference between the phases of the two carrier signals output from the frequency divider 900, by independently adjusting the main currents of the two latches using a bias.
  • FIGS 10A and 10B are a circuit diagram and a waveform diagram for explaining a method of compensating for a phase mismatch, according to another exemplary embodiment of the present invention.
  • an I signal and a Q signal output from two cross-coupled latches 1010, 1020 correspond to carrier signals having frequencies corresponding to, for example, 1/2 a clock frequency.
  • the phase mismatch compensator according to an exemplary embodiment of the present invention controls the difference between the phases of the two carrier signals by adjusting independently the main currents of the two latches.
  • the phase mismatch can be compensated for by independently controlling the phases of the I and Q signals.
  • a phase mismatch and a gain mismatch generated therein are accurately compensated for without depending on a special external circuit or a complicated algorithm. Therefore, the RF quadrature transceiver according to exemplary embodiments of the present invention provide improved performance.
  • Exemplary embodiments of the present invention can be implemented in digital signal processing (DSP) modules or microcomputers by converting the baseband signals input to the input ports of the transmission module and/or the baseband signals output from the output ports of the reception module into digital signals.
  • DSP digital signal processing
  • exemplary embodiments of the present invention can be written as programs that can be executed in the DSP modules or microcomputers.
  • exemplary embodiments of the present invention can be implemented in computers that execute the programs using a computer readable recording medium.
  • the computer readable recording medium include magnetic storage media (e.g., ROM, floppy disks, hard disks, etc.), optical recording media (e.g., CD-ROMs, or DVDs), and storage media such as carrier waves (e.g., transmission through the Internet).

Landscapes

  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Power Engineering (AREA)
  • Transceivers (AREA)
  • Digital Transmission Methods That Use Modulated Carrier Waves (AREA)
  • Circuits Of Receivers In General (AREA)
EP07108865.2A 2006-10-27 2007-05-24 Method and apparatus for compensating for mismatch occurring in radio frequency quadrature transceiver Expired - Fee Related EP1916764B1 (en)

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
KR1020060105040A KR101261527B1 (ko) 2006-10-27 2006-10-27 직접 변환 구조의 ｒｆ 쿼드러쳐 송수신기에서 부정합을보상하는 방법 및 장치

Publications (3)

Publication Number Publication Date
EP1916764A2 EP1916764A2 (en) 2008-04-30
EP1916764A3 EP1916764A3 (en) 2012-10-24
EP1916764B1 true EP1916764B1 (en) 2013-11-20

Family

ID=39099800

Family Applications (1)

Application Number Title Priority Date Filing Date
EP07108865.2A Expired - Fee Related EP1916764B1 (en) 2006-10-27 2007-05-24 Method and apparatus for compensating for mismatch occurring in radio frequency quadrature transceiver

Country Status (5)

Country Link
US (1) US7813424B2 (zh)
EP (1) EP1916764B1 (zh)
JP (1) JP5068109B2 (zh)
KR (1) KR101261527B1 (zh)
CN (1) CN101170537B (zh)

Families Citing this family (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20090079497A1 (en) * 2007-09-21 2009-03-26 Nanoamp Solutions, Inc. (Cayman) Phase tuning techniques
US8694409B2 (en) * 2008-09-29 2014-04-08 Battelle Memorial Institute Using bi-directional communications in a market-based resource allocation system
KR20110034433A (ko) 2009-09-28 2011-04-05 삼성전자주식회사 Ｉ/ｑ 부정합을 보상하는 발진 신호 발생기 및 이를 포함하는 통신 시스템
CN102340467B (zh) * 2011-05-19 2014-06-04 乐鑫信息科技（上海）有限公司 一种调制解调器失配的校准方法
US8639206B1 (en) * 2012-10-05 2014-01-28 Telefonaktiebolaget L M Ericsson (Publ) Method and apparatus for quadrature mixer circuits
CN103795435B (zh) * 2013-12-30 2015-10-28 北京星河亮点技术股份有限公司 一种镜频抑制方法和装置
US10374838B2 (en) * 2017-06-30 2019-08-06 Futurewei Technologies, Inc. Image distortion correction in a wireless terminal
US10749555B2 (en) * 2018-09-26 2020-08-18 Samsung Electronics Co., Ltd. Time-domain IQ mismatch compensator with frequency-domain observations

Family Cites Families (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4717894A (en) * 1986-10-23 1988-01-05 Hewlett-Packard Company Calibration of vector modulators using a scalar detector
US5579347A (en) * 1994-12-28 1996-11-26 Telefonaktiebolaget Lm Ericsson Digitally compensated direct conversion receiver
JPH09186729A (ja) * 1996-01-08 1997-07-15 Hitachi Denshi Ltd 直交変調器および直交復調器の振幅誤差制御方法
US6009317A (en) * 1997-01-17 1999-12-28 Ericsson Inc. Method and apparatus for compensating for imbalances between quadrature signals
US7346313B2 (en) * 2002-03-04 2008-03-18 Cafarella John H Calibration of I-Q balance in transceivers
TW200501611A (en) * 2003-03-12 2005-01-01 Koninkl Philips Electronics Nv Transceiver with mismatch compensation scheme
DE602004025561D1 (de) * 2003-04-24 2010-04-01 Nxp Bv Quadraturmodulator und kalibrierungsverfahren dafür
US7412006B2 (en) * 2003-07-24 2008-08-12 Freescale Semiconductor, Inc. Method and apparatus for RF carrier feedthrough suppression
JP4381945B2 (ja) * 2004-09-30 2009-12-09 株式会社ルネサステクノロジ 受信機、受信方法及び携帯無線端末
US20060133548A1 (en) * 2004-12-17 2006-06-22 Joungheon Oh Apparatus and method to calibrate amplitude and phase imbalance for communication receivers

Also Published As

Publication number Publication date
US20080151977A1 (en) 2008-06-26
KR20080037846A (ko) 2008-05-02
CN101170537B (zh) 2011-12-21
KR101261527B1 (ko) 2013-05-06
JP2008113411A (ja) 2008-05-15
CN101170537A (zh) 2008-04-30
EP1916764A3 (en) 2012-10-24
US7813424B2 (en) 2010-10-12
EP1916764A2 (en) 2008-04-30
JP5068109B2 (ja) 2012-11-07

Similar Documents

Publication Publication Date Title
EP1916764B1 (en) Method and apparatus for compensating for mismatch occurring in radio frequency quadrature transceiver
EP1860770B1 (en) Distortion compensating apparatus and method
US8526896B2 (en) Feedback compensation detector for a direct conversion transmitter
JP4573062B2 (ja) 位相雑音補正装置及びその方法
US9749172B2 (en) Calibration method and calibration apparatus for calibrating mismatch between first signal path and second signal path of transmitter/receiver
US8750441B2 (en) Signal cancellation to reduce phase noise, period jitter, and other contamination in local oscillator, frequency timing, or other timing generators or signal sources
EP1667331B1 (en) Amplifier circuit and amplifying method
US9948347B2 (en) Calibrating a transceiver circuit
US8867596B2 (en) Methods and apparatuses of calibrating I/Q mismatch in communication circuit
US9385656B2 (en) Low complexity frequency selective IQ mismatch digital RX balancer and TX inverse balancer for non-ideal RF front-end
CN112291173B (zh) 一种iq不平衡系数获取方法及装置、可读存储介质
US20050152481A1 (en) Method and apparatus of iq mismatch calibration
KR100847801B1 (ko) Ｉｑ 불일치 측정 장치 및 방법
WO2011086640A1 (ja) 送信装置、無線通信装置及び送信方法
Khandelwal et al. A novel gain, phase and offset calibration scheme for wideband direct-conversion transmitters
US8064863B1 (en) Image rejection calibration
US10230408B2 (en) Measurement receiver harmonic distortion cancellation
JP5834577B2 (ja) 直交信号生成回路、直交信号生成回路の調整方法、及び無線通信装置
EP3151500B1 (en) Frequency-selective quadrature baseband coupling cancellation
US20180083823A1 (en) Transmission and reception circuit, transceiver, and method of correcting time difference of signal
JP2003087344A (ja) ダイレクトコンバージョン受信機

Legal Events

Date Code Title Description
PUAI Public reference made under article 153(3) epc to a published international application that has entered the european phase

Free format text: ORIGINAL CODE: 0009012

17P Request for examination filed

Effective date: 20070524

AK Designated contracting states

Kind code of ref document: A2

Designated state(s): AT BE BG CH CY CZ DE DK EE ES FI FR GB GR HU IE IS IT LI LT LU LV MC MT NL PL PT RO SE SI SK TR

AX Request for extension of the european patent

Extension state: AL BA HR MK RS

RAP1 Party data changed (applicant data changed or rights of an application transferred)

Owner name: SAMSUNG ELECTRONICS CO., LTD.

PUAL Search report despatched

Free format text: ORIGINAL CODE: 0009013

AK Designated contracting states

Kind code of ref document: A3

Designated state(s): AT BE BG CH CY CZ DE DK EE ES FI FR GB GR HU IE IS IT LI LT LU LV MC MT NL PL PT RO SE SI SK TR

AX Request for extension of the european patent

Extension state: AL BA HR MK RS

RIC1 Information provided on ipc code assigned before grant

Ipc: H03D 3/00 20060101AFI20120919BHEP

Ipc: H04L 27/36 20060101ALI20120919BHEP

Ipc: H04L 27/38 20060101ALI20120919BHEP

REG Reference to a national code

Ref country code: DE

Ref legal event code: R079

Ref document number: 602007033855

Country of ref document: DE

Free format text: PREVIOUS MAIN CLASS: H03D0003000000

Ipc: H04L0027200000

GRAP Despatch of communication of intention to grant a patent

Free format text: ORIGINAL CODE: EPIDOSNIGR1

RIC1 Information provided on ipc code assigned before grant

Ipc: H04L 27/36 20060101ALI20130507BHEP

Ipc: H04L 27/38 20060101ALI20130507BHEP

Ipc: H04L 27/20 20060101AFI20130507BHEP

Ipc: H03D 3/00 20060101ALI20130507BHEP

AKX Designation fees paid

Designated state(s): DE FR GB

INTG Intention to grant announced

Effective date: 20130612

GRAS Grant fee paid

Free format text: ORIGINAL CODE: EPIDOSNIGR3

GRAA (expected) grant

Free format text: ORIGINAL CODE: 0009210

AK Designated contracting states

Kind code of ref document: B1

Designated state(s): DE FR GB

REG Reference to a national code

Ref country code: GB

Ref legal event code: FG4D

REG Reference to a national code

Ref country code: DE

Ref legal event code: R096

Ref document number: 602007033855

Country of ref document: DE

Effective date: 20140116

REG Reference to a national code

Ref country code: DE

Ref legal event code: R097

Ref document number: 602007033855

Country of ref document: DE

PLBE No opposition filed within time limit

Free format text: ORIGINAL CODE: 0009261

STAA Information on the status of an ep patent application or granted ep patent

Free format text: STATUS: NO OPPOSITION FILED WITHIN TIME LIMIT

26N No opposition filed

Effective date: 20140821

REG Reference to a national code

Ref country code: DE

Ref legal event code: R097

Ref document number: 602007033855

Country of ref document: DE

Effective date: 20140821

REG Reference to a national code

Ref country code: FR

Ref legal event code: ST

Effective date: 20150130

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: FR

Free format text: LAPSE BECAUSE OF NON-PAYMENT OF DUE FEES

Effective date: 20140602

PGFP Annual fee paid to national office [announced via postgrant information from national office to epo]

Ref country code: DE

Payment date: 20190423

Year of fee payment: 13

PGFP Annual fee paid to national office [announced via postgrant information from national office to epo]

Ref country code: GB

Payment date: 20190424

Year of fee payment: 13

REG Reference to a national code

Ref country code: DE

Ref legal event code: R119

Ref document number: 602007033855

Country of ref document: DE

GBPC Gb: european patent ceased through non-payment of renewal fee

Effective date: 20200524

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: GB

Free format text: LAPSE BECAUSE OF NON-PAYMENT OF DUE FEES

Effective date: 20200524

PG25 Lapsed in a contracting state [announced via postgrant information from national office to epo]

Ref country code: DE

Free format text: LAPSE BECAUSE OF NON-PAYMENT OF DUE FEES

Effective date: 20201201