EP1687908A1 - Procede et dispositif de connexion des systemes d'emission et de reception d'appareils radio multibandes/multimodes a une ou plusieurs antennes partagees - Google Patents

Procede et dispositif de connexion des systemes d'emission et de reception d'appareils radio multibandes/multimodes a une ou plusieurs antennes partagees

Info

Publication number
EP1687908A1
EP1687908A1 EP04766253A EP04766253A EP1687908A1 EP 1687908 A1 EP1687908 A1 EP 1687908A1 EP 04766253 A EP04766253 A EP 04766253A EP 04766253 A EP04766253 A EP 04766253A EP 1687908 A1 EP1687908 A1 EP 1687908A1
Authority
EP
European Patent Office
Prior art keywords
umts
filter
band
switch
dcs
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP04766253A
Other languages
German (de)
English (en)
Inventor
Christian Bildl
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
BenQ Mobile GmbH and Co OHG
BenQ Corp
Original Assignee
Siemens AG
BenQ Corp
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Siemens AG, BenQ Corp filed Critical Siemens AG
Publication of EP1687908A1 publication Critical patent/EP1687908A1/fr
Withdrawn legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/005—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
    • H04B1/40—Circuits
    • H04B1/403—Circuits using the same oscillator for generating both the transmitter frequency and the receiver local oscillator frequency
    • H04B1/406—Circuits using the same oscillator for generating both the transmitter frequency and the receiver local oscillator frequency with more than one transmission mode, e.g. analog and digital modes
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
    • H04B1/40—Circuits
    • H04B1/44—Transmit/receive switching
    • H04B1/48—Transmit/receive switching in circuits for connecting transmitter and receiver to a common transmission path, e.g. by energy of transmitter

Definitions

  • the present invention relates to a method and a device for connecting the transmitting and receiving devices of multiband / multimode radio devices to one or more partially shared antennas, including a filter device.
  • the present invention relates to the connection of transmitting and receiving devices, some of which are operated simultaneously.
  • - FDMA Frequency Division Multiple Access
  • TDMA Time Division Multiple Access
  • CDMA Code Division Multiple Access
  • Different users are assigned different codes; this enables simultaneous use of the same frequency - FDD (Frequency Division Duplex): transmission and reception takes place on different frequencies - TDD (Time Division Duplex): transmission and reception takes place in different time slots - full duplex system: transmission and reception occur at the same time time
  • TX transmitter; RX: receiver
  • - GSM900 TX: 880 ... 915 MHz; RX: 925 .. . 960 MHz; FDMA and TDMA; TDD and FDD
  • GMSK modulation, ie constant envelope hereinafter referred to as "GSM”
  • - GSM1800 TX: 1710 ... 1785 MHz; RX: 1805 ... 1880 MHz; otherwise identical to GSM900; hereinafter referred to as "DCS”
  • DCS - GSM1900
  • GSM850 1990 MHz; otherwise identical to GSM900; hereinafter referred to as "PCS" and - UMTS FDD ( TX: 1920 ... 1980 MHz; RX: 2110 ... 2170 MHz; FDMA and CDMA; FDD / full duplex; QPSK modulation with RRC baseband filtering, ie AM component; hereinafter referred to as "UMTS”) and optionally also - GSM850 (TX: 824 ... 849 MHz; RX: 869 ... 894 MHz; otherwise identical to GSM900; hereinafter referred to as "GSM850”) and / or - IS-95 or CDMA2000 in the 850 MHz band (TX: 824. ..
  • CDMA850 849 MHz; RX: 869 ... 894 MHz; FDMA and CDMA; FDD / full duplex lex; QPSK modulation with RRC baseband filtering, ie AM component; hereinafter referred to as "CDMA850") and / or - IS-95 or CDMA2000 in the 1900 MHz band (TX: 1850 ... 1910 MHz; RX: 1930 ... 1990 MHz; otherwise identical to "CDMA850”; hereinafter “CDMA1900 "called) and / or - UMTS TDD (TX / RX: 1900 ...
  • GSM TX GSM TX
  • UMTS RX UMTS receiver
  • GSM Global System for Mobile Communications
  • DCS and PCS EDGE 8PSK modulation with AM component
  • GMSK constant envelope, ie no AM component
  • GSM RX or DCS RX full duplex operation
  • Compressed Mode the simultaneous operation of UMTS TX and DCS RX is not intended due to the small frequency spacing and the associated high filter effort (the "compressed mode" must be used here).
  • a parallel operation of UMTS and PCS is not planned due to the different regional distribution (Europe and America).
  • No parallel operation is initially required during a GSM or DCS (or PCS) transmission because the TDD operation means that the transmitting and receiving devices are active at different times and because time slots are available for the neighboring cell monitoring as part of the TDMA operation ,
  • the time may be due to the implementation (for example, due to the software implementation or due to occupancy of too many time slots, for example, by HSCSD or GPRS) it is not sufficient to carry out a neighboring cell observation in the UMTS network in addition to the neighboring cell observation in the GSM or DCS network without parallel operation.
  • the telephone preferably has only one antenna or as few antennas as possible. Because every additional antenna increases the device volume and also makes the required antenna decoupling more difficult.
  • only one common antenna should be used for the systems / bands, for which operation with an external antenna should also be possible, e.g. when used in a vehicle. In this example, these are all GSM and UMTS bands, but not Bluetooth and WLAN. Otherwise several HF connections (e.g. coax connector or coupler) to the car kit would be necessary.
  • the RF paths in the car kit had to be merged again if the use of multiple external antennas was to be avoided. Or it had to be in some paths, e.g.
  • an external antenna is definitely required for the transmission paths in order to keep the HF power away from the vehicle interior and thus to avoid the occupants or vehicle electronics of a high level RF power are exposed.
  • the external antenna is only used for the transmission path but not for the reception path of a system / band, this leads to different link attenuations in the uplink (mobile phone to base station) and downlink (base station to mobile phone).
  • a common power amplifier 2 is used for DCS and PCS because of the proximity of the frequency bands.
  • At the output of each power amplifier there is an element for power decoupling 21, 22, 24 for power detection, e.g. B. a directional coupler, and in the UMTS path because of the AM component in the signal additionally an isolator 34 to suppress the return wave generated by mismatching the antenna.
  • an isolator may also be required in the GSM and DCS / PCS TX paths because of the AM component then also present.
  • the actual power detection is not shown here and is done e.g. B. with a Schottky diode, a second Schottky diode may be required for temperature compensation. in the
  • the GSM and DCS / PCS paths each have a low pass 41, 42 for suppressing the harmonics generated by the power amplifier, while in the UMTS path the transmit filter 44 of the duplexer 44/54, which together with the isolator 34 also takes over the function of suppressing harmonics.
  • the actual function of the duplexer, which consists of two bandpass filters 44, 54, is, however, the separation of the UMTS transmission and reception band, since it is not possible to switch between the transmitting and receiving device because of the full duplex operation.
  • a duplexer is a crossover and is created by "impedance-neutral" connection of two individual filters.
  • signals with a frequency in the pass band of one filter are hardly influenced by the other filter.
  • either filters can be developed whose stop band phase is in the idle range, or the stop band phase can be transformed into an idle by phase shifters, for example transformation lines or LC phase shifters.
  • the stop band impedance should be as reflective as possible.
  • ters can be used.
  • duplexers can also be realized monolithically.
  • the reception filter 54 of the duplexer is located in front of the UMTS-LNA 14 (LNA: low noise amplifier) as the first stage of the UMTS reception device.
  • the duplexer must have a very high isolation, namely in the TX band so that the rest of the transmission signal does not overload the LNA, and in the RX band so that the rest of the noise generated by the transmission device does not increase the system noise figure of the receiving device. Further selection requirements arise in the transmission filter due to the possibly necessary suppression of interference signals generated in the transmission device, such as e.g. B. of harmonics, image frequencies or noise in certain frequency ranges and in the reception filter by the necessary suppression of interference signals received on the antenna.
  • a bandpass filter 51, 52, 53 for interference signal suppression (the remaining part of the receiving devices is not shown here).
  • Fig. 1 all transmitting and receiving devices (via the filters described above) are connected to an SP6T switch 69. This in turn is connected to the common antenna 89.
  • the switch position of the SP6T switch 69 hangs from the currently active path, whereby only one path can be switched through at a time (UMTS TX and RX form a common path because of the duplexer). Apart from UMTS TX and RX, simultaneous operation is therefore not possible.
  • Fig. 2 shows a previously common arrangement in which a simultaneous operation of some, but not all of the bands required here is possible.
  • GSM transmitters and receivers are connected (again via the filters described above) to an SPDT switch 66.
  • DCS / PCS transmitter, DCS and PCS receiving device and antenna port of the UMTS duplexer 44/54 are connected to an SP4T switch 67.
  • SPDT and SP4T switches are in turn connected to the low-pass filter 76 and high-pass filter 77 of the diplexer 76/77 located directly on the antenna 89.
  • the diplexer is a crossover. In terms of frequency, however, it does not separate transmit and receive bands that are close to each other, but in this case the GSM band from the other bands.
  • the low-pass filter must be permeable from 880 ... 960 MHz (hereinafter referred to as "lower frequency range”) and the high-pass filter from 1710 ... 2110 MHz (hereinafter referred to as “upper frequency range”). If further systems / bands are implemented (see below), the "lower” or “upper frequency range” can extend over a larger range.
  • the switch settings in turn depend on the currently active paths, whereby a maximum of one path in the lower and one path in the upper frequency range can be switched through at the same time (e.g. GSM RX and UMTS; UMTS TX and RX in turn form a common one because of the duplexer Path).
  • an SP3T switch can be used instead of the SPDT switch 66, the third path being used for GSM850 RX. No further path is necessary for GSM850 TX, as it is usually for
  • GSM900 and GSM850 a common power amplifier 1 is used due to the small frequency differences.
  • a situation similar to that here in the upper frequency range would result in the lower frequency range if further systems such as CDMA850 were implemented, in which a duplexer is required due to the full duplex operation and an isolator may be required due to the AM component.
  • CDMA1900 for example, could be used in a similar manner in addition to UMTS.
  • UMTS TDD is also to be implemented, the most obvious solution is also an additional path for UMTS TDD RX, while UMTS FDD power amplifier 4 can also be used for UMTS TDD TX. I.e. here an SP5T switch is required instead of the SP4T switch 67.
  • the insertion loss between the power amplifier and antenna should be as low as possible so that the output power of the power amplifier and thus its current consumption can be as low as possible for a given transmission power. Lower power consumption increases the operating time of the device and reduces the power loss and the associated heating.
  • the insertion loss between the antenna and the LNAs should be low so that the system noise figure of the receiving devices is low and thus their sensitivity is high.
  • the harmonic filters and the diplexer are usually implemented as LC filters with discrete or printed coils and capacitors.
  • the reception filters and the duplexer are, for example, microwave ceramic filters, surface acoustic wave filters (SAW: surface acoustic wave) or other acoustic filters (e.g. BAW: bulk acoustic wave or FBAR: film bulk acoustic resonator).
  • SAW surface acoustic wave filters
  • BAW bulk acoustic wave
  • FBAR film bulk acoustic resonator
  • the RF switches can e.g. B. with pin diodes, as GaAs-FET switch (eg pHEMT switch) or as a micromechanical switch (MEMS: micro-electro-mechanical systems).
  • the isolator is, for example, a ferrite circulator in which one of the three connections is terminated with 50 ohms.
  • the directional coupler can be implemented with line structures, for example. If an isolator is present in the transmission path in question (here: UMTS), capacitive or resistive coupling can also take place instead of a directional coupler, since then there is no return wave and therefore no directional effect is required.
  • the object of the present invention is to enable a simultaneous operation of several transmitting and / or receiving devices without having to use additional antennas.
  • this object is achieved by a device for connecting the transmitting and receiving devices of multiband / multimode radio devices to one or more partially shared antennas, including a filter device, at least one transmitting and receiving device simultaneously with optionally one of at least two or at least two further transmitting and / or receiving devices using the same antenna can be operated.
  • the present object is also achieved by a method for operating the transmitting and receiving devices of multiband / multimode radio devices with one or more partially shared antennas, including filtering, at least one transmitting and receiving device simultaneously with optionally one of at least two or at least two more at the same time the same antenna ne transmitting and / or receiving devices can be operated.
  • radio devices for example mobile telephones which can transmit and receive in at least two frequency bands or systems (“multiband” or “multimode” devices)
  • the invention enables the transmission devices and the receiving devices to be connected to one or more antennas , wherein at least one antenna is used for several frequency bands.
  • the invention enables the simultaneous operation of several transmitting and / or receiving devices.
  • a frequency band / system eg UMTS
  • classic duplexers ie crossovers
  • Neighbor cell monitoring is necessary in cellular mobile radio networks so that a radio connection can be transferred from one base station to another ("handover") if the mobile phone leaves the range of one base station. Neighbor cell observation can take place not only in the same frequency band of the same system, but also in a different frequency band / system. This is necessary, for example, to enable the radio connection to be transferred even if only another frequency band / system is available in the neighboring cell and a call would otherwise have to be terminated due to the unavailability of the same frequency band / system.
  • the neighboring cells can be observed between the active time slots under certain, not always given conditions (for example, sufficient time, synchronicity), so that transmitting and / or receiving devices do not operate simultaneously necessary is.
  • the receiving device of the frequency band / system to be observed must be operated simultaneously with either the transmitting or receiving device of the active frequency band / system.
  • the transmitting and receiving device of the active frequency band and the receiving device of the frequency band / system to be observed ie a total of three devices, must be operated simultaneously. If several frequency bands / systems are to be observed, it is necessary in the case of the full-duplex system that three devices can be operated simultaneously, the third device (that for the frequency band / system to be observed) having to be able to be selected from several receiving devices.
  • radio applications may be necessary to operate several transmitting and / or receiving devices simultaneously if different radio applications are to run in one device at the same time. Examples are simultaneous operation of mobile radio (e.g. GSM or UMTS) and short-range radio (e.g. Bluetooth or WLAN) or radio reception.
  • mobile radio e.g. GSM or UMTS
  • short-range radio e.g. Bluetooth or WLAN
  • crossovers are necessary. Because a switch that switches the various inputs Direction with the antenna (s) enables the operation of only one device at a time.
  • Two closely spaced frequency bands can be connected to the antenna or one of several antennas using a classic duplexer (a common term for a crossover, usually consisting of two "impedance-neutral" bandpass filters).
  • Two far-away frequency bands can be connected to the antenna or one of several antennas using a classic diplexer (usually the term for a crossover consisting of a low-pass / high-pass structure constructed with capacitors and inductors).
  • the object of the present invention is to implement the simultaneous operation just described with lower insertion vaporization.
  • bandpass filtering is carried out in the reception paths (ie between the antenna and reception devices) to suppress interference signals received at the antenna.
  • performance detection is carried out for power measurement or power control, and filtering of interference signals generated in the transmission device, such as, for example, B. harmonics, image frequencies or noise in certain frequency ranges.
  • the returning wave occurring in the event of a mismatch on the antenna is also suppressed in the transmission paths. This means that the power amplifier always "sees" almost the same impedance at the output, even though mismatching occurs on the antenna due to reflections (e.g. device on a metal plate).
  • a constant load impedance may be necessary to ensure the stability of the power amplifier or to avoid a sharp increase in power consumption in the event of a mismatch. In particular, however, this may be necessary in systems whose modulation methods generate an AM component in the transmission signal.
  • An example of this is QPSK with RRC baseband filtering, as it is e.g. B. is used in CDMA systems (z. B. UMTS).
  • the power amplifier must be linear so that the AM component is retained, no signal distortion occurs and no excessive power caused by intermodulation is generated in the adjacent channel. The linearity and thus the generated adjacent channel power depends on the load impedance of the power amplifier, i.e.
  • a power amplifier uses more electricity ⁇ e the more linear it is.
  • a modulation method with a constant hull curve ie without an AM component, allows the use of power amplifiers which are operated in compression, since linearity is not required here.
  • An example of this is GMSK, as it is e.g. B. is used in GSM.
  • the invention is preferably used in a multiband / multimode mobile telephone (see example above) which can transmit and receive in at least three frequency bands in at least two systems, the frequency bands in each case can be divided into a transmission band and a reception band with an intervening duplex spacing and the individual frequency bands can overlap.
  • the frequency bands are divided into two frequency ranges ("lower” or "upper frequency range"), the frequency bands being relatively close to each other within a frequency range, while the two frequency ranges are relatively far apart.
  • At least one of the two frequency ranges preferably contains both at least one TDD system in which the transmitting and receiving device are active at different times (transmitting and receiving frequency can be the same or different), and at least one FDD full-duplex system.
  • at least one system is also involved, the modulation method of which generates an AM component in the sensor design.
  • Figures 1 and 2 each a basic diagram of a circuit arrangement of a mobile phone according to the prior art.
  • triple xer shows a circuit diagram of a first embodiment of the present invention (“triple xer”);
  • FIG. 4 shows a variant of the embodiment according to FIG. 2 (“multiplexer”);
  • FIG. 5 shows a circuit diagram of a second embodiment of the present invention (“single switched duplexer”);
  • FIG. 6 shows a variant of the embodiment according to FIG. 5 (“multiple switched duplexer”); FIGS. 7 and 8 implementations of block 67 in FIG. 6;
  • Fig. 11 is a circuit diagram of a third embodiment of the present invention ("Double Switched Duplexer");
  • Fig. 12 is a circuit diagram of a fourth embodiment of the present invention ("duplexer with switch");
  • Fig. 13 is a circuit diagram of a fourth embodiment of the present invention ("Multiplexer with Circulator");
  • the duplexer 44, 54 and the DCS RX filter 52 from FIG. 2 according to FIG. 3 are combined to form a triplexer.
  • volume summarizes.
  • two of the three filters are first connected to form a conventional, for example, monolithic duplexer. This is done by "impedance-neutral" interconnection (see above).
  • the UMTS TX filter 44 and the UMTS RX filter 54 are not connected to form a duplexer, but rather the UMTS TX filter 44 and the DCS RX filter 52, since the associated frequency bands lie closer together.
  • the duplexer 44/52 in turn is now connected to the UMTS RX filter 54, for example with the aid of phase shifters 102 and 104, with no impedance.
  • the phase shifter 102 does not transform the blocking band impedance of a single individual filter but that of the overall Dulexer 44/52 in, for example, an idle.
  • the stop band means the pass band of the third filter, in this example the UMTS RX band.
  • the phase shifter 104 transforms the stop band impedance of the UMTS RX filter 54 into an idle state, for example, where the stop band means the two pass bands of the duplexer 44/52, in this example the UMTS TX band and the DCS RX Tape.
  • the two phase shifters 102, 104 can be implemented, for example, by means of transformation lines (for example strip lines or microstrip lines) or by means of LC phase shifters made of discrete or printed coils and capacitors. While transformation lines only allow one phase rotation in one direction, both directions are possible with LC phase shifters. LC phase shifters may therefore be advantageous if
  • Transformation lines would require a phase shift of significantly more than 180 ° or almost 360 °. Depending on the frequency or wavelength, this would result in a very long line with consequent high losses. Since UMTS TX / RX and DCS RX are combined into a common path in FIG. 3, switch 67 is reduced to an SP3T switch here.
  • the triplexer 44/54/52 and the DCS TX filter 42 according to FIG. 4 are combined in a corresponding manner to form a multiplexer.
  • the DCS TX filter 42 must not be designed as a simple harmonic filter as is usual, but must have a high blocking attenuation in the passband of the other three filters and must be highly reflective.
  • the filter 42 can also be a pure bandstop filter instead of a low-pass filter, the harmonic filtering being carried out elsewhere, for example with the aid of an additional filter or in the filter 77 of the diplexer 76/77.
  • this multiplexer which consists of four filters
  • two filters can be combined to form a conventional, for example, monolithic duplexer, or three filters are first described as described above combined into a triplexer and this triplexer is then connected to the fourth filter in an impedance-neutral manner.
  • the DCS / PCS TX path must first be separated into two individual paths for DCS TX and PCS TX using the SPDT switch 62. Because the PCS TX band overlaps with the DCS RX band. With filters whose passbands overlap, a multiplexer cannot be implemented.
  • the PCS TX filter 43 may be a conventional harmonic filter.
  • the insertion loss of a multiplexer increases significantly with each additional filter, on the one hand because of the transformation losses, and on the other hand because of the fact that it becomes more and more difficult with each additional frequency band, the stop band impedance of each filter in all relevant frequency bands, for example in an idle state to transform.
  • Another disadvantage of a triplexer or multiplexer is that high demands are placed on the performance compatibility of the filters, in particular also on the DCS RX filter 52 in FIG. 3 or FIG. 4, since this represents a relatively large proportion of the UMTS (or in FIG. 4 also DCS) TX power can get (with the TX filters 42, 44 and the UMTS RX filter 54, the performance compatibility must be given anyway). This can be a problem, for example, if the DCS RX filter 52 is to be implemented as a SAW filter.
  • the triplexer 44/54/52 from FIG. 3 is replaced in a second embodiment of the invention according to FIG. 5 by a "switchable" duplexer, hereinafter referred to as “single switched duplexer".
  • This consists of the three filters, the switch 64 and the phase shifters 94, 102, 97 and 104. Since in the example no simultaneous operation of UMTS TX and DCS RX is required (which would be possible in FIGS. 3 and 4, respectively) , if the filters are sufficiently steep-edged), these two paths can be brought together via an SPDT switch 64.
  • phase shifters 94 and 102 The transformation of the stop band impedance of the UMTS TX filter 44 and the DCS RX filter 52 into, for example, an idle occurs here the phase shifters 94 and 102 across the SPDT switch 64. Part of the transformation can also take place for both paths simultaneously with the phase shifter 97, in which case one of the two phase shifters 94 and 102 may then be omitted. With a suitable stop band phase of the filter, further or all phase shifters may be omitted. It must be taken into account here that the SPDT switch 64 as well as any supply lines that are present carry out a transformation due to the electrical length. If the SPDT switch is designed as a pin-diode switch, for example, which itself already contains phase shifters (for exemplary embodiments, see FIGS.
  • the transformation of the switch can be very large and possibly used advantageously.
  • the SPDT switch 64 leads to an increase in the transformation losses due to the insertion loss, which affects not only the insertion loss in the UMTS TX and DCS RX path but also in the UMTS RX path. In the UMTS TX and DCS RX paths in particular, there is a high insertion loss since switches 67 and 64 are connected in series.
  • the DCS TX filter 42 must not be designed as a simple harmonic filter, but in this case must have high blocking attenuation in the UMTS RX band and be highly reflective. If the harmonic filtering takes place elsewhere, it can again be a pure bandstop filter. While the relevant stop band here only comprises the UMTS RX band, the phase shifter 104 must be used to transform a relatively large stop band as close as possible to, for example, an idle state. In FIG. 5, this includes the DCS RX band and the UMTS TX band, in FIG. 6 additionally the DCS and PCS TX band and the PCS RX band.
  • FIG. 7 shows a first embodiment of the SP4T switch 67 in FIG. 6 (the same applies to the other embodiments of the present invention).
  • the SP4T switch is implemented with three pin diodes 67a to 67c in series connection (series diodes), a pin diode 67d in parallel connection (shunt diode) and a phase shifter 67e.
  • This is a basic sketch, in which components for adaptation and power supply (e.g. coils and resistors, coupling and blocking coders) are omitted. If all four diodes are not turned on or are negative, for example to increase the insulation or linearity are almost idle for the RF signal. Thus, the shunt diode path is switched through and the series diode paths are blocked.
  • pin diodes through which sufficient current flows in the forward direction almost represent a short circuit for the HF signal. If one of the three series diodes and thus the shunt diode is simultaneously flowed because of the common DC path, the series is current -Diode path switched through and the remaining paths are blocked.
  • the current shunt diode represents approximately a short circuit for the HF signal, which is transformed into approximately no-load using the phase shifter 67e, so that the path switched through is influenced as little as possible.
  • the line length then corresponds to a quarter wavelength.
  • the path is selected as the shunt diode path , in which the current consumption is most critical, since only in the switched-on state does no current flow in the shunt diode path.
  • this circuit arrangement is used in such a way that the phase shifter 67e forms part of the phase shift in the context of the "switched duplexer", e.g. 6 takes over.
  • a path is selected as the shunt diode path, in which the phase shifter 67e reduces the residual phase shift that is still necessary, i.e. e.g. shortens the required length of the transformation lines and thus reduces their losses.
  • FIG. 8 shows a second form of realization of the SP4T switch 67 in FIG. 6, which increases the linearity of the switch in terms of circuitry and does not require any special diodes or negative bias.
  • the SP4T switch 67 is divided into an SP3T switch 67 'and an SPDT switch 67 ".
  • the UMTS TX signal only flows via the SPDT switch 67", while the other signals also via the SP3T switch This naturally increases the insertion vaporization in these paths, since since the linearity of an RF switch, for example also a GaAs-FET switch, the higher the fewer paths, the higher the result of this division Linearity for UMTS TX, which has a particularly advantageous effect in the case of a pin diode switch if the arrangement shown in Fig. 8 is selected, the series diode path of the SPDT switch 67 being the UMTS TX path here '', consisting of the series diode 67 '' a, used. In addition to this diode, there is no further - non-flowing - series diode in the SPDT switch 67 '' that can impair the linearity. This results in a particularly high linearity for the UMTS TX path.
  • a common transmission path for DCS, PCS and UMTS e.g. used because of a common power amplifier 7, in a variant according to FIG. 9 the switch 67 can simply be reduced to an SPDT switch ("Reduced Switched Duplexer"). Due to the above, an SPDT switch can e.g. have advantages over a multiple switch in terms of linearity. Compared to FIG. 6, a switch path can be saved due to the use of a common DCS / PCS and UMTS TX filter 47 and a common phase shifter 97 'instead of two separate filters 42, 44 and phase shifters 92, 94. This filter 47 must have a correspondingly wider pass band. In Fig.
  • the "switched duplexer” is implemented in a variant according to FIG 10 to a switchable multiplexer ("switched multiplexer") plausiblet.
  • GSM850, CDMA850, CDMA1900, UMTS TDD and Bluetooth and / or WLAN are also implemented, with a common antenna being used for all systems / bands.
  • the power amplifier 1, the power output 21 and for the GSM850 also the low-pass filter 41 are also used for GSM850 TX and for CDMA850 TX.
  • a separate filter 40 is required for CDMA850 TX, which is connected to the common GSM850 / CDMA850 RX filter 50 to form a duplexer 40/50 and is connected to the common GSM850 / CDMA850 LNA 10.
  • An isolator 30 may also be required for the CDMA850 TX due to the AM component.
  • the SPDT switch 61 separates GSM850 / GSM900 TX and CDMA850 TX into two paths.
  • the power amplifier 2 and the power output 22 are also used for the CDMA1900 TX.
  • a separate filter 43 is required for CDMA1900 TX, which is connected to the common PCS / CDMA1900 RX filter 53 to form a duplexer 43/53 and is connected to the common PCS / CDMA1900 LNA 13.
  • an isolator 33 may in turn be required because of the AM component.
  • the SPDT switch 62 separates DCS / PCS TX and CDMA1900 TX into two paths.
  • an isolator may be required in all four GSM TX bands because of the AM component.
  • isolators 30 and 33 had to be placed in front of SPDT switches 61 and 62 instead of behind.
  • it had to be sufficiently broadband in each case.
  • UMTS TDD TX the same path as for UMTS FDD TX is used because of the adjacent frequency range, while a separate path is required for UMTS TDD RX. This could be done through a separate path in switch 67.
  • the filter 44 for UMTS TDD RX is also used because of the same frequency range.
  • UMTS FDD / TDD TX and UMTS TDD RX are through the circulator 34 separated into two paths (an SPDT switch would also be possible). So that the circulator 34 also fulfills the function of the isolator for UMTS FDD / TDD TX, an SPDT switch 64 is required between the circulator 34 and the UMTS TDD LNA 14 ', which in the TX case detects a resistance with the system Impedance, e.g. 50 ohms, is switched. Otherwise, reflections on the antenna 89 are reflected on the possibly switched off LNA 14 'and returned to the power amplifier 4, but this should be prevented.
  • an SPDT switch 64 is required between the circulator 34 and the UMTS TDD LNA 14 ', which in the TX case detects a resistance with the system Impedance, e.g. 50 ohms, is switched. Otherwise, reflections on the antenna 89 are reflected on the possibly switched off LNA 14 'and returned to the power amplifier 4, but this should
  • the switch 64 can be dispensed with.
  • the Bluetooth / WLAN filter filter 48 is connected to the UMTS RX filter 54 to form a duplexer. Because of the same frequency band for TX and RX, a common filter 48 can be used. Bluetooth / WLAN TX and Bluetooth / WLAN RX can be separated by an SPDT switch 68 because of the TDD operation.
  • the interconnection is also carried out in FIG. 10 by means of phase shifters via the SP4T switch 67.
  • the phase shifter 104 now does not refer to a single filter 54, but to a duplexer 54/48. That is, the stop band impedance of the entire duplexer 54/58 has to be transformed into, for example, an idle via the phase shifter 104 all frequency bands for which the SP4T switch 67 is used.
  • the filters 42, 44 and 52 as well as the duplexer 43/53 must have high blocking attenuation and reflectivity not only in the UMTS RX band, but also in the Bluetooth / WLAN band. Because of the simultaneous operation with Bluetooth / WLAN, in contrast to FIG.
  • a phase shifter 93 is also required for PCS RX and CDMA1900 TX / RX. However, this can only be optimized for the Bluetooth / WLAN band. With the phase shifters 92, 94 and 102, a compromise between the UMTS RX band and the Bluetooth / WLAN band is necessary.
  • the "Switched Duplexer" z. 6 has the disadvantage that compared to the prior art according to FIGS. 1 and 2, for example due to transformation losses in some paths, higher insertion losses have to be accepted in order to enable the required parallel operations. This applies to the "Switched Duplexer" z. 6 according to FIG. 6 at all times, that is, even when parallel operation is not currently required, because, for example, no neighboring cell observation is taking place. In order to avoid this disadvantage, in a third embodiment of the present invention the SP5T
  • Switch 67 is used, which can optionally be switched through in one or in two paths simultaneously ("double switched duplexer").
  • the latter can e.g. in that two transistors of a GaAs-FET switch or two series diodes of a pin diode switch according to FIG. 7 (expanded by a series diode path) are switched through simultaneously.
  • a series diode path and a shunt diode path cannot be switched through at the same time. For this reason, a band must be selected for the shunt diode path for which no parallel operation is required, in this example PCS RX. At times when no parallel operation is required, only one path of the SP5T switch 67 is switched through.
  • Fig. 6 is omitted in this case, since both paths are brought together here directly at the switch "node".
  • the combination with the diplexer 76/77 and the absence of an expansion of the "double switched duplexer" to the lower frequency range has the advantage that the Transformation is limited to the upper frequency range and does not cover the entire frequency range.
  • the simultaneous operation of GSM RX or TX and UMTS RX or TX is achieved here by using the diplexer 76/77 on the basis of FIG. 2 and not by applying the "double switched duplexer" concept to the entire frequency range based on FIG. 1.
  • the linearity requirements described above for the switch 69 in FIG. 1 and for the switch 67 in FIGS. 2 to 6 and 9 to 11 (also switch 64 in FIG. 5) are so high, among other things, because there is between switch and Antenna is not a steep-sided filter that can effectively suppress intermodulation products created in the UMTS RX band.
  • the fourth embodiment of the present invention according to FIG. 12 is a solution to this problem.
  • a common low-pass filter 47 or the band-pass or band-stop filter, depending on the requirement for DCS / PCS and UMTS TX used.
  • the SPDT switch 67 from FIG. 9 is operated by a circulator replaced.
  • the aim here is to save the isolator 37 from FIG. 9 and thus to reduce the space requirement and costs and to reduce the insertion loss in the UMTS TX path.
  • the phase shifters 97, 102 'and 97' must be designed in such a way that, at the point of interconnection of the phase shifters 97 and 104 in the UMTS RX band, there is, for example, an idling.
  • the UMTS RX signal which reaches the circulator 67 via the phase shifter 97, is reflected on the duplexer 52/53/102/103 after passing through the phase shifter 102 '. It then traverses the phase shifter 102 ', the circulator 67 and the phase shifter 97' again. After reflection on the DCS / PCS / UMTS TX filter 47, it crosses again the phase shifter 94, the circulator 67 and the phase shifter 97. So that the circulator 67 also acts as an isolator for UMTS TX and the isolator 37 from FIG. 9 can be omitted here one
  • the SPDT switch 63 required in the PCS RX path, which in the UMTS TX case is connected to a resistor with the system impedance, e.g. 50 ohms, is switched.
  • the SPDT switch 63 is located in the PCS RX path because the PCS RX band is almost identical to the UMTS TX band.
  • the PCS RX filter 53 must be so broadband that it also covers the entire UMTS TX band. Then it is transparent to the UMTS TX signal reflected on the antenna 89 via the circulator 67 and can thus be absorbed in the above-mentioned resistance. Otherwise, it was reflected back on the filter 53 via the circulator 67 to the power amplifier 7, so that the circulator 67 would not act as an isolator.
  • the UMTS RX filter 54 could be combined directly with the DCS RX filter 52 and the PCS RX filter 53
  • Triplexer can be connected. This corresponds to FIG. 16 in the invention application No. 2001E11104DE.
  • the circulator 67 can have a narrow band, since it does not have to be permeable in the UMTS RX band. However, it should be more reflective in the UMTS RX band, since otherwise the higher through-attenuation has a negative effect on the transformation losses.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Transceivers (AREA)

Abstract

La présente invention concerne un procédé et un dispositif de connexion des systèmes d'émission et de réception d'appareils radio multibandes/multimodes à une ou plusieurs antennes partagées, faisant intervenir un système de filtrage. La présente invention concerne en particulier la connexion de systèmes d'émission et de réception utilisés simultanément.
EP04766253A 2003-09-30 2004-07-19 Procede et dispositif de connexion des systemes d'emission et de reception d'appareils radio multibandes/multimodes a une ou plusieurs antennes partagees Withdrawn EP1687908A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE2003145436 DE10345436A1 (de) 2003-09-30 2003-09-30 Verfahren und Vorrichtung zum Verbinden der Sende- und Empfangseinrichtungen von Multiband-/Multimode-Funkgeräten mit einer oder mehreren teilweise gemeinsam genutzten Antennen
PCT/EP2004/051534 WO2005034376A1 (fr) 2003-09-30 2004-07-19 Procede et dispositif de connexion des systemes d'emission et de reception d'appareils radio multibandes/multimodes a une ou plusieurs antennes partagees

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EP1687908A1 true EP1687908A1 (fr) 2006-08-09

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EP04766253A Withdrawn EP1687908A1 (fr) 2003-09-30 2004-07-19 Procede et dispositif de connexion des systemes d'emission et de reception d'appareils radio multibandes/multimodes a une ou plusieurs antennes partagees

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EP (1) EP1687908A1 (fr)
DE (1) DE10345436A1 (fr)
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Publication number Priority date Publication date Assignee Title
US8619639B2 (en) 2007-07-06 2013-12-31 Lantiq Deutschland Gmbh Power detector radio frequency multiplexer
DE102007040419A1 (de) * 2007-08-28 2009-03-26 Fraunhofer-Gesellschaft zur Förderung der angewandten Forschung e.V. Vorrichtung und Verfahren zum Bestimmen einer genutzten Übertragungskapazität eines Basisstationssendeempfängers
WO2009107081A1 (fr) 2008-02-25 2009-09-03 Nxp B.V. Procédés, systèmes et dispositifs pour dispositifs sans fil incluant plusieurs modules sans fil
DE102009003884B4 (de) * 2009-01-02 2012-03-29 Epcos Ag Multiplexer
EP2226948B1 (fr) 2009-03-03 2015-07-29 Qualcomm Technologies, Inc. Système de communication et procédé pour la transmission et la réception de signaux
US8798564B2 (en) 2009-03-17 2014-08-05 Provigent Ltd. Transmitter with replaceable power amplifier
DE102010000909B4 (de) 2010-01-14 2017-06-22 Airbus Operations Gmbh Vorrichtung zum Bereitstellen von Radiofrequenzsignalverbindungen
US8861407B2 (en) 2011-07-07 2014-10-14 Provigent Ltd. Multiple connection options for a transceiver
CN113660004B (zh) * 2021-08-19 2022-05-20 中国电子科技集团公司第三十八研究所 一种多模复用收发前端电路及控制方法

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FI88660C (fi) * 1991-01-09 1993-06-10 Nokia Telecommunications Oy Radiosaendarmottagarsystem
US6018644A (en) * 1997-01-28 2000-01-25 Northrop Grumman Corporation Low-loss, fault-tolerant antenna interface unit
DE10200048B4 (de) * 2002-01-02 2014-04-24 Qualcomm Incorporated Verbindung der Sende- und Empfangseinrichtungen von Multiband-/Multimode-Funkgeräten mit einer oder mehreren Antennen

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WO2005034376A1 (fr) 2005-04-14

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