EP0837479B1 - Circuit d'attaque pour électroaimant - Google Patents

Circuit d'attaque pour électroaimant Download PDF

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Publication number
EP0837479B1
EP0837479B1 EP97117371A EP97117371A EP0837479B1 EP 0837479 B1 EP0837479 B1 EP 0837479B1 EP 97117371 A EP97117371 A EP 97117371A EP 97117371 A EP97117371 A EP 97117371A EP 0837479 B1 EP0837479 B1 EP 0837479B1
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EP
European Patent Office
Prior art keywords
current
signal
voltage
value
coil
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Lifetime
Application number
EP97117371A
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German (de)
English (en)
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EP0837479A3 (fr
EP0837479A2 (fr
Inventor
Trent Lynn Goodnight
Vijay Manilal Dharia
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Deere and Co
Original Assignee
Deere and Co
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Filing date
Publication date
Application filed by Deere and Co filed Critical Deere and Co
Publication of EP0837479A2 publication Critical patent/EP0837479A2/fr
Publication of EP0837479A3 publication Critical patent/EP0837479A3/fr
Application granted granted Critical
Publication of EP0837479B1 publication Critical patent/EP0837479B1/fr
Anticipated expiration legal-status Critical
Expired - Lifetime legal-status Critical Current

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F7/00—Magnets
    • H01F7/06—Electromagnets; Actuators including electromagnets
    • H01F7/08—Electromagnets; Actuators including electromagnets with armatures
    • H01F7/18—Circuit arrangements for obtaining desired operating characteristics, e.g. for slow operation, for sequential energisation of windings, for high-speed energisation of windings
    • H01F7/1844—Monitoring or fail-safe circuits
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F7/00—Magnets
    • H01F7/06—Electromagnets; Actuators including electromagnets
    • H01F7/08—Electromagnets; Actuators including electromagnets with armatures
    • H01F7/18—Circuit arrangements for obtaining desired operating characteristics, e.g. for slow operation, for sequential energisation of windings, for high-speed energisation of windings
    • H01F7/1844—Monitoring or fail-safe circuits
    • H01F2007/1855—Monitoring or fail-safe circuits using a stored table to deduce one variable from another

Definitions

  • the invention relates to an electrical circuit for applying of an oscillating electric current to a coil of a Electromagnets, through which the electromagnet is dependent on Input or guide signals can be controlled.
  • Electromagnets are preferably the electromagnet a hydraulic control valve.
  • the control of the current is in such an application difficult because of the primary electrical properties of the Control valves, resistors and inductors not known and are not predictable.
  • the resistance of the coil of the Electromagnets can move within the temperature range the coil is exposed to change over 100%.
  • the inductance of the coil due to changes in the Temperature, the voltage pulse frequency and the supply voltage change by well over 100%.
  • the Amplitude of the voltage pulses in a range between 9 and 16 Volts.
  • US-A-4,764,840 describes a driver control circuit for one Solenoid through the for an initial pull-in period maximum current flow is adjustable to a fast ensure initial tripping of the solenoid. It a second hold period closes with a shorter one Holding current that is sufficient to the solenoid in its hold triggered position. For this, a Coil current value recorded and two separate comparators fed. Each comparator receives during the pull-in period, their duration by a monostable multivibrator fixed maximum and minimum Reference thresholds by which a maximum and a minimum Current limit set for a pulsating coil current become. After the pull-in period is over, the holding period a maximum and a minimum holding current limit set. No measures are specified to avoid the Coil current during the tripping phase, for example during switching a transmission between two gears Taxes.
  • DE-A-43 29 917 discloses a circuit arrangement for clocked supply of an electromagnetic consumer, in which a control unit is provided by means of which from the difference between an instantaneous signal on Consumer and a definable guide signal pulse width modulated control signal is formed. With this pulse width modulated control signal becomes a circuit breaker controlled by which the electromagnetic consumer with an electric current is applied. A modulation upper and lower limit current values are not described.
  • the object underlying the invention is seen in to design a generic electromagnetic driver circuit in such a way that the problems mentioned at the beginning are overcome.
  • an average current is to be generated, which in linear relationship with the input or command signal stands.
  • an electrical circuit provides one oscillating electrical current to the coil of a Electromagnets to cause the electromagnet to move in Dependency of a predetermined variable command signal to move.
  • the solenoid driver circuit powers the coil with a stream which variable upper and lower Has limit voltage values.
  • the lower limit voltage value increases essentially a constant relationship to the upper one Limit voltage value.
  • the limit voltage values can also with Peak current value or peak current value.
  • the solution according to the invention enables precise current control of the solenoid driver with an immediate Respond, i.e. a minimal time delay between the current setpoint and the actual current in the coil.
  • the Solenoid driver can be used with just a few components produce low cost.
  • the requirements for the microprocessor are very small because the microprocessor is only marginal intervenes in the current control (software effectiveness).
  • the frequency of the electromagnetic driver can be easily Way at a nominal operating point (nominal current, resistance, Optimize inductance and power supply) by suitable resistors for the circuit can be selected.
  • the circuit according to the invention enables maximum fault detection of the solenoid driver circuit. It is also advantageous that when switching on and / or during a Reset mode of the microprocessor from the solenoid driver circuit current output to the solenoid is zero.
  • the Circuit a signal divider through which of the command signal an upper limit voltage signal value and a lower limit voltage signal value, which is a constant relationship to the upper one Limit voltage signal value takes, are generated.
  • a current measuring resistor generates a current measurement voltage that flows through the current the coil corresponds.
  • a first comparator compares them Current measurement voltage with the upper limit voltage signal value.
  • a second Comparator compares the flow measurement voltage with the lower one Limit voltage signal value.
  • a current driver supplies a driver current the electromagnetic coil as a function of the output signals, which generated by the first comparator and the second comparator be so that the coil current has a lower limit current value which is essentially in a constant ratio to the upper limit current value.
  • the average current follows linear to the limit current because the lower peak is always in one constant percentage ratio to the given upper Limit current stands. Because the relationship between the borders or Peaks is constant, the linearity is maintained between Average current and specified limit current even if the inductance and / or the resistance of the coil or when the supply voltage changes. Because the amplitude value between the limits or peaks with the average current increases, is the frequency range of the electromagnetic driver minimized.
  • the electromagnetic driver circuit 10 controls that to the coil L1 an electromagnetically operated transmission control valve, not shown applied current depending on an analog Voltage control signal V-CMD, which from the PWM output (Pulse pause modulation) of a microprocessor MP is generated.
  • the command signal preferably has a voltage range of 0 to 5 volts, which with a desired coil current from 0 to Corresponds to 1000 mA. Therefore, convert one to a regulated one Power supply from 5 volt connected pull-up resistor R15 and an inverter 12 the command signal from PWM, which has a duty cycle of 0% to 100% has an analog voltage of 5 to 0 volts.
  • there becomes a 2 millisecond filter circuit consisting of the Resistor R14 and capacitor C5 are used.
  • the filtered command signal is then sent to a voltage divider applied, which is formed from the resistors R11 and R10 and a lead voltage at the connection between R11 and R10 V-PU (upper voltage limit) delivers.
  • a capacitor C4 which is connected in parallel to resistor R10 additionally a slight filtering contribution.
  • the voltage V-PU becomes the + input of a reset command comparator 14 and one between V-PU and earth through the resistors R8 and R9 Formed voltage divider supplied.
  • V-PL lower voltage limit
  • the output of the reset command comparator 14 is via a Resistor R6 connected to + 5 volts and connected to an input of a Set-reset flip-flops 18 (with Schmidt trigger input), that of two cross-linked NAND grids 20, 22 and a capacitor C2 is formed.
  • the output of the set command comparator 16 is via a resistor R7 connected to + 5 volts and to another input of the Set-reset flip-flops 18 created.
  • V-PU is also connected to the + input of a comparator 24 with a grounded capacitor C3 part of a shutdown circuit 26 is created.
  • a threshold which corresponds to a coil current of approximately 150 mA.
  • Capacitor C6 Between Earth and the connection point between R12 and R13 is located Capacitor C6.
  • the output of the comparator 24 (and the Switch-off circuit 26) has the input IN of a driver 28 connected.
  • the output OUT of driver 28 is at one end the solenoid coil L1 and a freewheeling diode D1 with earth connected.
  • the other end of the coil L1 is above the current measuring resistor R2 connected to earth.
  • the voltage across resistor R2 is proportional to the current flowing through coil L1. High frequency noise of this voltage is caused by the resistance R3, the capacitor C1 and the resistor R5 filtered out, to generate a voltage VSENSE. Through the diode D2 voltage compensation is suppressed (voltage transients).
  • the voltage VSENSE is connected to the + input of the Comparator 16 and applied to the input of the comparator 14.
  • a comparator 30 has a + input at which VSENSE is present, and an input at which the voltage VSHUTOFF is present.
  • the output of the comparator 30 is via a pull-up resistor R1 connected to + 5 volts and is directly connected to the status input ST of the driver 28 connected. He pulls the ST Entrance down if VSENSE is below VSHUTOFF.
  • the exit of the comparator 30 generates a status signal which is sent to a digital input of the microprocessor MP is applied.
  • the microprocessor can detect errors in the circuit, if the command voltage V-PU is greater than a value that corresponds to a coil current of 150 mA. The status signal will ignored if the command signal is not greater than 150 mA is.
  • the driver is preferably a Profet from Siemens or a Equivalent to this, which is capable of a line break or detect a short in coil L1. If the driver 28 detects an error, it pulls his status line ST down.
  • Comparator 16 pulls its output to ground when VSENSE closes becomes small (smaller than V-PL).
  • the comparator 14 pulls its Output to earth if VSENSE becomes too large (larger than V-PU).
  • the resistors R8 and R9 are like this selected that V-PL is 78.5% of V-PU. If VSENSE under V-PL, the driver 28 is turned on (set) and remains switched on until VSENSE rises above V-PU. If VSENSE reaches the value V-PU, the driver is switched off (reset) until VSENSE falls below V-PL again.
  • V-PU To ensure that driver 28 is off when the lead tension is too low (for example, static friction of the electromagnet), V-PU and a small constant voltage VSHUTOFF in the comparator 24 fed. If the lead voltage of the microprocessor MP is less than a value with a coil current of 150 mA corresponds, the comparator 24 pulls the input of the driver 28 low, turns off the driver 28 and prevents the flip-flop 18 turns on the driver 28.
  • the average current follows through the Coil L1 linear to the limit current, because the lower limit current always is in a constant relationship to the upper limit current.
  • the peak-to-peak amplitude also increases the ratio between the lower limit and however, the upper limit remains constant. The linearity remains even if the inductance and / or the Change the resistance of the coil L1 and / or if the Supply voltage fluctuates.
  • This circuit operates at a variable frequency.
  • the Frequency varies as a function of the command voltage, the Resistance and inductance of the coil as well as the Supply voltage. However, since the peak-to-peak amplitude increases in the same way as the average current Frequency variation much less than when the peak-to-peak amplitude would be constant.
  • R8, R9 can be the frequency of the nominal Operating point (nominal current, resistance and inductance the coil and supply voltage) can be optimized.
  • Only one of these control circuits can be used for several drivers be used provided the drivers are never at the same time are switched on.
  • a forward driver and a backward driver on a common drive and Use current measuring circuit.
  • the Input of the forward driver via an AND gate with a Forward switch and the reverse driver with an AND gate a reverse switch.
  • the microprocessor then drives the same command signal circuit regardless which valve (forward or reverse valve) is actually controlled.
  • the circuit is simple and consists of inexpensive Components.
  • the load on the microprocessor is extreme low since he. only has to generate the PWM command signal. Its A / D inputs are not used unnecessarily because of the Average current is not measured by the microprocessor. No equations or tables are required to To convert switching break ratios into current values, because of the Relationship is linear.
  • the PWM signal should be one have a fairly high frequency, so the time constant of the R14-C5 filter can be minimized or D / A converter can be used. It should be emphasized that resistance R2 is like this be chosen as large as possible and preferably a tolerance of ⁇ 1%.
  • Resistors R8, R9, R10, R11 and R14 preferably have a tolerance of ⁇ 1%.
  • the Ground path between the current measuring resistor R2 and the Comparators 14, 16, 24 and 30 should have a very low impedance exhibit.
  • the accuracy of the 5 volt control supply voltage for inverter 12 is also important.
  • inverted Power switching device instead of inverted Power switching device with an inverted device an inverting driver intermediate stage can be used.

Landscapes

  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Electronic Switches (AREA)
  • Magnetically Actuated Valves (AREA)
  • Reciprocating, Oscillating Or Vibrating Motors (AREA)
  • Feedback Control In General (AREA)
  • Control Of Linear Motors (AREA)
  • Color Printing (AREA)
  • Electromagnets (AREA)

Claims (6)

  1. Circuit électrique pour appliquer un courant électrique oscillant à une bobine (L1) d'un électroaimant, pour mettre l'électroaimant en mouvement en fonction de signaux de guidage de tension (V-CMD), caractérisé en ce que le circuit alimente la bobine (L1) avec un courant auquel correspondent des valeurs limites de tension supérieures et inférieures variables (V-PU, V-PL), la valeur limite de tension inférieure (V-PL) représentant sensiblement un pourcentage constant de la valeur limite de tension supérieure (V-PU) et ces valeurs limites de tension (V-PU, V-PL) servant à la comparaison avec un signal de mesure de tension (VSENSE), qui correspond au courant électrique oscillant mentionné se trouvant à la bobine (L1).
  2. Circuit selon la revendication 1, caractérisé par
    un diviseur de signaux (R8, R9), qui produit à partir du signal de guidage de tension (V-CMD) une valeur de signal supérieure (V-PU) et une valeur de signal inférieure (V-PL), la valeur de signal inférieure (V-PL) représentant un pourcentage constant de la valeur de signal supérieure (V-PU),
    un capteur de courant (R2) pour produire un signal de mesure de tension (VSENSE), qui représente le courant s'écoulant à travers la bobine (L1),
    un premier comparateur (14), qui compare le signal de mesure de tension (VSENSE) avec la valeur de signal supérieure (V-PU),
    un deuxième comparateur (16), qui compare le signal de mesure de tension (VSENSE) avec la valeur de signal inférieure (V-PL),
    un dispositif de commutation de puissance (28), qui est raccordé à une source de tension et à la bobine magnétique (L1) et qui, en fonction des signaux de sortie du premier et du deuxième comparateur (14, 16) relie en mode commandé la bobine (L1) avec la source de tension ou la déconnecte de celle-ci.
  3. Circuit selon la revendication 1 ou 2, caractérisé par un circuit de bascule de déclenchement et de remise à zéro (18) se trouvant entre les comparateurs (14, 16) et le dispositif de commutation de puissance (28).
  4. Circuit selon la revendication 2 ou 3, caractérisé par un circuit d'interruption (26), à la première entrée duquel est appliquée la valeur de signal supérieure (V-PU) et à la deuxième entrée duquel est appliqué un signal d'interruption (VSHUTOFF) et dont la sortie est reliée avec une entrée (ST) du dispositif de commutation de puissance (28), le circuit d'interruption (26) travaillant de telle façon que le dispositif de commutation de puissance (28) soit connecté jusqu'à ce que la valeur de signal supérieure (V-PU) atteigne le niveau du signal d'interruption (VSHUTOFF).
  5. Circuit selon l'une des revendications 1 à 4, caractérisé par un circuit de détecteurs de défauts (30) pour produire un signal de défaut dans la mesure où le signal de guidage de tension (V-PU) est plus grand qu'une valeur déterminée (VSHUTOFF).
  6. Circuit selon l'une des revendications 3 à 5, caractérisé par un circuit d'attaque de courant (28) pour l'application d'un courant d'attaque à la bobine magnétique (L1) en tant que fonction de signaux de sortie du circuit de bascule de déclenchement et de remise à zéro (18), le circuit d'attaque de courant (28) alimentant la bobine magnétique (L1) avec un courant, qui comprend des valeurs limites de courant supérieures et inférieures variables, et la valeur limite de courant inférieure représentant sensiblement un pourcentage fixe de la valeur limite de courant supérieure.
EP97117371A 1996-10-16 1997-10-08 Circuit d'attaque pour électroaimant Expired - Lifetime EP0837479B1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
US731472 1996-10-16
US08/731,472 US5748431A (en) 1996-10-16 1996-10-16 Solenoid driver circuit

Publications (3)

Publication Number Publication Date
EP0837479A2 EP0837479A2 (fr) 1998-04-22
EP0837479A3 EP0837479A3 (fr) 1999-01-13
EP0837479B1 true EP0837479B1 (fr) 2003-01-15

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ID=24939650

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EP97117371A Expired - Lifetime EP0837479B1 (fr) 1996-10-16 1997-10-08 Circuit d'attaque pour électroaimant

Country Status (10)

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US (1) US5748431A (fr)
EP (1) EP0837479B1 (fr)
JP (1) JP3068043B2 (fr)
AR (1) AR010497A1 (fr)
AU (1) AU693746B2 (fr)
BR (1) BR9705040A (fr)
CA (1) CA2209425C (fr)
DE (1) DE59709139D1 (fr)
ES (1) ES2185854T3 (fr)
MX (1) MX9707840A (fr)

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US6256185B1 (en) 1999-07-30 2001-07-03 Trombetta, Llc Low voltage direct control universal pulse width modulation module
US6407902B1 (en) 2000-02-29 2002-06-18 Dietrich Industries, Inc. Control system for a solenoid valve driver used to drive a valve of a compression cylinder
US6538345B1 (en) 2000-10-24 2003-03-25 Trombetta, Llc Load bank alternating current regulating control
US7740225B1 (en) * 2000-10-31 2010-06-22 Nordson Corporation Self adjusting solenoid driver and method
US6978978B2 (en) * 2000-10-31 2005-12-27 Nordson Corporation PWM voltage clamp for driver circuit of an electric fluid dispensing gun and method
FR2848019A1 (fr) * 2002-11-28 2004-06-04 Johnson Controls Tech Co Commande de relais electromagnetiques
US6765412B1 (en) 2003-05-01 2004-07-20 Sauer-Danfoss Inc. Multi-range current sampling half-bridge output driver
US7124047B2 (en) 2004-09-03 2006-10-17 Eaton Corporation Mathematical model useful for determining and calibrating output of a linear sensor
UA93051C2 (uk) * 2005-07-29 2011-01-10 Грако Міннесота Інк. Спосіб керування поршневим пневматичним насосом (варіанти)
US8059382B2 (en) * 2008-04-18 2011-11-15 Siemens Industry, Inc. Intrinsically safe circuit for driving a solenoid valve at low power
EP2662554A1 (fr) 2012-05-11 2013-11-13 Continental Automotive GmbH Circuit de commande pour vanne magnétique
DE102012212670B3 (de) * 2012-07-19 2014-02-13 Continental Automotive Gmbh Schaltungsanordnung zum Betätigen eines Magneteinspritzventils
DE102013103387A1 (de) 2013-04-05 2014-10-09 Continental Automotive Gmbh Verfahren und Vorrichtung zur Ansteuerung eines Magnetventils
US20150167589A1 (en) * 2013-12-13 2015-06-18 Hyundai Motor Company Method and apparatus for controlling high pressure shut-off valve
EP3224512A4 (fr) * 2014-11-25 2017-12-06 Aerojet Rocketdyne, Inc. Dispositif de commande d'actionneur
CN104633225B (zh) * 2014-12-05 2017-02-22 中国航空工业集团公司第六三一研究所 一种快速电磁阀的驱动控制电路
US11621134B1 (en) 2020-06-02 2023-04-04 Smart Wires Inc. High speed solenoid driver circuit

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Also Published As

Publication number Publication date
EP0837479A3 (fr) 1999-01-13
CA2209425A1 (fr) 1998-04-16
JP3068043B2 (ja) 2000-07-24
BR9705040A (pt) 1999-03-30
MX9707840A (es) 1998-04-30
AR010497A1 (es) 2000-06-28
AU693746B2 (en) 1998-07-02
AU3996197A (en) 1998-05-14
JPH10125529A (ja) 1998-05-15
ES2185854T3 (es) 2003-05-01
DE59709139D1 (de) 2003-02-20
US5748431A (en) 1998-05-05
CA2209425C (fr) 2000-02-22
EP0837479A2 (fr) 1998-04-22

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