EP0563765B1 - Circuit produisant une tension de référence en fonction d'une tension de commande - Google Patents

Circuit produisant une tension de référence en fonction d'une tension de commande Download PDF

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Publication number
EP0563765B1
EP0563765B1 EP93104805A EP93104805A EP0563765B1 EP 0563765 B1 EP0563765 B1 EP 0563765B1 EP 93104805 A EP93104805 A EP 93104805A EP 93104805 A EP93104805 A EP 93104805A EP 0563765 B1 EP0563765 B1 EP 0563765B1
Authority
EP
European Patent Office
Prior art keywords
voltage
comparator
resistor
input
output
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Lifetime
Application number
EP93104805A
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German (de)
English (en)
Other versions
EP0563765A3 (en
EP0563765A2 (fr
Inventor
Fredy Kamber
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
STARKSTROM-ELEKTRONIK AG
Original Assignee
STARKSTROM-ELEKTRONIK AG
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Publication of EP0563765A2 publication Critical patent/EP0563765A2/fr
Publication of EP0563765A3 publication Critical patent/EP0563765A3/de
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Publication of EP0563765B1 publication Critical patent/EP0563765B1/fr
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Classifications

    • G—PHYSICS
    • G05—CONTROLLING; REGULATING
    • G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
    • G05F1/00—Automatic systems in which deviations of an electric quantity from one or more predetermined values are detected at the output of the system and fed back to a device within the system to restore the detected quantity to its predetermined value or values, i.e. retroactive systems
    • G05F1/10—Regulating voltage or current
    • G05F1/46—Regulating voltage or current wherein the variable actually regulated by the final control device is dc
    • G05F1/462—Regulating voltage or current wherein the variable actually regulated by the final control device is dc as a function of the requirements of the load, e.g. delay, temperature, specific voltage/current characteristic
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B39/00—Circuit arrangements or apparatus for operating incandescent light sources
    • H05B39/04—Controlling
    • H05B39/041—Controlling the light-intensity of the source
    • H05B39/042—Controlling the light-intensity of the source by measuring the incident light
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/36—Controlling
    • H05B41/38—Controlling the intensity of light
    • H05B41/39—Controlling the intensity of light continuously
    • H05B41/392—Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor
    • H05B41/3921—Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor with possibility of light intensity variations

Definitions

  • the present invention relates to a circuit arrangement for generating an electrical voltage setpoint in a non-linear manner as a function of an electrical control voltage.
  • Circuit arrangements of this type are e.g. B. known from document EP-A-0 432 845 and proposed for numerous applications and in use. For higher demands on precision and reproducibility, however, the known circuit arrangements are complex and correspondingly expensive.
  • the object of the invention is to provide a circuit arrangement of the type mentioned, which requires only a few common electrical components in a simple construction and nevertheless generates a stable, reproducible voltage setpoint and is particularly suitable for use in an electronic ballast for regulating the brightness of low-pressure gas discharge lamps.
  • the task is to generate a setpoint voltage to be compared with a reference voltage, hereinafter referred to as setpoint, as a function of an externally adjustable control voltage.
  • setpoint a reference voltage
  • the comparison value of the target value and the reference voltage then serves to control an inverter bridge fed by an AC or DC network in such a way that the brightness of the discharge lamp connected to the inverter bridge changes in accordance with the value of the externally set control voltage. Since the perception of brightness of the human eye is quasi-logarithmic, it is impractical to base the brightness control of the discharge lamp on a linearly changing control variable.
  • FIG. 1 shows a first circuit part of the circuit arrangement according to the invention.
  • This circuit part has a positive supply voltage line labeled + and a zero line labeled 0.
  • This stabilized DC voltage supply of approximately 12 volts is independent, that is to say galvanically isolated from other parts of the device under consideration.
  • the supply voltage is therefore generated, for example, by means of a transformer connected to an alternating current source, to the secondary winding of which a rectifier and stabilizing circuit is connected. Since such a feed circuit here without It is not important that it is not shown in FIG. 1.
  • the first circuit part of FIG. 1 also has two terminals 1 and 2, to which an external, adjustable burden 3 can be connected via a control line, not shown.
  • a voltage divider is formed together with a resistor 4 connected to the positive feed line.
  • the resistor 4 is dimensioned such that a voltage which varies between 1 and 10 volts, depending on the setting of the burden 4, results in the voltage divider point 5.
  • the voltage divider point 5 is connected via a high-resistance resistor 6 to the positive input of a first comparator 7, this input also being connected to the zero line via a capacitor 8.
  • the resistor 6 and the capacitor 8 form a protective circuit of the comparator input against unintentional high voltages, for example if the AC mains voltage is accidentally connected to the terminal 2.
  • the mains voltage resistance of the control line connected to terminals 1 and 2 is thus guaranteed.
  • a second comparator 9 also has its positive input connected to a voltage divider formed by resistors 10 and 11.
  • the negative input of the comparator 9 is connected to the positive feed line via a resistor 12 and to the zero line via a capacitor 13.
  • the output of the comparator 9 is connected on the one hand to the positive comparator input via a resistor 14 and to the negative comparator input via the series connection of a diode 15 and a resistor 16. Finally, the negative input of the comparator 9 is still connected to the negative input of the comparator 7.
  • resistors 10 and 11 are relatively high, for example 100 k ⁇ or 330 k ⁇ .
  • the resistor 12 also has a value close to 100 k ⁇ .
  • the resistor 14 is relatively low-resistance, for example 6.8 k ⁇ .
  • the resistor 16 is very low, for example 100 ⁇ .
  • the positive input of the comparator 9 When the supply voltage is first applied to the positive supply line and the zero line, the positive input of the comparator 9 immediately assumes the value determined by the resistors 10 and 11. The capacitor 13 is charged via the resistor 12 with the time constant of these two components, so that the voltage at the negative input of the comparator rises exponentially. No current flows through the resistor 14, the diode 15 and the resistor, since the voltage at the positive input of the comparator 9 is higher than that at the negative comparator input and because the comparator output is open.
  • the comparator 9 switches, that is, its output practically assumes the voltage of the zero line.
  • the capacitor 13 discharges rapidly via the resistor 16 and the diode 15, while there is a very low voltage at the positive comparator input, since the resistor 14 is connected in parallel to the resistor 11 in this state.
  • the capacitor 13 can therefore discharge to this low voltage. If the voltage at the negative comparator input drops further, that at the positive comparator input is relatively higher.
  • the comparator 9 thus again reaches the blocking state with an open output, which corresponds to the initial state, so that the capacitor 13 is charged again via the resistor 12.
  • the transmission-side diode 18 of the optocoupler 19 is accordingly active as long as each of the exponentially increasing pulses generated by the comparator 9 has a lower voltage than the control voltage generated by the set burden 3.
  • the width of the square-wave pulses emitted by the active diode 18 is a measure of the magnitude of the control voltage. However, as intended, the relationship between the width of the pulses and the magnitude of the control voltage is not linear. Because of the exponential course of the pulses of the comparator 9 controlling the diode 18, the width of the diode pulses for changes in the small control voltages of the burden 3 increases more slowly than for changes in large control voltages.
  • comparators 7 and 9 are used in the exemplary embodiment described. However, it is also possible to provide other semiconductor components and other circuits for this purpose, for example operational amplifiers, etc.
  • a second circuit part, shown in FIG. 2, is provided to receive the square-wave pulses transmitted by the diode 18 of FIG. 1, to additionally deform and smooth them non-linearly, in order to generate a nominal value of low ripple.
  • a receiver-side transistor 21 of the optocoupler 19 is connected via a resistor 22 on the one hand to a positive voltage line + and on the other hand connected to the associated zero line 0.
  • the control electrode of a field-effect transistor 23 is connected to the transistor 21 of the optocoupler 19, the drain electrode of which is also fed by the positive voltage line via a resistor 24.
  • the drain electrode is connected via a further resistor 25 to a terminal 26, at which, as explained below, the desired setpoint occurs.
  • Terminal 26 is connected to the zero line via a capacitor 27.
  • the diode 18 of the optocoupler 19 (FIG. 1) is conductive, a current also flows through the transistor 21 of the optocoupler 19 (FIG. 2). Then the field effect transistor 23 is blocked, so that the capacitor charges via the series connection of the resistors 24 and 25. If then the diode 18 and thus also If the transistor 21 of the optocoupler 19 is blocked, the field-effect transistor 23 becomes conductive, so that the capacitor 27 can discharge via the field-effect transistor 23 and the resistor 25. Since the resistor 25 has an approximately four times smaller value than the sum of the resistors 24 and 25, the capacitor 27 is discharged faster than its charging.
  • the voltage at the terminal 26 rises considerably faster at a high control voltage than at a low control voltage, which significantly improves the desired quasi-logarithmic characteristic of the dependence of the voltage at the terminal 26 on the control voltage.
  • the capacitor 27 has a comparatively large capacitance (for example approximately 3 »F)
  • the ripple in the voltage at the terminal 26 is very low.
  • the voltage at terminal 26 represents the desired setpoint with a quasi-logarithmic dependence on the adjustable control voltage provided by burden 3 in FIG. 1.
  • the present circuit arrangement generates reproducible voltage setpoints.
  • the brightness of a large number of discharge lamps, the ballasts of which each have an existing circuit arrangement can be controlled without noticeable differences in the brightness set for the individual discharge lamps.

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  • Engineering & Computer Science (AREA)
  • Electromagnetism (AREA)
  • General Physics & Mathematics (AREA)
  • Radar, Positioning & Navigation (AREA)
  • Automation & Control Theory (AREA)
  • Physics & Mathematics (AREA)
  • Circuit Arrangements For Discharge Lamps (AREA)
  • Details Of Television Scanning (AREA)
  • Relay Circuits (AREA)
  • Emergency Protection Circuit Devices (AREA)
  • Electrophonic Musical Instruments (AREA)
  • Oscillators With Electromechanical Resonators (AREA)
  • Control Of Electrical Variables (AREA)

Claims (10)

  1. Circuit produisant une tension électrique de référence liée selon une fonction non linéaire à une tension de commande électrique, réglable, caractérisé par un générateur de signal (9-15) formant une tension de signal périodique qui correspond à une forme identique non linéaire et monotone pendant la même période et par un circuit de comparaison (4-8) comportant des entrées pour la tension du signal du générateur de signal et la tension de commande réglable ainsi qu'une sortie destinée à fournir un signal de comparaison lorsque la tension du signal du générateur de signal atteint la valeur de la tension de commande réglable, le signal de comparaison persistant jusqu'au début de la période suivante de la tension du signal du générateur de signal.
  2. Circuit selon la revendication 1, caractérisé en ce que la tension du signal du générateur de signal (9-15) a une forme exponentielle.
  3. Circuit selon la revendication 2, caractérisé en ce que pour donner à la tension du signal une forme exponentielle, on met en série une résistance (12) et un condensateur (13) entre les tensions d'alimentation (+, 0) d'une alimentation stabilisée en courant continu.
  4. Circuit selon la revendication 3, caractérisé en ce que la première entrée d'un comparateur (9) est reliée au point de jonction de la résistance (12) et du condensateur (13) et la seconde entrée du comparateur (9) est reliée au point de jonction de deux résistances (10, 11) qui forment un diviseur de tension entre les lignes d'alimentation (+, 0) et la première entrée du comparateur (9) est reliée par une résistance (16) à la sortie du comparateur (9).
  5. Circuit selon la revendication 4, caractérisé en ce que la sortie du comparateur (9) est en outre reliée par une résistance (14) à la seconde entrée de ce comparateur (9).
  6. Circuit selon la revendication 4 ou 5, caractérisé en ce que le point de jonction de la résistance (12) et du condensateur (13) est relié à la première entrée d'un autre comparateur (7) et la tension de commande est appliquée à la seconde entrée de cet autre comparateur (7).
  7. Circuit selon la revendication 6, caractérisé en ce que la sortie de ce comparateur (7) est reliée à un diviseur de tension (17, 18) branché entre les lignes d'alimentation (+, 0).
  8. Circuit selon les revendications 4 et 6, caractérisé en ce que la sortie de ce comparateur (7) est reliée à l'électrode de commande d'un transistor de commutation (23) dont l'électrode de sortie est reliée à un circuit de charge et de décharge (24, 25) pour un condensateur de lissage (27).
  9. Circuit selon la revendication 8, caractérisé en ce que l'électrode de sortie du transistor de commutation (23) est reliée par une première résistance (24) à l'une des lignes d'alimentation (+) et par une seconde résistance (25) à une borne (26) de la valeur de consigne de la tension (tension de référence) et la borne (26) est reliée par le condensateur de lissage (27) à l'autre ligne d'alimentation (0), et lorsque le transistor (23) est bloqué, le condensateur de lissage (27) se charge à travers le montage en série formé par les deux résistances (24, 25) et lorsque le transistor (23) est conducteur, le condensateur se charge par la seconde résistance (25) et le transistor de commutation (23).
  10. Circuit selon la revendication 8 ou 9, caractérisé en ce que la sortie de l'autre comparateur (7) est reliée à l'électrode de commande du transistor (23) par l'intermédiaire d'un coupleur optique (19) et une diode du côté de l'émission du coupleur optique (19) forme une partie (18) du diviseur de tension (17, 18) prévu à la sortie du comparateur (7), un transistor (21) du coupleur optique (19), du côté de l'entrée, étant relié à l'électrode de commande du transistor de commutation (23) et à une résistance d'alimentation (22).
EP93104805A 1992-04-02 1993-03-24 Circuit produisant une tension de référence en fonction d'une tension de commande Expired - Lifetime EP0563765B1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
CH1073/92A CH683462A5 (de) 1992-04-02 1992-04-02 Schaltungsanordnung zur Erzeugung eines elektrischen Spannungs-Sollwertes in Abhängigkeit von einer elektrischen Steuerspannung.
CH1073/92 1992-04-02

Publications (3)

Publication Number Publication Date
EP0563765A2 EP0563765A2 (fr) 1993-10-06
EP0563765A3 EP0563765A3 (en) 1993-12-08
EP0563765B1 true EP0563765B1 (fr) 1995-08-23

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Application Number Title Priority Date Filing Date
EP93104805A Expired - Lifetime EP0563765B1 (fr) 1992-04-02 1993-03-24 Circuit produisant une tension de référence en fonction d'une tension de commande

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EP (1) EP0563765B1 (fr)
AT (1) ATE126907T1 (fr)
CH (1) CH683462A5 (fr)
DE (1) DE59300495D1 (fr)
DK (1) DK0563765T3 (fr)

Family Cites Families (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3458801A (en) * 1967-06-01 1969-07-29 Itek Corp High voltage operational amplifier for use as an electronically controllable power supply regulator
EP0350518B1 (fr) * 1988-07-12 1993-08-25 Eppendorf-Netheler-Hinz Gmbh Photomètre
US5038079A (en) * 1989-12-11 1991-08-06 North American Philips Corporation Method for controlling fluorescent lamp dimmers and circuit for providing such control

Also Published As

Publication number Publication date
EP0563765A3 (en) 1993-12-08
ATE126907T1 (de) 1995-09-15
DK0563765T3 (da) 1995-12-27
CH683462A5 (de) 1994-03-15
EP0563765A2 (fr) 1993-10-06
DE59300495D1 (de) 1995-09-28

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