EP0547120B1 - Transfomateurs de puissance et inducteurs couples avec entrelacement optimal d'enroulement - Google Patents

Transfomateurs de puissance et inducteurs couples avec entrelacement optimal d'enroulement Download PDF

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Publication number
EP0547120B1
EP0547120B1 EP91916278A EP91916278A EP0547120B1 EP 0547120 B1 EP0547120 B1 EP 0547120B1 EP 91916278 A EP91916278 A EP 91916278A EP 91916278 A EP91916278 A EP 91916278A EP 0547120 B1 EP0547120 B1 EP 0547120B1
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EP
European Patent Office
Prior art keywords
turns
transformer
core
coupled inductor
primary
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EP91916278A
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German (de)
English (en)
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EP0547120A1 (fr
Inventor
Peter David Evans
William John Baxter Heffernan
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Electrotech Instruments Ltd
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Electrotech Instruments Ltd
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F30/00—Fixed transformers not covered by group H01F19/00
    • H01F30/06—Fixed transformers not covered by group H01F19/00 characterised by the structure
    • H01F30/16—Toroidal transformers
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F27/00—Details of transformers or inductances, in general
    • H01F27/28—Coils; Windings; Conductive connections
    • H01F27/2804—Printed windings
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F27/00—Details of transformers or inductances, in general
    • H01F27/28—Coils; Windings; Conductive connections
    • H01F27/2804—Printed windings
    • H01F2027/2814—Printed windings with only part of the coil or of the winding in the printed circuit board, e.g. the remaining coil or winding sections can be made of wires or sheets
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F29/00—Variable transformers or inductances not covered by group H01F21/00
    • H01F29/14—Variable transformers or inductances not covered by group H01F21/00 with variable magnetic bias
    • H01F2029/143—Variable transformers or inductances not covered by group H01F21/00 with variable magnetic bias with control winding for generating magnetic bias

Definitions

  • This invention relates to the concept, design, construction and deployment of electrical power transformers and coupled inductors primarily for application in switch-mode power supplies, and in particular to the concept and methods of making such components whereby high frequency eddy current loss mechanisms are minimised. These devices can be used to overcome the problems of low efficiency and excessive power dissipation in high frequency switching applications.
  • the two main mechanisms contributing to a. c. winding loss are well known.
  • the skin effect is caused by the current flowing within a conductor setting up a magnetic field which then induces eddy currents in the conductor.
  • the direction of eddy current flow is such as to cancel out the main current in the centre of the conductor but reinforce it as the edges (Fig. 2).
  • the proximity effect (1) is caused by the leakage flux due to all the windings (as in Fig. 1) inducing eddy currents in each winding in such a direction as to cancel the main current at the outer edge and to reinforce it at the inner edge (Fig. 3).
  • eddy current losses can be mimimized by using conductors less than two skin depths thick, or multiple stranded conductors such as Litz wire.
  • a bifilar winding arrangement is used in which the primary and secondary windings are twisted together prior to winding. This ensures that, for an N turn winding, the peak mmf is never greater than one Nth of its value in a single layer conventional arrangement; i.e. each primary turn is interleaved with a secondary turn.
  • Such transformers are usually wound on a toroidal core to give a closed main-flux path and have unity turns ratio.
  • US-A-4536733 discloses a conventional toroidal transformer which has been modified to incorporate a low-voltage, high-current secondary winding constituted by a number of copper segments placed over a conventionally-wound primary. Inter-connections between the segments are made through PCB tracks: these interconnections achieve different turns ratios.
  • the purpose of this earlier invention is to reduce leakage inductance.
  • US-A-4103267 discloses a process of manufacturing a transformer directly onto a substrate, for signal processing applications.
  • FR-A-2556493 discloses the interleaving of entire windings over an asymmetric core.
  • the purpose of that invention was to remove heat from the windings, but the interleaving of the windings appears to be accidental, without any indication of purpose.
  • EP-A-0071008 discloses a conventional sandwich type of power transformer, as acknowledged in the second paragraph of page 1 of the present description. Windings are interleaved on the same layer and also between layers, in a multiple winding transformer wound on a bobbin. This form of winding has the effect of reducing leakage inductance.
  • each winding consists of N physical turns of conductive material around a core which may be of soft magnetic material (e.g. ferrite or iron powder), the electrical turns ratio being determined by series or parallel, or combination series-parallel, connections of the physical turns of each winding.
  • ferrite or iron powder soft magnetic material
  • the invention allows the electrical turns ratio to take any desired value, including non-integral values.
  • the conductors for each physical turn are preferably optimally dimensioned to minimize or control winding losses.
  • More than one layer of interleaved windings may be employed, the primary/secondary interleaving preferably being both in each of the layers and also from layer to superimposed layer.
  • Any series, parallel, or series/parallel combination or array of such transformers or coupled inductors, may be used so as to optimise heat transfer or to control stray magnetic fields.
  • a portion of each or any physical turn is preferably formed by a printed, etched, plated or otherwise formed conductor on a substrate material.
  • the substrate may be a flexible or a preformed substrate. Multiple layer substrates are advantageous for more complex windings.
  • a portion of each or any physical turn is preferably formed by an ultrasonically or thermosonically welded, soldered, silver soldered or otherwise welded or attached conductor looped over a core.
  • a portion of at least one physical turn is constituted by a conductor formed on a substrate material, and each winding consists of physical turns of a conductive material (e.g. metal wire or ribbon) around a core, including the step of forming a portion of each physical turn as a loop of the conductive material over the core and bonding it at its ends to the conductors which are formed on the substrate (e.g. by ultrasonic welding, welding, soldering, or another appropriate method).
  • a conductive material e.g. metal wire or ribbon
  • the looped conductors may be positioned in an insulating former designed to give compliance with national and international standards for insulation and safety isolation.
  • this portion of each or any physical turn may be formed by a printed, etched, plated or otherwise formed conductor on the core material.
  • a portion of each or any physical turn may advantageously consist of a punched, pressed, plated, or otherwise manufactured preform.
  • each transformer or coupled inductor or array thereof it is preferred that a toroidal core or cores is/are used.
  • any or all of the windings are preferably terminated in the centre of the core, allowing optimal current distribution in the winding and reducing losses. This is especially advantageous in the case of windings employing parallelled turns.
  • Secondary side rectifier diode/s and/or any other components may be situated in the centre of the core, and the windings adapted for connection thereto. This is particularly relevant to a step-down transformer/coupled inductor. Additionally, where parallelled secondary turns are employed, individual rectifier diodes may be used with each turn, or group of turns, with inherent current sharing.
  • Primary side switching device/s and/or any other component/s may be situated in the centre of the core. Again, this is particularly relevant to a step-up transformer/coupled inductor.
  • the core material is advantageously a permeable ferrite, optionally with distributed 'air' gaps, where 'air' means any material of permeability lower than the said ferrite.
  • the core may however be of a powdered iron or other powdered permeable material (e.g. Moly-permalloy) construction; or of amorphous metal material, strip-wound or solid.
  • a powdered iron or other powdered permeable material e.g. Moly-permalloy
  • amorphous metal material strip-wound or solid.
  • the transformer or coupled inductor or array thereof may be air-cored or wound on a non-permeable former.
  • the core cross section is ideally arranged so as to facilitate manufacture of the component, e.g. by use of a domed shape or other convex shape.
  • the primary or primaries and secondary or secondaries of the transformer may be interleaved as in a bifilar or multifilar arrangement, i.e. one primary turn is adjacent to two secondary turns and vice versa (see Fig. 5).
  • a bifilar or multifilar arrangement i.e. one primary turn is adjacent to two secondary turns and vice versa (see Fig. 5).
  • the optimum shape for the core of the transformer (which is likely to be of a soft magnetic permeable material, possibly ferrite) is a toroid.
  • the physical relationship of any one turn to all the others is ideally identical, i.e. the sum of the mutual leakage flux linkages between any given turn and all other turns is identical.
  • current will be shared perfectly between each turn of every parallel connected winding; thus winding resistance will be minimized.
  • primary or secondary turns are not symmetrically positioned. In these cases good current sharing can still be achieved.
  • the technique may also be advantageous in any other core shape including E-cores employing conventional or planar spiral windings (see Fig. 6).
  • the interleaved planar spiral transformer of Fig. 6(d) is particularly interesting; the conductor width may be varied to give exact current sharing in the secondary turns despite variations in turn length.
  • the device thus far described is a transformer consisting of only one layer of winding.
  • this mmf cancelling technique can be applied to any number of layers (see Fig. 7); here primary and secondary turns are interposed both on each layer and also on alternate layers resulting in minimal leakage flux in either axis.
  • this method is applicable to coupled inductors (also known as flyback transformers).
  • coupled inductors also known as flyback transformers.
  • the core may preferably be made of low permeability magnetic material, e.
  • the optimal shape is a toroid, although any shape is possible (e.g. shape c) of Fig. 6 in which the centre of the core is of low permeability material with a highly permeable 'magnetic shunt' round the outside).
  • the physical size of typical transformers and inductors becomes such that the main (core) flux density has to be kept well below the saturation level of the material, for acceptable core temperature rise in operation. This is because total core losses, for a given flux density, are proportional to core volume, whereas heat transfer from the core is related directly to core surface area.
  • the surface area for a given volume can be increased and the material can be used more effectively.
  • the 12:1 arrangement is a simple matter of connecting the secondary turns (N p of them) in parallel as shown in Fig. 8(b).
  • the 12:2 ratio is a matter of paralleling up six turns, twice, and connecting the parallel sets in series.
  • There are numerous alternatives for selecting the turns to be connected in parallel and two examples are shown in Fig. 8(c). Physical convenience in laying out the substrate is likely to be a major influence in choosing the most suitable interconnection pattern. Similar series-parallel systems are available for other integer turns ratios, namely 12:3, 12:4 and 12:6 for the present case, as shown in Fig. 8(d).
  • N p N p .
  • N k 1, 2, 3, 4, 6, 12, ie factors of N p .
  • each winding segment contains turns from all windings. This provides for good current sharing among turns and serves to minimise the a.c. resistance.
  • An example of this type of arrangement is given in Fig. 10 with a twelve turn primary and one, three and eight turns secondaries. There is mmf cancellation every 30 . ( ⁇ /6).
  • Fig. 11 for a twelve turn primary with a 5 turn secondary, a centre tapped 2 turn secondary and a centre tapped one turn secondary.
  • the windings are usually arranged symmetrically to ensure good current sharing, but leakage flux within each winding segment and a.c. winding resistance are not minimized; instead the mmf driving leakage flux is minimized every ⁇ winding segments, where ⁇ is an integer, ⁇ being equal to three in the example in Fig. 11. In general therefore mmf is minimized every ( ⁇ /S).
  • a transformer or inductor as described can be made by thick film printing, plating or etching a pattern of conductors (e.g. copper) on a substrate material which is electrically insulating but preferably thermally conductive (e.g. Alumina, Beryllia, Aluminium Nitride). If the substrate is not a good thermal conductor, such as FR4 or Kapton, then thermally conducting vias may be provided for good thermal properties.
  • a pattern or multi-layered patterns may include the terminations for the transformer or inductor and determine the series or parallel connections of the individual turns. A suitabl insulation layer(s) may then be placed on top of these conductors on which is placed the core itself.
  • the turn are then completed over the core - these may take the form of conductive wire, ribbon or foil bonding leads, or of printed, plated or etched conductors which may be attached directly to the core or to a flexible substrate; additionally, particularly in the case of a single electrical turn primary or secondary winding, the parallel turns may be formed by a single conductive pressing or an etched, plated or printed preform.
  • the cross section of the core over which the windings are placed may advantageously be shaped so as to facilitate "winding" the device, for example, with a domed profile (Fig. 12).
  • an insulating former or formers in which to run the "winding/s" may be used, shaped so as to fit over the core, which may not only aid routing of conductors during manufacture, but also provide electrical insulation (e.g. Fig. 13).
  • Such a former can be designed to provide the necessary creepage and clearance distances for safety and other isolation/insulation standards.
  • a number of such formers placed on top of each other may be used in the case of multiple layers.
  • the former described may be incorporated as part of the core itself although this is likely to be less satisfactory electromagnetically. In some cases it may be advantageous to place one or more winding/s directly on to the core or former, with conventional techniques, prior to attachment to the substrate, particularly where many electrical turns are involved.
  • a pattern of etched, plated or printed conductive tracks (in this case etched copper) is formed on a substrate material (e.g. alumina).
  • the thickness of the conductor material is typically 1.5 to 2 times the skin depth at the desired frequency (in this case 70 ⁇ m copper, equivalent to 1.5 skin depths at 2 MHz).
  • the secondary turns may all be connected inside the toroid by circular conductors (rings) as shown.
  • the outer of the three rings, labelled C may be printed, plated or etched on a different layer from ring B, possibly with vias (inter-layer connections) at points D.
  • sprayed or adhesive insulation may be used either over the whole substrate (except for connection pads) or just at the crossovers marked E (at which the conductive paths cross each other). Otherwise ring C may be formed by wire or ribbon bonds with or without insulation at the crossover points E.
  • One other option is to dispense with these rings altogether and to run multiple bond conductors from each paralleled radial conductor to appropriate bonding pads in the centre of the toroid (e.g. direct bond to rectifier diodes).
  • conductor ring/s may be used on paralleled conductors outside the toroid; this may be useful for bonding purposes where a preformed secondary winding is employed.
  • the size of the conductive pattern depends on the desired winding resistance, the dimensions of the core and the required minimum spacing (for electrical isolation) between primary and secondary conductors. (Currently for safety isolation from mains supply this must be greater than 400 ⁇ m).
  • a permeable soft magnetic core in this case a commercially available toroid of ferrite coated with insulation
  • the core may be adhesively attached (e.g. with thermally conductive adhesive) to the substrate to give mechanical strength and good heat transfer.
  • Means for completing the turns e.g.
  • ultrasonic, thermosonic, thermocompression wire or ribbon bonder or solder/silver soldering, resistance or laser welding equipment are then employed (in this case soldered copper wire is used).
  • foil or ribbon conductors are used the thickness is again typically 1.5 to 2 times skin depth.
  • the width of conductors depends on required resistance and minimum spacing.
  • conductor diameter is typically twice skin depth (overall diameter with enamel insulation being roughly 130 ⁇ m in this case). Note that in order to reduce resistance with circular wire, (Fig. 15(a)) multiple strands can be connected in parallel within a single turn to approximate to a wide foil or ribbon (Fig. 15(b)).
  • each turn should be a single wire with alternate primary and secondary turns; however this ofter becomes impractical because of minimum spacing requirements and the added complexity of a combination of series and parallel primary turns. In the present case the reduction of the peak mmf, driving leakage flux, to one twelfth of its usual value is sufficient to render proximity effect losses negligible).
  • a combination of the techniques of Figures 15(a) and 15(b) could be used.
  • the completed transformer (Fig. 16(a) now consists of 12 primary turns P all connected in series, with connections outside the toroid, and two secondary windings, S 1 , S 2 , each with 12 paralleled turns, interleaved with the primary, with a common centre tap connection C, terminated in the centre of the toroid to give optimum current sharing in each secondary turn.
  • Rectifier diodes (not shown) may be placed in the centre of the transformer so that the space is used and D.C. can be led out.
  • the planar transformer has six primary turns and one secondary turn. Hence the square of the primary to secondary turns ratio, which determines leakage inductance, is 36 as opposed to 144 for the present device. Nevertheless, at 1MHz, the leakage inductance of the present transformer is only twice that of the planar structure, showing a two-to-one improvement.
  • FIG. 20 Overall dimensional drawings of the two transformers are given (Fig. 20). These drawings indicate a footprint area of 1210 mm 2 and a volume of 11492 mm 3 for the planar part with the present device occupying 707 mm 2 (or 900 mm 2 if considering square area) and 5656 mm 3 (or 7200 mm 3 if considering cube volume). Furthermore, the area/volume in the centre of the present device (included in figures) can be used for other components (e.g. rectifier diodes). Both transformers are designed to operate at frequencies around 1 MHz with a power throughput of about 150 W. Taking the circuit of Fig. 21 with a secondary RMS voltage of 6V for a 5V output, assuming 0.
  • planar transformer has a core volume of 4920 mm 3 , the present core volume being 2140 mm 3 .
  • total core losses are 116 mW and 885 mW respectively.
  • Total winding losses (I 2 R) are 6.08 and 2. 56 W giving overall losses of 6.2 and 3.45 W respectively.
  • the present transformer is clearly more efficient in this application and, despite its smaller footprint, has a similar heat dissipation to footprint ratio (about 5 mW per mm 2 ).
  • a power transformer or coupled inductor employing interleaving of individual primary and secondary physical turns on one or more layers around a permeable or air core to give optimal coupling and minimal magnetic leakage, with the resultant virtual elimination of proximity effect losses.
  • the physical turns thereof are appropriately sized so as to eliminate skin effect losses.
  • Such a transformer or coupled inductor preferably employs a toroidal core on which the sum of the mutual magnetic couplings between any one physical turn, and all the other turns, is identical for each turn, leading to optimal current distribution in the windings.
  • the core is preferably shaped to facilitate 'winding', and preferably printed, etched, plated or otherwise formed conducting tracks on a substrate form part of the windings, the turns being completed by conducting wire or ribbon bonds (which may or may not be placed on an insulating former) or by conducting punched, etched or otherwise formed preforms or by printed, etched, plated or otherwise formed conductors on a shaped or flexible substrate.
  • conducting wire or ribbon bonds which may or may not be placed on an insulating former
  • conducting punched, etched or otherwise formed preforms or by printed, etched, plated or otherwise formed conductors on a shaped or flexible substrate Alternatively, part or all of each or any turn are formed by printed, etched, placed or otherwise devised conductors on the core itself.
  • a step-down transformer or coupled inductor embodying the invention may have a multi-turn primary (e.g. N turns in series) and a single turn secondary (e.g. N turns in parallel) with the secondary terminated (e. g. by rectifier diode/s) in the centre of the toroid to give optimal current sharing in the paralleled secondary turns.
  • multi-turn and multiple secondary windings can also be made, using series and parallel combinations of turns with minimized leakage flux and a.c. resistance. Non-optimal solutions also exist, which may be more suitable for practical implementation.
  • the primary is driven (e.g. by a switching device/s) in the centre of the core.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Coils Or Transformers For Communication (AREA)
  • Coils Of Transformers For General Uses (AREA)

Abstract

Un transformateur ou un inducteur couplé, avec n'importe quel rapport de transformation arbitraire (par exemple non intégral), et éventuellement avec des enroulements secondaires multiples (S1, S2), comprend des enroulements primaires et secondaires entrelacés (P, S1, S2; P, S1, S2) sur la même couche d'enroulement, de préférence autour d'un noyau sans fer ou magnétiquement perméable. Ceci permet d'obtenir un couplage magnétique optimal, des champs de dispersion minimaux et des pertes par effet de proximité négligeables. Le rapport de transformation électrique est déterminé par des connexions en série ou parallèles, ou en série-parallèle combinées, des spires physiques de chaque enroulement.

Claims (18)

  1. Transformateur présentant un rapport de spires arbitraire dans lequel les spires physiques de primaire (P) et de secondaire (S) ne sont pas bifilaires et dans lequel les spires de primaire et de secondaire sont distribuées sur des parties d'un noyau du transformateur, caractérisé en ce que les spires physiques de primaire et de secondaire sont entrelacées sur la même couche d'enroulement, chaque dite partie du noyau contenant des spires provenant de tous les enroulements du transformateur de telle sorte que dans chaque partie, en utilisation, la force magnétomotrice qui pilote un flux de fuite soit minimisée.
  2. Inducteur couplé présentant un rapport de spires arbitraire, dans lequel les spires physiques de primaire et de secondaire ne sont pas bifilaires et sont entrelacées sur la même couche d'enroulement et dans lequel les spires de primaire (P) et de secondaire (S) sont distribuées sur des parties d'un noyau de l'inducteur, chaque partie contenant des spires provenant de tous les enroulements de l'inducteur de telle sorte que dans chaque partie, si l'inducteur devait être utilisé en tant que transformateur, la force magnétomotrice qui pilote un flux de fuite soit minimisée.
  3. Transformateur selon la revendication 1, dans lequel le noyau est toroïdal et les parties sont des secteurs équi-angulaires de celui-ci.
  4. Inducteur couplé selon la revendication 2, dans lequel le noyau est toroïdal et les parties sont des secteurs équi-angulaires de celui-ci.
  5. Transformateur ou inducteur couplé selon la revendication 1 ou 2, dans lequel le rapport de spires est non entier.
  6. Transformateur ou inducteur couplé selon la revendication 1 ou 2, dans lequel le rapport de spires est autre que l'unité.
  7. Transformateur ou inducteur couplé selon la revendication 1 ou 2, dans lequel les spires de primaire et de secondaire sont entrelacées autour d'un noyau magnétiquement perméable ou d'un noyau d'air.
  8. Transformateur ou inducteur couplé selon la revendication 1 ou 2, dans lequel chaque enroulement est constitué par des spires physiques d'un matériau conducteur autour d'un noyau et dans lequel le rapport des spires électriques est déterminé par des connexions de montage série, de montage parallèle ou de montage combinaison série-parallèle des spires physiques de chaque enroulement.
  9. Transformateur ou inducteur couplé selon la revendication 1 ou 2, dans lequel plus d'une telle couche de spires entrelacées sont prévues.
  10. Transformateur ou inducteur couplé selon la revendication 9, dans lequel les spires physiques de primaire et de secondaire sont entrelacées à la fois dans chacune des couches et également depuis une couche jusqu'à une couche superposée.
  11. Transformateur ou inducteur couplé selon la revendication 1, 2 ou 10, dans lequel une partie d'au moins une spire physique est constituée par un conducteur formé sur un matériau de substrat.
  12. Transformateur ou inducteur couplé selon la revendication 1, 2 ou 10, dans lequel au moins l'un des enroulements est terminé dans une région entourée par son noyau autour duquel les spires de primaire et de secondaire de ces enroulements sont entrelacées.
  13. Transformateur ou inducteur couplé selon l'une quelconque des revendications précédentes, comprenant en outre un composant ou des composants de circuit électronique supplémentaire(s) situé(s) dans une région entourée par un noyau du transformateur ou de l'inducteur couplé et dans lequel les enroulements incluant lesdites spires sont adaptés pour une connexion au composant de circuit ou à chaque composant de circuit.
  14. Procédé de fabrication d'un transformateur ou inducteur couplé selon la revendication 1, 2, 10 ou 13, incluant l'étape de formation d'une partie de chaque spire physique sur un matériau de substrat par impression, gravure ou placage d'un matériau conducteur.
  15. Procédé de fabrication d'un transformateur ou inducteur couplé selon la revendication 1, 2, 10 ou 13, incluant l'étape de formation d'une partie de chaque spire physique sur chacune d'un certain nombre de couches de substrat et de constitution de vias thermiquement conductrices (D, figure 14(a)) pour connecter les différentes couches.
  16. Procédé de fabrication d'un transformateur ou inducteur couplé selon la revendication 1, 2, 10 ou 13, incluant l'étape de formation d'une partie d'au moins une spire physique en tant que conducteur sur un noyau autour duquel les spires de primaire et de secondaire sont entrelacées.
  17. Procédé de fabrication d'un transformateur ou inducteur couplé selon la revendication 11, incluant l'étape de formation d'une partie de la spire physique en tant que boucle en un matériau conducteur sur le noyau, où ce matériau est lié à chaque extrémité au conducteur respectif qui est formé sur le substrat.
  18. Transformateur ou inducteur couplé selon la revendication 1, 2, 10 ou 13, dans lequel une pluralité des enroulements secondaires sont formés à partir de certaines correspondantes interconnectées de façon appropriée des spires physiques de secondaire entrelacées.
EP91916278A 1990-09-07 1991-09-04 Transfomateurs de puissance et inducteurs couples avec entrelacement optimal d'enroulement Expired - Lifetime EP0547120B1 (fr)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
GB909019571A GB9019571D0 (en) 1990-09-07 1990-09-07 Power transformers and coupled inductors with optimally interleaved windings
GB9019571 1990-09-07
PCT/GB1991/001505 WO1992004723A1 (fr) 1990-09-07 1991-09-04 Transfomateurs de puissance et inducteurs couples avec entrelacement optimal d'enroulement

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EP0547120A1 EP0547120A1 (fr) 1993-06-23
EP0547120B1 true EP0547120B1 (fr) 1996-06-05

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US (1) US5543773A (fr)
EP (1) EP0547120B1 (fr)
DE (1) DE69120085T2 (fr)
GB (1) GB9019571D0 (fr)
WO (1) WO1992004723A1 (fr)

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JPH06290972A (ja) * 1993-03-31 1994-10-18 Mitsubishi Electric Corp 金属プリント基板上で製作するリアクトル及びそのリアクトルを使用したインバータ装置
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EP0547120A1 (fr) 1993-06-23
US5543773A (en) 1996-08-06
WO1992004723A1 (fr) 1992-03-19
DE69120085D1 (de) 1996-07-11
GB9019571D0 (en) 1990-10-24
DE69120085T2 (de) 1997-02-06

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