EP0273926A1 - Procede de mise en action d'un circuit de reglage et circuit de reglage fonctionnant selon ce procede - Google Patents

Procede de mise en action d'un circuit de reglage et circuit de reglage fonctionnant selon ce procede

Info

Publication number
EP0273926A1
EP0273926A1 EP87903679A EP87903679A EP0273926A1 EP 0273926 A1 EP0273926 A1 EP 0273926A1 EP 87903679 A EP87903679 A EP 87903679A EP 87903679 A EP87903679 A EP 87903679A EP 0273926 A1 EP0273926 A1 EP 0273926A1
Authority
EP
European Patent Office
Prior art keywords
voltage
comparator
input
output
flyback converter
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP87903679A
Other languages
German (de)
English (en)
Inventor
Domenic Melcher
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Melcher Elektronische Gerate AG
Original Assignee
Melcher Elektronische Gerate AG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Melcher Elektronische Gerate AG filed Critical Melcher Elektronische Gerate AG
Publication of EP0273926A1 publication Critical patent/EP0273926A1/fr
Withdrawn legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters

Definitions

  • the present invention relates to a power supply device from the class of switching regulators or switching power supplies and from this class the subgroup of flyback converters.
  • the state of the art in relation to flyback converters is shown in the document "Switching Power Supplies” by Joachim Wüstehube (ed.), Grafenau / Berlin. Supplements to the state of the art can be found in the "Technical Notice” 3/85, Siemens AG, Kunststoff.
  • the direct short-circuit on the secondary side causes an almost complete breakdown of the output voltage U 0 when operating at a fixed frequency, combined with a sharp rise in the current. Therefore, the short circuit is answered by switching off the switching regulator and switching it on again with a so-called slow start circuit. If the short circuit persists, this process is repeated as often as desired, with the current increasing again and again in accordance with the threshold characteristic.
  • - Switching frequency should be variable but limited so that there is no relationship to an internal phase position of the controller; it should be limited and reasonably stable to prevent the prostitutes 1 to facilitate ionization and to stay outside the listening area.
  • 5 flyback converters according to the invention are characterized in that the output voltage U 0 , the maximum average output current Io, the demagnetization of the transformer via the minimum secondary current, the maximum input voltage-time integral in
  • the method and the device are characterized in that the value of the input voltage-time integral specified by the apparatus is reduced if the maximum output current at the voltage Uo is not used, as a result of which both the input
  • Switching time t » and the pause length thousand can be shortened; the switching frequency thus remains variable within narrow limits.
  • FIG. 2 an extension of FIG. 1 with additional monitoring and control functions
  • Fig. 3 shows the voltage and current curves over time
  • Fig. 4 shows the basic circuit diagram of a flyback converter
  • Fig. 5 shows the circuit diagram of the flyback converter according to the invention
  • FIG. 6 shows a first detailed variant of FIG. 5
  • FIG. 7 shows a second detailed variant of FIG. 5
  • Fig. 8 variants for obtaining a control signal in a flyback converter with several outputs.
  • a flyback converter 61 is subdivided into a primary part 62 and a secondary part 63.
  • the control method is implemented by five function blocks 64, 65, 66, 67, 68.
  • Function block 64 forms the integral
  • FIG. 4 shows the voltage and current curves over time that arise in a flyback converter according to the basic circuit diagram shown as FIG. 4.
  • the rectified direct voltage UE smoothed with the aid of a capacitor 3 is switched to the primary winding 1 of a transformer 2 with the aid of a transistor 4.
  • the transistor 4 is operated in a clocked or blocking manner by the control loop - which is formed by the function blocks 64 to 68 in FIG. 1.
  • a current will only flow on the secondary winding 5 of the transformer 2, owing to its connection to a diode 6, a capacitor 7 and possibly an external load 8, when the transistor 4 blocks.
  • FIG. 3a shows the voltage curve at the primary winding 1.
  • the output voltage Uo of the barrier wall which is transformed back by the translation ratio ü lers.
  • t e in) The extended current course applies to the so-called triangular mode, the dashed line for the trapezoidal mode. It is general
  • the voltage-time area formed by the integral is therefore a direct measure of Ipmax • W ⁇ rc * ⁇ acn t made the transistor 4 blocking, the maximum energy has been transferred to the primary winding:
  • Ipmax is determined by integral formation. If a predetermined value has been reached, the control phase of the transistor 4 is ended by a control signal to a bistable switch 70, which in turn acts on the transistor 4.
  • the function block 65 which receives its input signal from the secondary side 63 of the flyback converter 61, monitors this value and sends a control signal to an AND gate 69 when a predetermined threshold is reached.
  • the maximum current I 0 is monitored by the function block 66.
  • This function block only then sends a control or release signal to the AND gate 69 if the output current remains below the predetermined threshold I 0 .
  • a short circuit on the secondary side has the consequence here that the output current rises to this maximum value.
  • the short circuit is to be distinguished from sudden load changes by means of a suitable current notification method. Its input signal refersrhythms ⁇ the block 66 by the function block 65 - "since the integral of the secondary current i s over t from the time mean value of the output current corresponding to the circuit is short-circuit proof now..
  • the function block 67 monitors the output voltage Uo of the secondary side 63 of the flyback converter 61. It outputs its release control signal to the AND gate 69 if the predetermined size is undershot.
  • the time course of i s is given by
  • the comparison threshold which limits the size of the voltage-time integral in function block 64, is influenced by a further function block 68. Depending on the pause length t a us, the threshold for
  • the length of the break is also shortened, because - due to the smaller transmitted energy - the thresholds of the function blocks 65, 66, 67 are also closer
  • the frequency remains above a minimum frequency determined by the function block 68, both in the event of a short circuit and when idling.
  • FIG. 2 shows an expansion of the method according to FIG. 1 according to the invention by three further function blocks 71, 72, 73.
  • the function block 71 monitors the input voltage U for exceeding a predetermined maximum value; function block 72 blocks when U falls below a minimum value; Finally, the function block 73 is used for remote control and allows the bistable switch 70 to be held in the position in which the transistor 4 blocks.
  • a barrier wall 1er which corresponds to that of FIG. 4, is supplemented by a measuring resistor 9 and a voltage divider, consisting of resistors 27, 28, which divide the output voltage Uo.
  • the partial voltage UoR is fed to a comparator 29, which compares it with a reference voltage Upef. If U 0 R - ⁇ - U re f, the output of the comparator 29 is raised and feeds an input 30 of an AND gate 18.
  • the comparator 29 is the switching element corresponding to the function block 67; ., the AND gate 18 corresponds to the AND gate 69 of Figures 1 and 2.
  • the secondary current i s produced across the sense resistor 9 a wastehers ⁇ URS "in a comparator 20 with a small voltage Schwellenspan- URs m ⁇ - is compared to n . If URs- ⁇ URSmin ⁇ r ⁇ ⁇ c ' he output of the comparator 20 is raised and thus controls a further input 19 of the AND gate 18.
  • the threshold URSmin is reached when the transformer 2 is sufficiently de-magnetized to be from the Primary winding 1 to be re-magnetized. This prevents the core of the transformer 2 from becoming saturated.
  • the voltage URS is simultaneously applied to a resistor 33 which, together with a capacitor 34, forms an RC element.
  • the time constant of this RC element is large compared to the expected length of the switching frequency.
  • the comparison voltage U ⁇ 0 is the output of the comparator is Kom ⁇ 31 is only set high so chosen if URS ⁇ U IO. If this condition is not met - which is the case in the event of a short circuit, the AND gate 18 remains blocked since the comparator 31 connects to a further input 32 of the AND
  • the comparator 20 corresponds to the function block 65, the comparator 31 together with the RC element 33, 34 forms the function block 66.
  • Function block 64 shown in FIG. 5 (outlined with dashed lines), contains a comparator 13 which compares its voltage from function block 68
  • the input signal of the comparator 13 is obtained on an RC element consisting of a resistor 10, which is connected to the UE, and a capacitor 11.
  • Another RC element consisting of a resistor 47 and a capacitor 46, is connected to a constant voltage U ⁇ st ⁇ Ref *
  • the comparator 49 which is provided, for example, with an open collector output, then discharges a further capacitor 51 with the time constant given by the combination of two resistors 50, 52 and the capacitor 51 onto which Voltage, which is given by UR e f, which is present at resistor 52, and the division ratio of resistors 50, 52.
  • This voltage which is determined in this way, serves as a comparison voltage for the comparator 13. If the pause is a thousand short enough, the open collector output of the 5 comparator 49 remains inactive and the comparator 13 is connected to the resistor 52 the full reference voltage. This corresponds to the operation at maximum voltage-time area. The longer the time, thousand, the lower the comparison voltage for the comparator 13. This results in a shortening .
  • the above-mentioned switching elements 46 to 52 together form the functional block 68 according to FIGS. 1 and 2.
  • the comparator 13 acts on an individual pulse generator 14, which simultaneously transmits its output signal to a flip-flop 15 and an inverter 16.
  • the flip-flop 15 corresponds to the bistable switch 70 of FIGS. 1 and 2.
  • the pulse from the individual pulse generator 14 signals the end of the phase t e in u ⁇ is applied to the reset input R of the flip-flop 15. As a result, its output Q "is increased : phase thousand begins.
  • the switching elements contained in the function blocks 64, 68 thus represent a frequency control loop which regulates slowly in comparison to the switching frequency of the flyback converter.
  • the output signals of the inverter 16 and the comparators 20, 29, 31 are located at the AND gate 18. If two further comparators 53, 55 and an inverter 58 are initially disregarded, the output of the AND gate 18 is set high when the comparators 20, 29, 31 mentioned also have outputs which are set high.
  • the output of the inverter 16, which acts on an input 17 of the AND gate 18, is constantly high, with the exception of the pulse from the individual pulse generator 14. This prevents the simultaneous application of set and reset commands to the flip-flop 15 and defines a minimum duration of t a us »which corresponds to the pulse length of the individual pulse generator 14.
  • the comparators 53, 55 are used to monitor the input voltage U of the flyback converter, which supplies its input signal via two voltage dividers 74, 75.
  • the output of comparator 53 is set low when its input voltage becomes greater than the set threshold; the output of comparator 55 is set low when the minimum input The voltage falls below the set threshold. So wi rd t ei ne additional phase en prevented.
  • the inverter 58 the output of which is normally high, is used for remote control of the flyback converter according to the invention.
  • the comparators 53, 55 and the inverter 58 act on the inputs 54, 56, 57 of the AND gate 18.
  • the signal for the comparators 13, 20, 29 can be used simultaneously with the solution shown in FIG. 7 and 31 can be won.
  • 5 carries a third winding 24.
  • a capacitor 26, which forms an RC element together with a resistor 25 is charged, the voltage U c increases linearly, provided that RC ⁇ t a .
  • the capacitor 26 is discharged or reloaded in the time t off , and the voltage drops linearly.
  • the voltage rise is processed by the comparator 13, the drop by the comparator 20 or the comparator 31.
  • the reverse voltage of the winding 24 can be rectified via a diode (not shown) and can be screened in a known manner by means of a filter capacitor. An image of the output voltage U 0 is then obtained on this filter capacitor, which can be supplied to the comparator 29 for voltage regulation. It can be seen that the function blocks 64 to 68 are both primary and can be arranged secondary or mixed.
  • each individual output, or several together can be monitored for short-circuiting or simply exceeding the limit current I 0 .
  • Such devices are shown in Fig. 8a, b. Representing several outputs, two of them are provided here. 8a, the secondary winding 5 from FIG. 5 is divided into two partial windings 35, 36,. which each work via a diode 37, 38 on a capacitor 39, 40.
  • a resistor 41 is connected in series with the partial windings 35, 36, which thus monitors the sum of the output currents and the measuring resistor 9 from FIG 5 corresponds to.
  • a prerequisite for the functioning of the monitoring is that the consumers both work against ground.
  • FIG. 8b A variant of this is shown in Fig. 8b.
  • each output circuit has an individually monitored secondary winding 42.43.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Measurement Of Current Or Voltage (AREA)

Abstract

Le procédé de mise en action repose sur l'existence et la coopération d'au moins six blocs fonctionnels (64, 65, 66, 67, 68, 70), les blocs fonctionnels (65, 66, 67) ayant une fonction de surveillance et de commande, les blocs (64, 68, 70) formant ensemble le circuit de réglage de fréquence et de temps de repos. Le bloc (65) surveille la démagnétisation du transformateur (2), le bloc (66), le courant de sortie moyen dans le temps et le bloc (67) la tension de sortie du circuit de réglage. Le bloc fonctionnel (64) forme l'intégrale dans le temps de la tension d'entrée et le bloc (68) établit la valeur de consigne de cette intégrale selon la durée du temps de repos déterminée. Le procédé peut être élargi à la surveillance de la tension d'entrée quant au dépassement d'une valeur maximale par un bloc fonctionnel (71) et quant à une descente au-dessous d'une valeur minimale par un bloc fonctionnel (72). Une nouvelle phase d'enclenchement ne peut commencer que lorsque tous les blocs fonctionnels (65, 66, 67, 71, 72) à fonction de surveillance délivrent un signal de déblocage à une porte ET (69) qui commande un commutateur bistable (70).
EP87903679A 1986-07-03 1987-06-18 Procede de mise en action d'un circuit de reglage et circuit de reglage fonctionnant selon ce procede Withdrawn EP0273926A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
CH2687/86 1986-07-03
CH268786 1986-07-03

Publications (1)

Publication Number Publication Date
EP0273926A1 true EP0273926A1 (fr) 1988-07-13

Family

ID=4239316

Family Applications (1)

Application Number Title Priority Date Filing Date
EP87903679A Withdrawn EP0273926A1 (fr) 1986-07-03 1987-06-18 Procede de mise en action d'un circuit de reglage et circuit de reglage fonctionnant selon ce procede

Country Status (5)

Country Link
US (1) US4864480A (fr)
EP (1) EP0273926A1 (fr)
JP (1) JPH01500080A (fr)
KR (1) KR880701994A (fr)
WO (1) WO1988000408A1 (fr)

Families Citing this family (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0419724B1 (fr) * 1989-09-29 1994-02-16 Siemens Aktiengesellschaft Disposition de circuit pour alimentation à découpage du type à récupération
US5305192A (en) * 1991-11-01 1994-04-19 Linear Technology Corporation Switching regulator circuit using magnetic flux-sensing
FR2725324B1 (fr) * 1994-09-30 1996-12-20 Sgs Thomson Microelectronics Regulateur de courant a decoupage
DE19514555A1 (de) * 1995-04-20 1996-10-24 Bettermann Obo Gmbh & Co Kg Schaltungsanordnung einer Ladeschaltung für einen Schweißkondensator
US5680034A (en) * 1995-09-22 1997-10-21 Toko, Inc. PWM controller for resonant converters
EP1124315B1 (fr) * 2000-02-11 2007-01-03 Semiconductor Components Industries, LLC Alimentation à découpage avec mode de suppression d'impulsion programmable
KR20080086927A (ko) 2000-10-13 2008-09-26 엔엑스피 비 브이 스위치 모드 전원 및 집적 회로 및 모니터링 방법
US20060133115A1 (en) * 2004-12-22 2006-06-22 Phadke Vijay G Adaptive blanking of transformer primary-side feedback winding signals

Family Cites Families (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CA1069177A (fr) * 1976-07-21 1980-01-01 Gte Lenkurt Electric (Canada) Ltd. Regulateur de commutation serie a courant constant
WO1984000085A1 (fr) * 1982-06-14 1984-01-05 Domenic Melcher Procede pour commander une tension et appareil d'alimentation correspondant
US4504898A (en) * 1983-06-06 1985-03-12 At&T Bell Laboratories Start-up transient control for a DC-to-DC converter powered by a current-limited source
US4612610A (en) * 1984-03-06 1986-09-16 Hughes Aircraft Company Power supply circuit utilizing transformer winding voltage integration for indirect primary current sensing
US4654771A (en) * 1984-08-07 1987-03-31 Siemens Aktiengesellschaft Switched power supply comprising a free-running flow converter and electrically separated control loop
US4739462A (en) * 1984-12-26 1988-04-19 Hughes Aircraft Company Power supply with noise immune current sensing

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
See references of WO8800408A1 *

Also Published As

Publication number Publication date
JPH01500080A (ja) 1989-01-12
KR880701994A (ko) 1988-11-07
US4864480A (en) 1989-09-05
WO1988000408A1 (fr) 1988-01-14

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