EP0127101B1 - Convertisseur à courant alternatif continu pour alimenter des lampes à décharge - Google Patents

Convertisseur à courant alternatif continu pour alimenter des lampes à décharge Download PDF

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Publication number
EP0127101B1
EP0127101B1 EP84105786A EP84105786A EP0127101B1 EP 0127101 B1 EP0127101 B1 EP 0127101B1 EP 84105786 A EP84105786 A EP 84105786A EP 84105786 A EP84105786 A EP 84105786A EP 0127101 B1 EP0127101 B1 EP 0127101B1
Authority
EP
European Patent Office
Prior art keywords
voltage
inverter
capacitor
control
lamp
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired
Application number
EP84105786A
Other languages
German (de)
English (en)
Other versions
EP0127101A1 (fr
Inventor
Peter Ing. Grad. Krummel
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Siemens AG
Original Assignee
Siemens AG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Siemens AG filed Critical Siemens AG
Priority to AT84105786T priority Critical patent/ATE25800T1/de
Publication of EP0127101A1 publication Critical patent/EP0127101A1/fr
Application granted granted Critical
Publication of EP0127101B1 publication Critical patent/EP0127101B1/fr
Expired legal-status Critical Current

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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • H05B41/295—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices and specially adapted for lamps with preheating electrodes, e.g. for fluorescent lamps
    • H05B41/298—Arrangements for protecting lamps or circuits against abnormal operating conditions
    • H05B41/2981—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions
    • H05B41/2985—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions against abnormal lamp operating conditions

Definitions

  • the invention relates to an inverter according to the preamble of claim 1.
  • the inverter is adapted to a certain lamp power, the operating frequency of the inverter and the inductance of the inductor of the series resonant circuit being dimensioned at this operating frequency so that the discharge lamp receives the current required for its nominal power ; a very specific operating voltage is assumed.
  • Discharge lamps with the same nominal power have been on the market for some time now, which differ in their gas filling (previously only krypton, now also argon) and thus also in their burning voltage: Discharge lamps with argon filling have a significantly higher burning voltage. You would therefore consume an impermissibly high power with an inverter designed for a Krypton lamp.
  • the invention is therefore based on the object of designing the inverter so that it can be used for supplying lamps of the same nominal power regardless of their gas filling and thus of their operating voltage.
  • the inventive solution to this problem is characterized in claim 1.
  • the headset can have a pulse generator, the frequency of which increases with an input variable derived from the operating voltage of the discharge lamp: if this characteristic curve is designed accordingly, the frequency matching the respective operating voltage and thus the required lamp current are automatically set.
  • the frequency of the pulse generator can also be switchable, depending on whether certain threshold values of the operating voltage have been reached or fallen below.
  • Sufficient preheating of its electrodes is usually desirable before the discharge lamp is ignited.
  • it is known to increase the operating frequency of the inverter during a preheating time to such an extent that it is at a sufficient distance from the resonance frequency of the resonance circuit so that the voltage at the lamp is not sufficient for ignition. After this preheating time has elapsed, the operating frequency is reduced and approximated to the resonance frequency until the voltage at the lamp is sufficient for ignition.
  • an evaluator is provided between the headset and the combustion voltage sensor, to which the voltage of a timing element located at the input of the inverter is also fed and which during a preheating time beginning when the inverter is switched on and a subsequent ignition time determines the frequency of the control voltages and which then allows the output signal of the internal voltage sensor for the headset to take effect.
  • the operating frequency of the inverter is therefore not determined by the operating voltage but by the timing element, which in the simplest case is an RC element or a monostable multivibrator.
  • the switches of the inverter are field-effect power transistors T1, T2, which are connected in series to the DC voltage source Q.
  • the load circuit with a reversing capacitor C10, the discharge lamp LP and the series resonance circuit with the capacitor C9 and the choke L1 is parallel to T1, the capacitor C9 of the series resonance circuit being located between the heatable electrodes of the lamp.
  • T2 When T2 is activated, the load circuit is located at source Q and reloads in the following half-wave via activated T1.
  • a control set S with a pulse generator g, which generates control pulses with an adjustable frequency, is used to alternately control the transistors T1 and T2; these are alternately applied to the two transistors via a pulse distributor i.
  • the frequency of the pulses of the generator g is dependent on the output signal of the evaluator A, which is connected on the input side to a combustion voltage sensor B and to a timing element Z with two outputs z1, z2, and which essentially has the function of one of these inputs, depending on the operating phase to connect to the pulse generator g.
  • the evaluator A After switching on the DC voltage source Q, the evaluator A activates the first output z1 of the timing element Z, the voltage of which ensures the maximum operating frequency f v between the times t o and t 1 (preheating time): see FIG. 2. At this frequency, the Do not ignite the lamp. At time t 1 , the evaluator A - controlled by Z - switches on the second output z2 of the timing element, which supplies a smaller or a continuously decreasing voltage up to time t 2 : the associated lowering of the operating frequency leads to the vicinity of the resonance frequency of the resonance circuit and thus to the ignition of the lamp.
  • the evaluator After the time t 2 , the evaluator finally switches over to the operating voltage sensor B, so that an output signal dependent on the operating voltage of the lamp is then present at the pulse generator, which has an operating frequency f BA higher for an argon lamp and a lower operating frequency for a krypton lamp F BK (dotted line in Fig. 2) results.
  • a saturation transformer L2 is essentially used as the control set, the primary winding L21 of which is arranged in the load circuit and the secondary windings L22, L23 of which are connected to the control paths of the transistors T1, T2.
  • the load circuit and the saturation transformer are dimensioned in such a way that the lowest possible operating frequency, that is to say that for supplying a krypton lamp, is obtained without the interventions according to the invention described below.
  • the turn-through time of T2 is shortened with the aid of blocking transistors T3, T4, by which the control path of T2 is short-circuited.
  • the emitter of T4 is connected to a synchronizing capacitor C3, which is connected via a series resistor R2 to the DC voltage source Q and via a series capacitor C2 to the switching path of the transistor T2 to be blocked prematurely.
  • the course of the sawtooth voltage Des at the emitter of the blocking transistor T4 is shown in FIG. 4.
  • T4 lies on a voltage divider with the resistors R3, R4 and a comparison capacitor C4, on which a reference voltage which can be controlled in size occurs.
  • C4 is connected in parallel to a control transistor T5 and is also connected via R5 to an auxiliary voltage source which is formed by a capacitor C5 which is connected in parallel with the synchronization capacitor C3 via a charging diode D4.
  • the current of the load circuit continues to flow in the same direction, namely via the reverse current diode of transistor T1 (integrated in MOS-FET transistors).
  • the saturation transformer at L22 then generates a control voltage for T1, via which the discharge current of the reversing capacitor C10 can flow through the load circuit in the opposite direction.
  • the duration of this half-wave depends on the saturation transformer and is essentially constant; in this case, the change in the resulting operating frequency is only achieved by shortening the one half-wave determined by T2.
  • the magnitude of the reference voltage U c4 at the comparison capacitor C4 can be set differently by the control transistor T5 connected in parallel.
  • the control path of this transistor is connected to a voltage divider with resistors R6 and R7 and a Zener diode D8 and a voltage divider R8. R9 on a capacitor C8, which charges via D9 or D10, C7 and R12 to a value dependent on the lamp voltage.
  • R6 and R7 are connected in parallel to a capacitor C6, which is connected via a decoupling diode D6 to an RC element R1, C1 and is charged by the DC voltage source Q via resistors R11, R10 and an electrode of the lamp LP.
  • the voltage at C1 controls the transistor T2 via the switching diode D2 when the inverter is switched on, but then disappears because C1 is discharged via D1 and T2. Therefore, the decoupling diode D6 is blocked after the inverter starts to oscillate:
  • the control transistor T5 is therefore only activated after the inverter has started to oscillate during a short discharge time of the capacitor C6, which determines the preheating time with the resistors R6 and R7.
  • the blocking transistor T4 becomes conductive in each period due to the low reference voltage U c4v in time t S1 (FIG. 4) and thus the half-wave flowing via T2 is shortened.
  • the resulting increase in the operating frequency results in a correspondingly low voltage across the capacitor C4 in parallel with the discharge lamp LP, so that it cannot ignite.
  • T5 is increasingly controlled and thus the reference voltage at C4 increases, so that the half-waves flowing over T2 become longer and longer until the resulting operating frequency has approached the resonance frequency of the load circuit to such an extent that the lamp ignites.
  • T3, T4 and T5 are then blocked and the operating frequency is the same long half-waves, which is determined exclusively by the saturation transformer and is dimensioned for the operation of a Krypton lamp.
  • the voltage occurring at the capacitor C8 is too low to be able to again control the control transistor T5 via the zener diode D8.
  • the voltage at the capacitor C8 is also used to switch off the inverter when the lamp is permanently unable to ignite: If this voltage reaches a limit value specified by the monitoring device Ü, then this responds and short-circuits the starting capacitor C1 and the control electrode from T1 to D5.
  • the response threshold of this monitoring device is above the voltage that arises at C8 when the inverter is operated with an argon lamp.
  • the charging time constant of C8 is so great that the monitoring device cannot respond during the preheating and ignition phases, unless the lamp would not ignite in the specified time (t 1 / t 2 ).

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  • Circuit Arrangements For Discharge Lamps (AREA)
  • Ladders (AREA)
  • Medicines Containing Antibodies Or Antigens For Use As Internal Diagnostic Agents (AREA)

Claims (6)

1. Onduleur comportant deux commutateurs commandables (T1, T2), qui sont conducteurs en alternance, un circuit de charge parallèle au premier commutateur (T1) et qui est raccordé par l'intermédiaire du second commutateur (T2) à une source de tension continue (Q) et est constitué par le circuit série formé d'un condensateur à version de charge (C10), d'un circuit résonnant série constitué par une bobine d'arrêt (L1) et par un condensateur (C9), et d'une lampe à décharge (LP) possédant des électrodes pouvant être chauffées, ces électrodes étant situées dans le circuit de charge et étant reliées entre elles par l'intermédiaire du condensateur (C9) du circuit résonnant série, et comportant une unité de commande (S) qui délivre des tensions de commande commandant en alternance les commutateurs, caractérisé par un capteur (B) de la tension de décharge, qui contrôle la tension de décharge de la lampe (LP) et délivre un signal de sortie qui dépend de la tension de décharge et qui est envoyé à l'unité de commande (S) et détermine la fréquence des tensions de commande qui lui sont envoyées.
2. Onduleur suivant la revendication 1, caractérisé par un dispositif d'évaluation (A) disposé entre l'unité de commande (S) et le capteur (B) de la tension de décharge et auquel est envoyée en supplément la tension d'un circuit de temporisation (Z) relié à l'entrée de l'onduleur et qui, pendant une durée de préchauffage (to/tl), qui commence lors du branchement de la source de tension continue, et détermine la fréquence des tensions de commande pendant une durée de préchauffage (to/tl), qui commence avec le branchement de la source de tension continue, et pendant une durée d'amorçage (t1/t2), succédant à la durée de préchauffage, et laisse ensuite agir le signal de sortie du capteur (B) de la tension de décharge pour l'unité de commande (S).
3. Onduleur suivant la revendication 2, caractérisé par le fait que le dispositif d'évaluation (A) compare une tension en dents de scie (VC3) à une tension de référence (Vc4) et commande, en fonction de cette comparaison, un transistor de blocage (T3, T4) qui interrompt la tension de commande de l'un des commutateurs (T2) de l'onduleur, la tension en dents de scie étant prélevée sur un condensateur de synchronisation (C3) qui est raccordé par l'intermédiaire d'une résistance additionnelle (R2) à la source de tension continue (Q) et est branché en parallèle avec le commutateur (T2) devant être bloqué, par l'intermédiaire d'un condensateur additionnel (C2).
4. Onduleur suivant la revendication 3, caractérisé par le fait que la tension de référence (Vc4) est prélevée sur un condensateur de comparaison (C4) en parallèle avec lequel se trouve monté un transistor de commande (C5) dont la voie de commande est raccordée par l'intermédiaire d'une diode Zener (D8) à une source de tension (R8, R9, C8), qui délivre une tension proportionnelle à la tension aux bornes de la lampe (LP).
5. Onduleur suivant la revendication 4, caractérisé par le fait que la voie de commande du transistor de commande (T5) est raccordée à un circuit RC (R6, R7, C6), qui est chargé par l'intermédiaire d'une diode de découplage (D6) qui est conductrice uniquement entre le branchement de l'onduleur et le début de son entrée en oscillations.
6. Onduleur suivant la revendication 5, comportant un dispositif de contrôle qui débranche l'onduleur lorsqu'une lampe se trouve en permanence en état d'amorçage, caractérisé par le fait que le dispositif de contrôle (Ü) est également raccordé, côté entrée, à la source de tension (C8), qui est réalisée sous la forme d'un circuit RC (R8, R9, C8), et dont la constante de temps est suffisamment élevée pour que la tension aux bornes du condensateur (C8) n'atteigne pas le seuil de réponse du dispositif de contrôle, lorsque la lampe s'amorce en un intervalle de temps prédéterminé.
EP84105786A 1983-05-27 1984-05-21 Convertisseur à courant alternatif continu pour alimenter des lampes à décharge Expired EP0127101B1 (fr)

Priority Applications (1)

Application Number Priority Date Filing Date Title
AT84105786T ATE25800T1 (de) 1983-05-27 1984-05-21 Wechselrichter zur speisung von entladungslampen.

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE19833319352 DE3319352A1 (de) 1983-05-27 1983-05-27 Wechselrichter zur speisung von entladungslampen
DE3319352 1983-05-27

Publications (2)

Publication Number Publication Date
EP0127101A1 EP0127101A1 (fr) 1984-12-05
EP0127101B1 true EP0127101B1 (fr) 1987-03-04

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Family Applications (1)

Application Number Title Priority Date Filing Date
EP84105786A Expired EP0127101B1 (fr) 1983-05-27 1984-05-21 Convertisseur à courant alternatif continu pour alimenter des lampes à décharge

Country Status (4)

Country Link
EP (1) EP0127101B1 (fr)
AT (1) ATE25800T1 (fr)
DE (2) DE3319352A1 (fr)
FI (1) FI76906C (fr)

Cited By (20)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB2180418A (en) * 1985-09-14 1987-03-25 Contrology Limited Fluorescent lamp supply circuit
EP0241279A1 (fr) * 1986-04-08 1987-10-14 Actronic Lighting Cc Dispositif de réglage pour lampes luminescentes à gaz
EP0359860A1 (fr) * 1988-09-23 1990-03-28 Siemens Aktiengesellschaft Dispositif et procédé de mise en oeuvre d'au moins une lampe à décharge
GB2226463A (en) * 1988-12-21 1990-06-27 Sirous Yazdanian Control of fluorescent lights
EP0396621A1 (fr) * 1988-01-19 1990-11-14 Etta Industries, Inc. Ballast fluorescent atenuateur de lumiere utilisant un convertisseur d'ondes sinusoidales resonant
EP0413991A1 (fr) * 1989-07-28 1991-02-27 Toshiba Lighting & Technology Corporation Appareil d'alimentation d'une lampe à décharge commandant la lampe en fonction de son type
EP0422255A1 (fr) * 1989-10-09 1991-04-17 Siemens Aktiengesellschaft Ballast électronique
WO1991007863A1 (fr) * 1989-11-18 1991-05-30 Ac/Dc Lighting Limited Onduleurs et dispositifs pour lampes cathodiques
EP0435228A2 (fr) * 1989-12-29 1991-07-03 Zumtobel Aktiengesellschaft Circuit et procédé pour alimenter (et amorcer) une lampe à décharge
US5798617A (en) 1996-12-18 1998-08-25 Pacific Scientific Company Magnetic feedback ballast circuit for fluorescent lamp
US5866993A (en) 1996-11-14 1999-02-02 Pacific Scientific Company Three-way dimming ballast circuit with passive power factor correction
US5925986A (en) 1996-05-09 1999-07-20 Pacific Scientific Company Method and apparatus for controlling power delivered to a fluorescent lamp
US5955841A (en) 1994-09-30 1999-09-21 Pacific Scientific Company Ballast circuit for fluorescent lamp
US5982111A (en) 1994-09-30 1999-11-09 Pacific Scientific Company Fluorescent lamp ballast having a resonant output stage using a split resonating inductor
US6037722A (en) 1994-09-30 2000-03-14 Pacific Scientific Dimmable ballast apparatus and method for controlling power delivered to a fluorescent lamp
WO2000024233A2 (fr) * 1998-10-16 2000-04-27 Electro-Mag International, Inc. Circuit regulateur
US6169375B1 (en) 1998-10-16 2001-01-02 Electro-Mag International, Inc. Lamp adaptable ballast circuit
WO2001097574A2 (fr) * 2000-06-14 2001-12-20 Brenex Electrics Pty. Limited Circuit de commande pour tubes fluorescents
DE102008031409A1 (de) * 2008-07-02 2010-01-07 Tridonicatco Gmbh & Co. Kg Erkennung des Typs einer an einem Betriebsgerät angeschlossenen Gasentladungslampe
DE102008047440A1 (de) * 2008-09-16 2010-03-25 Tridonicatco Gmbh & Co. Kg Bestimmung des Typs eines Leuchtmittels oder der Topologie mehrerer Leuchtmittel

Families Citing this family (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE3521496A1 (de) * 1985-04-22 1986-10-23 Sorbios Verfahrenstech Verfahren und vorrichtung zur mittel- und hochfrequenten hochspannungsversorgung fuer impedanzartige lasten, insbesondere bei gasentladungen
DE3628989A1 (de) * 1986-08-26 1988-03-03 Ceag Licht & Strom Elektronisches vorschaltgeraet
US6160361A (en) * 1998-07-29 2000-12-12 Philips Electronics North America Corporation For improvements in a lamp type recognition scheme
US6677719B2 (en) * 2002-06-03 2004-01-13 Stmicroelectronics, Inc. Ballast circuit
US20050168171A1 (en) 2004-01-29 2005-08-04 Poehlman Thomas M. Method for controlling striations in a lamp powered by an electronic ballast

Family Cites Families (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4060752A (en) * 1976-03-01 1977-11-29 General Electric Company Discharge lamp auxiliary circuit with dI/dt switching control
DE2924331A1 (de) * 1979-06-15 1980-12-18 Siemens Ag Anordnung zum betrieb einer entladungslampe
DE2928490A1 (de) * 1979-07-14 1981-01-29 Frei Hans Joachim Elektrische schaltung zum betreiben von niederdruckentladungslampen
GB2095930A (en) * 1981-03-27 1982-10-06 Stevens Carlile R Constant power ballast

Cited By (25)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB2180418A (en) * 1985-09-14 1987-03-25 Contrology Limited Fluorescent lamp supply circuit
EP0241279A1 (fr) * 1986-04-08 1987-10-14 Actronic Lighting Cc Dispositif de réglage pour lampes luminescentes à gaz
EP0396621A1 (fr) * 1988-01-19 1990-11-14 Etta Industries, Inc. Ballast fluorescent atenuateur de lumiere utilisant un convertisseur d'ondes sinusoidales resonant
EP0396621A4 (en) * 1988-01-19 1992-01-15 Etta Industries, Inc. Fluorescent dimming ballast utilizing a resonant sine wave power converter
EP0359860A1 (fr) * 1988-09-23 1990-03-28 Siemens Aktiengesellschaft Dispositif et procédé de mise en oeuvre d'au moins une lampe à décharge
US5049790A (en) * 1988-09-23 1991-09-17 Siemens Aktiengesellschaft Method and apparatus for operating at least one gas discharge lamp
GB2226463A (en) * 1988-12-21 1990-06-27 Sirous Yazdanian Control of fluorescent lights
US5039921A (en) * 1989-07-28 1991-08-13 Toshiba Lighting And Technology Corporation Discharge lamp lighting apparatus for driving discharge lamp according to rating thereof
EP0413991A1 (fr) * 1989-07-28 1991-02-27 Toshiba Lighting & Technology Corporation Appareil d'alimentation d'une lampe à décharge commandant la lampe en fonction de son type
EP0422255A1 (fr) * 1989-10-09 1991-04-17 Siemens Aktiengesellschaft Ballast électronique
US5066894A (en) * 1989-10-09 1991-11-19 Siemens Aktiengesellschaft Electronic ballast
WO1991007863A1 (fr) * 1989-11-18 1991-05-30 Ac/Dc Lighting Limited Onduleurs et dispositifs pour lampes cathodiques
EP0435228A2 (fr) * 1989-12-29 1991-07-03 Zumtobel Aktiengesellschaft Circuit et procédé pour alimenter (et amorcer) une lampe à décharge
EP0435228A3 (en) * 1989-12-29 1992-07-08 Zumtobel Aktiengesellschaft Circuit and process for operating (and igniting) a discharge lamp
US6037722A (en) 1994-09-30 2000-03-14 Pacific Scientific Dimmable ballast apparatus and method for controlling power delivered to a fluorescent lamp
US5955841A (en) 1994-09-30 1999-09-21 Pacific Scientific Company Ballast circuit for fluorescent lamp
US5982111A (en) 1994-09-30 1999-11-09 Pacific Scientific Company Fluorescent lamp ballast having a resonant output stage using a split resonating inductor
US5925986A (en) 1996-05-09 1999-07-20 Pacific Scientific Company Method and apparatus for controlling power delivered to a fluorescent lamp
US5866993A (en) 1996-11-14 1999-02-02 Pacific Scientific Company Three-way dimming ballast circuit with passive power factor correction
US5798617A (en) 1996-12-18 1998-08-25 Pacific Scientific Company Magnetic feedback ballast circuit for fluorescent lamp
WO2000024233A2 (fr) * 1998-10-16 2000-04-27 Electro-Mag International, Inc. Circuit regulateur
US6169375B1 (en) 1998-10-16 2001-01-02 Electro-Mag International, Inc. Lamp adaptable ballast circuit
WO2001097574A2 (fr) * 2000-06-14 2001-12-20 Brenex Electrics Pty. Limited Circuit de commande pour tubes fluorescents
DE102008031409A1 (de) * 2008-07-02 2010-01-07 Tridonicatco Gmbh & Co. Kg Erkennung des Typs einer an einem Betriebsgerät angeschlossenen Gasentladungslampe
DE102008047440A1 (de) * 2008-09-16 2010-03-25 Tridonicatco Gmbh & Co. Kg Bestimmung des Typs eines Leuchtmittels oder der Topologie mehrerer Leuchtmittel

Also Published As

Publication number Publication date
FI841794A (fi) 1984-11-28
FI841794A0 (fi) 1984-05-04
EP0127101A1 (fr) 1984-12-05
DE3319352A1 (de) 1984-11-29
DE3462574D1 (en) 1987-04-09
FI76906B (fi) 1988-08-31
ATE25800T1 (de) 1987-03-15
FI76906C (fi) 1988-12-12

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