EP0000261A1 - Schaltung zur direkten und rückgekoppelten Steuerung einer Positioniereinrichtung - Google Patents

Schaltung zur direkten und rückgekoppelten Steuerung einer Positioniereinrichtung Download PDF

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Publication number
EP0000261A1
EP0000261A1 EP78300061A EP78300061A EP0000261A1 EP 0000261 A1 EP0000261 A1 EP 0000261A1 EP 78300061 A EP78300061 A EP 78300061A EP 78300061 A EP78300061 A EP 78300061A EP 0000261 A1 EP0000261 A1 EP 0000261A1
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Prior art keywords
signal
velocity
phase
positioning system
signals
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EP78300061A
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English (en)
French (fr)
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EP0000261B1 (de
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Richard Karl Oswald
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International Business Machines Corp
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International Business Machines Corp
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    • G—PHYSICS
    • G11—INFORMATION STORAGE
    • G11B—INFORMATION STORAGE BASED ON RELATIVE MOVEMENT BETWEEN RECORD CARRIER AND TRANSDUCER
    • G11B5/00—Recording by magnetisation or demagnetisation of a record carrier; Reproducing by magnetic means; Record carriers therefor
    • G11B5/48—Disposition or mounting of heads or head supports relative to record carriers ; arrangements of heads, e.g. for scanning the record carrier to increase the relative speed
    • G11B5/54—Disposition or mounting of heads or head supports relative to record carriers ; arrangements of heads, e.g. for scanning the record carrier to increase the relative speed with provision for moving the head into or out of its operative position or across tracks
    • G11B5/55—Track change, selection or acquisition by displacement of the head
    • G11B5/5521—Track change, selection or acquisition by displacement of the head across disk tracks
    • G11B5/5526—Control therefor; circuits, track configurations or relative disposition of servo-information transducers and servo-information tracks for control thereof
    • G11B5/553—Details
    • G11B5/5547—"Seek" control and circuits therefor
    • G—PHYSICS
    • G05—CONTROLLING; REGULATING
    • G05B—CONTROL OR REGULATING SYSTEMS IN GENERAL; FUNCTIONAL ELEMENTS OF SUCH SYSTEMS; MONITORING OR TESTING ARRANGEMENTS FOR SUCH SYSTEMS OR ELEMENTS
    • G05B19/00—Programme-control systems
    • G05B19/02—Programme-control systems electric
    • G05B19/18—Numerical control [NC], i.e. automatically operating machines, in particular machine tools, e.g. in a manufacturing environment, so as to execute positioning, movement or co-ordinated operations by means of programme data in numerical form
    • G05B19/19—Numerical control [NC], i.e. automatically operating machines, in particular machine tools, e.g. in a manufacturing environment, so as to execute positioning, movement or co-ordinated operations by means of programme data in numerical form characterised by positioning or contouring control systems, e.g. to control position from one programmed point to another or to control movement along a programmed continuous path
    • G05B19/21—Numerical control [NC], i.e. automatically operating machines, in particular machine tools, e.g. in a manufacturing environment, so as to execute positioning, movement or co-ordinated operations by means of programme data in numerical form characterised by positioning or contouring control systems, e.g. to control position from one programmed point to another or to control movement along a programmed continuous path using an incremental digital measuring device
    • G05B19/23—Numerical control [NC], i.e. automatically operating machines, in particular machine tools, e.g. in a manufacturing environment, so as to execute positioning, movement or co-ordinated operations by means of programme data in numerical form characterised by positioning or contouring control systems, e.g. to control position from one programmed point to another or to control movement along a programmed continuous path using an incremental digital measuring device for point-to-point control
    • G05B19/231—Numerical control [NC], i.e. automatically operating machines, in particular machine tools, e.g. in a manufacturing environment, so as to execute positioning, movement or co-ordinated operations by means of programme data in numerical form characterised by positioning or contouring control systems, e.g. to control position from one programmed point to another or to control movement along a programmed continuous path using an incremental digital measuring device for point-to-point control the positional error is used to control continuously the servomotor according to its magnitude
    • G05B19/232—Numerical control [NC], i.e. automatically operating machines, in particular machine tools, e.g. in a manufacturing environment, so as to execute positioning, movement or co-ordinated operations by means of programme data in numerical form characterised by positioning or contouring control systems, e.g. to control position from one programmed point to another or to control movement along a programmed continuous path using an incremental digital measuring device for point-to-point control the positional error is used to control continuously the servomotor according to its magnitude with speed feedback only
    • G—PHYSICS
    • G05—CONTROLLING; REGULATING
    • G05B—CONTROL OR REGULATING SYSTEMS IN GENERAL; FUNCTIONAL ELEMENTS OF SUCH SYSTEMS; MONITORING OR TESTING ARRANGEMENTS FOR SUCH SYSTEMS OR ELEMENTS
    • G05B2219/00—Program-control systems
    • G05B2219/30—Nc systems
    • G05B2219/41—Servomotor, servo controller till figures
    • G05B2219/41086—Bang bang control
    • G—PHYSICS
    • G05—CONTROLLING; REGULATING
    • G05B—CONTROL OR REGULATING SYSTEMS IN GENERAL; FUNCTIONAL ELEMENTS OF SUCH SYSTEMS; MONITORING OR TESTING ARRANGEMENTS FOR SUCH SYSTEMS OR ELEMENTS
    • G05B2219/00—Program-control systems
    • G05B2219/30—Nc systems
    • G05B2219/41—Servomotor, servo controller till figures
    • G05B2219/41355—Electro magnetic coil actuator, voice coil
    • G—PHYSICS
    • G05—CONTROLLING; REGULATING
    • G05B—CONTROL OR REGULATING SYSTEMS IN GENERAL; FUNCTIONAL ELEMENTS OF SUCH SYSTEMS; MONITORING OR TESTING ARRANGEMENTS FOR SUCH SYSTEMS OR ELEMENTS
    • G05B2219/00—Program-control systems
    • G05B2219/30—Nc systems
    • G05B2219/41—Servomotor, servo controller till figures
    • G05B2219/41434—Feedforward FFW

Definitions

  • the present invention relates to positioning systems for moving a member between positions in response to a position input command.
  • the invention relates particularly to systems in which each such movement, between a current and a target reference position, is completed before a subsequent command is accepted and comprises a single acceleration phase in which such a member is accelerated to a maximum velocity and a single deceleration phase in which said member is decelerated from said maximum velocity to a state of rest at said target reference position.
  • a typical positioning application to which the present invention relates is the positioning of a data recording head or heads over a selected track of a magnetic disk file.
  • the aspect of this positioning operation which is of interest is the movement of heads between tracks, known as the “track access” or “seek” operation, as opposed to the “track follow” operation which maintains the heads in position over a selected track.
  • Time optimal motion between tracks implies maximum acceleration and deceleration of the heads within the physical constraints of the system.
  • To control such motion with typical access times of a few tens of microseconds, and bring the heads to rest on the target track, with an accuracy better than a hundred microns, feedback control of head velocity has been widely employed.
  • Velocity control offers a higher performance than position control because velocity is the time derivative of position.
  • a typical system for controlling a disk file head access operation is described in an article entitled "Design of a Disk File Head-Positioning Servo" by R K Oswald (IBM Journal of Research and Development, Nov 1974, pp 506 to 512).
  • an access operation is controlled by means of a generated reference velocity trajectory representing the required velocity of the heads for deceleration at the maximum attainable rate to a state of rest over the target track.
  • a velocity transducer or tachometer measures the actual velocity of the heads and the measured velocity is compared with the reference velocity trajectory and amplified in an error amplifier to provide a velocity error signal.
  • the velocity error signal is applied to control the head actuator, typically a voice coil motor, to cause the actual velocity to follow the deceleration curve as closely as possible. Initially, actual velocity is low and the heads are accelerated under open loop (saturated) conditions until the actual velocity equals the reference velocity.
  • the sign of the velocity error changes and reverse current is applied to the actuator.
  • the reverse current is controlled as a function of the velocity error to cause the head velocity to follow the reference velocity trajectory accurately.
  • a velocity signal has-been derived from incremental position signals provided by an external position transducer linked to motion or, by a servo head and dedicated servo surface on one of the disks.
  • Control systems for innumerable other applications than position control are also found in the prior art.
  • a large variety of control schemes also exist, and these have tended to develop according to the particular application and its unique problems.
  • control systems have been developed which have some resemblance to the positioning control system of the present invention.
  • Feedforward control involves predicting the change with time of a manipulated variable necessary to produce the desired change in a controlled variable of the process.
  • the feedforward function is based on a model of the process and is applied to the actual system independently of any feedback. Feedforward control is essentially an open- loop technique allowing immediate response to an input command. The accuracy of such control is only as good as that of the process model.
  • control and feasible response means provides a feasible response signal, representing the predicted response of the controlled variable to the change of the manipulated variable in accordance with the feedforward control signal.
  • the feasible response signal is compared with the actual measured response of the controlled variable to provide an error signal. This error signal is summed with the fed forward manipulated variable to provide fine feedback control of the process.
  • the velocity feedback loop is Type 1 and the reference velocity trajectory is approximately a ramp so that the velocity error can never be completely eliminated.
  • the magnitude of the velocity error is dependent on the overall gain of the feedback loop which also affects the bandwidth of the loop. A compromise is necessary between the reduction of velocity error and the limitations imposed by the mechanical resonances of the system. If the gain is more than unity at a resonance frequency, the system will be unstable. This problem is becoming increasingly acute with the higher frequencies inherent in increased track densities
  • the present invention offers a solution to the above problems in providing a positioning system, responsive to a position input command to move a member along a predetermined path of travel between a current and a target reference position defined by said command, each such movement being completed before a subsequent command is accepted and comprising a single acceleration phase in which such a member is accelerated to a maximum velocity and a single deceleration phase in which said member is decelerated from said maximum velocity to a state of rest at said target reference position, said system comprising an electrically controlled actuator for moving said member along said predetermined path in response to electrical drive signals and having an input circuit to which said signals are applied, reference signal generating means responsive to said position input command to generate a reference signal at least a portion of which represents the variation with time of a position related attribute of said member for deceleration of said member in a predetermined manner during said deceleration phase, and a feedback control loop including a transducer for providing a signal indicating the value of said position related attribute of said member, error determining means for producing an
  • the invention allows time optimal positioning movement while permitting a low bandwidth in the feedback loop.
  • the invention preferably provides that the bandwidth of said feedback control loop as a whole is arranged to be predominantly below the frequency of said resonances, such that the overall loop gain is substantially below unity at the frequency of said resonances and that the bandwidth of said feedforward control means is higher than that of said feedback control loop and overlaps the frequency of said resonances. In this way the system is desensitized to high frequency disturbances without loss of performance.
  • the present invention also relaxes considerably the constraints on minimum bandwidth required of transducer signals for rapid motion between positions.
  • This archer allows normal velocity feedback and the associated velocity transducing circuitry to be dispensed with entirely, if desired, and the more easily derived position information to be employed in the feedback'loop.
  • the incremental position of the member from equally spaced reference positions along its path of travel can be used.
  • said reference signal generating means comprising an integrator for integrating said velocity representation up and down alternately between positive and negative thresholds to generate said reference signal in the form of an incremental position signal.
  • said predictive drive signal generating means includes means for reducing the absolute magnitude of said predictive drive signal as a function of velocity during said deceleration phase of said movement.
  • This feature enables the system to take account of the back of e.m.f. of a coil type actuator.
  • Feedforward control may advantageously be employed both during acceleration and deceleration of the member and to that end it is a preferred feature of the invention to provide a positioning system further comprising phase indicating means for indicating acceleration and deceleration phases of said motion, and means for providing a representation of the velocity of said member, said feedforward control means being connected to receive said phase indications and said velocity representation and being responsive thereto to generate said predictive drive signal comprising an initial portion consisting of a constant component of one polarity and a component of opposite polarity proportional to said velocity representation during the acceleration phase and having a final portion consisting of a constant component of said opposite polarity and a further component of said opposite polarity proportional to said velocity signal during the deceleration phase of said movement.
  • FIG 1 there is shown a preferred positioning system according to the present invention.
  • the positioning system controls the positioning of heads 10 relative to information bearing concentric tracks on disks 11 of a schematically illustrated disk file.
  • the heads are moved by an actuator 12 of the well known voice coil motor type,
  • the mechanical connection between the actuator 12 and heads 10 is schematically indicated by dashed line 13 and includes a carriage (not shown) for supporting the heads.
  • the motor 12, the heads 10 and disks 11 together with other support components including the head carriage constitute a mechanical system 14.
  • This system as a whole has natural resonance frequencies typically of the order of a few thousand Hertz which, as will be explained further below, may affect the stability of the positioning system, if they are excited and amplified.
  • the input circuit of actuator 12 comprises a power amplifier 15 which amplifies an input drive signal to provide a current to the actuator coil.
  • a feedforward control signal on line 16 and a feedback control signal on line 17 are summed in summing junction 18 and selectively inverted by inverter 19, depending on the direction of motion, to provide the drive signal to the power amplifier 15.
  • the feedforward control signal is generated by.feedforward current generator 20, the details of which will be explained below in connection with Figure 3.
  • the feedforward current trajectory is illustrated as waveform 101 of Figure 4 and represents the actuator current required for a nominal system to cause the actuator to move the heads from_one track to another in a minimum time. If the actual system were exactly the same as the nominal system, the heads would be moved to the target track and brought to rest there in a minimum time without further control being necessary. However, since there will be parameter differences between the nominal and actual systems, the actual response of the system is measured and fed back for use in a feedback control arrangement to ensure accurate positioning.
  • the quantity which is measured to determine the response of the system is velocity.
  • the velocity of the heads 10 moving radially across the disk is determined by a velocity transducer circuitry 21 from the integral of the current in the actuator coil and the derivative of a periodic incremental position signal from position transducer circuitry 22.
  • a suitable circuit for deriving a velocity signal from these inputs is described in US Patent 3 820 712 (Oswald).
  • the position transducer circuitry 22 comprises demodulating circuitry for deriving a position error signal from servo signals read by one of the heads 10 from a dedicated servo surface of one of the disks 11.
  • the demodulated position error signal is a cyclic triangular waveform whose zero crossings correspond to track centres.
  • the measured velocity signal on line 23 is applied to a summing junction 24 to which is also applied a reference velocity signal on line 25.
  • the summing junction forms the difference between the reference velocity signal and the measured velocity signal which is amplified in error amplifier 26 to provide the feedback control signal on line 17.
  • the reference velocity signal is conventionally produced in response to a position command at input 30 which loads a difference counter 31 with a value equal to the number of tracks between the current track position of the heads and the target position to which they are to be moved.
  • a zero crossing detector 32 As the heads move towards the target position, zero crossings of the position signal from position transducer circuitry 22 are detected by a zero crossing detector 32.
  • the zero crossing detector output is a series of pulses each of which decrements the difference counter 31 every time a track is crossed.
  • the output of the difference counter 31 applied on a bus 33 to a digital-to-analog converter 34 which converts the decreasing count to an analog staircase function representative of the instantaneous absolute position error between the heads and the target track.
  • An interpolator 35 receives the track crossing pulses from zero crossing sector 32 and the velocity signal on line 23 and provides a "fill-in" signal which is summed in junction 36 to smooth the output of the DAC 34.
  • the fill-in signal comprises a falling ramp with a slope proportional to velocity which is reset on every track crossing pulse. Circuits for generating such signals are well known and comprise, for example, an integration for integrating the velocity input signal, which is reset to a predetermined level by the track crossing pulses.
  • the smoothed absolute position error signal from junction 36 is applied to a function generator 37 whose output on line 25 is the reference velocity signal as shown in curve l03, Figure 4.
  • the function generator 37 modifies the absolute position error signal in shape according to a predetermined function.
  • a simple function which has been used is a square root function as this represents the variation of velocity with position for a constant maximum deceleration.
  • the relationship of velocity to position may be a more complex function to allow for the effect of the actuator back e.m.f. and to meet servo system stability criteria.
  • a circuit for generating a second order function having both a squared and linear term is described below in connection with Figure 2.
  • the reference velocity signal from function generator 37 represents the required velocity of the heads lO while decelerating towards target position with the maximum deceleration attainable by a worst case system.
  • the anticipate circuit 39 is effective, while the heads are accelerating, to lower slightly the absolute position error signal and thus the reference velocity curve by an amount proportional to velocity.
  • the accelerate phase of the motion is indicated by the output of a flip-flop 44 which is set at input 45 at the start of each new seek.
  • the output of flip-flop 44 is reset by ground level comparator 41, indicating the sign of the velocity error signal from junction 24 and the end of the accelerate phase.
  • the inverted accelerate signal from flip-flop 44 and the saturation signal from logic 38 are applied to an AND gate 42 to produce a "coast" mode signal which indicates the portion of the motion when the heads are at coast velocity. This signal is used in the feedforward current generator 20.
  • Another input to the feedforward current generator is a "stop velocity" indication from threshold detector 43. This indicates that the heads have come substantially to rest and that the seek motion is complete.
  • the DAC 34 receives the output of difference counter on lines 33 and also the output of saturation logic 38 on additional line 50.
  • the DAC output appears on line 51 and is smoothed by the addition of the fill-in signal from interpolator 35 applied at terminal 52.
  • the anticipate circuitry 39 comprises a switching transistor 53 responsive to an inverted accelerate mode indication at terminal 54 to inhibit the anticipate function.
  • the measured velocity from line 23, Figure 1 is applied at terminal 55 and, when transistor 53 is off, acts to lower slightly the DAC output level on line 51.
  • the function generator 37 of Figure 1 is seen in Figure 2, to comprise an amplifier 60 with a resistive feedback connection to provide a linear term of the required function.
  • a two quadrant transconductance multiplier 61 is connected in feedback configuration around the amplifier 60 to provide the second order term of the function.
  • the output at terminal 62 represents the reference velocity signal on line 25 of Figure 1.
  • feedforward current generator 20 together with other associated portions of the system of Figure 1 will now be described in greater detail with reference to Figure 3 and the waveforms of Figure 4.
  • the inputs to the circuit of Figure 3 comprise the accelerate signal from comparator 41 at terminal 70, the coast signal from AND gate 42, or the stop velocity signal from detector 43 at terminal 71, the reference velocity signal from function generator 37 at terminal 72, and measured velocity from velocity transducer circuitry 23 at terminals 73 and 74.
  • the reference velocity signal at terminal 72 and the measured velocity at terminal 73 are algebraically summed at node 75, corresponding to junction 24 of Figure 1, to produce the velocity error signal.
  • An operational amplifier 76 amplifies the velocity error.
  • the amplified velocity error is provided at output 79.
  • the amplifier output is limited by diodes 77 and 78 to prevent an excessive output signal during accelerate mode when the velocity error is very large.
  • the limiting function also ensures that the feedback control signal cannot exceed more than a small predetermined fraction (around 15%) of the feedforward control signal.
  • the feedforward current generator comprises a resistive network for providing a current input to an operational amplifier 80, the input being switchable under control of transistors 81 and 82.
  • transistor 81 is off and transistor 82 is on.
  • a current I flows from positive supply through resistor 83.
  • a current T v proportional to the velocity signal input at terminal 74 is summed with T o so that a combined current T o + I v flows through resistor 84 to the input terminal of amplifier 80. Since transistor 82 is on, current flows from positive supply through resistor 85 to ground and there is no net current through resistor 86.
  • a current of magnitude 21 flows from the input terminal of the amplifier 80 to negative supply through resistor 87.
  • the net input current to the amplifier during accelerate mode is thus T o - T v and is shown as the dashed line 100 in the left hand half of the upper waveform of Figure 4. As the velocity rises so does I and the level of the waveform falls.
  • the velocity factor is introduced to represent the effect of back e.m.f. on current in a high performance electromagnetic coil actuator.
  • the back e.m.f. reduces the voltage applied across the coil in the accelerate mode and is added to the voltage applied across the coil in the decelerate mode.
  • the amplifier 80 is connected in lag-lead filter configuration with a feedback loop comprising resistors 88 and 89 and capacitor 90.
  • the filter modifies the dashed waveform portions 100 of Figure 4 to the shape of continuous line 101.
  • the filtering action represents the effect of motor coil inductance on the transient response of coil current. It will be noted that the feedback control voltage from amplifier 76 is effectively summed with the feedforward function at the input to the feedforward current generator rather than at the output as'suggested by summing junction 18 of Figure 1. This difference has no practical effect.
  • the output waveform 101 as drawn in Figure 4 is that which would be produced in the absence of a feedback control signal.
  • a final element of the circuitry of Figure 3 is selective inversion circuitry responsive to input commands indicating forward or reverse direction at terminals 90 and 91.
  • Amplifier 94 passes the feedforward signal to output 93 without inversion if line 91, indicating the forward direction of motion is active.
  • Amplifier 92 inverts the feedforward signal at output 93 if line 90, indicating the reverse direction of motion, is active.
  • This circuitry corresponds to the selective inversion circuit 19 of Figure 1.
  • the feedforward current waveform 101 of Figure 4 represents a prediction of the actual current which would exist in the coil of an electromagnetic actuator of a nominal system with full forward then full reverse power applied, less a small margin for control.
  • This waveform is fed forward to the power amplifier of the real system and applied as the actuator input current.
  • the velocity of the heads is thus caused to follow the trajectory 102 in Figure 4.
  • the reference velocity signal 103 is generated, as described in connection with Figures 1 and 2, which represents the variation of velocity with distance necessary to bring the heads to rest on the target track in the minimum time, ie, with a worst case system operating at full reverse power.
  • the reference velocity signal is lowered during acceleration from the dashed curve 103' by the action of the anticipate function.
  • the reference curve 103 is compared with the actual velocity 102 to provide a feedback control to provide fine correction to the feedforward action.
  • a feedback control signal is produced, but, because of the large velocity error between curves 102 and 103, is always of the maximum amplitude determined by the limiting diodes of the error amplifier.
  • the maximum amplitude error signal is simply added as a small increment to the positive portions of the feedforward function and full forward power is applied to the actuator in open loop fashion.
  • the velocity error would disappear entirely, in theory, if the feedforward function were 100% accurate. However, more realistically, if a feedforward function such as waveform 101 is 90% accurate, then the corrective action required from the feedback control loop is only 10% of what would be required without the feedforward function. Thus, the gain of the error amplifier and, roughly
  • the gain of the error amplifier is set sufficiently low to reduce the bandwidth of the feedback loop to a few hundred Hertz, well below the lowest resonance frequency of a few thousand Hertz.
  • the lag-lead filter formed by resistors 88 and 89 and capacitor 90 in Figure 3 does reduce the bandwidth somewhat, but the effect is insignificant compared with that of the gain of amplifier 76.
  • FIG. 5 there is shown another embodiment of the present invention which makes use of the reduction in feedback loop bandwidth permitted by the addition of feedforward control, to employ a position signal directly as the feedback controlled variable.
  • the system of Figure 5 is a system for positioning magnetic heads 210 in relation to tracks on disks 211 of a disk file by means of an electromagnetic voice coil actuator 212.
  • the actuator input circuit comprises a power amplifier 215.
  • the control signal to the power amplifier input comprises a feedforward signal on line 216 and a feedback signal on line 217 which are summed in junction 218 and selectively inverted by inverter 219 in dependence on the direction of motion.
  • the feedforward signal is provided by feedforward current generator 220 which operates in exactly the same way as the generator 20 of Figure 1, though the inputs to the generator are derived somewhat differently as will be described below.
  • a periodic position signal is derived by position transducing circuitry 222 from servo signals read back by one of the heads 210 from a dedicated servo surface on one of the disks 211.
  • the operation of the circuitry and the form of the triangular position signal is exactly the same as for the circuit of Figure 1.
  • no velocity transducer circuitry is provided and the periodic position signal is fed back directly to a summing junction 223 for comparison with areference periodic position on line 224.
  • the difference signal from junction 223 is alter- nately inverted by inverter 228 in dependence on the slope of the reference periodic position signal as detected by slope detector 227.
  • the alternately inverted difference signal constitutes the position error signal and is amplified by error amplifier 225 to provide the feedback control signal.
  • the reference periodic position signal is generated by integrating a reference velocity signal repeatedly up and down between predetermined levels in incremental integrator 226, the operation of which will be described below in connection with Figures 6 and 7.
  • the reference velocity signal comprises both an accelerate and decelerate portion and feedback control is thus available for the complete duration of the motion.
  • the decelerate portion of the reference velocity signal is provided in very similar fashion to Figure 1.
  • a difference counter 230 is loaded at terminal 231 with a value representing the number of tracks to be crossed.
  • the difference counter is decremented by output pulses from zero crossing detector 232 during the motion and its output converted to an analog function by DAC 233 and smoothed by fill-in signals from interpolator 234.
  • the absolute position error signal thus derived from summing junction 235 is applied to decelerate function generator 236 to produce a reference velocity signal in the manner of Figure 1.
  • the accelerate portion of the reference velocity signal is produced somewhat similarly.
  • An up counter 240 is set to zero as difference counter 230 is loaded with the difference count.
  • a DAC 242, summing junction 243 and accelerate function generator 244 produce a rising curve representing the required velocity for time optimal motion at successive
  • the acceleration curve and the deceleration curve are passed through a circuit 248 for passing whichever has the lower value.
  • the output of this circuit is the reference velocity curve which is input to the incremental integrator 226.
  • a comparator circuit 249 provides an output signal indicating which of the acceleration and deceleration curves is of greater magnitude. This indication identifies the acceleration phase of the motion and is applied to the feedforward generator 220 as an input.
  • a second input to the feedforward generator is a "coast" signal, provided by the AND gate 250 from the output of saturation logic 246 and the accelerate signal from comparator 249.
  • a second input to the same line is provided by stop velocity detector 251 which detects when the reference velocity effectively falls to zero, indicating that the seek is complete.
  • FIG. 6 A preferred form of incremental integrator and associated switching circuitry suitable for use in the general system of Figure 5 is shown in Figure 6. Waveforms produced by the circuitry of Figure 6 are shown in Figure 7.
  • the circuitry of Figure 6 is directly applicable to the system of Figure 5 with the modification that two phases of position signal (both measured and reference) are provided.
  • the two phases are of identical form to the sawtooth signals described in the Oswald article, referenced above, but are phase displaced by 90 degrees.
  • One signal is normally referred to as the "normal" (in phase) position signal and the other as the "quadrature" position signal.
  • the measured in phase and quadrature position signals are applied at terminals 310 and 311 for comparison with reference quadrature position signals N and Q, Figure 7 in junctions 312 and 313 respectively.
  • the junctions 312 and 313 correspond to the summing junction 223 of Figure 5 and their outputs are alternately selected by logic to be described to remove the effect on the position error signal of the slope changes and peaks of the position signals.
  • a single position error output signal is provided at output 314.
  • the two phases of reference periodic position signal are produced by applying the reference velocity signal from circuit 248 ( Figure 5) to the input 319 of a selective inverter 320.
  • the inverter is controlled by a signal d, Figure 7, from the normal output of a set/reset flip-flop 321.
  • the reference velocity signal is passed through circuit 320 without inversion.
  • the reference velocity signal is inverted.
  • An integrator 322 integrates the alternately inverted reference signal to produce a signal a, Figure 7, which is of triangular form and resembles a single phase position signal.
  • the alternation of the flip-flop 321 is controlled by comparators 323 and 324 wich compare the magnitude of the integrator output a with predetermined reference levels +V/2 and -Y/2. Thus, the integrator output reverses slope every time one of the levels ⁇ V/2 is reached.
  • flip-flop 321 The normal and inverted outputs of flip-flop 321 are used to clock respective data/clock flip-flops 325 and 326 which produce output signals'e and f as shown in Figure 7. These signals are at half the frequency of signal d and are 90 degrees displaced in phase from each other. They are employed to switch selective inverters 327 and 328 in the generation of reference periodic position signals N and Q.
  • the two signals N and Q are produced by applying waveform a to a level shifting network including amplifiers 329 and 330 to produce two intermediate signals N' and Q', Figure 7, which, are centered about +V/2 and -V/2 volts respectively.
  • Application of these intermediate signals N' and Q' to selective inverters 327 and 328 produce the reference periodic position signals N and Q, Figure 7, which are of twice the amplitude and half the frequency of intermediate signals N' and Q'.
  • the reference position signals N and Q from inverters 327 and 328 are next compared with the measured in phase and quadrature position signals in summing junctions 312 and 313.
  • a switch circuit 331 is employed to select either the "in phase” or the quadrature position error in dependence on the value of a waveform b, also shown in Figure 7.
  • the waveform b is produced by an overdriven comparator 332 in response to the waveform a.
  • the switch 331 operates to select alternately only the position error signal derived from central linear portions of the position signals. This signal will invert according to whether the slope of the position signals is positive or negative when the comparison is made.
  • a selective inverter 333 is interposed between the output of switch 331 and output terminal 314.
  • the selective inverter is controlled by a waveform c, shown in Figure 7, derived by data/clock flip-flop 334 from waveform b.
  • the system of Figures 5, 6 and 7 employs feedback control only as a fine correction imposed on the basic feedforward control.
  • the use of approximate feedforward control permits the gain and bandwidth of the minor feedback loop to be significantly lower than where feedback control alone is employed.
  • this fact permits the use of the position transducer output directly as a feedback controlled variable.
  • a position feedback loop is not used where high performance is required since the bandwidth available with position signal feedback is low compared to that of a velocity feedback loop,
  • the position transducer circuitry 222 could have a provision for sampling the information from heads 10 at sector times only and for holding sampled position signals, or interpolating between them, between sectors.
  • the output of the error amplifier 225 could be sampled and then held or interpolated between sectors.

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  • Engineering & Computer Science (AREA)
  • Human Computer Interaction (AREA)
  • Manufacturing & Machinery (AREA)
  • Physics & Mathematics (AREA)
  • General Physics & Mathematics (AREA)
  • Automation & Control Theory (AREA)
  • Control Of Position Or Direction (AREA)
  • Feedback Control In General (AREA)
  • Moving Of Head For Track Selection And Changing (AREA)
EP78300061A 1977-06-29 1978-06-21 Schaltung zur direkten und rückgekoppelten Steuerung einer Positioniereinrichtung Expired EP0000261B1 (de)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
US811350 1977-06-29
US05/811,350 US4200827A (en) 1977-06-29 1977-06-29 Positioning system employing feedforward and feedback control

Publications (2)

Publication Number Publication Date
EP0000261A1 true EP0000261A1 (de) 1979-01-10
EP0000261B1 EP0000261B1 (de) 1981-10-07

Family

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EP78300061A Expired EP0000261B1 (de) 1977-06-29 1978-06-21 Schaltung zur direkten und rückgekoppelten Steuerung einer Positioniereinrichtung

Country Status (9)

Country Link
US (1) US4200827A (de)
EP (1) EP0000261B1 (de)
JP (1) JPS5412082A (de)
AU (1) AU511484B2 (de)
BR (1) BR7804158A (de)
CA (1) CA1100609A (de)
DE (1) DE2861129D1 (de)
ES (1) ES470846A1 (de)
IT (1) IT1111180B (de)

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FR2600436A1 (fr) * 1986-06-20 1987-12-24 Benson Sa Procede et dispositif de commande de moteur de machine a dessiner
GB2238888A (en) * 1989-11-15 1991-06-12 Okuma Machinery Works Ltd Index control apparatus for tool rest of an NC lathe
WO1994007187A1 (de) * 1992-09-22 1994-03-31 Robert Bosch Gmbh Verfahren zur überprüfung der arbeitsgenauigkeit einer nc-maschine
US5329409A (en) * 1991-07-24 1994-07-12 Seagate Technology, Inc. Correction of current feedback offset for disc drive servo systems
US5537016A (en) * 1992-09-22 1996-07-16 Robert Bosch Gmbh Method for verifying the performance accuracy of a numerically controlled machine
EP0774754A2 (de) * 1995-11-17 1997-05-21 Fujitsu Limited Plattenspeichergerät
CN114326378A (zh) * 2022-01-27 2022-04-12 三一重机有限公司 作业机械轨迹控制方法、装置及作业机械

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Cited By (14)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0013326A2 (de) * 1978-12-27 1980-07-23 International Business Machines Corporation Servo-Lageregelungssystem mit abgetasteten Positionswerten und seine Anwendung in einem Plattenspeicher mit Servo-Sektoren
EP0013326A3 (en) * 1978-12-27 1980-09-17 International Business Machines Corporation Sampled data servo positioning system and sector disk file employing same
FR2600436A1 (fr) * 1986-06-20 1987-12-24 Benson Sa Procede et dispositif de commande de moteur de machine a dessiner
GB2238888B (en) * 1989-11-15 1994-05-04 Okuma Machinery Works Ltd Index control apparatus for tool rest of an NC lathe
US5121039A (en) * 1989-11-15 1992-06-09 Okuma Machinery Works Index control apparatus for tool rest of nc lathe
GB2238888A (en) * 1989-11-15 1991-06-12 Okuma Machinery Works Ltd Index control apparatus for tool rest of an NC lathe
US5329409A (en) * 1991-07-24 1994-07-12 Seagate Technology, Inc. Correction of current feedback offset for disc drive servo systems
WO1994007187A1 (de) * 1992-09-22 1994-03-31 Robert Bosch Gmbh Verfahren zur überprüfung der arbeitsgenauigkeit einer nc-maschine
US5537016A (en) * 1992-09-22 1996-07-16 Robert Bosch Gmbh Method for verifying the performance accuracy of a numerically controlled machine
EP0774754A2 (de) * 1995-11-17 1997-05-21 Fujitsu Limited Plattenspeichergerät
EP0774754A3 (de) * 1995-11-17 1997-12-17 Fujitsu Limited Plattenspeichergerät
US5859742A (en) * 1995-11-17 1999-01-12 Fujitsu Limited Disk storage apparatus having head overshoot and undershoot control
CN114326378A (zh) * 2022-01-27 2022-04-12 三一重机有限公司 作业机械轨迹控制方法、装置及作业机械
CN114326378B (zh) * 2022-01-27 2023-12-05 三一重机有限公司 作业机械轨迹控制方法、装置及作业机械

Also Published As

Publication number Publication date
DE2861129D1 (en) 1981-12-17
ES470846A1 (es) 1979-02-01
BR7804158A (pt) 1979-04-10
IT7823829A0 (it) 1978-05-26
JPS5412082A (en) 1979-01-29
CA1100609A (en) 1981-05-05
AU3483578A (en) 1979-10-11
IT1111180B (it) 1986-01-13
US4200827A (en) 1980-04-29
AU511484B2 (en) 1980-08-21
EP0000261B1 (de) 1981-10-07

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