CN201910768U - High-linearity foldable image mixer - Google Patents
High-linearity foldable image mixer Download PDFInfo
- Publication number
- CN201910768U CN201910768U CN201120006874XU CN201120006874U CN201910768U CN 201910768 U CN201910768 U CN 201910768U CN 201120006874X U CN201120006874X U CN 201120006874XU CN 201120006874 U CN201120006874 U CN 201120006874U CN 201910768 U CN201910768 U CN 201910768U
- Authority
- CN
- China
- Prior art keywords
- frequency
- grid
- connects
- voltage
- stage
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Lifetime
Links
Images
Abstract
The utility model relates to a high-linearity foldable image mixer, which adopts a structure that a double-balanced switch pair is embedded in a current mirror. Under the joint effect of the current mirror and the double-balanced switch pair, transconductance-stage radio-frequency current generates frequency-converted medium-frequency current signals of which the magnitude is in image proportion to the radio-frequency current; and then, the current forms output voltage on a load resistance. Since the current mirror has a proportional reproduction characteristic, compared with a foldable Gilbert mixer which adopts a cascade structure, the linearity is better. Moreover, most traditional mixers adopt a cascade structure sequentially formed by a transconductance stage, a mixing switch pair and a load stage from a power supply to the ground. The mixer realizes the parallel cascade of the transconductance stage, the mixing stage and the load stage, and is suitable for low power supply voltage application.
Description
Technical field
The utility model relates to a kind of high-linearity folding mirror image frequency mixer, adopts embedded pair of right structure of balance cock of current mirror.Have the advantages that conversion gain is big, the linearity is high, be suitable for low supply voltage.
Background technology
In radiofrequency signal received link, the effect of frequency mixer was the input radio frequency signal is downconverted to base band or intermediate frequency so that subsequent module is handled.As the consideration of whole reception link, frequency mixer should have higher conversion gain with the influence to whole reception chain noise factor of the noise that suppresses back level intermediate frequency amplifier circuit and filter circuit.In addition, frequency mixer itself should have and compares the lower noise factor of ifd module to alleviate the design pressure of low noise amplifier.Along with multi-transceiver technology and complex modulation technology are applied in the wireless telecommunications more and more, to the also raising gradually of linearity requirement of receiver.Because the limitation of integrated circuit technology is difficult to radio circuit is adopted the technology that improves the linearity such as amplifier feedback, mutual conductance bootstrapping etc.; This makes the linearity of radio circuit, and that works that the various Analog Circuit Design methods of flexible Application improve unlike intermediate-frequency circuit.Frequency mixer is positioned at the afterbody of radio-frequency front-end, and according to system's cascade formula, frequency mixer has decisive influence to the linearity of whole radio-frequency front-end, and the linearity that therefore how to improve frequency mixer is the target that the designer constantly pursues.
Frequency mixer can be divided into active mixer and passive frequency mixer, passive frequency mixer often has the better linearity degree, but because it is lower than the conversion gain of 0dB, make the noise factor of back level module produce comparatively serious deterioration (noise factor of ifd module is usually than about the high 10dB of radio circuit), therefore in the telecommunication circuit of having relatively high expectations, seldom be used whole receiver.Active mixer then can have the enlarging function to signal in the lump when the mixing function is provided, suppressed comparatively serious intermediate-frequency circuit noise effectively.Therefore active mixer has occupied the status of main flow in radio-frequency transmitter.
The structure of active mixer is a lot, wherein adopts the gilbert mixer based on two balance cock frequency mixers of Gilbert cell to obtain using comparatively widely.Gilbert mixer has the performance index of comparison balance, but its stacked transistor too much from the power supply to ground makes it be not suitable for the application scenario of low supply voltage.People attempt mixer stage and load stage and transconductance stage are folded open, and such frequency mixer is called as collapsible gilbert mixer.Collapsible frequency mixer has solved the problem of low supply voltage, owing to reduced the bias current of local oscillator switching stage, its noise factor also is improved simultaneously simultaneously.But, because the limited output impedance of transconductance stage transistor and the influence of parasitic capacitance, between transconductance stage and local oscillator level, have the distributary phenomenon of radio-frequency current.Whole collapsible frequency mixer can be regarded the cascade of transconductance stage and local oscillator level and load stage as, and according to linearity cascade formula, the linearity of whole frequency mixer has been worsened.This also is the not high main cause of the accordion structure linearity.In the design, adopted the local oscillator level of embedded pair of balance cock of current mirror.Be (transconductance stage, local oscillator level, load stage are arranged in juxtaposition) that folds from this frequency mixer of structure like this, solved the problem of low supply voltage.From the angle of the linearity, radio-frequency current accurately copies to load stage by current mirror, rather than simple cascade, and the linearity and single-level circuit are similar.
Summary of the invention
Technical problem: the purpose of this utility model is to provide a kind of high-linearity folding mirror image frequency mixer, and this frequency mixer adopts embedded pair of right structure of balance cock of current mirror.Have the advantages that conversion gain is big, the linearity is high, be suitable for low supply voltage.
Technical scheme: the utility model purpose realizes by the following method: utilize embedded pair of balance cock mixer stage of current-mirror structure, two balance cock mixer stages realize the mixing function, and current-mirror structure has realized that being arranged in juxtaposition of structure ensured the comparatively desirable linearity simultaneously.
A kind of high-linearity folding mirror image frequency mixer comprises the radio frequency transconductance stage, voltage mixing core circuit and the intermediate frequency output stage that connect successively; The radio frequency transconductance stage comprises: NMOS pipe M1 and M2, and PMOS manages M3, M4, M5 and M6; Voltage mixing core circuit comprises: PMOS manages M12, M13, M14 and M15;
The input radio frequency signal is capacitively coupled to input mutual conductance pipe M1, and M2 is converted into radio-frequency current;
M3 and M4, and M5, M6 have together constituted the current mirror of difference; Described radio-frequency current forms voltage signal on M3 and M4, M3, M4, the same channel length of M5, M6;
This voltage signal two balance cock pipes through being made of M12～M15 are timing at local oscillation signal, and the gate voltage of M3 is transported to M6, and the gate voltage of M4 is transported to M5; When negative, the gate voltage of M3 is transported to M5 at local oscillation signal, the gate voltage of M4 is transported to M6; Like this, the electric current that M5, M6 duplicate along with local frequency, switches between transconductance stage anode electric current and negative terminal electric current back and forth, forms the frequency conversion electric current, through forming output voltage after the low-pass filtering on the load resistance of intermediate frequency output stage.
Also comprise error amplifier A1;
Described radio frequency transconductance stage also comprises: isolation resistance R1 and R2; Input pipe biasing resistor R0 and R3;
Voltage mixing core circuit also comprises: NMOS pipe M10 and M7; NMOS pipe M11 and M8; Capacitor C 2;
The intermediate frequency output stage comprises: load resistance R4 and R5;
The input radio frequency positive pole is linked the top crown of capacitor C 0, and the bottom crown of capacitor C 0 links to each other with the grid of M1 pipe; The input radio frequency negative pole is linked the top crown of capacitor C 1, and the bottom crown of capacitor C 1 links to each other with the grid of M2 pipe;
The anode of the source electrode connecting resistance R1 of M1 pipe, the negativing ending grounding of R1; The anode of the source terminating resistor R2 of M2 pipe, the negativing ending grounding of R2;
The grid of the positive termination M1 of biasing resistor R0, the grid of the positive termination M2 of R3, the negative terminal of R0 and R3 connects bias voltage;
The drain terminal of M1 connects the drain terminal of M3, and the drain terminal of M3 is connected with grid, and source electrode connects power supply; The drain electrode of M2 connects the drain electrode of M4, and the drain electrode of M4 is connected with grid, and source electrode connects power supply;
The source electrode of M12 and the source electrode of M13 connect the grid of M4, and the grid of M12 and M15 connects the local oscillation signal negative pole, and the grid of M13 and M14 connects the local oscillation signal positive pole;
The drain electrode of M12 and M14 connects the grid of M6, and the drain electrode of M13 and M15 connects the grid of M5;
The source electrode of M5 and M6 connects supply voltage;
The anode of the drain electrode connecting resistance R4 of M5, the negativing ending grounding of R4; The anode of the drain electrode connecting resistance R5 of M6, the negativing ending grounding of R5;
M10 and M7 constitute the cascode current source, are connected in parallel on the two ends of R4; Constitute the cascode current source by M11 and M8, be connected in parallel on the two ends of R5;
The grid of M10, M11 connects the output of error amplifier A1; The output common mode voltage that the positive input termination of A1 is gathered, negative input end connects with reference to common-mode voltage;
The loop that described error amplifier A1, M7, M8, M10, M11, VIF+ and VIF-constitute is common mode feedback circuit.
The principle of the technical program is as follows:
This frequency mixer has comprised radio frequency transconductance stage, voltage mixing core circuit and intermediate frequency output stage.The radio frequency transconductance stage comprises NMOS pipe M1, the M2 as radio frequency mutual conductance pipe, source degeneracy resistance R 1, R2, and input radio frequency coupling capacitance C0, C1, input pipe biasing resistor R0, R3 are as diode connection PMOS pipe M3, the M4 of load pipe.Voltage mixing core circuit comprises two balance cocks to M12-M15.The intermediate frequency output stage comprises PMOS pipe M5, M6, capacitor C 2, load resistance R4, R5, electric current injection current source M10, M7 and M11, M8; Common mode feedback circuit etc.
In the technical program, the input radio frequency signal is capacitively coupled to input mutual conductance pipe M1, and M2 is converted into radio-frequency current.Because transconductance stage two metal-oxide-semiconductors of a cascade from the power supply to ground, can there be enough voltage margins to use source degeneracy resistance R 1, R2 improves the linearity of radio frequency mutual conductance itself.M3 and M4, and M5, M6 have together constituted the current mirror of difference.The radio-frequency current that transconductance stage produces forms voltage signal on load PMOS pipe M3 that diode connects and M4.M3, M4, the same channel length of M5, M6.This voltage signal two balance cock pipes through being made up of M12～M15 are timing at local oscillation signal, and the gate voltage of M3 is transported to M6, and the gate voltage of M4 is transported to M5.When negative, the gate voltage of M3 is transported to M5 at local oscillation signal, the gate voltage of M4 is transported to M6, thus.The electric current that M5, M6 duplicate along with local frequency, switches between transconductance stage anode electric current and negative terminal electric current back and forth, forms the frequency conversion electric current, through form output voltage after the low-pass filtering on load resistance.In order to reach higher conversion gain, in parallel-current source, load resistance two ends, this current source adopts cascodes to avoid influencing the mixer linearity degree to improve output impedance.In order to stablize common-mode voltage, used voltage common mode negative-feedback circuit simultaneously.
Beneficial effect: this frequency mixer is applicable to low supply voltage, and simulation result and test result all show simultaneously: this frequency mixer has higher linearity, higher conversion gain and moderate noise factor.
Description of drawings
Fig. 1 is frequency mixer main body circuit of the present utility model (principle frame) figure;
Fig. 2 a is collapsible gilbert mixer block diagram; The linearity IIP3 of the collapsible gilbert mixer of Fig. 2 a analyzes schematic diagram; As can be seen, partial distortion has increased extra IM3 among the figure;
Fig. 3 is that mixer linearity degree IIP3 of the present utility model analyzes schematic diagram;
Figure 4 shows that mixer linearity degree test result of the present utility model;
Embodiment
High-linearity folding mirror image frequency mixer of the present utility model adopts embedded pair of right structure of balance cock of current mirror.The radio-frequency current of transconductance stage produces the electric current of intermediate frequency signal after the frequency conversion under the right acting in conjunction of current mirror and two balance cocks, its size becomes the mirror image proportionate relationship with radio-frequency current; This electric current forms output voltage on load resistance subsequently.Because the ratio duplication characteristic of current mirror, this frequency mixer has the better linearity than the collapsible gilbert mixer that adopts cascade structure.In addition, conventional mixer mostly is greatly and is respectively transconductance stage, the mixing switch stepped construction to, load stage from the power supply to ground.This frequency mixer has been realized the cascade arranged side by side of transconductance stage, mixer stage, load stage, is suitable for the low supply voltage application scenario.
Above-mentioned high-linearity folding mirror image frequency mixer comprises radio frequency transconductance stage, voltage mixing core circuit and intermediate frequency output stage.The radio frequency transconductance stage comprises NMOS pipe M1, the M2 as radio frequency mutual conductance pipe, source degeneracy resistance R 1, R2, and input radio frequency coupling capacitance C0, C1, input pipe biasing resistor R0, R3 are as diode connection PMOS pipe M3, the M4 of load pipe.Voltage mixing core circuit comprises two balance cocks to M12-M15.The intermediate frequency output stage comprises PMOS pipe M5, M6, M3, M4, the same channel length of M5, M6.Capacitor C 2, load resistance R4, R5, electric current injection current source M10, M7 and M11, M8; Common mode feedback circuit etc.
The input radio frequency positive pole is linked the top crown of capacitor C 0, and the bottom crown of capacitor C 0 links to each other with the grid of M1 pipe.The input radio frequency negative pole is linked the top crown of capacitor C 1, and the bottom crown of capacitor C 1 links to each other with the grid of M2 pipe.The anode of the source electrode connecting resistance R1 of M1 pipe, the negativing ending grounding of resistance R 1.The anode of the source terminating resistor R2 of M2 pipe, the negativing ending grounding of resistance R 2.The grid of the positive termination M1 of biasing resistor R0, the grid of the positive termination M2 of R3, the negative terminal of R0 and R3 connects bias voltage.The drain terminal of M1 connects the drain terminal of M3, and the drain terminal of M3 is connected with grid, and source electrode connects power supply.The drain electrode of M2 connects the drain electrode of M4, and the drain electrode of M4 is connected with grid, and source electrode connects power supply.The source electrode of M12 and the source electrode of M13 connect the grid of M4, and the grid of M12 and M15 connects the local oscillation signal negative pole, and the grid of M13 and M14 connects the local oscillation signal positive pole.The drain electrode of M12 and M14 connects the grid of M6, and the drain electrode of M13 and M15 connects the grid of M5.The source electrode of M5 and M6 connects supply voltage.The anode of the drain electrode connecting resistance R4 of M5, the negativing ending grounding of R4.The anode of the drain electrode connecting resistance R5 of M6, the negativing ending grounding of R5.Capacitor C 2 is connected in parallel between the drain electrode of the drain electrode of M5 and M6.M10 and M7 form the cascode current source, are connected in parallel on the two ends of R4.Form the cascode current source by M11 and M8, be connected in parallel on the two ends of R5.M10, the grid of M11 connects the output of error amplifier A1.The output common mode voltage that the positive input termination of A1 is gathered, negative input end connects with reference to common-mode voltage.
Below in conjunction with accompanying drawing and embodiment the utility model is described in further detail.
Figure 1 shows that mixer schematic diagram of the present utility model, but to detailed description and the explanation reference technique scheme and the embodiment part of this circuit.
Among Fig. 2 a and Fig. 2 b as can be seen because collapsible frequency mixer mixing switch and load stage are to be parallel-connection structure with transconductance stage.The limited output impedance meeting of transconductance stage produces the effect of shunting to radio-frequency current, and the radio-frequency current that causes transconductance stage to produce can not all enter the local oscillator level.In fact this accordion structure can regard the cascade of transconductance stage and mixer stage as, because mixer stage can produce extra distortion product (among Fig. 2 b, partial distortion has increased extra IM3), overall linearity has been worsened.
Figure 3 shows that linearity analysis of the present utility model, as can be seen from the figure, owing to adopted the two right structures of balance cock of the embedded mixing of current mirror.It is a linear process that radio-frequency current is mirrored to output stage, and the fundamental frequency of first order electric current and IM3 are exaggerated in same ratio to output stage.Therefore the linearity of whole frequency mixer is identical with first approximation.Avoided because the linearity that transconductance stage and output stage parallel construction cause worsens.
Figure 4 shows that mixer linearity degree test result of the present utility model, as can be seen from the figure, this frequency mixer is when realizing the 12.5dB gain, and OIP3 can reach 20.5dBm.
Claims (2)
1. a high-linearity folding mirror image frequency mixer is characterized in that, comprises the radio frequency transconductance stage, voltage mixing core circuit and the intermediate frequency output stage that connect successively; The radio frequency transconductance stage comprises: NMOS pipe M1 and M2, and PMOS manages M3, M4, M5 and M6; Voltage mixing core circuit comprises: PMOS manages M12, M13, M14 and M15:
The input radio frequency signal is capacitively coupled to input mutual conductance pipe M1, and M2 is converted into radio-frequency current;
M3 and M4, and M5, M6 have together constituted the current mirror of difference; Described radio-frequency current forms voltage signal on M3 and M4, M3, M4, the same channel length of M5, M6;
This voltage signal two balance cock pipes through being made of M12～M15 are timing at local oscillation signal, and the gate voltage of M3 is transported to M6, and the gate voltage of M4 is transported to M5; When negative, the gate voltage of M3 is transported to M5 at local oscillation signal, the gate voltage of M4 is transported to M6; Like this, the electric current that M5, M6 duplicate along with local frequency, switches between transconductance stage anode electric current and negative terminal electric current back and forth, forms the frequency conversion electric current, through forming output voltage after the low-pass filtering on the load resistance of intermediate frequency output stage.
2. high-linearity folding mirror image frequency mixer according to claim 1 is characterized in that: also comprise error amplifier A1;
Described radio frequency transconductance stage also comprises: isolation resistance R1 and R2; Input pipe biasing resistor R0 and R3;
Voltage mixing core circuit also comprises: NMOS pipe M10 and M7; NMOS pipe M11 and M8; Capacitor C 2;
The intermediate frequency output stage comprises: load resistance R4 and R5;
The input radio frequency positive pole is linked the top crown of capacitor C 0, and the bottom crown of capacitor C 0 links to each other with the grid of M1 pipe; The input radio frequency negative pole is linked the top crown of capacitor C 1, and the bottom crown of capacitor C 1 links to each other with the grid of M2 pipe;
The anode of the source electrode connecting resistance R1 of M1 pipe, the negativing ending grounding of R1; The anode of the source terminating resistor R2 of M2 pipe, the negativing ending grounding of R2;
The grid of the positive termination M1 of biasing resistor R0, the grid of the positive termination M2 of R3, the negative terminal of R0 and R3 connects bias voltage;
The drain terminal of M1 connects the drain terminal of M3, and the drain terminal of M3 is connected with grid, and source electrode connects power supply; The drain electrode of M2 connects the drain electrode of M4, and the drain electrode of M4 is connected with grid, and source electrode connects power supply;
The source electrode of M12 and the source electrode of M13 connect the grid of M4, and the grid of M12 and M15 connects the local oscillation signal negative pole, and the grid of M13 and M14 connects the local oscillation signal positive pole;
The drain electrode of M12 and M14 connects the grid of M6, and the drain electrode of M13 and M15 connects the grid of M5;
The source electrode of M5 and M6 connects supply voltage;
The anode of the drain electrode connecting resistance R4 of M5, the negativing ending grounding of R4; The anode of the drain electrode connecting resistance R5 of M6, the negativing ending grounding of R5;
Capacitor C 2 is connected in parallel between the drain electrode of the drain electrode of M5 and M6; The two ends of capacitor C 2 are medium frequency output end VIF+ and VIF-;
M10 and M7 constitute the cascode current source, are connected in parallel on the two ends of R4; Constitute the cascode current source by M11 and M8, be connected in parallel on the two ends of R5;
The grid of M10, M11 connects the output of error amplifier A1; The output common mode voltage that the positive input termination of A1 is gathered, negative input end connects with reference to common-mode voltage;
The loop that described error amplifier A1, M7, M8, M10, M11, VIF+ and VIF-constitute is common mode feedback circuit.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201120006874XU CN201910768U (en) | 2011-01-11 | 2011-01-11 | High-linearity foldable image mixer |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201120006874XU CN201910768U (en) | 2011-01-11 | 2011-01-11 | High-linearity foldable image mixer |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CN201910768U true CN201910768U (en) | 2011-07-27 |
Family
ID=44302966
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201120006874XU Expired - Lifetime CN201910768U (en) | 2011-01-11 | 2011-01-11 | High-linearity foldable image mixer |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN201910768U (en) |
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103647565A (en) * | 2013-12-13 | 2014-03-19 | 中国电子科技集团公司第三十八研究所 | CMOS radio frequency receiving front end with wide temperature work gain automatic control function |
| CN107231130A (en) * | 2017-05-24 | 2017-10-03 | 东南大学 | The upconverter of fusion structure is switched based on mutual conductance pipe local oscillator |
| CN113746431A (en) * | 2021-08-06 | 2021-12-03 | 天津大学 | Ultra-wideband high-linearity frequency mixer with image rejection function |
-
2011
- 2011-01-11 CN CN201120006874XU patent/CN201910768U/en not_active Expired - Lifetime
Cited By (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103647565A (en) * | 2013-12-13 | 2014-03-19 | 中国电子科技集团公司第三十八研究所 | CMOS radio frequency receiving front end with wide temperature work gain automatic control function |
| CN103647565B (en) * | 2013-12-13 | 2015-10-21 | 中国电子科技集团公司第三十八研究所 | There is the CMOS receiver rf front-end of wide temperature working gain automatic control function |
| CN107231130A (en) * | 2017-05-24 | 2017-10-03 | 东南大学 | The upconverter of fusion structure is switched based on mutual conductance pipe local oscillator |
| CN107231130B (en) * | 2017-05-24 | 2020-06-30 | 东南大学 | Up-converter based on transconductance tube local oscillator switch fusion structure |
| CN113746431A (en) * | 2021-08-06 | 2021-12-03 | 天津大学 | Ultra-wideband high-linearity frequency mixer with image rejection function |
| CN113746431B (en) * | 2021-08-06 | 2024-01-05 | 天津大学 | Ultra-wideband high-linearity mixer with image rejection function |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN102075145B (en) | High-linearity folding image mixer | |
| CN103490731B (en) | A kind of Low-noise passive frequency mixer | |
| CN102163954B (en) | Low-voltage low-noise wideband mixer | |
| CN110138351B (en) | CMOS broadband balun radio frequency receiving front-end circuit | |
| CN106921346B (en) | High linearity broadband up-mixer | |
| CN105262443A (en) | High-linearity low-noise transconductance amplifier | |
| CN103401508A (en) | Fusion structure of LNA (low noise amplifier) and frequency mixer | |
| CN110557130B (en) | Receiver front-end circuit with current mode structure with enhanced out-of-band linearity | |
| CN104124923B (en) | A kind of low-noise mixer circuit | |
| CN107196611A (en) | Broadband single-ended transfer difference low-noise amplifier | |
| CN203368404U (en) | High-gain low noise amplifier | |
| CN102868377A (en) | Total 3G (Third Generation Telecommunication) CMOS (Complementary Metal-Oxide-Semiconductor Transistor) differential low-noise amplifier based on controllable active inductor | |
| CN104242830B (en) | Reconfigurable ultra-wideband low-noise amplifier based on active inductance | |
| CN106253854B (en) | A kind of mixer with local oscillator phase mismatch compensation function | |
| CN102522954B (en) | Current reuse high linearity folding current mirror mixer | |
| CN201910768U (en) | High-linearity foldable image mixer | |
| CN102638227A (en) | Ultra-wideband frequency mixer circuit with on-chip active balanced-unbalanced converter | |
| CN104065346A (en) | Broadband low noise amplifier circuit based on cross-coupled feedback | |
| CN202068377U (en) | Low-voltage low-noise broadband mixer | |
| CN107896093B (en) | Low-noise low-power consumption high-gain mixer | |
| CN112491371B (en) | High-linearity programmable AB-C class mixed transconductance low-noise transconductance amplifier | |
| CN202772848U (en) | Fully third generation telecommunication (3G) complementary metal oxide semiconductor (CMOS) difference low noise amplifier based on controllable active inductor | |
| CN101662261B (en) | High-linearity folding mixer | |
| CN108039869B (en) | Mixer based on transconductance coefficient correction structure | |
| KR20200128870A (en) | Resistive wideband low noise amplifier with noise canceller |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C14 | Grant of patent or utility model | ||
| GR01 | Patent grant | ||
| AV01 | Patent right actively abandoned |
Granted publication date: 20110727 Effective date of abandoning: 20130529 |
|
| RGAV | Abandon patent right to avoid regrant |