CN1834825A - 数字双回路输出电压调节 - Google Patents

数字双回路输出电压调节 Download PDF

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CN1834825A
CN1834825A CNA2006100036738A CN200610003673A CN1834825A CN 1834825 A CN1834825 A CN 1834825A CN A2006100036738 A CNA2006100036738 A CN A2006100036738A CN 200610003673 A CN200610003673 A CN 200610003673A CN 1834825 A CN1834825 A CN 1834825A
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阿莱恩·查普斯
丹尼斯·R.·洛阿克
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Abstract

一种开关模式电压调节器具有包括双数字控制回路的数字控制系统。电压调节器包括至少一个用于在电压调节器的相应输入和输出端之间传送电力的电源开关，和用于响应电压调节器的输出来控制电源开关的操作的数字控制器。数字控制器还包括双数字控制回路，其中第一控制回路提供高速率和低调节精确度，第二控制回路具有高精确度和低速率。因此，数字控制系统提供了高速率和高调节精确度的优势。

Description

数字双回路输出电压调节
技术领域
本发明涉及电压调节器电路，更具体地，涉及对利用双反馈回路(loop)来改善调节的开关模式电压调节器进行数字控制。
背景技术
开关模式电压调节器是本领域公知的将可用直流(DC)电平电压转换为另一种DC电平电压的电压调节器。开关模式电压调节器通过借助于将电流切换到输出电感来有选择地将能量存储在耦合到负载的输出电感中而将所调节的DC输出电压提供给负载。降压转换器(buckconverter)是一种特殊类型的开关模式电压调节器，它包括两个一般由MOSFET晶体管提供的电源开关。与负载并联连接的滤波电容器降低了输出电流的波动。脉宽调制(PWM)控制电路被用于以交替的方式控制电源开关的选通，从而控制输出电感中的电流。PWM控制电路响应负载条件的变化，利用反映输出电压和/或电流电平的反馈信号来调整被施加到电源开关上的占空周期。
传统的PWM控制电路是用模拟电路元件，如运算放大器和比较器来构建的。然而，我们希望用数字电路代替模拟电路元件，因为数字电路占用更少的物理空间和消耗更少的能量。一种传统的数字PWM控制电路包括减法器，它产生表示受控信号(如，输出电压(Vo))和参考电压之间的差异的误差信号。模数转换器(ADC)将误差信号转换为数字信号。数字误差信号被提供给具有传递函数H(z)的回路补偿滤波器，该回路补偿滤波器为电压调节反馈回路提供稳定性。然后，由数字脉宽调制器(DPWM)产生比例脉宽调制信号，其被用于控制电压调节器的电源开关。
为了使PWM控制电路的复杂度低，我们希望将数字信号的比特数保持为一个较小的数目。然而，此时，数字信号的比特数要足够高，以提供足够的分辨率，从而保证输出值的精确控制。如果输出电压需要在大范围内是可编程的，则很难在减法器上维持一个小的DC误差，并且因此，设定点的精确度误差将会增大。在通过提供可调整的增益和偏移量使得电路在宽范围内更加精确的同时，带来了额外的成本和复杂度。而且，ADC需要是很快的以响应负载条件的变化和使得反馈回路能够进行快速瞬时响应。当前的微处理器所展示的电源电流转换(slew)率达到20A/μs，以及未来的微控制器预期可达到超过350A/μs的转换率，因此电压调节器需要很快的响应。通常，快速的响应时间和DC精确度是相互矛盾的要求。数字信号的比特数量也会影响实现传递函数(H(z))的数字电路的复杂度，从而影响相关的成本。
因此，提供一种克服现有技术的这些及其它缺陷的用于对开关模式电压调节器进行数字控制的系统和方法是有利的。更具体地，有利地提供一种双回路输出电压控制电路，其用于利用具有更高可重复性和精确度的数字电路来控制开关模式电压调节器。
发明内容
本发明提供了一种带有数字控制系统的开关模式电压调节器。电压调节器一般包括至少一个适合于在电压调节器的相应输入和输出端之间传送电力的电源开关，和适合于响应电压调节器的输出来控制电源开关操作的数字控制器。数字控制器还包括双数字控制回路，其中第一控制回路提供高速率和低调节精确度，而第二控制回路具有高精确度和低速率。因此，本发明提供了高速率和高精确度的优势。
更具体地，第一数字控制回路包括：第一模数转换器，所述第一模数转换器提供了表示电压调节器的第一输出测量值和参考值之间的差异的第一数字误差信号；基于第一数字误差信号提供数字控制输出的第一数字滤波器；和提供控制信号给电源开关的数字脉宽调制器。控制信号具有与数字控制输出相对应的脉宽。第二数字控制回路包括提供电压调节器的第二输出测量值的第二模数转换器。第二数字控制回路提供了表示第二输出测量值和参考值之间的差异的第二数字误差信号。第二模数转换器比第一模数转换器具有更高的分辨率(resolution)。第二数字误差信号被施加到第一数字控制回路，从而提高第一输出测量值的精确度。
在本发明的一个实施例中，串行接口在操作上被耦合到第一和第二数字控制回路并适合于接收定义参考值的参考数据。串行接口还适合于发送对应于第二输出测量值的监控数据。串行接口还适合于接收系数数据和提供系数数据给第一数字滤波器，系数数据定义第一数字滤波器的滤波特性。数模转换器在操作上被耦合到串行接口，并且适合于将参考数据转换为参考值。
通过考虑以下优选实施例的详细描述，本领域的技术人员能够更全面地了解所述用于对开关模式电压调节器进行数字控制的系统和方法，以及能够实现其另外的优点和目的。将会对附图进行参考，首先简要地描述附图。
附图说明
图1描述了具有传统数字控制电路的开关模式电压调节器；
图2描述了具有数字控制电路的开关模式电压调节器，其中数字控制电路带有第二模拟控制回路；
图3描述了根据本发明第一实施例的具有数字双回路控制电路的开关模式电压调节器；
图4描述了用于图3的数字双回路控制电路的示例性数字滤波器；
图5描述了根据本发明第二实施例的具有数字双回路控制电路的开关模式电压调节器；以及
图6描述了用于图5的数字双回路控制电路的示例性的数字滤波器。
优选的实施方式
本发明提供了用于控制开关模式电压调节器的数字双回路输出电压控制电路。在以下的详细描述中，相同的元件序号在一个或多个附图中被用于描述相同的元件。
图1描述了具有传统数字控制电路的开关模式电压调节器10。电压调节器10包括将输入DC电压Vin转换为被施加到电阻性负载20(Rload)的输出DC电压Vo的降压转换器拓扑结构。电压调节器10包括一对由MOSFET装置提供的电源开关12，14。上侧的电源开关12的漏极端被耦合到输入电压Vin，下侧的电源开关14的源极端被连接到地，以及电源开关12的源极端和电源开关14的漏极端被耦合到一起以定义相位节点。输出电感16被串联耦合到相位节点和提供输出电压Vo的端之间，以及电容18与电阻性负载Rload并联耦合。相应的驱动器22，24交替驱动电源开关12，14的栅极端。数字控制电路30(以下描述)依次控制驱动器22，24的工作。电源开关12，14的打开和闭合在相位节点提供了具有一般矩形波形的中间电压，以及由输出电感16和电容18构成的滤波器将矩形波形转换为基本上DC的输出电压Vo。
数字控制电路30从电压调节器10的输出部分接收反馈信号。如图1所示，反馈信号与输出电压Vo相对应，但是应当理解，反馈信号还(或另外)可以对应于由电阻性负载Rload所牵引(draw)的输出电流或其组合。反馈通路还可包括由电阻26，28提供的分压器，从而将被检测的输出电压Vo降低到一代表电压电平。数字控制电路30提供了具有占空周期的脉宽调制波形，该占空周期被控制以调节输出电压Vo(或输出电流)至期望电平。尽管示例性的电压调节器10作为具有降压转换器拓扑结构被示出，但是，应该理解，使用数字控制电路30的电压调节器10的反馈回路控制的使用同样适用于其它公知的电压调节器拓扑结构，例如，以独立或非独立配置的增压和冲跳升压(buck-boost)转换器。
更具体地，数字控制电路30包括减法器32，模数转化器(ADC)34，数字滤波器36，和数字脉宽调制器(DPWM)38。减法器32接收反馈信号(即输出电压Vo)和电压参考(Ref)作为输入，并且提供模拟电压误差信号(Ref-Vo)。ADC34产生电压误差信号的数字表示。数字滤波器36具有传递函数H(z)，它将电压误差信号变换为数字输出提供给DPWM38，DPWM 38将数字输出转换为具有比例脉宽的波形。正如以上所讨论的那样，由DPWM 38产生的脉冲调制波形通过各自的驱动器22，24被耦合到电源开关12，14的栅极端。数字滤波器36还可以包括具有滤波系数的无限脉冲响应(IIR)滤波器，所述滤波系数通过适当的输入可以被选择性地修改，从而改变数字滤波器的性能特性。正如以上所讨论的，传统数字控制电路30的缺陷在于减法器32具有有限的静态精确度。
为了提高数字控制电路30的输出电压设定点的精确度，可以添加第二模拟控制回路40，如图2所示。第二控制回路40包括放大器46和积分器48。同第一控制回路一样，第二控制回路40从电压调节器10的输出部分接收与输出电压Vo相对应的反馈信号。反馈通路还可以包括由电阻器42，44提供的分压器，从而将被检测的输出电压Vo降低至一代表电压电平。反馈信号被提供给放大器46的反相输入端，放大器的非反相输入端被耦合到参考电压。放大器被选择为比减法器32具有更小的带宽，从而允许有高精确度以及低速率。放大器46的输出被提供给积分器48，积分器48接着通过适当的电阻器提供调整电压给第一回路的减法器32。积分器48保证了：第二控制回路的误差信号在稳态工作期间保持为零。在稳态条件下，第一控制回路提供快速瞬时响应，而第二控制回路提供高DC精确度。
现在参考图3，图中示出了根据本发明的第一实施例的具有数字双回路控制电路的开关模式电压调节器。数字控制回路包括串行接口52，它允许与主机系统进行双向数据通信，从而接收数据以控制数字控制电路的工作，从而控制电压调节器，以及将状态信息发送回主机系统。数模转换器56被耦合到串行接口52。从主机系统通过串行接口52提供的数字参考值被数模转换器56转换为参考电压，参考电压又被提供给减法器32用于与输出电压Vo的表示值相比较。通过这种方式，主机系统能够定义参考电压，从而控制输出电压Vo。串行接口52还将滤波器系数值从主机系统传递给数字滤波器36，从而控制数字滤波器36的特性。在这些方面中，数字控制电路包括与关于图1的上述电路基本相同的第一控制回路。
第二数字控制回路由模数转换器58和数字滤波电路70提供。模数转换器58接收与输出电压Vo相对应的反馈信号，其被由电阻器62，66提供的分压器降低到代表电压电平。模数转换器58通过监控电路54被耦合到串行接口52。这样，模数转换器58提供了输出电压的精确的数字测量值，以及该信息可以通过监控电路和串行接口52被传递回主机系统。在本发明的优选实施例中，数模转换器56具有比进行监控的模数转换器58低得多的分辨率。数模转换器56的分辨率被选择成与不同负载Rload的特定供电电压要求相对应。模数转换器34具有小的转换范围，但是需要是快速的。由于调节器的输出总是存在一些残余波动电压并且模数转换器34需要具有快速响应时间，所以，波动电压不能被过滤掉，因为这样将会减缓转换过程。因此波动在第一回路产生附加的误差信号。进行监控的模数转换器58能以相当低的采样速率工作，但是其应当是精确的。为了提高精确性，进行监控的模数转换器58将在其输入上包括抗混叠(anti-aliasing)滤波器，它也将减少调节器的输出上见到的波动电压。模数转换器58因此会测量输出的真均值，因此自然比模数转换器34具有更高的精确度。
数字滤波电路70还包括数字比较器76，数字滤波器74和可变电阻器72。数字比较器76在第一输入接收由主机系统提供的数字参考值，以及在第二输入接收输出电压Vo的数字测量值，并产生数字误差值。数字误差值通过数字滤波器74并控制可变电阻器72的设置。可变电阻器72是由电阻器28和64所定义的分压器的一部分。因此，提供给减法器32的输出电压Vo的代表值可以通过控制可变电阻器72的设置来调整。
图4更加详细地的示出了数字滤波电路70的实施例。正如以上所讨论的，数字参考值通常比模数转换器58的监控输出具有更低的分辨率。在图4的实施例中，参考信号具有9位的分辨率，而监控输出具有12位的分辨率。所示数字比较器82具有两个12位输入。参考信号被8乘(即，加上3个尾部的0比特)以使其增大到与监控输出相同的宽度。数字比较器82比较所述值并产生两个输出(即，A＞B，和A＜B)。所述两个信号控制作为积分器的上/下计数器84。因此，而当参考信号超过监控输出时(A＞B)计数器增加，而当监控输出超过参考信号时(A＜B)计数器减少。计数器84被选择以使得其不会过翻转(over-roll)(即，计数不会降到零以下并且当它达到其最大值时停止)。如图4所示，计数器84具有0到15范围内的4位分辨率。
可变电阻器由场效应晶体管861-864构成，每一个场效应晶体管具有耦合到地的源极端，并且其相应的漏极端耦合到电阻器882-885。电阻器881和921-924被串连耦合在一起并且在晶体管861-864的相继晶体管之间。晶体管861-864的栅极端被耦合到计数器84的4位输出的相应位。通过触发场效应晶体管861-864中的各个，从而将所述电阻器中的相关电阻器并联耦合，可变电阻器的有效电阻被改变。当计数器从0到15变化时，电阻器的值可被选择以使得输出电压变化(如，从-2％到+2％)。
计数器84由这样的信号提供时钟，该信号具有基本上比第一数字控制回路的PWM频率低的频率。在本发明的实施例中，计数器84由这样的信号提供时钟，该信号具有比PWM频率低100到1000倍范围内的频率。因此，第二数字控制回路基本上比第一数字控制回路慢，但是由于进行监控的模数转换器58的较大的分辨率，其提供了较高的精确度。
由于数字比较器82和计数器84是简单的数字电路，因此，在包含两个数字控制回路的单个数字控制电路中实现这些电路是相对容易的。这个实施例的缺陷是，数字滤波器74仍然作用于模拟电路，即，可变电阻器72。因此，数字较正值在作用于第一数字控制回路之前被转换为模拟信号。因此，一种可以使用完全的数字电路来实现的控制电路是更有利的。
现在参考图5，图中示出了根据本发明的第二实施例的具有数字双回路控制电路的开关模式电压调节器。这个实施例与前述实施例的不同在于包括具有数字比较器102、数字滤波器104和加法器106的数字滤波电路100。正如在前述实施例中的那样，数字比较器102在第一输入接收由主机系统提供的数字参考值，以及在第二输入接收输出电压Vo的数字测量值，并产生数字误差值。数字误差值经过数字滤波器104并提供数字值给加法器106。加法器将数字参考值与滤波的数字值合并以产生调整的数字参考值。调整的数字参考值被提供给数模转换器56，其将数字参考值转换为参考电压，参考电压接着被提供给减法器32用于与输出电压Vo的代表值比较。因此，数字滤波器104直接修改参考值，而不使用第一控制回路的分阻器。
由于参考数模转换器56比进行监控的模数转换器58具有更低的分辨率，因此，调整的数字参考值可能会落在模数转换器的离散点之间，这种情形会因为第二数字控制回路以低得多的频率运行而加剧。因此，在本发明的实施例中，数字滤波电路100适合于实际上增大参考数模转换器56的分辨率。另外，数字滤波电路100利用了第一数字控制回路具有低通滤波特性的优势，具体地，如果数字参考值能够足够快速地上下切换一个计数，则第一数字控制回路将切换参考值平均化并且在参考数模转换器56的输出得到平均参考值。
更具体地，图6更加详细地示出了图5的数字滤波电路100。数字滤波电路包括提供数字参考值的抖动(dithering)的相位累加器。数字滤波电路还被示出为包括计数器112，加法器114，116，120和相位转换器118。如图4的实施例，数字比较器102比较监控的值和参考的值并且产生两个输出(即，A＞B，和A＜B)。这两个信号控制作为积分器的上/下计数器112。因此，当参考信号超过监控输出时(A＞B)计数器增加，当监控输出超过参考信号时(A＜B)计数器减少。计数器112产生6位的数字误差值，其被分割以使得最高的两位被提供给加法器114，而最低的四位被提供给加法器120。这些最低的位被视为校正信号的小数部分并随时间被相位寄存器118抖动，相位寄存器118存储了4位误差值的连续的和。加法器120与相位寄存器118结合起来提供相位累加器，其中误差值的低4位被加到相位值，加法器120又被反馈回相位寄存器。只要加法器溢出，它产生一个进位，该进位被提供给加法器116。通过将该进位加入由加法器114产生的数字误差值，加法器116导致了数字误差值(5:0)的小数部分的抖动。
通过例子的方式，所抖动的参考值的平均值可以用1，1/16，2/16，...15/16，...314/16，315/16等范围内的增量来设置。因此，数模转换器56的分辨率可以用零数(fractional amount)来编程，以允许用更精确的方式对第一回路的输出电压进行控制，而不需要具有高分辨率的数模转换器。
通过这样描述用于对开关模式电压调节器进行数字控制的系统和方法的优选实施例，对于本领域的技术人员显而易见的是，该系统的某些优点已经被实现。还应当理解，在本发明的范围和精神之内还可以产生各种修改、改变及其另外的实施例。本发明还由下面的权利要求所限定。

Claims (21)

1.一种电压调节器，包括：
至少一个电源开关，用于在所述电压调节器的相应输入和输出端之间传送电力；和
数字控制器，用于响应所述电压控制器的输出来控制所述至少一个电源开关的操作，所述数字控制器包括：
第一数字控制回路，包括用于提供表示所述电压调节器的第一输出测量值和参考值之间的差异的第一数字误差信号的第一模数转换器，用于基于所述第一数字误差信号提供数字控制输出的第一数字滤波器，和用于提供控制信号给所述至少一个电源开关的数字脉宽调制器，所述控制信号具有与所述数字控制输出相对应的脉宽；和
第二数字控制回路，包括用于提供所述电压调节器的第二输出测量值的第二模数转换器，所述第二数字控制回路用于提供表示所述第二输出测量值和所述参考值之间的差异的第二数字误差信号，所述第二模数转换器比所述第一模数转换器具有更高的分辨率，所述第二数字误差信号被施加到所述第一数字控制回路上以提高所述第一输出测量值的精确度，并由此改善所述电压调节器的调节。
2.根据权利要求1的电压调节器，还包括串行接口，其在操作上被耦合到所述第一和第二数字控制回路并且用于接收定义所述参考值的参考数据。
3.根据权利要求2的电压调节器，其中所述串行接口还用于发送相应于所述第二输出测量值的监控数据。
4.根据权利要求2的电压调节器，其中所述串行接口还用于接收系数数据和提供所述系数数据给所述第一数字滤波器，所述系数数据用于定义所述第一数字滤波器的滤波特性。
5.根据权利要求2的电压调节器，还包括在操作上被耦合到所述串行接口的数模转换器，所述数模转换器将所述参考数据转换成所述参考值。
6.根据权利要求1的电压调节器，其中所述第一数字控制回路还包括减法器，用于提供表示所述第一输出测量值和所述参考值之间的所述差异的模拟误差信号，所述模拟误差信号被提供给所述第一模数转换器。
7.根据权利要求1的电压调节器，其中所述第二数字控制回路还包括数字比较器，用于接收所述第二输出测量值和所述参考值并且提供所述第二数字误差信号。
8.根据权利要求7的电压调节器，其中所述第二数字控制回路还包括在操作上被耦合到所述数字比较器的计数器，如果所述第二输出测量值小于所述参考值，则所述计数器沿第一方向计数，如果所述第二输出测量值大于所述参考值，则所述计数器沿相反方向计数。
9.根据权利要求8的电压调节器，其中所述第二数字控制回路还包括可变电阻器，其在操作上被耦合到所述输出端，并且响应所述计数器来调整所述第一输出测量值。
10.根据权利要求1的电压调节器，其中所述第二数字控制回路还包括可变电阻器，其在操作上被耦合到所述输出端，并且响应所述第二数字误差信号来调整所述第一输出测量值。
11.根据权利要求1的电压调节器，其中所述第二数字控制回路使用所述第二数字误差信号来调整所述参考值。
12.根据权利要求11的电压调节器，其中所述第二数字控制回路还包括提供所述参考值的抖动的相位累加器。
13.根据权利要求1的电压调节器，其中所述第一模数转换器以基本上高于所述第二模数转换器的速率被提供时钟。
14.一种控制电压调节器的方法，所述电压调节器包括用于在所述电压调节器的输入和输出端之间传送电力的至少一个电源开关，所述方法包括：
接收所述电压调节器的第一和第二输出测量值；
对所述第一输出测量值进行采样以提供表示所述输出测量值和参考值之间的差异的第一数字误差信号；
对所述第一数字误差信号进行滤波以提供数字控制输出；
提供控制信号给所述至少一个电源开关，所述控制信号具有与所述数字控制输出相对应的脉宽；
对所述第二输出测量值进行采样以提供表示所述输出测量值和参考值之间的差异的第二数字误差信号；和
使用所述第二数字误差信号来调整所述第一输出测量值；
其中，所述第一采样步骤以基本上比所述第二采样步骤更高的速度和更低的分辨率来执行。
15.根据权利要求14的方法，还包括接收定义所述参考值的参考数据。
16.根据权利要求14的方法，还包括发送与所述第二输出测量值相对应的监控数据。
17.根据权利要求14的方法，还包括在执行所述滤波步骤中接收系数数据和使用所述系数数据。
18.根据权利要求15的方法，还包括将所述参考数据转换为所述参考值。
19.根据权利要求14的方法，还包括提供表示所述第一输出测量值和所述参考值之间的所述差异的模拟误差信号。
20.根据权利要求14的方法，还包括使用所述第二数字误差信号来调整所述参考值。
21.根据权利要求14的方法，还包括抖动所述参考值。
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US7141956B2 (en) 2006-11-28
US20060208716A1 (en) 2006-09-21
KR20060101213A (ko) 2006-09-22
KR100779785B1 (ko) 2007-11-27
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US20070069706A1 (en) 2007-03-29
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