CN1391719A

CN1391719A - Non-saturating magnetic elements power converters and surge protection

Info

Publication number: CN1391719A
Application number: CN00815983A
Authority: CN
Inventors: 克里斯托弗·A·里吉奥; 加思·B·伍德兰德
Original assignee: Online Power Supply Inc
Current assignee: Online Power Supply Inc
Priority date: 1999-10-01
Filing date: 2000-09-26
Publication date: 2003-01-15
Also published as: CA2385145A1; EP1222732A2; WO2001026207A3; JP2003511999A; WO2001026207A2; KR20020038789A; AU7715000A; IL148862A0

Abstract

Single, multistage, and distributed magnetic switched and tank resonant power conversion systems utilizing NSME. The NSME provide, superior protection to conducted lightning transients, superior thermal operating bandwidth, higher magnetizing efficiency, greater flux/power density potential and form factor flexibility when implemented with the disclosed circuit strategies. Output voltage is maintained substantially constant and ripple free in the presence of line and load variations by the action of various feedback strategies. These mechanisms combine to produce compensations by controlling the duration and/or frequency of a switch or switches. A novel function generator implementation supplies a signal, which is a function of magnetic flux tracking, AC line phasing, and output voltage feedback to provide output regulation, active ripple rejection, and power factor correction to the AC line. Efficient energy storage and transfer is achieved by the optimized application of NSME. The use of efficient rectifying flyback management techniques protects switches and provides additional output. A second novel generator implementation supplies a two-phase signal, which is a function of switching frequency/duty cycle, and output voltage, provides regulation. Further efficiencies are realized by the inclusion of switching buffers that substantially reduce switching losses by presenting a high slew rate, low source impedance critically damped drive current to the main switch or switches.

Description

Non-saturating magnetic elements power converters and surge protection

The cross-application application

The application is the continuation of the part of the application 09/410/849 of submitting on October 1st, 1999.

Technical field

The present invention relates to converter, power supply; relate in particular to single-stage or multistage, AC/DC or DC/DC, isolation and push-pull converter non-isolation; include but not limited to; forward direction, backhaul, step-down, boost, recommend and mode of resonance converter and power supply; have the NSME independent or that distribute and the effectively backhaul management of band high speed FET switch, and/or have input PFC (power factor correction) and the input protection of lightning transition.It is distributed that the present invention also allows magnetic element, to adapt to the restriction of encapsulation, a plurality of secondary coil windings, or the work under very high winding voltage.

Background technology

Several basic topological structures are arranged, be normally used for realizing switch converters.

The DC-DC converter is the equipment that a kind of dc voltage of level is transformed to the dc voltage of another kind of level.This converter generally includes a magnetic element, is wound with primary coil and secondary coil winding thereon to form transformer.Come the energy delivery that takes place between winding is controlled by opening and closing the primary coil circuit with proper spacing.Magnetic element provides alternating voltage and electric current, and its amplitude can recently be regulated by the number of turn and the number of turn that change every group of winding.Magnetic element provides the isolation of electric current between the input and output of converter.

A kind of topological structure is a push-pull converter.Output signal is the output of IC network, and it is " connection " and " shutoff " transistor alternately.High frequency square wave driving magnetic element in transistor output is AC (alternating current) biasing.The second coil side output rectified wave of isolating is to produce DC (direct current).Compare with other topological structure, push-pull converter has more parts usually.Push pull mode has used magnetic element effectively by producing the AC biasing, but that the problem of bringing is a number of components is many, hot off-load, excessive magnet and complicated iron core replacement scheme.The use of the spacing network by the power consumption on the primary side switch occurs in the destructive backswing voltage Be Controlled on the switch.Another kind of topological structure is a forward converter.When the primary side of forward direction converter powered up, energy was sent to the secondary coil winding immediately.Except above-mentioned problem, the problem that forward converter brings is that invalid (the dc biasing) of magnetic element used.The prior art power supply uses the apertured ferrimagnetism element of high magnetic permeability.These are known and widely used in this area.The magnet of prior art power supply is typically designed to the twice that is used for needed rated power, and needs complicated method to reset and the cooling magnetic element, has caused cost to increase and limited working temperature.This is because in the course of the work, produces heat in iron core, and it has increased magnetic permeability and has reduced saturation threshold, makes the high magnetic permeability magnetic element saturated.This has produced heat out of control, current spike and/or in air-gap big leakage current, the efficient of reduction and the final power under high temperature and/or high capacity reduce.Whole effect is, lower efficient, and lower power density and depend on the power supply that compulsory air/heat descends, it is for the excessive ferrimagnetism element of given output needs certain hour, temperature and load under.

Improve

The improvement of combination of the present invention is converted into higher system effectiveness, higher power density, and lower working temperature and improved hot holding capacity, thus reduce or removed the air cooled needs of exporting for each unit of pressure.The unsaturation magnetic characteristic is more insensitive (seeing Figure 17) to temperature, thereby allows converter to be operated in bigger temperature range.In practice, the working temperature of NSME is restricted to 200 ℃ by lead/core insulation; But not saturable magnetic materials still can be worked near its Curie temperature of 500 ℃.

The circuit strategy that needed converter has has advantageously utilized independent and distributed NSME.

The buffer circuits that needed converter has provides the quick of main FET, Low ESR critical damping switch.

Needed converter has been adopted effective a plurality of " little stress " backhaul administrative skill, the excessive node voltage on converter switches with rectification and critical damping.

Needed converter has the magnetic flux feedback frequency modulation(FM).

Needed converter is proofreaied and correct the AC power factor.

Needed converter satisfies and has surpassed the EMI requirement of category-B conducting.

Needed converter can bear lightning and harsh thermal environment.The present invention will handle these and more problem.

Summary of the invention

Main aspect of the present invention is in order to realize having the converter of following circuit strategy, and it has utilized independent and distributed NSME to realize the improvement in performance of key disclosed herein.

Another aspect of the present invention provides has independent and unique resonant groove path circuit converter strategy distributed NSME, and it has utilized higher primary side circuit voltage amplitude, produces high frequency/high density flux.

Another aspect of the present invention is the resonant groove path converter topology structure of the high-energy-density single-stage FREQUENCY CONTROL that realizes by independent and use distributed NSME.Another aspect of the present invention provides a kind of converter design, has utilized the FET Driving technique, comprises ultrafast, the low RDS on the N-channel fet, the main FET gate pole that is used to charge, and ultrafast P-channel transistor, and main FET gate pole is used to discharge.

Another aspect of the present invention is for converter is provided, and it has adopted effective a plurality of " little stress (stress-less) " backhaul administrative skill, the excessive node voltage on converter switches with rectification and critical damping.

Another aspect of the present invention is for a kind of converter being provided, having the frequency modulation(FM) of iron core (magnetic flux) synchronization zero passage.

Another aspect of the present invention is in order to provide High Power Factor to the AC circuit.

Another aspect of the present invention is for the protection to high voltage (incoming line) transition is provided.

Another aspect of the present invention is for advantageously in conjunction with distributed magnet and other converter aspects.

Another aspect of the present invention is that the fluctuation of the active that provided by the control of several high-gain high-speed isolated and reponse system suppresses.

Others of the present invention obtain embodying from following description and claims, and wherein with reference to the accompanying drawing as this specification part, wherein identical reference symbol is specified corresponding components in several figure.

Description of drawings

Fig. 1 and 1A are the schematic diagrames of the output translator embodiment that isolates of the AC-DC of two-stage correcting power factors of the present invention.

Fig. 2 is the schematic diagram of single-stage DC-AC converter embodiment with output branch circuit DCAC1 of isolation.

Fig. 3 and 3A are the schematic diagrames of the output translator embodiment of three grades of AC-DC isolation of the present invention.

Fig. 4 is the schematic diagram of the single-stage AC-DC converter branch circuit ACDFPF of correcting power factors.

Fig. 4 A is the schematic diagram with another power factor controller of load balancing converter branch circuit ACDFPF1.

Fig. 5 is the figure of the typical winding current of comparison in the saturated and unsaturation magnet that equates inductance.

Fig. 6 is the schematic diagram of the low-end switch buck converter branch circuit NILBK of non-isolation.

Fig. 7 is the preferred embodiment schematic diagram of the single-stage converter branch circuit TCSSC of tank circuit connection.

Fig. 8 is the schematic diagram of totem rod (totem pole) the converter branch circuit TCTP of tank circuit connection.

Fig. 9 is the block diagram of the DC-DC booster converter NILSBST of the non-isolation of single-stage.

Figure 10 is the boost schematic diagram of push-pull converter BSTPP of control of DC-DC that two-stage is isolated.

Figure 11 is the figure as the magnetic permeability of the function of temperature of prior art typical case magnetic element material.

Figure 12 is the figure as the magnetic flux density of the function of temperature of prior art typical case magnetic element material.

Figure 12 A is the figure of prior art typical case magnetic element material for the magnetic element loss of various magnetic flux densities and operating frequency.

Figure 13 is the figure that the standard switch loss is shown.

Figure 14 illustrates the figure than the low switch loss of the present invention.

Figure 15 is the figure of magnetization curve (BH) that the NSME material is shown.

Figure 15 A is the figure of the magnetization curve of H material.

Figure 16 is the figure of the magnetic element loss of the various magnetic flux densities of NSME material and operating frequency.

Figure 17 is the figure as the magnetic permeability of the function of temperature of NSME.

Figure 18 is that the boost schematic diagram of NSME branch circuit PFT1 is represented.

Figure 18 A is that the schematic diagram of NSME branch circuit PFT1A is represented.

Figure 18 B is that the schematic diagram of unsaturation two ends NSME branch circuit BL1 is represented.

Figure 18 C is the schematic diagram with the NSME PFT1D of distributed magnet accessory realization.

Figure 19 is that the schematic diagram of recommending NSME branch circuit PPT1 is represented.

Figure 19 A is that the schematic diagram that another kind is recommended NSME branch circuit PPT1A is represented.

Figure 20 is the schematic diagram of NSME input transient protective and line filter branch circuit LL.

Figure 20 A is the schematic diagram that another line filter LF is shown.

Figure 21 is the schematic diagram of another NSME input transient protective and line filter branch circuit LLA.

Figure 22 is the schematic diagram of AC line rectifier branch circuit BR.

Figure 23 is the schematic diagram of power factor controller branch circuit PFA.

Figure 24 is the schematic diagram of the control element branch circuit PFB that boosts of another power factor correction.

Figure 25 is the schematic diagram of output rectifier and filter branch circuit OUTA.

Figure 25 A is the schematic diagram of another rectifier branch circuit OUTB.

Figure 25 B is the schematic diagram of another last output rectifier and filter branch circuit OUTBB.

Figure 26 is the schematic diagram of the power controlling branch circuit CP of 18 volts of DC of drift.

Figure 26 A is the schematic diagram of another 18 volts of DC power controlling branch circuit CP1.

Figure 26 B is as watt to be the figure of VCC control voltage of function of the power output of unit in the process of branch circuit ACDCPF1 (Fig. 4 A) work.

Figure 27 is the schematic diagram of recommending power controlling branch circuit CPA of 18 volts of DC of another drift.

Figure 28 is the schematic diagram of overheat protector branch circuit OTP.

Figure 29 is the schematic diagram of the anti-buffer branch circuit of High speed and low resistance AMP, AMP1, AMP2 and AMP3.

Figure 30 is the schematic diagram of the spacing branch circuit SN of main switch.

Figure 30 A is the schematic diagram of the spacing branch circuit DSN of main switch rectifier diode.

Figure 30 B is the schematic diagram of the spacing branch circuit SNBB of main switch.

Figure 31 is the schematic diagram of another spacing branch circuit SNA.

Figure 32 is the schematic diagram of the spacing branch circuit SNB of mirror image (mirror).

Figure 33 is the schematic diagram of pulsewidth/frequency modulator branch circuit PWFM.

Figure 34 is the node voltage oscillogram of measuring in the course of work of branch circuit PWFM (Figure 33).

Figure 35 is the oscillogram of the primary side tank circuit voltage measured in the course of work of branch circuit TCTP (Fig. 8).

Figure 36 is the schematic diagram of 18 volts of DC power controlling branch circuit REG of non-isolation.

Figure 37 is the schematic diagram of the high-end switch buck converter branch circuit HSBK of non-isolation.

Figure 38 is the schematic diagram with 2 stage converter embodiment that recommends the low side reduction regulation of exporting branch circuit LSBKPP of isolation.

Figure 39 is the schematic diagram of the two-stage low-end switch buck converter branch circuit LSBKPPBR of another isolation.

Figure 40 is the schematic diagram of overvoltage feedback branch circuit I PFFB.

Figure 40 A is the schematic diagram of the output voltage feedback branch circuit FBA that boosts of non-isolation.

Figure 40 B is the schematic diagram of the output voltage feedback branch circuit I FB of isolation.

Figure 40 C is the schematic diagram of the overvoltage feedback branch circuit I OVFB of another isolation.

Figure 40 D is the schematic diagram of the output voltage feedback branch circuit FBD that boosts of another non-isolation.

Figure 41 is the schematic diagram of the output voltage feedback branch circuit FBI of non-isolation.

Figure 41 A is the schematic diagram of the feedback branch circuit FB2 of another non-isolation.

Figure 42 is the schematic diagram of overvoltage protection branch circuit OVP.

Figure 42 A is the schematic diagram of the overvoltage feedback branch circuit OVP1 of isolation.

Figure 42 B is the schematic diagram of overvoltage protection branch circuit OVP2.

Figure 42 C is the schematic diagram of the overvoltage feedback branch circuit OVP3 of isolation.

Figure 43 is the schematic diagram of pusb pull oscilator branch circuit PPG.

Figure 44 is the schematic diagram of soft start/inrush current restriction branch circuit SS1.

Figure 44 A is the line current in the course of work of branch circuit SS1 (Figure 44) and the oscillogram of output voltage.

Figure 45 is the schematic diagram that starts branch circuit FS1 fast.

Figure 45 A is the oscillogram of branch circuit FS1 in the course of work of branch circuit SS1 (Figure 44).

Figure 46 is the schematic diagram of another transient protective branch circuit TRN.

Figure 46 A is another schematic diagram that is used for the transient protective branch circuit TRNX of applications.

Figure 46 B is the oscillogram of converter in the process of high voltage transient incident.

Figure 47 is a signal flow graph of telling about the load balancing system.

Figure 47 A is another signal flow graph of telling about the load balancing system.

Embodiment

Before in detail explaining disclosed embodiment of the present invention, be appreciated that the details that the invention is not restricted to be applied to shown or the specific device described, because the present invention can be applied to other embodiment.

Representation " distributed magnet (distributed magnetics) " is meant that the primary coil winding of the shared single series connection of a plurality of magnetic elements is so that induce the structure of the output current of isolation in the secondary coil winding of a plurality of serial or parallel connections.

And employed here term is for purpose of description, and unrestricted purpose.

In this description and other description of being included in here, following symbol will have the meaning of giving them: "+" expression is connected in series, and connects with resistance B such as resistance A, is shown " A+B "." ‖ " expression is connected in parallel, and is in parallel with resistance B such as resistance A, is shown " A ‖ B ".

At first with reference to figure 7, Fig. 7 is the schematic diagram of the preferred embodiments of the present invention.

Fig. 7 is the schematic diagram that the tank circuit connects the preferred embodiment of (tank coupled) single-stage converter branch circuit TCSSC.Branch circuit TCSSC comprises resistance R 20 and RLOAD, capacitor C 10, transistor Q21 and Q11, branch circuit CP (Figure 26), branch circuit PFT1 (Figure 18), branch circuit OUTA (Figure 25), branch circuit AMP (Figure 29), branch circuit IFB (Figure 40 B) and branch circuit PWFM (Figure 33).

Fig. 7	Table
Fig. 7	Table	Element	Value/parts number
????R20	1k ohm	Element	Value/parts number
????R20	1k ohm	????R61	2k ohm
????Q21	????TST541	????R61	2k ohm
????Q21	????TST541	????U12	????4N29
????Q11	????IRFP460	????U12	????4N29
????Q11	????IRFP460	????C10	????1.8uf

TCSSC can be configured to the converter as AC-DC, DC-DC converter, DC-AC converter and the work of AC-AC converter.Branch circuit TCSSC comprises resistance R 20 and RLOAD, capacitor C 10, switch Q11 and Q21, optical isolator U12, branch circuit PFT1 (Figure 18), branch circuit OUTA (Figure 25), branch circuit CP (Figure 26), branch circuit AMP (Figure 29), branch circuit IFB (Figure 40 B) and branch circuit PWFM (Figure 33).External power source VBAT is connected to pin DCIN+ and DCIN-.Power supply also can have the AC-DC converter of the single-stage correcting power factors of isolating output from the AC circuit such as the rectification of Figure 20 or Figure 21 with formation.From DCIN+, resistance R 20 is connected to branch circuit CP pin CP+, branch circuit AMP pin GA+, the anode of U12LED and branch circuit PWFM pin PWFM+.Resistance R 20 provides starting power to arrive converter, arrives 18 volts of desired outputs up to power controlling adjuster branch circuit CP.The VBAT negative pole is earth-return (ground return) node, is connected to branch circuit PWFM pin PWFMB, Q11 source electrode, branch circuit AMP pin GA0, branch circuit CP pin CT0, pin DCIN-and branch circuit PFT1 pin S1CT.The magnetic element winding node S1H of branch circuit PFT1 is connected to CP pin CT1A.The magnetic element winding node S1L of branch circuit PFT1 is connected to CP pin CT2A.Branch circuit PWFM is designed to the variable frequency generator of constant 50% conduction ratio.Branch circuit PWFM clock output pin CLK is connected to the input of buffering branch circuit AMP pin GA1.The output of buffering branch circuit AMP pin GA2 is connected to gate pole and the R21 of Q11.Resistance R 21 is connected to the negative electrode of U12 LED.The leakage level of the emitter of Q21 and Q11 is connected to branch circuit PFT1 pin P1A.The pin P1B of branch circuit PFT1 is connected to node DCIN+ by tank capacitance C10, and the Q21 collector electrode is connected to U12 photoelectric crystal pipe collector by resistance R 61.The emitter of U12 phototransistor is connected to the base stage of Q21.If PWFM pin CLK is high, then transistor Q11 conducting by NSME PFT1, comes charging capacitor C10 by VBAT, stored energy in PFT1.If branch circuit PWFM switch CLK is low, then Q11 ends.If CLK is low, then the LED of U12 is switched on, and injects base current to Q21.Along with transistor Q21 conducting, tank circuit is done, and allows capacitor C 10 to discharge into NSMEPFT1 winding 100 (Figure 18).Now, the energy that is not sent to load is released to present forward biased NPN switch Q2 from NSME PFT1, returns capacitor C 10.Thereby any energy that is not used by the secondary coil load still remains in the primary coil circuit (winding 100) of tank circuit connection.When switch took place with resonance frequency, high voltage vibrated between C10 and winding 100, generated high magnetic flux density AC amplitude (excursion) in PFT1.C10 and PFT1 exchange variable AC electric current, and its amplitude is by frequency modulation schemes IFB and PWFM control.Big primary coil voltage produces big high frequency bias in NSME PFT1, thereby produces high magnetic flux density AC amplitude, and (Figure 18) gathered in the crops by secondary coil winding 102 and 103, with holding load or rectifier branch circuit OUTA.The magnetic element winding node S2H of branch circuit PFT1 is connected to OUTA pin C7B.The magnetic element winding node S2L of branch circuit PFT1 is connected to OUTA pin C8B.The magnetic element winding node S2CT of branch circuit PFT1 is connected to OUTA pin OUT-.Node OUT-is connected to RLOAD, pin B-and branch circuit IFB pin OUT-.The power of rectification is sent to the pin OUT+ of OUTA and is connected to RLOAD, pin B+ and branch circuit IFB pin OUT+.What branch circuit IFB provided isolation feeds back signal to branch circuit PWFM.The FREQUENCY CONTROL pin FM1 of branch circuit PWFM is connected to branch circuit IFB pin FBE.The reference pin REF of the inside of branch circuit PWFM is connected to branch circuit IFB pin FBC.PWFM is designed to work in the tank circuit (tank) resonance frequency (2 ^*π ^*SQR (C10 ^*The inductance of 100 (Figure 18))).When branch circuit IFB detected converter and is output as target voltage, electric current injected FM1 from PWFM pin REF.Injection current then orders PWFM to provide lower clock frequency to arrive pin CLK to FM1.Drive the tank circuit and leave the energy that resonance has reduced the adding tank circuit, thereby reduced the converter output voltage.If the feedback signal order PWFM from IFB turn-offs or 0Hz, and is promptly non-loaded, then all primary side actions stop.Input current from VBAT can be stable state or variable DC.When TCSSC works in the AC (branch circuit LL Figure 20) of rectification, high input (line) power factor and input transient protective have then been realized.The primary coil of PFT1 and secondary current are sinusoidal wave, do not have the border transition, make converter very quiet.In addition, switch Q11 and the Q21 big cyclical voltage (seeing Figure 35) that will not be subjected in the tank circuit, responding to.This makes and can use the more switch of low-voltage in design, thereby has reduced loss and increased MTBF.In the topological structure of this converter, branch circuit TCSSC has utilized the desired characteristics of NSME.TCSSC is suitable for realizing (Figure 18 C) with distributed NSME PFT1D very much.This combination examples distributed magnet how can make favourable high voltage converter design support the form factor flexibility and obtain the secondary coil output of a plurality of parallel connections from the primary coil winding of the dividing potential drop of the series connection on a plurality of NSME.This magnet strategy is for solving lead/core insulation, form factor and packages limits, and the problem of circuit complexity and manufacturability aspect is useful.These converter strategies are of great use for the high current density output that the primary side from the high voltage low current series connection obtains to isolate.Adjust the second coil side turn ratio and make TCSSC can produce very large AC or DC output voltage, and low voltage and high current output.

Other embodiment

Fig. 1 and 1A are the schematic diagrames of the AC-DC converter of two-stage correcting power factors.The present invention includes route protection filter branch circuit LL (Figure 20) and full-wave rectifier branch circuit BR (Figure 22), have the adjusting voltage-boosting stage of the correcting power factors of branch circuit PFA2 (Figure 23), spacing branch circuit SN (Figure 30), magnetic element branch circuit PFT1 (Figure 18), branch circuit CP (Figure 26), buffering branch circuit AMP (Figure 29), excess temperature branch circuit OTP (Figure 28), overvoltage feedback branch circuit I PFFB (Figure 40) and Voltage Feedback branch circuit IFB (Figure 40 B); Starting resistance R2, filter capacitor C1, PFC capacitor C 2, backhaul (flyback) diode D4, switching transistor Q1 supports (holdup) capacitor C 17 and C16 and resistance R 17; What have branch circuit CPA (Figure 27), PPG (Figure 43), AMP1 (Figure 29), AMP2 (Figure 29), spacing branch circuit SNB (Figure 32) and SNA (Figure 31), resistance R LOAD, transistor Q6 and Q9, magnetic element PPT1 (Figure 19) and OUTA (Figure 25) effectively recommends isolation level.

Fig. 1	Table
Fig. 1	Table	Element	Value/parts number
????C1	????0.01uf	Element	Value/parts number
????C1	????0.01uf	????C2	????1.8uf
????R2	100k ohm	????C2	????1.8uf
????R2	100k ohm	????D4	????8A，600V
????Q1	????IRFP?460	????D4	????8A，600V
????Q1	????IRFP?460	????C17	????100uf
????C16	????100uf	????C17	????100uf
????C16	????100uf	????R17	375k ohm
????Q6	????FS?14SM-18A	????R17	375k ohm
????Q6	????FS?14SM-18A	????Q9	????FS?14SM-18A

In 2 stage converter, input (boosting) level that is corrected power factor to the primary side voltage of second push-pull output stage is modulated.Each level can comprise monomer-type and distributed NSME.The B-H hysteresis of unsaturation magnet as shown in figure 15.Although following description is based on specific converter topology structure, that is, the primary side of backhaul control and constant conduction ratio recommend second coil side, but the number of the output of several topological structures, style and layout are bright for instance, but not in order to restriction.In addition, unsaturation magnet BL1, PFT1 and PPT1 can realize with distributed NSME.As an example, PFT1 is illustrated as distributed magnet PFT1A (Figure 18 C).Distributed magnet can make favourable high-voltage variable parallel operation design variations support the form factor flexibility and obtain the secondary coil output of a plurality of parallel connections from the primary coil winding of the dividing potential drop of the series connection on a plurality of NSME.Support the negative pole of electric capacity [C17 ‖ C16] to be connected to the positive pole of bridge.This makes the line voltage distribution of rectification not comprise the booster voltage of supporting on the electric capacity.And this makes push-pull cascade directly to regulate from (PFC) level of boosting.This has just removed common PWM control and many branch circuit parts of transformer of the too huge hot off-load of prior art.The AC circuit is connected between the pin LL1 and LL2 of branch circuit LL (Figure 20).Be connected to node LL0 AC/.AC circuit filtering and voltage limit appears at node/pin LL5 of branch circuit LL and is connected to the Node B R1 (Figure 22) of bridge rectifier branch circuit BR.Filtering and neutrality/AC return branch of AC voltage limit appear at the pin LL6 of branch circuit LL, are connected to the input pin BR2 of BR.Circuit is by full-wave rectification and be converted into positive haversine, appears at the Node B R+ (Figure 22) of branch circuit BR.Starting resistance R2 connects BR+ to branch circuit CP pin CP+.Node CP+ is connected to pin PFA+ (Figure 23) and excess temperature switch branch circuit OTP (Figure 28) the pin GAP of control element branch circuit PFA.Resistance R 2 provides starting power to arrive control element, is in output in full up to rectifier/adjuster CP.The node S1H of PFT1 is connected to the node PFVC of branch circuit PFA.When the voltage of S1H is zero, detected iron core zero crossing.The zero crossing of iron core is used to reset PFC and new cycle of beginning.The cathode node BR+ of the DC side of bridge is connected to BR-by capacitor C 2.Select C2 to be used for various circuits and loading condition, improved power factor and reduced line harmonic and EMI simultaneously so that switching current is disconnected from circuit.The primary side pin P1B of NSME branch circuit PFT1 (Figure 18) and S2CT are connected to the pin SNL1 of spacing branch circuit SN (Figure 30), are connected to branch circuit BR pin BR+ and are connected to pin BR+ (Figure 1A).The return line BR-of the AC power of rectification is connected to following pin: the BR-of branch circuit BR, PFA pin BR-, branch circuit AMP pin GA0, output switch Q1 source electrode, capacitor C 2, branch circuit CP pin CT0, branch circuit PFT1 pin S1CT and CT20, C1 is connected to ground node LL0 by the EMI filter capacitor.Pin BR+ among Fig. 1 is connected to the branch circuit CPA pin of Figure 1A, SN pin SNL1, branch circuit PFT1 pin P1B and branch circuit PFT1 pin S2CT.Pin BR+ continues to be connected to the branch circuit CPA pin CT20 of Figure 1A, PPG (Figure 43) pin PPG0, branch circuit AMP1 pin GA0, branch circuit AMP2 pin GA0, branch circuit IPFFB pin PF-, electric capacity [C16 ‖ C17 ‖ resistance R 17], transistor Q6 source electrode, transistor Q9 source electrode, branch circuit SNA pin SNA2 and branch circuit SNB pin SNB2.The leakage level of output switch Q1 is connected to diode D4 anode, branch circuit SNB pin SNL2 and branch circuit PFT1 pin P1A and branch circuit SN pin SNL2.Spacing network SN has reduced the high voltage stress to Q1, and D4 begins conducting up to the backhaul diode.The circuit coupling of AC-DC transducer-level (Fig. 1), the output voltage that boosts and regulate of correcting power factors appears at node PF+.By connecting the branch circuit DSN (Figure 30 A) in parallel, can realize other efficient with D4.The output PF+ that regulates that boosts is connected to following node: branch circuit SN pin SNOUT, branch circuit DSN pin SNOUT and diode D4 negative electrode.Node PF+ also is connected to the electric capacity [C16 ‖ C17 ‖ R17] among Figure 1A, branch circuit IPFFB (Figure 40) pin PF+, branch circuit PPT1 (Figure 19) pin P2CT, spacing branch circuit SNA (Figure 31) pin SNA3 and spacing SNB (Figure 32) pin SNB3.The magnetic element winding pin S1H of branch circuit PFT1 is connected to the pin PFVC of CP pin CT1A and branch circuit PFA.The magnetic element winding node S1L of branch circuit PFT1 is connected to CP pin CT2A.The magnetic element winding node S2H of branch circuit PFT1 is connected to pin one 0, is connected to the CPA pin CT1B of Figure 1A then.The magnetic element winding node S2L of branch circuit PFT1 is connected to pin one 2, is connected to the CPA pin CT2B of Figure 1A then.Use AC circuit phase place, load voltage and magnetic element feedback, branch circuit PFA produces command pulse PFCLK.The pin pfc LK of branch circuit PFA (Figure 23) is connected to the input of the buffer amplifier pin GA1 of branch circuit AMP1 (Figure 29).The high speed gate-drive output pin GA2 of the buffering of branch circuit AMP is connected to the gate pole of switch FETQ1.The buffering that is provided by AMP has shortened the time of switch Q1ON and OFF, has significantly reduced switching loss (seeing Figure 13 and 14).The source electrode of Q1 and pin GA0 are connected to return node BR-.From branch circuit OTP pin TS+, power is connected to branch circuit AMP pin GA+.Thermal switch THS1 is connected to Q1.If Q1 arrives about 105 ℃, then THS1 opens, and power transfer to branch circuit AMP, is turn-offed first (input) level safely.After THS1 is turn-offed in 20-30 ℃ of switch temperature decline, recover operate as normal.The leakage level of output switch Q1 is connected to the primary coil winding pin P1A of unsaturation magnet branch circuit PFT1 (Figure 18) and the pin SNL2 of spacing branch circuit SN (Figure 30).Reference voltage from PFC branch circuit PFA pin PFA2 is connected to feedback network branch circuit IPFFB pin FBC and branch circuit IFB pin FBC.The Control current feedback network is always added at the node PF1 of branch circuit PFA.Pin PF1 is connected to feedback network branch circuit IPFFB pin FBE and branch circuit IFB pin FBE.The non-overlapped two-phase generator of constant frequency/conduction ratio branch circuit PPG (Figure 43,1A) produces the driving of push-pull output stage.The first phase output pin PH1 is connected to branch circuit AMP1 pin GA1, and the second phase output pin PH2 is connected to branch circuit AMP2 pin GA1.The output of amplifier buffer branch circuit AMP1 pin GAP2 is connected to the gate pole of recommending output switch Q6.The output of amplifier buffer branch circuit AMP2 pin GAP2 is connected to the gate pole of recommending output switch Q9.Provide fast for Q6 and Q9 from the buffer current of AMP1 and AMP2, the switch of Low ESR critical damping has significantly reduced ON-OFF fringe time and switching loss.18 volts of power from the adjusting of branch circuit CPA (Figure 1A) pin CP2+ are connected to amplifier buffer branch circuit AMP1 pin GA+, amplifier buffer branch circuit AMP2 pin GA+ and branch circuit PPG pin PPG+.The leakage level of transistor Q6 is connected to spacing network branches circuit SNB pin SNB1 and the tapped primary coil magnetic element of unsaturation branch circuit PPT1 pin P2H.The leakage level of transistor Q9 is connected to spacing network branches circuit SNA (Figure 31) pin SNA1 and branch circuit PPT1 pin P2L.The source electrode of transistor Q6 is connected to spacing network branches circuit SNB pin SNB2, transistor Q9 source electrode, branch circuit SNA pin SNA2 and return node BR+.The output of the isolation of NSME branch circuit PPT1 pin SH is connected to the pin C7B of rectifier branch circuit OUTA (Figure 25 A), and pin SL is connected to branch circuit OUTA C8B.The centre tap of PPT1 pin SCT is that output is returned or negative pole node OUT-, and it is connected to branch circuit OUTA pin OUT-and branch circuit IFB (Figure 40 B) pin OUT-and RLOAD.The anodal output of converter is connected to RLOAD and branch circuit IFB pin OUT+ from branch circuit OUTA pin OUT+.Fig. 1 element LL1, BR, PFA, AMP, Q1, IPFFB, IFB and PFT1 (input stage) carry out the AC-DC conversion of correcting power factors.The high voltage output of the adjusting of this converter provides the effectively push-pull cascade of fixing frequency/conduction ratio, comprises PPG, AMP1, AMP2, Q6, Q9, PPT1 and OUTA (Figure 1A).Magnetic element branch circuit PPT1 provides electric current to isolate and crosses the mediation fluctuation at the voltage of secondary coil minimum, thereby minimizes the filtering requirements to rectifier branch circuit OUTA.5 volts of reference outputs are connected to pin one 5 from branch circuit PFA pin PFA2, are connected to branch circuit IPFFB pin FBC and the branch circuit IFB pin FBC of Figure 1A then.The pulse width control input is connected to pin one 4 from branch circuit PFA pin PF1, is connected to branch circuit IPFFB pin FBE and the branch circuit IFB pin FBE of Figure 1A then.The high-speed feedback that provides branch circuit IFB arrives the AC-DC converter, and the speed of voltage-boosting stage provides precise output voltage to regulate and fluctuation initiatively suppresses.If circuit or load flip-flop, then branch circuit IPFFB proofreaies and correct inner boosting with the voltage stabilizing of the output that remains on isolation.Load remote sensing known in the prior art and other feedback scheme can be realized with branch circuit IPFFB.This structure provides the input transient protective of correcting power factors, fast circuit-load response, excellent adjusting, the output of isolation and at high temperature quiet effectively work.

Fig. 2 is the schematic diagram of the embodiment of a DC-AC converter.DCAC1 of the present invention is an effective push-pull converter, comprises branch circuit PPG (Figure 43), AMP1 (Figure 29), AMP2 (Figure 29), SNB (Figure 32), SNA (Figure 31), PPT1 (Figure 19) and OUTA (Figure 25), switch Q6 and Q9.

Fig. 2	Table
Fig. 2	Table	Element	Value/parts number
????Q6	????FS?14SM-18A	Element	Value/parts number
????Q6	????FS?14SM-18A	????Q9	????FS?14SM-18A

Converter ACDC1 receives variable dc voltage and effectively it is transformed to the variable AC voltage output of fixing frequency.Simple change by to PPG can realize variable frequency work.In this embodiment, require fixing frequency work.Magnetic element comprises the unsaturation magnet.The figure of the B-H hysteresis of unsaturation magnet as shown in figure 15.Variable dc voltage is applied to pin DC+.Pin DC+ is connected to following node: branch circuit PPT1 (Figure 19) pin P2CT, spacing branch circuit SNA (Figure 31) pin SNA3 and spacing SNB (Figure 32) pin SNB3.The non-overlapped two-phase generator of constant frequency branch circuit PPG (Figure 43) produces the driving of recommending the output switch.The first phase output pin PH1 is connected to branch circuit AMP1 pin GA1, and the second phase output pin PH2 is connected to branch circuit AMP2 pin GA1.The output of amplifier buffer branch circuit AMP1 pin GAP2 is connected to the gate pole of recommending output switch Q6.The output of amplifier buffer branch circuit AMP2 pin GAP2 is connected to the gate pole of recommending output switch Q9.The buffering that is provided by AMP1 and AMP2 has shortened switch Q1ON and OFF time, has significantly reduced switching loss (seeing Figure 13 and 14).Outside 18 volts of power regulating are connected to amplifier buffer branch circuit AMP1 pin GA+ from pin P18V, amplifier buffer branch circuit AMP2 pin GA+ and branch circuit PPG pin PPG+.The leakage level of transistor Q6 is connected to spacing network branches circuit SNB pin SNB1 and the tapped primary coil magnetic element of unsaturation branch circuit PPT1 pin P2H.The leakage level of transistor Q9 is connected to spacing network branches circuit SNA (Figure 31) pin SNA1 and branch circuit PPT1 pin P2L.The source electrode of transistor Q6 is connected to spacing network branches circuit SNB pin SNB2, transistor Q9 source electrode, branch circuit SNA pin SNA2, branch circuit AMP1 pin GA0, branch circuit AMP2 pin GA0, branch circuit PPG pin PPG0 and return pin DC-.The AC output of NSME branch circuit PPT1 pin SH is connected to pin ACH, and pin SL is connected to pin ACL.The centre tap pin SCT of PPT1 is connected to pin AC0.Magnetic element branch circuit PPT1 provides electric current to isolate and crosses the mediation fluctuation at the voltage of secondary coil minimum, thereby minimizes the filtering requirements when adding the rectifier accessory.Branch circuit DCAC1 can be used as unit converter or the effective level of the quick peace and quiet of conduct in the multilevel converter system.Branch circuit DCAC1 has realized the output of isolating, quietly work, effectively conversion and the work under high temperature and low temperature.

Fig. 3 and 3A are three grades of forms of the present invention.This layout comprises AC-DC or DC-DC booster converter level, DC-DC forward converter level, and push-pull cascade.By in every grade in conjunction with the low current reduction regulation, buffer switch, the spacing and NSME of rectification, this system has reduced loss.The voltage-boosting stage of correcting power factors is used to guarantee, it seems that any AC circuit that loads on that is connected to converter all resemble resistive load, eliminated undesirable harmonic wave and displacement electric current in AC power circuit.The NSME that compared with prior art has lower magnetic permeability, be used to minimize magnetization loss, improve coupling efficiency, minimize the magnetic element heating, eliminate saturable core pin/slit electric current and leaked, reduced number of components, reduced fire damage, with increased MTBF (mean time before failure, fault-free average time).The present invention has also used the emitter follower circuit with speed-sensitive switch FET, so that turn round (slew) main FET gate pole apace.The use of unsaturation magnet makes it possible to be operated in higher voltage, and it has reduced electric current pro rata, owing to also reduced I ²The switch that the heating of R causes, magnetic element and conductor losses.High voltage FET switch also has the advantage of lower gate pole capacity, and this has brought switch faster.When connecting, the N-raceway groove gate-drive FET main FET gate pole that charges apace.When turn-offing, the PNP Darlington transistor switch main FET gate pole that discharges apace.Backhaul effect in the PFC level is managed by using the rectification RC network, this rectification RC network is at the two ends with output diode, have other capacity coupled diode,, thereby disconnect and the further backhaul of damping perception at the two ends of the magnetic element of switch.The present invention includes: the adjusting voltage-boosting stage of correcting power factors has route protection filter branch circuit LL1 (Figure 21) and full-wave rectifier branch circuit BR (Figure 22) and capacitor C 1 and C2; Branch circuit PFB (Figure 24), resistance R 2, rectifier CP (Figure 26), magnetic element PFT1 (Figure 18), the spacing SN of overheat protector OTP (Figure 28) (Figure 30) gate pole buffering AMP (Figure 29), switching transistor Q1, backhaul diode D4, support capacitor C 17 and C16, ooze out (bleed) resistance R 17 and Voltage Feedback branch circuit FBA (Figure 40 A); The effective second preconditioning buck stages, has branch circuit PWFM (Figure 33), current sense resistor R26, rectifier CPA (Figure 27), magnetic element BL1 (Figure 18 B), overvoltage protection OVP (Figure 42), IPFFB (Figure 40), gate pole buffering AMP3 (Figure 29), switching transistor Q2, backhaul diode D70, storage capacitance C4 and Voltage Feedback branch circuit IFB (Figure 40 B); With the effective the 3rd recommend isolation level, has branch circuit CPA (Figure 27), two-phase generator PPG (Figure 43), gate pole buffering AMP1 (Figure 29) and AMP2 (Figure 29), switching transistor Q6, and Q9, spacing SNA (Figure 31) and SNB (Figure 32), magnetic element PPT1 (Figure 19) and rectifier OUTA (Figure 25).

Fig. 3,3a	Table
Fig. 3,3a	Table	Element	Value/parts number
????C1	????.01uf	Element	Value/parts number
????C1	????.01uf	????C2	????1.8uf
????R2	100k ohm	????C2	????1.8uf
????R2	100k ohm	????D4	The STA1206 diode
????R17	375k ohm	????D4	The STA1206 diode
????R17	375k ohm	????Q1	????IRFP460
????C16	????100uf	????Q1	????IRFP460
????C16	????100uf	????C17	????100uf
????R26	.05 ohm	????C17	????100uf
????R26	.05 ohm	????D70	????STA1206?DI
????Q2	????IRFP460	????D70	????STA1206?DI
????Q2	????IRFP460	????C4	????10uf
????Q6	????FS14Sm-18A	????C4	????10uf
????Q6	????FS14Sm-18A	????Q9	????FS14Sm-18A

The AC circuit is connected to branch circuit LLA (Figure 21), between pin LL1 and LL2.Be connected to node LL0 AC/.The AC circuit of filtering and voltage limit appears at node/pin LL5 of branch circuit LLA and is connected to the Node B R1 of bridge rectifier branch circuit BR.The neutrality of the AC of filtering and voltage limit/AC return branch appears at the pin LL6 of branch circuit LL, and it is connected to the input pin BR2 of BR.Circuit is by full-wave rectification and be converted into positive haversine, appears at the Node B R+ of branch circuit BR.Starting resistance R2 connects BR+ to branch circuit CP pin CP+.Node CP+ is connected to pin PFA+ and the excess temperature switch branch circuit OTP pin GAP of control element branch circuit PFB.Resistance R 2 provides starting power to arrive control element, is output in full up to adjuster CP.Node S1H is connected to pin 31 (Fig. 3) from PFT1, is connected to the pin CT1A of branch circuit CP and the pin PFVC of branch circuit PFB then.When the voltage of S1H is zero with respect to BR-, detected iron core biasing zero crossing.The zero crossing of iron core is used to reset PFC and new cycle of beginning.The cathode node BR+ of the DC side of bridge is connected to BR-by capacitor C 2.Select C2 to be used for various circuits and loading condition, improved power factor so that switching current is disconnected from circuit.Branch circuit BR pin BR+ is connected to the pin SNL1 of spacing branch circuit SN, and branch circuit PFB pin BR+ and pin BR+ (Fig. 3 A) are connected to the pin P1B and the branch circuit OVP pin BR+ of NSME branch circuit PFT1 primary side then.The return line of the AC power of rectification is connected to following pin: the BR-of branch circuit BR, branch circuit PFT1 pin S1CT, PFC branch circuit PFB pin BR-, branch circuit FBA pin BR-, capacitor C 2, branch circuit CP pin CT0, branch circuit IPFFB pin FBE and be connected to ground node LL0 by EMI filter capacitor C1.Node B R-proceeds to Fig. 3 A, is connected to R26, electric capacity [C16 ‖ C17 ‖ R17], branch circuit OVP pin BR-, branch circuit PWFM pin PWFM0, branch circuit AMP3 pin GA0, switch Q2 source electrode.Drift ground node PF-is connected to magnetic element branch circuit PFT1 pin S2CT, rectifier branch circuit CPA pin CT20, generator branch circuit PPG (Figure 43) pin PPG0, branch circuit AMP1 pin GA0, branch circuit AMP2 pin GA0, capacitor C 4, magnetic element BL1 pin, transistor Q6 source electrode, transistor Q9 source electrode, branch circuit SNA pin SNA2, branch circuit SNB pin SNB2, pin PF-(Fig. 3) is connected to branch circuit IPFFB pin PF-then.The leakage level of output switch Q1 is connected to diode D4 anode, and branch circuit SN pin SNL2 is connected to the pin 34 of Fig. 3 A then, is connected to branch circuit PFT1 pin P1A then.Spacing SN has reduced the high voltage stress to Q1, and D4 begins conducting up to the backhaul diode.Other rectification efficiency and protection have been realized by increase branch circuit DSN (Figure 30 A) at backhaul diode D4 two ends.The output voltage that boosts of the feedback compensation of the AC-DC transducer-level of correcting power factors appears between node PF+ and the PF-.385 volts of output node PF+ that boost that regulate are connected to following node; Branch circuit SN pin SNOUT, diode D4 negative electrode, branch circuit IPFFB (Figure 40) pin PF+, branch circuit FBA pin PF+ is connected to the pin PF+ of Fig. 3 A then, electric capacity [C16 ‖ C17 ‖ R17], magnetic element branch circuit PTT1 (Figure 19) pin P2CT, spacing branch circuit SNA (Figure 31) pin SNA3 and spacing SNB (Figure 32) pin SNB3, branch circuit OVP pin PF+, capacitor C 4 and diode D70 negative electrode.The magnetic element winding node S1H of branch circuit PFT1 is connected to the pin 31 of Fig. 3, is connected to the pin PFVC of branch circuit CP pin CT1A and branch circuit PFB then.The magnetic element winding node S1L of branch circuit PFT1 is connected to the pin 33 of Fig. 3, is connected to branch circuit CP pin CT2A then.The magnetic element winding node S2H of branch circuit PFT1 is connected to CPA pin CT1B.The magnetic element winding node S2L of branch circuit PFT1 is connected to CP pin CT2B.Branch circuit PFB uses the feedback from the phase place of AC circuit, the Q1 switching current, and the magnetic bias first order and output voltage feedback produce command pulse at pin pfc LK.The pin pfc LK of branch circuit PFB (Figure 24) is connected to the input of the buffering AMP amplifier pin GA1 of branch circuit AMP1.The anti-gate-drive output pin of the High speed and low resistance of the buffering of branch circuit AMP GA2 is connected to the gate pole of switch FETQ1.The buffering that is provided by AMP has shortened switch Q1 " ON " and " OFF " time, has significantly reduced switching loss (seeing Figure 13 and 14).The source electrode of Q1 is connected to branch circuit AMP pin GA0, and the pin 35 of Fig. 3 A is connected to current sense resistor R26 then, and it is connected to return node BR-.Voltage on R26 is fed back to PFB pin PFSC.By reducing pulsewidth in response to low circuit or high capacity to the current failure induction, this signal is used to protect this switch.The return line of branch circuit FBA pin BR-is connected to the pin BR-of Node B R-and branch circuit PFB.This feedback is non-isolation; Select network values to make the first order 385 volts of outputs be arranged at PF+.Branch circuit feedback network FBA (Figure 40 A) pin PF1 is connected to branch circuit PFB pin PF1.Controller PFB modulation PFCLK signal to be maintaining the constant in fact 385V voltage of PF+, and irrelevant with circuit and loading condition.If in branch circuit FBA unit failure is arranged, then PBF can order converter to arrive very high voltage.Branch circuit OVP monitors that the first order boosts, if it surpass 405 volts then OVP the fuse F1 among the branch circuit LLA is opened the output of clamper branch circuit BR.Another overvoltage network OVP1 (Figure 42 A) can replace OVP, 8 volts of power controlling of clamper, and the boost action of the device that stops transformation, and do not open fuse.Converter output in the sampling of the node of branch circuit FBA pin PF1 is connected to branch circuit PFB pin PF1.Haversine and inner multiplier at BR+ are used by PFB, so that produce the variable-width control impuls at pin pfc LK.The high frequency modulated of switch Q1 makes load/converter resistive to the performance of AC circuit.Overheat protector branch circuit OTP pin TS+ is connected to branch circuit AMP pin GA+.Thermal switch THS1 is connected to Q1.If Q1 arrive about 105 ℃ then THS1 open, power transfer to branch circuit AMP, is turn-offed the first order safely.Reduce 20-30 ℃ in temperature, close after the THS, operate as normal is recovered.The second level is constructed to buck stages.It accepts 385 volts of outputs of the first order.By adopting the second drift reference node PF-energy storage elements capacitor C 4, can regulate with the loss of minimum to the voltage of final push-pull cascade.Power is connected to branch circuit PWFM (Figure 33) pin PWM+ and AMP3 pin GA+ then from the pin 30 that branch circuit CP pin CP18V+ is connected to Fig. 3 A.Feedback current is connected to branch circuit IFB pin FBC and branch circuit PWFM pin PF1 then from the pin 36 that branch circuit IPFFB pin FBC is connected to Fig. 3 A.When having only partial output greater than 200 volts, branch circuit IPFFB is just from this node shunt current.When converter reached its desirable output voltage, IFB was from PWFM pin PF1 shunt current, and indication PWFM is to reduce in pin PWMCLK pulsewidth.Branch circuit AMP3 input pin is connected to branch circuit PWFM pin PWMCLK.The output of AMP3 buffering pin GA2 is connected to the gate pole of switch Q2.The leakage level of Q2 is connected to anode and the unsaturation magnet branch circuit BL1 pin P2B (Figure 18 B) of D70.Connect switch Q2 charging C4, the while is stored energy in magnetic element BL1 also.Release-push Q2 makes and to be stored in energy among the magnetic element BL1 by the backhaul diode D70 C4 that charges.Bigger pulsewidth charging C4 arrives bigger voltage, thereby stops part first order voltage to final push-pull cascade effectively.This action provides the voltage that is conditioned for final transducer-level.The 3rd and last recommending (transformer) transducer-level provide electric current to isolate, filtering and usually the inner high voltage bus of conversion to the output voltage of lower adjusting.Effectively push-pull cascade produces the ac magnetization electric current with maximum load-iron core mass ratio in NSME.The non-overlapped two-phase generator of constant frequency branch circuit PPG (Figure 43) produces the driving of push-pull output stage.The first phase output pin PH1 is connected to branch circuit AMP1 pin GA1, and output pin PH2 is connected to branch circuit AMP2 pin GA1.The output of amplifier buffer branch circuit AMP1 pin GAP2 is connected to the gate pole of recommending output switch Q6.The output of amplifier buffer branch circuit AMP2 pin GAP2 is connected to the gate pole of recommending output switch Q9.The buffering that is provided by AMP1 and AMP2 has shortened switch Q1ON and OFF time, has significantly reduced switching loss.18 volts of power that (seeing Figure 13 and 14) regulated are connected to amplifier buffer branch circuit AMP1 pin GA+ from branch circuit CPA pin CP18+, amplifier buffer branch circuit AMP2 pin GA+ and branch circuit PPG pin PPG+.The leakage level of transistor Q6 is connected to spacing network branches circuit SNB pin SNB1 and the tapped primary coil magnetic element of to unsaturation branch circuit PPT1 pin P2H.The leakage level of transistor Q9 is connected to spacing network branches circuit SNA (Figure 31) pin SNA1 and branch circuit PPT1 pin P2L.Return node PF-connects the source electrode of transistor Q6 to spacing network branches circuit SNB pin SNB3, transistor Q9 source electrode, branch circuit SNA pin SNA3 and to return node GND2.The output of NSME branch circuit PPT1 pin SH is connected to the pin C7B of rectifier branch circuit OUTA (Figure 25), and pin SL is connected to C8B.The centre tap pin SCT of PPT1 is that output is returned or negative pole node OUT-, and it is connected to branch circuit pin OUT-and branch circuit IFB pin OUT-and RLOAD.Positive source output is connected to RLOAD and branch circuit IFB pin OUT+ from branch circuit OUTA pin OUT+.Element LL1, BR, PFA, AMP, Q1, IPFFB, IFB and PFT1 provide the AC-DC conversion of correcting power factors and DC output to regulate.The high-tension output of the adjusting of this converter is used to provide power to the push-pull cascade PPG of effective fixed frequency, AMP1, AMP2, Q6, Q9, PPT1 and OUTA.Magnetic element branch circuit PPT1 provides electric current to isolate and in the voltage toning of the minimum of second coil side, thereby minimizes the filtering requirements of rectifier branch circuit OUTA.The high-speed feedback that provides branch circuit IFB arrives the AC-DC converter, and the speed of voltage-boosting stage provides precise output voltage to regulate and initiatively (active) fluctuation suppresses.If unexpected circuit or load variations take place, branch circuit IPFFB compensates for inner boosting.This system is controlled in centre (low current) level of converter and by use unsaturation magnet, buffer switch and rectification stop in every grade, has reduced loss by concentrating output.In conjunction with improvement brought higher system effectiveness, higher power density, lower working temperature has improved thermal endurance, thereby has reduced or removed the output of each unit for the needs that force air cooling.The unsaturation magnetic characteristic is more insensitive (seeing Figure 17) to temperature, thereby allows converter to be operated in bigger temperature range.In practice, the working temperature of Kool Mu NSME is limited in 200 ℃ by lead/core insulation; The unsaturation magnetic material still can be worked near its Curie temperature of 500 ℃.This structure provides the input transient protective of correcting power factors, circuit-load fast and oscillation compensation, and excellent output is regulated, and output is isolated and quiet effectively work at high temperature.

Fig. 4 is the schematic diagram of the single-stage AC-DC converter branch circuit ACDCPF of correcting power factors.The present invention includes route protection filter branch circuit LL (Figure 20) and full-wave rectifier branch circuit BR (Figure 22).The voltage-boosting stage of the adjusting of correcting power factors has branch circuit PFB (Figure 24), spacing branch circuit SN (Figure 30), magnetic element branch circuit PFT1A (Figure 18 A), branch circuit CP (Figure 26), buffering branch circuit AMP (Figure 29), excess temperature branch circuit OTP (Figure 28) and Voltage Feedback branch circuit FBA (Figure 40 A).Starting resistance R2, filter capacitor C1, PFC capacitor C 2, backhaul diode D4, switching transistor Q1 supports capacitor C 17 and C16 and resistance R 17.

Fig. 4	Table
Fig. 4	Table	Element	Value/parts number
????C1	????.01uf	Element	Value/parts number
????C1	????.01uf	????C2	????1.8uf
????R2	100k ohm	????C2	????1.8uf
????R2	100k ohm	????R26	0.05 ohm
????Q1	????IRFP?460	????R26	0.05 ohm
????Q1	????IRFP?460	????D4	????STA1206?DI
????C17	????100uf	????D4	????STA1206?DI
????C17	????100uf	????C16	????100uf
????R17	375k ohm	????C16	????100uf

The AC circuit is connected to branch circuit LL (Figure 20), between pin LL1 and LL2.Be connected to node LL0 AC/.AC circuit filtering and voltage limit appears at node/pin LL5 of branch circuit LL1 and is connected to the Node B R1 of bridge rectifier branch circuit BR (Figure 22).Filtering and neutrality/AC return branch of AC voltage limit appear at the pin LL6 of branch circuit LL, and it is connected to the input pin BR2 of BR.Circuit is by full-wave rectification and be converted into positive haversine, appears at the Node B R+ of branch circuit BR (Figure 22).Starting resistance R2 connects BR+ to branch circuit CP pin CP+.Node CP+ is connected to pin PFA+ and excess temperature switch branch circuit OTP (Figure 28) the pin GAP of power factor controller branch circuit PFA (Figure 24).Resistance R 2 provides starting power to arrive, and control element is output in full up to rectifier and adjuster CP.Node S1H is connected to the node PFVC of branch circuit PFB from PFT1A.When the voltage of S1H is zero, detected iron core biasing zero crossing.The zero crossing of iron core is used to reset PFC and new cycle of beginning.The cathode node BR+ of the DC side of bridge is connected to BR-by capacitor C 2.Select C2 to be used for various circuits and loading condition, improved power factor so that switching current is disconnected from circuit.The primary side pin P1B of NSME branch circuit PFT1A (Figure 18 A) is connected to the pin SNL1 of spacing branch circuit SN (Figure 30), branch circuit PFB pin BR+ and be connected to Node B R+.The return line BR-of the AC power of rectification is connected to following pin: the BR-of branch circuit BR, branch circuit PFB pin BR-, branch circuit AMP pin GA0, detect resistance R 26, electric capacity [C16 ‖ C17 ‖ resistance R 17], capacitor C 2, branch circuit CP pin CT0, branch circuit PFT1A pin S1CT and be connected to ground node LL0 by EMI filter capacitor C1.The leakage level of output switch Q1 is connected to diode D4 anode, branch circuit PFT1A pin P1A and spacing branch circuit SN pin SNL2.Other rectification efficiency and protection have been realized by increasing the branch circuit DSN (Figure 30 A) in parallel with backhaul diode D4.Branch circuit provides the high voltage stress that has reduced to Q1, and D4 begins conducting up to the backhaul diode.The circuit coupling of AC-DC transducer-level (Fig. 1), the output voltage of regulating that boosts of correcting power factors appears at node PF+.The output PF+ that boosts that regulates is connected to following node: branch circuit SN pin SNOUT, diode D4 negative electrode, electric capacity [C16 ‖ C17 ‖ R17] and stop DSN (Figure 30 A) pin SNOUT.The magnetic element winding node S1H of branch circuit PFT1A is connected to the pin PFVC of CP pin CT1A and branch circuit PFB.The magnetic element winding node S1L of branch circuit PFT1A is connected to CP pin CT2A.Branch circuit PFB uses the phase place of AC circuit and load voltage to produce command pulse PFCLK.The pin pfc LK of branch circuit PFB (Figure 24) is connected to the input of the buffer amplifier pin GA1 of branch circuit AMP1 (Figure 29).The high speed gate-drive output pin GA2 of the buffering of branch circuit AMP is connected to the gate pole of switch FETQ1.The buffering that is provided by AMP has shortened switch Q1ON and OFF time, has significantly reduced switching loss.The source electrode of Q1 is connected to current sense resistor R26, and the pin PFSC of branch circuit PFB is connected to return node BR-then.Voltage at the R26 two ends is fed back to PFB pin PFSC.This signal is used to protect this switch when overcurrent fault.Thermal switch THS1 is connected to Q1.If Q1 arrives about 105 ℃, then THS1 opens, and power transfer to branch circuit AMP, is turn-offed the first order safely.After THS1 is closed in 20-30 ℃ of switch temperature reduction, recover operate as normal.Branch circuit feedback network FBA (Figure 40 A) pin PF1 is connected to branch circuit PFB pin PF1.Converter output (tie point of [C17 ‖ C16] and D4) at node PF+ is connected to branch circuit FBA pin PF+.The return line of branch circuit FBA pin BR-is connected to the pin BR-of branch circuit PFB.This feedback is non-isolation; Select network values to make the 385 volt outputs constant in fact with respect to BR-are arranged at PF+.The high voltage haversine is connected to branch circuit PFB pin BR+ from rectifier part BR pin BR+.Haversine and inner multiplier are used by PFB, make converter ACDCPF reveal resistive for the AC circuit table.Branch circuit LL1, BR, PFB, AMP, Q1, OTP, FBA, IFB and PFT1A carry out the AC-DC conversion of correcting power factors.The high-tension output of the adjusting of this converter can be used to provide power to the one or more external transducer that is connected to PF+ and BR-node.NSME branch circuit PPT1A provides effective boost function with high power levels and very little form factor.Branch circuit FBA provides high-speed feedback to arrive converter, and the speed of voltage-boosting stage provides precise output voltage to regulate and fluctuation initiatively suppresses.This structure provides the input transient protective of correcting power factors, fast circuit-load response, excellent adjusting and at high temperature quiet effectively work.

Fig. 4 A is the schematic diagram of converter with correcting power factors of automatic load calibration (leveling) branch circuit ACDCPF1.The present invention includes line filter branch circuit LF (Figure 20 A), start branch circuit FS1 (Figure 45) fast, transient state diode D460, D461, and D462 (Figure 46) and pour in (inrush) limiter branch circuit SS1 (Figure 44).The voltage-boosting stage of the adjusting of correcting power factors has branch circuit PFB (Figure 24), spacing branch circuit SNBB (Figure 30 B), magnetic element branch circuit PFT1A (Figure 18 A), branch circuit CP1 (Figure 26 A), buffering branch circuit AMP (Figure 29), excess temperature branch circuit OTP (Figure 28), overvoltage branch circuit FB2 (Figure 41 A) and Voltage Feedback branch circuit FBD (Figure 40 D).Automatic load-calibrating resistance R345, filter capacitor C1, PFC capacitor C 2, backhaul diode D4, switching transistor Q1 supports capacitor C 442 and C417.

Fig. 4 A	Table
Fig. 4 A	Table	Element	Value/parts number
????C1	????.01uf	Element	Value/parts number

????C2	????1.8uf
????C2	????1.8uf	????R26	0.05 ohm
????Q1	????ATP5014B2LC	????R26	0.05 ohm
????Q1	????ATP5014B2LC	????D460	????STA1206?DI
????C442	????330?uf	????D460	????STA1206?DI
????C442	????330?uf	????C417	????0.58?uf
????R345	1MEG ohm	????C417	????0.58?uf

The AC circuit is connected between branch circuit LF (Figure 20 A) node LL1 and the LL2.Be connected to node LL0 AC/.AC circuit filtering and rectification appears at the pin BR+ of branch circuit LF, and it is connected to the anode of transient state diode D460-462.The negative electrode of diode D460-462 is connected to node PF+ and primary storage capacitor C 442.Circuit is converted to positive haversine by full-wave rectification, appear at the Node B of branch circuit LF (Figure 20 A)+.The Node B of filter branch circuit LF+be connected to the input pin BR2 of PFB (Figure 24), the positive pole of C2, the pin PB1 of PFT1A, the pin B+ of SS1.Select capacitor C 2 to be suitable for various circuits and loading condition, so that, improved power factor from circuit cut-off switch electric current.Start branch circuit FS1 node TP17 fast and be connected to branch circuit CP1 pin TP17.The node VCC of CP1 is connected to the pin PFA+ of power factor controller branch circuit PFA (Figure 24), and automatic load calibrating resistance R345 is connected to the pin PF1 of PFB and the PF1 of FBD.The VCC of FS1 is connected to excess temperature switch branch circuit OTP (Figure 28) pin GAP.Starting FS1 fast provides starting power, is full power up to converter.Under the situation of the excessive loss of boosting, it also provides power controlling.Node S1H is connected to the node PFVC of branch circuit PFB from PFT1A.When the voltage of S1H is zero, detected iron core biasing zero crossing.The zero crossing of iron core is used to reset U1B and new cycle of beginning.The primary side pin P1B of NSME branch circuit PFT1A (Figure 18 A) is connected to the pin SNL2 of spacing branch circuit SNBB (Figure 30 B), branch circuit PFB pin BR+ and be connected to Node B+.The return line BR-of the AC power of rectification is connected to following pin: the BR-of branch circuit LF, branch circuit PFB pin BR-, branch circuit AMP pin GA0, branch circuit SS1 pin BR-, detect resistance R 26, branch circuit SS1 pin BR-, capacitor C 417 and C2, branch circuit CP1 pin CT0, branch circuit FB2 pin BR-, branch circuit FBD pin BR-, branch circuit FS1 pin BR-, branch circuit PFT1A pin S1CT and be connected to ground node LL0 by EMI filter capacitor C1.The leakage level of output switch Q1 is connected to diode D4 anode, branch circuit PFT1A pin P1A and spacing branch circuit SNBB pin SNL2.Realized switch protection by increasing the branch circuit SNBB (Figure 30 B) in parallel with backhaul diode D4.Branch circuit SNBB provides the high voltage stress that has reduced to Q1, and D4 begins conducting up to the backhaul diode.The output voltage of the adjusting of converter appears at node PF+.The output PF+ that boosts that regulates is connected to following node: branch circuit SNBB pin SNOUT, diode D4 negative electrode, capacitor C 417, branch circuit FS1 pin PF+, branch circuit SS1 pin PF+ and diode D460-462 negative electrode.The magnetic element winding node S1H of branch circuit PFT1A is connected to the pin PFVC of CP1 pin CT1A and branch circuit PFB.The magnetic element winding node S1L of branch circuit PFT1A is connected to CP1 pin CT2A.Branch circuit PFB uses the phase place of AC circuit and load voltage to produce command pulse PFCLK.The pin pfc LK of branch circuit PFB (Figure 24) is connected to the input of the buffer amplifier pin GA1 of branch circuit AMP1 (Figure 29).The high speed gate-drive output pin GA2 of the buffering of branch circuit AMP is connected to the gate pole of main switch Q1.The buffering that is provided by AMP has shortened switch Q1 " ON " and " OFF " time, has significantly reduced switching loss.The source electrode of Q1 is connected to current sense resistor R26, and the pin PFSC of branch circuit PFB is connected to return node BR-then.Voltage at the R26 two ends is fed back to PFB pin PFSC.This signal is used to protect this switch when overcurrent fault.Thermal switch THS1 is thermally connected to Q1.If Q1 arrives about 105 ℃, then THS1 opens, and power transfer to branch circuit AMP, is turn-offed the work of boosting safely.After THS1 is closed in 20-30 ℃ of switch temperature reduction, recover operate as normal.Branch circuit feedback network FBD (Figure 40 D) pin PF1 is connected to branch circuit PFB pin PF1.Branch circuit feedback network FB2 (Figure 41 A) pin PF2 is connected to branch circuit PFB pin PF2.This feedback is non-isolation; Select network values to make the 385 volt outputs constant in fact with respect to BR-are arranged at PF+.Height-voltage haversine is connected to branch circuit PFB pin BR+ from rectifier part pin B+.Haversine and inner multiplier are used by PFB, make converter ACDCPF reveal resistive for the AC circuit table.The high-tension output of the adjusting of this converter can be used to and one or more external transducer uses in parallel.The unique property of converter ACDCPF1 is that automatic load is shared characteristic.As signal VCC during as the function of load, shown in Figure 26 B, being connected load calibrating resistance between node VCC and the PF1 increases along with load/boost and turns down output voltage.This unique function makes that the unit can parallel operation, and does not have common major-minor to connect.By this way, thus underloaded converter will increase its output voltage accepts more load.Equally, heavy duty converter will reduce voltage, automatically load be unloaded the converter to parallel connection.By this way, any amount of converter can be connected in parallel, to be used for high power or superfluous application scenario.In the master/auxiliary structure of prior art, the damaged of master unit is catastrophic.In the present invention, the fault of a unit or remove other load is born in the unit that makes other.NSME branch circuit PPT1A1 provides effective boost function with high power levels and very little form factor.Pouring in limiter branch circuit SS1 allows to carry out " heat exchange " (hotswapping) with the system disturbance of minimum.Unique magnet characteristic allows the impossible temperature range full power operation of converter at common technology; provide High Power Factor, transient protective, low inrush current; excellent adjusting is from the automatic recovery of malfunction and quiet effectively work under extreme temperature.

Fig. 5 is the figure of the exemplary currents of comparison in saturated and non-saturating magnetic elements.Because inductance does not significantly change when high temperature and big electric current in NSME, owing to the big current spike that inductance general in saturation magnets reduces to cause is not fast seen.The result is, in NSME, and destructive current value, undue air gap leakage (gap leakage), magnetization loss and magnetic element heating are avoided.

Fig. 6 is the schematic diagram of low side (low side) switch step-down (buck) the converter branch circuit NILBK of non-isolation.Branch circuit NILBK comprises resistance R 20, diode D6, capacitor C 6, FET transistor Q111, branch circuit CP (Figure 26), branch circuit PFT1A (Figure 18 A), branch circuit IFB (Figure 40 B), branch circuit AMP (Figure 29) and branch circuit PWFM (Figure 33).

Fig. 6	Table
Fig. 6	Table	Element	Value/parts number
????R20	100k ohm	Element	Value/parts number
????R20	100k ohm	????R20	????STA1206?DI
????Q111	????IRFP460	????R20	????STA1206?DI
????Q111	????IRFP460	????C6	????10uf

External power source VBAT is connected to pin DCIN+ and DCIN-.Be connected to branch circuit CP pin CP+ from DCIN+ by resistance R 20, branch circuit AMP pin GA+ and branch circuit PWFM pin PWFM+.Before adjuster branch circuit CP arrived its 18 volts of outputs in full, resistance R 20 provided starting power to arrive converter.The VBAT negative pole is connected to pin DCIN-, is connected to branch circuit PWFM pin PWFM0, branch circuit AMP pin GA0, Q111 source electrode, branch circuit IFB pin FBE, branch circuit CP pin CT0 and branch circuit PFT1 pin S1CT.The magnetic element winding node S1H of branch circuit PFT1A is connected to CP pin CT1A.The magnetic element winding node S1CT of branch circuit PFT1 is connected to CP pin CT0.The magnetic element winding node S1H of branch circuit PFT1A is connected to CP pin CT2A.18 volts of voltages regulating are connected to R20 from branch circuit CP+, branch circuit AMP pin GA+ and branch circuit PWFM pin PWFM+.Branch circuit PWFM is designed to variable impulse width work.PWFM is constructed to maximum pulse width 90-95%, does not have feedback current from branch circuit IFB pin FBC.Increase the output voltage that feedback current has reduced pulsewidth and converter NILBK.Branch circuit PWFM clock/PWM output pin CLK is connected to the input pin GA1 of buffering branch circuit AMP.The output of branch circuit AMP pin GA2 is connected to the gate pole of Q111.Input node DCIN+ is connected to the negative electrode of backhaul diode D6, branch circuit IFB pin OUT+, resistance R LOAD, capacitor C 6 and pin B+.The leakage level of Q111 is connected to the anode of branch circuit PFT1 pin P1B and D6.The pin P1A of branch circuit PFT1A is connected to capacitor C 6, RLOAD, and branch circuit IFB pin OUT-and Node B-.If branch circuit PWFM pin CLK is high, then cushion the gate pole of AMP output pin GA2 charging transistor switch Q111.Switch Q111 passes through NSME PFT1A conducting charging capacitor C10, stored energy in PFT1A from power supply VBAT.Feedback output pin FBC is connected to branch circuit PWFM pulse-width regulated pin PW1 from branch circuit IFB.Branch circuit IFB reduces electric current from PW1, and order PWFM is to reduce pulsewidth or the ON time of signal CLK.After the pulsewidth that branch circuit PWFM arrival is ordered, it is low that PWFM makes output pin CLK, and " ending " Q111 stops electric current and enters PFT1A.The energy that is not sent to adjuster branch circuit CP load is discharged into present forward biased diode D6, charging capacitor C6 from NSME PFT1A.By " conducting " time of modulation switch Q111, the converter step-down voltage is conditioned.The voltage that is conditioned be added in Node B-and B+ between.Branch circuit IFB provides the feedback voltage of isolation to branch circuit PWFM.When branch circuit IFB detected converter output (Node B+and B-between) at designed voltage, the electric current of REF was reduced from PM1.The current order PWFM that descends from PM1 shortens pulsewidth, thereby reduces the converter output voltage.If the feedback signal order PWFM of IFB is to minimum output, the gate-drive of switch Q111 is removed, and stops all step-down activities, and capacitor C 6 is discharged by RLOAD.Input current from VBAT is sinusoidal wave, makes converter very quiet.In addition, switch Q111 is not subjected to the influence of big backswing voltage.Less stress is applied to switch, thereby has increased MTBF.In the topological structure of this converter, branch circuit NILBK has utilized the desired characteristics of NSME.Be adjusted in NSME 100 (Figure 18 A) primary inductance and component values among the branch circuit IFB, determined output buck voltage.

Fig. 8 is the schematic diagram of the single-stage converter branch circuit TCTP of tank circuit connection.Branch circuit TCTP comprises resistance R 20 and RLOAD, capacitor C 10, Darlington transistor Q10 and Q20, branch circuit CP (Figure 26), branch circuit PFT1 (Figure 18), branch circuit OUTB (Figure 25 A), branch circuit IFB (Figure 40 B) and branch circuit PWFM (Figure 33).

Fig. 8	Table
Fig. 8	Table	Element	Value/parts number
????R20	5k ohm	Element	Value/parts number
????R20	5k ohm	????Q10	????TST541
????Q20	????IRFP460	????Q10	????TST541
????Q20	????IRFP460	????C10	????1.8uf

External power source VBAT is connected to pin DCIN+ and DCIN-.Be connected to the Q10 collector electrode from DCIN+ and be connected to branch circuit CP pin CP+ and branch circuit PWFM pin PWFM+ by resistance R 20 then.Before adjuster branch circuit CP arrived its 18 volts of outputs in full, resistance R 20 provided starting power to arrive converter.The VBAT negative pole is connected to pin DCIN-ground/return node GND.Node GND is connected to branch circuit PWFM0 pin PWFM0, Q20 collector electrode, C10, branch circuit CP pin CT0 and branch circuit PFT1 pin S1CT.The magnetic element winding node S1H of branch circuit PFT1 is connected to CP CT1A.The magnetic element winding node S1L of branch circuit PFT1 is connected to CP CT2A.The magnetic element winding node S1CT of branch circuit PFT1 is connected to CP pin CT0.The magnetic element winding node S2H of branch circuit PFT1 is connected to CP pin CT2A.18 volts of voltages regulating are connected to R20 and branch circuit PWFM pin PWFM+ from branch circuit CP+.Branch circuit PWFM is designed to the variable frequency generator of constant 50% conduction ratio.Branch circuit PWFM clock output pin CLK is connected to the base stage of Q10 and Q20.The emitter of Q10 and Q20 is connected to branch circuit PFT1 pin P1B.This has formed emitter and has followed structure.The pin P1A of branch circuit PFT1 is connected to node GND by tank capacitance C10.If PWFM CLK pin be high, then the transistor Q10 of forward bias provides electric current to the tank circuit from BAT1, by NSMEPFT1 charging capacitor C10 and transmission energy to PFT1.Branch circuit PWFM switch CLK is for the low Q10 that then turn-offs, by the electric current that enters PFT1.The energy that is not sent to load is discharged into the PNP transistor Q20 of present forward bias from NSME PFT1, return capacitor C 10.Thereby any energy that is not used by the secondary coil lateral load is sent to the primary side tank circuit, so that use at next cycle.When switch occurred in resonance frequency, big circulating current produced in the tank circuit.C10 also is charged and discharged to very large voltage.Oscillogram among Figure 35 is VBAT when equaling 18 volts, the virtual voltage on capacitor C 10.P-to-P voltage between NSME PFT1 node P1A and P1A is very large 229 volts.Big primary side voltage produces big biasing in NSME PFT1, so that gathered in the crops (flux harvested) and be sent to load or rectifier branch circuit OUTB by winding 102 and 103 (Figure 18) institute magnetic flux.The magnetic element winding node S2L of branch circuit PFT1 is connected to OUTB C8b.The magnetic element winding node S2H of branch circuit PFT1 is connected to the node OUT-of the C7B of branch circuit OUTB.Node OUT-is connected to RLOAD, pin B-and branch circuit IFB pin OUT-.The power of rectification is sent to the pin OUT+ of OUTB and is connected to RLOAD, pin B+ and branch circuit IFB pin OUT+.What branch circuit IFB provided isolation feeds back signal to branch circuit PWFM.The FREQUENCY CONTROL pin FM1 of branch circuit PWFM is connected to branch circuit IFB pin FBE.The reference pin REF of the inside of branch circuit PWFM is connected to branch circuit IFB pin FBC.PWFM is designed to work in the resonance frequency of the tank circuit.When branch circuit IFB detected converter output at designed voltage, electric current was injected into FM1 from REF.Injection current then orders PWFM to arrive more low frequency to FM1.Be operated in and reduced the energy that is added to the primary side tank circuit under the resonance, thereby reduce the converter output voltage.If to 0-Hz, then all primary side activities stop from the feedback signal order PWFM of IFB.Input current from VBAT is sinusoidal wave, makes converter very quiet.In addition, switch Q10 and Q20 never are subjected to the influence of big cyclical voltage (Figure 35).Less stress is applied to switch, thereby has increased MTBF.In the topological structure of this converter, branch circuit TCTP has utilized the desired characteristics of NSME.Regulate the second coil side number of turn, make TCTP can produce very large AC or DC output voltage and low voltage and high current output.

Fig. 9 is the schematic diagram of the low-end switch booster converter branch circuit NILSBST of non-isolation.Branch circuit NILSBST comprises resistance R 20 and RLOAD, diode D6, capacitor C 6, FET transistor Q111, branch circuit CP (Figure 26), branch circuit PFT1A (Figure 18 A), branch circuit FBI (Figure 41), branch circuit AMP (Figure 29) and branch circuit PWFM (Figure 33).

Fig. 9	Table
Fig. 9	Table	Element	Value/parts number
????R20	100k ohm	Element	Value/parts number
????R20	100k ohm	????Q111	????IRFP460
????D6	????STA1206?DI	????Q111	????IRFP460
????D6	????STA1206?DI	????C6	????200uf

External power source VBAT is connected to pin DCIN+ and DCIN-.Be connected to branch circuit CP pin CP+ from DCIN+ resistance R 20, branch circuit AMP pin GA+ and branch circuit PWFM pin PWFM+.Before adjuster branch circuit CP arrived its 18 volts of outputs in full, resistance R 20 provided starting power to arrive converter.The VBAT negative pole is connected to pin DCIN-and ground return node GND.Node GND is connected to branch circuit PWFM pin PWFM0, branch circuit AMP pin GA0, Q111 source electrode, branch circuit FBA pin BR-, branch circuit FBA pin FBA, branch circuit CP pin CT0, capacitor C 6, resistance R LOAD, transistor Q111 source electrode and branch circuit PFT1 pin S1CT.The magnetic element winding node S1H of branch circuit PFT1A is connected to CP pin CT1A.The magnetic element winding node S1CT of branch circuit PFT1 is connected to CP pin CT0.The magnetic element winding node S2H of branch circuit PFT1A is connected to CP pin CT2A.18 volts of voltages regulating are connected to R20 from branch circuit CP+, branch circuit AMP pin GA+ and branch circuit PWFM pin PWFM+.Branch circuit PWFM is designed to variable impulse width work.PWFM is constructed to maximum pulse width 90-95% (maximum booster voltage), does not have the feedback current from branch circuit FBI.Increase feedback current and reduced pulsewidth, reduced booster voltage and reduced from the output of converter NILSBST.Branch circuit PWFM clock/PWM output pin CLK is connected to the input pin GA1 of buffering branch circuit AMP.The output of branch circuit AMP pin GA2 is connected to the gate pole of Q111.Input node DCIN+ is connected to NSME PFT1A pin P1A.The leakage level of Q11 is connected to the anode of branch circuit PFT1A pin P1B and D6.The negative electrode of diode D6 is connected to branch circuit FBA pin PF+, resistance R LOAD, C6 and pin BK+.If branch circuit PWFM pin CLK is high, then cushion the gate pole of AMP output pin GA2 charging transistor switch Q111.Switch Q111 conducting, reversed biased diodes D6, capacitor C 10 stops to charge from power supply VBAT by NSME PFT1A.In the time of Q111 conducting, energy is stored among the NSME branch circuit PFT1A.The feedback output pin FBC of branch circuit FBI is connected to branch circuit PWFM pulse-width regulated pin PW1.Branch circuit FBI is from the PW1 transfer current, and order PWFM is to reduce pulsewidth or the ON time of signal CLK.After the pulsewidth that branch circuit PWFM arrival is ordered, it is low that PFFM makes CLK, and " ending " Q111 stops electric current and enters PFT1A.The energy that is not sent to adjuster branch circuit CP load is discharged into present forward biased diode D6, charging capacitor C6 from NSME PFT1A.By " conducting " time of modulation switch Q111, converter boost voltage is conditioned.The voltage that is conditioned be added in Node B-and B+ between.Branch circuit IFB provides feedback current to branch circuit PWFM.When branch circuit IFB detected converter output (Node B+and B-between) at designed voltage, electric current was shifted from PM1.The current order PWFM that descends from PM1 shortens pulsewidth, thereby reduces the converter output voltage.If the feedback signal order PWFM of IFB is to minimum output, the gate-drive of switch Q111 is removed, and stops all activities of boosting, and capacitor C 6 is charged to VBAT.Input current from VBAT is sinusoidal wave, makes converter very quiet.In addition, switch Q111 is not subjected to the influence of big backswing voltage.Less stress is applied to switch, thereby has increased MTBF.In the topological structure of this converter, branch circuit NILBK has utilized the desired characteristics of NSME.Be adjusted in NSME 100 (Figure 18 A) primary inductance and component values among the branch circuit IFB, determined the output booster voltage.

Figure 10 is the boost schematic diagram of push-pull converter BSTPP of control of DC-DC that two-stage is isolated.Branch circuit BSTPP comprises diode D14, capacitor C 14, FET transistor Q14, branch circuit REG (Figure 36), branch circuit BL1 (Figure 18 B), branch circuit IFB (Figure 40 B), branch circuit AMP (Figure 29), branch circuit DCAC1 and branch circuit PWFM (Figure 33).External power source VBAT is connected to pin DCIN+ and DCIN-.

Figure 10	Table
Figure 10	Table	Element	Value/parts number
????Q31	????IRFP460	Element	Value/parts number
????Q31	????IRFP460	????D14	????STA1206?DI
????C14	????10uf	????D14	????STA1206?DI

Pin DCIN+ is connected to branch circuit REG pin RIN+ and branch circuit BL1 pin P1A.Voltage regulator branch circuit output pin+18V is connected to branch circuit AMP pin GA+ and branch circuit PWFM pin PWFM+.Branch circuit REG provides the low-voltage power of adjusting to controller and main switch buffer.The VBAT negative pole is connected to pin DCIN-and ground return node GND.Node GND is connected to branch circuit PWFM pin PWFM0, branch circuit AMP pin GA0, Q14 source electrode, capacitor C 14, branch circuit IFB pin FBE, branch circuit REG pin REG0, branch circuit DCAC1 pin DC-.Branch circuit PWFM (Figure 33) is designed to variable impulse width work.Rated frequency is between 20-600Khz, and PWFM is constructed to maximum pulse width 90% (maximum booster voltage), does not have the feedback current from branch circuit FBI.Increase feedback current and reduced pulsewidth, reduced booster voltage and reduced from the output of converter BSTPP.Branch circuit PWFM clock/PWM output pin CLK is connected to the input pin GA1 of buffering branch circuit AMP (Figure 29).The output of switch acceleration (speed up) buffering branch circuit AMP pin GA2 is connected to the gate pole of Q14.Input node DCIN+ is connected to NSME BL1 pin P1A.The leakage level of Q14 is connected to the anode of branch circuit BL1 pin P1B and D14.The negative electrode of backhaul diode D14 is connected to branch circuit DCAC1 pin DC+ and C14.If branch circuit PWFM pin CLK is high, then cushion the gate pole of AMP output pin GA2 charging transistor switch Q14.Switch Q14 conducting, reversed biased diodes diode D14 electric capacity, C14 stop to charge from power supply VBAT by NSME BL1.In the time of Q14 conducting, energy is stored among the NSME branch circuit BL1.The feedback output pin FBC of branch circuit IFB is connected to branch circuit PWFM pulse-width regulated pin PW1.Branch circuit FBI is from the PW1 transfer current, and order PWFM is to reduce pulsewidth or the ON time of signal CLK.After the pulsewidth that branch circuit PWFM arrival is ordered, it is low that PFFM makes CLK, and " ending " Q14 stops electric current and enters BL1.Energy is discharged into present forward biased backhaul diode D14, charging capacitor C14 from NSME BL1.By " conducting " time of modulation switch Q14, converter boost voltage is conditioned.The voltage that is conditioned is added between the C14.Node DC+ and GND are provided to the constant frequency of isolation and recommend DC-AC converter branch circuit DCAC1 (Fig. 2).Branch circuit DCAC1 provides the booster voltage of adjusting to the effective conversion of being determined higher or lower voltage by magnetic element-ratio of winding.The centre tap of recommending the output magnet is connected to branch circuit OUTB pin OUT-, RLOAD, branch circuit IFB pin OUT-and pin OUT-, the return line of formation load and feedback network.The output of branch circuit DCAC1 pin ACH is connected to branch circuit OUTB pin C7b.The output of branch circuit DCAC1 pin ACL is connected to branch circuit OUTB pin C8b.Branch circuit OUTB provides the rectification of the AC power that is produced by branch circuit DCAC1.Because unsaturation magnet converter has low output pulsation, OUTB only needs minimum filtering.This has further reduced cost and has improved efficient, because the loss of filter part is minimized.Branch circuit IFB provides the feedback current of isolation to branch circuit PWFM.When branch circuit IFB detect converter output (between node OUT+ and the OUT-) greater than design/during the voltage of expectation, electric current is shifted from node PM1.The current order PWFM that descends from PM1 shortens pulsewidth, thereby has reduced the converter output voltage.If the feedback signal order PWFM of IFB is to minimum output, the gate-drive of switch Q14 is removed, and stops all activities of boosting, and capacitor C 14 is charged to VBAT.Because unsaturation can not make destructive noise current saturated, electric current " spike " common in the prior art disappears.The electric current of importing with charging C14 from VBAT is sinusoidal wave, makes converter very quiet.In addition, switch Q14 is not subjected to the influence of potential destructive current spike.Less stress is applied to switch, thereby has increased MTBF.Branch circuit BSTPP has utilized the desired characteristics of NSME.Regulate NSME BL1 (Figure 18 B) and set the last booster voltage amount of recommending isolation level that can be used for.Realized bigger efficient with higher voltage.Last output voltage is recently set by the feedback set point and the number of turn of recommending element PPT1 (Figure 19).

Figure 11 is the figure as the magnetic permeability of the function of temperature of prior art typical case magnetic element material.High-permeability material in Figure 11 shows almost 100% big magnetic permeability in 100 ℃ scope changes, and by contrast, the material in Figure 17 is only less than 5% variation.The material of prior art magnetic permeability at high temperature increases, and has increased magnetic flux density, causes the core sataration of firm power grade.The iron core of (seeing Figure 12) thereby prior art must move (derate) at least 100% by off-load, so that be operated in wideer temperature range.The present invention has utilized the desired characteristics of NSME, has cancelled the requirement to the operation of magnetic element off-load.Because magnetic element is at high temperature carried out better, and temperature is limited by the fusing wire insulation.

Figure 12 is the figure as the magnetic flux density of the function of temperature of prior art typical case magnetic element material.Peakflux density is along with the minimizing of temperature, is typical to the prior art material of saturation magnetization element.Thereby the common off-load operation at least 100% of prior art iron core, so that be operated in wideer temperature range, caused bigger more expensive design, and/or to cooling off the needs of iron core.

Figure 13 is the figure that the standard switch loss is shown.The shadow region represents that switch is in the time of resistive state.Amount of power loss when the shadow region is proportional to the work of each output switch.Total power loss is that each switch multiply by the long-pending of switching frequency.

Figure 14 is the figure that switching loss of the present invention is shown.The shadow region represents that switch is in the time of resistive state.The shadow region is less to be because buffer in Figure 29 and the effect of the spacing isolating diode D805 in Figure 30.Usually, NSME has wideer available band, can be by higher primary side voltage magnetization.For given power grade, higher operating voltage has proportional littler electric current, thereby has reduced loss pro rata.Switching loss more likes I ²The R loss.Most of switching losses occur in the process of " connection " and " shutoff " conversion; The lower switching frequency of disclosed NSME converter and faster the conversion time characteristic reduced total switching loss pro rata.In addition, the characteristic of NSME allows to be operated in extreme temperature conditions, has exceeded the holding capacity of standard prior art magnet and their geometrical condition.The combination of above-mentioned characteristic has been brought the converter (seeing Figure 15,16 and 17) that need seldom or not need to force air cooling.

Figure 15 is the magnetization curve figure of the NSME of Kool Mu material.The present invention has utilized the available saturation range of NSME.

Figure 15 A is the figure of the magnetization curve of H material.

Figure 16 is the figure of Kool Mu NSME for the loss of various magnetic flux densities and operating frequency.From these data as can be seen, for specific loss, have the magnetic flux density more much higher than prior art.

Figure 17 is the magnetic permeability of several Kool Mu materials and the figure of temperature relation.This tables of data is understood serviceability and the stability of magnetic characteristic for variations in temperature.

Figure 18 is that the boost schematic diagram of element PFT1 of non-saturation magnets is represented.Branch circuit PFT1 is included in the primary coil winding 100 on the NSME 101, and NSME 101 has two tapped windings 102 and 103.

Figure 18	Table
Figure 18	Table	Element	Value/parts number
????100	55 circle 203uh	Element	Value/parts number
????100	55 circle 203uh	????101	????2×77932-A7
????102	14 circles	????101	????2×77932-A7
????102	14 circles	????102	14 circles

Primary coil winding 100 has node P1B and P1A, to be connected to the external AC power supply.Secondary coil 102 windings have tapped node S1CT and node S1H and S1L, are connected respectively to top and following half one (halves).Secondary coil 103 windings have tapped node S2CT and node S2H and S2L, are connected respectively to top and half following one.102 and 103 all are connected to outside full-wave rectifier parts.Magnetic element 101 comprises unsaturation, the low magnetic permeability magnetic material.With scope is that prior art from 1500u to 5000u is compared, the about 26u of its magnetic permeability, and scope is that 1u is to 550u.When using NSME in booster converter, the backhaul management is important because the reverse recovery time of backhaul (output) diode magnetic element on the primary coil switch, produce high drain-source voltage.For given input magnetizing force, with respect to prior art, the amplitude in each cycle of the backhaul electric current of NSME is bigger.(see figure 5) for example, Kool Mu ferrite (torroids) (from the material of magnet) is suitable for this application scenario.Indicate this material and be not purpose in order to restriction.This material comprises by weight: 85% iron, 6% aluminium and 9% silicon.In addition, this magnetic element can be an air, (magnetic permeability=1); The molybdenum permalloy powder, (MPP) high magnetic flux MPP, powder has the space ferrite, is with around (tape wound) die-cut (cut) magnetic element, magnetic element lamination or unbodied.Do not resemble prior art, NSME is a heatproof, and owing to the condition of work in extreme heat, along with the past of time, the key parameter of magnetic permeability and saturability is unaffected in fact.Some materials, such as air, also to the time, temperature and condition show magnetic permeability or very little variation or the not variation of saturation grade.Prior art is used the high magnetic permeability saturated material greater than the 2000u magnetic permeability usually.These magnets are being operated in specified output or when the specified output, are showing magnetic permeability and the saturated variation do not expected, make to be operated in high power level and the temperature difficulty that becomes.See the Figure 11 that concerns of magnetic permeability and temperature.This weakness can be by costliness the bulk magnetic element use or overcome with a plurality of power sharing output currents and (to see figure b _SatThe Figure 12 that concerns with temperature).The present invention has utilized the desired characteristics of NSME.See the Figure 17 that concerns of magnetic permeability and temperature.The saturation magnetization element of prior art is usually operated at greater than the frequency of 500kHz to realize bigger power grade.The result is that when high frequency, the professional experiences the core loss (seeing Figure 12 A) that index increases.The NSME support performance has further reduced switching loss and magnetic element loss at lower frequency 20-600kHz, allows to be operated in higher temperature.See the relation (Figure 16) of loss density and magnetic flux density.Do not resemble prior art, the present invention uses has the voltage mode control that overcurrent turn-offs.Material selects also to be based on quality and efficient.By increasing the quality of magnetic element, more energy more effectively is coupled.Owing to reduced loss, loss roughly is I ²The R/ copper loss.Magnetic element is operated in the conduction ratio of 0%+ to 90%, and when being used to control the primary side push pull voltage, it has caused about 90% efficient.

Figure 18 A is that the schematic diagram of the PFT1A branch circuit of NSME is represented.Transformer PFT1A is included in the primary coil winding 100 on the NSME 101, and NSME 101 has tapped winding 102.

Figure 18 A	Table
Figure 18 A	Table	Element	Value/parts number
????100	55 circle 230uh	Element	Value/parts number
????100	55 circle 230uh	????101	????2×77932-A7
????102	14 circles	????101	????2×77932-A7

Primary coil winding 100 has node P1B and P1A, to be connected to the external AC power supply.Secondary coil 102 windings have tapped node S1CT and node S1H and S1L, are connected respectively to top and half following one.Winding 102 is connected to outside full-wave rectifier parts usually.Magnetic element 101 comprises unsaturation low magnetic permeability magnetic material.With scope is that prior art from 1500u to 5000u is compared, the about 26u of its magnetic permeability, and scope is that 1u is to 550u.When using this magnetic element, the backhaul management is important because the reverse recovery time of backhaul (output) diode magnetic element on the primary coil switch, produce high drain-source voltage.After the primary side switch opens, backhaul electric current (see figure 5) was arranged in the longer cycle.For example, Kool Mu (from the material of magnet) is suitable for this application scenario.Indicate this material and be not purpose in order to restriction.This material comprises by weight: 85% iron, 6% aluminium and 9% silicon.In addition, this magnetic element can be an air, (air permeability=1); The molybdenum permalloy powder, (MPP) magnetic element, high magnetic flux MPP magnetic element, the powder magnetic element has space ferrimagnetism element, is with around magnetic element die-cut magnetic element, the magnetic element of lamination or unbodied magnetic element.At work, the temperature of NSME raises, and magnetic permeability slowly reduces, thereby improves saturation point.Some materials, such as air, also to the time, temperature and condition show magnetic permeability or very little variation or the not variation of saturation grade.Do not resemble the prior art of use greater than the high-permeability material of 2000u, magnetic permeability increases when high temperature fast.See the relation (Figure 11) of magnetic permeability and temperature.Prior art also is limited by the minimizing of magnetic element saturation when high temperature, makes to be operated in become difficulty and may need to use expensive bulk magnetic element of high power level and temperature.See figure b _SatRelation (Figure 12) with temperature.The present invention has utilized the desired characteristic of NSME.See the relation (Figure 17) of magnetic permeability and temperature.Be operated in more low frequency 20-600kHz, reduced switching loss and magnetic element loss, allow to be operated in higher temperature.See the Figure 16 that concerns of loss density and magnetic flux density.Do not resemble prior art, the present invention uses has the voltage mode control that overcurrent turn-offs.Material selects also to be based on quality and efficient.By increasing the quality of magnetic element, more energy more effectively is coupled.Owing to reduced loss, loss roughly is I ²The R/ copper loss.Magnetic element is operated in the conduction ratio of 0%+ to 90%, and when being used to control the primary side push pull voltage, it has caused about 90% efficient.

Figure 18 B is that the schematic diagram of the BL1 of NSME is represented.Branch circuit BL1 is included in the primary coil winding 100 on the NSME 101.

Figure 18	Table
Figure 18	Table	Element	Value/parts number
????107	40 circle 50uh	Element	Value/parts number
????107	40 circle 50uh	????101	????2×77932-A7

Magnetic element BL1 also can be made of the magnetic element of one or more serial or parallel connections.Suppose minimum mutual inductance, then total inductance is the arithmetic sum of single inductance.For the element of parallel connection (mutual inductance that supposition is minimum), then total inductance is the inverse of arithmetic sum of the inverse of single inductance.By this way, a plurality of magnetic elements can be to arrange to satisfy packing, manufacturing and power requirement.Primary coil winding 100 has node P2B and P2A, to be connected to the external AC power supply.Magnetic element 101 comprises unsaturation, the low magnetic permeability magnetic material.With scope is that prior art from 1500u to 5000u is compared, the about 26u of its magnetic permeability, and scope is that 1u is to 550u.When using this magnetic element, the backhaul management is important because the reverse recovery time of backhaul (output) diode magnetic element on the primary coil switch, produce high drain-source voltage.After the primary side switch opens, the backhaul electric current was arranged in the longer cycle.(see figure 5) for example, KoolMu (from the material of magnet) is suitable for this application scenario.Indicate this material and be not purpose in order to restriction.This material comprises by weight: 85% iron, 6% aluminium and 9% silicon.In addition, this magnetic element can be an air, (air permeability=1); The molybdenum permalloy powder, (MPP) magnetic element, high magnetic flux MPP magnetic element, the powder magnetic element has space ferrimagnetism element, is with around magnetic element die-cut magnetic element, the magnetic element of lamination or unbodied magnetic element.At work, the temperature of magnetic element raises, and magnetic permeability slowly reduces, thereby improves saturation point.Some materials, such as air, also to the time, temperature and condition show magnetic permeability or very little variation or the not variation of saturation grade.Do not resemble the prior art of use greater than the high-permeability material of 2000u, magnetic permeability increases when high temperature fast.See the relation (Figure 11) of magnetic permeability and temperature.Prior art also is limited by the minimizing of magnetic element saturation when high temperature, makes to be operated in become difficulty and may need to use expensive bulk magnetic element of high power level and temperature.See figure b _SatRelation (Figure 12) with temperature.The present invention has utilized the NSME desired characteristics.See the relation (Figure 17) of magnetic permeability and temperature.Prior art often is operated in high switching frequency 100-1000kHz to avoid saturation problem.Only be to have increased switch and core loss (seeing Figure 12 A).The present invention uses the NSME characteristic of expectation, allows to be operated in more low frequency 20-600kHz, has further reduced switching loss and magnetic element loss.See the Figure 16 that concerns of loss density and magnetic flux density.Do not resemble prior art, the present invention uses has the voltage mode control that overcurrent turn-offs.Material selects also to be based on quality and efficient.By increasing the quality of magnetic element, more energy more effectively is coupled.Owing to reduced loss, loss roughly is I ²The R/ copper loss.

Figure 18 C is that the schematic diagram of distributed NSME PFT1D is represented.This figure is illustrated with example distribution formula magnet, and it can realize favourable high voltage converter design, and it supports form factor flexibility and from the secondary coil output of a plurality of parallel connections of the primary coil winding of the dividing potential drop of connecting at a plurality of NSME.This magnet strategy is solving wire insulation, form factor and encapsulation limit, and the problem in circuit complexity and the manufacturability is useful.In this embodiment, the 500W converter need adapt to very little encapsulation.Branch circuit PFTD1 comprises three magnetic elements 120,121 and 124, with the primary coil that is connected in series.

Figure 18 C	Table
Figure 18 C	Table	Element	Value/parts number
????113	????77352-A7	Element	Value/parts number
????113	????77352-A7	????122	23 circles
????123	23 circles	????122	23 circles
????123	23 circles	????112	67uh (55 circle)
????114	????77352-A7	????112	67uh (55 circle)
????114	????77352-A7	????116	67uh (55 circle)
????117	????77352-A7	????116	67uh (55 circle)
????117	????77352-A7	????118	67uh (55 circle)

AC voltage is applied to 112 pin P1B, passes through conductor 115 to 116 pin P1D from P1C then.Winding 116 pin P1E are connected to 118 pin P1F by conductor 119, arrive pin P1A then.Initial branch circuit PFT1 (Figure 18) is included in the primary coil winding 100 on the NSME 101, and NSME 101 has two tapped windings 122 and 123.For instance, branch circuit PFT1D will realize as three magnetic elements.For 500 watts situation, in winding 100, need the total inductance (Figure 18) of 203uH.Press the number assignment primary side inductance of element, in this case, need three elements 112,116 and 118 to have the inductance of 67uH.The energy storage is distributed in magnet assembly 120,121 and 124 fifty-fifty.Two (Kool Mu parts number 77932-A7) 0.9 ounce of (25 gram) NSME of 500 watts of converter using in Fig. 1 are to form 101 (Figure 18).Branch circuit PFT1 magnetic element 101 (Figure 18) can be expressed as three 0.5-0.7 ounces (14-19 gram) element.Three 0.5 ounce Kool Mu element (parts number 77352-A7) is selected.In order to realize the primary side inductance element of 67uH, 112,116 and 118 need 55 circles.The primary coil circuit has node P1B and P1A, to be connected to the external AC power supply.Secondary coil 102 windings have tapped node S1CT and node S1H and S1L, are connected respectively to top and half following one.Secondary coil 123 windings have tapped node S2CT and node S2H and S2L, are connected respectively to top and half following one.122 and 123 all are connected to outside full-wave rectifier parts.Magnetic element 120,121 and 124 comprises unsaturation, the low magnetic permeability magnetic material.Compare with the prior art of about 2500u, the about 26u of its magnetic permeability, scope is that 1u is to 550u.When using this magnetic element, the backhaul management is important because the reverse recovery time of backhaul (output) diode magnetic element on the primary coil switch, produce high drain-source voltage.After the primary side switch opens, the backhaul electric current was arranged in the longer cycle.(see figure 5) for example, Kool Mu (from the material of magnet) is suitable for this application scenario.Indicate this material and be not purpose in order to restriction.This material comprises by weight: 85% iron, 6% aluminium and 9% silicon.In addition, this magnetic element can be an air, (air permeability=1); The molybdenum permalloy powder, (MPP) magnetic element, high magnetic flux MPP magnetic element, the powder magnetic element has space ferrimagnetism element, is with around magnetic element die-cut magnetic element, the magnetic element of lamination or unbodied magnetic element.At work, the temperature of NSME raises, and magnetic permeability slowly reduces, thereby improves saturation point.Some materials, such as air, also to the time, temperature and condition show magnetic permeability or very little variation or the not variation of saturation grade.Do not resemble the prior art of use greater than the high-permeability material of 2000u, magnetic permeability increases when high temperature fast.See the Figure 11 that concerns of magnetic permeability and temperature.Prior art also is limited by the minimizing of magnetic element saturation when high temperature, makes to be operated in become difficulty and may need to use expensive bulk magnetic element of high power level and temperature.(see figure b _SatThe Figure 12 that concerns with temperature).The present invention has utilized the NSME desired characteristics.See the relation (Figure 17) of magnetic permeability and temperature.The saturation magnetization element of prior art is usually operated at the frequency greater than 500kHz, to realize bigger power grade.The result is that when high frequency, the professional experiences the core loss (seeing Figure 12 A) that index increases.The NSME support performance has further reduced switching loss and magnetic element loss at lower frequency 20-600kHz, allows to be operated in higher temperature.See the relation (Figure 16) of loss density and magnetic flux density.Do not resemble prior art, the present invention uses has the voltage mode control that overcurrent turn-offs.Material selects also to be based on quality and efficient.By increasing the quality of magnetic element, more energy more effectively is coupled.Owing to reduced loss, loss roughly is I ²The R/ copper loss.Magnetic element is operated in the conduction ratio of 0%+ to 90%, and when being used to control the primary side push pull voltage, it has caused about 90% efficient.

Figure 19 is that the schematic diagram that magnetic element branch circuit PPT1 is recommended in unsaturation is represented.

Branch circuit PPT1 is included in the primary coil winding 104 on the NSME106, and NSME106 has a tapped winding 105 of second coil side.

Figure 19	Table
Figure 19	Table	Element	Value/parts number
????106	????77259-A7	Element	Value/parts number
????106	????77259-A7	????105	10 circles
????104	70 circles	????105	10 circles

Primary coil winding 104 has node P2H and P2L, to be connected to the external AC power supply; With public centre tap node P2CT.Secondary coil winding 105 has tapped node SCT and node SH and SL, is connected respectively to top and half following one.The invention is not restricted to single output.Can increase more secondary coil winding, be used for other output.Secondary coil 105 is connected to outside full-wave rectifier parts (for example, Figure 25 or 26).Magnetic element 106 comprises unsaturation, the low magnetic permeability magnetic material.Compare with the prior art of about 2500u, the about 26u of its magnetic permeability, scope is that 1u is to 550u.When using this magnetic element, the backhaul management is important because the reverse recovery time of backhaul (output) diode magnetic element on the primary coil switch, produce high drain-source voltage.The backhaul electric current that decline was arranged in the long cycle.(see figure 5) for example, Kool Mu (from the material of magnet) is suitable for this application scenario.Indicate this material and be not purpose in order to restriction.This material comprises by weight: 85% iron, 6% aluminium and 9% silicon.In addition, this magnetic element can be air (comprising the aeromagnetic element); Molybdenum permalloy powder (MPP) magnetic element, high magnetic flux MPP magnetic element, the powder magnetic element has space ferrimagnetism element, is with around magnetic element die-cut magnetic element, the magnetic element of lamination or unbodied magnetic element.At work, the temperature of NSME raises, and magnetic permeability slowly reduces, thereby improves saturation point.Do not resemble the prior art of use greater than the high-permeability material of 2000u, magnetic permeability increases when high temperature fast.See the relation (Figure 11) of magnetic permeability and temperature.Prior art also is limited by the minimizing of magnetic element saturation when high temperature, makes to be operated in become difficulty and may need to use expensive bulk magnetic element of high power level and temperature.See figure b _SatRelation (Figure 12) with temperature.The present invention has utilized the NSME desired characteristics.See the relation (Figure 17) of magnetic permeability and temperature.Be operated in more low frequency 20-600kHz, reduced switching loss and magnetic element loss, allow to be operated in higher temperature.See the Figure 16 that concerns of loss density and magnetic flux density.Do not resemble prior art, the present invention uses has the voltage mode control that overcurrent turn-offs.Material selects also to be based on quality and efficient.By increasing the quality of magnetic element, more energy more effectively is coupled.Owing to reduced loss, loss roughly is I ²The R/ copper loss.The magnetic element primary coil is driven the effective use that has caused the magnetic element volume with push pull mode by the conduction ratio of 48-49%.

Figure 19 A is that the schematic diagram that magnetic element branch circuit PPT1 is recommended in unsaturation is represented.Branch circuit PPT1 is included in the tapped primary coil winding 134 on the NSME136, and NSME101 has a tapped secondary coil winding 135.

Figure 19 A	Table
Figure 19 A	Table	Element	Value/parts number
????136	????77259-A7	Element	Value/parts number
????136	????77259-A7	????135	10 circles
????134	70 circles	????135	10 circles

Primary coil winding 134 has node P2H and P2L, to be connected to the external AC power supply; With public centre tap node P2CT.Secondary coil 135 windings have tapped node SCT and node SH and SL, are connected respectively to top and half following one.The invention is not restricted to single output.Can increase more secondary coil winding, be used for other output.Secondary coil 135 is connected to outside full-wave rectifier parts, such as OUTA (Figure 25), and OUTB (Figure 25 A) and OUTBB (Figure 25 B).Magnetic element 136 comprises unsaturation, the low magnetic permeability magnetic material.Compare with the prior art of about 2500u, the about 26u of its magnetic permeability, scope is that 1u is to 550u.When using this magnetic element, the backhaul management is important because the reverse recovery time of backhaul (output) diode magnetic element on the primary coil switch, produce high drain-source voltage.The backhaul electric current that decline was arranged in the long cycle.(see figure 5) for example, Kool Mu (from the material of magnet) is suitable for this application scenario.Indicate this material and be not purpose in order to restriction.This material comprises by weight: 85% iron, 6% aluminium and 9% silicon.In addition, this magnetic element can be air (comprising the aeromagnetic element); Molybdenum permalloy powder (MPP) magnetic element, high magnetic flux MPP magnetic element, the powder magnetic element has space ferrimagnetism element, is with around magnetic element die-cut (cut) magnetic element, the magnetic element of lamination or unbodied magnetic element.At work, the temperature of NSME raises, and magnetic permeability slowly reduces, thereby improves saturation point.Do not resemble the prior art of use greater than the high-permeability material of 2000u, magnetic permeability increases when high temperature fast.See the relation (Figure 11) of magnetic permeability and temperature.Prior art also is limited by the minimizing of magnetic element saturation when high temperature, makes to be operated in become difficulty and may need to use expensive bulk magnetic element of high power level and temperature.See figure b _SatRelation (Figure 12) with temperature.The present invention has utilized the NSME desired characteristics, sees the relation (Figure 17) of magnetic permeability and temperature.Be operated in more low frequency 20-600kHz, reduced switching loss and magnetic element loss, allow to be operated in higher temperature.See the Figure 16 that concerns of loss density and magnetic flux density.Do not resemble prior art, the present invention uses has the voltage mode control that overcurrent turn-offs.Material selects also to be based on quality and efficient.By increasing the quality of magnetic element, more energy more effectively is coupled.Owing to reduced loss, loss roughly is I ²The R/ copper loss.The magnetic element primary coil is driven with the conduction ratio of push pull mode by 48-49%, has caused the effective use of magnetic element volume.

Figure 20 illustrates the filtering of the converter that AC circuit of the present invention connects and the schematic diagram of lightning (lightning) input protection circuit.Protection branch circuit LL comprises gap (Spark gap) A1, diode D20 and D21, capacitor C 1 and magnetic element L1 and L2.

Figure 20	Table
Figure 20	Table	Element	Value/parts number
????L1	????375uH	Element	Value/parts number
????L1	????375uH	????L2	????375uH
????C61	????0.01uF	????L2	????375uH
????C61	????0.01uF	????C60	????0.01uF
????A1	The 400V gap	????C60	????0.01uF
????A1	The 400V gap	????C1	????0.1uF
????D20	????1000V/25A	????C1	????0.1uF
????D20	????1000V/25A	????D21	????1000V/25A
????D22	????1000V/25A	????D21	????1000V/25A
????D22	????1000V/25A	????D23	????1000V/25A
????C2	????1.8uf	????D23	????1000V/25A

The AC circuit is connected to node LL2.DC can expand to along with the selection of parts outside this scope to the public incoming frequency of 440Hz.Node LL2 is connected to NSMEL1, arrives node LL5 then, gap A1, the negative electrode of the anode of diode D22 and diode D20.Filter capacitor C60 is connected between node LL0 and the LL6.Filter capacitor C61 is connected between node LL0 and the LL5.The low side of AC circuit (low side) is connected to node LL1, arrives magnetic element L2 then, and the opposite side of L2 is connected to gap A1, the negative electrode of the anode of diode D23 and diode D21 and node LL6.Capacitor C 1 is connected to ground C1, weakens the noise that is produced by converter.The use of unsaturation magnet makes the input magnetic element can absorb the very large voltage and current that is produced by lightning usually, usually needn't cause gap A1 clamper (clamp).In the process of UL test, the 2000V pulse of 60 16ms is applied between LL1 and the LL2, and does not cause gap A1 action, not loss.In normal work period, the NSMEL1 magnetic flux density is hundreds of Gauss.75u material among the figure of magnetic flux density and magnetizing force relation (Figure 15) can be accepted the magnetic flux density more than at least 50 times, and without limits.This is the example of the ability that can well move under the magnetic flux density bigger a lot of times than prior art of magnetic element.That element L1 and L2 will stop difference or common mode line transients (transient).If the transition of very large or long circuit alignment (neutral) takes place, then gap A1 is with the lsafety level of clamp voltage to about 400V.NSME L1 and L2 also bring the benefit of minimizing by the conducting noise of converter generation.

Figure 20 A is the schematic diagram that another line filter is shown.Filter branch circuit LF comprises capacitor C 2 and C60-66, inductance L 64 and L62, magnetic element L63 and diode D20-D23.

Figure 20 A	Table
Figure 20 A	Table	Element	Value/parts number
????L64	270 uH common mode H iron cores are bifilar	Element	Value/parts number
????L64	270 uH common mode H iron cores are bifilar	????L63	1.0 mH 125u differential mode
????L62	12 mH common mode H iron cores are bifilar	????L63	1.0 mH 125u differential mode
????L62	12 mH common mode H iron cores are bifilar	????C66	????0.01uF
????C63，C62	????0.47?uF	????C66	????0.01uF

????C61，C61，C64，C65	2.2nf Y type electric capacity
????C61，C61，C64，C65	2.2nf Y type electric capacity	????C20	????0.01uF
????D20	????1000V/25A	????C20	????0.01uF
????D20	????1000V/25A	????D21	????1000V/25A
????D22	????1000V/25A	????D21	????1000V/25A
????D22	????1000V/25A	????D23	????1000V/25A
????C2	????1.5uf	????D23	????1000V/25A

The AC circuit is connected to node LL2 and LL1.Node LL2 is connected to first branch road of y type electric capacity (y-cap) C64 by the last branch road of inductance L 64, arrives capacitor C 63 then, then to the last branch road of the inductance L 62 of bifilar coiling.Node LL1 is connected to second branch road of y type capacitor C 65 by the following branch road of inductance L 64, arrives capacitor C 63 then, arrives the following branch road of the inductance L 62 of bifilar coiling then.Capacitor C 66 is connected between LL2 and the LL1.Inductance L 62 second on branch road be connected to first branch road of y type capacitor C 61, arrive capacitor C 62 then, arrive the anode of D22 and the negative electrode of D20 then.Second time branch road of inductance L 62 is connected to second branch road of y type capacitor C 60, arrives capacitor C 62 then, arrives the anode of D23 and the negative electrode of D21 then.Y type capacitor C 60, C61, the middle branch of C64 and C65 is connected to chassis (chassis), returns LL0.Capacitor C 69 connected node BR-are to ground, chassis LLO.The anode of diode D20 and D21 is connected to Node B R-.The anode of diode D22 and D23 is connected to MSMEL63 in parallel with C20 and Node B R+.Capacitor C 21 is connected to the other end of BR-and the L63 in parallel with C20, form Node B+.Common mode inductance L64 and L62 are at high magnetic permeability core material H41-406-TC, the last structure of H42-109-TC, they are made by the Magnetics Inc. of the Butler of U.S. Pennsylvania respectively.This material is for instance, is not to be used for restriction.Capacitor C 69 is connected to ground, has weakened the noise that is produced by converter.The present invention has utilized the ferritic high magnetic permeability characteristic of using in inductance L 64 and L62.(seeing Figure 15 A).At all four quadrants, made full use of core material.Inductance L 64 and L62 are effective removing on the common mode EMI component.The differential mode noise that is produced by main switch Q1 is stoped effectively by the NSME L63 in parallel with C20.Inductance L 63 is operated in first quartile, has utilized the unsaturation characteristic of the uniqueness of Kool Mu core material (being made by Magnetics Inc.).This material allows with big DC magnetizing current work, and can be unsaturated.125u material among the figure of magnetic flux density and magnetizing force relation (Figure 15) is selected for this occasion.This is for instance, but not is used for restriction.This is the example of the ability that can well move under the magnetic flux density bigger a lot of times than prior art of magnetic element.The NSME L63 in parallel with C20 forms the tuning tank circuit, stoped the high frequency from the AC circuit effectively.Element L64 and L62 will stop the common mode line transients.If the transition of very large or long circuit to neutral point takes place, the branch circuit TRN (Figure 46) that then is connected to BR+ is incorporated into primary storage capacitor C 442 with transition.The present invention has used the material of ferrite type and has used the NSME that expects in the DC side in AC side the best, so that high-performance filtering to be provided under low cost.

Figure 21 is the schematic diagram that another lightning protection branch circuit LLA of the converter that AC circuit of the present invention connects is shown.Protective circuit comprises fuse F1, gap A1, capacitor C 1, C60 and C61 and NSMEL3.

Figure 21	Table
Figure 21	Table	Element	Value/parts number
????L3	????750uH	Element	Value/parts number
????L3	????750uH	????C61	????0.01uF
????C60	????0.01uF	????C61	????0.01uF
????C60	????0.01uF	????F1	????10A
????A1	The 400V gap	????F1	????10A
????A1	The 400V gap	????C1	????0.1uF
????D20	????1000V/25A	????C1	????0.1uF
????D20	????1000V/25A	????D21	????1000V/25A
????D22	????1000V/25A	????D21	????1000V/25A
????D22	????1000V/25A	????D23	????1000V/25A
????C2	????1.8uf	????D23	????1000V/25A

The high-end node LL2 that is connected to of AC circuit, fuse F1, the load-side of fuse is connected to NSME L3 and capacitor C 61.Load-side L3 is connected to the negative electrode of gap A1 and diode D20 and the anode of D22, forms node LL5.The low side of AC circuit is connected to node LL6, capacitor C 60, the negative electrode of gap A1 and diode D21 and the anode of D23.The anode of diode D20 and D21 is connected to capacitor C 1.Capacitor C 1 is connected to ground.C1 has weakened radiated noise or the EMI that is produced by converter.The negative electrode of diode D22 and D23 is connected to capacitor C 2.Capacitor C 2 disconnects the high-frequency harmonic electric current from circuit.Capacitor C 1, C61 and C60 are connected to ground node LL0.The use of unsaturation magnet makes the input magnetic element can absorb the very large voltage and current that is produced on the AC circuit by lightning usually.Transition on the AC circuit will by capacitor C 60 and C61 be limited and stoped by unsaturation magnet L3.If the transition of very large or long circuit alignment takes place, then magnetic element L3 will make voltage raise on gap A1, and gap is with the level of clamp voltage to safety, with protection rectifier diodes D20-D23.NSME L3 also brings the benefit of minimizing by the conducting noise of converter generation.C1 is connected to ground, is effective weakening aspect EMI conducting and radiation.

Figure 22 is the schematic diagram that AC line rectifier of the present invention is shown.Rectifier branch circuit BR1 comprises diode D20, D21, D22 and D23 and capacitor C 2.

Figure 22	Table
Figure 22	Table	Element	Value/parts number
????D20	????1000V/25A	Element	Value/parts number
????D20	????1000V/25A	????D21	????1000V/25A
????D22	????1000V/25A	????D21	????1000V/25A
????D22	????1000V/25A	????D23	????1000V/25A
????C2	????1.8uf	????D23	????1000V/25A

AC or DC signal are connected to bridge rectifier from input filter, to Node B R1 and BR2.Node B R1 connects diode D22 anode to the D20 negative electrode.Node B R2 connects diode D23 anode to the D21 negative electrode.Node B R+ connects diode D22 negative electrode to the D23 negative electrode.Node B R-connects diode D20 anode to the D21 anode.DC can expand to along with the selection of parts outside this scope to the public incoming frequency of 440Hz.Select capacitor C 2 with the power factor of raising particular job frequency with from circuit cut-off switch electric current.Select diode to stop the possible line voltage distribution and the current requirements of next transducer-level reliably.

Figure 23 is an AC-DC controller branch circuit of the present invention.Branch circuit PFA comprises resistance R 313 and R316, capacitor C 308 and C313 and PWM controller IC U1A.

Figure 23	Table
Figure 23	Table	Element	Value/parts number
????C311	????0.1uf	Element	Value/parts number
????C311	????0.1uf	????C308	????.01uf
????R313	15k ohm	????C308	????.01uf
????R313	15k ohm	????R316	15k ohm
????C313	????4700pf	????R316	15k ohm

????R308	25k ohm
????R308	25k ohm	????U1A	????MIC38C43(Micrel)

Control element U1A is connected to has the following circuit that is connected in series: from the pin one to the feedback node/pin PF1, arrive capacitor C 308 then, arrive U1A pin two node then.Inner 5.1 volts reference point U1A pins 8 or node PFA2 arrive pin 4 nodes by resistance R 308.U1A pin 4 is connected to return node BR-by capacitor C 313.This structure makes PFC export and is used the voltage pulse-width modulation that is applied to PF1.The external feedback electric current is applied to U1A pin one and node PF1.Node PFVC is connected to resistance R 313, to the pin 3 of U1A.Resistance R 316 is connected to pin 3, arrives return node BR-then, and power pin 7 is connected to node PFA+.Control element switch drive U1A pin 6 is connected to node PFCLK.The ground node pin 5 that returns of U1A is connected to return node BR-.If such as IPFFB (Figure 40), FBA (Figure 40 A), generation part fault in the primary coil feed network of IFB (Figure 40 B) and FB1 (Figure 41), then the output voltage of voltage-boosting stage may be increased to destructive level apace.Overvoltage feedback network IOVFB (Figure 40 C) or OVP2 (Figure 42 B) have increased the electric current that enters PF1 fast, thereby the restriction output voltage is to the level of safety.In addition, also can use the overvoltage protection network that latchs type, such as OVP (Figure 42), OVP1 (Figure 42 A) and OVP2 (Figure 42 B).Latch type and be depleted to the power of control circuit, thereby stop boost action.Latch the type network required power and be recycled to converter, with the replacement latch.IFB input node PFVC is connected to resistance R 313, arrives return node BR-to the zero-crossing detector of the inside that is connected to pin 3 with by R316 again.PFVC is connected to the magnetic element winding and is referenced to BR-.In each magnetic element be biased to zero the time, new turn-on cycle begins.By with the high frequency chopping input, realize the power factor of proofreading and correct.For given load, at high line voltage distribution, average pulse reduces, and average pulse increases when low-voltage.At the circuit peak value, frequency is lower, and near zero-crossing point, frequency is higher.By this way, converter is with high input power factor work.

Figure 24 is another power factor controller branch circuit.Branch circuit PFB comprises resistance R 313, R339, R314, R315, R328, R340, R341 and R346, diode D308, capacitor C 310, C318, C338, C340, C341 and C342, transistor Q305 and control element ICU 1B.

Figure 24	Table
Figure 24	Table	Element	Value/parts number
????Q305	????BCX70KCT	Element	Value/parts number
????Q305	????BCX70KCT	????R339	432k ohm

????C338	????0.22?uf
????C338	????0.22?uf	????C318	????0.22?uf
????R314	2.2M ohm	????C318	????0.22?uf
????R314	2.2M ohm	????R315	715k ohm
????C341	????0.33?uf	????R315	715k ohm
????C341	????0.33?uf	????C342	????0.01?uf
????C340	????0.001?uf	????C342	????0.01?uf
????C340	????0.001?uf	????R328	1M ohm
????R346	7.15k ohm	????R328	1M ohm
????R346	7.15k ohm	????D308	????10BQ040
????R340	449k ohm	????D308	????10BQ040
????R340	449k ohm	????R313	22k ohm
????U1B	????MC34262(Motorola)	????R313	22k ohm
????U1B	????MC34262(Motorola)	????R341	499k ohm

Control element U1B is connected to has the following circuit that is connected in series: from the pin one to the node/pin PF1, to the capacitor C 338 of connecting, arrive the pin two node of U1B then with resistance R 339.Pin one is the input to the error amplifier of inside, is connected to external feedback network (seeing Figure 40,40A, 40B, 40C and 41).Be increased in the pulsewidth that voltage on the pin one has reduced PFCLK node pin 7.Resistance R 328 is connected to the AC circuit haversine voltage of full-wave rectification, at Node B R+, arrives U1B pin 3 then, arrives then and capacitor C 342 parallel resistor R346, to return node BR-.Node PFSC is connected to series resistance [R341+R340], and it is connected to U1B pin 4, arrives then and capacitor C 340 diode connected in parallel D308, arrives return node BR-again.Power to pfc controller is applied to node PFB+ and U1B pin 8.Output clock node PFCLK is connected to U1B pin 7, arrives external buffer branch circuit AMP (Figure 29) again.Transistor Q305 collector electrode is connected to the pin two node of U1B.Base stage is connected in series to capacitor C 318 by resistance R 314, arrives the pin two node of U1B then.Base stage also is connected to [C310 ‖ R315], arrives return node BR-then, and the emitter of Q305 is connected to return node BR-.Transistor Q305 provides soft start compensation inclined-plane (ramp) to the controller error amplifier, has reduced stress and and DC toning when powering in the converter.Capacitor C 341 is connected to return node BR-from the U1 pin two.The U1B pin one is connected to pin PF1, and the capacitor C 338 of connecting with resistance R 339 arrives transistor Q305 collector electrode and U1 pin two again.Electric current (Fig. 4 and 3) by PFC power switch Q1 switch detects (see figure 4) by R26.Series resistance [R340+R341] to U1B pin 4 is connected the voltage that R26 goes up generation.This voltage is compared with 1.5 volts reference voltages of inside, big electric current takes place when starting in or during at very high load or low line condition, the switch drive pin 7 of comparator output shutoff U1B.Capacitor C 340 is connected between U1 pin 4 and the return node BR-, the filtering high fdrequency component.Schottky diode D308 is connected between U1 pin 4 and the return node BR-, prevents that the reverse current of controller (U1 pin 4) substrate from injecting.Maximum switching current value is set by R26, and in each cycle, overcurrent is automatically limited by pfc controller.Be multiplied with the in the error voltage of pin two in the all-wave haversine of the rectification of the pin 3 of U1B.The long-pending quilt of gained is compared with the magnetic element/switching current by the R26 measurement at pin 4.When the magnetic element electric current that detects is increased to the current comparator rank, turn-off in the gate-drive of pin 7.This action has the AC of tracking line voltage distribution, the effect of modulation switch Q1 " conducting " time.The external feedback network is connected to node PF1.If such as IPFFB (Figure 40), FBA (Figure 40 A), generation part fault in the primary coil feed network of IFB (Figure 40 B) and FB1 (Figure 41), then the output voltage of voltage-boosting stage may be increased to destructive level apace.Overvoltage feedback network IOVFB (Figure 40 C) or OVP2 (Figure 42 B) have increased the electric current that enters PF1 fast, thereby the restriction output voltage is to the level of safety.In addition, also can use the overvoltage protection network that latchs type, such as OVP (Figure 42), OVP1 (Figure 42 A) and OVP2 (Figure 42 B).Latch the type transfer power to control circuit, thereby stop boost action.Latch the type network required power and be recycled to converter, with the replacement latch.The voltage that is modulated at PF1 has changed the conduction ratio of PFC and last output voltage.By this way, PFC can be used as the preconditioner of other output stage.

Figure 25 is the schematic diagram of full-wave rectification output stage and filter branch circuit OUTA.Rectifier stage comprises diode D80 and D90.Filter comprises resistance R 21, magnetic element L30 and capacitor C 26, C27, C28, C29, C30, C31 and C32.

Figure 25	Table
Figure 25	Table	Element	Value/parts number
????D80	????40CTQ150	Element	Value/parts number
????D80	????40CTQ150	????D90	????40CTQ150
????R21	100 ohm	????D90	????40CTQ150
????R21	100 ohm	????C26	????500pf
????C27	????200pf	????C26	????500pf

????C28	????0.1uf
????C28	????0.1uf	????C29	????10,000uf
????C30	????10,000uf	????C29	????10,000uf
????C30	????10,000uf	????C31	????0.1uf
????C32	????200pf	????C31	????0.1uf
????C32	????200pf	????L30	????10uh

Input node/pin C7B is connected to the high-end of outside tapped magnetic element secondary coil winding.Node C7B is connected to the anode of diode D8 and the capacitor C 26 and the C27 of following structure.Capacitor C 27 is connected the two ends of diode D80, and capacitor C 26 is connected in series to R21.Input node/pin C8B is connected to the low side of outside tapped magnetic element secondary coil winding.Pin C8B is connected to anode and the resistance R 21 of diode D9, and capacitor C 32 is connected the two ends of diode D90.Capacitor C 27 and C32 value are very little, to reduce the high-frequency noise that is produced by switch high-speed rectifier D80 and D90 apace respectively.Capacitor C 26 and resistance R 21 are used to further dissipate high-frequency energy.The anode of diode D80 and D90 is connected to shunt capacitance C28 ‖ C29 and NSMEL30.Capacitor C 28 and C31 are the solid dielectric types, for Low ESR and high-frequency signal are selected.Capacitor C 29 and C30 are bigger polarization type, for the Low ESR when the low frequency and energy storage are selected.Magnetic element L3 is connected to diode D8 negative electrode, and second end of L30 is connected to shunt capacitance C31 and C30 and pin OUT+.Node OUT+ is an output cathode, is connected to the external feedback detection line, to the feedback network of isolating.The other end of shunt capacitance [C28 ‖ C29 ‖ C30 ‖ C31] is connected to the centre tap of pin OUT-and magnetic element secondary coil winding, forms return node.Electric capacity [C28 ‖ C29], L30 and electric capacity [C30 ‖ C31] be combined to form low pass ∏ mode filter.Branch circuit OUTA carries out effective full-wave rectification and filtering.

Figure 25 A is the schematic diagram of full-wave rectification output stage.Rectifier stage comprises diode D80 and D90 and capacitor C 931 and C928.

Figure 25 A	Table
Figure 25 A	Table	Element	Value/parts number
????D80	????40CTQ150	Element	Value/parts number
????D80	????40CTQ150	????D90	????40CTQ150
????C928	????.01uf	????D90	????40CTQ150
????C928	????.01uf	????C931	????10,000uf

Input node/pin C7B is connected to the high-end of outside tapped magnetic element secondary coil winding.Node C7B is connected to the anode of diode D80.Input node/pin C8B is connected to the low side of outside tapped magnetic element secondary coil winding, is connected to the anode of diode D90.Node OUT-is negative pole output and arrives the feedback network of unshowned external isolation and the return line of load.The anode of diode D80 and D90 is connected to shunt capacitance C931 and C928.Capacitor C 928 is solid dielectric types, for Low ESR and high-frequency signal are selected.Capacitor C 931 is bigger polarization type, for the Low ESR when the low frequency and energy storage are selected.Node OUT+ is an output cathode, is connected to the external feedback detection line, to the feedback network of isolating.The other end of shunt capacitance C928 ‖ C931 is connected to the centre tap of magnetic element secondary coil winding, forms node OUT-.Recommend the use of the NSME of magnetic element only need be after rectification minimum filtering.

Figure 25 B is the schematic diagram of another last output rectifier and filter branch circuit OUTB.Rectifier branch circuit OUTB comprises diode D40, D41, D42 and D43 and capacitor C 931 and C928.

Figure 25 B	Table
Figure 25 B	Table	Element	Value/parts number
????D40	????40CTQ150	Element	Value/parts number
????D40	????40CTQ150	????D41	????40CTQ150
????D42	????40CTQ150	????D41	????40CTQ150
????D42	????40CTQ150	????D43	????40CTQ150
????C928	????.01uf	????D43	????40CTQ150
????C928	????.01uf	????C931	????10,000uf

AC or DC signal are connected to node C7B and C8b.Node C7B connects diode D41 anode to the D40 negative electrode.Node C8b connects diode D42 anode to the D43 negative electrode.Node OUT+ connects diode D42 negative electrode to the D43 negative electrode.Node OUT-connects diode D40 anode to the D43 anode.Diode is selected to stop the possible line voltage distribution and the current requirements of load reliably.For low-voltage output, use Schottky type diode, because their low forward voltage falls.Higher voltage just uses the high-speed silicon diode, because they can bear high peak inverse voltage (PIV).Recommend the use of the NSME of magnetic element only need be after rectification minimum filtering.Capacitor C 928 is schematically illustrated as individual devices.Capacitor C 931 is bigger polarization type, selects for the Low ESR when the low frequency and energy storage, and representative value can be 200uF.In order to increase capacitance or to reduce output impedance, can use a plurality of electric capacity.C931 is the solid dielectric type, for Low ESR and high-frequency signal are selected.Its selection is in order to reduce the noise of particular job frequency and power level.Capacitor C 928 selects to be used for operating frequency and power grade.Because additional node, branch circuit OUTB carries out AC-DC rectification and filtering with lower slightly efficient.

Figure 26 is drift (Floating) 18 volts of DC power controlling branch circuit CP.Branch circuit CP comprises diode D501, D502 and D503, resistance R 507, adjuster Q504 and capacitor C 503, C504, C505, C506, and C507.

Figure 26	Table
Figure 26	Table	Element	Value/parts number
????C503	????.33uF	Element	Value/parts number
????C503	????.33uF	????C504	????100uF
????D501	????MURS120T3	????C504	????100uF
????D501	????MURS120T3	????C505	????.33uf
????Q504	????LM7818A	????C505	????.33uf
????Q504	????LM7818A	????C508	????100uf
????C507	????100uf	????C508	????100uf
????C507	????100uf	????D503	????MURS130T3
????D502	????MURS120T3	????D503	????MURS130T3

Node CT1A is connected to the anode of D503 and the outside tapped secondary coil winding on top.Node CT2A is connected to the anode of D502 and the outside tapped secondary coil winding of bottom.Node CT0 is connected to the centre tap of outside winding.Node CT0 also is a return line, and it is connected to Q504 pin two and capacitor C 503, C504, C505, C506, and C507.The negative electrode of diode D502 and D503 all is connected to resistance R 507.R507 is connected to pin one (input) node of voltage regulator Q504 then.Voltage regulator Q504 pin 3 is that 18Vdc regulates.DC output is connected to the anode of blocking diode D501.Three-prong voltage regulator Q504 is the LM7818 type, by the public device of many manufacturers manufacturing.Capacitor C 503, C505, C506 are 0.1uF solid dielectric types, are used to the filtering high-frequency fluctuation and prevent the Q504 vibration.C503, the node of C504 and D501 negative electrode is output node CP1+.18 volts of DC that isolate are between node CT0 and CP+.Be used for adjuster circuit and output switch drive in normal work period.

Figure 26 A is another power controlling branch circuit CP1, and branch circuit CP1 comprises diode D260, resistance R 261, transistor Q260 and capacitor C 261-C265, and C260.

Figure 26 A	Table
Figure 26 A	Table	Element	Value/parts number
????C261-C263	????0.33uF	Element	Value/parts number
????C261-C263	????0.33uF	????C260	????0.1uF
????D260	????BZX84C16	????C260	????0.1uF
????D260	????BZX84C16	????D261-262	????MURS120TS
????C265	????0.33uf	????D261-262	????MURS120TS
????C265	????0.33uf	????Q260	????FTZ605CT
????C266	????0.01uF	????Q260	????FTZ605CT
????C266	????0.01uF	????L260	????1mh
????R261	100k ohm	????L260	????1mh
????R261	100k ohm	????R262	10 ohm
????C264	????220uf	????R262	10 ohm

Node CT1A is connected to the anode of D261 and the outside tapped secondary coil winding on top.Node CT2A is connected to the anode of D262 and the outside tapped secondary coil winding of bottom.Node B R-is connected to the centre tap of outside winding.Node B R-also is a return line, and it is connected to the Q260 emitter, capacitor C 261-C265 and R261.The negative electrode of diode D261 and D262 is connected inductance L 260 and capacitor C 266.The other end of capacitor C 266 is connected to node FSC.Resistance R 262 is connected between the other end and node VCC of inductance L 260 then.The node of R262 and L260 forms node TP15.Node VCC connects positive terminal, the collector electrode of Q260 and the negative electrode of D260 of capacitor C 260-265.The low anode that leaks Zener D260 is connected to base stage, resistance R 261 and the capacitor C 260 of Q260.Select zener diode voltage so that begin to regulate in high boost level.Thereby make VCC follow the load level, shown in G260 (Figure 26 B).Near full load level (maximum is boosted) time, the beginning voltage limit.This is for instance, but not is used for restriction.In 1000 watts of power supplys,, can see the VCC restriction along with the increase of slope in section 262 (Figure 26 B).This idiosyncratic behavior has three benefits.At first, in bigger boost level (load), when needs maximum gate pole power, extra voltage automatically is provided to main switch Q1.When the boosting of minimum, reduce gate voltage and reduced stress, thereby improved MBTF and efficient main switch Q1 gate pole and relevant buffer unit.The second, VCC provides inner load detection signal, is used for servo output voltage and is used for load and carries on a shoulder pole altogether.The load of design will be told about in Fig. 4 A the load aspect altogether.The 3rd, can there be a signal to be used to pass on the load size, and need not extra current sensor.Diode D262 and D261 provide the power of rectification, and capacitor C 226 connects the node TP17 (Figure 45) of AC voltage to branch circuit FS1.When converter is worked, suppress the action of fast start circuit at the AC of TP17 voltage.Adjuster CP1 is a parallel regulator.Alternative pack makes and to be limited near the maximum startup of boosting.By this way, when little load level, do not waste power.In addition, the modulated excess power when being provided at maximum and boosting of main switch Q1 gate voltage is to guarantee the maximal efficiency under various loading conditions.

Figure 26 B is the figure as the VCC of the function of power output.Figure 26 be when load when 0-1000 watt changes, VCC on ACDCPF1 (Fig. 4 A) produces by measuring.。

Figure 27 is that 18 volts of DC of second drift recommend power controlling branch circuit CPA.Branch circuit CPA comprises diode D601, D602 and D603, resistance R 607, adjuster B604 and capacitor C 603, C604, C605, C606, C607 and C608.

Figure 27	Table
Figure 27	Table	Element	Value/parts number
????C603	????.33uF	Element	Value/parts number
????C603	????.33uF	????C604	????100uF
????D601	????MURS12OT3	????C604	????100uF
????D601	????MURS12OT3	????C605	????.33uF
????Q604	????LM7818A	????C605	????.33uF
????Q604	????LM7818A	????C608	????100uF
????C607	????.22uF	????C608	????100uF
????C607	????.22uF	????R607	7.5 ohm
????D603	????MURS120T3	????R607	7.5 ohm
????D603	????MURS120T3	????D602	????MURS120T3

Node CT1B is connected to the anode of D603 and the outside tapped secondary coil winding on top.Node CT2B is connected to the anode of D602 and the outside tapped secondary coil winding of bottom.Node CT20 is connected to outside winding centre tap.Node CT0 also is a return line, and it is connected to Q604 pin two and capacitor C 603, C604, C605, C606, and C607.The negative electrode of diode D602 and D603 all is connected to resistance R 607.R607 is connected to pin one (input) node of voltage regulator Q604 then.Voltage regulator Q604 pin 3 is the DC output that 18VDC regulates, and is connected to the anode that stops diode D601.Capacitor C 603, C605, C606 are the solid dielectric types, are used to the filtering high-frequency fluctuation and prevent the Q604 vibration.C603, the node of C604 and D601 negative electrode is output node CP1+.18 volts of DC that isolate are between node CT20 and CP2+.Be used as adjuster circuit and output switch drive in normal work period

Figure 28 is main switch overheat protector branch circuit OTP.Branch circuit OTP comprises thermal switch and resistance R 711 and R712.

Figure 28	Table
Figure 28	Table	Element	Value/parts number
????THS1	????67F105(105℃)	Element	Value/parts number
????THS1	????67F105(105℃)	????R711	20 ohm
????R712	20 ohm	????R711	20 ohm

Gate-drive power is applied to input node GAP and thermal switch THS1.Maximum FET gate voltage needs input power voltage less than 20 volts, and selected voltage is 18 volts.The other end of THS1 is connected to parallel resistance [R711 ‖ R712].Single resistance may be represented a plurality of resistance.The figure shows surface installation structure.The other end of [R711 ‖ R712] is connected to output node TS+.The thermal switch TS1 that closes under the normal condition contacts with main switching transistor Q1.If temperature is greater than 105 ℃, then THS1 opens, thereby power transfer is arrived buffering branch circuit AMP1 (Figure 29), makes switch Q1 default to blocking state, can protect boosted switch under the situation of optional fan failure or circuit arrival high temperature.In this invention, for given power grade, acceleration buffering AMP (Figure 29), unsaturation magnet (Figure 18,18A and 19) make that temperature was low when main switch moved than prior art.When switch temperature is returned normal range (NR), THS1 will close, and allow PFC to recover operate as normal work.Under normal load and ambient temperature, thermal switch THS1 will can not open.

Figure 29 is PFC buffer circuit branch circuit AMP, AMP1, AMP2, AMP3.The switch drive order of PFCLK (Figure 23 and 24) or PWFM (Figure 33) control element is connected to the gate pole buffer circuit.Branch circuit AMP comprises power fet Q702, Darlington pair Q703, capacitor C 709 and C715 and resistance R 710 and R725.

Figure 29	Table
Figure 29	Table	Element	Value/parts number
????C715	????1000pf	Element	Value/parts number
????C715	????1000pf	????C709	????33uF
????Q702	????NOS355NCT	????C709	????33uF
????Q702	????NOS355NCT	????Q703	????FZT705CT
????R710	0 ohm	????Q703	????FZT705CT
????R710	0 ohm	????R725	22.1k ohm

DC power is applied to node GAT+, transistor Q702 drain electrode and capacitor C 709, capacitor C 709 ground connection.It must be less than 20 volts that maximum gate voltage needs input power voltage, has therefore selected 18 volts.Input node GA1 is connected to the gate pole of FETQ702, be connected to Darlington pair Q703 BJT1 base stage and be connected to capacitor C 715.C715 is connected the Darlington pair two ends, from base stage, and pin one, to collector electrode, pin two and 4, the Q703 collector node also is connected to ground.The emitter of BJT2 is connected to the gate pole of FET Q1.The source electrode of FET Q702 is connected to the gate pole or the node GA2 of output switch by little optional series resistance R710.When driving such as this buffer low-impedance power, some power fets are vibration easily under some load.May need about 2 ohm or littler small resistor, and switch can be significantly not slack-off.In most of the cases, R710 is replaced by zero ohm wire jumper.Resistance R 725 is connected to the source electrode of Q702 from node GA0.Arrive the scope of 600kHz at 20kHz to the input switch signal of node GAP.By providing Low ESR to be connected to the output switch gate pole of node GA2, realized very fast " connection " time with quick charge.When Q702 connected, capacitor C 709 provided extra current transistor Q703 that Low ESR is provided, and, has significantly reduced " shutoff " time to remove charging from gate pole apace.Compare with the rise time of the 250ns of industrial standard, this specific topological structure provides output about 10ns of switch rise time.Compare its corresponding fall time＜10ns (seeing Figure 13 and 14) with the fall time of the 200-300ns of industrial standard.If converter is operated in very high ambient temperature, then thermal switch can be connected with input power pin GA+.This makes that switching transistor is moderately forbidden.Branch circuit AMP has significantly reduced switching loss, in some cases, allows converter work, and need not the forced air-cooling of prior art.

Figure 30 is the schematic diagram of spacing branch circuit of the present invention.Spacing branch circuit SN comprises diode D804 and D805 and resistance R 800, R817, R818 and capacitor C 814 and C819.

Figure 30	Table
Figure 30	Table	Element	Value/parts number
????R800	????12	Element	Value/parts number
????R800	????12	????R817	1m ohm
????R818	1m ohm	????R817	1m ohm
????R818	1m ohm	????C814	????33pF
????C819	????560pF	????C814	????33pF
????C819	????560pF	????D805	????MUR160

Node SNL2 is connected to the drain electrode end of outside output switch and the backhaul side of inductive load.Input node SNL2 is connected to the R800 that connects with capacitor C 819, arrives node SNOUT again.Diode D805 anode and be connected to node SNL2 with D805 parallel resistor [R817 ‖ R818].Resistance R 817 and R818 can be combined into single resistance.The negative electrode of D805 is connected to capacitor C 814, and capacitor C 814 is connected to node/pin SNL1.Node SNL1 is connected to the mains side of external loading magnetic element.Another branch road of external magnetic element is connected to the anode of D805 and the anode tap of outside backhaul diode D4.One megohm resistance R 817 and R818 discharge from C814, to reset it, are used for next cycle.From the conversion of outside backhaul diode D4, capacitor C 819 and resistance R 800 are caught high-frequency process, portion of energy is moved on to the outside that is connected to node SNOUT support in the electric capacity.Because outside backhaul diode D4 and D805 have isolated the leakage level of output switch, because the output switch needn't turn round the extra capacitor of the limit circuit of common drain/source connection, so high-speed switch takes place.Should be noted that not trial this backhaul of absorption in the big RC network that useful energy is converted to loss of this circuit.It is not attempted the backhaul plug to (stuff) yet, and doing has like that just increased electric capacity, slack-off output switch and increased switching loss.This branch circuit uses with outside its mirror image SNB (Figure 32) that recommends switch ends.This design turns back to input power supply or output loading with some backhaul energy.The spacing ＂ action of ＂ makes the rising of backhaul slack-off, thereby starts the time of conducting for outside backhaul diode.This circuit has been managed high frequency backhaul pulse effectively.

Figure 30 A is the schematic diagram of the spacing branch circuit of diode of the present invention.Spacing branch circuit DSN comprises diode D51, D52, D53, D54 and D55 and capacitor C 51, C52, C53, C54 and C55.

Figure 30 A	Table
Figure 30 A	Table	Element	Value/parts number

????C51	????220?pf?100V
????C51	????220?pf?100V	????C52	????220?pf?100V
????C53	????220?pf?100V	????C52	????220?pf?100V
????C53	????220?pf?100V	????C54	????220?pf?100V
????C55	????220?pf?100V	????C54	????220?pf?100V
????C55	????220?pf?100V	????D51	Schottky 1-2ns 100V SMBSR1010MSCT
????D52	Schottky 1-2ns 100V SMBSR1010MSCT	????D51	Schottky 1-2ns 100V SMBSR1010MSCT
????D52	Schottky 1-2ns 100V SMBSR1010MSCT	????D53	Schottky 1-2ns 100V SMBSR1010MSCT
????D54	Schottky 1-2ns 100V SMBSR1010MSCT	????D53	Schottky 1-2ns 100V SMBSR1010MSCT
????D54	Schottky 1-2ns 100V SMBSR1010MSCT	????D55	Schottky 1-2ns 100V SMBSR1010MSCT

Pin SNL2 is connected to the anode of D51, the negative electrode of D51 is connected to the anode of D52, and the negative electrode of D52 is connected to the anode of D53, and the negative electrode of D53 is connected to the anode of D54, the negative electrode of D54 is connected to the anode of D55, and the negative electrode of D55 is connected to pin SNOUT.Electric capacity is connected the two ends of each diode, forms the connection in series-parallel combination of [D51 ‖ C51]+[D52 ‖ C52]+[D53 ‖ C53]+[D54 ‖ C54]+[D55 ‖ C55].Node SNL2 is connected to the drain electrode end of outside output switch and the backhaul side of inductive load.Outside backhaul rectifier diodes D4 (Fig. 1,3 and 4) anode is connected to node SNL2.Node SNOUT is connected to the negative electrode of storage capacitance [C16 ‖ C17] (Fig. 1,3 and 4) and backhaul diode D4.The external diode D4 in parallel with DSN forms compound diode.Schottky diode has desired characteristics, and fast recovery time is (less than 6 nanosecond (6*10 ^-9)) and when high electric current low forward voltage (0.4-0.9 volt) falls.The present maximum of Schottky diode can be born the limited reverse blocking voltage of 100V.Each diode will block 100V; Shunt capacitance distributes reverse voltage fifty-fifty on the diode string.Because the reverse node capacitance of each diode is little more than shunt capacitance less than 10pf, thus reverse voltage mean allocation on diode almost.In order to guarantee that average voltage distributes, need 5% better electric capacity coupling.For little electric capacity pinpoint accuracy is common and not expensive.By regulating the right number of diode/electric capacity, can realize different blocking voltages.Selecting 500V is for instance, and nonrestrictive.Main backhaul rectifier diodes D4 will block high voltage, be limited by long reverse recovery time, and in fast recovery diode, 50-500 nanosecond is common.Needed is to have low-voltage to fall, the diode of high blocking voltage and very short recovery time.The stop DSN in parallel with main backhaul rectifier is very near this ideal diode.Block voltage by the single diode of addition, obtain total blocking voltage.Determined by the slowest diode in the string, usually be recovery time less than 5 nanoseconds.When slower main converter begins conducting, realized that low forward voltage falls.Because capacitance is 1/5 of a single electric capacity, has also realized low-voltage capacity.After main switch stop conducting and unsaturation magnet began to discharge its energy, this compound diode began rectification immediately.This has limited high voltage backhaul toning (over shoot) effectively and has lied prostrate less than 40-70.This remains on switch in its area of safety operaton (SOA) well, allows switch to be operated in higher voltage under and has higher power output and extra efficiency gain, perhaps uses not expensive low tension switch and keeps identical voltage to have more than needed simultaneously.Because outside backhaul diode D4 and D805 have isolated the leakage level of output switch, because the output switch needn't turn round the extra capacitor of common limit circuit, high-speed switch takes place.Should be noted that not trial this backhaul of absorption in the big RC network that produces additional heat of this circuit.It is not attempted the backhaul plug to ground yet, and doing has like that just increased electric capacity, slack-off output switch and increased switching loss.Branch circuit DSN can with the use in parallel of any slower rectifier such as backhaul diode D4 to help main converter.This provides extra protection for switch, rectifying part backhaul pulse before main converter starts.The noise that the high-frequency energy result becomes heat or distributes.

Figure 30 B is the schematic diagram of another spacing branch circuit SNBB of the present invention.Spacing branch circuit SNBB comprises resistance R 310 and capacitor C 821.

Figure 30 B	Table
Figure 30 B	Table	Element	Value/parts number
????R821	????470pF	Element	Value/parts number
????R821	????470pF	????R310	12 ohm

Node SNL2 is connected to resistance R 821 by capacitor C 821, arrives node SNOUT again.Node SNOUT is connected to the negative electrode of backhaul diode.Node SNL2 is connected to the drain electrode end of outside output switch and the backhaul side of inductive load.The spacing ＂ action of ＂ makes the rising of backhaul slack-off, thereby starts the time of conducting for the external rectifier diode.

Figure 31 is the schematic diagram of spacing branch circuit of the present invention.Spacing branch circuit SNA comprises resistance R 810 and R811 and capacitor C 820 and C821.

Figure 31	Table
Figure 31	Table	Element	Value/parts number

????R810	????500pF
????R810	????500pF	????C811	????330pF
????C820	12 ohm	????C811	????330pF
????C820	12 ohm	????C821	10 ohm

Node SNA1 is connected to series resistance R810, arrives capacitor C 820 again, and node SNA2 arrives capacitor C 821 and series resistance R811 then, arrives node SNA3 again.Node SNA1 is connected to external magnetic element centre tap.Node SNA2 is connected to the drain electrode end of outside output switch and the backhaul side of inductive load.Node SNA3 is connected to the source terminal of outside output switch.Resistance R 810 and C820 attempt the absorption portion backhaul to reduce the voltage transient on switch.The part backhaul turns back to ground by C821.This branch circuit uses with outside its mirror image SNA (Figure 31) that recommends switch ends.The spacing ＂ action of ＂ makes the rising of backhaul slack-off, thereby has given the external rectifier diode D8 of Figure 25 or 25A and the time that D9 starts conducting.This circuit has been managed high frequency backhaul pulse effectively.

Figure 32 is the schematic diagram of spacing branch circuit of the present invention.Spacing branch circuit SNB comprises resistance R 820 and R821 and capacitor C 840 and C841.

Figure 32	Table
Figure 32	Table	Element	Value/parts number
????C840	????500pF	Element	Value/parts number
????C840	????500pF	????C841	????330pF
????R820	12 ohm	????C841	????330pF
????R820	12 ohm	????R821	10 ohm

Node SNB1 is connected to series resistance R820, arrives capacitor C 820 again, node SNA2, and capacitor C 841 and series resistance R821 arrive node SNB3 again.Node SNB1 is connected to external magnetic element centre tap.Node SNB2 is connected to the drain electrode end of outside output switch and the backhaul side of inductive load.Node SNB3 is connected to the source terminal of outside output switch.Resistance R 820 and C840 attempt the backhaul of absorption portion high frequency to reduce the voltage transient on switch.C841 and the backhaul of R821 returning part are to ground." spacing " action makes the rising of backhaul slack-off, thereby has given the external rectifier diode D8 of Figure 25 or 25A and the time that D9 starts conducting.This circuit has been managed high frequency backhaul pulse effectively.

Figure 33 is PWM of the present invention (pulse width modulator) and FM (frequency modulator) branch circuit.Branch circuit PWFM comprises resistance R 401, R402, R403 and R404 capacitor C 401, C402, C403, C404, C405 and C406, controller IC U400 and diode D401.

Figure 33	Table
Figure 33	Table	Element	Value/parts number
????R404	50k ohm	Element	Value/parts number
????R404	50k ohm	????C406	????100uf
????C401	????0.22uF	????C406	????100uf
????C401	????0.22uF	????C403	????0.01uF
????C405	????2200pF	????C403	????0.01uF
????C405	????2200pF	????C404	????470pF
????C402	????0.22uF	????C404	????470pF
????C402	????0.22uF	????R403	50k ohm
????D401	RLS139 (the low leakage)	????R403	50k ohm
????D401	RLS139 (the low leakage)	????R401	2.2M ohm
????R402	150k ohm	????R401	2.2M ohm
????R402	150k ohm	????U400	????MIC38C43

Control element U400 is connected to has the following circuit that is connected in series: to feeding back pin PW1 then to the moving contact of adjustable resistance R404, arrive return node PWFM0 from pin one again.Resistance R 404 can replace with two fixing resistance.Capacitor C 403 is connected to pin one from pin two.Capacitor C 403 is used to the output of filtering error amplifier.The first half of resistance R 404 is connected to 5.0 volts of inner reference voltages of node R EF1 pin 8.Inner 5.0 volts of reference voltage U400 pins 8 or node R EF1 are connected to the first half of resistance R 403 and are connected to return node PWFM0 by capacitor C 402.Reference voltage provides current to the external feedback network.The moving contact connected node FM1 of R403 arrives return node PWFM0 by R402 to pin 3 with by C404 to pin 4.Resistance R 403 can replace with two fixing resistance.Pulsewidth timing capacitor C404 connects pin 3 to return node PWFM0.Low leakage diode D401 anode is connected to pin 3, and negative electrode is to output pin and node CLK.Resistance R 404 is set the specified pulsewidth of output pin 6 node CLK.Pulsewidth can be adjusted to 95% from 0 (shutoff).Resistance R 403 and C404 determine the nominal operation frequency.Along with apply 20 volts of voltages between node PWFM+ and PWFM0, controller U400 produces 5.0 inner reference voltages, to pin 7 node R EF1.Output pin 6 node CLK are set to high about 20 volts (seeing Figure 34 oscillogram track G6 section 60).C404 begins the charging by R401, arrives comparator level (seeing Figure 34 oscillogram track G1 section 61) up to the voltage on the C404 of pin 3, and replacement pin 6 is low (seeing Figure 34 oscillogram track G6 section 62).Capacitor C 404 is by D401 repid discharge (seeing Figure 34 oscillogram track G1 section 63).At pin 6 is between low period, and pin remains on PWFM0 node above 0.6 volt (seeing Figure 34 oscillogram track G1 section 64).At the rising edge of pin 6, capacitor C 405 beginning quick charges are up to the inner comparator level (seeing Figure 34 oscillogram track G4 section 65) of voltage arrival of pin 4.Comparator triggers inner transistor with the C404 that discharges apace (seeing Figure 34 oscillogram track G4 section 66).Along with output pin 6 is set to high level, repeat this cycle.Be applied to the output voltage of the external feedback current following reality of U400 pin one and node PW1 (seeing Figure 34 oscillogram track G1 section).Oscillogram track G1 section 67 (Figure 34) are the time periods of output switch conduction stored energy in NSME.Oscillogram track G1 section 68 (Figure 34) are that the output switch is turned off the time period that is sent to storage capacitance in NSME with the energy that allows to store.Applying external current source or feedback network makes pulsewidth modulated to pin one or node PW1.Remove electric current from PW1 and reduced comparator level, make comparator trigger when lower voltage is arranged on C404, reduced pulsewidth.Introducing electric current has increased pulsewidth to node PW1, from the rated value to the maximum 95%.Resistance R 404 and C404 determine specified pulsewidth.This design makes CLK output by pulse-width modulation.Applying the external feedback network makes frequency modulated to pin 4 or node FW1.From FW1 remove electric current slack-off the charging of C405.The longer charging interval reduces frequency from specified setting.This structure makes CLK output by frequency modulation(FM).When using with resonant controller, R403 and C405 determine rated frequency, are generally equal to tank circuit resonance frequency.External feedback is configured to reduce frequency to zero frequency " shutoff " from specified (maximum output).When being used as pulse width controller, specified 90% the maximum pulse width that is set to about, feedback has reduced pulsewidth.Branch circuit PWFM can be frequency and pulse-width modulation simultaneously.This structure and mode of operation are that this invention is unique.Feedback to the output of error amplifier is unique mode of operation of control element U400.Branch circuit PWFM has big dynamic range concurrently, accurate control and response fast.

Figure 34 is the oscillogram track of PWFM (Figure 33) controller under PWM mode.

Figure 35 is the oscillogram track of TCTP (Fig. 8) controlled resonant converter primary coil voltage.Figure 35 is the oscillogram track of the voltage on capacitor C 10 (Fig. 8).In this embodiment, power supply VBAT only is 18 volts.

The inductance 203uH of primary coil winding 100 (Figure 18) is realized by 55 circles on 26u, 2.28 ounces of KoolMu magnetic elements 101.Secondary coil winding 103 (Figure 18) is 15 circles on the iron core 101.5.5 tile load is connected to winding 103.NSME primary coil winding 100 (Figure 18) produces the driving voltage of 229 volts of peak values, and is bigger more than ten times than VBAT.Tank circuit converter TCTP and TCSSC (Fig. 7) have utilized the desired characteristics of unsaturation magnet, to produce big magnetic flux biasing.Useful big magnetic flux can be gathered in the crops useful power by increasing " magnetic flux net (flux nets) " winding to magnetic element.

Figure 36 is 18 volts of DC power controlling branch circuit REG that regulate.Branch circuit REG comprises resistance R 517, adjuster Q514 and capacitor C 514, C515, C516, C518, and C517.

Figure 36	Table
Figure 36	Table	Element	Value/parts number
????Q514	????LM7818	Element	Value/parts number
????Q514	????LM7818	????C515	????0.1uF
????C517	????0.1uF	????C515	????0.1uF
????C517	????0.1uF	????C514	????10?uF
????C518	????10?uF	????C514	????10?uF

Pin REG0 is connected to the external power source loop.Node R EG0 also is a return line, and it is connected to Q514 pin two and capacitor C 518, C514, C515, and C517.Resistance R 517 is connected to pin one (input) node and the input pin RIN+ of voltage regulator Q514.Voltage regulator Q514 pin 3 is the DC output that 18vdc regulates, and is connected to capacitor C 515, C514 and output pin 18V.Capacitor C 515, C517 is the solid dielectric type, is used to the filtering high-frequency fluctuation and prevents the Q514 vibration.Branch circuit REG provides the power of adjusting to control circuit and output switch buffering AMP (Figure 29).

Figure 37 is the schematic diagram of the high-end switch buck converter branch circuit HSBK of non-isolation.Figure 37 is the high-end switch buck converter branch circuit HSBK of non-isolation.This converter topology structure comprises the efficient voltage reducing level of non-isolation, and its power that adjusting is provided is to effectively recommending isolation level.Branch circuit HSBK comprises diode D8, capacitor C 8, FET transistor Q31, branch circuit TCTP (Fig. 8), branch circuit BL1 (Figure 18 B), branch circuit IFB (Figure 40 B), branch circuit AMP (Figure 29) and branch circuit PWFM (Figure 33).

Figure 37	Table
Figure 37	Table	Element	Value/parts number
????C68	????250uf	Element	Value/parts number
????C68	????250uf	????D68	????MUR820
????Q31	????IRF540N	????D68	????MUR820

External power source VBAT is connected to pin DCIN+ and DCIN-.Pin DCIN+ is connected to transistor Q31 source electrode, branch circuit PWFM pin PWFM0, branch circuit AMP pin GA0 and branch circuit IFB pin FBE, branch circuit TCTP pin DCIN+ and B-.18 volts of outputs regulating are connected to branch circuit AMP pin GA+ and branch circuit PWFM pin PWFM+ from branch circuit TCTP pin B+.With respect to the source electrode of Q31, this provides positive gate-drive.Power supply VBAT loop is connected to pin DCIN-, branch circuit TCTP pin DCIN-, diode D68 anode, capacitor C 68, RLOAD, branch circuit IFB pin OUT-, output pin B-and ground/return node GND.Branch circuit PWFM is designed to from 0 to 90% scalable pulsewidth work, and maximum pulse width occurs in when not having feedback current to pin PW1.Increase the output voltage that feedback current has reduced pulsewidth and converter HSBK.Branch circuit PWFM clock/PWM output pin CLK is connected to the input pin GA1 of buffering branch circuit AMP.The output of branch circuit AMP pin GA2 is connected to the gate pole of Q31.The leakage level of Q31 is connected to the negative electrode of branch circuit BL1 pin P1B and D68.The pin P1A of branch circuit BL1 is connected to capacitor C 8, branch circuit IFB pin OUT-and RLOAD.If branch circuit PWFM pin CLK is a high level, then cushion the gate pole of AMP output pin GA2 charging transistor switch Q31.Switch Q31 conducting, by NSME BL1 from power supply VBAT charging capacitor C68 and among BL1 stored energy.Feedback output pin FBC is connected to branch circuit PWFM pulse-width regulated pin PW1 from branch circuit IFB.Along with output voltage arrives the level that designs, branch circuit IFB is from the PW1 transfer current, and order PWFM is to reduce the ON time of pulsewidth or signal CLK.Arrive the pulsewidth of order at branch circuit PWFM after, PWFM becomes low level with output pin CLK, turn-offs Q31, stops electric current and enters BL1.The energy of being stored is released to the diode D68 of present forward bias, charging capacitor C68 from NSME BL1.By the ON time of modulation switch Q31, the voltage that converter " step-down " is applied is adjusted to more low-voltage effectively.The voltage that is conditioned Node B-and the B+ two ends between.Branch circuit IFB provides the feedback voltage of isolation to branch circuit PWFM.Export when branch circuit IFB detects converter (Node B+and B-) when being the voltage of design, by the more electric current of phototransistor conducting.The current order PWFM of the decline of PM1 is narrower pulsewidth, thereby reduces the converter output voltage.If the feedback signal order PWFM of IFB is minimum output, then the gate-drive of switch Q31 is removed, and stops all step-down activities, and capacitor C 68 is discharged by RLOAD.Input current from VBAT is sinusoidal wave, makes converter very quiet.Because this switch Q31 is not exposed to big current spike common in the saturation magnets of prior art, thereby switch has been applied less stress, thereby increase MTBF.In the topological structure of this converter, branch circuit HSBK has utilized the desired characteristics of NSME.

Figure 38 is the schematic diagram of the two-stage low-end switch buck converter branch circuit LSBKPP of isolation.This converter topology structure comprises high efficiency low-end switch buck stages, and its power that adjusting is provided is to effectively recommending isolation level.Effectively the centre tap full-wave rectifier provides rectification.Branch circuit LSBKPP comprises diode D46, capacitor C 46, FET transistor Q141, branch circuit REG (Figure 36), branch circuit OUTB (Figure 25 A), branch circuit BL1 (Figure 18 B), branch circuit TCTP (Fig. 8), branch circuit IFB (Figure 40 B), branch circuit AMP (Figure 29), branch circuit DCAC1 and branch circuit PWFM (Figure 33).

Figure 38	Table
Figure 38	Table	Element	Value/parts number
????C46	????250uf	Element	Value/parts number
????C46	????250uf	????D46	????MUR820
????Q141	????IRF540N	????D46	????MUR820

External power source VBAT is connected to pin DCIN+ and DCIN-.Be connected to branch circuit REG pin RIN+ from pin DCIN+, D46 negative electrode, capacitor C 46, branch circuit TCTP (Fig. 8) pin DCIN+ and branch circuit DCAC1 pin DC+.Voltage regulator branch circuit REG output pin+18V is connected to branch circuit AMP pin GA+ and branch circuit PWFM pin PWFM+.Branch circuit REG provides the low-voltage power of adjusting to controller and main switch buffering.The VBAT negative pole is connected to pin DCIN-and ground return node GND.Node GND is connected to branch circuit PWFM pin PWFM0, branch circuit AMP pin GA0, Q141 source electrode, branch circuit IFB pin FBE, branch circuit REG pin REG0 and branch circuit TCTP pin DCIN-.Branch circuit PWFM (Figure 33) is designed to variable impulse width work.Rated frequency is between 20-600khz, and PWFM is constructed to maximum pulse width 90% (maximum reducing voltage) corresponding to the feedback current that does not have from branch circuit IFB.Increase feedback current and reduced the Q111 ON time, reduced to the voltage of push-pull cascade with from the output of converter LSBKPP.Branch circuit PWFM clock output pin CLK is connected to the input pin GA1 of buffering branch circuit AMP (Figure 29).The output of switch acceleration buffering branch circuit AMP pin GA2 is connected to the gate pole of Q141.18 volts of power supplys of the isolation of drift are connected to branch circuit DCAC1 pin P18V from branch circuit TCTP pin B+.The leakage level of Q141 is connected to the anode of branch circuit BL1 pin P1A and D46.The return line of branch circuit DCAC1 pin DC-is connected to branch circuit BL1 pin P1B, branch circuit TCTP pin B-and C46.If branch circuit PWFM pin CLK is a high level, then cushion the gate pole of AMP output pin GA2 charging transistor switch Q141.Switch Q141 conducting, reversed biased diodes D46; Capacitor C 46 begins to charge from power supply VBAT by NSME BL1.In Q141 conduction period, energy is stored among the NSME branch circuit BL1.Charging C46 provide power push-pull converter level DCAC1 to the end.The output of output rectifier branch circuit OUTB is connected to feedback branch circuit I FB output pin FBC, is connected to branch circuit PWFM pulse-width regulated pin PW1 from branch circuit IFB.Branch circuit IFB is from the PW1 transfer current, and order PWFM is to reduce the ON time of pulsewidth or signal CLK.Arrive the pulsewidth of order at branch circuit PWFM after, PFFM becomes low level with CLK, turn-offs Q141, stops electric current and enters BL1.Energy is released to the backhaul diode D46 of present forward bias, charging capacitor C46 from NSME BL1.By the ON time of modulation switch Q141, converter voltage is conditioned.The voltage that is conditioned is between C46 node DC+ and GND two ends.Provide energy to recommend DC-AC converter branch circuit DCAC1 (Fig. 2) to the constant frequency of isolation.Branch circuit DCAC1 provides the effective conversion of the step-down voltage of adjusting to higher or lower voltage, and its ratio is set by magnetic element winding strands circuit PPT1 (Figure 19).The centre tap of recommending the output magnet is connected to branch circuit OUTB pin OUT-, RLOAD, branch circuit IFB pin OUT-and pin OUT-, the return line and the feedback network of formation load.The output of branch circuit DCAC1 pin ACH is connected to branch circuit OUTB pin C7B.The output of branch circuit DCAC1 pin ACL is connected to branch circuit OUTB pin C8B.Branch circuit OUTB provides the rectification of the AC power that is produced by branch circuit DCAC1.Because unsaturation magnet converter very, OUTB only requires minimum filtering.This has also reduced cost and has improved efficient, owing to be minimized to the loss of filter part.Branch circuit IFB provides the feedback current of isolation to branch circuit PWFM.When branch circuit IFB detect converter output (node OUT+ and OUT-) greater than design/during the voltage of expectation, electric current is shifted from node PM1.The current order PWFM of the decline of PM1 is narrower pulsewidth, thereby has increased antihypertensive effect, has reduced first order converter output voltage.If the feedback signal order PWFM of IFB is minimum output, then the gate-drive of switch Q141 is removed, and stops all step-down activities, capacitor discharge C46.Input current from the charging C46 of VBAT is sinusoidal wave, makes converter very quiet.In addition, switch Q141 can not be exposed to potential destructive current spike.Switch is applied less stress, thereby increased MTBF.In the topological structure of this converter, branch circuit LSBKPP has utilized the desired characteristics of NSME.Regulate NSME BL1 (Figure 18 B) and set the amount of the step-down voltage that can be used for recommending at last isolation level.Realized bigger efficient with higher voltage.Last output voltage is set by the turn ratio of recommending element PPT1 (Figure 19).Converter LSBKPP provides the efficient transformation of the output of isolating from high-voltage power supply to high electric current.

Figure 39 is the schematic diagram of the two-stage low-end switch buck converter branch circuit LSBKPPBR of isolation.This converter topology structure comprises the high efficiency low-end switch buck stages of non-isolation, and its power that adjusting is provided is to effectively recommending isolation level.Full wave bridge rectifier provides rectification.Branch circuit LSBKPPBR comprises diode D6, capacitor C 6, FET transistor Q111, branch circuit REG (Figure 36), branch circuit OUTBB (Figure 25 B), branch circuit BL1 (Figure 18 B), branch circuit TCTP (Fig. 8), branch circuit IFB (Figure 40 B), branch circuit AMP (Figure 29), branch circuit DCAC1 (Fig. 2) and branch circuit PWFM (Figure 33).

Figure 39	Table
Figure 39	Table	Element	Value/parts number
????C6	????250uf	Element	Value/parts number
????C6	????250uf	????D6	????MUR820
????Q111	????IRFP	????D6	????MUR820

External power source VBAT is connected to pin DCIN+ and DCIN-.Be connected to branch circuit REG pin RIN+ from pin DCIN+, D6 negative electrode, capacitor C 6, branch circuit TCTP (Fig. 8) pin DCIN+ and branch circuit DCAC1 pin DC+.Voltage regulator branch circuit REG output pin+18V is connected to branch circuit AMP pin GA+ and branch circuit PWFM pin PWFM+.Branch circuit REG provides the low-voltage power of adjusting to controller and main switch buffering.The VBAT negative pole is connected to pin DCIN-, is connected to branch circuit PWFM pin PWFM0, branch circuit AMP pin GA0, Q111 source electrode, branch circuit IFB pin FBE, branch circuit REG pin REG0, branch circuit TCTP pin DCIN-.Branch circuit PWFM (Figure 33) is designed to variable impulse width work.Rated frequency is between 20-600Khz, and PWFM is constructed to maximum pulse width 90% (maximum reducing voltage) corresponding to the feedback current that does not have from branch circuit IFB.Increase feedback current and reduced the Q111 ON time, reduced to the voltage of push-pull cascade with from the output of converter LSBKPPBR.Branch circuit PWFM clock output pin CLK is connected to the input pin GA1 of buffering branch circuit AMP (Figure 29).The output of switch acceleration buffering branch circuit AMP pin GA2 is connected to the gate pole of Q111.18 volts of power of the isolation of drift are connected to branch circuit DCAC1 pin P18V from branch circuit TCTP pin B+.The leakage level of Q111 is connected to the anode of branch circuit BL1 pin P1A and D6.The return line of branch circuit DCAC1 pin DC-is connected to branch circuit BL1 pin P1B, branch circuit TCTP pin B-and C6.If branch circuit PWFM pin CLK is a high level, then cushion the gate pole of AMP output pin GA2 charging transistor switch Q111.Switch Q111 conducting, reversed biased diodes D6; Capacitor C 6 begins to charge from power supply VBAT by NSMEBL1.In Q111 conduction period, energy is stored among the NSME branch circuit BL1.Charging provides power push-pull converter level DCAC1 to the end to C6.The output of output rectifier branch circuit OUTBB is connected to feedback branch circuit I FB output pin FBC, is connected to branch circuit PWFM pulse-width regulated pin PW1 from branch circuit IFB.Branch circuit IFB is from the PW1 transfer current, and order PWFM is to reduce the ON time of pulsewidth or signal CLK.Arrive the pulsewidth of order at branch circuit PWFM after, PFFM becomes low level with CLK, turn-offs Q111, stops electric current and enters BL1.Energy is released to the backhaul diode D6 of present forward bias, charging capacitor C6 from NSME BL1.By the ON time of modulation switch Q111, converter voltage is conditioned.The voltage that is conditioned is between C6 node DC+ and DC-two ends.Provide energy to recommend DC-AC converter branch circuit DCAC1 (Fig. 2) to the constant frequency of isolation.Branch circuit DCAC1 provides the effective conversion of the step-down voltage of adjusting to higher or lower voltage, and its ratio is set by magnetic element winding strands circuit PPT1 (Figure 19).The return node of branch circuit OUTBB pin OUT-is connected to RLOAD, branch circuit DCAC1 pin AC0, branch circuit IFB pin OUT-and pin OUT-.Node OUT-is the return line and the feedback network of load.The output of branch circuit DCAC1 pin ACH is connected to branch circuit OUTBB pin C7B.The output of branch circuit DCAC1 pin ACL is connected to branch circuit OUTBB pin C8B.Branch circuit OUTBB provides the rectification of the AC power that is produced by branch circuit DCAC1.Because disclosed unsaturation magnet converter has minimum output pulsation, OUTBB only requires less filtering.This has also reduced cost and has improved efficient, owing to be minimized to the loss of filter part.Branch circuit IFB provides the feedback current of isolation to branch circuit PWFM.The collector electrode output of IFB pin FBC is connected to PWFM pin PW1.When branch circuit IFB detect converter output (node OUT+ and OUT-) greater than design/during the voltage of expectation, electric current is shifted from node PM1.The current order PWFM of the decline of PM1 is narrower pulsewidth, thereby has increased antihypertensive effect, has reduced first order converter output voltage.If the feedback signal order PWFM of IFB is minimum output, then the gate-drive of switch Q111 is removed, and stops all step-down activities, capacitor discharge C6.Because NSME is unsaturated, common in the prior art destructive noise current spikes can not occur.Input current from the charging C6 of VBAT is sinusoidal wave, makes converter very quiet.In addition, switch Q111 can not be exposed to potential destructive current spike.Switch is applied less stress, thereby increased MTBF.In the topological structure of this converter, branch circuit LSBKPPBR has utilized the desired characteristics of NSME.Regulate NSME BL1 (Figure 18 B) and set the amount of the step-down voltage that can be used for recommending at last isolation level.Realized bigger efficient with higher voltage.Last output voltage is set by the turn ratio of recommending element PPT1 (Figure 19).Converter LSBKPPBR provides the effective conversion from high voltage source, such as the High Power Factor AC-DC converter of branch circuit ACDCPF (Fig. 4).

Figure 40 is the schematic diagram of the overvoltage feedback network branch circuit IPFFB of isolation of the present invention.Branch circuit IPFFB comprises resistance R 926, R927, R928, R929 and R930, capacitor C 927, Zener diode D928 and D903, transistor Q915 and optical isolator U903.

Figure 40	Table
Figure 40	Table	Element	Value/parts number
????U903	????NEC2501	Element	Value/parts number
????U903	????NEC2501	????Q915	????FZT705?CT
????D903	????ML5248B(18V)	????Q915	????FZT705?CT
????D903	????ML5248B(18V)	????D928	????1SMB5956BT3(200V)
????R926	20k ohm	????D928	????1SMB5956BT3(200V)
????R926	20k ohm	????R927	10k ohm
????R928	10k ohm	????R927	10k ohm
????R928	10k ohm	????R929	10k ohm
????R930	20k ohm	????R929	10k ohm

Node PF+ is connected to the negative electrode of D903 and the anode of optical isolator U903 by resistance R 927.The negative electrode of diode D903 is connected to pin PF+.Resistance R 928 is connected to the base stage of Q915 from the anode of D928.Capacitor C 927 is connected in parallel with Zener diode D903.The maximum base current of resistance R 928 restrictions.Resistance R 929 is connected between the base stage and emitter of Q915.Resistance R 929 is used to from base bleeder current common too much Zener leakage current high voltage diode.The negative electrode of two hectovolt Zener diode D928 is connected to pin PF+.The anode of D928 is connected to R930 and R928.Resistance R 930 provides a path for the leakage current of 200 volts of Zener D928.The maximum current that resistance R 926 enters restriction the light-emitting diode of U903 inside is about 10mA.Maximum Zener current when resistance R 927 is set in about 200 volts maximum booster voltage is 20mA.When the voltage between node PF+ and the PF-during less than 200 volts Zener voltage, transistor Q915 is biased to shutoff.Transistor is in and turn-offs or nonconducting state, does not have electric current to be injected into U903 LED.Inner phototransistor also is in nonconducting state.The external control branch circuit that is connected is not changed its output by order.Along with 200 volts or bigger voltage are applied between node PF+ and the PF-, back-biased Zener diode D928 injection current is to the base stage of Q915.Resistance R 927, capacitor C 927 and diode D903 provide the collector electrode of 18 volts of voltages to Q915.Transistor Q915 conducting, electric current enters U903 LED, injects base current to the U903 phototransistor.Modulation LED electric current is reflected at the variableimpedance between FBC and the FBE.This phototransistor can be connected as variable current source or impedance.This branch circuit detects excessive booster voltage, and feeds back to control branch circuit (seeing PFA (Figure 23), PFB (Figure 24) or (PWFM Figure 33)) apace, has automatically reduced booster voltage.

Figure 40 A is the schematic diagram of the output voltage feedback branch circuit FBA that boosts of non-isolation.Branch circuit FBA comprises resistance R 1120, R1121, R1122, R1123 and R1124.

Figure 40 A	Table
Figure 40 A	Table	Element	Value/parts number
????R1123	499k ohm	Element	Value/parts number
????R1123	499k ohm	????R1124	499k ohm
????R1122	6.65k ohm	????R1124	499k ohm
????R1122	6.65k ohm	????R1121	499k ohm
????R1120	1MEG ohm	????R1121	499k ohm

Input node PF+ is connected to series resistance [R1123+R1124], arrives parallel resistance [R20 ‖ R21 ‖ R22] then, arrives return node BR-again.Resistance R 1120, R1121, R1122, the selection of R1123 and R1124 value makes that specified input voltage is 385 volts, the output feedback voltage is 3.85.(see oscillogram G1, Figure 34) resistance R 1120, R1121, and R1122, R1123 and R1124 are illustrated with surface installation structure, but they can be combined into two through hole resistances.Feedback output node PF1 is connected to the node PF1 of branch circuit PFA (Figure 23) or PFB (Figure 24).Return the BR-that pin BR-is connected to PFA (Figure 23) or PFB (Figure 24).Node FBE and FBC also can be connected between control branch circuit PWFM (Figure 33) node FM1 pin PWFM0 or the PW1 pin PWFM0.

Figure 40 B is the schematic diagram of the low-voltage feedback network branch circuit FBA of isolation of the present invention.Branch circuit IFB comprises resistance R 900, R901 and R902, Zener diode D900, Darlington transistor Q900 and optical isolator U900.

Figure 40 B	Table
Figure 40 B	Table	Element	Value/parts number
????U900	????NEC2501	Element	Value/parts number
????U900	????NEC2501	????Q900	????FZT705?CT
????D900	????IN5261BDICT	????Q900	????FZT705?CT
????D900	????IN5261BDICT	????R900	1k ohm

????R902	4k ohm
????R902	4k ohm	????R901	40k ohm

Node OUT+ connects the negative electrode of D900 to R901.The anode of diode D900 is connected to series resistance R900, arrives the base stage of Darlington transistor Q900 again.Resistance R 902 is connected to emitter from the Q900 base stage.Resistance R 901 is connected to the anode of optical isolator U900 LED (light-emitting diode), and negative electrode is connected to the Q900 collector electrode.The emitter of Q900 is the return current path, is connected to pin/node OUT-.The maximum current that resistance R 901 restrictions enter the light-emitting diode of U900 inside is about 20mA.Resistance R 902 is from some Zener leakage currents of base bleeder current.Zener diode voltage is selected to set the converter output voltage, and general value can be 48 volts.Zener voltage is that the output of last expectation deducts two Base-Emitter node voltages and falls (1.4V).In case the OUT+ node arrives Zener voltage, then little base current biasing Q900 enters conducting state, the LED of " connection " optical isolator U900 inside.Resistance R 900 has limited the maximum base current of Q900.Select resistance R 900 and R901 so that with the Darlington transistor Q900 collector current of setovering of the rated voltage between node OUT+ and the OUT-.Voltage between OUT+ and OUT-changes light modulated isolator U900 LED electric current, thereby changes the base current of the phototransistor of U900 inside.The phototransistor emitter is node FBE, and collector electrode is node FBC.Modulation LED electric current is reflected at the variableimpedance between FBC and the FBE.This phototransistor can be connected as variable current source or impedance.When with control branch circuit PFA (Figure 23), PFB (Figure 24) or (PWFM Figure 33) are when using together, phototransistor is connected as electric current and shunts.Applying higher voltage at OUT+ and OUT-node has increased the feedback shunt current, and order control branch circuit (seeing PFA (Figure 23) or PFB (Figure 24) or PWFM (Figure 33)) reduces pulsewidth or frequency.Because the quick response of the transducer-level of gain that Darlington transistor is very high and inside, IFB has realized high-speed feedback, has obtained fluctuation minimizing and excellent load regulation initiatively.

Figure 40 C is the schematic diagram of the overvoltage feedback network branch circuit IOVFB of another PFC isolation.Branch circuit IOVFB comprises resistance R 917, R938, R939 and R940, diode D911, Darlington transistor Q914 and optical isolator U905.

Figure 40 C	Table
Figure 40 C	Table	Element	Value/parts number
????U905	????NEC2501	Element	Value/parts number
????U905	????NEC2501	????Q914	????FZT705CT
????R938	160k ohm	????Q914	????FZT705CT

????R939	70k ohm
????R939	70k ohm	????D911	????1N5261BOTCT
????R940	50k ohm	????D911	????1N5261BOTCT
????R940	50k ohm	????R917	40k ohm

PFC is connected to R917 in the output of pin PF+, is connected to the collector electrode of Q914 then.Resistance R 917 is set the maximum current of U905 light-emitting diode.Resistance R 938 is connected to Zener diode D911 negative electrode and R938 from return node PF+.Resistance R 939 is connected to Zener diode D911 negative electrode and R938 from return node PF-.The anode of D911 is connected to the moving contact arm of adjustable resistance R940.The branch road of R940 is connected to the base stage of transistor Q914, and another is connected to R939 and U905LED anode and R939.The emitter of Q914 is connected to the anode of U904.Before transistor Q914 was biased conducting and provides current to U905 LED, adjustable resistance R940 set maximum or tripping voltage.The phototransistor emitter is node FBE, and collector electrode is node FBC.Modulation LED electric current is reflected at the variableimpedance between FBC and the FBE.This phototransistor is connected to shunting usually, so that control element is minimum output.This branch circuit detects booster voltage and feeds back to PFC, and wherein excessive booster voltage makes PFC automatically reduce booster voltage.

Figure 40 D is the schematic diagram of the output voltage feedback branch circuit FBD that boosts of another non-isolation.Branch circuit FBD comprises resistance R 1120, R1121, R1122, R1123 and R1124.

Figure 40 D	Table
Figure 40 D	Table	Element	Value/parts number
????R1123，R1124	499k ohm	Element	Value/parts number
????R1123，R1124	499k ohm	????R1122	1.00k ohm
????R1121	1.00k ohm	????R1122	1.00k ohm
????R1121	1.00k ohm	????R1123	66.5k ohm
????R1120	6.65k ohm	????R1123	66.5k ohm

Input node PF+ is connected to series resistance [R1123+R1124], is connected to parallel resistance [R1122 ‖ R1121].The other end of [R1122 ‖ R1121] is connected to the moving contact arm of R1121, arrives return node BR-by [R1123 ‖ R1120].The selection of resistance value makes that specified input voltage is 385 volts.Resistance R 1120-R1124 illustrates with surface installation structure, but they also can be combined into other connection in series-parallel combinations to form other equivalent electric circuit.Feedback output node PF1 is connected to the node PF1 of branch circuit PFA (Figure 23) or PFB (Figure 24).Return the BR-that pin BR-is connected to PFA (Figure 23) or PFB (Figure 24).Node FBE and FBC also can be connected between the node FM1 pin PWFM0 or PW1 pin PWFM0 of control branch circuit PWFM (Figure 33).Component values is selected so that 15 volts of adjustable ranges to be provided.

Figure 41 is the schematic diagram of another low-voltage feedback network branch circuit FBI.Branch circuit FBI comprises resistance R 81, R82 and R83, Zener diode D80, NPN transistor Q80 and capacitor C 80.

Figure 41	Table
Figure 41	Table	Element	Value/parts number
????R81	1k ohm	Element	Value/parts number
????R81	1k ohm	????D80	Zener voltage=(output of expectation-0.65V)
????Q80	????BCX70KCT	????D80	Zener voltage=(output of expectation-0.65V)
????Q80	????BCX70KCT	????C80	????1000pf
????R82	1k ohm	????C80	????1000pf
????R82	1k ohm	????R83	715k ohm

Node OUT+ connects the negative electrode of D80.The anode of diode D80 is connected to OUT-by resistance R 83 and is connected to the base stage of transistor Q80 by resistance R 82.Capacitor C 80 is connected to pin OUT-from base stage.Capacitor C 80 bypass high-frequency noises are to OUT-.Resistance R 81 is connected to node OUT-from the emitter of Q80.Resistance R 81 increases local negative feedback to reduce the influence that transistor gain changes.The collector electrode of Q80 is connected to pin FBC.The return current node is connected to pin FBE and OUT-.The maximum base current of resistance R 82 restrictions is with protection Q80.Resistance R 83 is from some Zener leakage currents of base bleeder current.Zener diode voltage is selected to set the converter output voltage, and general value can be 48 volts.Zener voltage is that the output of last expectation deducts a Base-Emitter node voltage and falls (0.65 volt).When OUT+ node arrival nominal level, back-biased Zener begins conducting, injects little base current to Q80.Bias transistor enters conducting state.Voltage between OUT+ and OUT-changes modulation Q80 collector current.In normal work period, Zener diode is biased in its knee point (knee), thereby the little change of voltage causes bigger collector current to change.As branch circuit FBI and control branch circuit PFA (Figure 23), PFB (Figure 24) or (Figure 33) when using together, transistor is connected as electric current and shunts.The higher voltage that is applied to OUT+ and OUT-node has increased the feedback shunt current, and order control branch circuit (sees that PFA (Figure 23) or PFB (Figure 24) or PWFM (Figure 33) reduce pulsewidth or frequency.Branch circuit FBI provides high-speed feedback and gains to the fluctuation parts.Along with the response fast of the transducer-level of inside, obtained that fluctuation initiatively reduces and excellent load regulation.

Figure 41 A is the schematic diagram of another overvoltage feedback network branch circuit FB2.Branch circuit FB2 comprises resistance R 419, R418, R414 and R410, Zener diode D410 and NPN transistor Q414 and Q413.

Figure 41 A	Table
Figure 41 A	Table	Element	Value/parts number
????R414	22k ohm	Element	Value/parts number
????R414	22k ohm	????D410	????BZX84C10
????Q413-Q414	????FMMT2222ACT	????D410	????BZX84C10
????Q413-Q414	????FMMT2222ACT	????R418	25.5K ohm
????R410，R419	499k ohm	????R418	25.5K ohm

Node PF+ is connected to series resistance R410+R419+R418 and arrives common port or ground then, forms voltage divider.The node of R418 and R419 is connected to the collector electrode of Q414 and the negative electrode of Zener diode D410.Diode D410 anode is connected to the base stage of transistor Q414.The emitter of Q414 is connected to the base stage of Q413 and passes through resistance R 414 ground connection.The emitter of Q413 also is connected to ground.The collector electrode of Q413 is connected to node PF2, to be connected to adjuster branch circuit PFB pin two.Select resistance R 410, R419, R418 and D410, forward bias transistor Q413 and Q414 when surpassing 450VDC with respect to common port with convenient node PF+.This has regulated the process of boosting, and goes down up to fault state, rapid and reliable another kind of the adjusting is provided, thereby has satisfied the UL test request.

Figure 42 is the schematic diagram of overvoltage protection embodiment branch circuit OVP1 of the present invention.Branch circuit OVP1 comprises SCR (thyristor) SCR1200, resistance R 1200, capacitor C 1200 and Zener diode D1200, D1202 and D1203.

Figure .42	Table
Figure .42	Table	Element	Value/parts number
????SCR1200	????MCR265-10	Element	Value/parts number
????SCR1200	????MCR265-10	????D1203	????BZT03-C200(200V)
????D1202	????BZT03-C200(200V)	????D1203	????BZT03-C200(200V)
????D1202	????BZT03-C200(200V)	????D1200	????IN4753(5.1V)

????C1200	????220?pf
????C1200	????220?pf	????R1200	10,0k ohm

Input pin PF+ is connected to the negative electrode of Zener diode D1203, and the anode of D1203 is connected to series zener diode [D1202+D1200], arrives the gate pole of SCR1200 then.The acoustic noise reducing network of [R1200 ‖ C1200] is connected to return node BR-from the SCRSCR1200 gate pole.Diode D1102 and D1103 are 200 volts; D1101 is 5.1 volts of types, and total Zener voltage is set the trip-point of OVP at 405 volts.By selecting other Zener diode combinations can realize other tripping voltages.Capacitor C 1200 and R1200 prevent leakage current and the transition OVP that trips by accident.If in the very high or feedback loop (Figure 40 A, 40B, 40C or 40) of AC line voltage distribution unit failure is arranged, then booster voltage can be increased to the level to output switch or the danger of output storage capacitance apace.When the output booster voltage of node PF+ rises to 405V when above, Zener diode D1203, D1202 and the little electric current of D1200 conducting are to the gate pole of SCR1200, conducting SCR1200.Conducting SCR1200 makes and be provided with low impedance path in the AC circuit by rectifier branch circuit BR (Figure 22).Must select SCR1200 and bridge rectifier diode to surpass 100 amperes circuital current in short-term, open up to the input fuse to bear.Thereby limit the level of output voltage that boost apace for safety.Under normal AC line condition, this circuit should not worked.By changing Zener voltage, this branch circuit also is applicable to the output on rectifier, overpressure conditions do not occur with the protection load.Branch circuit OVP1 turn-offs converter and need not to open line fuse.Branch circuit OVP can be used in combination with OVP1 (Figure 42 A), as the fail-safe reserve of critical loads.

Figure 42 A is the schematic diagram of overvoltage protection embodiment branch circuit OVP2 of the present invention.Branch circuit OVP2 comprises SCR (thyristor) SCR1101 and SCR1100, resistance R 1101 and R1102, capacitor C 1100 and C1101 and Zener diode D1100, D1102 and D1103.

Figure 42 A	Table
Figure 42 A	Table	Element	Value/parts number
????SCR1101	????S101E(Teccor)	Element	Value/parts number
????SCR1101	????S101E(Teccor)	????SCR1100	????S601E(Teccor)
????D1103	????BZT03-C200(200V)	????SCR1100	????S601E(Teccor)
????D1103	????BZT03-C200(200V)	????D1102	????BZT03-C200(200V)
????D1100	????IN4753(5.1V)	????D1102	????BZT03-C200(200V)
????D1100	????IN4753(5.1V)	????R1100	????16000
????R1101	5.1k ohm	????R1100	????16000

????R1102	5.1k ohm
????R1102	5.1k ohm	????C1100	????1200?pf
????C1101	????1200?pf	????C1100	????1200?pf

The anode of SCR1101 is node/pin CP18V+, and it is connected to external control DC source.Return node BR-is connected to SCR1101 negative electrode and capacitor C 1100.Input node PF+ is connected to negative electrode and the series resistance R1100 of Zener diode D1103, arrives the anode of SCRSCR1102 then.The anode of D1103 is connected to the negative electrode of D1102.The anode of D1102 is connected to the negative electrode of D1100.The negative electrode of SCR1100 is connected to the gate pole of SCR1101.The anode of D1103 is connected to series zener diode [D1102+D1100], arrives capacitor C 1100 then, arrives return node BR-then.Electric capacity [C1200 ‖ R1200] prevents leakage current and the transition OVP that trips by accident.If in the very high or feedback loop (IPFFB Figure 40 A, FBA Figure 40 B, IFB Figure 40 C or FBI Figure 41) of AC line voltage distribution unit failure is arranged, then booster voltage can be increased to the level to output switch or the danger of output storage capacitance apace.When the output booster voltage of node PF+ rises to 405V when above, Zener diode D1103, D1102 and the little electric current of D1100 conducting latch the SCR1101 conducting to the gate pole of SCR1101.Resistance R 1100 provides the holding current of SCR1101.Conducting SCR1101 provides gate current to SCR1100, and resistance R 1100 and R1101 have limited gate current and provide holding current to SCR1100.Along with gate current arrives SCR1100, SCR is switched on, and the low impedance path from node CP18V+ to BR-is provided.This action cushions the power transfer of regulating and/or PWM controller PFA (Figure 23) or PWFM (Figure 33) and/or buffering AMP (Figure 29) to main switch, thereby turn-offs main switch.Converter is maintained at off state, can not keep the holding current of SCR1101 by R1100 up to booster voltage PF+.Usually power must shift from system, with replacement SCR1101.The minimum holding current of SCR1101 is 5-10mA normally.The action of OVP1 limits the level of output voltage for safety that boost apace.Under normal AC line condition, this circuit should not worked.By changing Zener voltage, this branch circuit also is applicable to the output on rectifier, overpressure conditions do not occur with the protection load.Branch circuit OVP1 suitably turn-offs converter, requires manual intervention with this fault that resets.

Figure 42 B is the schematic diagram of the output overvoltage feedback network branch circuit OVP2 of isolation.Branch circuit OVP2 comprises resistance R 970, R971, and R972, capacitor C 970, Zener diode D970, SCRSCR970, Darlington transistor Q970 and optical isolator U970.

Figure 42 B	Table
Figure 42 B	Table	Element	Value/parts number

????D970	????1N5261BOTCT
????D970	????1N5261BOTCT	????U970	????NEC2501
????Q970	????FZT705CT	????U970	????NEC2501
????Q970	????FZT705CT	????R970	160k ohm
????R971	10k ohm	????R970	160k ohm
????R971	10k ohm	????R972	22k ohm
????C970	????200pf	????R972	22k ohm

Converter is connected to the negative electrode of R972 and Zener diode D970 in the output of pin OUT+.The anode of D970 is connected to series resistance R970, arrives the base stage of Q970 then.Resistance R 970 is set the maximum base current of Q970.Resistance R 971 is connected between the anode and return node OUT-of D970.The anode of light-emitting diode U970 is connected to resistance R 972, arrives OUT+ then.The negative electrode of U970 LED is connected to the Q980 collector electrode.The emitter of Q980 is connected to return node OUT-.Before transistor Q970 was biased conducting and provides current to U970 LED, Zener diode D960 set maximum or tripping voltage.Applying voltage greater than the Zener voltage of D970 makes and injects little base current to Q970.Transistor Q970 connects the LED of the inside of U970, makes phototransistor be in conducting state, Low ESR between pin OVC and the OVE.By making pin PPEN is high level, stops output stage, and outside push-pull driver branch circuit PPG (Figure 43) is turn-offed immediately.Branch circuit OVP2 detects output voltage and feeds back to apace and recommends PFC.Wherein excessive booster voltage makes PFC automatically reduce booster voltage.

Figure 42 C is the schematic diagram of output overvoltage short-circuit protection circuit (crowbar) the network branches circuit OVP3 of isolation.Branch circuit OVP3 comprises resistance R 980, R981, R982, R983, R984 and R985, capacitor C 980, C981 and C982 Zener diode D980, SCR SCR980 and SCR981, Darlington transistor Q980 and optical isolator U980.

Figure 42 C	Table
Figure 42 C	Table	Element	Value/parts number
????D980	????1N5261BOTCT	Element	Value/parts number
????D980	????1N5261BOTCT	????SR980	????S601E(Teccor)
????U980	????NEC2501	????SR980	????S601E(Teccor)
????U980	????NEC2501	????Q980	????FZT705?CT

????R980	160k ohm
????R980	160k ohm	????R981	10k ohm
????R982	22k ohm	????R981	10k ohm
????R982	22k ohm	????R983	51k ohm
????R984	1200 ohm	????R983	51k ohm
????R984	1200 ohm	????R985	510 ohm
????C980	????200pf	????R985	510 ohm
????C980	????200pf	????C981	????1200pf
????C982	????1200pf	????C981	????1200pf

Detect converter output in pin OUT+ reference point to pin OUT-.Pin OUT+ is connected to resistance R 982, arrives the negative electrode of Zener diode D980 again.The anode of D980 is connected to series resistance R980, arrives the base stage of Q980 then.Resistance R 980 is restricted to the base current of Q980.Resistance R 981 is connected between the anode of D980 and the return node OUT-so that the diode leakage current path to be provided.The anode of light-emitting diode U980 is connected to OUT+ by resistance R 982.The negative electrode of U980 LED is connected to the Q980 collector electrode.The emitter of Q980 is connected to return node OUT-.Before transistor Q980 was biased conducting and provides current to U980 LED, Zener diode D980 set maximum or tripping voltage.Applying voltage greater than the Zener voltage of D980 makes and injects little base current to Q980.The emitter of optical isolator U980 is connected to the gate pole of SCR981, arrives return node BR-by [R984 ‖ C982].Transistor Q980 connects the LED of the inside of U980, makes phototransistor be in conducting state, provides gate current to SCR981 from the 18 volts of power supplys in outside that are connected to pin CP18V+.Network [R984 ‖ C982] prevents the false triggering of SCR981.The negative electrode of SCR981 is connected to the gate pole of SCR980 and is connected to and returns BR-by [R985 ‖ C981].Along with SCR981 connects, gate current is provided to low-voltage SCR980.High voltage boosts to export and is connected to pin PF+, and resistance R 983 provides holding current to SCR981, keeps the SCR980 conducting.SCR980 is selected for low electric current and the maximum booster voltage that can stop at PF+ of keeping.The SRC980 anode is connected to pin CP18V+.The SRC980 negative electrode is connected to and returns pin BR-.SCR980 clamper LVPS CP (Figure 26) or CPA (Figure 27).Along with low power supply compacting, the gate-drive of main switch is under an embargo, and turn-offs converter.Along with main switch Q1 (Fig. 1,3,4) is turned off, support that capacitor C 17 is charged to AC circuit peak value.Along with pin PF+ keeps near the circuit peak value, SCR981 will keep the SCR981 conducting, be transferred to converter up to the AC line power.As OVP (Figure 42), branch circuit OVP3 detects illegal output voltage and the device that stops transformation apace, thereby protection load and converter do not produce destructive electric current.

Figure 43 is pusb pull oscilator branch circuit PPG.Figure 43 is a pusb pull oscilator branch circuit of the present invention.This execution mode uses Motorola MC33025 pulse width modulator IC to drive push-pull output stage with clocking.Branch circuit PPG comprises biphase oscillation device U14, resistance R 126, R130, R131, R132, R133, R134, R135, R136 and R137, capacitor C 143, C136, C139, C140, C141 and C142.

Figure 43	Table
Figure 43	Table	Element	Value/parts number
????U14	????MC33025	Element	Value/parts number
????U14	????MC33025	????R126	12k ohm
????R130	10 ohm	????R126	12k ohm
????R130	10 ohm	????R131	10 ohm
????R132	47k ohm	????R131	10 ohm
????R132	47k ohm	????R133	10k ohm
????R134	100k ohm	????R133	10k ohm
????R134	100k ohm	????R135	15k ohm
????R136	1.5M ohm	????R135	15k ohm
????R136	1.5M ohm	????R137	15k ohm
????C136	????0.22uf	????R137	15k ohm
????C136	????0.22uf	????C139	????0.22uf
????C140	????0.22uf	????C139	????0.22uf
????C140	????0.22uf	????C141	????0.01uf
????C142	????0.001uf	????C141	????0.01uf
????C142	????0.001uf	????C143	????.33uf

This execution mode uses Motorola MC33025 pulse width modulator IC to drive push-pull cascade with clocking.But any non-overlapped two frequency generators that fix can be used.The pin one of U14 is connected to [capacitor C 143 ‖ resistance R 132], arrives pin 3 then.5.1 volts of references that resistance R 134 connects the inside of U14 pin one 6 output to pin one.The resistance R 135 of connecting with R137 to return node PPG0, forms voltage divider from 5.1 volts of reference voltages; The center is connected to the U14 pin two, makes pin two be in 2.55 volts.Resistance R 126 is connected to return node PPG0 from U14 pin 5.Resistance R 133 is connected to return node PPG0 from the U14 pin one.Timing capacitor C142 is connected to return node PPG0 from U14 pin 6 and 7.Resistance R 126 and capacitor C 142 are set the operating frequency of inner oscillator.Timing resistor can be used JFET, MOSFET, and transistor, or similarly switching device replaces so that variable frequency work to be provided.Transistorized leakage level can be connected to pin 5.Power supply can be connected to return node PPG0.Variable frequency command voltage/electric current is applied between gate pole and the source electrode.Capacitor C 141 is connected to return node PPG0 from U14 pin 8.Capacitor C 136 is connected to return node PPG0 from U14 pin one 6.Capacitor C 140 is connected to return node PPG0 from U14 pin one 5.Capacitor C 139 is connected to return node PPG0 from U14 pin one 3.Resistance R 136 is connected to return node PPG0 from U14 pin 9.U14 pin one 0 and 12 is connected to return node PPG0.External power is connected to node/pin PPG+, is connected on the pin one 5 of PWM (pulse width modulator) IC U14 by the resistance R 130 that is connected to 18 volts of control power supplys.Resistance R 131 is connected to pin one 3 and the PPG+ of U14, provides power to recommend (totem-poll) output stage.The power return line is connected to node PPG0.ICU14 is designed to work in the constant frequency of about 20-600Khz, has the fixing conduction ratio of 35-49.9%.Resistance R 135, R137, R133 make U14 be operated in maximum pulse width.Produce the non-overlapped square wave of two-phase and be sent in the drawings the acceleration buffering AMP that describes in 29 at pin one 1 node PH2 and pin one 4 node PH1.Structure two-phase generator is in order to prevent invalid iron core biasing of overlapping drive signal meeting and the problem of giving the excessive electric current of switch.Branch circuit PPG offers the driving of recommending switch and has effectively utilized NSME.

Figure 44 pours in (inrush) limiter branch circuit SS1.Branch circuit SS1 comprises diode D447, resistance R 441, R442, R443, R444, R445 and R446, transistor Q446 and capacitor C 449, C442, and C448.

Figure 44	Table
Figure 44	Table	Element	Value/parts number
????D447	????1N5246	Element	Value/parts number
????D447	????1N5246	????R441，R442	300k ohm
????R443-445	100 ohm	????R441，R442	300k ohm
????R443-445	100 ohm	????C448	????0.33uF

????C442	????330?uF?450V
????C442	????330?uF?450V	????C449	????0.1uF
????R446	4.7M ohm	????C449	????0.1uF

Node PF+ is connected to electrode input end and the series resistance R441+R442 of storage capacitance C442.Series resistance R441 and R442 can replace with discrete component.Series resistance R441 and R442 are in parallel with C442, for C442 provides safe discharge path.The leakage level of transistor Q446 is connected to negative pole end and the R442 of C442.The source electrode of Q446 is connected to return node BR-.Resistance [R443 ‖ R445] is connected in parallel with Q446 source electrode and drain electrode end.Resistance R 443, R444 and R445 can replace with discrete component.Resistance R 446 is connected to the line node BR+ of rectification and the gate pole of Q446.The negative electrode of Zener diode D447 is connected the gate pole of Q446.The anode of Zener diode D447 is connected to the source electrode of Q446.It is about 16 volts that diode D447 limits maximum gate voltage.Shunt capacitance C448 and C449 are connected in parallel to D447.Resistance R 446 and electric capacity [C448 ‖ C449] provide the time delay of (0.05 to 0.2 second) when powering on.This delay scope is for instance, but not is used for restriction.Transistor Q446 is in high impedance status when powering on.Thereby capacitor C 442 charging currents are limited by [R443 ‖ R444 ‖ R445].With reference to oscillogram G44 interval 441 (Figure 44 A), 441 is time periods of not conducting of transistor at interval, thereby [R443 ‖ R444 ‖ R445] provides charge path, thus the restriction inrush current.Significantly reduced in power up stress to line filter and rectifier means.The exponentially that can see inrush current in interval 441 reduces.Because series resistance, the soft start of oscillogram GPF+-interval 444 (Figure 44 A) also indicates bigger AC fluctuation voltage.Because electric capacity [C448 ‖ C449] is by the R446 charging, the gate voltage of Q446 increases, " conducting " Q446.(Figure 44 A) transistor Q446 conducting in interval 442.This action is marked as the minimizing of the increase of charging current 446 and AC fluctuation in interval 445.Similarly, along with the C442 charging, can see the index decreased of charging current in 442 processes.Transistor Q446 keeps conducting state, shifts from converter up to power.Booster converter is started working in interval 447.The restriction that pours in is in addition provided by branch circuit SST (Figure 33 B), at interval 448 this gently produce output voltage.Increased to load in full by line current in 443 processes and to have illustrated.The present invention selects to provide the limit interval that pours in that can set with simple resistance/capacitance values.Thereby realized other novel soft start booster circuit SST.In starting at interval, kept High Power Factor simultaneously.Suitable startup has significantly reduced the externally stress of fuse and the parts in big current path.Increased MBTF with minimum optional feature.This invention also allows " heat " to insert the unit of a plurality of parallel connections, is used for higher power and/or redundancy.Pour in limiter SS1 simply from main DC bus isolated storage electric capacity.By this way, " heat exchange " big interference of generation on AC or main outside DC bus.Few load (the master less load) sharing method of the main road of the uniqueness of telling about among the 4A allows any amount of unit to be connected in parallel in the drawings, to satisfy high power and reliability.

Figure 44 A is the oscillogram of line current and output voltage in the course of work of branch circuit SS1 (Figure 44).

Figure 45 is the schematic diagram that starts branch circuit FS1 fast.Start branch circuit FS1 fast and comprise diode D452 and D451, resistance R 451, R452, R453, R454, R455 and R456, transistor Q450 and Q451 and capacitor C 452, C453, and C451.

Figure 45	Table
Figure 45	Table	Element	Value/parts number
????D451	Rlz5.1 Zener 5.1V	Element	Value/parts number
????D451	Rlz5.1 Zener 5.1V	????D452	Rlz24 Zener 24V
????R451	1 M ohm	????D452	Rlz24 Zener 24V
????R451	1 M ohm	????R452-453，R454	2.2 M ohm
????R455	4.3k ohm	????R452-453，R454	2.2 M ohm
????R455	4.3k ohm	????R456	499k ohm
????C453	????0.01?uF	????R456	499k ohm
????C453	????0.01?uF	????C451	????4.7?uF
????C452	????1.0?uF	????C451	????4.7?uF
????C452	????1.0?uF	????Q450	????FMMT2222
????Q451	????STD3NC80	????Q450	????FMMT2222

Resistance R 451 connected node VCC arrive and capacitor C 451 parallel resistor R454 then to the base stage of transistor Q450, arrive ground or BR-again.The anode of Zener diode D451 and D452 is connected to ground.The negative electrode of Zener diode D451 is connected to the emitter of Q450.The negative electrode of Zener diode D452 is connected to the collector electrode of Q450, the gate pole of Q451 and by resistance R 452+R453 to node PF+.Resistance R 455 is connected to the leakage level of Q451 from PF+.Resistance R 456 from BR-() source electrode that is connected to Q451 forms node TP15, by the gate pole of capacitor C 452 to Q451.Capacitor C 453 is connected between node TP17 and the TP45.Along with AC power is applied to node PF+, voltage increases sharply.Because VCC is that zero (nothing is boosted) transistor Q450 is not in conducting state.The resistance R 452+R453 C452 that charges, forward bias Q451.Oscillogram G45 (Figure 45 A) is the figure of the source electrode gate voltage of Q451.In the G451 of interval, transistor Q451 conducting provides power to VCC by R455 from PF+.The interval G452 of oscillogram GVCC shows the fast rise of VCC.Thereby full power is provided to main switch Q1 switch buffering AMP (Figure 29) and power factor controller PFA, PFB or PFB1 immediately.Along with VCC 12.6V or more than, booster converter is started working gradually.This can be found out from little AC voltage occurs at TP45 among interval G454 (Figure 45 A).Transistor Q451 continues to provide power to VCC, and simultaneously at soft start at interval among the G455, boost operations is fiercely moved (ramp up).In case the soft start stage finishes, the AC of rectification provides power to VCC through D261 and D260.Capacitor C 453 coupling HF boost energy are with the C451 that charges apace.R451 provide continuous bias current to C451 to prevent activation as VCC Q451 during greater than 5 volts.Forward bias Q450 has reduced the gate voltage on the Q451.Behind G456, transistor Q451 gate pole is reverse biased to source electrode, turn-offs fast to start.If the overpressure conditions of elevated track situation occurs or unexpected deduct load, the activity of boosting will stop at TP45 and shift AC voltage.Remove this base drive and reduced electric current in the collector circuit of G450, thereby allow Q451 when VCC drops to below 5 volts, to become forward bias.Whenever drop to below 5 volts at C451, power will be provided to VCC.This new-type circuit provides a kind of method of uniqueness, so as before the work of boosting begins, to provide apace power controlling and excessive overvoltage or non-loaded during keep power controlling.Thereby guarantee in the four corner of load and fault condition under reliably fast start and recover.

Figure 45 A is the oscillogram of branch circuit FS1 in branch circuit SS1 (Figure 45) course of work.

Figure 46 is transient protective branch circuit TRN, comprises diode D460-D462, bridge rectifier 461 and capacitor C 260, C2.

Figure 46	Table
Figure 46	Table	Element	Value/parts number
????D460-D462	????S3M?3A/1000V	Element	Value/parts number
????D460-D462	????S3M?3A/1000V	????C260	????330?ufd?450V
????461	Bridge 15A/800V	????C260	????330?ufd?450V
????461	Bridge 15A/800V	????C2	????1.5?ufd?630V

Line voltage distribution AC adds that high voltage source HV1 is connected to the AC-voltage end of bridge rectifier 461.The DC+ of bridge end is connected to anode and the inductance L 63 in parallel with capacitor C 20 of Node B R+ and transient protective diode D460-D462.Therefore inductance L 63 and capacitor C 20 do not influence the effect of transient protection circuit in fact, only for complete and illustrate.The anode of D460-D462 is connected to boost output and storage capacitance C2 and C260.18A has in the drawings told about the work of booster circuit in 30,29 and 24.Three transient protective diodes are illustrational, and unrestricted.The number of device is the function of selected device forward current capacity and possible peak current.Capacitor C 260 is polarization electrolysis devices, is for instance, but not is used for restriction.Solid dielectric electric capacity can be added C260 to reduce impedance and to improve high frequency performance by parallel connection.In normal work period, transient protective diode D460-D462 is because the action of boosting is back-biased.Along with the high voltage HV1 of any polarity is applied to the AC circuit, the rectification situation appears at Node B R+, also shown in the oscillogram G463 (Figure 46 B).If transient voltage surpasses the voltage of C2, then the D460-D462 forward bias transmits energy to storage capacitance C260.Prior art Transient Method energy drain is to gap or MOV types of devices.The problem of these devices is limited life cycles, excessive leakage current or catastrophic fault.If select suitable device, very large transition can be absorbed, and can not surpass the rated value of device.Thereby component count and cost with minimum have guaranteed high reliability.The present invention goes for other the off-line converter with storage capacitance, and it is maintained on the peak line voltage of (boosting) rectification.This topological structure will be worked with reference to converter with plus or minus.

Figure 46 A is transient protective branch circuit TRNX, comprises resistance R 468, bridge rectifier BR468 and capacitor C 468.

Figure 46 A	Table
Figure 46 A	Table	Element	Value/parts number
????R458	1M ohm	Element	Value/parts number
????R458	1M ohm	????R468	????220?ufd?450V
????BR468	????35A/600V	????R468	????220?ufd?450V

Circuit AC adds that high voltage source HV1 is connected to the AC-voltage end of bridge rectifier BR468.The output cathode end of bridge be connected to Node B R+ and with C468 parallel resistor R486.The output negative pole end of bridge be connected to Node B R-and with C468 parallel resistor R486.Branch circuit TRNX can be connected in parallel with any AC that needs transient protective or DC load.Along with power is applied to bridge, capacitor C 468 is charged to crest voltage.Resistance R 468 is emitted small amount of charge from C468.In case charging is finished, only Xiao Liang power is dissipated by R468.In the type of the transient event of in figure G462 (Figure 46 B), describing.High voltage transient will be imported into capacitor C 468.The high forward current capacity of the low internal driving of C468 and BR468 has limited the amplitude of transition by transient energy is imported C468.Produced voltage oscillogram response G461.Can add other electric capacity, be used for higher voltage, electric current and/or lower impedance.

Figure 46 B is the oscillogram of converter work in the high voltage transient process.Oscillogram G461 is output voltage PF+.Oscillogram G462 is the AC line voltage distribution BR+ of rectification.Oscillogram G463 is the gate voltage of main boosted switch Q1.

Figure 47 is the signal graph of power supply automatic load calibration.For telling about the present invention, for clear, Figure 47 only shows necessary element.Be provided to 473 power and enter regulator stage 470.Regulator stage 470 can be such as series via, and variable reactance (AC) boosts, any kind of step-down and shunting.These just illustrate, and unrestricted.Adjuster 470 only needs to control pin 479, and itself and control signal are modulated output N470 pro rata.Power or load detecting element 471 provide output signal 472, and it is with to send to the power of load 476 by 470 proportional.The load detecting element can be hall effect sensor (electric current), has the resistance of differential amplifier, watt transducer or current transformer.These just illustrate, and unrestricted.Requirement is that signal 472 is proportional with the power that is sent.For particular sensor, simple inverting amplifier (not shown) can be required for the polarity of level shift, buffering or reversed phase signal 472.For instance, provide this signal from the sampling VCC that magnetic element PFT1A (Fig. 4 A) draws that boosts through CP1 (Figure 26 A).Signal 472 (VCC) is as the function of load, shown in 26B figure.The resistance R 476 that is connected between node 472 and 477 with adding realizes the load calibration.Resistance R 345 in Fig. 4 A is the corresponding components among the converter ACDCPF1.Power signal 472 is converted into electric current and injects summation node 477 by R476.Summation node 477 from R473 accept from transducer T473 with the proportional electric current of converter temperature.By this way, the converter load balancing is based on power and/or temperature.Simple resistance ratios layout the load balancing ratio, kept the converter adjusting simultaneously.Voltage and summed current on the resistance R 479 are proportional, and this voltage are applied to the backward end of comparator 478.Reference voltage V470 is applied to the non-inverting input of comparator 478.Comparator produces command signal 479 with modulation adjuster 470.The action of comparator is in order to remain on the voltage difference of the minimum between the comparator input terminal.External power source 475 and 475N are connected to output node N474 and common common load 476.This structure allows many converters to be connected in parallel.Signal 472 (VCC) is as the function of load, 26B as shown in the figure.The load calibration realizes by the adding that is connected the resistance R 476 between node 472 and 477.Thereby regulate output voltage lower along with load increases, this individual part makes N power supply parallel operation, and does not have common principal and subordinate's connection and circuit.By this way, thus the converter of underloading has increased output voltage accepts more load.Similarly, the converter of heavy duty will reduce voltage, automatically load be unloaded converter or power supply to other.By this way, the converter of any number can be connected in parallel, and is used for high power or superfluous application.In the master/slave structure of prior art, the loss of master unit is catastrophic.In the present invention, removing of a fault or a unit makes remaining unit increase output to absorb extra load.Optionally temperature sensor T473 makes load balancing except being subjected to load effect, also is subjected to the power supply Temperature Influence.Thereby be minimized in the thermal gradient in the individual unit.This automatic load calibration steps can be applied to AC or DC power supply.Parts select to have set rated operational voltage and load balancing ratio.This method allows dynamic load sharing, and does not have the minimizing of common principal and subordinate's connection, cost problem and reliability.This method allows the mixing of power supply type, and promptly automatic load is shared, and only requires their output voltage equal substantially.Thereby excellent adjusting is provided, simply has been provided with and structure, " heat exchange " ability and from the automatic recovery of fault state.

Figure 47 A is another signal graph of power supply automatic load calibration.For telling about the present invention, for clear, Figure 47 A only shows necessary element.Be provided to 473 power and enter regulator stage 470.Regulator stage 471 can be such as series via, and variable reactance (AC) boosts, any kind of step-down and shunting.These just illustrate, and unrestricted.Adjuster 470 only needs to control pin 479, and itself and control signal are modulated output N470 pro rata.Power or load detecting element 471 provide output signal 472, and it is with to send to the power of load 476 by 470 proportional.The load detecting element can be hall effect sensor (electric current), has the resistance of differential amplifier, watt transducer or current transformer.These just illustrate, and unrestricted.Requirement is that signal 472 is proportional with the power that is sent.For particular sensor, simple inverting amplifier A470 can be required for the polarity of level shift, buffering or reversed phase signal 472.For instance, provide this signal from the sampling VCC that magnetic element PFT1A (Fig. 4 A) draws that boosts through CP1 (Figure 26 A).Signal 472 (VCC) is as the function of load, shown in 26B figure.Amplifier A470, resistance R 478 and R475 provide signals reverse with correction signal polarity.The resistance R 476 that is connected with adding between the output and 477 of node A470 realizes the automatic load calibration.Resistance R 345 in Fig. 4 A is the corresponding components among the converter ACDCPF1.Power signal 472 is converted into electric current and injects datum node N476 by R476.Reference voltage V470 is by the non-inverting input of R470 to comparator 478.Thereby modulation reference voltage effectively is to reduce the converter output voltage and to have higher power.Summation node 477 accepts proportional electric current with converter output N474 from R475, thereby makes the converter load balancing be based on power.Simple resistance ratios layout load balancing ratio and output voltage, kept the converter adjusting simultaneously.Voltage and summed current on the resistance R 479 are proportional, and this voltage are applied to the backward end of comparator 478.Comparator produces command signal 479 with modulation adjuster 470.The action of comparator is in order to remain on the voltage difference of the minimum between the comparator input terminal.Other external power source 475 and 475N are connected to output node N474, and towards common load 476.This structure allows many converters to be connected in parallel.Thereby regulate output voltage lower along with load increases, this individual part makes N power supply parallel operation, and does not have common principal and subordinate's connection and circuit.By this way, thus the converter of underloading has increased output voltage accepts more load.Similarly, the converter of heavy duty will reduce voltage, automatically load be unloaded converter or power supply to other.By this way, the converter of any number can be connected in parallel, and is used for high power or redundant application.In the master/slave structure of prior art, the loss of master unit is catastrophic.In the present invention, removing of a fault or a unit makes remaining unit increase output to absorb extra load.This automatic load calibration steps can be applied to AC or DC power supply.Parts select to have set rated operational voltage and load balancing ratio.This method allows dynamic load sharing, and does not have the minimizing of common principal and subordinate's connection, cost problem and reliability.This method also allows the mixing of power supply type, and promptly automatic load is shared and the constant voltage type.And only require for giving their output voltages alone of fixed load equal substantially.This provides excellent adjusting, and " heat exchange " ability and from the automatic recovery of fault state simply is set and structure.

Although described the present invention with reference to its preferred embodiment,, can carry out various corrections and change, its result still falls within the scope of the present invention.For any restriction of specific embodiment disclosed herein, not inventor's purpose, there is not such restriction to be pushed out yet.

Claims

1. converter comprises:

The backhaul converter of correcting power factors has a feedback circuit;

Push-pull converter has a conduction ratio;

The backhaul converter of described correcting power factors provides a variable signal to described push-pull converter;

The full-wave rectification output circuit;

Described push-pull converter provides one to have the signal of an operating frequency to described full-wave rectification output circuit; With

Described push-pull converter comprises that also one is operated in the magnetic element (NSME) in unsaturation zone.

2. converter as claimed in claim 1, wherein said NSME also comprises low magnetic permeability.

3. converter as claimed in claim 2, wherein said NSME also comprise being 85% iron by weight, the mixture of 6% aluminium and 9% silicon, thus for providing wide thermal technology, described magnetic element makes scope.

4. converter as claimed in claim 1, wherein said low magnetic permeability has 1 to 500 scope.

5. converter as claimed in claim 4, wherein said NSME are the aeromagnetic elements.

6. converter as claimed in claim 1, wherein said NSME also comprise a BH curve characteristic, scope from B=1 to 10000 gaussian sum H=1 to 100 oersteds.

7. converter as claimed in claim 1 also comprises a frequency modulation circuit, with the output signal of the described NSME of optimization.

8. converter as claimed in claim 7, wherein said push-pull converter also comprises a pair of side controller, has a fixed pulse width.

9. converter as claimed in claim 7, wherein said push-pull converter also comprises a pair of side controller, has a variable frequency.

10. converter as claimed in claim 7, wherein said push-pull converter also comprises a pair of side controller, has the conduction ratio of the fixed pulse width of scope from 40% to 60%.

11. converter as claimed in claim 7, wherein said push-pull converter also comprises a pair of side controller, has an optimized circuit, is used to change the relation between pulsewidth and the frequency.

12. converter as claimed in claim 1, wherein said conduction ratio are constants.

13. converter as claimed in claim 1, wherein said conduction ratio are variablees.

14. converter as claimed in claim 10, wherein said conduction ratio is 50.

15. converter as claimed in claim 1 also comprises a control circuit, biasing and control frequency and pulsewidth with monitoring NSME are used for optimization NSME efficient.

16. converter as claimed in claim 1, wherein said NSME selects from the group that comprises following element:

The aeromagnetic element;

Molybdenum permalloy powder (MPP) magnetic element;

High magnetic flux MPP magnetic element;

The powder magnetic element;

Space ferrimagnetism element is arranged;

Band is around magnetic element;

Die-cut magnetic element;

The magnetic element of lamination; With

Unbodied magnetic element.

17. a converter comprises:

The backhaul converter of correcting power factors has a feedback circuit;

Push-pull converter has a conduction ratio;

The full-wave rectification output circuit;

Described backhaul converter comprises that also one is operated in the magnetic element (NSME) in unsaturation zone.

18. converter as claimed in claim 17, wherein said NSME also comprises low magnetic permeability.

It is 85% iron by weight that 19. converter as claimed in claim 18, wherein said NSME also comprise, the mixture of 6% aluminium and 9% silicon, thus for providing wide thermal technology, described magnetic element makes scope.

20. converter as claimed in claim 17, wherein said low magnetic permeability has 1 to 500 scope.

21. converter as claimed in claim 20, wherein said NSME are the aeromagnetic elements.

22. converter as claimed in claim 17, wherein said NSME also comprise a BH curve characteristic, scope from B=1 to 10000 gaussian sum H=1 to 100 oersteds.

23. converter as claimed in claim 17 also comprises a frequency modulation circuit, with the output signal of the described NSME of optimization.

24. converter as claimed in claim 17, wherein said push-pull converter also comprises a pair of side controller, has a fixed pulse width.

25. converter as claimed in claim 17, wherein said push-pull converter also comprises a pair of side controller, has a variable frequency.

26. converter as claimed in claim 17, wherein said push-pull converter also comprises a pair of side controller, has the conduction ratio of the fixed pulse width of scope from 40% to 60%.

27. converter as claimed in claim 17, wherein said push-pull converter also comprises a pair of side controller, has an optimized circuit, is used to change the relation between pulsewidth and the frequency.

28. converter as claimed in claim 17, wherein said conduction ratio are constants.

29. converter as claimed in claim 17, wherein said conduction ratio are variablees.

30. converter as claimed in claim 17, wherein said conduction ratio is 50.

31. converter as claimed in claim 17 also comprises a control circuit, biasing and control frequency and pulsewidth with monitoring NSME are used for optimization NSME efficient.

32. converter as claimed in claim 17, wherein said NSME selects from the group that comprises following element:

The aeromagnetic element;

Molybdenum permalloy powder (MPP) magnetic element;

High magnetic flux MPP magnetic element;

The powder magnetic element;

Space ferrimagnetism element is arranged;

Band is around magnetic element;

Die-cut magnetic element;

The magnetic element of lamination; With

Unbodied magnetic element.

33. a converter comprises:

The backhaul converter of correcting power factors has a feedback circuit;

Push-pull converter has a conduction ratio;

The full-wave rectification output circuit;

Described push-pull converter provides one to have the signal of an operating frequency to described full-wave rectification output circuit;

Described push-pull converter comprises that also one is operated in the magnetic element (NSME) in unsaturation zone; With

Described backhaul converter comprises that also one second is operated in the magnetic element (NSME) in unsaturation zone.

34. converter as claimed in claim 33, wherein said NSME also comprises low magnetic permeability.

It is 85% iron by weight that 35. converter as claimed in claim 34, wherein said NSME also comprise, the mixture of 6% aluminium and 9% silicon, thus for providing wide thermal technology, described magnetic element makes scope.

36. converter as claimed in claim 33, wherein said low magnetic permeability has 1 to 500 scope.

37. converter as claimed in claim 34, wherein said NSME are the aeromagnetic elements.

38. converter as claimed in claim 33, wherein said NSME also comprise a BH curve characteristic, scope from B=1 to 10000 gaussian sum H=1 to 100 oersteds.

39. converter as claimed in claim 33 also comprises a frequency modulation circuit, with the output signal of the described NSME of optimization.

40. converter as claimed in claim 33, wherein said push-pull converter also comprises a pair of side controller, has a fixed pulse width.

41. converter as claimed in claim 33, wherein said push-pull converter also comprises a pair of side controller, has a variable frequency.

42. converter as claimed in claim 33, wherein said push-pull converter also comprises a pair of side controller, has the conduction ratio of the fixed pulse width of scope from 40% to 60%.

43. converter as claimed in claim 33, wherein said push-pull converter also comprises a pair of side controller, has an optimized circuit, is used to change the relation between pulsewidth and the frequency.

44. converter as claimed in claim 33, wherein said conduction ratio are constants.

45. converter as claimed in claim 33, wherein said conduction ratio are variablees.

46. converter as claimed in claim 33, wherein said conduction ratio is 50.

47. converter as claimed in claim 33 also comprises a control circuit, biasing and control frequency and pulsewidth with monitoring NSME are used for optimization NSME efficient.

48. converter as claimed in claim 33, wherein said NSME selects from the group that comprises following element:

The aeromagnetic element;

Molybdenum permalloy powder (MPP) magnetic element;

High magnetic flux MPP magnetic element;

The powder magnetic element;

Space ferrimagnetism element is arranged;

Band is around magnetic element;

Die-cut magnetic element;

The magnetic element of lamination; With

Unbodied magnetic element.

49. converter as claimed in claim 1 also comprises:

Voltage regulator has an electric capacity, and described electric capacity has the voltage that draws from the pulsewidth of described backhaul converter;

Described electric capacity is with reference to the booster voltage on the described magnetic element;

Described electric capacity has a reference voltage, is used for the primary side of described push-pull converter; With

Described voltage follow load.

50. converter as claimed in claim 1 also comprises power factor controlling (PFC) circuit, wherein said pfc circuit also comprises:

A FET and buffer with switching mode;

Described buffer comprises that the 2nd FET and Darlington transistor are right, thereby is turned back to the gate pole of a described FET at period 1 one voltage, second round one voltage removed from the gate pole of a described FET.

51. a transformer that is used for supply convertor comprises:

Iron core;

The primary coil winding is wound on the described iron core;

At least one secondary coil winding is wound on the described iron core; With

Wherein said iron core comprises a magnetic element (NSME) that is operated in the unsaturation zone at least.

52. an AC-DC converter comprises:

Input is used to receive a variable dc voltage;

The magnetic element branch circuit is electrically connected to described input;

At least one recommends the output switch, is electrically connected to described magnetic element branch circuit; With

Wherein said magnetic element branch circuit comprises a magnetic element (NSME) that is operated in the unsaturation zone at least.

53. a converter comprises:

The backhaul converter of correcting power factors has a feedback circuit;

Forward direction step-down (buck) converter;

The backhaul converter of described correcting power factors provides an output signal to described forward direction buck converter;

Push-pull converter has a conduction ratio;

Described forward direction buck converter provides a voltage that is conditioned to described push-pull converter;

The full-wave rectification output circuit;

Wherein said backhaul converter, each comprises a magnetic element (NSME) that is operated in the unsaturation zone at least described forward direction buck converter and described push-pull converter.

54. a backhaul management circuit that combines with the switch that produces high voltage transient (backhaul) comprises:

Electric source modes;

Rectifier is connected to described switch;

The first resistance network has resistance that is connected in parallel with described rectifier and the electric capacity that all is connected in series with described rectifier and described switch;

The second resistance network is connected between a described switch and the output mode; With

Wherein said backhaul management circuit returns described high voltage transient to described output mode and voltage mode.

55. a high voltage protection circuit that is used for described switch that combines with switch, power supply, output mode and perceptual energy storage elements, described high voltage protection circuit comprises:

The backhaul rectifier diodes;

The high-speed rectifier in parallel with the electric capacity branch circuit;

Described branch circuit and described backhaul rectifier diodes are connected in parallel; With

Wherein Bi He switch high voltage spike at first shifts by described branch circuit, shifts by described backhaul rectifier diodes then.

56. a transient protective network comprises:

The power input;

Output;

The first and second input nodes, one of them has the magnetic element that is operated in the unsaturation zone (NSME) of a series connection at least;

Be parallel-connected to the shunting capacitance on ground;

The shunting gap that is connected in parallel with described shunting capacitance;

With the rectifier parallel connection of described shunting gap, that be connected with the bridge type topology structure;

The electric capacity that is connected in parallel with described output; With

Be connected the electric capacity between output negative pole and the described ground.

57. also comprising, network as claimed in claim 56, wherein said NSME have 1 low magnetic permeability to the scope of 550u.

58. network as claimed in claim 57, wherein said NSME also comprise vertical substantially BH curve characteristic.

59. to the improvement of switch drive gate pole buffer with amplifier function, described buffer comprises high speed N-channel fet, a DC power supply is to the drain electrode end of described FET, and an input signal is to the gate pole of described FET, and described improvement comprises:

Described input signal is connected to the transistorized base stage of high speed PNP, and high speed PNP transistor is connected between FET source electrode and the described ground again;

The transistorized base stage of described PNP is connected to the gate pole of described FET;

Electric capacity is connected between transistorized base stage of described PNP and the transistorized collector electrode of described PNP; With

The transistorized emitter-base bandgap grading of wherein said PNP is connected to the source electrode of described FET.

60. improvement as claimed in claim 59 also comprises the source electrode that is connected described FET and the resistance between the described switch gate pole.

61. improvement as claimed in claim 59 also comprises shunt resistance, the source electrode that connects described FET is to described ground.

62. improvement as claimed in claim 59 also comprises the switch that temperature activates, and is connected in series with described DC power supply.

63. a distributed magnet circuitry comprises:

At least two magnetic elements (NSME) that are operated in the unsaturation zone; With

Wherein said element is connected in series.

64. a distributed magnet circuitry comprises:

Wherein said element is connected in parallel.

65. a converter feedback circuit comprises:

Positive pole and negative input all are connected to the output of converter;

Circuit output end is connected to converter control circuit;

Described electrode input end is connected in series to one and regulates diode and a resistance, and is connected to a transistorized base stage;

Described negative input is connected to described transistorized emitter-base bandgap grading, and is connected to a resistance branch circuit in parallel, and it is connected to described transistorized base stage again;

Described transistorized collector electrode is connected to the negative electrode of an optical isolator;

The anode of described optical isolator connects a series connection resistance to described electrode input end, and its output is connected to described circuit output end.

66. an overvoltage protection branch circuit comprises:

Positive pole and negative input all are connected to the output of a converter;

At least one Zener diode is connected to described electrode input end;

The anode of described Zener diode is connected to the gate pole of first thyristor (SCR), is connected to parallel resistance/electric capacity branch circuit, and described parallel resistance/electric capacity branch circuit is connected to described negative input;

The anode of a described SCR and resistance are connected in series to described anodal input;

Described negative input is connected to the second resistance branch circuit;

The described second resistance branch circuit is parallel-connected to the gate pole of the 2nd SCR and the negative electrode of described the 2nd SCR;

The described gate pole of wherein said the 2nd SCR is connected to the negative electrode of a described SCR;

The negative electrode of described the 2nd SCR is connected to a cathode output end; With

The anode of described the 2nd SCR is connected to a cathode output end.

67. a converter comprises:

The mode of resonance controller of correcting power factors;

The mode of resonance converter has a feedback circuit;

Switch drive gate pole buffer;

The full-wave rectification output circuit;

Described power factor controller provides a variable frequency signal to described mode of resonance converter; With

Described mode of resonance converter also comprises:

Be operated in the magnetic element (NSME) in unsaturation zone;

Positive pole and negative input all are connected to a power supply;

Described electrode input end is connected to the collector electrode of a NPN transistor;

Described electrode input end is also connected to a resonant capacitance and a resistance, is also connected to the collector electrode of an optical isolator;

The emitter of described optical isolator is connected to the base stage of described NPN transistor;

One resonant capacitance is connected to first end of described NSME;

The emitter of described NPN transistor is connected to the leakage level of N-channel fet and second end of described NSME; With

Described negative input is connected to the source electrode of described N-channel fet and the return node of a switch buffer.

68. as the described converter of claim 67, wherein said NSME also comprises low magnetic permeability.

69. as the described converter of claim 67, wherein said NSME also comprises being 85% iron by weight, the mixture of 6% aluminium and 9% silicon, thus for providing wide thermal technology, described magnetic element makes scope.

70. as the described converter of claim 68, wherein said low magnetic permeability has 1 to 550u scope.

71. as the described converter of claim 67, wherein said NSME is the aeromagnetic element.

72. as the described converter of claim 67, wherein said NSME also comprises a BH curve characteristic, scope is from B=1 to 10, and 000 gaussian sum H=1 is to 100 oersteds.

73. as the described converter of claim 67, also comprise a frequency modulation circuit, to regulate the output signal of described NSME.

74. as the described converter of claim 67, wherein said mode of resonance converter by the mode of resonance controller of described correcting power factors through the variable frequency controller drives.

75. as the described converter of claim 67, wherein said NSME also comprises distributed magnetic element.

76. as the described converter of claim 67, wherein said NSME selects from the group that comprises following element:

The aeromagnetic element;

Molybdenum permalloy powder (MPP) magnetic element;

High magnetic flux MPP magnetic element;

The powder magnetic element;

Space ferrimagnetism element is arranged;

Band is around magnetic element;

Die-cut magnetic element;

The magnetic element of lamination; With

Unbodied magnetic element.

77. a controlled resonant converter comprises:

The mode of resonance controller of correcting power factors;

The mode of resonance converter has a feedback circuit;

The full-wave rectification output circuit;

The mode of resonance controller of described correcting power factors provides a variable frequency signal to described mode of resonance converter; With

Described mode of resonance converter also comprises:

Be operated in the magnetic element (NSME) in unsaturation zone;

Positive pole and negative input all are connected to a power supply;

The emitter of described NPN transistor is connected to first end of transistorized emitter of a PNP and described NSME;

Described negative input is connected to a resonant capacitance and the transistorized collector electrode of described PNP;

The transistorized base stage of described PNP is connected to the output of the mode of resonance controller of the base stage of described NPN transistor and described correcting power factors; With

Described resonant capacitance is also connected to second end of described NSME.

78. as the described converter of claim 77, wherein said NSME also comprises low magnetic permeability.

79. as the described converter of claim 77, wherein said NSME also comprises being 85% iron by weight, the mixture of 6% aluminium and 9% silicon, thus for providing wide thermal technology, described magnetic element makes scope.

80. as the described converter of claim 78, wherein said low magnetic permeability has 1 to 550u scope.

81. as the described converter of claim 77, wherein said NSME is the aeromagnetic element.

82. as the described converter of claim 77, wherein said NSME also comprises a BH curve characteristic, scope from B=1 to 10000 gaussian sum H=1 to 100 oersteds.

83. as the described converter of claim 77, also comprise a frequency modulation circuit, to regulate the output signal of described NSME.

84. as the described converter of claim 77, wherein said mode of resonance converter by the mode of resonance controller of described correcting power factors through the variable frequency controller drives.

85. as the described converter of claim 77, wherein said NSME also comprises distributed magnetic element.

86. as the described converter of claim 77, wherein said NSME selects from the group that comprises following element:

The aeromagnetic element;

Molybdenum permalloy powder (MPP) magnetic element;

High magnetic flux MPP magnetic element;

The powder magnetic element;

Space ferrimagnetism element is arranged;

Band is around magnetic element;

Die-cut magnetic element;

The magnetic element of lamination; With

Unbodied magnetic element.

87. a resonance branch circuit comprises:

Electric capacity is connected to a magnetic element, thereby forms the resonance relation between them;

Wherein said magnetic element also comprises the magnetic element (NSME) that is operated in its unsaturation zone.

88. as the described branch circuit of claim 87, be also connected to a filter circuit, thereby give described filter circuit lower quality, complexity and cost for given filtering characteristic.

89. as the described converter of claim 88, wherein said NSME also comprises low magnetic permeability.

90. as the described converter of claim 89, wherein said NSME also comprises being 85% iron by weight, the mixture of 6% aluminium and 9% silicon, thus for providing wide thermal technology, described magnetic element makes scope.

91. as the described converter of claim 89, wherein said low magnetic permeability has 1 to 500 scope.

92. as the described converter of claim 89, wherein said NSME is an aeromagnetic element.

93. as the described converter of claim 89, wherein said NSME also comprises a BH curve characteristic, scope from B=1 to 10000 gaussian sum H=1 to 400 oersteds.

94. as the described branch circuit of claim 88, wherein said connection is to be connected in parallel.

95. as the described branch circuit of claim 88, wherein said connection is to be connected in series.

96. in the power conversion circuit of the magnetic element with energising, described improvement comprises:

Described magnetic element is operated in its unsaturation zone (NSME);

Described magnetic element has natural frequency; With

Described energising power approximately is matched with described natural frequency, thus the conversion efficiency that higher power density, improved thermal stability is provided and increases.

97. as the described converter of claim 96, wherein said NSME also comprises low magnetic permeability.

98. as the described converter of claim 97, wherein said NSME also comprises being 85% iron by weight, the mixture of 6% aluminium and 9% silicon, thus for providing wide thermal technology, described magnetic element makes scope.

98. as the described converter of claim 97, wherein said low magnetic permeability has 1 to 500 scope.

99. as the described converter of claim 97, wherein said NSME is an aeromagnetic element.

100. as the described converter of claim 97, wherein said NSME also comprises a BH curve characteristic, scope from B=1 to 10000 gaussian sum H=1 to 400 oersteds.

101. a transient protection circuit comprises:

The rectifier branch circuit;

Shunt capacitance/resistance circuit has the path to ground;

Wherein regular link voltage causes Passive Mode (passive mode); With

Wherein then cause electric current to flow to described electric capacity by the low-impedance mode in described rectifier just over line voltage distribution.

102. a method that prevents the electric capacity of excessive inrush current to the DC output of power inverter, described method comprises:

Provide series resistance to output capacitance;

One switch is provided on described series resistance;

After described power inverter activates, produce control signal, thereby close described switch and shunt described series resistance to ground; Thereby with the controlled charging that produces described output capacitance.

103. the topological structure at a plurality of power supplys of the parallel connection that is used for load balancing and superfluous and heat exchange power supply, be used for remaining on the device of N power subsystem load level about equally, described device comprises:

For each (N1, N2, Nx) power subsystem, the part output voltage is supplied to comparison circuit, this comparison circuit has a comparator, is used for more described part output voltage and reference voltage;

The output signal current loading measuring circuit that is used for each power subsystem;

The output of described measuring circuit forms summation signals with described part output voltage; With

Thereby being provided in the described N power subsystem almost equal power shares.

104. the topological structure at a plurality of power supplys of the parallel connection that is used for load balancing and superfluous and heat exchange power supply, be used for remaining on the device of N power subsystem load level about equally, described device comprises:

The output of described measuring circuit forms bias current to described reference voltage; With

105. in economize on electricity and high temperature circuit startup environment, be used for the device of startup of the power control circuit of accelerating power converter, described device comprises:

The rectified current potential source has identical earth potential with described control circuit, and is independent of described control circuit, is used for the described power control circuit of initial start;

One switch connects a part of described rectified current potential source to described power control circuit;

One detector circuit is used for determining the mode of operation of described power inverter being used for turn-offing described switch;

Thereby under normal operative condition, provide fast start circuit with little energy dissipation.