CN114624695A - Microwave detection method and device - Google Patents
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Abstract
The invention provides a microwave detection method and a device, wherein the microwave detection method comprises the step of accessing an echo signal in a balanced differential signal form from a receiving antenna of the microwave detection device, to output a Doppler intermediate frequency signal in a balanced differential signal form based on a subsequent mixing process of said echo signal and a corresponding excitation signal in a balanced differential signal form, and a digital conversion process of the doppler intermediate frequency signal in a balanced differential signal form to form a digitized form of the doppler intermediate frequency signal in a balanced differential signal form, and based on the digitized characteristics of the common-mode interference, the common-mode interference information in the digitized forms of the Doppler intermediate frequency signals of the forms of the balanced differential signals is suppressed and processed by a corresponding algorithm, therefore, the accuracy of the Doppler intermediate frequency signal is improved by suppressing electromagnetic interference in the environment in a state that the initial echo signal is in a differential signal form.
Description
Technical Field
The invention relates to the field of microwave detection, in particular to a microwave detection method and device based on the Doppler effect principle.
Background
With the development of the internet of things technology, the requirements of artificial intelligence, smart home and intelligent security technology on environment detection, particularly on detection accuracy of human existence, movement and micro motion characteristics are higher and higher, and accurate judgment basis can be provided for intelligent terminal equipment only by obtaining a stable enough detection result. The microwave detection technology based on the Doppler effect principle is used as a human-object, and an important junction connected between the objects has unique advantages in behavior detection and existence detection technologies, and can detect moving objects, such as motion characteristics, moving characteristics and micro-motion characteristics of a human, even heartbeat and respiration characteristic information of the human under the condition of not invading the privacy of the human, so that the microwave detection technology has wide application prospects. In particular, the respective microwave probe is fed by an excitation signal to emit a microwave beam corresponding to the frequency of said excitation signal into said target space, further forming a detection region in the target space, and receiving a reflected echo formed by the reflection of the microwave beam by a corresponding object in the detection region to transmit an echo signal corresponding to the frequency of the reflected echo to a mixer detection unit, wherein the mix detection unit mixes the excitation signal and the echo signal to output a Doppler intermediate frequency signal corresponding to a frequency/phase difference between the excitation signal and the echo signal, wherein, based on the principle of Doppler effect, when the object reflecting the microwave beam is in motion, the echo signal and the excitation signal have a certain frequency/phase difference, and the Doppler intermediate frequency signal presents corresponding amplitude fluctuation to feed back human body activity.
In ISM bands defined by ITU-R (ITU radio communication Sector) and open to organizations such as industry, science and medicine without license, the frequency bands applied to microwave detection mainly include limited frequency band resources such as 2.4Ghz, 5.8Ghz, 10.525Ghz, 24.125 Ghz, etc., and when these frequency bands are used, the corresponding microwave detectors need to observe a certain transmission power (generally, the transmission power is lower than 1W) to reduce interference to other radio devices, although the definition and license of different frequency bands can standardize the use frequency bands of radio and reduce the probability of mutual interference between radio devices of different frequency bands, under the license of limited frequency band resources, with the high-speed development of the internet of things technology, the radio use coverage rate corresponding to adjacent frequency bands or the same frequency band is increased at a high speed, such as increasingly popular 5G wireless routers, or a 5G frequency band is newly added on the basis of a duplex mode on the basis of the original 2.4G wireless router, so that the problem of mutual interference between radios in adjacent or same frequency bands is increasingly serious, and along with people-oriented intelligent competition, the requirement on accurate detection of human motion characteristics including respiratory motion and even heartbeat motion is also rapidly improved. Therefore, the anti-interference performance is one of the factors for measuring the accuracy of the corresponding microwave detection module, and under the background that the problem of mutual interference between radios is becoming more serious, the accuracy of the existing microwave detector is difficult to maintain, and no mention is promoted to meet the requirement of accurate detection of human motion characteristics including breathing motion and even heartbeat motion.
Further, since the boundary of the corresponding microwave beam is a gradient boundary where the radiation energy is attenuated to a certain degree and has non-determinacy, and since there is a lack of effective control means for the electromagnetic radiation, i.e. shaping means for the gradient boundary of the corresponding microwave beam, which is mainly reflected in the lack of adjustment means for the beam angle of the microwave beam, the actual detection space covered by the microwave beam emitted by the corresponding microwave detector is difficult to be stably controlled, and further based on the reflection and penetration behavior of the microwave beam in different target detection spaces, the actual detection space of the existing microwave detector cannot be matched with the corresponding target detection space independently based on the adjustment of the beam angle of the microwave beam, so as to be in a state where the target detection space outside the actual detection space cannot be effectively detected, and/or in a state where there is environmental interference in the actual detection space outside the target detection space, the microwave detection method comprises the steps of action interference, electromagnetic interference and self-excitation interference caused by an electromagnetic shielding environment, and solves the problems that the existing microwave detection technology based on the Doppler effect principle is poor in accuracy and/or poor in anti-interference performance, namely, because the boundary of a microwave beam is a gradient boundary of which the radiation energy is attenuated to a certain degree, a shaping means for the gradient boundary of the microwave beam is lacked, and based on the reflection and penetration characteristics of the microwave beam, the actual detection space of the existing microwave detector is difficult to match with the corresponding target detection space in actual application, and the defects that the existing microwave detector is limited in adaptability to different application scenes in the actual application and poor in detection stability are caused.
In order to solve the above drawbacks, the conventional microwave detector mainly reduces the probability of mutual interference between antennas in the same frequency band by narrowing the frequency bandwidth of the antennas, and reduces the sensitivity of the microwave detection module by increasing the amplitude difference of the corresponding effective signal relative to the interference signal in the doppler intermediate frequency signal by increasing the strength of the echo signal and setting the corresponding threshold value of the doppler intermediate frequency signal on the amplitude value, so as to eliminate the environmental interference of the actual detection space outside the target detection space corresponding to the interference signal with low amplitude value based on the reduction of the sensitivity. On one hand, although the probability of mutual interference between antennas in the same frequency band can be reduced by narrowing the frequency bandwidth of the antennas, based on the difference in the operating principle, antennas for communication use (such as antennas in a wireless router) are often designed to have a wider frequency bandwidth to meet the requirement of multi-channel communication, and narrowing the frequency bandwidth of the antennas for the microwave detector cannot ensure that the antennas for the existing microwave detector are not interfered by the antennas for communication use or do not cause interference to the antennas for communication use in the background that the coverage of radio use in adjacent frequency bands or the same frequency band is rapidly improved; in addition, based on the corresponding relationship between the frequency bandwidth of the antenna and the structural form and size of the antenna, the narrowing of the frequency bandwidth of the antenna of the microwave detector can simultaneously form high-precision requirements on the structure and size of the antenna, and the corresponding high-precision requirements are severer along with the improvement of the resonant frequency point of the antenna, so that additional cost burden is correspondingly generated. On the other hand, since the amplitude of the doppler intermediate frequency signal is related to the energy of the reflected echo and is simultaneously related to the size of the reflecting surface area in the environment, the size and the movement speed of the reflecting surface of the moving object and the distance between the microwave detection module, the environmental interference and the motion interference of the actual detection space outside the target detection space cannot be accurately excluded based on the reduction of the sensitivity of the microwave detector, so that the detection of the target detection space is unstable and accurate; in addition, based on the high strength requirement of the existing microwave detector for the echo signal, the range adjustment for the actual detection space tends to have a higher electromagnetic radiation energy density in the target detection space while covering the corresponding target detection space, so that the existing microwave detector cannot avoid interference to the antenna for communication use in the target detection space based on the reduction of the sensitivity, and it is difficult to avoid interference to the antenna for communication use in the target detection space based on the reduction of the sensitivity in pursuit of the antenna for communication use for high signal strength.
Disclosure of Invention
An object of the present invention is to provide a microwave detection method and apparatus, wherein the microwave detection method breaks through a technical tendency that a person skilled in the art tends to improve the strength of the echo signal, and based on a general pursuit of an antenna for communication use for high signal strength, by reducing the transmission power of a transmission antenna of the microwave detection apparatus, the signal strength of the corresponding microwave beam and the reflected echo is reduced, that is, the electromagnetic radiation energy density of the microwave beam and the reflected echo is reduced, and further, a bottom noise suppression mechanism of the communication apparatus itself can be utilized to avoid interference on the corresponding communication apparatus, so that the limitation of the installation position of the communication apparatus in an installation environment on the installation position of the microwave detection apparatus in the corresponding installation environment can be reduced or even removed.
Another object of the present invention is to provide a microwave detection method and apparatus, wherein the signal intensity of the microwave beam is reduced by reducing the transmitting power of the transmitting antenna of the microwave detection apparatus, so that the loss generated by the penetrating action of the microwave beam on the concrete wall or glass of the masonry structure is much larger than the loss generated by the propagation in the space, and in the state that the signal intensity of the microwave beam is reduced and the microwave beam is in a weak signal form, the absorption of the microwave beam in the weak signal form by the concrete wall or glass of the masonry structure defining the target detection space forms an adaptive definition of the gradient boundary of the microwave beam in the weak signal form, and in the state that the spatial form of the target detection space is not limited, the effective detection space of the microwave detection apparatus bounded by the concrete wall or glass of the masonry structure can be matched with the corresponding target detection space And the adaptability of the microwave detection device to different target detection spaces in practical application is improved.
Another object of the present invention is to provide a microwave detection method and apparatus, wherein the signal strength of the microwave beam is reduced to be in a weak signal form by reducing the transmitting power of the transmitting antenna of the microwave detection apparatus, and the ratio of the loss generated based on the reflection behavior of the microwave beam to the radiation energy of the microwave beam is increased, so as to avoid the self-excitation interference generated based on the multiple reflection behavior.
Another object of the present invention is to provide a microwave detection method and apparatus, wherein by reducing the transmitting power of the transmitting antenna of the microwave detection apparatus, the dependence of the noise immunity of the transmitting antenna on the frequency bandwidth of the transmitting antenna is reduced, which correspondingly reduces the precision requirement of the transmitting antenna and is beneficial to reduce the production cost of the transmitting antenna.
Another object of the present invention is to provide a microwave detection method and apparatus, wherein the reduction of the transmitting power of the transmitting antenna of the microwave detection apparatus is not aimed at adjusting the gradient boundary in the conventional sense of the microwave beam, and based on the principle that the coverage space of the microwave beam corresponds to the gain (dBd or dBi) of the transmitting antenna of the microwave detection apparatus without being controlled by the transmitting power of the transmitting antenna in the state that the transmitting antenna of the microwave detection apparatus is excited to transmit the microwave beam, the invention reduces the electromagnetic radiation energy density of the microwave beam in the coverage space thereof by reducing the transmitting power of the transmitting antenna, so as to increase the ratio of the loss generated by the penetrating action of the microwave beam with respect to the radiation energy of the microwave beam, thereby reducing the signal intensity of the microwave beam to be in a weak signal form, the microwave detection device has the advantages that the microwave beams in weak signal forms are absorbed by the concrete walls or glass of the masonry structure defining the target detection space, the concrete walls or glass of the masonry structure are used as boundaries to form adaptive definition of gradient boundaries of the microwave beams in weak signal forms, and therefore adaptability of the microwave detection device to different target detection spaces in practical application is improved.
Another object of the present invention is to provide a microwave detection method and apparatus, wherein the reduction of the transmitting power of the transmitting antenna of the microwave detection apparatus is not aimed at adjusting the gradient boundary in the conventional sense of the microwave beam, and based on the principle that the coverage space range of the microwave beam corresponds to the gain (dBd or dBi) of the transmitting antenna of the microwave detection apparatus but is not controlled by the transmitting power of the transmitting antenna, in the state that the transmitting antenna of the microwave detection apparatus is excited to transmit the microwave beam, the energy density of the electromagnetic radiation of the microwave beam in the coverage space thereof is reduced by reducing the transmitting power of the transmitting antenna to a weak signal form suitable for being suppressed by the corresponding communication apparatus based on the self-contained bottom noise suppression mechanism, thereby breaking through the tendency of those skilled in the art to increase the strength of the echo signal and tend to cover the corresponding target detection space while the microwave beam covers the corresponding target detection space The technical trend of higher electromagnetic radiation energy density in the target detection space.
Another object of the present invention is to provide a microwave detection method and apparatus, wherein based on the theoretical knowledge that the transmitting power (dBm) of the transmitting antenna of the microwave detection apparatus is signal source power (dBm) -transmission line loss (dB) + transmitting antenna gain (dBd or dBi), and experimental exploration and cognition of a background noise suppression mechanism of a communication device in the non-field, the invention forms a weak signal form of the microwave beam in a mode of reducing the transmitting power of the transmitting antenna to be less than or equal to 0dBm, the energy density of the electromagnetic radiation corresponding to the microwave beam in the covered space approaches the gradient boundary in the traditional sense and the energy density of the electromagnetic radiation outside the gradient boundary, the reduction of the transmitting power of the transmitting antenna of the microwave detection device is therefore not aimed at adjusting the gradient boundaries in the conventional sense of the microwave beam.
Another objective of the present invention is to provide a microwave detection method and apparatus, wherein the microwave detection method includes a step of improving a conversion efficiency of the transmitting antenna, so as to avoid a technical obstacle that the transmitting antenna cannot transmit the corresponding microwave beam due to failure of initial polarization in a state where its transmitting power is reduced based on its own dielectric loss, and reduce a minimum transmitting power limit value of the transmitting antenna corresponding to a state of ensuring stable transmission of the microwave beam, so as to ensure stable transmission of the microwave beam in a micro-signal form in a state where the transmitting power of the transmitting antenna is reduced to a corresponding target transmitting power.
Another object of the present invention is to provide a microwave detecting method and apparatus, wherein the minimum transmitting power limit of the transmitting antenna is reduced by implementing a circular polarization form of the transmitting antenna in a phase difference feeding manner, and the minimum transmitting power limit of the transmitting antenna is reduced in a state of ensuring stable transmission of the microwave beam, so as to ensure stable transmission of the microwave beam in a micro signal form in a state of reducing the transmitting power of the transmitting antenna to a target transmitting power.
Another objective of the present invention is to provide a microwave detection method and apparatus, wherein a differential feeding with a phase difference greater than 90 ° is implemented in the linear polarization direction of the transmitting antenna in a state that the transmitting antenna adopts a linearly polarized transmitting antenna, so as to reduce the loss generated by the electric field coupling during the initial polarization process of the transmitting antenna, thereby reducing the transmitting power of the transmitting antenna to the target transmitting power, and ensuring the stable transmission of the microwave beam in the form of a micro signal by the transmitting antenna.
Another object of the present invention is to provide a microwave detection method and apparatus, wherein the minimum emission power limit of the transmitting antenna is reduced based on a manner of reducing a self dielectric loss of the transmitting antenna, the microwave detection apparatus employs a half-wave folded-back directional microwave detecting antenna as the transmitting antenna, reduces the self dielectric loss of the transmitting antenna based on a structural characteristic that the half-wave folded-back directional microwave detecting antenna uses air as a medium to reduce the minimum emission power limit of the transmitting antenna, and further reduces the minimum emission power limit of the transmitting antenna based on a high gain characteristic of the half-wave folded-back directional microwave detecting antenna, thereby ensuring stable emission of the microwave beam in a form of a micro signal in a state of reducing the emission power of the transmitting antenna to 0dBm or less.
Another objective of the present invention is to provide a microwave detection method and apparatus, wherein the minimum transmitting power extremum of the transmitting antenna is reduced based on the manner of reducing the self dielectric loss of the transmitting antenna, the microwave detection apparatus employs a dual-fed differential antenna as the transmitting antenna, wherein the dual-fed differential antenna includes a reference ground and two strip-shaped elements, two ends of the two strip-shaped elements, which are connected to excitation signals, are respectively the feeding ends of the two strip-shaped elements, the two strip-shaped elements extend from the two feeding ends in the same lateral space of the reference ground and respectively have a wavelength electrical length greater than or equal to 3/16 and less than or equal to 5/16, wherein the two strip-shaped elements respectively have a coupling segment, and one end of the coupling segment, which is close to the feeding end of the strip-shaped element to which the coupling segment belongs, is the proximal end of the coupling segment, the two coupling sections extend in the dislocation opposite direction from the near end and have a dislocation distance which is greater than or equal to lambda/256 and less than or equal to lambda/6, namely, the distance from any point on one coupling section to the other coupling section is greater than or equal to lambda/256 and less than or equal to lambda/6, wherein lambda is a wavelength parameter corresponding to the frequency of the excitation signal, so that the double-ended feed type differential antenna is used as the transmitting antenna, the excitation signals with a difference of greater than 90 DEG are accessed to the two feeding ends of the two strip-shaped elements to be subjected to phase difference feeding, a polarization form tending to linear polarization is realized on the basis that the coupling between the two strip-shaped elements and the reference ground has a difference of greater than 90 DEG, and the coupling between the two coupling sections is formed on the basis that the two coupling sections extend in the dislocation opposite direction from the near end, and a common resonant frequency point is formed based on mutual coupling between the two coupling sections, that is, in a state that the double-ended feed type differential antenna is used for the transmitting antenna to access excitation signals with a phase difference of more than 90 degrees at the two feeding ends of the two strip-shaped oscillators, differential feed to the transmitting antenna is realized in a polarization direction of the transmitting antenna tending to linear polarization, the minimum transmitting power extreme value of the transmitting antenna is reduced in a state of ensuring stable transmission of the microwave beam, and further stable transmission of the microwave beam in a micro-signal form is ensured in a state of reducing the transmitting power of the transmitting antenna to a target transmitting power.
Another object of the present invention is to provide a microwave detection method and apparatus, wherein in a state of the transmitting antenna employing a linearly polarized version, in a polarization direction of the transmitting antenna, preferably based on balanced differential feeding tending to 180 ° phase difference with respect to the transmitting antenna, or in a state of employing the double-ended differential antenna as the transmitting antenna, preferably based on balanced differential feeding tending to 180 ° phase difference with respect to the transmitting antenna, a minimum transmitting power extremum of the transmitting antenna is lowered in a state of securing stable transmission of the microwave beam, thereby securing stable transmission of the microwave beam in a form of a micro-signal in a state of lowering the transmitting power of the transmitting antenna to 0dBm or less.
It is another object of the present invention to provide a microwave detection method and apparatus, wherein the microwave detection apparatus includes a differential feed circuit, wherein the differential feed circuit is provided in the form of discrete components and has a three-pole circuit processor provided as a MOS transistor or a triode, an inductor, a first resistor, a second resistor, a third resistor, a first capacitor, a second capacitor, an oscillation capacitor and a power connection terminal adapted to be connected to a corresponding power source, wherein the three-pole circuit processor has a first connection terminal corresponding to a collector of the triode or a drain of the MOS transistor, a second connection terminal corresponding to a base of the triode or a gate of the MOS transistor, and a third connection terminal corresponding to an emitter of the triode or a source of the MOS transistor, wherein one terminal of the second resistor is electrically connected to the first connection terminal of the three-pole circuit processor, the other end of the second resistor is connected to the power connection terminal via the inductor and is grounded via the first capacitor, wherein one end of the third resistor is electrically connected to the third connection terminal of the three-pole circuit processor, and the other end of the third resistor is grounded, wherein one end of the oscillation capacitor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the oscillation capacitor is grounded, wherein one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the first resistor is electrically connected between the inductor and the second resistor or to the power connection terminal, wherein both ends of the second capacitor are electrically connected to the first connection terminal and the third connection terminal of the three-pole circuit processor, respectively, the second resistor and the third resistor are set with equal resistance values, so that in the state that the differential feed circuit is connected to a corresponding power supply at the power supply connecting end, the excitation signal is output at two ends of the second capacitor in a balanced differential signal form with a phase difference approaching 180 degrees, and thus phase difference feeding of the transmitting antenna approaching 180 degrees is realized.
It is another object of the present invention to provide a microwave detection method and apparatus, wherein the microwave detection apparatus includes a differential feed circuit, wherein the differential feed circuit is configured in an integrated circuit form and has two inverted outputs, so as to output the excitation signals in the form of balanced differential signals with phases different by 180 ° at the two inverted outputs.
Another object of the present invention is to provide a microwave detection method and apparatus, wherein the microwave detection method further includes a step of improving the accuracy of the echo signal, so as to ensure the accuracy and stability of the detection range and detection of the activity characteristics corresponding to the human body movement, micromotion, respiration and heartbeat movements based on the improvement of the accuracy of the echo signal in a state that the intensity of the echo signal is reduced based on the transmitting power of the transmitting antenna.
Another object of the present invention is to provide a microwave detecting method and apparatus, wherein the step of improving the accuracy of the echo signal includes accessing the echo signal in a balanced differential signal form from a receiving antenna of the microwave detecting apparatus, so that the electromagnetic interference in the environment exists in a common-mode interference form in the echo signal, and thus can be suppressed during the receiving and transmitting processes of the echo signal in the balanced differential signal form, and then outputting the doppler intermediate frequency signal in the balanced differential signal form based on the step of mixing the echo signal in the balanced differential signal form and outputting the doppler intermediate frequency signal in a single-ended signal form based on the step of converting the difference of the doppler intermediate frequency signal in the balanced differential signal form into the single-ended signal form, so as to perform the step of mixing the echo signal in the balanced differential signal form and/or the step of converting the doppler intermediate frequency signal in the balanced differential signal form A signal differential-to-single-ended processing step for further suppressing common mode interference in said echo signals and/or said doppler intermediate frequency signals in balanced differential signal form, outputting said doppler intermediate frequency signals in single-ended signal form free from environmental electromagnetic interference, thereby improving the feedback accuracy of the Doppler intermediate frequency signal to the movement characteristics corresponding to the movement action, the inching action, the breathing action and the heartbeat action of the human body, the processing system of the balanced differential signal is constructed corresponding to the step of accessing the echo signal in the form of the balanced differential signal from the receiving antenna of the microwave detection device of the micro transmitting power and the subsequent steps, the microwave detection method and the device of the micro transmitting power ensure the movement action and the micro movement action of the micro transmitting power and the human body, and the detection range and the detection accuracy and stability of the activity characteristics corresponding to the breathing and the heartbeat actions.
Another object of the present invention is to provide a microwave detecting method and apparatus, wherein the step of improving the accuracy of the echo signal includes the step of accessing the echo signal in a balanced differential signal form from a receiving antenna of the microwave detecting apparatus, so that the electromagnetic interference in the environment exists in a common-mode interference form in the echo signal, and thus can be suppressed during the receiving and transmitting processes of the echo signal in the balanced differential signal form, and subsequently, the echo signal in the balanced differential signal form is output based on the further suppressing effect of the common-mode interference in the echo signal in the balanced differential signal form by the step of processing the echo signal in the balanced differential signal form to a single-end signal, and the doppler intermediate frequency signal in the environment electromagnetic interference free single-end signal form is output based on the step of processing the echo signal in the single-end signal form, the feedback accuracy of the Doppler intermediate frequency signal to the activity characteristics corresponding to the human body movement action, the micro-movement action and the respiration and heartbeat action is improved, and the detection range and the detection accuracy and stability of the microwave detection method and device of the micro-transmission power to the activity characteristics corresponding to the human body movement action, the micro-movement action and the respiration and heartbeat action are guaranteed by a processing system of the balance differential signal, which is constructed by the step of accessing the echo signal in the form of the balance differential signal to the receiving antenna of the microwave detection device of the micro-transmission power and the subsequent steps.
Another object of the present invention is to provide a microwave detecting method and apparatus, wherein the further suppressing effect of the step of processing the doppler intermediate frequency signals in a balanced differential signal form from a differential to a single end is further applied to the common mode interference in the doppler intermediate frequency signals in a balanced differential signal form, or the further suppressing effect of the step of processing the echo signals in a balanced differential signal form from a differential to a single end is further applied to the echo signals in a balanced differential signal form, so that the electromagnetic radiation interference which is not homologous to the echo signals in the environment can be effectively suppressed in the state of being received by the receiving antenna in the form of the common mode in the echo signals in a balanced differential signal form, including the electromagnetic radiation interference which is in the same frequency as the echo signals in the environment, thereby improving the motion of the doppler intermediate frequency signals to the human body, Fine motion, and feedback accuracy of motion characteristics corresponding to respiration and heartbeat motions.
Another object of the present invention is to provide a microwave detection method and apparatus, wherein the step of accessing the echo signal of a balanced differential signal form from a receiving antenna of the microwave detection apparatus includes accessing the echo signal of a balanced differential signal form based on a phase-shifting step of an echo signal accessed from one of receiving feed points in a state where the two receiving feed points of the receiving antenna are orthogonally arranged, to secure isolation between the echo signals accessed from the two receiving feed points of the receiving antenna based on an orthogonal form between the two receiving feed points of the receiving antenna, and to correspondingly secure accuracy of the echo signal of a balanced differential signal form accessed based on a phase-shifting step of an echo signal accessed from one of the receiving feed points.
Another object of the present invention is to provide a microwave detection method and apparatus, wherein in the step of accessing the echo signal in a balanced differential signal form from a receiving antenna of the microwave detection apparatus, two receiving feeding points of the receiving antenna are arranged in opposite phases to access the echo signal in a balanced differential signal form from the two receiving feeding points.
Another object of the present invention is to provide a microwave detecting method and apparatus, wherein the transmitting antenna and the receiving antenna of the microwave detecting apparatus are disposed in a structure sharing the reference ground, thereby facilitating the miniaturization design of the microwave detecting apparatus.
Another object of the present invention is to provide a microwave detecting method and apparatus, wherein the transmitting antenna and the receiving antenna of the microwave detecting apparatus are integrally disposed in a transceiving separated manner, so as to ensure isolation between the corresponding feeding points (terminals) and accuracy of the echo signal, and facilitate miniaturization design of the microwave detecting apparatus.
Another object of the present invention is to provide a microwave detecting method and apparatus, wherein the transmitting antenna and the receiving antenna of the microwave detecting apparatus are integrally disposed in a transmitting-receiving integrated manner, so as to simplify the circuit design of the microwave detecting apparatus and facilitate the miniaturization design of the microwave detecting apparatus.
According to one aspect of the present invention, there is provided a microwave detection method comprising the steps of:
A. a transmitting antenna fed by an excitation signal to transmit a microwave beam corresponding to the frequency of said excitation signal;
B. accessing an echo signal which has a phase difference of about 180 degrees and is in a balanced differential signal form from a receiving antenna, wherein the echo signal comprises a signal of a reflection echo formed by reflecting a microwave beam by a corresponding object, and electromagnetic interference in the environment exists in the echo signal in a common mode interference form and can be inhibited in the receiving and transmitting processes of the echo signal in the balanced differential signal form; and
C. mixing the excitation signal and the echo signal in the form of a balanced differential signal with a mixing circuit to output the Doppler intermediate frequency signal in the form of a balanced differential signal, and a digital conversion process of the Doppler intermediate frequency signal in a balanced differential signal form with an A/D conversion unit to form a digital form of the Doppler intermediate frequency signal in a balanced differential signal form, and a data processing unit for suppressing and processing the common mode interference information in the digitized morphology of the Doppler intermediate frequency signal in a balanced differential signal morphology by a corresponding algorithm based on the digitized characteristics of the common mode interference, in this way, in a state where the echo signal is initially in a differential signal form, electromagnetic interference in the environment is suppressed and the accuracy of the doppler intermediate frequency signal is improved based on the suppression processing of the common mode interference information in the digitized form of the doppler intermediate frequency signal in a balanced differential signal form.
In an embodiment, wherein in the step (C), further comprising the steps of: the echo signals in balanced differential signal form are amplified between the mixing circuit and the receiving antenna by at least one amplifying circuit adapted to amplify signals in differential signal form.
In an embodiment, wherein in the step (C), further comprising the steps of: the doppler intermediate frequency signal in the form of a differential signal is amplified between the mixing circuit and the a/D conversion unit with at least one amplification circuit adapted to amplify a signal in the form of a differential signal.
In one embodiment, wherein in the step (C), the doppler intermediate frequency signal corresponding to the balanced differential signal form has two signals with equal amplitude and opposite phase with respect to the reference potential, the digitized morphology of the Doppler intermediate frequency signal in the balanced differential signal morphology formed by the digitized conversion processing of the Doppler intermediate frequency signal in the balanced differential signal morphology by the A/D conversion unit is represented by two groups of numerical data which are equal in absolute value relative to a reference potential value and opposite in numerical value change trend in a time domain, wherein the common mode interference is represented by the digitalized characteristics of adding two groups of numerical values with equal numerical values and same numerical value variation trend to the two groups of numerical data in time domain, the data processing unit suppresses and processes common-mode interference information in the digitized form of the Doppler intermediate frequency signal in the form of a balanced differential signal by an algorithm for solving the difference of the two sets of numerical data.
In one embodiment, wherein in the step (C), the a/D conversion unit is integrally provided with the data processing unit.
In one embodiment, in the step (a), a differential feeding circuit provides excitation signals with a phase difference of 180 ° for the transmitting antenna, so as to output the excitation signals with a phase difference of 180 ° in a differential signal form to the mixing circuit, and the doppler intermediate frequency signals with a differential signal form are output based on the mixing processing of the excitation signals and the echo signals with a differential signal form by the mixing circuit.
In one embodiment, wherein the differential feed circuit is provided in the form of discrete components and has a three-pole circuit processor provided as a MOS transistor or a triode, an inductor, a first resistor, a second resistor, a third resistor, a first capacitor, a second capacitor, an oscillation capacitor and a power connection terminal adapted to be connected to a corresponding power source, wherein the three-pole circuit processor has a first connection terminal corresponding to a collector of the triode or a drain of the MOS transistor, a second connection terminal corresponding to a base of the triode or a gate of the MOS transistor, and a third connection terminal corresponding to an emitter of the triode or a source of the MOS transistor, wherein one end of the second resistor is electrically connected to the first connection terminal of the three-pole circuit processor, and the other end of the second resistor is connected to the power connection terminal via the inductor and is grounded via the first capacitor, wherein one end of the third resistor is electrically connected to the third connection terminal of the three-pole circuit processor, and the other end of the third resistor is grounded, wherein one end of the oscillation capacitor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the oscillation capacitor is grounded, wherein one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the first resistor is electrically connected between the inductor and the second resistor, wherein two ends of the second capacitor are electrically connected to the first connection terminal and the third connection terminal of the three-pole circuit processor, respectively, wherein the second resistor and the third resistor are set to have equal resistance values so as to switch the differential feed circuit into the corresponding power supply at the power connection terminal, and outputting the excitation signal in a balanced differential signal form with a phase difference of about 180 degrees at two ends of the second capacitor, so that the phase difference feeding of about 180 degrees of the transmitting antenna is realized.
In one embodiment, wherein the differential feed circuit is provided in the form of discrete components and has a three-pole circuit processor provided as a MOS transistor or a transistor, an inductor, a first resistor, a second resistor, a third resistor, a first capacitor, a second capacitor, an oscillation capacitor and a power connection terminal adapted to be connected to a corresponding power source, wherein the three-pole circuit processor has a first connection terminal corresponding to a collector of the transistor or a drain of the MOS transistor, a second connection terminal corresponding to a base of the transistor or a gate of the MOS transistor, and a third connection terminal corresponding to an emitter of the transistor or a source of the MOS transistor, wherein one end of the second resistor is electrically connected to the first connection terminal of the three-pole circuit processor, and the other end of the second resistor is connected to the power connection terminal via the inductor and is grounded via the first capacitor, wherein one end of the third resistor is electrically connected to the third connection terminal of the three-pole circuit processor, and the other end of the third resistor is grounded, wherein one end of the oscillation capacitor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the oscillation capacitor is grounded, wherein one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the first resistor is electrically connected to the power connection terminal, wherein two ends of the second capacitor are electrically connected to the first connection terminal and the third connection terminal of the three-pole circuit processor, respectively, wherein the second resistor and the third resistor are set to be equal in resistance value, so as to output the excitation signal in a balanced differential signal form with a difference of approximately 180 ° between the two ends of the second capacitor in a state where the differential feed circuit is connected to the corresponding power supply at the power connection terminal, thus realizing phase difference feeding of the transmitting antenna which is inclined to 180 degrees.
In one embodiment, the differential feed circuit further has a third capacitor and a fourth capacitor, wherein the third capacitor and the fourth capacitor are electrically connected to two ends of the second capacitor respectively, so as to output the excitation signal in a balanced differential signal form with a phase difference approaching 180 ° through the third capacitor and the fourth capacitor.
In one embodiment, the differential feed circuit is configured in an integrated circuit form and outputs the excitation signal in a balanced differential signal form with a phase difference of about 180 ° in a differential oscillation circuit, wherein the differential oscillation circuit has two N-channel MOS transistors, two P-channel MOS transistors, an oscillation inductor and an oscillation capacitor, wherein the sources of the two N-channel MOS transistors are electrically connected, the sources of the two P-channel MOS transistors are electrically connected, and the drains of the two N-channel MOS transistors are electrically connected to the drains of the different P-channel MOS transistors, respectively, so as to form a drain of one of the N-channel MOS transistors electrically connected to the drain of one of the P-channel MOS transistors, the source of the P-channel MOS transistor is electrically connected to the source of the other P-channel MOS transistor, and the drain of the other P-channel MOS transistor is electrically connected to the drain of the other N-channel MOS transistor, and the source of the other N-channel MOS transistor is electrically connected with the source of the previous N-channel MOS transistor in a sequential connection relationship, wherein in the two N-channel MOS transistors, the grid of any one N-channel MOS transistor is electrically connected with the drain of the other N-channel MOS transistor, wherein in the two P-channel MOS transistors, the grid of any one P-channel MOS transistor is electrically connected with the drain of the other P-channel MOS transistor, wherein the two ends of the oscillation inductor are respectively and electrically connected with the drains of the different P-channel MOS transistors, the two ends of the oscillation capacitor are respectively and electrically connected with the drains of the different P-channel MOS transistors and are connected with the oscillation inductor in parallel, so that the oscillation and the frequency selection are formed on the basis of a parallel resonance loop consisting of the oscillation inductor and the oscillation capacitor, and the sizes of the oscillation inductor and the two ends of the oscillation capacitor are equal, the electric signals in opposite directions enable one of the N-channel MOS transistor and the P-channel MOS transistor electrically connected with the grid electrode of the N-channel MOS transistor to be conducted at the same time, and enable the other N-channel MOS transistor and the P-channel MOS transistor electrically connected with the grid electrode of the N-channel MOS transistor to be conducted at the same time, so that the excitation signals are output at two ends of the oscillation inductor in a balanced differential signal mode with 180-degree difference.
In an embodiment, the differential feeding circuit further includes a low dropout regulator, an oscillator, a phase-locked loop, and a logic control unit, wherein the low dropout regulator provides a constant voltage to the differential oscillating circuit in a powered state, wherein the oscillator is configured such that the logic control unit provides a basic clock signal and a quartz crystal oscillator is externally disposed or an internal oscillating circuit is integrally disposed in the logic control unit, wherein the logic control unit is electrically connected to the oscillating inductor of the differential oscillating circuit, wherein the phase-locked loop is electrically connected between the logic control unit and the differential oscillating circuit in a state of being externally disposed or integrated in the logic control unit, so as to calibrate the differential oscillating circuit at both ends of the oscillating inductor based on the feedback of the excitation signal outputted by the differential oscillating circuit from the logic control unit The excitation signal frequency is output by the balanced differential signal forms with the phase difference of 180 degrees, so that the stable output of the excitation signal in the balanced differential signal forms by the differential feed circuit is guaranteed.
In one embodiment, the differential feeding circuit further comprises two amplifiers for amplifying the driving signal outputted from the differential oscillating circuit in a balanced differential signal form, wherein the logic control unit is electrically connected to the oscillating inductor of the differential oscillating circuit in a state of being electrically connected to at least one of the amplifiers to receive feedback of the driving signal outputted from the differential oscillating circuit from the amplifiers.
In one embodiment, in the step (B), the receiving antenna is configured in a planar patch antenna configuration to have a reference ground and a radiation source, wherein the radiation source is configured in a state spaced apart from the reference ground on one side of the reference ground, wherein the radiation source is configured in a unit radiation source configuration, the radiation source has a single number of radiation elements, the radiation elements have two feeding points, the two feeding points are arranged in an inverted phase, and a connection line direction from one of the feeding points to a physical center point of the radiation element coincides with a connection line direction from the other feeding point to a physical center point of the radiation element, so as to output the echo signals in a balanced differential signal configuration at the two feeding points based on a structural state that the two feeding points are arranged in an inverted phase.
In one embodiment, the radiating element is electrically connected to the reference ground at its physical center point.
In one embodiment, the radiating element has at least one group and/or at least one pair of grounding points electrically connected to the reference ground, wherein the grounding points of the same group are positioned at each vertex of the same regular polygon taking the physical central point of the radiating element as a midpoint, each grounding point corresponding to the grounding point in the same group is arranged around the physical central point of the radiation element at equal angles in a state of being equidistant from the physical central point of the radiation element, wherein the grounding points of the same pair are symmetrically distributed on the radiating element with the physical center point of the radiating element, the connecting line segment corresponding to the grounding point of the same pair takes the physical central point of the radiating element as a midpoint, and forms a zero potential point at the physical central point of the radiating element based on the electrical connection relationship between the grounding point and the reference ground, so that the connecting line segment is equivalent to the physical central point of the radiating element and the reference ground in electrical connection.
In an embodiment, in a state where the transmitting antenna is also set in a planar patch antenna state, the transmitting antenna and the receiving antenna are integrally set in a transceiving split form based on a structural form of sharing the reference ground.
In an embodiment, the transmitting antenna and the receiving antenna are integrally disposed in a transceiving separated form based on a structural configuration of sharing the reference ground and the radiation source.
In an embodiment, in a state where the transmitting antenna is also set in a planar patch antenna state, the transmitting antenna and the receiving antenna are integrally set in a transmitting-receiving integrated form based on a structural form in which the reference ground and the radiation source are shared.
In an embodiment, in the step (B), the receiving antenna is configured as a planar patch antenna having a ground reference and a radiation source, wherein the radiation source is configured on one side of the ground reference in a state spaced apart from the ground reference, wherein the radiation source is configured as a binary radiation source, and the radiation source has two radiation elements, wherein each radiation element has a feeding point, and wherein the two radiation elements are arranged in an inverted phase, and a connection line direction from the feeding point to a physical central point of one of the radiation elements is opposite to a connection line direction from the feeding point to a physical central point of the other radiation element, so as to output the echo signals in a balanced differential signal form at the two feeding points based on a structural state in which the two radiation elements are arranged in an inverted phase.
In one embodiment, at least one of the radiating elements is electrically connected to the ground reference at its physical center point.
In one embodiment, at least one of the radiating elements has at least one set and/or at least one pair of grounding points electrically connected to the reference ground, wherein the grounding points of the same group are positioned at each vertex of the same regular polygon taking the physical central point of the radiating element as a midpoint, each grounding point in the grounding points corresponding to the same group is arranged around the physical central point of the radiation element at equal angles in a state of being equidistant from the physical central point of the radiation element, wherein the grounding points of the same pair are symmetrically distributed on the radiating element at the physical central point of the radiating element, the connecting line segment corresponding to the grounding point of the same pair takes the physical central point of the radiating element as a midpoint, and forms a zero potential point at the physical central point of the radiating element based on the electrical connection relationship between the grounding point and the reference ground, so that the zero potential point is equivalent to the physical central point of the radiating element and the reference ground are electrically connected.
In an embodiment, in a state where the transmitting antenna is also provided in a planar patch antenna configuration, the transmitting antenna and the receiving antenna are integrally provided in a transceiving split form based on a structural configuration sharing the reference ground.
In an embodiment, in a state where the transmitting antenna is also provided in a planar patch antenna configuration, the transmitting antenna and the receiving antenna are integrally provided in a transceive-integrated manner based on a structural configuration in which the reference ground and the radiation source are shared.
In one embodiment, wherein in the step (B), the receiving antenna is configured as a half-wave folded directional microwave detecting antenna in a vertical structure with opposite-phase polarization, and comprises a ground reference, a half-wave oscillator and two feeding lines, wherein the half-wave oscillator has an electrical length equal to or greater than 1/2 and equal to or less than 3/4, and has two coupling sections, wherein each coupling section has an electrical length equal to or greater than 1/6, one end of each coupling section is a feeding end of the coupling section, and the other end of each coupling section is two ends of the half-wave oscillator, wherein a distance between the two feeding ends is equal to or less than λ/4, a distance between the two ends of the half-wave oscillator is equal to or greater than λ/128 and equal to or less than λ/6, wherein λ is a wavelength parameter corresponding to the frequency of the excitation signal, the half-wave oscillator is spaced from the reference ground in a state that a distance between two ends of the half-wave oscillator and the reference ground is greater than or equal to lambda/128 and less than or equal to lambda/6, wherein the two feeder lines are electrically connected to the corresponding feed ends respectively, the half-wave oscillator is arranged in an inverted phase, namely, a direction perpendicular to the reference ground is taken as a height direction of the half-wave folded directional microwave detection antenna, the half-wave oscillator is reversed from the two feed ends in an extending direction perpendicular to the height direction of the half-wave folded directional microwave detection antenna, and the echo signals in a balanced differential signal form are output from the two feed ends based on a structural state that the half-wave oscillator is arranged in an inverted phase.
In an embodiment, the transmitting antenna and the receiving antenna are integrally disposed in a transceiving separated form based on a structural configuration sharing the reference ground.
In an embodiment, the receiving antenna and the transmitting antenna are integrally disposed in a transceiving mode based on a structural configuration of sharing the transmitting antenna.
In an embodiment, in the step (B), the receiving antenna is configured as a dual-feed differential antenna, and the receiving antenna includes a reference ground and two strip-shaped elements, where two ends of the two strip-shaped elements, which are connected to the excitation signal, are respectively feed ends of the two strip-shaped elements, the two strip-shaped elements extend from the two feed ends in the same lateral space of the reference ground and respectively have a wavelength electrical length greater than or equal to 3/16 and less than or equal to 5/16, and each of the two strip-shaped elements has a coupling section, where one end of the coupling section, which is close to the feed end of the strip-shaped element to which the coupling section belongs, is a proximal end of the coupling section, and the two coupling sections extend from the proximal end in opposite directions, so as to form a structure in which the two coupling sections extend from the proximal ends in opposite directions, based on the structural characteristic that two coupling sections of the two strip-shaped oscillators extend from the near end in opposite directions and can be mutually coupled to form a common resonance frequency point, the two strip-shaped oscillators are formed in a structural state of being arranged in a reverse phase manner in a polarization direction tending to linear polarization, and therefore when the double-feed differential antenna is used as a receiving antenna, the echo signals in a balanced differential signal form are directly output from the two feed ends.
In one embodiment, two of the coupling sections of the double-ended feed differential antenna extend from the proximal end in opposite directions of the offset, and have offset distances of λ/256 or more and λ/6 or less, i.e. the distance from any point on one of the coupling sections to the other coupling section is λ/256 or more and λ/6 or less, where λ is a wavelength parameter corresponding to the frequency of the excitation signal.
In an embodiment, the transmitting antenna and the receiving antenna are integrally disposed in a transceiving mode based on a structural configuration of sharing the receiving antenna.
In one embodiment, wherein in the step (B), the receiving antenna is disposed in a planar patch antenna configuration to have a reference ground and a radiation source, wherein the radiation source is disposed at one side of the reference ground in a state spaced apart from the reference ground, wherein the radiation source is arranged in a unit radiation source configuration having a single number of radiation elements corresponding to the radiation source, wherein the radiating element has two feeding points, wherein the two feeding points are orthogonally arranged, connecting lines corresponding to the two feeding points and the physical center point of the radiating element are mutually perpendicular, and one of the feeding points is electrically connected with a phase shifter, so that the echo signals in a balanced differential signal form are output between one end of the phase shifter far away from the feeding point and the other feeding point based on the phase shifting processing of the phase shifter on the echo signals accessed from the feeding point.
In one embodiment, the radiating element is electrically connected to the reference ground at its physical center point.
In an embodiment, wherein the radiating element has at least one set and/or at least one pair of grounding points electrically connected to the reference ground, wherein the grounding points of the same group are positioned at each vertex of the same regular polygon taking the physical central point of the radiating element as a midpoint, each grounding point corresponding to the grounding point in the same group is arranged around the physical central point of the radiation element at equal angles in a state of being equidistant from the physical central point of the radiation element, wherein the grounding points of the same pair are symmetrically distributed on the radiating element with the physical center point of the radiating element, the connecting line segment corresponding to the grounding point of the same pair takes the physical central point of the radiating element as a midpoint, and forms a zero potential point at the physical central point of the radiating element based on the electrical connection relationship between the grounding point and the reference ground, so that the connecting line segment is equivalent to the physical central point of the radiating element and the reference ground in electrical connection.
In an embodiment, in a state where the transmitting antenna is also set in a planar patch antenna state, the transmitting antenna and the receiving antenna are integrally set in a transceiving split form based on a structural form of sharing the reference ground.
In one embodiment, in the step (B), the receiving antenna is configured in a planar patch antenna configuration to have a ground reference and a radiation source, wherein the radiation source is configured in a state of being spaced apart from the ground reference on one side of the ground reference, wherein the radiation source is configured in a binary radiation source configuration, and the radiation source has two radiation elements, wherein each radiation element has a feeding point, wherein the two radiation elements are orthogonally arranged, and a connection line direction from the feeding point to a physical central point of one of the radiation elements is perpendicular to a connection line direction from the feeding point to a physical central point of the other radiation element, wherein a phase shifter is electrically connected to one of the feeding points, so that a balanced differential signal configuration is output between one end of the phase shifter far from the feeding point and the other feeding point based on a phase shift processing of the phase shifter on the echo signal accessed from the feeding point Of the echo signal.
In one embodiment, the radiating element is electrically connected to the reference ground at its physical center point.
In one embodiment, at least one of the radiating elements has at least one set and/or at least one pair of grounding points electrically connected to the reference ground, wherein the grounding points of the same group are positioned at each vertex of the same regular polygon taking the physical central point of the radiating element as a midpoint, each grounding point corresponding to the grounding point in the same group is arranged around the physical central point of the radiation element at equal angles in a state of being equidistant from the physical central point of the radiation element, wherein the grounding points of the same pair are symmetrically distributed on the radiating element with the physical center point of the radiating element, the connecting line segment corresponding to the grounding point of the same pair takes the physical central point of the radiating element as a midpoint, and forms a zero potential point at the physical central point of the radiating element based on the electrical connection relationship between the grounding point and the reference ground, so that the connecting line segment is equivalent to the physical central point of the radiating element and the reference ground in electrical connection.
In an embodiment, in a state where the transmitting antenna is also provided in a planar patch antenna configuration, the transmitting antenna and the receiving antenna are integrally provided in a transceiving split form based on a structural configuration sharing the reference ground.
In one embodiment, wherein in the step (B), the receiving antenna is configured as a half-wave folded directional microwave detecting antenna in a cross-polarized vertical structure, and comprises a ground reference, two half-wave oscillators and four feeding lines, wherein each half-wave oscillator has a wavelength electrical length equal to or greater than 1/2 and equal to or less than 3/4, and has two coupling sections, wherein each coupling section has a wavelength electrical length equal to or greater than 1/6, one end of each coupling section is a feeding end of the coupling section, and the other end of each coupling section is two ends of the half-wave oscillator, wherein a distance between the two feeding ends of each half-wave oscillator is equal to or less than λ/4, and a distance between the two ends of each half-wave oscillator is equal to or greater than λ/128 and equal to or less than λ/6, wherein λ is a wavelength parameter corresponding to a frequency of the excitation signal, wherein each of the half-wave resonators is spaced apart from the reference ground in a state where a distance between both ends of each of the half-wave resonators and the reference ground is λ/128 or more and λ/6 or less, wherein four of the feed lines are electrically connected to the corresponding feed terminals, respectively, wherein the two half-wave resonators are arranged orthogonally to correspond to a direction perpendicular to the reference ground as a height direction of the half-wave folded-back directional microwave probe antenna, the two half-wave resonators are perpendicular to each other in an extending direction perpendicular to the height direction of the half-wave folded-back directional microwave probe antenna, wherein one of the feed terminals of one of the half-wave resonators is connected with a phase shifter via the feed line to perform phase shifting processing on the echo signal received from the feed terminal based on the phase shifter, and outputting the echo signal in a balanced differential signal form between one end of the phase shifter, which is far away from the feed end, and one of the feed ends of the other half-wave oscillator.
In one embodiment, the transmitting antenna and the receiving antenna are integrally arranged based on a structural configuration of sharing the receiving antenna.
According to another aspect of the present invention, there is also provided a microwave detection apparatus, comprising:
a transmitting antenna, wherein the transmitting antenna is configured to transmit a microwave beam corresponding to a frequency of an excitation signal in a state of being fed by the excitation signal;
the receiving antenna has a polarization direction tending to linear polarization and outputs corresponding echo signals in a balanced differential signal form with a phase difference tending to 180 degrees after receiving reflected echo formed by reflecting the microwave beam by a corresponding object;
a mixer circuit, wherein the mixer circuit is configured to mix the excitation signal and the echo signal in a balanced differential signal form to output the doppler intermediate frequency signal in a differential signal form;
an a/D conversion unit, wherein the a/D conversion unit is configured to digitize the doppler intermediate frequency signals in a balanced differential signal configuration to form a digitized configuration of the doppler intermediate frequency signals in a balanced differential signal configuration; and
A data processing unit, wherein the data processing unit is configured to perform a corresponding algorithm based on the digitized feature of the common-mode interference to suppress and process the common-mode interference information in the digitized form of the doppler intermediate frequency signal in a balanced differential signal form, so as to suppress the electromagnetic interference in the environment and improve the accuracy of the doppler intermediate frequency signal based on the suppression processing of the common-mode interference information in the digitized form of the doppler intermediate frequency signal in a balanced differential signal form in the initial state where the echo signal is in a differential signal form.
In an embodiment, the microwave detection device further comprises at least one amplifying circuit adapted to amplify a signal in a differential signal form, wherein the amplifying circuit is disposed between the receiving antenna and the mixing circuit to amplify and output the echo signal in a balanced differential signal form to the mixing circuit.
In an embodiment, the microwave detecting device further comprises another amplifying circuit adapted to amplify a signal in a differential signal form, wherein the amplifying circuit is disposed between the mixing circuit and the a/D converting unit to amplify the doppler intermediate frequency signal in a differential signal form to the a/D converting unit.
In one embodiment, the doppler intermediate frequency signal corresponding to the balanced differential signal configuration has two signals with equal amplitude and opposite phase relative to the reference potential, the digitized morphology of the Doppler intermediate frequency signal in the balanced differential signal morphology formed by the digitized conversion processing of the Doppler intermediate frequency signal in the balanced differential signal morphology by the A/D conversion unit is represented by two groups of numerical data which are equal in absolute value relative to a reference potential value and opposite in numerical value change trend in a time domain, wherein the common mode interference is represented by the digitalized characteristics of adding two groups of numerical values with equal numerical values and same numerical value variation trend to the two groups of numerical data in time domain, the data processing unit is configured to suppress processing common mode interference information in a digitized version of the doppler intermediate frequency signal in a balanced differential signal version by an algorithm that differentiates the two sets of numerical data.
In an embodiment, the a/D conversion unit is integrally disposed in the data processing unit.
In an embodiment, the microwave detecting device further includes a differential feeding circuit, wherein the differential feeding circuit is configured to output excitation signals with a phase difference of 180 ° in a powered state, to output the excitation signals with a phase difference of 180 ° in a differential signal form to the mixing circuit, and to output the doppler intermediate frequency signal with a differential signal form based on mixing processing of the excitation signals and the echo signals with the differential signal form by the mixing circuit.
In one embodiment, wherein the differential feed circuit is provided in the form of discrete components and has a three-pole circuit processor provided as a MOS transistor or a transistor, an inductor, a first resistor, a second resistor, a third resistor, a first capacitor, a second capacitor, an oscillation capacitor and a power connection terminal adapted to be connected to a corresponding power source, wherein the three-pole circuit processor has a first connection terminal corresponding to a collector of the transistor or a drain of the MOS transistor, a second connection terminal corresponding to a base of the transistor or a gate of the MOS transistor, and a third connection terminal corresponding to an emitter of the transistor or a source of the MOS transistor, wherein one end of the second resistor is electrically connected to the first connection terminal of the three-pole circuit processor, and the other end of the second resistor is connected to the power connection terminal via the inductor and is grounded via the first capacitor, wherein one end of the third resistor is electrically connected to the third connection terminal of the three-pole circuit handler, and the other end of the third resistor is grounded, wherein one end of the oscillation capacitor is electrically connected to the second connection terminal of the three-pole circuit handler, and the other end of the oscillation capacitor is grounded, wherein one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit handler, and the other end of the first resistor is electrically connected between the inductor and the second resistor, wherein both ends of the second capacitor are electrically connected to the first connection terminal and the third connection terminal of the three-pole circuit handler, respectively, wherein the second resistor and the third resistor are set to equal resistance values, so as to switch in the differential feed circuit to the corresponding power supply at the power connection terminal, and outputting the excitation signal at two ends of the second capacitor in a balanced differential signal form with the phase difference approaching 180 degrees, thereby realizing the phase difference feeding of the transmitting antenna approaching 180 degrees.
In one embodiment, the differential feed circuit further has a third capacitor and a fourth capacitor, wherein the third capacitor and the fourth capacitor are electrically connected to two ends of the second capacitor respectively, so as to output the excitation signal in a balanced differential signal form with a phase difference approaching 180 ° through the third capacitor and the fourth capacitor.
In one embodiment, wherein the differential feed circuit is provided in the form of discrete components and has a three-pole circuit processor provided as a MOS transistor or a triode, an inductor, a first resistor, a second resistor, a third resistor, a first capacitor, a second capacitor, an oscillation capacitor and a power connection terminal adapted to be connected to a corresponding power source, wherein the three-pole circuit processor has a first connection terminal corresponding to a collector of the triode or a drain of the MOS transistor, a second connection terminal corresponding to a base of the triode or a gate of the MOS transistor, and a third connection terminal corresponding to an emitter of the triode or a source of the MOS transistor, wherein one end of the second resistor is electrically connected to the first connection terminal of the three-pole circuit processor, and the other end of the second resistor is connected to the power connection terminal via the inductor and is grounded via the first capacitor, wherein one end of the third resistor is electrically connected to the third connection terminal of the three-pole circuit processor, and the other end of the third resistor is grounded, wherein one end of the oscillation capacitor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the oscillation capacitor is grounded, wherein one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the first resistor is electrically connected to the power connection terminal, wherein two ends of the second capacitor are electrically connected to the first connection terminal and the third connection terminal of the three-pole circuit processor, respectively, wherein the second resistor and the third resistor are set to be equal in resistance value, so as to output the excitation signal in a balanced differential signal form with a difference of approximately 180 ° between the two ends of the second capacitor in a state where the differential feed circuit is connected to the corresponding power supply at the power connection terminal, thus realizing phase difference feeding of the transmitting antenna which is inclined to 180 degrees.
In one embodiment, the differential feed circuit further has a third capacitor and a fourth capacitor, wherein the third capacitor and the fourth capacitor are electrically connected to two ends of the second capacitor respectively, so as to output the excitation signal in a balanced differential signal form with a phase difference approaching 180 ° through the third capacitor and the fourth capacitor.
In one embodiment, the differential feed circuit is configured in an integrated circuit form and outputs the excitation signal in a balanced differential signal form with a phase difference of about 180 ° in a differential oscillation circuit, wherein the differential oscillation circuit has two N-channel MOS transistors, two P-channel MOS transistors, an oscillation inductor and an oscillation capacitor, wherein the sources of the two N-channel MOS transistors are electrically connected, the sources of the two P-channel MOS transistors are electrically connected, and the drains of the two N-channel MOS transistors are electrically connected to the drains of the different P-channel MOS transistors, respectively, so as to form a drain of one of the N-channel MOS transistors electrically connected to the drain of one of the P-channel MOS transistors, the source of the P-channel MOS transistor is electrically connected to the source of the other P-channel MOS transistor, and the drain of the other P-channel MOS transistor is electrically connected to the drain of the other N-channel MOS transistor, and the source of the other N-channel MOS transistor is electrically connected to the source of the previous N-channel MOS transistor in a sequential connection relationship, wherein the gate of any one of the N-channel MOS transistors is electrically connected to the drain of the other N-channel MOS transistor, wherein the gate of any one of the P-channel MOS transistors is electrically connected to the drain of the other P-channel MOS transistor, wherein the two ends of the oscillation inductor are electrically connected to the drains of the different P-channel MOS transistors, respectively, and the two ends of the oscillation capacitor are electrically connected to the drains of the different P-channel MOS transistors and are connected in parallel with the oscillation inductor, respectively, so as to form oscillation and frequency selection based on the parallel resonant circuit composed of the oscillation inductor and the oscillation capacitor and form an equal size at the two ends of the oscillation inductor and the oscillation capacitor, the electric signals in opposite directions enable one of the N-channel MOS tubes and the P-channel MOS tube electrically connected with the grid electrode of the N-channel MOS tube to be conducted at the same time, and enable the other N-channel MOS tube and the P-channel MOS tube electrically connected with the grid electrode of the N-channel MOS tube to be conducted at the same time, so that the excitation signals are output at two ends of the oscillation inductor in a balanced differential signal mode with a 180-degree difference.
In an embodiment, the differential feeding circuit further includes a low dropout regulator, an oscillator, a phase-locked loop, and a logic control unit, wherein the low dropout regulator provides a constant voltage to the differential oscillating circuit in a powered state, wherein the oscillator is configured such that the logic control unit provides a basic clock signal and a quartz crystal oscillator is externally disposed or an internal oscillating circuit is integrally disposed in the logic control unit, wherein the logic control unit is electrically connected to the oscillating inductor of the differential oscillating circuit, wherein the phase-locked loop is electrically connected between the logic control unit and the differential oscillating circuit in a state of being externally disposed or integrated in the logic control unit, so as to calibrate the differential oscillating circuit at both ends of the oscillating inductor based on the feedback of the excitation signal outputted by the differential oscillating circuit from the logic control unit The excitation signal frequency is output by the balanced differential signal forms with the phase difference of 180 degrees, so that the stable output of the excitation signal in the balanced differential signal forms by the differential feed circuit is guaranteed.
In one embodiment, the differential feeding circuit further comprises two amplifiers for amplifying the driving signal outputted from the differential oscillating circuit in a balanced differential signal form, wherein the logic control unit is electrically connected to the oscillating inductor of the differential oscillating circuit in a state of being electrically connected to at least one of the amplifiers to receive feedback of the driving signal outputted from the differential oscillating circuit from the amplifiers.
In an embodiment, the receiving antenna is configured as a planar patch antenna having a ground reference and a radiation source, wherein the radiation source is configured as a unit radiation source, and has a single number of radiation elements corresponding to the radiation source, wherein the radiation elements have two feeding points, and wherein the two feeding points are arranged in opposite phases, and a connection line direction from one of the feeding points to a physical center point of the radiation element and a connection line direction from the other feeding point to the physical center point of the radiation element are coincident with each other, so as to output the echo signals in a balanced differential signal form at the two feeding points based on a structural state that the two feeding points are arranged in opposite phases.
In one embodiment, the radiating element is electrically connected to the reference ground at its physical center point.
In an embodiment, wherein the radiating element has at least one set and/or at least one pair of grounding points electrically connected to the reference ground, wherein the grounding points of the same group are positioned at each vertex of the same regular polygon taking the physical central point of the radiating element as a midpoint, each grounding point corresponding to the grounding point in the same group is arranged around the physical central point of the radiation element at equal angles in a state of being equidistant from the physical central point of the radiation element, wherein the grounding points of the same pair are symmetrically distributed on the radiating element at the physical central point of the radiating element, the connecting line segment corresponding to the grounding point of the same pair takes the physical central point of the radiating element as a midpoint, and forms a zero potential point at the physical central point of the radiating element based on the electrical connection relationship between the grounding point and the reference ground, so that the connecting line segment is equivalent to the physical central point of the radiating element and the reference ground in electrical connection.
In an embodiment, in a state where the transmitting antenna is also set in a planar patch antenna state, the transmitting antenna and the receiving antenna are integrally set in a transceiving split form based on a structural form of sharing the reference ground.
In an embodiment, the transmitting antenna and the receiving antenna are integrally disposed in a transceiving separated form based on a structural configuration of sharing the reference ground and the radiation source.
In an embodiment, in a state where the transmitting antenna is also provided in a planar patch antenna configuration, the transmitting antenna and the receiving antenna are integrally provided in a transceive-integrated manner based on a structural configuration in which the reference ground and the radiation source are shared.
In an embodiment, the receiving antenna is configured as a planar patch antenna and has a ground reference and a radiation source, wherein the radiation source is configured as a binary radiation source, the radiation source has two radiation elements corresponding to the radiation source, each of the radiation elements has a feeding point, the two radiation elements are arranged in opposite phases, and a connection line from the feeding point to a physical center point of one of the radiation elements is opposite to a connection line from the feeding point to the physical center point of the other radiation element, so that the echo signals in a balanced differential signal form are output at the two feeding points based on a structural state that the two radiation elements are arranged in opposite phases.
In one embodiment, at least one of the radiating elements is electrically connected to the ground reference at its physical center point.
In one embodiment, at least one of the radiating elements has at least one set and/or at least one pair of grounding points electrically connected to the reference ground, wherein the grounding points of the same group are positioned at each vertex of the same regular polygon taking the physical central point of the radiating element as a midpoint, each grounding point corresponding to the grounding point in the same group is arranged around the physical central point of the radiation element at equal angles in a state of being equidistant from the physical central point of the radiation element, wherein the grounding points of the same pair are symmetrically distributed on the radiating element with the physical center point of the radiating element, the connecting line segment corresponding to the grounding point of the same pair takes the physical central point of the radiating element as a midpoint, and forms a zero potential point at the physical central point of the radiating element based on the electrical connection relationship between the grounding point and the reference ground, so that the connecting line segment is equivalent to the physical central point of the radiating element and the reference ground in electrical connection.
In an embodiment, in a state where the transmitting antenna is also set in a planar patch antenna state, the transmitting antenna and the receiving antenna are integrally set in a transceiving split form based on a structural form of sharing the reference ground.
In an embodiment, in a state where the transmitting antenna is also provided in a planar patch antenna configuration, the transmitting antenna and the receiving antenna are integrally provided in a transceive-integrated manner based on a structural configuration in which the reference ground and the radiation source are shared.
In one embodiment, the receiving antenna is configured as a half-wave folded directional microwave detecting antenna in a vertical structure with reverse polarization, and comprises a ground reference, a half-wave oscillator and two power supply lines, wherein the half-wave oscillator has an electrical length greater than or equal to 1/2 and less than or equal to 3/4 and has two coupling sections, wherein each coupling section has an electrical length greater than or equal to 1/6, one end of each coupling section is a feeding end of the coupling section, and the other end of each coupling section is two ends of the half-wave oscillator, wherein the distance between the two feeding ends is less than or equal to λ/4, the distance between the two ends of the half-wave oscillator is greater than or equal to λ/128 and less than or equal to λ/6, wherein λ is a wavelength parameter corresponding to the frequency of the excitation signal, the half-wave oscillator is spaced from the reference ground in a state that a distance between two ends of the half-wave oscillator and the reference ground is greater than or equal to lambda/128 and less than or equal to lambda/6, wherein the two feeder lines are electrically connected to the corresponding feed ends respectively, the half-wave oscillator is arranged in an inverted phase, namely, a direction perpendicular to the reference ground is taken as a height direction of the half-wave folded directional microwave detection antenna, the half-wave oscillator is reversed from the two feed ends in an extending direction perpendicular to the height direction of the half-wave folded directional microwave detection antenna, and the echo signals in a balanced differential signal form are output from the two feed ends based on a structural state that the half-wave oscillator is arranged in an inverted phase.
In an embodiment, the transmitting antenna and the receiving antenna are integrally disposed in a transceiving separated form based on a structural configuration sharing the reference ground.
In an embodiment, the half-wave folded directional microwave detecting antenna in a vertical structure with reverse polarization of the transmitting antenna is provided, the integrated structure corresponding to the transmitting antenna and the receiving antenna includes two half-wave oscillators respectively arranged in opposite phases, wherein the two half-wave oscillators are arranged orthogonally to each other, corresponding to a direction perpendicular to the reference ground direction as a height direction of the half-wave folded directional microwave detecting antenna, each half-wave oscillator is inverted from the two feeding terminals in an extending direction perpendicular to the height direction of the half-wave folded directional microwave detecting antenna, and the two half-wave oscillators are perpendicular to each other in the extending direction perpendicular to the height direction of the half-wave folded directional microwave detecting antenna.
In an embodiment, in an integrated structure of the transmitting antenna and the receiving antenna, each half-wave element is shifted and inverted from the two feeding ends in an extending direction perpendicular to a height direction of the half-wave folded directional microwave detecting antenna, and a state in which the two half-wave elements are orthogonally arranged corresponds to a structural form in which the four feeding ends are located at four vertex positions of a square with a connecting line of the two feeding ends of each half-wave element as a diagonal line.
In an embodiment, the receiving antenna and the transmitting antenna are integrally disposed in a transceiving mode based on a structural form of sharing the transmitting antenna.
In an embodiment, the receiving antenna is configured as a dual-feed differential antenna, and includes a reference ground and two strip-shaped elements corresponding to the receiving antenna, where two ends of an access excitation signal of the two strip-shaped elements are respectively used as feeding ends of the two strip-shaped elements, the two strip-shaped elements extend from the two feeding ends in the same lateral space of the reference ground and respectively have a wavelength electrical length greater than or equal to 3/16 and less than or equal to 5/16, the two strip-shaped elements respectively have a coupling segment, where one end of the coupling segment near the feeding end of the strip-shaped element to which the coupling segment belongs is used as a proximal end of the coupling segment, the two coupling segments extend from the proximal end in opposite directions, and the two coupling segments of the two strip-shaped elements can be coupled with each other to form a common coupling based on a structural configuration that the two coupling segments extend from the proximal end in opposite directions, and the two coupling segments of the two strip-shaped elements extend from the proximal end in opposite directions and can be coupled with each other to form a common coupling segment The structural characteristics of resonance frequency points form a structural state that the two strip-shaped oscillators are arranged in an inverted phase in the polarization direction tending to linear polarization, so that when the double-feed differential antenna is used as a receiving antenna, the echo signals in a balanced differential signal form are directly output at the two feed ends.
In one embodiment, two of the coupling sections of the double-fed differential antenna extend from the proximal end in opposite directions of the offset, and have an offset distance of λ/256 or more and λ/6 or less, that is, a distance from any point on one of the coupling sections to the other coupling section is λ/256 or more and λ/6 or less, where λ is a wavelength parameter corresponding to the frequency of the excitation signal.
In an embodiment, the transmitting antenna and the receiving antenna are integrally disposed in a transceiving mode based on a structural configuration of sharing the receiving antenna.
In one embodiment, wherein the receiving antenna is configured in a planar patch antenna configuration with a reference ground and a radiation source, wherein the radiation source is disposed at one side of the reference ground in a state spaced apart from the reference ground, wherein the radiation source is arranged in a unit radiation source configuration having a single number of radiation elements corresponding to the radiation source, wherein the radiating element has two feeding points, wherein the two feeding points are orthogonally arranged, connecting lines corresponding to the two feeding points and the physical center point of the radiating element are mutually perpendicular, and one of the feeding points is electrically connected with a phase shifter, so that the echo signals in a balanced differential signal form are output between one end of the phase shifter far away from the feeding point and the other feeding point based on the phase shifting processing of the phase shifter on the echo signals accessed from the feeding point.
In one embodiment, the radiating element is electrically connected to the reference ground at its physical center point.
In an embodiment, wherein the radiating element has at least one set and/or at least one pair of grounding points electrically connected to the reference ground, wherein the grounding points of the same group are positioned at each vertex of the same regular polygon taking the physical central point of the radiating element as a midpoint, each grounding point corresponding to the grounding point in the same group is arranged around the physical central point of the radiation element at equal angles in a state of being equidistant from the physical central point of the radiation element, wherein the grounding points of the same pair are symmetrically distributed on the radiating element with the physical center point of the radiating element, the connecting line segment corresponding to the grounding point of the same pair takes the physical central point of the radiating element as a midpoint, and forms a zero potential point at the physical central point of the radiating element based on the electrical connection relationship between the grounding point and the reference ground, so that the connecting line segment is equivalent to the physical central point of the radiating element and the reference ground in electrical connection.
In an embodiment, in a state where the transmitting antenna is also set in a planar patch antenna state, the transmitting antenna and the receiving antenna are integrally set in a transceiving split form based on a structural form of sharing the reference ground.
In one embodiment, wherein the receiving antenna is configured in a planar patch antenna configuration with a reference ground and a radiation source, wherein the radiation source is disposed at one side of the reference ground in a state spaced apart from the reference ground, wherein the radiation source is arranged in the form of a binary radiation source having two radiation elements corresponding to the radiation source, wherein each of the radiating elements has a feeding point, wherein two of the radiating elements are orthogonally arranged, and a connecting line direction from the feeding point to a physical center point of one of the radiating elements is perpendicular to a connecting line direction from the feeding point to the physical center point of the other radiating element, and one of the feeding points is electrically connected with a phase shifter, so that the echo signals in a balanced differential signal form are output between one end of the phase shifter far away from the feeding point and the other feeding point based on the phase shifting processing of the phase shifter on the echo signals accessed from the feeding point.
In one embodiment, the radiating element is electrically connected to the reference ground at its physical center point.
In one embodiment, at least one of the radiating elements has at least one set and/or at least one pair of grounding points electrically connected to the reference ground, wherein the grounding points of the same group are positioned at each vertex of the same regular polygon taking the physical central point of the radiating element as a midpoint, each grounding point corresponding to the grounding point in the same group is arranged around the physical central point of the radiation element at equal angles in a state of being equidistant from the physical central point of the radiation element, wherein the grounding points of the same pair are symmetrically distributed on the radiating element with the physical center point of the radiating element, the connecting line segment corresponding to the grounding point of the same pair takes the physical central point of the radiating element as a midpoint, and forms a zero potential point at the physical central point of the radiating element based on the electrical connection relationship between the grounding point and the reference ground, so that the connecting line segment is equivalent to the physical central point of the radiating element and the reference ground in electrical connection.
In an embodiment, in a state where the transmitting antenna is also set in a planar patch antenna state, the transmitting antenna and the receiving antenna are integrally set in a transceiving split form based on a structural form of sharing the reference ground.
In one embodiment, the receiving antenna is configured as a half-wave folded directional microwave detecting antenna in a cross-polarized vertical structure, and comprises a ground reference, two half-wave oscillators and four feeding lines, wherein each half-wave oscillator has an electrical length equal to or greater than 1/2 and equal to or less than 3/4, and has two coupling sections, each coupling section has an electrical length equal to or greater than 1/6, one end of each coupling section is a feeding end of the coupling section, and the other end of each coupling section is two ends of the half-wave oscillator, wherein the distance between the two feeding ends of each half-wave oscillator is equal to or less than λ/4, the distance between the two ends of each half-wave oscillator is equal to or greater than λ/128 and equal to or less than λ/6, wherein λ is a wavelength parameter corresponding to the frequency of the excitation signal, wherein each of the half-wave resonators is spaced apart from the reference ground in a state where a distance between both ends of each of the half-wave resonators and the reference ground is λ/128 or more and λ/6 or less, wherein four of the feeder lines are electrically connected to the corresponding feed terminals, respectively, wherein the two half-wave resonators are orthogonally arranged corresponding to a direction perpendicular to the reference ground as a height direction of the half-wave backfolding type directional microwave detecting antenna, each of the half-wave resonators is inverted from the two feed terminals in an extending direction perpendicular to the height direction of the half-wave backfolding type directional microwave detecting antenna, and the two half-wave resonators are perpendicular to each other in the extending direction perpendicular to the height direction of the half-wave backfolding type directional microwave detecting antenna, wherein one of the feed terminals of one of the half-wave resonators is connected with a phase shifter via the feeder line to perform phase shift processing on the echo signal accessed from the feed terminal based on the phase shifter, and the echo signal in a balanced differential signal form is output between one end of the phase shifter, which is far away from the feed end, and one of the feed ends of the other half-wave oscillator.
In an embodiment, the half-wave oscillators are staggered and inverted in an extending direction perpendicular to a height direction of the half-wave backfolding type directional microwave detecting antenna from the two feeding ends, and the state in which the two half-wave oscillators are orthogonally arranged corresponds to a structural form in which the four feeding ends are located at four vertex positions of a square with a diagonal line connecting the two feeding ends of each half-wave oscillator.
In an embodiment, the transmitting antenna is integrally provided with the receiving antenna based on a structural configuration of sharing the receiving antenna.
Drawings
Fig. 1A is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to an embodiment of the present invention.
Fig. 1B is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 1C is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 2A is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 2B is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 3A is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 3B is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the invention.
Fig. 4A is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the invention.
Fig. 4B is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the invention.
Fig. 4C is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the invention.
Fig. 4D is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4E is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4F is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4G is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4H is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4I is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4J is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4K is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the invention.
Fig. 4L is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the invention.
Fig. 4M is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the invention.
Fig. 4N is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the invention.
Fig. 5A is a schematic structural diagram of a differential feed circuit of a microwave detection device according to an embodiment of the invention.
Fig. 5B is a schematic structural diagram of a differential feed circuit of a microwave detection device according to another embodiment of the present invention.
Fig. 6 is a schematic structural diagram of a differential oscillation circuit of a microwave detection device according to an embodiment of the present invention.
Fig. 7A is a schematic structural diagram of a microwave detecting device according to an embodiment of the present invention.
Fig. 7B is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention.
Fig. 7C is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention.
FIG. 7D is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention.
Fig. 8A is a schematic structural diagram of a receiving antenna of a microwave detecting device according to an embodiment of the invention.
Fig. 8B is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the invention.
Fig. 8C is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 8D is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 9A is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 9B is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 9C is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 9D is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 9E is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 10A is a schematic structural diagram illustrating a transmitting antenna and a receiving antenna of a microwave detecting device according to an embodiment of the present invention are integrally disposed.
Fig. 10B is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Fig. 10C is a schematic structural diagram illustrating a microwave detecting device according to another embodiment of the invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Fig. 10D is a schematic structural diagram illustrating a microwave detecting device according to another embodiment of the invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Fig. 10E is a schematic structural diagram illustrating a microwave detecting device according to another embodiment of the invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Fig. 10F is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Fig. 10G is a schematic structural diagram illustrating a microwave detecting device according to another embodiment of the invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Fig. 10H is a schematic structural diagram illustrating a microwave detecting device according to another embodiment of the invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Fig. 10I is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Fig. 10J is a schematic structural diagram illustrating a microwave detecting device according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Detailed Description
The following description is provided to disclose the invention so as to enable any person skilled in the art to practice the invention. The preferred embodiments in the following description are given by way of example only, and other obvious variations will occur to those skilled in the art. The basic principles of the invention, as defined in the following description, may be applied to other embodiments, variations, modifications, equivalents, and other technical solutions without departing from the spirit and scope of the invention.
It will be understood by those skilled in the art that in the present disclosure, the terms "longitudinal," "lateral," "upper," "lower," "front," "rear," "left," "right," "vertical," "horizontal," "top," "bottom," "inner," "outer," and the like are used in an orientation or positional relationship indicated in the drawings for ease of description and simplicity of description, and do not indicate or imply that the referenced devices or components must be constructed and operated in a particular orientation and thus are not to be considered limiting.
It is understood that the terms "a" and "an" should be interpreted as meaning that a number of one element or element is one in one embodiment, while a number of other elements is one in another embodiment, and the terms "a" and "an" should not be interpreted as limiting the number.
The invention provides a microwave detection method and a device, wherein the microwave detection method breaks through the technical tendency that technical personnel in the field tend to improve the strength of corresponding echo signals, based on the general pursuit of communication antenna for high signal strength, the signal strength of corresponding microwave wave beams and reflected echoes is reduced by reducing the transmission power of the transmission antenna of the microwave detection device, namely the electromagnetic radiation energy density of the microwave wave beams and the reflected echoes is reduced, and further the limitation of the installation position of the microwave detection device in the corresponding installation environment caused by the interference on the corresponding communication device can be reduced and even removed by utilizing the bottom noise suppression mechanism of the communication device.
The transmitting power of the transmitting antenna of the microwave detection device is reduced, the signal intensity corresponding to the microwave beam is reduced to be in a weak signal form, and the corresponding communication device in the environment can resist the interference of the microwave detection device based on the self-contained noise suppression mechanism, so that the influence of the frequency bandwidth of the transmitting antenna of the microwave detection device on the interference capability of the corresponding communication device by the microwave detection device is reduced, namely the dependence of the immunity of the transmitting antenna on the narrowed frequency bandwidth is reduced, the precision requirement on the transmitting antenna is correspondingly reduced, and the production cost of the transmitting antenna is favorably reduced.
Meanwhile, because the signal intensity of the microwave beam is reduced, based on the characteristic that the loss generated by the penetration behavior of the microwave beam to the concrete wall or glass of the masonry structure is much larger than the loss generated by the propagation in the space, in a state where the signal intensity of the microwave beam is lowered to be in a weak signal form, by absorption of the microwave beam in a weak signal form by a concrete wall or glass of a masonry structure defining a target detection space, i.e. an adaptive definition of the gradient boundaries of the microwave beam, which can form weak signal morphology, corresponding to a state in which the spatial morphology of the target detection space is not restricted, the effective detection space of the microwave detection device, which is bounded by a concrete wall or glass with a masonry structure, can be matched with the corresponding target detection space, so that the adaptability of the microwave detection device to different target detection spaces in practical application is improved.
Further, since the signal intensity of the microwave beam is reduced to be in a weak signal form, the ratio of the loss generated based on the reflection behavior of the microwave beam to the radiation energy of the microwave beam is increased, so that the self-excited interference generated based on the multiple reflection behavior can be avoided.
That is, the transmitting power of the transmitting antenna of the microwave detecting device is reduced, and the signal strength of the corresponding microwave beam is reduced to be in a weak signal form, so that the strength of the corresponding echo signal is reduced, and thus the microwave detecting method breaks through the technical trend that a person skilled in the art tends to increase the strength of the corresponding echo signal and tends to have a higher electromagnetic radiation energy density in the target detecting space while the microwave beam covers the corresponding target detecting space, wherein the reduction of the transmitting power of the transmitting antenna of the microwave detecting device is not aimed at adjusting the gradient boundary traditionally meaning of the microwave beam, but is based on the state that the transmitting antenna of the microwave detecting device is excited to transmit the microwave beam, and the coverage space range of the microwave beam corresponds to the gain (dBd or dBi) of the transmitting antenna of the microwave detecting device and is not controlled by the transmitting power of the transmitting antenna Reasonably recognizing that the electromagnetic radiation energy density of the microwave beam in the coverage space is reduced to a weak signal form which is suitable for being suppressed by a corresponding communication device based on a self-contained bottom noise suppression mechanism by reducing the transmission power of the transmitting antenna, thereby avoiding interference with the corresponding communication device, and increasing the ratio of the loss generated by the penetration action of the microwave beam to the radiation energy of the microwave beam, the absorption of said microwave beam in weak signal form by masonry-structured concrete walls or glass delimiting the target detection space can then be utilized, the masonry concrete wall or glass boundary forms an adaptive definition of the gradient boundary of the microwave beam of weak signal morphology, correspondingly, the adaptability of the microwave detection device to different target detection spaces in practical application is improved.
Further, based on the theoretical knowledge that the transmission power (dBm) of the transmitting antenna of the microwave detection apparatus is equal to the signal source power (dBm) -transmission line loss (dB) + the transmitting antenna gain (dBd or dBi), and the experimental exploration knowledge of the noise floor suppression mechanism of the communication apparatus not in the art, the microwave detection method may be characterized by feeding the transmitting antenna with a feeding power of less than 1mW, preferably by reducing the transmitting power of the transmitting antenna to a target transmission power of 0dBm or less, such as by reducing the transmitting power of the transmitting antenna to a target transmission power of-3 dBm or-6 dBm, to form a weak signal morphology of the microwave beam corresponding to an electromagnetic radiation energy density of the microwave beam in its coverage space approaching a conventionally significant gradient boundary and an electromagnetic radiation energy density outside the gradient boundary, the reduction of the transmitting power of the transmitting antenna of the microwave detection device is therefore not aimed at adjusting the gradient boundaries in the conventional sense of the microwave beam.
It can be understood that, due to the dielectric loss of the transmitting antenna itself, the conversion efficiency of the transmitting antenna may not reach 100%, and corresponding to the process that the transmitting power of the transmitting antenna is reduced, the transmitting antenna may not transmit the corresponding microwave beam when the transmitting power of the transmitting antenna is not reduced to the target transmitting power, that is, the initial polarization process cannot be completed based on the dielectric loss of the transmitting antenna itself. That is to say, the minimum transmitting power capable of guaranteeing the stable transmission of the microwave beam is taken as the minimum transmitting power extreme value of the transmitting antenna, and in the state that the minimum transmitting power extreme value of the transmitting antenna is less than 0dBm, the specific type and structural form of the transmitting antenna are not limited, but based on the medium loss of the transmitting antenna, the transmitting antenna has a technical obstacle that the minimum transmitting power extreme value of the transmitting antenna may be greater than the target transmitting power and cannot be further reduced in the state of guaranteeing the stable transmission of the microwave beam. Based on this, the microwave detection method of the present invention further includes a method step of improving the conversion efficiency of the transmitting antenna, so as to avoid a technical obstacle that the transmitting antenna cannot complete initial polarization and cannot transmit the corresponding microwave beam in a state where its transmission power is reduced based on the dielectric loss of the transmitting antenna itself, and reduce the minimum transmission power extremum of the transmitting antenna corresponding to a state where stable transmission of the microwave beam is ensured, so as to ensure stable transmission of the microwave beam in a form of a micro signal in a state where the transmission power of the transmitting antenna is reduced to a target transmission power.
Specifically, in the method step of improving the conversion efficiency of the transmitting antenna, the circularly polarized form of the transmitting antenna is realized by the phase difference feeding to reduce the minimum transmitting power extreme value of the transmitting antenna, or the differential feeding with a phase difference larger than 90 ° is realized in the linear polarization direction of the transmitting antenna in the state that the transmitting antenna adopts the linearly polarized form of the transmitting antenna, so as to reduce the loss of the transmitting antenna generated based on the electric field coupling effect in the initial polarization process to reduce the minimum transmitting power extreme value of the transmitting antenna, thereby ensuring the stable transmission of the microwave beam in the form of a micro signal by the transmitting antenna in the state of reducing the transmitting power of the transmitting antenna to the target transmitting power.
Accordingly, referring to fig. 1A to 1C of the drawings accompanying the present specification, various embodiments of the transmitting antenna 10 for implementing a circular polarization state based on a phase difference feeding are illustrated, wherein the transmitting antenna 10 is exemplarily provided in a planar patch antenna configuration to have a reference ground 11 and a radiation source 12, and wherein the radiation source 12 is provided at one side of the reference ground 11 in a spaced state from the reference ground 11.
Corresponding to fig. 1A and fig. 1B, the radiation source 12 is configured as a unit radiation source, the radiation source 12 has a single number of radiation elements 121, wherein, corresponding to fig. 1A, the radiation element 121 has two feeding points 1211, wherein the two feeding points 1211 are orthogonally arranged, and connecting lines of the two feeding points 1211 and a physical central point 1212 of the radiation element 121 are perpendicular to each other, so that two feeding points 1211 of the radiation element 121 are connected to excitation signals with a 90 ° phase difference by means of phase difference feeding to realize a circular polarization configuration of the transmitting antenna 10; corresponding to fig. 1B, the radiation element 121 has at least three feeding points 1211, wherein each of the feeding points 1211 is arranged around the physical center point 1212 of the radiation element 121 at the same distance, and an angle between a connecting line between any two adjacent feeding points 1211 and the physical center point 1212 of the radiation element 121 is equal to 360 °/n corresponding to a direction around the physical center point 1212 of the radiation element 121, where n is the number of the feeding points 1211 of the radiation element 121, so that the circularly polarized configuration of the transmitting antenna 10 is realized by sequentially accessing excitation signals with a 360 °/n difference between the feeding points 1211 of the radiation element 121 in the direction around the physical center point 1212 of the radiation element 121 by means of phase difference feeding, in particular, in the transmitting antenna 10 illustrated in fig. 1B, the number of the feeding points 1211 of the radiation element 121 is 4, and an angle between a connecting line between any two adjacent feeding points 1211 and the physical center point 1212 of the radiation element 121 is equal to 90 ° in a direction around the physical center point 1212 of the radiation element 121, so that excitation signals with a 90 ° difference are sequentially input to the feeding points 1211 of the radiation element 121 in a direction around the physical center point 1212 of the radiation element 121 in a phase difference feeding manner, so as to implement a circular polarization form of the transmitting antenna 10.
Corresponding to fig. 1C, the radiation source 12 is disposed in a multi-element radiation source configuration, and at least three radiation elements 121 are disposed corresponding to the radiation source 12, wherein each radiation element 121 has a feeding point 1211, and each radiation element 121 is circumferentially arranged such that, in a circumferential arrangement direction of the radiation elements 121, an angle between a connecting line between the feeding point 1211 and a physical central point 1212 of any two adjacent radiation elements 121 is equal to 360 °/m, where m is the number of the radiation elements 121, so that excitation signals with a difference of 360 °/m are sequentially connected to the feeding point 1211 of each radiation element 121 in the circumferential arrangement direction of the radiation elements 121 in a phase-difference feeding manner to achieve a circular polarization configuration of the transmitting antenna 10. Preferably, each of the radiation elements 121 further satisfies that, while an angle between a connecting line between the feeding point 1211 and the physical center point 1212 of any two adjacent radiation elements 121 is equal to 360 °/m when the circumferential arrangement direction of the radiation elements 121 is satisfied, the connecting line between the feeding point 1211 and the physical center point 1212 of the radiation element 121 intersects at a point, and distances from the feeding point 1211 of each radiation element 121 to the point are the same, or satisfies that the connecting line between the feeding point 1211 and the physical center point 1212 of each radiation element 121 intersects to form a regular polygon corresponding to the number of the radiation elements 121, and distances from the feeding point 1211 of each radiation element 121 to midpoints of the regular polygon are the same, specifically, in the transmitting antenna 10 illustrated in fig. 1C, the number of the radiation elements 121 is four, corresponding to the circumferential arrangement direction of the radiation elements 121, an included angle between a connecting line between the feeding point 1211 of any two adjacent radiating elements 121 and the physical center point 1212 thereof is equal to 90 °, and the connecting line between the feeding point 1211 of each radiating element 121 and the physical center point 1212 thereof intersects to form a positive quadrangle, and the feeding point 1211 of each radiating element 121 has the same distance from a midpoint of the positive quadrangle. In this way, the circular polarization form of the transmitting antenna 10 is realized in a manner of being based on phase difference feeding, and the stability of the circular polarization form of the transmitting antenna 10 is guaranteed.
It is worth mentioning that, in the embodiments of the present invention, based on the difference of the feeding structures of the radiation elements 121, the definition of the positions of the feeding points 1211 differs, specifically, in the state of the feeding structure in which the radiation elements 121 adopt probe feeding or microstrip feeding (including microstrip corner feeding), the feeding point 1211 corresponds to a point on the radiation elements 121 to access a feeding signal (including an excitation signal), and in the state of the feeding structure in which the radiation elements 121 adopt edge feeding, the feeding point 1211 corresponds to a midpoint of an edge on the radiation elements 121 to access a feeding signal (including an excitation signal) based on coupling, and in the description of the present invention, in the state in which the transmitting antenna 10 is set in a planar patch antenna state, the description of the feeding point 1211 does not constitute a limitation on the feeding structure of the radiation elements 121.
In addition, in some embodiments of the present invention, when the transmitting antenna 10 is configured in a planar patch antenna configuration, two feeding points 1211 connected to the same radiating element 121 and having the same phase as the excitation signal are connected to the same radiating element 121, and a structural state in which a centerline of a connection line of the two feeding points 1211 passes through a physical center point 1212 of the radiating element 121 is equivalent to the feeding point 1211 at the midpoint of the connection line of the two feeding points 1211 in the description of the present invention, which is not limited in this respect.
Preferably, in the embodiments of the present invention, the radiating element 121 is further directly and/or equivalently grounded at the physical center point 1212 thereof, specifically, a structural state in which the radiating element 121 is directly grounded at the physical center point 1212 thereof is formed based on the electrical connection between the radiating element 121 and the ground reference 11, and a structural state in which the radiating element 121 is equivalently grounded at the physical center point 1212 thereof is formed based on the electrical connection between at least one group and/or at least one pair of grounding points on the radiating element 121 and the ground reference 11, wherein the grounding points of the same group are located at the vertices of the same regular polygon with the physical center point 1212 of the radiating element 121 as the midpoint, and the corresponding grounding points of the same group are arranged at equal angles around the physical center point 1212 of the radiating element 121 in a state of equal distance from the physical center point 1212 of the radiating element 121, the same pair of grounding points are symmetrically distributed on the radiating element 121 about the physical center point 1212 of the radiating element 121, and the connecting line segment corresponding to the same pair of grounding points is centered about the physical center point 1212 of the radiating element 121, so that the impedance of the transmitting antenna 10 is reduced by forming a zero potential point at the physical center point 1212 of the radiating element 121 and a direct and/or equivalent connection with the reference ground 11, and the frequency bandwidth of the transmitting antenna 10 is narrowed at the expense of the improvement of the precision requirement of the transmitting antenna 10 in structure and size, thereby improving the immunity of the transmitting antenna 10, reducing the precision requirement of the transmitting antenna 10, and being beneficial to reducing the production cost of the transmitting antenna 10.
Further, referring to fig. 2A and 2B of the drawings of the present specification, different embodiments of implementing differential feeding of a phase difference of more than 90 ° to the transmitting antenna 10 in a linear polarization direction of the transmitting antenna 10 in a state of the transmitting antenna 10 adopting a linear polarization state based on a phase difference feeding manner are illustrated, wherein the transmitting antenna 10 is disposed in a planar patch antenna state to have a reference ground 11 and a radiation source 12, wherein the radiation source 12 is disposed at one side of the reference ground 11 in a state of being spaced apart from the reference ground 11.
Corresponding to fig. 2A, the radiation source 12 is configured in a unit radiation source configuration, the radiation source 12 has a single number of radiation elements 121, the radiation element 121 has two feeding points 1211, wherein the two feeding points 1211 are arranged in opposite phase, the connecting direction from one feeding point 1211 to the physical central point 1212 of the radiation element 121 coincides with the connecting direction from the other feeding point 1211 to the physical central point 1212 of the radiation element 121, then the radiation element 121 has a linearly polarized polarization configuration in a state that the feeding point 1211 is connected to an excitation signal and takes the connecting direction of the two feeding points 1211 as the linear polarization direction, so that in a manner of feeding by phase difference, the differential feeding to the transmission antenna 10 is realized in the linear polarization direction of the transmission antenna 10 in a state that the two feeding points 1211 of the radiation element 121 are connected to excitation signals with a phase difference of more than 90 °, so as to reduce the loss generated by the transmitting antenna 10 based on the electric field coupling effect during the initial polarization process and reduce the minimum transmitting power extreme value of the transmitting antenna 10, thereby ensuring the stable transmission of the microwave beam in the form of micro-signals by the transmitting antenna 10 in the state of reducing the transmitting power of the transmitting antenna 10 to the target transmitting power.
Preferably, in this embodiment of the present invention, the two feeding points 1211 of the radiating element 121 are arranged symmetrically with respect to the physical center point 1212 of the radiating element 121, so that in a phase difference feeding manner, in a state that the two feeding points 1211 of the radiating element 121 access excitation signals with a phase difference of about 180 °, a balanced differential feeding is implemented on the transmitting antenna 10 in the linear polarization direction of the transmitting antenna 10, so as to further reduce the minimum transmitting power extremum of the transmitting antenna 10 based on the loss generated by the electric field coupling effect during the initial polarization process of the transmitting antenna 10, thereby ensuring stable transmission of the microwave beam in a micro-signal form by the transmitting antenna 10 in a state of reducing the transmitting power of the transmitting antenna 10 to the target transmitting power.
Corresponding to fig. 2B, the radiation source 12 is configured in a binary radiation source configuration, and has two radiation elements 121 corresponding to the radiation source 12, wherein each of the radiation elements 121 has a feeding point 1211, wherein the two radiation elements 121 are arranged in an inverted phase, and a connection direction of the feeding point 1211 of one of the radiation elements 121 to a physical central point 1212 is opposite to a connection direction of the feeding point 1211 of the other radiation element 121 to the physical central point, then the two radiation elements 121 have a polarization configuration of linear polarization in a state that the two feeding points 1211 are connected to an excitation signal, and have a connection direction of the two feeding points 1211 as a linear polarization direction, so that in a manner of feeding by phase difference, differential feeding to the transmission antenna 10 is realized in a state that the two feeding points 1211 of the two radiation elements 121 are connected to excitation signals with a phase difference of more than 90 ° in the linear polarization direction of the transmission antenna 10, so as to reduce the loss generated by the transmitting antenna 10 based on the electric field coupling effect during the initial polarization process and reduce the minimum transmitting power extreme value of the transmitting antenna 10, thereby ensuring the stable transmission of the microwave beam in the form of micro-signals by the transmitting antenna 10 in the state of reducing the transmitting power of the transmitting antenna 10 to the target transmitting power.
Preferably, in this embodiment of the present invention, the two radiating elements 121 are arranged in a mirror image, so that in a manner of feeding by phase difference, in a state that the two feeding points 1211 of the radiating element 121 access excitation signals with phase difference approaching 180 °, balanced differential feeding is implemented to the transmitting antenna 10 in the linear polarization direction of the transmitting antenna 10, so as to further reduce the loss generated by the transmitting antenna 10 during the initial polarization process based on the electric field coupling effect and reduce the minimum transmitting power extreme value of the transmitting antenna 10, thereby ensuring stable transmission of the microwave beam in a micro-signal form by the transmitting antenna 10 in a state of reducing the transmitting power of the transmitting antenna 10 to the target transmitting power.
It is also worth mentioning that in both embodiments of the invention, based on the difference in the feeding structure of the radiating element 121, the position of the corresponding feeding point 1211 is defined differently, particularly in a state that the radiating element 121 adopts a feeding structure of probe feeding or microstrip feeding (including microstrip angle feeding), the feeding point 1211 corresponds to a point on the radiating element 121 to which a feeding signal (including an excitation signal) is coupled, and a state of the feeding structure in which the radiating element 121 adopts an edge feed, the feeding point 1211 corresponds to a midpoint of an edge of the radiating element 121 which is coupled into a feeding signal (including an excitation signal) based on a coupling effect, in the description of the present invention, in a state where the transmitting antenna 10 is set in a planar patch antenna state, the description of the feeding point 1211 does not constitute a limitation on the feeding structure of the corresponding radiating element 121.
In addition, in some embodiments of the present invention, when the transmitting antenna 10 is configured in a planar patch antenna configuration, two feeding points 1211 connected to the same phase of the excitation signal on the same radiating element 121 have a structure where a centerline of a connection line of the two feeding points 1211 passes through a physical center point 1212 of the radiating element 121, which is equivalent to the feeding point 1211 at the midpoint of the connection line of the two feeding points 1211 in the description of the present invention, and the present invention is not limited thereto.
Preferably, in the embodiments of the present invention, the radiation element 121 is further directly and/or equivalently grounded at the physical center point 1212 thereof, and particularly, a structural state in which the radiation element 121 is directly grounded at the physical center point 1212 thereof is formed based on an electrical connection between the physical center point 1212 of the radiation element 121 and the ground reference 11, and a structural state in which the radiation element 121 is equivalently grounded at the physical center point 1212 thereof is formed based on an electrical connection between at least one group and/or at least one pair of ground points on the radiation element 121 and the ground reference 11, wherein the ground points of the same group are located at vertices of the same regular polygon with the physical center point 1212 of the radiation element 121 as a midpoint, and the ground points corresponding to the ground points in the same group are arranged at equal angles around the physical center point 1212 of the radiation element 121 in a state of equal distance from the physical center point 1212 of the radiation element 121, the same pair of grounding points are symmetrically distributed on the radiating element 121 with the physical center point 1212 of the radiating element 121, and the connecting line segment corresponding to the same pair of grounding points takes the physical center point 1212 of the radiating element 121 as the midpoint, so that a zero potential point is formed at the physical center point 1212 of the radiating element 121 and a direct and/or equivalent connection with the reference ground 11 is formed to reduce the impedance of the transmitting antenna 10, and the frequency bandwidth of the transmitting antenna 10 is narrowed correspondingly not at the expense of the improvement of the precision requirement of the transmitting antenna 10 in structure and size, thereby reducing the precision requirement of the transmitting antenna 10 while improving the immunity of the transmitting antenna 10, and being beneficial to reducing the production cost of the transmitting antenna 10.
Further, the minimum transmitting power extreme value of the transmitting antenna 10 is reduced based on a manner of reducing the self dielectric loss of the transmitting antenna 10, the microwave detecting device adopts a half-wave folded-back directional microwave detecting antenna as the transmitting antenna 10, reduces the self dielectric loss of the transmitting antenna 10 based on the structural characteristic that the half-wave folded-back directional microwave detecting antenna takes air as a medium to reduce the minimum transmitting power extreme value of the transmitting antenna 10, and further reduces the minimum transmitting power extreme value of the transmitting antenna 10 based on the high-gain characteristic of the half-wave folded-back directional microwave detecting antenna, so as to ensure stable transmission of the microwave beam in the form of the micro signal in a state of reducing the transmitting power of the transmitting antenna 10 to the target transmitting power.
As shown in fig. 3A and 3B corresponding to the drawings referring to the description of the present invention, the structures of the half-wave folded directional microwave detecting antenna 10A in the vertical structure and the horizontal structure are respectively exemplified.
Corresponding to fig. 3A, the half-wave folded directional microwave detecting antenna 10A of vertical structure includes a ground reference 11A, a half-wave oscillator 12A and two power feeding lines 13A, wherein the half-wave oscillator 12A has a wavelength electrical length greater than or equal to 1/2 and less than or equal to 3/4 and has two coupling sections 121A, wherein each of the coupling sections 121A has a wavelength electrical length greater than or equal to 1/6, one end of each of the coupling sections 121A is a feeding end 1211A of the coupling section 121A, and the other ends of the coupling sections 121A are two ends of the half-wave oscillator 12A, wherein a distance between the feeding ends 1211A is less than or equal to λ/4, a distance between the two ends of the half-wave oscillator 12A is greater than or equal to λ/128 and less than or equal to λ/6, so as to connect two poles of an excitation signal or two poles with a phase difference to the two feeding ends 1211A of the half-wave oscillator 12A respectively A signal feeding state in which both ends of the half-wave oscillator 12A can be coupled to each other with a phase difference therebetween, where λ is a wavelength parameter corresponding to the frequency of the excitation signal; wherein the half-wave vibrator 12A is spaced from the reference ground 11A in a state where a distance between both ends thereof and the reference ground 11A is λ/128 or more and λ/6 or less; the two feeder lines 13A are electrically connected to the corresponding feed ends 1211A, respectively, so that the half-wave oscillator 12A is fed by the feed ends 1211A of the half-wave oscillator 12A in a state where the two feeder lines 13A are electrically coupled to the corresponding feed circuits to access two poles of an excitation signal or access an excitation signal having a phase difference, and the half-wave oscillator 12A is spaced from the reference ground 11A by the electrical connection of the feeder lines 13A and the feed ends 1211A.
Corresponding to fig. 3B, the half-wave folded directional microwave detecting antenna 10A of the horizontal structure comprises a ground reference 11A, a half-wave oscillator 12A and a power feeding line 13A, wherein the half-wave oscillator 12A has a wavelength electrical length equal to or greater than 1/2 and equal to or less than 3/4, wherein the half-wave oscillator 12A is folded back to form a state where the distance between both ends thereof is equal to or greater than λ/128 and equal to or less than λ/6, wherein the half-wave oscillator 12A has a feeding point 121A, the feeding point 121A and one end of the half-wave oscillator 12A have a wavelength electrical length equal to or less than 1/6 along the half-wave oscillator 12A, so that in a state where the half-wave oscillator 12A is fed with a corresponding excitation signal being connected to the feeding point 121A, both ends of the half-wave oscillator 12A can be coupled to each other with a phase difference tending to be in opposite phase, wherein λ is a wavelength parameter corresponding to a frequency of the excitation signal; wherein the half-wave vibrator 12A is spaced from the reference ground 11A in a state where a distance between both ends thereof and the reference ground 11A is λ/128 or more and a distance between at least one end thereof and the reference ground 11A is λ/6 or less; one end of the power feeding line 13A is electrically connected to the feeding point 121A of the half-wave vibrator 12A, wherein the power feeding line 13A has a wavelength electrical length greater than or equal to 1/128 and less than or equal to 1/4, so that when the power feeding line 13A is electrically coupled to the corresponding feeding circuit at the other end thereof to receive the excitation signal, the half-wave vibrator 12A is fed at the feeding point 121A of the half-wave vibrator 12A in a state where the feeding point is electrically connected to the half-wave vibrator 12A via the power feeding line 13A and the half-wave vibrator 12A is spaced apart from the reference ground 11A.
Further, referring to fig. 4A to 4N of the drawings of the specification of the present invention, based on the manner of reducing the self dielectric loss of the transmitting antenna 10, the minimum transmitting power extreme value of the transmitting antenna 10 is reduced by combining to perform differential feeding on the transmitting antenna 10, and the present invention further provides a dual feed type differential antenna 10B, so as to reduce the minimum transmitting power extreme value of the transmitting antenna 10 in the state that the microwave detection apparatus adopts the dual feed type differential antenna 10B as the transmitting antenna 10, so as to ensure stable transmission of the microwave beam in the form of a micro-signal in the state that the transmitting power of the transmitting antenna 10 is reduced to the target transmitting power.
Corresponding to fig. 4A to 4N, the dual feed differential antenna includes a reference ground 11B and two strip-shaped elements 12B, wherein two ends of the two strip-shaped elements 12B, which are connected to excitation signals, are respectively used as feeding ends 121B of the two strip-shaped elements 12B, the two strip-shaped elements 12B extend from the two feeding ends 121B in the same lateral space of the reference ground 11B and respectively have a wavelength electrical length equal to or greater than 3/16 and equal to or less than 5/16, wherein the two strip-shaped elements 12B respectively have a coupling section 122B, wherein one end of the coupling section 122B, which is close to the feeding end 121B of the strip-shaped element 12B to which the coupling section belongs, is used as a proximal end of the coupling section 122B, and the two coupling sections 122B extend from the proximal end in opposite directions, so that the dual feed differential antenna 10B is used as the transmitting antenna 10, and the two feeding ends 121B of the two strip-shaped elements 12B are connected to differ by more than 90 °(s) ° in phase difference The phase-difference fed state of the excitation signal is based on the polarization state that the phase difference between the two strip-shaped oscillators 12B and the reference ground 11B is larger than 90 degrees to realize the polarization tending to linear polarization, and the structural state that the two coupling sections 122B extend from the near end in the opposite direction is based on the coupling between the two coupling sections 122B, and a common resonance frequency point is formed based on the mutual coupling between the two coupling sections 122B, namely, the double-ended feed type differential antenna 10B is used as the transmitting antenna 10, the phase difference of the excitation signal larger than 90 degrees is accessed to the two feeding ends 121B of the two strip-shaped oscillators 12B, the differential feeding to the transmitting antenna 10 is realized in the polarization direction tending to linear polarization of the transmitting antenna 10, and the minimum transmitting power extreme value of the transmitting antenna 10 is reduced in the state of guaranteeing the stable transmission of the microwave beam, and further, the stable transmission of the microwave beam in the form of a micro signal is ensured in a state of reducing the transmission power of the transmitting antenna 10 to the target transmission power.
Specifically, corresponding to fig. 4A, two of the strip-shaped oscillators 12B extend from two of the feeding terminals 121B in the same lateral spatial sequence of the reference ground 11B in a direction vertically away from the reference ground 11B, and extend toward each other at a position equidistant from the reference ground 11B to form the proximal ends of two of the coupling sections 122B at this position.
Corresponding to fig. 4B, two of the strip-shaped oscillators 12B extend from two of the feeding terminals 121B in the same lateral spatial order of the reference ground 11B in a direction vertically away from the reference ground 11B, extend toward each other at a position equidistant from the reference ground 11B to form the coupling section 122B, and extend in a direction vertically close to the reference ground 11B.
Corresponding to fig. 4C to 4N, the two coupling segments 122B extend from the proximal end in the offset direction and have an offset distance of λ/256 or more and λ/6 or less, i.e. the distance from any point on one coupling segment 122B to the other coupling segment 122B is λ/256 or more and λ/6 or less, where λ is a wavelength parameter corresponding to the frequency of the excitation signal.
Specifically, corresponding to fig. 4C to 4L, the two coupling sections 122B of the two strip-shaped oscillators 12B extend from the proximal ends toward each other in a mutually parallel offset direction.
Corresponding to fig. 4C, the two strip-shaped oscillators 12B extend in the direction away from the reference ground 11B vertically in the same lateral spatial order of the reference ground 11B from the two feeding terminals 121B, and extend in opposite directions parallel to each other at the same distance from the reference ground 11B, so as to form the proximal ends of the two coupling sections 122B at the same position.
Corresponding to fig. 4D, two of the strip-shaped oscillators 12B extend in the same lateral spatial sequence of the reference ground 11B from the two feeding terminals 121B in the direction vertically away from the reference ground 11B, extend in opposite directions at positions equidistant from the reference ground 11B in parallel offset directions to form the coupling sections 122B, and extend in the direction vertically close to the reference ground 11B.
Corresponding to fig. 4E, on the basis of the structure of the dual feed differential antenna illustrated in fig. 4D, one of the coupling sections 122B is electrically connected to the middle of the other coupling section 122B.
Corresponding to fig. 4F, the coupling section 122B has a change in cross-sectional area in the cross-sectional direction of the strip-shaped element 12B on the basis of the structure of the double-feed differential antenna illustrated in fig. 4D.
Corresponding to fig. 4G, two of the strip-shaped oscillators 12B extend in the direction perpendicular to and away from the reference ground 11B from the two feeding terminals 121B in the same lateral spatial order of the reference ground 11B, extend in the opposite directions parallel to each other in the offset direction at the positions equidistant from the reference ground 11B, extend in the direction perpendicular to and away from the reference ground 11B, and extend in the opposite directions parallel to each other in the offset direction at the positions equidistant from the reference ground 11B to form the coupling sections 122B.
Corresponding to fig. 4H, the two strip-shaped oscillators 12B extend in the direction vertically away from the reference ground 11B in the same lateral spatial order of the reference ground 11B from the two feeding terminals 121B, extend back in the mutually parallel offset directions at positions equidistant from the reference ground 11B, extend in the direction vertically away from the reference ground 11B, extend toward each other in the mutually parallel offset directions at positions equidistant from the reference ground 11B to form the coupling sections 122B, and extend in the direction vertically close to the reference ground 11B.
Corresponding to fig. 4I, two of the strip-shaped oscillators 12B extend in the direction vertically away from the reference ground 11B in the same lateral spatial order of the reference ground 11B from the two feeding terminals 121B, extend toward each other in the offset directions parallel to each other at positions equidistant from the reference ground 11B to form the coupling sections 122B, extend in the direction vertically close to the reference ground 11B, and extend toward each other again in the offset directions parallel to each other at positions equidistant from the reference ground 11B.
Corresponding to fig. 4J, the two strip-shaped oscillators 12B extend from the two feeding terminals 121B in the same lateral spatial order of the reference ground 11B in the direction away from the reference ground 11B, extend back to the opposite direction in parallel with the offset direction at the position equidistant from the reference ground 11B, extend in the direction away from the reference ground 11B in the perpendicular direction, extend toward each other in parallel with the offset direction at the position equidistant from the reference ground 11B to form the coupling section 122B, extend in the direction approaching the reference ground 11B in the perpendicular direction, and extend toward each other again in parallel with the offset direction at the position equidistant from the reference ground 11B.
Corresponding to fig. 4K, two strip-shaped oscillators 12B extend in the direction perpendicular to and away from the reference ground 11B from the two feeding terminals 121B in the same lateral space sequence of the reference ground 11B, and extend oppositely in the mutually parallel offset directions at different distances from the reference ground 11B to form the coupling sections 122B, wherein the lengths of the two coupling sections 122B are not limited to be the same.
Corresponding to fig. 4L, the two strip-shaped oscillators 12B extend from the two feeding terminals 121B in the same lateral space of the reference ground 11B in the direction perpendicular to and away from the reference ground 11B, are bent in order at positions equidistant from the reference ground 11B to extend in opposite directions in parallel to each other in the offset direction, are bent to extend in opposite directions in parallel to each other in the offset direction to form the coupling sections 122B, and are bent again to extend in opposite directions in parallel to each other in the offset direction.
Corresponding to fig. 4M and 4N, the two coupling sections 122B of the two strip-shaped oscillators 12B extend from the near end in opposite directions in a staggered manner. Specifically, corresponding to fig. 4M, the two strip-shaped oscillators 12B extend in the direction perpendicular to and away from the reference ground 11B from the two feeding terminals 121B in the same lateral space sequence of the reference ground 11B, and extend oppositely in the staggered direction of the opposite offset and away from the reference ground 11B at the same distance from the reference ground 11B to form the coupling section 122B. Corresponding to fig. 4N, the two strip-shaped oscillators 12B extend in the direction vertically away from the reference ground 11B in the same lateral spatial sequence of the reference ground 11B from the two feeding terminals 121B, extend in opposite directions away from the reference ground 11B at positions equidistant from the reference ground 11B to form the coupling sections 122B, and extend in the direction vertically away from the reference ground 11B at positions equidistant from the reference ground 11B.
It is worth mentioning that the dual-feed differential antenna has various structural forms, and when one end of the coupling segment 122B close to the feeding end 121B of the strip-shaped element 12B to which the coupling segment 122B belongs is a proximal end of the coupling segment 122B, in a state where the two coupling segments 122B extend from the proximal end in opposite directions, the extending direction of each coupling segment 122B is not limited to a fixed extending direction, that is, in some embodiments of the present invention, the two coupling segments 122B extend from the proximal end in dynamically opposite directions to form the coupling segment 122B in a curved shape, and similarly, in a state where the dual-feed differential antenna 10B is used as the transmitting antenna 10 and the two feeding ends 121B of the strip-shaped elements 12B are fed with excitation signals having a phase difference larger than 90 ° and fed with a phase difference, a linear polarization trend is realized based on the phase difference between the two strip-shaped elements 12B and the reference ground 11B being larger than 90 ° And a structural form extending in the opposite direction from the proximal end based on the two coupling sections 122B forms coupling between the two coupling sections 122B, and forms a common resonant frequency point based on mutual coupling between the two coupling sections 122B, which is not limited in the present invention.
In addition, in some embodiments of the present invention, the strip-shaped vibrator 12B is disposed in a microstrip line carried on a circuit board, which is not limited by the present invention.
It should be noted that, in a state of the transmitting antenna 10 adopting a linear polarization form, preferably in a linear polarization or a polarization direction tending to the linear polarization of the transmitting antenna 10, based on feeding the transmitting antenna 10 tending to a phase difference of 180 °, a balanced differential feeding of the transmitting antenna 10 is implemented, so as to reduce a minimum transmitting power extreme value of the transmitting antenna 10 in a state of ensuring stable transmission of the microwave beam, thereby ensuring stable transmission of the microwave beam in a micro signal form in a state of reducing the transmitting power of the transmitting antenna 10 to a target transmitting power.
Based on this, the present invention further provides a differential feed circuit, and in some embodiments of the present invention, the microwave detection apparatus includes the differential feed circuit, wherein in a state where the differential feed circuit is provided in the form of discrete components, corresponding to fig. 5A and 5B, the circuit structures of the differential feed circuit 20 of different embodiments are respectively illustrated.
Corresponding to fig. 5A and 5B, in this embodiment of the invention, the differential feed circuit has a three-pole circuit processor (corresponding to Q1 in the figure), an inductor (corresponding to L1 in the figure), a first resistor (corresponding to R1 in the figure), a second resistor (corresponding to R2 in the figure), a third resistor (corresponding to R3 in the figure), a first capacitor (corresponding to C1 in the figure), a second capacitor (corresponding to C2 in the figure), an oscillating capacitor (corresponding to C5 in the figure), and a power connection terminal (corresponding to Vcc in the figure) adapted to connect to a corresponding power source, wherein the three-pole circuit processor has a first connection terminal corresponding to the collector of the transistor or the drain of the MOS transistor, a second connection terminal corresponding to the base of the transistor or the gate of the MOS transistor, and a third connection terminal corresponding to the emitter of the transistor or the source of the MOS transistor, wherein one end of the second resistor is electrically connected to the first connection terminal of the three-pole circuit handler, the other end of the second resistor is connected to the power connection terminal via the inductor, and is grounded via the first capacitor, wherein one end of the third resistor is electrically connected to the third connection terminal of the three-pole circuit handler, the other end of the third resistor is grounded, wherein one end of the oscillation capacitor is electrically connected to the second connection terminal of the three-pole circuit handler, the other end of the oscillation capacitor is grounded, wherein one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit handler, the other end of the first resistor is electrically connected between the inductor and the second resistor corresponding to fig. 5A, or is electrically connected to the power connection terminal corresponding to fig. 5B, the two ends of the second capacitor are electrically connected to the first connection end and the third connection end of the three-pole circuit processor, respectively, wherein the second resistor and the third resistor are set to have equal resistance values, so that the excitation signal is output at the two ends of the second capacitor in a balanced differential signal form with a phase difference of approximately 180 degrees in a state that the differential feed circuit is connected to a corresponding power supply at the power supply connection end, and thus, the phase difference feed of approximately 180 degrees to the transmitting antenna is realized.
It is worth mentioning that the inductor functions to isolate ac and direct current to isolate the high frequency ac excitation signal from the power supply voltage signal, the first capacitor is a decoupling capacitor, can prevent the circuit from generating parasitic oscillation caused by a positive feedback path formed by a power supply and prevent the current fluctuation generated in the power supply circuit by the current size change of the front circuit and the back circuit from influencing the normal operation of the circuit, wherein, since one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit processor to provide a divided current to the second connection terminal of the three-pole circuit processor, the inductor does not participate in the voltage division, therefore, the other end of the first resistor may be electrically connected between the inductor and the second resistor corresponding to fig. 5A, or may be electrically connected to the power connection terminal corresponding to fig. 5B.
Further, in the two embodiments of the present invention, the differential feeding circuit further has a third capacitor (corresponding to C3 in the figure) and a fourth capacitor (corresponding to C4 in the figure), wherein the third capacitor and the fourth capacitor are electrically connected to two ends of the second capacitor, respectively, so as to output the excitation signal in a balanced differential signal form with a phase difference approaching 180 ° through the third capacitor and the fourth capacitor, thereby realizing phase difference feeding of the transmitting antenna approaching 180 °.
It should be noted that, corresponding to the differential feeding circuit illustrated in fig. 5A and 5B, in other embodiments of the present invention, the inductor may not be disposed, and one end of the second resistor is electrically connected to the first connection terminal of the three-pole circuit processor, the other end of the second resistor is electrically connected to the power connection terminal, and is grounded via the first capacitor, one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the first resistor is electrically connected to the power connection terminal.
It should be noted that, in the embodiments of the present invention, the first capacitor, the second capacitor, the third capacitor, the fourth capacitor and the oscillating capacitor can be disposed in a microstrip distributed capacitor manner in an actual circuit structure, which is not limited by the present invention.
Referring further to fig. 6 of the drawings accompanying the present specification, a partial circuit structure of a differential feed circuit according to an embodiment of the present invention is illustrated, wherein the differential feed circuit is provided in the form of an integrated circuit and outputs the excitation signal in the form of a balanced differential signal with a phase difference of approximately 180 ° in a differential oscillation circuit.
Specifically, the differential oscillation circuit has two N-channel MOS transistors (corresponding to Q1 and Q2 in the figure), two P-channel MOS transistors (corresponding to Q3 and Q4 in the figure), an oscillation inductor (corresponding to L in the figure) and an oscillation capacitor (corresponding to C in the figure), wherein the sources of the two N-channel MOS transistors are electrically connected, the sources of the two P-channel MOS transistors are electrically connected, the drains of the two N-channel MOS transistors are electrically connected to the drains of different P-channel MOS transistors, respectively, so as to form a sequential connection relationship that the drain of one of the N-channel MOS transistors is electrically connected to the drain of one of the P-channel MOS transistors, the source of the P-channel MOS transistor is electrically connected to the source of the other P-channel MOS transistor, the drain of the other P-channel MOS transistor is electrically connected to the drain of the other N-channel MOS transistor, and the source of the other N-channel MOS transistor is electrically connected to the source of the previous N-channel MOS transistor, wherein a gate of one of the N-channel MOS transistors is electrically connected to a drain of the other N-channel MOS transistor, a gate of one of the P-channel MOS transistors is electrically connected to a drain of the other P-channel MOS transistor, two ends of the oscillation inductor are electrically connected to drains of different P-channel MOS transistors, and two ends of the oscillation capacitor are electrically connected to drains of different P-channel MOS transistors in parallel, so that oscillation and frequency selection are formed by a parallel resonant circuit formed by the oscillation inductor and the oscillation capacitor, and electrical signals having the same magnitude and opposite directions are formed at two ends of the oscillation inductor and the oscillation capacitor, so that one of the N-channel MOS transistors and the P-channel MOS transistor electrically connected to the gate of the N-channel MOS transistor can be turned on at the same time, the other N-channel MOS tube and the P-channel MOS tube electrically connected with the grid electrode of the N-channel MOS tube can be conducted at the same time at the other moment, so that the excitation signal is output at two ends of the oscillation inductor in a balanced differential signal form with a phase difference of 180 degrees.
With further reference to fig. 7A to 7D of the drawings accompanying the present specification, in a state where the differential feed circuit is provided in the form of an integrated circuit and the differential oscillation circuit outputs the excitation signal in the form of a balanced differential signal with a phase difference of approximately 180 °, structural block diagrams of the microwave detecting apparatus according to various embodiments of the present invention are illustrated.
Wherein the differential feed circuit comprises a low dropout linear regulator (corresponding to the internal LDO in the figure), the differential oscillating circuit, an oscillator (corresponding to the Osc in the figure), a phase-locked loop (corresponding to the PLL in the figure) and a logic control unit, wherein the low dropout linear regulator provides a constant voltage for the differential oscillating circuit in a powered state, wherein the oscillator is configured such that the logic control unit provides a basic clock signal and is externally arranged with a quartz crystal oscillator or is integrally arranged with an internal oscillating circuit in the logic control unit, wherein the logic control unit is arranged with a DSP, a MCU or a RAM and is electrically connected to the oscillating inductor of the differential oscillating circuit, wherein the phase-locked loop is electrically connected between the logic control unit and the differential oscillating circuit in a state of being externally or integrated with the logic control unit, based on the feedback of the logic control unit to the excitation signal output by the differential oscillating circuit, the frequency/phase of the excitation signal output by the differential oscillating circuit in a balanced differential signal form with a 180-degree difference at two ends of the oscillating inductor is calibrated, so that the stable output of the excitation signal in the balanced differential signal form by the differential feed circuit is guaranteed.
It should be noted that, for the purpose of reducing the cost of the differential feed circuit, in some embodiments of the present invention, the phase-locked loop may not be provided, that is, the logic control unit is electrically connected to the differential oscillating circuit, so as to control and maintain the stability of the frequency/phase of the excitation signal outputted by the differential oscillating circuit in the form of balanced differential signals with a 180 ° difference between two ends of the oscillating inductor by the logic control unit based on the feedback of the excitation signal outputted by the differential oscillating circuit.
Further, in these embodiments of the present invention, the differential feeding circuit further includes two amplifiers (corresponding to PA1 and PA2 directly led out from the differential oscillating circuit in the figure) for amplifying the excitation signals outputted from the differential oscillating circuit in a balanced differential signal form, wherein the logic control unit is electrically connected to the oscillating inductor of the differential oscillating circuit in a state of being electrically connected to at least one of the amplifiers, so as to receive feedback of the amplifiers on the excitation signals outputted from the differential oscillating circuit.
It is worth mentioning that in a state where the microwave beam is in a weak signal form based on the reduction of the transmitting power of the transmitting antenna, although the above-mentioned series of advantages are exhibited, since the strength of the corresponding echo signal is simultaneously reduced, in a state where there is environmental electromagnetic interference in the corresponding target detection space, the corresponding doppler intermediate frequency signal is more susceptible to interference of environmental electromagnetic radiation, and it is difficult to accurately feed back the motion characteristics corresponding to the human body movement, the inching motion, and the breathing and heartbeat motions. Based on this, the microwave detection apparatus illustrated in fig. 7A to 7C corresponding to the drawings of the present specification, the corresponding microwave detection method further includes a method step of improving the accuracy of the echo signal, so as to ensure the accuracy and stability of the microwave detection method and apparatus for detection of the activity characteristics corresponding to the human body movement, the micromotion, and the respiration and heartbeat movements based on the improvement of the accuracy of the echo signal in a state where the intensity of the echo signal is reduced based on the transmission power of the transmission antenna (TX in the corresponding diagram).
Specifically, the method step of improving the accuracy of the echo signal includes the step of accessing the echo signal in a balanced differential signal form from a receiving antenna (corresponding to RX in the figure) of the microwave detection device, so that the electromagnetic interference in the environment exists in a common-mode interference form in the echo signal, and can be suppressed during the receiving and transmitting processes of the echo signal in the balanced differential signal form, and subsequently, corresponding to fig. 7D, outputting the doppler intermediate frequency signal in the balanced differential signal form based on the mixing processing step of the echo signal in the balanced differential signal form, and forming the digitized form of the doppler intermediate frequency signal in the balanced differential signal form based on the digitized conversion of the doppler intermediate frequency signal in the balanced differential signal form by an a/D conversion unit, wherein a data processing unit connected to the a/D conversion unit is configured to be capable of forming the digitized form of the doppler intermediate frequency signal in the balanced differential signal form based on the digitized feature of common-mode interference The corresponding algorithm suppresses (including eliminates) common-mode interference information in the digitized morphology of the doppler intermediate frequency signal in the balanced differential signal morphology, so as to form the doppler intermediate frequency signal in the digitized morphology free from environmental electromagnetic interference according to the further suppressing processing of the common-mode interference information in the digitized morphology of the doppler intermediate frequency signal in the balanced differential signal morphology based on the corresponding algorithm, thereby improving the feedback accuracy of the doppler intermediate frequency signal in the digitized morphology to the activity characteristics corresponding to the human body movement action, the micromotion action, and the respiration and heartbeat action; or subsequently, corresponding to fig. 7B and 7C, outputting the doppler intermediate frequency signal in a balanced differential signal form based on a step of mixing the echo signal in a balanced differential signal form and outputting the doppler intermediate frequency signal in a single-ended signal form based on a step of differential to single-ended processing the doppler intermediate frequency signal in a balanced differential signal form, in order to further suppress common-mode interference in the echo signal and/or the doppler intermediate frequency signal in a balanced differential signal form based on a step of mixing the echo signal in a balanced differential signal form and/or a step of differential to single-ended processing the doppler intermediate frequency signal in a balanced differential signal form, for example by taking advantage of the characteristic of constant amplitude asymmetry of common-mode interference in the signal in a differential signal form having symmetrical characteristic, by a step of differential to single-ended processing based on the principle of differencing The Doppler intermediate-frequency signal in a single-ended signal form free of environmental electromagnetic interference is output under the action of counteraction in the superposition process, so that the feedback accuracy of the Doppler intermediate-frequency signal on the motion characteristics corresponding to the movement action, the inching action and the breathing and heartbeat actions of a human body is improved; or subsequently, corresponding to fig. 7A, outputting the echo signal in the form of a single-ended signal free from environmental electromagnetic interference based on further suppressing effect of the step of processing the echo signal in the form of a balanced differential signal from differential to single-ended signal on common-mode interference in the echo signal in the form of a balanced differential signal, and outputting the doppler intermediate frequency signal free from environmental electromagnetic interference based on the step of processing the echo signal in the form of a single-ended signal free from environmental electromagnetic interference by frequency mixing, thereby improving the feedback accuracy of the doppler intermediate frequency signal on activity characteristics corresponding to human body movement, micromotion, and respiration and heartbeat, corresponding to the step of accessing the echo signal in the form of a balanced differential signal from the receiving antenna of the microwave detection device with micro-transmitting power and the processing system of a balanced differential signal constructed in subsequent steps, the microwave detection method and the device for guaranteeing the micro-transmitting power have the advantages of ensuring the detection range and the detection accuracy and stability of the activity characteristics corresponding to the movement action, the micro-movement action, the breathing action and the heartbeat action of the human body.
It is worth mentioning that, since the echo signal is in a balanced differential signal form when being accessed from the receiving antenna, and the electromagnetic radiation interference in the environment exists in a common mode interference form in the echo signal, it can be suppressed during the receiving and transmitting processes of the echo signal in the balanced differential signal form, i.e. the echo signal includes both the signal corresponding to the reflected echo formed by the microwave beam emitted by the transmitting antenna being reflected by the corresponding object and the electromagnetic radiation interference signal in the common mode interference form, so that no matter what corresponds to fig. 7D, the doppler intermediate frequency signal in the balanced differential signal form is output in the subsequent mixing processing step based on the echo signal in the balanced differential signal form, and the digitized form of the doppler intermediate frequency signal in the balanced differential signal form is formed based on the digitized conversion of the doppler intermediate frequency signal in the balanced differential signal form by the a/D conversion unit, and the common-mode interference information in the digitized morphology of the Doppler intermediate frequency signal in the form of the balanced differential signal is suppressed by a corresponding algorithm based on the digitized characteristics of the common-mode interference by the data processing unit; or to fig. 7B and 7C to output the doppler intermediate frequency signals in a balanced differential signal form in a subsequent mixing processing step based on the echo signals in a balanced differential signal form and to output the doppler intermediate frequency signals in a single-ended signal form in a subsequent differential-to-single-ended processing step based on the doppler intermediate frequency signals in a balanced differential signal form; or the echo signal in single-ended signal form outputted in the following processing step of converting the echo signal into single-ended signal form based on the balanced differential signal form, and the doppler intermediate frequency signal outputted in the processing step of mixing the echo signal in single-ended signal form based on the balanced differential signal form, based on the common-mode interference suppression effect of the processing step of converting the doppler intermediate frequency signal into single-ended signal form, wherein the echo signal in balanced differential signal form and/or the doppler intermediate frequency signal in balanced differential signal form are processed by mixing the echo signal in balanced differential signal form and/or the processing step of converting the doppler intermediate frequency signal into single-ended signal form based on the digitized characteristics of common-mode interference in the processing step of converting the echo signal into differential signal form corresponding to fig. 7D and fig. 7B and fig. 7C Further suppression of common mode interference, or the further suppression of common mode interference in the echo signals in the balanced differential signal form based on the differential-to-single-ended processing step of the echo signals in the balanced differential signal form corresponding to fig. 7A, the doppler intermediate frequency signals in the digitized form or the analog signal form that are finally output are all free from environmental electromagnetic interference, so that the feedback accuracy of the doppler intermediate frequency signals on the activity characteristics corresponding to human body movement, micromotion, and respiration and heartbeat can be improved, the processing system of the balanced differential signals constructed by the step of accessing the echo signals in the balanced differential signal form from the receiving antenna of the microwave detection device with micro transmitting power and the subsequent steps is corresponded, the microwave detection method and device for micro transmitting power guarantee the microwave detection method and device for micro transmitting power on the motion of human body, The detection range and the detection accuracy and stability of the micro-motion, the respiration and the heartbeat motion corresponding to the activity characteristics.
Correspondingly, the microwave detecting apparatus further includes a mixing circuit and a differential-to-single-ended circuit corresponding to fig. 7A to 7C, wherein the mixing circuit is electrically connected between the differential oscillating circuit and the receiving antenna to output the doppler intermediate frequency signal in a single-ended signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal corresponding to fig. 7A based on the mixing process of the echo signals in the excitation signal and single-ended signal form, or output the doppler intermediate frequency signal in a differential signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal corresponding to fig. 7B and 7C based on the mixing process of the echo signals in the excitation signal and balanced differential signal form; accordingly, the differential to single-ended circuit is disposed between the receiving antenna and the mixing circuit corresponding to FIG. 7A, outputting the echo signals in a single-ended signal form free from electromagnetic environment interference to the mixer circuit by performing differential-to-single-ended processing on the echo signals in a balanced differential signal form based on a differencing principle, or is arranged to be electrically connected to the mixing circuit corresponding to fig. 7B and 7C to receive the doppler intermediate frequency signals in differential signal form outputted from the mixing circuit and to perform differential-to-single-ended processing on the doppler intermediate frequency signals in differential signal form based on the principle of difference finding to output the doppler intermediate frequency signals in single-ended signal form free from electromagnetic environment interference, therefore, the feedback accuracy of the Doppler intermediate frequency signal to the activity characteristics corresponding to the human body movement action, the micro-motion action, the respiration action and the heartbeat action is improved.
Corresponding to fig. 7D, the microwave detecting device further comprises a mixing circuit and an a/D converting unit and a data processing unit, wherein the mixing circuit is electrically connected between the differential oscillating circuit and the receiving antenna to output the doppler intermediate frequency signals in a differential signal form corresponding to the frequency/phase difference between the excitation signals and the echo signals based on the mixing process of the excitation signals and the echo signals in a balanced differential signal form, wherein the a/D converting unit is electrically connected to the mixing circuit in a structural state integrated with or external to the data processing unit to digitize the doppler intermediate frequency signals in a balanced differential signal form to form a digitized form of the doppler intermediate frequency signals in a balanced differential signal form, the data processing unit is arranged in a structural state integrated with the logic control unit or independent from the logic control unit and is capable of suppressing (including eliminating) common-mode interference information in a digitized form of the Doppler intermediate frequency signal in a balanced differential signal form by a corresponding algorithm based on the digitized feature of the common-mode interference, for example, the Doppler intermediate frequency signal in the balanced differential signal form has the feature of two signals with equal amplitude and opposite phase relative to a reference potential, the Doppler intermediate frequency signal in the balanced differential signal form can be converted into two sets of numerical data with equal absolute value relative to the reference potential value and opposite change trend of numerical value in a time domain based on the digitized conversion processing of the Doppler intermediate frequency signal in the balanced differential signal form, so that the two sets of numerical data are sequentially added with two sets of numerical data with equal numerical value and same change trend of numerical value in the time domain based on the common-mode interference, and the two sets of numerical data with equal numerical value and same change trend of numerical value are displayed in the time domain based on the common-mode interference And the digitization characteristic is that the common-mode interference information in the digitization form of the Doppler intermediate frequency signal which balances the differential signal form is inhibited or even eliminated by an algorithm of subtracting the two sets of numerical data or an algorithm of filtering the numerical data which does not accord with the opposite change trend by comparing the two sets of numerical data, and the digitization form of the Doppler intermediate frequency signal which is free from the electromagnetic environment interference is correspondingly obtained, so that the feedback accuracy of the Doppler intermediate frequency signal to the motion characteristics corresponding to the movement action, the inching action and the respiration and heartbeat actions of the human body is improved. Or the difference component generated based on the common-mode interference is eliminated through the difference or comparison of the two sets of numerical data after corresponding operation processing, for example, the two sets of numerical data are independently processed based on corresponding operation to obtain two sets of control data, and then the difference component generated based on the common-mode interference is eliminated through comparison and analysis based on the two sets of control data, so as to output an accurate control result.
Further, corresponding to fig. 7A, in a state where the mixing circuit is configured to output the doppler intermediate frequency signal in a single-ended signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal based on the mixing process of the echo signal in the excitation signal and the single-ended signal form, the microwave detecting apparatus optionally includes another differential to single-ended circuit, wherein the differential to single-ended circuit is configured between the differential oscillating circuit and the mixing circuit to output the excitation signal in a single-ended signal form free from electromagnetic environment interference to the mixing circuit based on the differential to single-ended process of the excitation signal in a differential signal form, so as to facilitate an improvement in accuracy of the doppler intermediate frequency signal in a single-ended signal form output from the mixing circuit, correspondingly secure the doppler intermediate frequency signal pair with a human body moving motion, Fine motion, and feedback accuracy of motion characteristics corresponding to respiration and heartbeat motions. That is, in a state where the differential-to-single-ended circuit is not provided, the excitation signal in a single-ended signal form may be selectively output to the mixer circuit by directly extracting the excitation signal in a single-ended signal form from the differential oscillator circuit, which is not limited in the present invention.
It is worth mentioning that, based on the difference in the usage/transmission path of the signals derived from the differential oscillating circuits, in some documents in the art, the names of the signals derived from the respective oscillating circuits may be different, for example, in some documents in the art, the transmission object of the signals derived from the respective oscillating circuits is an antenna for feeding the respective antenna is called an excitation signal, and the transmission object of the derived signals is a mixer is called a local oscillation signal, the invention is not limited thereto, i.e. in the description of the invention, the same names are used for the excitation signal derived from the differential oscillating circuit and transmitted to the transmitting antenna and the excitation signal also derived from the differential oscillating circuit and transmitted to the mixer circuit in order to facilitate understanding that the excitation signals are both provided by the differential oscillating circuit, the designation of the excitation signal itself does not constitute a limitation of its use/transmission path.
Corresponding to fig. 7B to 7D, in a state where the mixing circuit is set to output the doppler intermediate frequency signal of a balanced differential signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal of a balanced differential signal form based on the mixing processing of the excitation signal and the echo signal of a balanced differential signal form, the mixer circuit illustrated in figure 7C may alternatively correspond to the integrated version of the mixer circuit of figure 7B arranged for two mixing processes of the excitation signal and the echo signal in a single ended signal version, outputting the Doppler intermediate frequency signal in a differential signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal with a mixing process based on the mixing circuit for the excitation signal and the echo signal in a differential signal form.
It is understood that, in some embodiments of the present invention, the mixing circuit may be optionally implemented as an integrated form of the mixing circuit and the differential to single-ended circuit corresponding to fig. 7A to 7C, and the mixing circuit is configured to output the doppler intermediate frequency signal of a single-ended signal form in a state of switching in the echo signal and the excitation signal of a balanced differential signal form, including but not limited to outputting the doppler intermediate frequency signal of a single-ended signal form based on the differential to single-ended processing of the echo signal of a balanced differential signal form and the mixing processing of the echo signal and the excitation signal of a single-ended signal form corresponding to fig. 7A, or outputting the doppler intermediate frequency signal of a single-ended signal form based on the mixing processing of the echo signal and the excitation signal of a balanced differential signal form and the mixing processing of the single-ended doppler intermediate frequency signal of a balanced differential signal form corresponding to fig. 7B and 7C The doppler intermediate frequency signal, which is not limited by the present invention.
Specifically, the signal based on the balanced differential signal form has two paths of signals which have equal-amplitude and opposite-phase relative to the reference potential and have symmetrical characteristics, in some embodiments of the present invention, the differential-to-single-ended circuit is configured to perform the inverse phase processing on one of the two paths of signals based on the signal in the differential signal form, and output the signal in the single-ended signal form after being superimposed on the other path of signals, so that the common-mode interference information in the signal in the balanced differential signal form can be suppressed or even eliminated by using the equal-amplitude and asymmetrical characteristics of the common-mode interference in the signal in the differential signal form with symmetrical characteristics based on the differential-to-single-ended processing on the signal in the balanced differential signal form by the differential-to-single-ended circuit.
In these embodiments of the present invention, when the mixing circuit is implemented in a fully integrated manner corresponding to the mixing circuit and the differential-to-single-ended circuit in fig. 7A to 7C to implement that the mixing circuit outputs the doppler intermediate frequency signal in a single-ended signal form in a state of accessing the echo signal and the excitation signal in a balanced differential signal form, the mixing circuit may be further implemented to output the doppler intermediate frequency signal in a single-ended signal form sequentially based on an inversion process on one of two signals of the echo signal in a balanced differential signal form, a mixing process on the two signals respectively, and a superposition process on the two doppler intermediate frequency signals output by the mixing process, so as to suppress or even eliminate interference information generated by corresponding common-mode interference.
In other embodiments of the present invention, when the mixing circuit is implemented as a partially integrated form corresponding to the mixing circuit and the differential-to-single-ended circuit in fig. 7A to 7C, so as to output the doppler intermediate frequency signal in a single-ended signal form by the mixing circuit in a state of accessing the echo signal and the excitation signal in a balanced differential signal form, the mixing circuit may be implemented as a reverse-phase processing unit sequentially based on one of two signals of the echo signal in a balanced differential signal form, and a mixing processing unit respectively outputting the doppler intermediate frequency signal in a two-way single-ended signal form for the two-way signal, so as to be able to suppress or even eliminate interference information caused by corresponding common-mode interference based on a superposition processing unit for the two-way intermediate frequency doppler signals, or generate interference information in a time domain equal absolute value with respect to a reference potential value based on a digital conversion unit for the two-way doppler intermediate frequency signals, in succession And the two groups of numerical data with the same numerical value change trend are represented by the digitalized characteristics of the two groups of numerical data with the same absolute value and the opposite numerical value change trends respectively added to the two groups of numerical data on the time domain according to the common-mode interference, and the digitalized form of the Doppler intermediate frequency signal free from the electromagnetic environment interference is correspondingly obtained by inhibiting or even eliminating the interference information generated based on the common-mode interference through an algorithm of summing the two groups of numerical data or an algorithm of filtering the numerical data which do not accord with the same change trends through the comparison of the two groups of numerical data, so that the feedback accuracy of the Doppler intermediate frequency signal to the activity characteristics corresponding to the movement action, the inching action and the breathing and heartbeat actions of the human body is improved. Or the difference component generated based on the common-mode interference is eliminated through the difference or comparison of the two sets of numerical data after corresponding operation processing, for example, the two sets of numerical data are independently processed based on corresponding operation to obtain two sets of control data, and then the difference component generated based on the common-mode interference is eliminated through comparison and analysis based on the two sets of control data, so as to output an accurate control result.
It should be noted that, in some embodiments of the present invention, the echo signal and/or doppler intermediate frequency signal in balanced differential signal form is further amplified, for example, on the basis of the circuit structure illustrated in fig. 7A, a corresponding amplifying circuit adapted to amplify signals in differential signal form is further disposed between the receiving antenna and the corresponding differential-to-single-ended circuit to amplify and output the echo signal in balanced differential signal form to the differential-to-single-ended circuit, or on the basis of the circuit structures illustrated in fig. 7B to 7C, a corresponding amplifying circuit adapted to amplify signals in differential signal form is further disposed between the receiving antenna and the mixing circuit and/or between the mixing circuit and the differential-to-single-ended circuit to amplify and output the echo signal in balanced differential signal form to the mixing circuit and/or amplify and output the multiple echo signals in differential signal form The present invention also does not limit the above-mentioned problem, wherein preferably, a circuit having electrical characteristics of amplifying signals in differential signal form, such as a circuit of a meter amplifier, is used for the differential to single-ended conversion circuit, so as to simultaneously implement the amplification processing and the single-ended conversion processing of signals in differential signal form, thus, it is simple and easy to operate.
In particular, in some embodiments of the present invention, the processing step of amplifying the echo signal and/or the doppler intermediate frequency signal in a single-ended signal form is further included, for example, on the basis of the circuit structure illustrated in fig. 7A, a corresponding amplifying circuit adapted to amplify the signal in a single-ended signal form is further disposed between the differential-to-single-ended circuit and the mixing circuit and/or at the output end of the mixing circuit, so as to amplify the echo signal in a single-ended signal form to the mixing circuit and/or amplify the doppler intermediate frequency signal in a single-ended signal form, or on the basis of the circuit structures illustrated in fig. 7B and 7C, a corresponding amplifying circuit adapted to amplify the signal in a single-ended signal form is further disposed at the output end of the differential-to-single-ended circuit, so as to amplify the doppler intermediate frequency signal in a single-ended signal form, the invention is not limited in this regard.
Further, in some embodiments of the present invention, the step of accessing the echo signal of a balanced differential signal form from a receiving antenna of the microwave detection device includes accessing the echo signal of a balanced differential signal form based on a phase-shifting step of an echo signal accessed from one of the receiving feeding points (ends) in a state where the two receiving feeding points (ends) of the receiving antenna are orthogonally arranged, to secure an isolation between echo signals accessed from the two receiving feeding points (ends) of the receiving antenna based on an orthogonal form between the two receiving feeding points (ends) of the receiving antenna, corresponding to securing an accuracy of the echo signal of a balanced differential signal form accessed based on a phase-shifting step of an echo signal accessed from one of the receiving feeding points (ends).
As shown in fig. 8A to 8D of the accompanying drawings referring to the present specification, the echo signals of the balanced differential signal form are accessed based on the phase shift step of the echo signal accessed to one of the two receiving feeding points (ends) of the receiving antenna in a state where the two receiving feeding points (ends) of the receiving antenna are orthogonally arranged, and the structural forms of the receiving antenna of the different embodiments are illustrated, wherein the reference numbers of the receiving antenna and the names of the corresponding structures are adopted in the description and the drawings of the present invention based on the transceiving reciprocity characteristics of the antenna.
In both embodiments of the present invention, corresponding to fig. 8A and 8B, the receiving antenna 10 is exemplarily provided in a planar patch antenna configuration to have a reference ground 11 and a radiation source 12, wherein the radiation source 12 is provided on one side of the reference ground 11 in a spaced state from the reference ground 11.
Specifically, corresponding to fig. 8A, the radiation source 12 is configured in a unit radiation source form, the radiation source 12 has a single number of radiation elements 121, the radiation element 121 has two feeding points 1211, the two feeding points 1211 are orthogonally arranged, connecting lines of the two feeding points 1211 and a physical central point 1212 of the radiation element 121 are perpendicular to each other, one of the feeding points 1211 is electrically connected with a phase shifter, such as a microstrip line configured with a corresponding electrical length, so as to output the echo signals in a balanced differential signal form between one end of the phase shifter, which is far from the feeding point 1211, and the other feeding point 1211 based on the phase shifting processing of the phase shifter on the echo signals accessed from the feeding point 1211.
Corresponding to fig. 8B, the radiation source 12 is configured as a binary radiation source, and the radiation source 12 has two radiation elements 121, wherein each of the radiation elements 121 has a feeding point 1211, wherein the two radiation elements 121 are orthogonally arranged, a connection direction of the feeding point 1211 to the physical central point 1212 of one of the radiation elements 121 is perpendicular to a connection direction of the feeding point 1211 to the physical central point 1212 of the other radiation element 121, and one of the feeding points 1211 is electrically connected with a phase shifter, such as a microstrip line configured with a corresponding electrical length, so as to output the echo signal in a balanced differential signal form between an end of the phase shifter far from the feeding point 1211 and the other feeding point 1211 based on a phase shifting process of the phase shifter on the echo signal accessed from the feeding point 1211.
In both embodiments of the invention, the receiving antenna is arranged as an example with the half-wave folded directional microwave detection antenna 10A of orthogonal polarization, corresponding to fig. 8C and 8D.
Specifically, corresponding to fig. 8C, the half-wave folded-back directional microwave detecting antenna 10A of the horizontal structure with orthogonal polarization of the receiving antenna is disposed, the half-wave folded-back directional microwave detecting antenna 10A includes two half-wave oscillators 12A, wherein the two half-wave oscillators 12A are orthogonally arranged, the extending direction of the half-wave folded-back directional microwave detecting antenna 10A is perpendicular to the height direction of the reference ground 11A, the extending direction of the two half-wave oscillators 12A is perpendicular to the height direction of the half-wave folded-back directional microwave detecting antenna 10A, the feeding point 121A of one half-wave oscillator 12A is connected with a phase shifter via the feeding line 13A, such as a microstrip line disposed with a corresponding electrical length, to perform phase shift processing on the echo signal received from the feeding point 121A based on the phase shifter, the echo signals are output in a balanced differential signal form between one end of the phase shifter far from the feeding point 121A and the other feeding point 121A.
Corresponding to fig. 8D, the half-wave folded back directional microwave probe antenna 10A of the receiving antenna in a cross-polarized vertical structure is disposed, the half-wave folded back directional microwave probe antenna 10A includes two half-wave elements 12A, wherein the two half-wave elements 12A are orthogonally arranged, a direction of extension of the two half-wave elements 12A in a direction perpendicular to the reference ground 11A is perpendicular to a direction of height of the half-wave folded back directional microwave probe antenna 10A, wherein one of the feeding ends 1211A of one of the half-wave elements 12A is connected with a phase shifter such as a microstrip line disposed in a corresponding electrical length via the feeding line 13A for phase shifting processing of the echo signal inputted from the feeding end 1211A based on the phase shifter, and outputting the echo signal in a balanced differential signal form between one end of the phase shifter, which is far away from the feed end 1211A, and one feed end 1211A of the other half-wave oscillator 12A.
It is worth mentioning that in some preferred embodiments of the present invention, in the step of accessing the echo signal in balanced differential signal form from the receiving antenna of the microwave detection device, two receiving feeding points of the receiving antenna are arranged in opposite phase to directly access the echo signal in balanced differential signal form from the two receiving feeding points.
As shown in fig. 9A to 9E of the drawings corresponding to the description of the present invention, the echo signals in the form of balanced differential signals are directly received from the two receiving feeding points (ends) of the receiving antenna in a state where the two receiving feeding points (ends) are arranged in opposite phases, and the structural form of the receiving antenna in different embodiments is illustrated.
In both embodiments of the present invention, corresponding to fig. 9A and 9B, the receiving antenna 10 is exemplified in a planar patch antenna configuration to have a reference ground 11 and a radiation source 12, wherein the radiation source 12 is disposed on one side of the reference ground 11 in a spaced state from the reference ground 11.
Specifically, corresponding to fig. 9A, the radiation source 12 is configured in a unit radiation source form, and the radiation source 12 has a single number of radiation elements 121, wherein the radiation element 121 has two feeding points 1211, wherein the two feeding points 1211 are arranged in opposite phases, and a connection direction from one of the feeding points 1211 to a physical center point 1212 of the radiation element 121 coincides with a connection direction from the other feeding point 1211 to the physical center point 1212 of the radiation element 121, so as to output the echo signals in a balanced differential signal form at the two feeding points 1211 based on a structural state that the two feeding points 1211 are arranged in opposite phases.
Preferably, in this embodiment of the present invention, the two feeding points 1211 of the radiating element 121 are arranged symmetrically with respect to the physical center point 1212 of the radiating element 121, such that the two feeding points 1211 are arranged in opposite phases, and the two feeding points 1211 are arranged at equal distances from the physical center point 1212 of the radiating element 121, and the echo signals in a balanced differential signal form with a phase difference of 180 ° are output at the two feeding points 1211.
Corresponding to fig. 9B, the radiation source 12 is configured in a binary radiation source form, and has two radiation elements 121 corresponding to the radiation source 12, wherein each of the radiation elements 121 has a feeding point 1211, wherein the two radiation elements 121 are arranged in an inverted state, and a connection direction of the feeding point 1211 to the physical central point 1212 of one of the radiation elements 121 and a connection direction of the feeding point 1211 to the physical central point of the other radiation element 121 are opposite to each other, so that the two feeding points 1211 output the echo signals in a balanced differential signal form based on a structural state that the two radiation elements 121 are arranged in an inverted state.
Preferably, in this embodiment of the present invention, the two radiating elements 121 are arranged in a mirror image, so that the two feeding points 1211 output the echo signals in a balanced differential signal form with a phase difference of 180 ° at the two feeding points 1211 based on the structural state that the two radiating elements 121 are arranged in opposite phase and the two feeding points 1211 are equidistant from the physical central point 1212 of the radiating element 121 to which the two feeding points 1211 belong.
In both embodiments of the present invention, the receiving antenna is exemplified by the half-wave folded directional microwave detecting antenna 10A with opposite polarization, corresponding to fig. 9C and 9D.
Specifically, corresponding to fig. 9C, the half-wave folded-back directional microwave detecting antenna 10A of the horizontal structure with the receiving antenna polarized in opposite phase is disposed, and the half-wave folded-back directional microwave detecting antenna 10A includes two half-wave oscillators 12A, wherein the two half-wave oscillators 12A are arranged in opposite phase, and the direction perpendicular to the reference ground 11A is the height direction of the half-wave folded-back directional microwave detecting antenna 10A, and the two half-wave oscillators 12A are reversed from the feeding point 121A in the extending direction perpendicular to the height direction of the half-wave folded-back directional microwave detecting antenna 10A, so as to output the echo signal in a balanced differential signal form at the two feeding points 121A based on the structural state that the two half-wave oscillators 12A are arranged in opposite phase.
Corresponding to fig. 9D, the half-wave folded-back directional microwave detecting antenna 10A of the receiving antenna in a vertical structure with reverse polarization is disposed, the half-wave elements 12A corresponding to the half-wave folded-back directional microwave detecting antenna 10A are arranged in reverse phase, i.e., in a direction perpendicular to the reference ground 11A as a height direction of the half-wave folded-back directional microwave detecting antenna 10A, the half-wave elements 12A are reversed from the two feeding terminals 1211A in an extending direction perpendicular to the height direction of the half-wave folded-back directional microwave detecting antenna 10A, so as to output the echo signals in a balanced differential signal form at the two feeding terminals 1211A based on a structural state that the half-wave elements 12A are arranged in reverse phase.
In this embodiment of the present invention, corresponding to fig. 9E, the receiving antenna is exemplified by the double-fed differential antenna 10B, so that the two strip-shaped elements 12B are formed in a structure state in which the polarization directions tending to linear polarization are arranged in opposite phases based on a structural characteristic that the two coupling sections 122B of the two strip-shaped elements 12B extend from the proximal end in opposite directions and can be coupled with each other to form a common resonant frequency point, and thus the echo signals in a balanced differential signal form can be directly output at the two feeding ends 121B when the double-fed differential antenna 10B is used as a receiving antenna.
It should be noted that, in other embodiments of the present invention, in a state that the microwave beam is in a weak signal form due to the transmitting power of the transmitting antenna being reduced to a target transmitting power, the doppler intermediate frequency signal pair is increased to perform a human body movement action and a micromotion action in a manner of increasing the strength of the echo signal, and the accuracy and stability of the feedback of the activity characteristics corresponding to the breathing and heartbeat movements, the respective transmit antennas allow to be set in an orthogonal polarization configuration, the radiation sources are orthogonally arranged in a binary radiation source configuration corresponding to a state in which the transmitting antennas are arranged in a planar patch antenna configuration, namely, the radiation source is provided with two radiation elements, and the direction of a connecting line from the feeding point to a physical central point of one radiation element is opposite to and vertical to the direction of a connecting line from the feeding point to a physical central point of the other radiation element; and in the state that the transmitting antenna is set by the half-wave folded-back directional microwave detection antenna, the half-wave folded-back directional microwave detection antenna is set in an orthogonal polarization state, namely, the half-wave folded-back directional microwave detection antenna comprises two half-wave oscillators, wherein the two half-wave oscillators are orthogonally arranged, and correspondingly, the direction perpendicular to the reference ground direction is taken as the height direction of the half-wave folded-back directional microwave detection antenna, and the extending directions of the two half-wave oscillators perpendicular to the height direction of the half-wave folded-back directional microwave detection antenna are mutually perpendicular.
It should be noted that, in some embodiments of the present invention, different combinations of the transmitting antenna and the receiving antenna of the above embodiments can be integrally disposed in a form of separate transceiving or a form of combining transceiving in a structural form that shares the reference ground, thereby facilitating the miniaturization design of the microwave detection apparatus.
For example, referring to fig. 10A to 10J of the drawings of the present specification, based on different combinations of the transmitting antenna and the receiving antenna of the above embodiments, the transmitting antenna and the receiving antenna integrally provided in a transmission/reception separated form or a transmission/reception integrated form in a structural form sharing the reference ground are illustrated.
Corresponding to fig. 10A, based on the combination of the transmitting antenna illustrated in fig. 1A and the receiving antenna illustrated in fig. 8A, in the structural configuration that the transmitting antenna and the receiving antenna share the ground reference 11 and the radiation source 12, the integral structure of the transmitting antenna and the receiving antenna is illustrated, wherein the integral structure of the transmitting antenna and the receiving antenna has the ground reference 11 and the radiation source 12, wherein the radiation source 12 is disposed on one side of the ground reference 11 in a state of being spaced apart from the ground reference 11, wherein the radiation source 12 is disposed in a unit radiation source configuration, corresponding to the radiation source 12, having a single number of radiation elements 121, wherein the radiation elements 121 have four feeding points 1211, wherein an included angle between connecting lines between any two adjacent feeding points 1211 and a physical central point 1212 of the radiation element 121 in a direction around the physical central point 1212 of the radiation element 121 is equal to 90 °, the circularly polarized configuration of the transmitting antenna 10 is realized in a state of sequentially accessing excitation signals different by 90 ° to two adjacent ones of the feeding points 1211 in a direction around a physical center point 1212 of the radiating element 121 by phase-difference feeding, and the echo signal in a form of a balanced differential signal is output between one of the feeding points 1211 of the two feeding points 1211 and an end of the phase shifter distant from the other feeding point 1211 based on a phase-shifting process of the phase shifter on the echo signal accessed from the feeding point 1211 in a manner of accessing the phase shifter to one of the other feeding points 1211 in a direction around the physical center point 1212 of the radiating element 121, so as to form an integral structure of the transmitting antenna and the receiving antenna in a transceiving separated form.
Corresponding to fig. 10B and 10C, based on the combination of the transmitting antenna illustrated in fig. 2A and the receiving antenna illustrated in fig. 9A, in a structural configuration in which the transmitting antenna and the receiving antenna share the reference ground 11, an integrated structure of the transmitting antenna and the receiving antenna of different embodiments is illustrated, wherein the integrated structure of the transmitting antenna and the receiving antenna has the reference ground 11 and the radiation source 12, wherein the radiation source 12 is disposed on one side of the reference ground 11 in a state of being spaced apart from the reference ground 11, wherein corresponding to fig. 10B, the radiation source 12 is disposed in a unit radiation source configuration, corresponding to the radiation source 12, having a single number of radiation elements 121, wherein the radiation elements 121 have four feeding points 1211, wherein in a direction around a physical center point 1212 of the radiation elements 121, an included angle between any two adjacent feeding points 1211 and a connecting line between the physical center points 1212 of the radiating elements 121 is equal to 90 °, and a structural state that the two opposite feeding points 1211 are arranged in opposite phase is correspondingly formed, so that differential feeding to the transmitting antenna 10 is realized in a state that the two opposite feeding points 1211 of the radiating elements 121 are connected to excitation signals with a phase difference larger than 90 °, and the echo signals in a balanced differential signal form are output from the two opposite feeding points 1211, so as to form an integrated structure of the transmitting antenna and the receiving antenna in a transceiving separated form; corresponding to fig. 10C, the radiation source 12 is configured as a binary radiation source, and has two radiation elements 121 corresponding to the radiation source 12, wherein each of the radiation elements 121 has two feeding points 1211, wherein the two feeding points 1211 of each of the radiation elements 121 are arranged in opposite phases, a connection direction from one of the feeding points 1211 to the physical central point 1212 of each of the radiation elements 121 coincides with a connection direction from the other of the feeding points 1211 to the physical central point 1212 thereof, so that a polarization direction of each of the radiation elements 121 corresponds to a connection direction of the two feeding points 1211 thereof, wherein the two radiation elements 121 are arranged orthogonally, and a polarization direction of one of the radiation elements 121 is perpendicular to a polarization direction of the other radiation element 121, such that differential feeding to the transmitting antenna 10 is realized in a manner of feeding by phase difference in a state in which the two feeding points 1211 of one of the radiation elements 121 are connected to excitation signals having a phase difference greater than 90 °, and outputting the echo signals in a balanced differential signal form at the two feeding points 1211 of the other radiating element 121, so as to form an integrated structure of the transmitting antenna and the receiving antenna in a transceiving separation mode.
Corresponding to fig. 10D, on the basis of the receiving antenna illustrated in fig. 8B, the transmitting antenna arranged in the orthogonal polarization state is combined for the purpose of improving the intensity of the echo signal, and the integral structure of the transmitting antenna and the receiving antenna is illustrated in the structural form that the transmitting antenna and the receiving antenna share the reference ground 11, wherein the integral structure of the transmitting antenna and the receiving antenna has the reference ground 11 and the radiation source 12, wherein the radiation source 12 is arranged on one side of the reference ground 11 in a state of being spaced apart from the reference ground 11, wherein the radiation source 12 is arranged in the quaternary radiation source state, corresponding to the radiation source 12, having four radiation elements 121, wherein each of the radiation elements 121 has a feeding point 1211, wherein each of the radiation elements 121 is arranged circumferentially and satisfies the circumferential arrangement direction of the radiation elements 121, the angle between the connection line between the feeding point 1211 of any two adjacent radiating elements 121 and the physical center point 1212 thereof is equal to 90 degrees, one of the feeding points 1211 is electrically connected to a phase shifter, so that the echo signals in a balanced differential signal form are output between one end of the phase shifter far from the feeding point 1211 and another feeding point 1211 adjacent to the feeding point 1211 in the circumferential arrangement direction of the radiating element 121 based on the phase shifting processing of the phase shifter on the echo signals accessed from the feeding point 1211, and in the state that the other two feeding points 1211 are connected with the excitation signal, based on the orthogonal polarization state of the two radiation elements 121 to which the two feeding points 1211 belong, the intensity of the echo signal is improved, so as to form an integral structure of the transmitting antenna and the receiving antenna in a transceiving separated form.
Corresponding to fig. 10E, based on the combination of the transmitting antenna illustrated in fig. 2B and the receiving antenna illustrated in fig. 9B, a structure of the transmitting antenna and the receiving antenna sharing the reference ground 11 is illustrated, wherein the structure of the transmitting antenna and the receiving antenna is an integrated structure, the integrated structure of the transmitting antenna and the receiving antenna has the reference ground 11 and the radiation source 12, the radiation source 12 is disposed on one side of the reference ground 11 in a state of being spaced from the reference ground 11, the radiation source 12 is disposed in a form of a quaternary radiation source, the radiation source 12 has four radiation elements 121, each radiation element 121 has a feeding point 1211, each radiation element 121 is circumferentially arranged and satisfies that in a circumferential arrangement direction of the radiation elements 121, an included angle between a connecting line between the feeding point 1211 and a physical central point 1212 of any two adjacent radiation elements 121 is equal to 90 ° degree Wherein, two feeding points 1211 of two radiation elements 121 opposite in the circumferential arrangement direction of the radiation elements 121 are used as transmitting feeding points, differential feeding to the transmitting antenna 10 is realized in a state that the two feeding points 1211 are connected to excitation signals with a phase difference larger than 90 ° by means of phase difference feeding, and the echo signals in a form of balanced differential signals are output at the other two feeding points 1211, so as to correspondingly form an integrated structure of the transmitting antenna and the receiving antenna in a transmitting-receiving separation mode.
Particularly, in the two embodiments of the present invention corresponding to fig. 10D and 10E, in the circumferential arrangement direction of the radiation elements 121, in two opposite radiation elements 121, a connection line from the feeding point 1211 to the physical central point 1212 of one radiation element 121 and a connection line from the feeding point 1211 to the physical central point 1212 of the other radiation element 121 are staggered and opposite, and the connection line between the feeding point 1211 and the physical central point 1212 of each radiation element 121 correspondingly formed intersects to form a regular quadrilateral structure, so as to facilitate reducing the radial area occupied by the arrangement of the radiation elements 121.
Corresponding to fig. 10F, on the basis of the receiving antenna illustrated in fig. 8C, the transmitting antenna arranged in the orthogonal polarization form is combined for the purpose of increasing the intensity of the echo signal, and the structural form of the reference ground 11A is shared by the transmitting antenna and the receiving antenna, and the integral structure of the transmitting antenna and the receiving antenna is illustrated, wherein the transmitting antenna and the receiving antenna are respectively arranged in the half-wave folded-back directional microwave detecting antenna 10A of the orthogonal polarization horizontal structure, the half-wave folded-back directional microwave detecting antenna 10A includes four half-wave vibrators 12A, wherein the four half-wave vibrators 12A are arranged in the circumferential direction and satisfy the circumferential arrangement direction of the half-wave vibrators 12A, and any two adjacent half-wave vibrators 12A are arranged orthogonally corresponding to the height direction of the half-wave folded-back directional microwave detecting antenna 10A in the direction perpendicular to the reference ground 11A In a configuration in which any two adjacent half-wave oscillators 12A are perpendicular to each other in an extending direction perpendicular to a height direction of the half-wave folded directional microwave detecting antenna 10A in a circumferential arrangement direction of the half-wave oscillators 12A, the feeding point 121A of one of the half-wave oscillators 12A is connected to a phase shifter via the feeding line 13A, the echo signal inputted from the feeding point 121A is subjected to phase shift processing by the phase shifter, the echo signal in a balanced differential signal form is outputted between one end of the phase shifter remote from the feeding point 121A and another feeding point 121A adjacent to the feeding point 121A in the circumferential arrangement direction of the half-wave oscillator 12A, and in a state in which excitation signals are inputted to the other two feeding points 121A, the two half-wave oscillators 12A to which the two feeding points 121A belong are orthogonally arranged, and improving the strength of the echo signal so as to form an integrated structure of the transmitting antenna and the receiving antenna in a transceiving separation mode.
Corresponding to fig. 10G, on the basis of the receiving antenna illustrated in fig. 9C, the transmitting antenna provided in a reverse-phase polarization form is combined for the purpose of improving the accuracy of the echo signal, and a structural form of the reference ground 11A is shared by the transmitting antenna and the receiving antenna, and an integrated structure of the transmitting antenna and the receiving antenna is illustrated, wherein the transmitting antenna and the receiving antenna are respectively provided in the half-wave folded-back type directional microwave detecting antenna 10A of a reverse-phase polarization horizontal type structure, the half-wave folded-back type directional microwave detecting antenna 10A includes four half-wave vibrators 12A, wherein the four half-wave vibrators 12A are arranged circumferentially and satisfy a circumferential arrangement direction of the half-wave vibrators 12A, and any two adjacent half-wave vibrators 12A are arranged orthogonally, corresponding to a height of the half-wave folded-back type directional microwave detecting antenna 10A in a direction perpendicular to the reference ground 11A direction In the circumferential arrangement direction of the half-wave oscillators 12A, the extension directions of any two adjacent half-wave oscillators 12A in the direction perpendicular to the height direction of the half-wave folded directional microwave detection antenna 10A are perpendicular to each other, wherein two feeding points 121A of the two half-wave oscillators 12A opposite in the circumferential arrangement direction of the half-wave oscillators 12A are used as transmitting feeding points, differential feeding to the transmitting antenna is realized in a state that excitation signals with a phase difference larger than 90 ° are connected to the two feeding points 121A in a phase difference feeding manner, and echo signals in a balanced differential signal form are output from the other two feeding points 121A, so that an integrated structure of the transmitting antenna and the receiving antenna in a transceiving separation form is correspondingly formed.
Corresponding to fig. 10H, on the basis of the receiving antenna illustrated in fig. 8D, the transmitting antenna configured in an orthogonal polarization form is combined, specifically, the receiving antenna is the transmitting antenna, and an integrated structure of the transmitting antenna and the receiving antenna is illustrated, wherein the transmitting antenna and the receiving antenna are configured in the half-wave folded-back directional microwave detecting antenna 10A of a vertical structure of the same orthogonal polarization, the half-wave folded-back directional microwave detecting antenna 10A includes two half-wave oscillators 12A, two half-wave oscillators 12A are orthogonally arranged, and an extending direction of the two half-wave oscillators 12A in a direction perpendicular to a height direction of the half-wave folded-back directional microwave detecting antenna 10A is perpendicular to a direction of the reference ground 11A, one of the feeding ends 1211A of the half-wave oscillators 12A is connected to a phase shifter through the feeding line 13A, so as to output the echo signal in a balanced differential signal form between one end of the phase shifter, which is far away from the feeding end 1211A of the half-wave oscillator 12A, and one of the feeding ends 1211A of the other half-wave oscillator 12A based on the phase shift processing of the echo signal accessed from the feeding end 1211A by the phase shifter, and to increase the intensity of the echo signal based on the structural form that the two half-wave oscillators 12A to which the two feeding ends 1211A belong are orthogonally arranged in a state that the other two feeding ends 1211A are accessed with an excitation signal, thereby forming an integrated structure of the transmitting antenna and the receiving antenna in a transceiving form.
Corresponding to fig. 10I, based on the combination of the transmitting antenna illustrated in fig. 3A and the receiving antenna illustrated in fig. 9D, in the structural form that the transmitting antenna and the receiving antenna share the reference ground 11A, the integrated structure of the transmitting antenna and the receiving antenna is illustrated, wherein the transmitting antenna and the receiving antenna are respectively provided with the half-wave folded-back directional microwave detection antenna 10A of the vertical structure of the opposite-phase polarization, the integrated structure corresponding to the transmitting antenna and the receiving antenna includes two half-wave oscillators 12A, wherein each of the half-wave oscillators 12A is arranged in the opposite phase, and the two half-wave oscillators 12A are arranged orthogonally to each other, and corresponding to the height direction of the half-wave folded-back directional microwave detection antenna 10A in the direction perpendicular to the reference ground 11A, each of the half-wave oscillators 12A is arranged from the two feeding terminals 1211A in the height direction perpendicular to the half-wave folded-back directional microwave detection antenna 10A The extending direction of the two half-wave oscillators 12A is reversed, and the extending directions of the two half-wave oscillators 12A in the direction perpendicular to the height direction of the half-wave folded directional microwave detecting antenna 10A are perpendicular to each other, so that based on the structural state that each half-wave oscillator 12A is arranged in reverse phase, the two feeding ends 1211A of one half-wave oscillator 12A output the echo signals in a balanced differential signal form, and the state that the two feeding ends 1211A of the other half-wave oscillator 12A are connected with excitation signals with a difference of more than 90 degrees realizes differential feeding to the transmitting antenna, thereby forming an integrated structure of the transmitting antenna and the receiving antenna in a transmitting and receiving separation mode.
In particular, in correspondence with the integrated structure of the transmitting antenna and the receiving antenna illustrated in fig. 10H and 10I, each half-wave element 12A is shifted from the two feeding terminals 1211A in the extending direction perpendicular to the height direction of the half-wave folded-back directional microwave detecting antenna 10A, wherein the state in which the two half-wave elements 12A are orthogonally arranged corresponds to the structural form in which the four feeding terminals 1211A are located at the four vertex positions of the square having the connection line of the two feeding terminals 1211A of each half-wave element 12A as two diagonal lines, so as to maintain the state in which the distance between the two feeding terminals 1211A of each half-wave element 12A is equal to or less than λ/4 and the distance between the two ends of each half-wave element 12A is equal to or greater than λ/128 and equal to or less than λ/6, which is advantageous in the state in which the two half-wave elements 12A are orthogonally arranged, based on the structure form that the extending directions of the two feeding ends 1211A of the half-wave oscillators 12A in the direction perpendicular to the height direction of the half-wave folded directional microwave detecting antenna 10A are staggered and reversed, the stability of the integrated structure of the transmitting antenna and the receiving antenna under the corresponding volume limitation due to the too close distance between the feeding end 1211A of one half-wave oscillator 12A and the feeding end 1211A of the other half-wave oscillator 12A is avoided.
Corresponding to fig. 10J, on the basis of the receiving antenna illustrated in fig. 9E, based on the purpose of improving the accuracy of the echo signal, based on the transceiving reciprocity characteristic of the antenna, the receiving antenna is the transmitting antenna, and the integral structure of the transmitting antenna and the receiving antenna is illustrated, wherein the receiving antenna is exemplified by the double-feed differential antenna 10B, so that the two strip-shaped elements 12B are formed in a structural state in which they are arranged in opposite phases in the polarization direction tending to linear polarization based on the structural characteristic that the two coupling sections 122B of the two strip-shaped elements 12B extend in opposite directions from the near end and can be coupled with each other to form a common resonant frequency point, and thus the echo signal in a balanced differential signal form can be directly output at the two feeding ends 121B when the double-feed differential antenna 10B is used as a receiving antenna, and when the double-feed differential antenna 10B is used as a transmitting antenna, the differential feed to the transmitting antenna is realized in the polarization direction of the transmitting antenna, which tends to be linearly polarized, by accessing the state of excitation signals with a phase difference of more than 90 ° at the two feed ends 121B of the two strip-shaped oscillators 12B, so as to form an integrated structure of the transmitting antenna and the receiving antenna in a transceiving integrated mode.
In response to the above description, the microwave detection method according to an embodiment of the present invention includes the following steps:
A. feeding the transmitting antenna with an excitation signal with a phase difference larger than 90 degrees in the polarization direction of the transmitting antenna tending to linear polarization by means of phase difference feeding so as to realize differential feeding of the transmitting antenna with the phase difference larger than 90 degrees;
B. accessing the echo signals with phase difference of 180 degrees and in a balanced differential signal form from the receiving antenna; and
C. outputting the Doppler intermediate frequency signals in a single-ended signal form with a frequency/phase difference between the excitation signals and the echo signals based on the step (C1) or the step (C2) with a mixing processing step and a differential-to-single-ended processing step, wherein in the step (C1), the echo signals in a single-ended signal form are output based on a differential-to-single-ended processing of the echo signals in a balanced differential signal form by the differential-to-single-ended circuit, and the Doppler intermediate frequency signals in a single-ended signal form are output based on a mixing processing of the excitation signals and the echo signals in a single-ended signal form by the mixing circuit, wherein in the step (C2), the Doppler intermediate frequency signals in a balanced differential signal form are output based on a mixing processing of the excitation signals and the echo signals in a balanced differential signal form by the mixing circuit, and outputting the Doppler intermediate frequency signal in a single-ended signal form based on differential-to-single-ended processing of the Doppler intermediate frequency signal in a balanced differential signal form by the differential-to-single-ended circuit.
In some embodiments of the present invention, corresponding to fig. 2A, the transmitting antenna is configured with a reference ground 11 and a radiation source 12 in a planar patch antenna configuration, wherein the radiation source 12 is configured at one side of the reference ground 11 in a spaced state from the reference ground 11, the radiation source 12 is configured in a unit radiation source configuration, the radiation source 12 has a single number of radiation elements 121, the radiation element 121 has two feeding points 1211, wherein the two feeding points 1211 are arranged in an inverted state, a connection direction from one of the feeding points 1211 to a physical central point 1212 of the radiation element 121 coincides with a connection direction from the other feeding point 1211 to a physical central point 1212 of the radiation element 121, and then the radiation element 121 has a linear polarization configuration in a state that the feeding point 1211 is connected to an excitation signal, and the connection direction of the two feeding points 1211 is a linear polarization direction, in this way, in a manner of feeding by phase difference, the differential feeding to the transmitting antenna is implemented in the linear polarization direction of the transmitting antenna in a state that the two feeding points 1211 of the radiating element 121 access the excitation signals with a phase difference greater than 90 °.
In some embodiments of the present invention, corresponding to fig. 2B, the transmitting antenna is configured with a reference ground 11 and a radiation source 12 in a planar patch antenna configuration, wherein the radiation source 12 is configured at one side of the reference ground 11 in a spaced state from the reference ground 11, the radiation source 12 is configured in a binary radiation source configuration, the radiation source 12 has two radiation elements 121, each of the radiation elements 121 has a feeding point 1211, the two radiation elements 121 are arranged in an inverted state, a connection direction of the feeding point 1211 to a physical central point 1212 of one of the radiation elements 121 is opposite to a connection direction of the feeding point 1211 to a physical central point of the other radiation element 121, and then the two radiation elements 121 have a linear polarization configuration in a state that the two feeding points 1211 are connected to an excitation signal, and a connection direction of the two feeding points 1211 is a linear polarization direction, in this way, in a manner of feeding by phase difference, the differential feeding to the transmitting antenna is implemented in the linear polarization direction of the transmitting antenna in a state that the two feeding points 1211 of the two radiating elements 121 access the excitation signals with a phase difference greater than 90 °.
In some embodiments of the present invention, corresponding to fig. 3A, the transmitting antenna is configured as the half-wave folded directional microwave detecting antenna in a vertical structure, and includes a ground reference 11A, a half-wave oscillator 12A and two power feeding lines 13A, wherein the half-wave oscillator 12A has a wavelength electrical length greater than or equal to 1/2 and less than or equal to 3/4 and has two coupling sections 121A, wherein each of the coupling sections 121A has a wavelength electrical length greater than or equal to 1/6, one end of each of the coupling sections 121A is the feeding end 1211A of the coupling section 121A, and the other end of each of the coupling sections 121A is the two ends of the half-wave oscillator 12A, wherein the distance between the feeding ends 1211A is less than or equal to λ/4, the distance between the two ends of the half-wave oscillator 12A is greater than or equal to λ/128 and less than or equal to λ/6, then, the half-wave oscillator 12A is fed by accessing two poles of the excitation signal or accessing the excitation signal with a phase difference to the two feeding ends 1211A, the two ends of the half-wave oscillator 12A can form a phase difference to form a polarization mode tending to linear polarization in a mutual coupling manner, and when the direction perpendicular to the reference ground 11A is the height direction of the half-wave folded-back directional microwave detecting antenna 10A, the extending direction of the half-wave oscillator 12A in the direction perpendicular to the height direction of the half-wave folded-back directional microwave detecting antenna 10A is the linear polarization direction, so that the differential feeding to the transmitting antenna is realized in the linear polarization direction of the transmitting antenna in the state that the two feeding ends 1211A of the half-wave oscillator access the excitation signal with a phase difference larger than 90 ° in the phase difference manner.
In some embodiments of the present invention, the transmitting antenna is disposed corresponding to the half-wave folded back type directional microwave detecting antenna 10A of the horizontal type structure in which the receiving antenna is polarized in reverse phase as illustrated in fig. 9C, the half-wave folded back type directional microwave detecting antenna 10A includes two half-wave oscillators 12A, wherein the two half-wave oscillators 12A are arranged in reverse phase, corresponding to a height direction of the half-wave folded back type directional microwave detecting antenna 10A in a direction perpendicular to the reference ground 11A, the two half-wave oscillators 12A are reversed in an extending direction perpendicular to the height direction of the half-wave folded back type directional microwave detecting antenna 10A from the feeding point 121A, based on a structural state in which the two half-wave oscillators 12A are arranged in reverse phase, in a state in which the two feeding points 121A are fed with excitation signals having a phase difference, the two half-wave oscillators 12A can form a phase difference to form a polarization state tending to linear polarization in a mutual coupling manner, and when the direction perpendicular to the reference ground 11A is the height direction of the half-wave folded-back directional microwave detection antenna 10A, the extension direction of the half-wave oscillators 12A in the height direction perpendicular to the half-wave folded-back directional microwave detection antenna 10A is the linear polarization direction, so that in a phase difference feeding manner, differential feeding to the transmitting antenna is realized in the linear polarization direction of the transmitting antenna in a state that the two feeding points 121A are connected to excitation signals with a phase difference larger than 90 °.
In some embodiments of the present invention, corresponding to fig. 4A to 4N, the transmitting antenna is configured as the double-ended feed differential antenna, and includes a reference ground 11B and two strip-shaped elements 12B, wherein two ends of the two strip-shaped elements 12B, which are connected to excitation signals, are respectively the feeding ends 121B of the two strip-shaped elements 12B, the two strip-shaped elements 12B extend from the two feeding ends 121B in the same lateral space of the reference ground 11B and respectively have a wavelength electrical length equal to or greater than 3/16 and equal to or less than 5/16, wherein the two strip-shaped elements 12B respectively have a coupling section 122B, wherein one end of the coupling section 122B, which is close to the feeding end 121B of the strip-shaped element 12B to which the coupling section 122B belongs, is a proximal end of the coupling section 122B, and the two coupling sections 122B extend from the proximal ends in opposite directions, based on the structure form that the two coupling sections 122B extend from the near end in opposite directions, the two feeding ends 121B of the two strip-shaped oscillators 12B are connected with excitation signals with phase difference to form coupling between the two coupling sections 122B and form a polarization form tending to linear polarization, so that the two feeding ends 121B of the two strip-shaped oscillators 12B are connected with excitation signals with phase difference larger than 90 degrees in a phase difference feeding mode and realize differential feeding to the transmitting antenna in the polarization direction tending to linear polarization of the transmitting antenna.
In some embodiments of the invention, wherein in the step (a), the transmitting power of the transmitting antenna is equal to or less than 0 dBm.
In response to the above description, the microwave detection method according to another embodiment of the present invention includes the following steps:
A. setting a transmit power of the transmit antenna at a target transmit power of less than or equal to 0dBm based on a corresponding parameter setting of an excitation signal;
B. accessing the echo signals with phase difference of 180 degrees and in a balanced differential signal form from the receiving antenna; and
C. outputting the Doppler intermediate frequency signal in a single-ended signal form with a frequency/phase difference between the excitation signal and the echo signal in a mixing processing step and a differential-to-single-ended processing step based on step (C1) or step (C2), wherein in the step (C1), the echo signal in a single-ended signal form is output based on the differential-to-single-ended processing of the echo signal in a balanced differential signal form by the differential-to-single-ended circuit, and the Doppler intermediate frequency signal in a single-ended signal form is output based on the mixing processing of the excitation signal and the echo signal in a single-ended signal form by the mixing circuit, wherein in the step (C2), the Doppler intermediate frequency signal in a balanced differential signal form is output based on the mixing processing of the excitation signal and the echo signal in a balanced differential signal form by the mixing circuit, and outputting the Doppler intermediate frequency signal in a single-ended signal form based on differential-to-single-ended processing of the Doppler intermediate frequency signal in a balanced differential signal form by the differential-to-single-ended circuit.
In some embodiments of the present invention, in the step (a), the circular polarization form of the transmitting antenna is implemented by means of phase difference feeding to reduce the minimum transmitting power extremum of the transmitting antenna.
In some embodiments of the present invention, in the step (a), the differential feeding of the transmitting antenna with a phase difference of more than 90 ° is implemented by feeding the transmitting antenna with an excitation signal with a phase difference of more than 90 ° in a polarization direction tending to linear polarization of the transmitting antenna by means of phase difference feeding.
In the description of the specification, reference to the description of "one embodiment," "some embodiments," "an example," "a specific example," or "some examples" or the like means that a particular feature, structure, material, or characteristic described in connection with the embodiment or example is included in at least one embodiment or example of the invention. In this specification, the terminology used in the description presented above is not necessarily for the same embodiment or example. Furthermore, the particular features, structures, materials, or characteristics described may be combined in any suitable manner in any one or more embodiments or examples. Moreover, various embodiments or examples and features of various embodiments or examples described in this specification can be combined and combined by one skilled in the art without being mutually inconsistent.
It will be appreciated by persons skilled in the art that the embodiments of the invention described above and shown in the drawings are given by way of example only and are not limiting of the invention. The objects of the present invention have been fully and effectively accomplished. The functional and structural principles of the present invention have been shown and described in the examples, and any variations or modifications of the embodiments of the present invention may be made without departing from the principles.
Claims (83)
1. The microwave detection method is characterized by comprising the following steps:
A. a transmitting antenna fed by an excitation signal to transmit a microwave beam corresponding to the frequency of said excitation signal;
B. accessing an echo signal which has a phase difference of about 180 degrees and is in a balanced differential signal form from a receiving antenna, wherein the echo signal comprises a signal of a reflection echo formed by reflecting a microwave beam by a corresponding object, and electromagnetic interference in the environment exists in the echo signal in a common mode interference form and can be inhibited in the receiving and transmitting processes of the echo signal in the balanced differential signal form; and
C. mixing the excitation signal and the echo signal in the form of a balanced differential signal with a mixing circuit to output a Doppler intermediate frequency signal in the form of a balanced differential signal, and a digital conversion process of the Doppler intermediate frequency signal in a balanced differential signal form with an A/D conversion unit to form a digital form of the Doppler intermediate frequency signal in a balanced differential signal form, and a data processing unit for suppressing and processing the common mode interference information in the digitized morphology of the Doppler intermediate frequency signal in a balanced differential signal morphology by a corresponding algorithm based on the digitized characteristics of the common mode interference, in this way, in a state where the echo signal is initially in a differential signal form, based on further suppression processing of common mode interference information in a digitized form of the doppler intermediate frequency signal in a balanced differential signal form, electromagnetic interference in the environment is suppressed, and accuracy of the doppler intermediate frequency signal is improved.
2. The microwave detection method according to claim 1, wherein in the step (C), further comprising the steps of: the echo signals in balanced differential signal form are amplified between the mixing circuit and the receiving antenna by at least one amplifying circuit adapted to amplify signals in differential signal form.
3. The microwave detection method according to claim 1, wherein in the step (C), further comprising the steps of: the doppler intermediate frequency signal in the form of a differential signal is amplified between the mixing circuit and the a/D conversion unit with at least one amplification circuit adapted to amplify a signal in the form of a differential signal.
4. The microwave detection method according to claim 1, wherein in the step (C), the doppler intermediate frequency signal corresponding to the balanced differential signal form has characteristics of two signals with equal amplitude and opposite phase with respect to a reference potential, the digitized form of the doppler intermediate frequency signal of the balanced differential signal form formed by the digitized conversion processing of the doppler intermediate frequency signal of the balanced differential signal form by the a/D conversion unit is represented as two sets of numerical data with equal absolute value and opposite variation trend of numerical value with respect to the reference potential value in a time domain, wherein based on the digitized characteristics of two sets of numerical values with equal numerical value and same variation trend of numerical value are respectively added to the two sets of numerical data in the time domain, the data processing unit suppresses the common mode interference in the digitized form of the doppler intermediate frequency signal of the balanced differential signal form by an algorithm of differencing the two sets of numerical data And disturbing the information.
5. The microwave detection method according to claim 4, wherein in the step (C), the A/D conversion unit is integrally provided to the data processing unit.
6. The microwave detection method according to claim 1, wherein in the step (a), a differential feed circuit provides the transmitting antenna with excitation signals 180 ° out of phase, so as to output the excitation signals 180 ° out of phase and in differential signal form to the mixing circuit, and outputs the doppler intermediate frequency signals in differential signal form based on mixing processing of the excitation signals and the echo signals in differential signal form by the mixing circuit.
7. The microwave detection method according to claim 6, wherein the differential feeder circuit is provided in the form of discrete components and has a three-pole circuit processor provided as a MOS tube or a triode, an inductor, a first resistor, a second resistor, a third resistor, a first capacitor, a second capacitor, an oscillation capacitor and a power connection terminal adapted to be connected to a corresponding power source, wherein the three-pole circuit processor has a first connection terminal corresponding to a collector of the triode or a drain of the MOS tube, a second connection terminal corresponding to a base of the triode or a gate of the MOS tube, and a third connection terminal corresponding to an emitter of the triode or a source of the MOS tube, wherein one end of the second resistor is electrically connected to the first connection terminal of the three-pole circuit processor, and the other end of the second resistor is connected to the power connection terminal via the inductor, and is grounded via the first capacitor, wherein one end of the third resistor is electrically connected to the third connection terminal of the three-pole circuit processor, and the other end of the third resistor is grounded, wherein one end of the oscillating capacitor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the oscillating capacitor is grounded, wherein one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the first resistor is electrically connected between the inductor and the second resistor, wherein two ends of the second capacitor are electrically connected to the first connection terminal and the third connection terminal of the three-pole circuit processor, respectively, wherein the second resistor and the third resistor are set with equal resistance values so as to switch on the differential feed circuit to the corresponding power supply at the power supply connection terminal, and outputting the excitation signal at two ends of the second capacitor in a balanced differential signal form with the phase difference approaching 180 degrees, thereby realizing the phase difference feeding of the transmitting antenna approaching 180 degrees.
8. The microwave detection method according to claim 7, wherein the differential feed circuit further comprises a third capacitor and a fourth capacitor, wherein the third capacitor and the fourth capacitor are electrically connected to two ends of the second capacitor respectively, so as to output the excitation signal in the form of balanced differential signal with a phase difference approaching 180 ° through the third capacitor and the fourth capacitor.
9. The microwave detection method according to claim 6, wherein the differential feed circuit is provided in the form of discrete components and has a three-pole circuit processor provided as a MOS tube or a triode, an inductor, a first resistor, a second resistor, a third resistor, a first capacitor, a second capacitor, an oscillation capacitor and a power connection terminal adapted to be connected to a corresponding power source, wherein the three-pole circuit processor has a first connection terminal corresponding to a collector of the triode or a drain of the MOS tube, a second connection terminal corresponding to a base of the triode or a gate of the MOS tube, and a third connection terminal corresponding to an emitter of the triode or a source of the MOS tube, wherein one end of the second resistor is electrically connected to the first connection terminal of the three-pole circuit processor, and the other end of the second resistor is connected to the power connection terminal via the inductor, and is grounded via the first capacitor, wherein one end of the third resistor is electrically connected to the third connection terminal of the three-pole circuit handler, and the other end of the third resistor is grounded, wherein one end of the oscillation capacitor is electrically connected to the second connection terminal of the three-pole circuit handler, and the other end of the oscillation capacitor is grounded, wherein one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit handler, and the other end of the first resistor is electrically connected to the power connection terminal, wherein two ends of the second capacitor are electrically connected to the first connection terminal and the third connection terminal of the three-pole circuit handler, respectively, wherein the second resistor and the third resistor are set at equal resistances to switch on the respective power supply at the power connection terminal of the differential feed circuit, and outputting the excitation signal at two ends of the second capacitor in a balanced differential signal form with the phase difference approaching 180 degrees, thereby realizing the phase difference feeding of the transmitting antenna approaching 180 degrees.
10. The microwave detection method according to claim 9, wherein the differential feed circuit further comprises a third capacitor and a fourth capacitor, wherein the third capacitor and the fourth capacitor are electrically connected to two ends of the second capacitor respectively, so as to output the excitation signal in the form of balanced differential signal with a phase difference approaching 180 ° through the third capacitor and the fourth capacitor.
11. The microwave detecting method according to claim 6, wherein the differential feed circuit is configured as an integrated circuit and outputs the excitation signal in a balanced differential signal form with a phase difference of about 180 ° in a differential oscillating circuit, wherein the differential oscillating circuit has two N-channel MOS transistors, two P-channel MOS transistors, an oscillating inductor and an oscillating capacitor, wherein sources of the two N-channel MOS transistors are electrically connected, sources of the two P-channel MOS transistors are electrically connected, and drains of the two N-channel MOS transistors are electrically connected to drains of different P-channel MOS transistors, respectively, so as to form a drain of one of the N-channel MOS transistors electrically connected to a drain of one of the P-channel MOS transistors, a source of the P-channel MOS transistor is electrically connected to a source of the other P-channel MOS transistor, and a drain of the other P-channel MOS transistor is electrically connected to a drain of the other N-channel MOS transistor, and the source of the other N-channel MOS transistor is electrically connected to the source of the previous N-channel MOS transistor in a sequential connection relationship, wherein the gate of any one of the N-channel MOS transistors is electrically connected to the drain of the other N-channel MOS transistor, wherein the gate of any one of the P-channel MOS transistors is electrically connected to the drain of the other P-channel MOS transistor, wherein the two ends of the oscillation inductor are electrically connected to the drains of the different P-channel MOS transistors, respectively, and the two ends of the oscillation capacitor are electrically connected to the drains of the different P-channel MOS transistors and are connected in parallel with the oscillation inductor, respectively, so as to form oscillation and frequency selection based on the parallel resonant circuit composed of the oscillation inductor and the oscillation capacitor and form an equal size at the two ends of the oscillation inductor and the oscillation capacitor, the electric signals in opposite directions enable one of the N-channel MOS transistor and the P-channel MOS transistor electrically connected with the grid electrode of the N-channel MOS transistor to be conducted at the same time, and enable the other N-channel MOS transistor and the P-channel MOS transistor electrically connected with the grid electrode of the N-channel MOS transistor to be conducted at the same time, so that the excitation signals are output at two ends of the oscillation inductor in a balanced differential signal mode with 180-degree difference.
12. The microwave detection method according to claim 11, wherein the differential feed circuit further comprises a low dropout regulator, an oscillator, a phase-locked loop and a logic control unit, wherein the low dropout regulator provides a constant voltage to the differential oscillating circuit in a powered state, wherein the oscillator is configured such that the logic control unit provides a basic clock signal and a quartz crystal oscillator is externally disposed or an internal oscillating circuit is integrally disposed in the logic control unit, wherein the logic control unit is electrically connected to the oscillating inductor of the differential oscillating circuit, wherein the phase-locked loop is electrically connected between the logic control unit and the differential oscillating circuit in a state of being externally disposed or integrated in the logic control unit, so as to calibrate the differential oscillating circuit based on the feedback of the excitation signal outputted from the differential oscillating circuit by the logic control unit The two ends of the oscillating inductor are connected to output the frequency of the excitation signal in a balanced differential signal form with a 180-degree difference, so that the stable output of the excitation signal in the balanced differential signal form by the differential feed circuit is guaranteed.
13. The microwave detection method according to claim 12, wherein the differential feed circuit further includes two amplifiers for amplifying the excitation signal outputted from the differential oscillation circuit in a balanced differential signal form, wherein the logic control unit is electrically connected to the oscillation inductor of the differential oscillation circuit in a state of being electrically connected to at least one of the amplifiers to receive feedback of the amplifier on the excitation signal outputted from the differential oscillation circuit.
14. The microwave detection method according to any one of claims 1 to 13, wherein in the step (B), the receiving antenna is arranged in a planar patch antenna configuration with a reference ground and a radiation source, wherein the radiation source is disposed at a side of the reference ground in a state spaced apart from the reference ground, wherein the radiation sources are arranged in a unit radiation source configuration having a single number of radiation elements corresponding to the radiation sources, wherein the radiating element has two feeding points, wherein the two feeding points are arranged in opposite phase, and the connection direction from one of the feeding points to the physical center point of the radiating element and the connection direction from the other feeding point to the physical center point of the radiating element are coincided oppositely, and outputting the echo signals in a balanced differential signal form at the two feeding points based on a structural state that the two feeding points are arranged in an inverted state.
15. A method of microwave detection according to claim 14 wherein the radiating element is electrically connected to the reference ground at its physical centre point.
16. The microwave detection method according to claim 15, wherein the radiating element has at least one set and/or at least one pair of grounding points electrically connected to the reference ground, wherein the grounding points of the same group are positioned at each vertex of the same regular polygon taking the physical central point of the radiating element as a midpoint, each grounding point corresponding to the grounding point in the same group is arranged around the physical central point of the radiation element at equal angles in a state of being equidistant from the physical central point of the radiation element, wherein the grounding points of the same pair are symmetrically distributed on the radiating element with the physical center point of the radiating element, the connecting line segment corresponding to the grounding point of the same pair takes the physical central point of the radiating element as a midpoint, and forms a zero potential point at the physical central point of the radiating element based on the electrical connection relationship between the grounding point and the reference ground, so that the connecting line segment is equivalent to the physical central point of the radiating element and the reference ground in electrical connection.
17. The microwave detection method according to claim 15, wherein in a state where the transmission antenna is also set in a planar patch antenna state, the transmission antenna and the reception antenna are integrally set in a transceiving separated form based on a structural form of sharing the reference ground.
18. The microwave detection method according to claim 17, wherein the transmitting antenna and the receiving antenna are integrally provided in a transceiving separated form based on a structural form of sharing the reference ground and the radiation source.
19. The microwave detection method according to claim 15, wherein in a state where the transmission antenna is also set in a planar patch antenna configuration, the transmission antenna and the reception antenna are integrally set in a transmission and reception integrated form based on a structural configuration in which the reference ground and the radiation source are shared.
20. The microwave detection method according to any one of claims 1 to 13, wherein in the step (B), the receiving antenna is arranged in a planar patch antenna configuration with a reference ground and a radiation source, wherein the radiation source is disposed at a side of the reference ground in a state spaced apart from the reference ground, wherein the radiation source is arranged in a binary radiation source configuration with two radiation elements for the radiation source, wherein each of the radiating elements has a feeding point, wherein the two radiating elements are arranged in opposite phase, and the direction of the connection line from the feeding point to the physical center point of one of the radiating elements is opposite to the direction of the connection line from the feeding point to the physical center point of the other radiating element, and outputting the echo signals in a balanced differential signal form at the two feeding points based on the structural state that the two radiating elements are arranged in an inverted state.
21. A method of microwave detection according to claim 20 and wherein at least one of said radiating elements is electrically connected to said reference ground at its physical centre point.
22. The microwave detection method according to claim 21, wherein at least one of the radiating elements has at least one set and/or at least one pair of grounding points electrically connected to the reference ground, wherein the grounding points of the same group are positioned at each vertex of the same regular polygon taking the physical central point of the radiating element as a midpoint, each grounding point corresponding to the grounding point in the same group is arranged around the physical central point of the radiation element at equal angles in a state of being equidistant from the physical central point of the radiation element, wherein the grounding points of the same pair are symmetrically distributed on the radiating element at the physical central point of the radiating element, the connecting line segment corresponding to the grounding point of the same pair takes the physical central point of the radiating element as a midpoint, and forms a zero potential point at the physical central point of the radiating element based on the electrical connection relationship between the grounding point and the reference ground, so that the connecting line segment is equivalent to the physical central point of the radiating element and the reference ground in electrical connection.
23. The microwave detection method according to claim 21, wherein in a state where the transmission antenna is also set in a planar patch antenna state, the transmission antenna and the reception antenna are integrally set in a transceiving separated form based on a structural form of sharing the reference ground.
24. The microwave detection method according to claim 21, wherein in a state where the transmission antenna is also set in a planar patch antenna form, the transmission antenna and the reception antenna are integrally set in a transceive-united form based on a structural form that shares the reference ground and the radiation source.
25. The microwave detection method according to any one of claims 1 to 13, wherein in the step (B), the receiving antenna is provided as a half-wave folded directional microwave detection antenna in a vertical structure with reverse polarization, and includes a ground reference, a half-wave oscillator and two feeder lines corresponding to the receiving antenna, wherein the half-wave oscillator has an electrical length of 1/2 or more and 3/4 or less in wavelength, and has two coupling sections, wherein each of the coupling sections has an electrical length of 1/6 or more in wavelength, one end of each of the coupling sections is named as a feeding end of the coupling section, and the other end of each of the coupling sections is named as both ends of the half-wave oscillator, wherein a distance between the feeding ends is λ/4 or less, and a distance between the both ends of the half-wave oscillator is λ/128 or more and λ/6 or less, wherein λ is a wavelength parameter corresponding to the frequency of the excitation signal, wherein the half-wave dipole is spaced apart from the reference ground in a state where a distance between two ends of the half-wave dipole and the reference ground is greater than or equal to λ/128 and less than or equal to λ/6, wherein the two feeder lines are electrically connected to the corresponding feed ends, respectively, wherein the half-wave dipole is arranged in reverse phase, that is, a direction perpendicular to the reference ground is a height direction of the half-wave backfolding type directional microwave detection antenna, the half-wave dipole is reversed from the two feed ends in an extending direction perpendicular to the height direction of the half-wave backfolding type directional microwave detection antenna, so as to output the echo signals in a balanced differential signal form at the two feed ends based on a structural state where the half-wave dipole is arranged in reverse phase.
26. A microwave detection method as claimed in claim 25 wherein the transmitting antenna and the receiving antenna are integrally provided in a transceiving separated form based on a structural configuration sharing the reference ground.
27. A method for microwave detection according to claim 25 wherein the receiving antenna is integrated with the transmitting antenna in a transceive mode based on a configuration of sharing the transmitting antenna.
28. The microwave detection method according to any one of claims 1 to 13, wherein in the step (B), the receiving antenna is configured as a dual-feed differential antenna, and the receiving antenna includes a reference ground and two strip-shaped elements, wherein two ends of the two strip-shaped elements, which are connected to the excitation signal, are respectively feed ends of the two strip-shaped elements, the two strip-shaped elements extend from the two feed ends in the same lateral space of the reference ground and respectively have a wavelength electrical length greater than or equal to 3/16 and less than or equal to 5/16, wherein the two strip-shaped elements respectively have a coupling section, wherein one end of the coupling section, which is close to the feed end of the strip-shaped element to which the coupling section belongs, is a proximal end of the coupling section, and the two coupling sections extend from the proximal ends in opposite directions to each other, based on a structural configuration that the two coupling sections extend from the proximal ends in opposite directions, based on the structural characteristic that two coupling sections of the two strip-shaped oscillators extend from the near end in opposite directions and can be mutually coupled to form a common resonance frequency point, the two strip-shaped oscillators are formed in a structural state of being arranged in a reverse phase manner in a polarization direction tending to linear polarization, and therefore when the double-feed differential antenna is used as a receiving antenna, the echo signals in a balanced differential signal form are directly output from the two feed ends.
29. A method of microwave detection according to claim 28 wherein the two coupled sections of the double-fed differential antenna extend in offset opposing directions from the proximal end and have offset distances of λ/256 or greater and λ/6 or less, i.e. the distance from any point on one of the coupled sections to the other of the coupled sections is λ/256 or greater and λ/6 or less, where λ is a wavelength parameter corresponding to the frequency of the excitation signal.
30. A method for microwave detection according to claim 29 wherein the transmitting antenna is integrated with the receiving antenna in a transceive manner based on a configuration of the common receiving antenna.
31. The microwave detecting method according to any one of claims 1 to 13, wherein in the step (B), the receiving antenna is provided in a planar patch antenna configuration to have a reference ground and a radiation source, wherein the radiation source is provided in a spaced state from the reference ground on one side of the reference ground, wherein the radiation source is provided in a unit radiation source configuration, the radiation source has a single number of radiation elements, wherein the radiation elements have two feeding points, wherein the two feeding points are orthogonally arranged, and connecting lines corresponding to physical center points of the two feeding points and the radiation elements are perpendicular to each other, wherein one of the feeding points is electrically connected with a phase shifter, so as to output the echo signal in a balanced differential signal configuration between one end of the phase shifter far from the feeding point and the other feeding point based on a phase shift processing of the echo signal by the phase shifter on the feeding point Number (n).
32. A method of microwave detection according to claim 31 wherein the radiating element is electrically connected to the reference ground at its physical centre point.
33. The microwave detection method according to claim 32, wherein the radiating element has at least one set and/or at least one pair of grounding points electrically connected to the reference ground, wherein the grounding points of the same group are positioned at each vertex of the same regular polygon taking the physical central point of the radiating element as a midpoint, each grounding point in the grounding points corresponding to the same group is arranged around the physical central point of the radiation element at equal angles in a state of being equidistant from the physical central point of the radiation element, wherein the grounding points of the same pair are symmetrically distributed on the radiating element with the physical center point of the radiating element, the connecting line segment corresponding to the grounding point of the same pair takes the physical central point of the radiating element as a midpoint, and forms a zero potential point at the physical central point of the radiating element based on the electrical connection relationship between the grounding point and the reference ground, so that the connecting line segment is equivalent to the physical central point of the radiating element and the reference ground in electrical connection.
34. The microwave detection method according to claim 32, wherein in a state where the transmission antenna is also set in a planar patch antenna state, the transmission antenna and the reception antenna are integrally set in a transceiving separated form based on a structural form of sharing the reference ground.
35. The microwave detecting method according to any one of claims 1 to 13, wherein in the step (B), the receiving antenna is provided in a planar patch antenna configuration having a ground reference and a radiation source, wherein the radiation source is provided on one side of the ground reference in a state spaced apart from the ground reference, wherein the radiation source is provided in a binary radiation source configuration having two radiation elements corresponding to the radiation source, wherein each of the radiation elements has a feeding point, wherein the two radiation elements are orthogonally arranged, a connecting line direction of the feeding point to a physical central point corresponding to one of the radiation elements is perpendicular to a connecting line direction of the feeding point to a physical central point corresponding to the other of the radiation elements, wherein one of the feeding points is electrically connected with a phase shifter for phase-shifting the echo signal inputted from the feeding point based on the phase shifter, and outputting the echo signal in a balanced differential signal form between one end of the phase shifter far away from the feeding point and the other feeding point.
36. A method of microwave detection according to claim 35, wherein the radiating element is electrically connected to the reference ground at its physical centre point.
37. The microwave detection method according to claim 36, wherein at least one of said radiating elements has at least one set and/or at least one pair of grounding points electrically connected to said reference ground, wherein the grounding points of the same group are positioned at each vertex of the same regular polygon taking the physical central point of the radiating element as a midpoint, each grounding point corresponding to the grounding point in the same group is arranged around the physical central point of the radiation element at equal angles in a state of being equidistant from the physical central point of the radiation element, wherein the grounding points of the same pair are symmetrically distributed on the radiating element with the physical center point of the radiating element, the connecting line segment corresponding to the grounding point of the same pair takes the physical central point of the radiating element as a midpoint, and forms a zero potential point at the physical central point of the radiating element based on the electrical connection relationship between the grounding point and the reference ground, so that the connecting line segment is equivalent to the physical central point of the radiating element and the reference ground in electrical connection.
38. The microwave detection method according to claim 36, wherein in a state where the transmission antenna is also set in a planar patch antenna state, the transmission antenna and the reception antenna are integrally set in a transceiving separated form based on a structural form of sharing the reference ground.
39. The microwave detection method according to any one of claims 1 to 13, wherein in the step (B), the receiving antenna is provided as a half-wave folded directional microwave detection antenna in a orthogonally polarized vertical structure, the receiving antenna includes a ground reference, two half-wave oscillators and four feed lines, wherein each of the half-wave oscillators has an electrical length of 1/2 or more and 3/4 or less in correspondence with the receiving antenna, and has two coupling sections, wherein each of the coupling sections has an electrical length of 1/6 or more in correspondence with naming of one of the ends of each of the coupling sections as a feeding end of the coupling section, and the other end of each of the coupling sections as both ends of the half-wave oscillator, wherein a distance between both the feeding ends of each of the half-wave oscillators is λ/4 or less, a distance between both the ends of each of the half-wave oscillator is λ/128 or more and λ/6 or less, wherein λ is a wavelength parameter corresponding to a frequency of the excitation signal, wherein each of the half-wave resonators is spaced apart from the reference ground in a state where a distance between both ends of each of the half-wave resonators and the reference ground is λ/128 or more and λ/6 or less, wherein four of the feeder lines are electrically connected to the corresponding feed terminals, respectively, wherein the two half-wave resonators are arranged orthogonally, and extend in a direction perpendicular to a height direction of the half-wave backfolding type directional microwave detecting antenna corresponding to a direction perpendicular to the reference ground, and the two half-wave resonators are perpendicular to each other in an extending direction perpendicular to the height direction of the half-wave backfolding type directional microwave detecting antenna, wherein one of the feed terminals of one of the half-wave resonators is connected with a phase shifter via the feeder line, so as to perform phase shift processing on the echo signal received from the feed terminal based on the phase shifter, and outputting the echo signal in a balanced differential signal form between one end of the phase shifter, which is far away from the feed end, and one of the feed ends of the other half-wave oscillator.
40. A microwave detection method as claimed in claim 39 wherein the transmitting antenna is provided integrally with the receiving antenna based on a configuration which shares the receiving antenna.
41. Microwave detection device, its characterized in that includes:
a transmitting antenna, wherein the transmitting antenna is set to transmit a microwave beam corresponding to a frequency of an excitation signal in a state of being fed by the excitation signal;
a receiving antenna, wherein the receiving antenna has a polarization direction tending to linear polarization and outputs a corresponding echo signal in a balanced differential signal form with a phase difference approaching 180 ° after receiving a reflected echo formed by the microwave beam reflected by a corresponding object;
a mixer circuit, wherein the mixer circuit is configured to mix the excitation signal and the echo signal in the form of a balanced differential signal to output a doppler intermediate frequency signal in the form of a differential signal;
an a/D conversion unit, wherein the a/D conversion unit is configured to digitize the doppler intermediate frequency signal in a balanced differential signal form to form a digitized form of the doppler intermediate frequency signal in a balanced differential signal form; and
a data processing unit, wherein the data processing unit is configured to perform rejection processing on common mode interference information in the digitized morphology of the doppler intermediate frequency signal in a balanced differential signal morphology with a corresponding algorithm based on the digitized characteristics of the common mode interference, so as to suppress electromagnetic interference in an environment and improve the accuracy of the doppler intermediate frequency signal based on the rejection processing on the common mode interference information in the digitized morphology of the doppler intermediate frequency signal in a balanced differential signal morphology in a state where the echo signal is initially in a differential signal morphology.
42. A microwave detection device according to claim 41, wherein the microwave detection device further comprises at least one amplification circuit adapted to amplify signals of differential signal form, wherein the amplification circuit is disposed between the receiving antenna and the mixing circuit to amplify and output the echo signals of balanced differential signal form to the mixing circuit.
43. A microwave detection device according to claim 41, wherein the microwave detection device further comprises another amplifying circuit adapted to amplify signals in differential signal form, wherein the amplifying circuit is arranged between the mixing circuit and the A/D conversion unit to amplify the Doppler intermediate frequency signals in differential signal form to the A/D conversion unit.
44. The microwave detection device according to claim 41, wherein the Doppler intermediate frequency signal corresponding to the balanced differential signal configuration has two signals with equal amplitude and opposite phase relative to a reference potential, the digitized morphology of the Doppler intermediate frequency signal of the balanced differential signal morphology formed by the digitized conversion processing of the Doppler intermediate frequency signal of the balanced differential signal morphology by the A/D conversion unit is represented by two groups of numerical data which are equal in absolute value relative to a reference potential value and opposite in numerical value change trend in time domain, wherein the common-mode interference-based expression is characterized in that two groups of numerical values with equal numerical values and the same numerical value change trend are respectively added to the two groups of numerical value data in the time domain, the data processing unit is arranged to process common mode interference information in a digitized version of the doppler intermediate frequency signal balanced in a differential signal version by an algorithm that differentiates the two sets of numerical data.
45. A microwave detection apparatus as claimed in claim 44 wherein the A/D conversion unit is integrally provided with the data processing unit.
46. The microwave detection device according to claim 41, wherein the microwave detection device further comprises a differential feed circuit, wherein the differential feed circuit is configured to output excitation signals 180 ° out of phase in a powered state, to output the excitation signals 180 ° out of phase in a differential signal form to the mixing circuit, and to output the Doppler intermediate frequency signals in a differential signal form based on mixing processing of the excitation signals and the echo signals in a differential signal form by the mixing circuit.
47. A microwave detection device according to claim 46, wherein the differential feed circuit is provided in discrete component form and has a three-pole circuit processor provided as a MOS tube or a triode, an inductor, a first resistor, a second resistor, a third resistor, a first capacitor, a second capacitor, an oscillation capacitor and a power connection terminal adapted to be connected to a corresponding power source, wherein the three-pole circuit processor has a first connection terminal corresponding to a collector of the triode or a drain of the MOS tube, a second connection terminal corresponding to a base of the triode or a gate of the MOS tube, and a third connection terminal corresponding to an emitter of the triode or a source of the MOS tube, wherein one end of the second resistor is electrically connected to the first connection terminal of the three-pole circuit processor, and the other end of the second resistor is connected to the power connection terminal via the inductor, and is grounded via the first capacitor, wherein one end of the third resistor is electrically connected to the third connection terminal of the three-pole circuit processor, and the other end of the third resistor is grounded, wherein one end of the oscillating capacitor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the oscillating capacitor is grounded, wherein one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the first resistor is electrically connected between the inductor and the second resistor, wherein two ends of the second capacitor are electrically connected to the first connection terminal and the third connection terminal of the three-pole circuit processor, respectively, wherein the second resistor and the third resistor are set with equal resistance values so as to switch on the differential feed circuit to the corresponding power supply at the power supply connection terminal, and outputting the excitation signal in a balanced differential signal form with a phase difference of about 180 degrees at two ends of the second capacitor, so that the phase difference feeding of about 180 degrees of the transmitting antenna is realized.
48. A microwave detection apparatus as claimed in claim 47 wherein the differential feed circuit further comprises a third capacitor and a fourth capacitor, wherein the third capacitor and the fourth capacitor are electrically connected across the second capacitor respectively, so as to output the excitation signal via the third capacitor and the fourth capacitor in the form of balanced differential signals with a phase difference of approximately 180 °.
49. A microwave detection device according to claim 46, wherein the differential feed circuit is provided in discrete component form and has a three-pole circuit processor provided as a MOS tube or a triode, an inductor, a first resistor, a second resistor, a third resistor, a first capacitor, a second capacitor, an oscillation capacitor and a power connection terminal adapted to be connected to a corresponding power source, wherein the three-pole circuit processor has a first connection terminal corresponding to a collector of the triode or a drain of the MOS tube, a second connection terminal corresponding to a base of the triode or a gate of the MOS tube, and a third connection terminal corresponding to an emitter of the triode or a source of the MOS tube, wherein one end of the second resistor is electrically connected to the first connection terminal of the three-pole circuit processor, and the other end of the second resistor is connected to the power connection terminal via the inductor, and is grounded via the first capacitor, wherein one end of the third resistor is electrically connected to the third connection terminal of the three-pole circuit handler, and the other end of the third resistor is grounded, wherein one end of the oscillation capacitor is electrically connected to the second connection terminal of the three-pole circuit handler, and the other end of the oscillation capacitor is grounded, wherein one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit handler, and the other end of the first resistor is electrically connected to the power connection terminal, wherein two ends of the second capacitor are electrically connected to the first connection terminal and the third connection terminal of the three-pole circuit handler, respectively, wherein the second resistor and the third resistor are set at equal resistances to switch on the respective power supply at the power connection terminal of the differential feed circuit, and outputting the excitation signal in a balanced differential signal form with a phase difference of about 180 degrees at two ends of the second capacitor, so that the phase difference feeding of about 180 degrees of the transmitting antenna is realized.
50. A microwave detection device according to claim 49 wherein the differential feed circuit further comprises a third capacitor and a fourth capacitor, wherein the third capacitor and the fourth capacitor are electrically connected across the second capacitor respectively, so as to output the excitation signal via the third capacitor and the fourth capacitor as a balanced differential signal with a phase difference of approximately 180 °.
51. A microwave detecting device according to claim 46, wherein the differential feed circuit is provided in the form of an integrated circuit and outputs the excitation signal in the form of a balanced differential signal which is shifted toward 180 ° in a differential oscillating circuit having two N-channel MOS transistors, two P-channel MOS transistors, an oscillating inductor and an oscillating capacitor in which the sources of the two N-channel MOS transistors are electrically connected, the sources of the two P-channel MOS transistors are electrically connected, and the drains of the two N-channel MOS transistors are electrically connected to the drains of the different P-channel MOS transistors, respectively, so as to form a structure in which the drain of one of the N-channel MOS transistors is electrically connected to the drain of one of the P-channel MOS transistors, the source of the P-channel MOS transistor is electrically connected to the source of the other P-channel MOS transistor, and the drain of the other P-channel MOS transistor is electrically connected to the drain of the other N-channel MOS transistor, and the source of the other N-channel MOS transistor is electrically connected to the source of the previous N-channel MOS transistor in a sequential connection relationship, wherein the gate of any one of the N-channel MOS transistors is electrically connected to the drain of the other N-channel MOS transistor, wherein the gate of any one of the P-channel MOS transistors is electrically connected to the drain of the other P-channel MOS transistor, wherein the two ends of the oscillation inductor are electrically connected to the drains of the different P-channel MOS transistors, respectively, and the two ends of the oscillation capacitor are electrically connected to the drains of the different P-channel MOS transistors and are connected in parallel with the oscillation inductor, respectively, so as to form oscillation and frequency selection based on the parallel resonant circuit composed of the oscillation inductor and the oscillation capacitor and form an equal size at the two ends of the oscillation inductor and the oscillation capacitor, the electric signals in opposite directions enable one of the N-channel MOS transistor and the P-channel MOS transistor electrically connected with the grid electrode of the N-channel MOS transistor to be conducted at the same time, and enable the other N-channel MOS transistor and the P-channel MOS transistor electrically connected with the grid electrode of the N-channel MOS transistor to be conducted at the same time, so that the excitation signals are output at two ends of the oscillation inductor in a balanced differential signal mode with 180-degree difference.
52. A microwave detection device according to claim 51, wherein the differential feed circuit further comprises a low dropout regulator, an oscillator, a phase locked loop and a logic control unit, wherein the low dropout regulator provides a constant voltage to the differential oscillation circuit in a powered state, wherein the oscillator is configured such that the logic control unit provides a basic clock signal and a quartz crystal oscillator is externally arranged or an internal oscillation circuit is integrally arranged on the logic control unit, wherein the logic control unit is electrically connected to the oscillation inductance of the differential oscillation circuit, wherein the phase locked loop is electrically connected between the logic control unit and the differential oscillation circuit in a state of being externally arranged or integrated on the logic control unit, so as to calibrate the differential oscillation circuit based on the feedback of the excitation signal output by the differential oscillation circuit from the logic control unit The two ends of the oscillating inductor are connected to output the frequency of the excitation signal in a balanced differential signal form with a 180-degree difference, so that the stable output of the excitation signal in the balanced differential signal form by the differential feed circuit is guaranteed.
53. A microwave detecting device according to claim 52, wherein said differential feed circuit further includes two amplifiers for amplifying the excitation signal outputted from said differential oscillating circuit in a balanced differential signal form, wherein said logic control unit is electrically connected to said oscillating inductor of said differential oscillating circuit in a state of being electrically connected to at least one of said amplifiers for receiving feedback of said amplifiers on the excitation signal outputted from said differential oscillating circuit.
54. A microwave detection device according to any one of claims 41-53, wherein the receiving antenna is arranged in a planar patch antenna configuration with a reference ground and a radiation source, wherein the radiation source is disposed at one side of the reference ground in a state spaced apart from the reference ground, wherein the radiation source is arranged in a unit radiation source configuration having a single number of radiation elements corresponding to the radiation source, wherein the radiating element has two feeding points, wherein the two feeding points are arranged in opposite phase, and the connecting line direction from one of the feeding points to the physical center point of the radiating element is opposite to and coincident with the connecting line direction from the other feeding point to the physical center point of the radiating element, and outputting the echo signals in a balanced differential signal form at the two feeding points based on the structural state that the two feeding points are arranged in an inverted state.
55. A microwave detection device as claimed in claim 54 wherein the radiating element is electrically connected to the reference ground at its physical centre point.
56. A microwave detection apparatus as claimed in claim 55 wherein the radiating element has at least one set and/or at least one pair of ground points electrically connected to the reference ground, wherein the grounding points of the same group are positioned at each vertex of the same regular polygon taking the physical central point of the radiating element as a midpoint, each grounding point in the grounding points corresponding to the same group is arranged around the physical central point of the radiation element at equal angles in a state of being equidistant from the physical central point of the radiation element, wherein the grounding points of the same pair are symmetrically distributed on the radiating element at the physical central point of the radiating element, the connecting line segment corresponding to the grounding point of the same pair takes the physical central point of the radiating element as a midpoint, and forms a zero potential point at the physical central point of the radiating element based on the electrical connection relationship between the grounding point and the reference ground, so that the zero potential point is equivalent to the physical central point of the radiating element and the reference ground are electrically connected.
57. A microwave detection apparatus as claimed in claim 54 wherein, in a state where the transmission antenna is also provided in a planar patch antenna configuration, the transmission antenna and the reception antenna are integrally provided in a transceiving split form based on a configuration sharing the reference ground.
58. A microwave detection apparatus as claimed in claim 57 wherein the transmission antenna and the reception antenna are integrally arranged in a transceived split form based on a configuration that shares the reference ground and the radiation source.
59. A microwave detection apparatus as claimed in claim 54 wherein, in a state in which the transmitting antenna is also provided in a planar patch antenna configuration, the transmitting antenna and the receiving antenna are integrally provided in a transceive united form based on a configuration in which the reference ground and the radiation source are shared.
60. The microwave detection apparatus of any one of claims 41-53, wherein the receiving antenna is configured in a planar patch antenna configuration with a reference ground and a radiation source, wherein the radiation source is disposed at a side of the reference ground in a state spaced apart from the reference ground, wherein the radiation source is arranged in a binary radiation source configuration with two radiation elements for the radiation source, wherein each of the radiating elements has a feeding point, wherein the two radiating elements are arranged in opposite phase, and the direction of the connection line from the feeding point to the physical center point of one of the radiating elements is opposite to the direction of the connection line from the feeding point to the physical center point of the other radiating element, and outputting the echo signals in a balanced differential signal form at the two feeding points based on the structural state that the two radiating elements are arranged in an inverted state.
61. A microwave detection apparatus as claimed in claim 60 wherein at least one of the radiating elements is electrically connected to the reference ground at its physical centre point.
62. The microwave detection apparatus of claim 61, wherein at least one of the radiating elements has at least one set and/or at least one pair of grounding points electrically connected to the reference ground, wherein the grounding points of the same group are positioned at each vertex of the same regular polygon taking the physical central point of the radiating element as a midpoint, each grounding point in the grounding points corresponding to the same group is arranged around the physical central point of the radiation element at equal angles in a state of being equidistant from the physical central point of the radiation element, wherein the grounding points of the same pair are symmetrically distributed on the radiating element with the physical center point of the radiating element, the connecting line segment corresponding to the grounding point of the same pair takes the physical central point of the radiating element as a midpoint, and forms a zero potential point at the physical central point of the radiating element based on the electrical connection relationship between the grounding point and the reference ground, so that the connecting line segment is equivalent to the physical central point of the radiating element and the reference ground in electrical connection.
63. The microwave detection apparatus according to claim 60, wherein in a state where the transmission antenna is also set in a planar patch antenna configuration, the transmission antenna and the reception antenna are integrally set in a transceiving separated form based on a configuration sharing the reference ground.
64. A microwave detection apparatus as claimed in claim 60 wherein, in a state where the transmitting antenna is also provided in a planar patch antenna configuration, the transmitting antenna and the receiving antenna are integrally provided in a transceive-united form based on a configuration which shares the reference ground and the radiation source.
65. The microwave detection apparatus of any one of claims 41-53, wherein the receiving antenna is configured as a half-wave folded-back directional microwave detection antenna in a reverse-phase polarized vertical structure, comprising a ground reference, a half-wave oscillator and two feeding lines corresponding to the receiving antenna, wherein the half-wave oscillator has an electrical length of 1/2 or more and 3/4 or less, and has two coupling sections, wherein each of the coupling sections has an electrical length of 1/6 or more, one end of each of the coupling sections is named as a feeding end of the coupling section correspondingly, and the other ends of the coupling sections are both ends of the half-wave oscillator, wherein a distance between the feeding ends is λ/4 or less, a distance between the both ends of the half-wave oscillator is λ/128 or more and λ/6 or less, wherein λ is a wavelength parameter corresponding to a frequency of the excitation signal, wherein the half-wave dipole is spaced apart from the reference ground in a state where a distance between both ends of the half-wave dipole and the reference ground is greater than or equal to λ/128 and less than or equal to λ/6, wherein the two feeding lines are electrically connected to the respective feeding ends, respectively, wherein the half-wave dipole is arranged in an inverted phase, that is, a direction perpendicular to the reference ground is a height direction of the half-wave folded directional microwave detection antenna, and the half-wave dipole is inverted from an extending direction of the two feeding ends in a direction perpendicular to the height direction of the half-wave folded directional microwave detection antenna, so as to output the echo signals in a balanced differential signal form at the two feeding ends based on a structural state where the half-wave dipole is arranged in an inverted phase.
66. A microwave detection apparatus as claimed in claim 65 wherein the transmit antenna and the receive antenna are integrally provided in a transceive split fashion based on a configuration which shares the reference ground.
67. The microwave detection device according to claim 66, wherein the half-wave folded-back directional microwave detection antenna of the vertical structure with reverse polarization of the transmitting antenna is disposed, the integrated structure corresponding to the transmitting antenna and the receiving antenna includes two half-wave oscillators respectively disposed in reverse phase, wherein the two half-wave oscillators are disposed orthogonally to each other, corresponding to a direction perpendicular to the reference ground direction as a height direction of the half-wave folded-back directional microwave detection antenna, each of the half-wave oscillators is inverted from the two feeding terminals in an extending direction perpendicular to the height direction of the half-wave folded-back directional microwave detection antenna, and the two half-wave oscillators are perpendicular to each other in the extending direction perpendicular to the height direction of the half-wave folded-back directional microwave detection antenna.
68. The microwave detection device of claim 67, wherein in the integrated structure of the transmitting antenna and the receiving antenna, the half-wave oscillators are staggered and inverted from the two feeding ends in the extending direction perpendicular to the height direction of the half-wave folded directional microwave detection antenna, and the two half-wave oscillators are orthogonally arranged corresponding to the structure that the four feeding ends are located at the four vertex positions of a square with the connecting line of the two feeding ends of each half-wave oscillator as a diagonal line.
69. A microwave detection apparatus as claimed in claim 65 wherein the receive antenna is integrated with the transmit antenna in a transceive mode based on a configuration of the common transmit antenna.
70. The microwave detection apparatus of any one of claims 41-53, wherein the receiving antenna is configured as a double-ended feed differential antenna, and comprises a reference ground and two strip-shaped elements, wherein two ends of the two strip-shaped elements, which are connected to excitation signals, are respectively the feeding ends of the two strip-shaped elements, the two strip-shaped elements extend from the two feeding ends in the same lateral space of the reference ground and respectively have a wavelength electrical length equal to or greater than 3/16 and equal to or less than 5/16, wherein the two strip-shaped elements respectively have a coupling section, wherein one end of the coupling section, which is close to the feeding end of the strip-shaped element to which the coupling section belongs, is a proximal end of the coupling section, and the two coupling sections extend from the proximal end in opposite directions, so as to form a structure that the two coupling sections extend from the proximal end in opposite directions, based on the structural characteristic that two coupling sections of the two strip-shaped oscillators extend from the near end in opposite directions and can be mutually coupled to form a common resonance frequency point, the two strip-shaped oscillators are formed in a structural state of being arranged in a reverse phase manner in a polarization direction tending to linear polarization, and therefore when the double-feed differential antenna is used as a receiving antenna, the echo signals in a balanced differential signal form are directly output from the two feed ends.
71. The microwave detection device of claim 70, wherein the two coupled sections of the dual feed differential antenna extend from the proximal end in offset opposing directions and have offset distances of λ/256 or more and λ/6 or less, i.e., the distance from any point on one of the coupled sections to the other coupled section is λ/256 or more and λ/6 or less, where λ is a wavelength parameter corresponding to the frequency of the excitation signal.
72. A microwave detection apparatus as claimed in claim 71 wherein the transmit antenna is integrated with the receive antenna in a transceive mode based on a configuration of the common receive antenna.
73. A microwave detection device according to any one of claims 41-53, wherein the receiving antenna is arranged in a planar patch antenna configuration with a reference ground and a radiation source, wherein the radiation source is disposed at one side of the reference ground in a state spaced apart from the reference ground, wherein the radiation source is arranged in a unit radiation source configuration having a single number of radiation elements corresponding to the radiation source, wherein the radiating element has two feeding points, wherein the two feeding points are orthogonally arranged, connecting lines corresponding to the two feeding points and the physical center point of the radiating element are mutually perpendicular, and one of the feeding points is electrically connected with a phase shifter, so that the echo signals in a balanced differential signal form are output between one end of the phase shifter far away from the feeding point and the other feeding point based on the phase shifting processing of the phase shifter on the echo signals accessed from the feeding point.
74. A microwave detection apparatus as claimed in claim 73 wherein the radiating element is electrically connected to the reference ground at its physical centre point.
75. The microwave detection apparatus of claim 74, wherein the radiating element has at least one set and/or at least one pair of grounding points electrically connected to the reference ground, wherein the grounding points of the same group are positioned at each vertex of the same regular polygon taking the physical central point of the radiating element as a midpoint, each grounding point corresponding to the grounding point in the same group is arranged around the physical central point of the radiation element at equal angles in a state of being equidistant from the physical central point of the radiation element, wherein the grounding points of the same pair are symmetrically distributed on the radiating element with the physical center point of the radiating element, the connecting line segment corresponding to the grounding point of the same pair takes the physical central point of the radiating element as a midpoint, and forms a zero potential point at the physical central point of the radiating element based on the electrical connection relationship between the grounding point and the reference ground, so that the connecting line segment is equivalent to the physical central point of the radiating element and the reference ground in electrical connection.
76. The microwave detection apparatus according to claim 73, wherein in a state where the transmission antenna is also set in a planar patch antenna state, the transmission antenna and the reception antenna are integrally set in a transceiving separated form based on a structural form of sharing the reference ground.
77. The microwave detecting device according to any of claims 41-53, wherein the receiving antenna is configured in a planar patch antenna configuration having a ground reference and a radiation source, wherein the radiation source is configured in a state spaced apart from the ground reference at one side of the ground reference, wherein the radiation source is configured in a binary radiation source configuration having two radiation elements corresponding to the radiation source, wherein each of the radiation elements has a feeding point, wherein the two radiation elements are orthogonally arranged, and a connection line direction from the feeding point to a physical center point of one of the radiation elements is perpendicular to a connection line direction from the feeding point to a physical center point of the other radiation element, wherein one of the feeding points is electrically connected with a phase shifter for phase-shifting the echo signal received from the feeding point based on the phase shifter, and outputting the echo signals in a balanced differential signal form between one end of the phase shifter far away from the feeding point and the other feeding point.
78. A microwave detection apparatus as claimed in claim 77 wherein the radiating element is electrically connected to the reference ground at its physical centre point.
79. The microwave detection apparatus of claim 78 wherein at least one of said radiating elements has at least one set and/or at least one pair of ground points electrically connected to said reference ground, wherein the grounding points of the same group are positioned at each vertex of the same regular polygon taking the physical central point of the radiating element as a midpoint, each grounding point in the grounding points corresponding to the same group is arranged around the physical central point of the radiation element at equal angles in a state of being equidistant from the physical central point of the radiation element, wherein the grounding points of the same pair are symmetrically distributed on the radiating element with the physical center point of the radiating element, the connecting line segment corresponding to the grounding point of the same pair takes the physical central point of the radiating element as a midpoint, and forms a zero potential point at the physical central point of the radiating element based on the electrical connection relationship between the grounding point and the reference ground, so that the zero potential point is equivalent to the physical central point of the radiating element and the reference ground are electrically connected.
80. The microwave detection apparatus according to claim 77, wherein in a state where the transmission antenna is also set in a planar patch antenna state, the transmission antenna and the reception antenna are integrally set in a transceiving separated form based on a structural form of sharing the reference ground.
81. The microwave detecting device according to any one of claims 41-53, wherein the receiving antenna is provided as a half-wave folded directional microwave detecting antenna in a cross-polarized vertical structure, and comprises a ground reference, two half-wave oscillators and four feeding lines corresponding to the receiving antenna, wherein each of the half-wave oscillators has an electrical length of 1/2 or more and 3/4 or less in wavelength, and has two coupling sections, wherein each of the coupling sections has an electrical length of 1/6 or more in wavelength, one end of each of the coupling sections is named as a feeding end of the coupling section, and the other ends of the two coupling sections are both ends of the half-wave oscillator, wherein a distance between the feeding ends of each of the half-wave oscillators is λ/4 or less, and a distance between both ends of each of the half-wave oscillator is λ 128 or more and λ/6 or less, wherein λ is a wavelength parameter corresponding to a frequency of the excitation signal, wherein each of the half-wave resonators is spaced apart from the reference ground in a state where a distance between both ends of each of the half-wave resonators and the reference ground is λ/128 or more and λ/6 or less, wherein four of the feeder lines are electrically connected to the corresponding feeder terminals, respectively, wherein two of the half-wave resonators are orthogonally arranged, corresponding to a direction perpendicular to the reference ground as a height direction of the half-wave backfolding type directional microwave detecting antenna, each of the half-wave resonators is inverted from the two feeder terminals in an extending direction perpendicular to the height direction of the half-wave backfolding type directional microwave detecting antenna, and two of the half-wave resonators are perpendicular to each other in an extending direction perpendicular to the height direction of the half-wave backfolding type directional microwave detecting antenna, wherein one of the feeder terminals of one of the half-wave resonators is connected with a phase shifter through the feeder line, and outputting the echo signal in a balanced differential signal form between one end of the phase shifter far away from the feed end and one of the feed ends of the other half-wave oscillator based on the phase shift processing of the phase shifter on the echo signal accessed from the feed end.
82. The microwave detection device of claim 81, wherein each half-wave dipole is shifted and reversed in an extending direction perpendicular to a height direction of the half-wave folded directional microwave detection antenna from the two feeding ends, and a state in which the two half-wave dipoles are orthogonally arranged corresponds to a structural form in which the four feeding ends are located at four vertex positions of a square diagonal from a line connecting the two feeding ends of each half-wave dipole.
83. A microwave detection apparatus according to claim 82 wherein the transmit antenna is integrally provided with the receive antenna based on a configuration which shares the receive antenna.
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| CN202220775915.XU Active CN217332843U (en) | 2022-01-25 | 2022-04-02 | Microwave detection device with micro-transmitting power |
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| CN202220769697.9U Active CN217332838U (en) | 2022-01-25 | 2022-04-02 | Microwave detection device |
| CN202320035830.2U Active CN218958019U (en) | 2022-01-25 | 2023-01-06 | Double-end feed type differential antenna |
| CN202310020857.9A Pending CN116148833A (en) | 2022-01-25 | 2023-01-06 | Micro-emission power microwave detection device |
| CN202310020862.XA Pending CN116231275A (en) | 2022-01-25 | 2023-01-06 | Double-end feed type differential antenna |
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| CN218331959U (en) * | 2022-01-25 | 2023-01-17 | 深圳迈睿智能科技有限公司 | Microwave detection device |
| CN116794607A (en) * | 2023-04-16 | 2023-09-22 | 深圳迈睿智能科技有限公司 | Anti-interference microwave detection method and device |
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| CN114624698A (en) | 2022-06-14 |
| CN217332841U (en) | 2022-08-30 |
| WO2023143104A1 (en) | 2023-08-03 |
| CN218958019U (en) | 2023-05-02 |
| CN217766842U (en) | 2022-11-08 |
| CN217332843U (en) | 2022-08-30 |
| CN218727992U (en) | 2023-03-24 |
| CN217360292U (en) | 2022-09-02 |
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| CN218331959U (en) | 2023-01-17 |
| CN116148833A (en) | 2023-05-23 |
| CN217332839U (en) | 2022-08-30 |
| CN116231275A (en) | 2023-06-06 |
| CN217820849U (en) | 2022-11-15 |
| CN217820850U (en) | 2022-11-15 |
| CN114624696A (en) | 2022-06-14 |
| CN217332838U (en) | 2022-08-30 |
| CN219811054U (en) | 2023-10-10 |
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| CN114624697A (en) | 2022-06-14 |
| CN217332842U (en) | 2022-08-30 |
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