CN217820850U - Microwave detection device with micro-transmitting power - Google Patents

Microwave detection device with micro-transmitting power Download PDF

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CN217820850U
CN217820850U CN202220784827.6U CN202220784827U CN217820850U CN 217820850 U CN217820850 U CN 217820850U CN 202220784827 U CN202220784827 U CN 202220784827U CN 217820850 U CN217820850 U CN 217820850U
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signal
antenna
differential
feeding
microwave
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邹高迪
孙毅
邹新
邹明志
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Shenzhen Merrytek Technology Co Ltd
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    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
    • G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
    • G01S13/50—Systems of measurement based on relative movement of target
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01N—INVESTIGATING OR ANALYSING MATERIALS BY DETERMINING THEIR CHEMICAL OR PHYSICAL PROPERTIES
    • G01N22/00—Investigating or analysing materials by the use of microwaves or radio waves, i.e. electromagnetic waves with a wavelength of one millimetre or more
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01V—GEOPHYSICS; GRAVITATIONAL MEASUREMENTS; DETECTING MASSES OR OBJECTS; TAGS
    • G01V3/00—Electric or magnetic prospecting or detecting; Measuring magnetic field characteristics of the earth, e.g. declination, deviation
    • G01V3/12—Electric or magnetic prospecting or detecting; Measuring magnetic field characteristics of the earth, e.g. declination, deviation operating with electromagnetic waves
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors

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  • Remote Sensing (AREA)
  • Physics & Mathematics (AREA)
  • Radar, Positioning & Navigation (AREA)
  • General Physics & Mathematics (AREA)
  • Life Sciences & Earth Sciences (AREA)
  • Computer Networks & Wireless Communication (AREA)
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  • General Health & Medical Sciences (AREA)
  • Immunology (AREA)
  • Pathology (AREA)
  • Radar Systems Or Details Thereof (AREA)
  • Variable-Direction Aerials And Aerial Arrays (AREA)
  • Waveguide Aerials (AREA)
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Abstract

The utility model provides a little transmitted power's microwave detection device, wherein little transmitted power's microwave detection device has broken through technical staff in the field and has tended to improve the technical tendency of echo signal's intensity, the antenna based on communication usage pursues high signal strength's universality, through reducing little transmitted power's microwave detection device's transmitting antenna's transmitted power, the combination is with the echo signal's of the balanced difference signal form of access mode, and it is corresponding to reduce microwave beam with the signal strength to the weak signal form of reflection echo to the end suppression mechanism of making an uproar on the basis of communication device is from, avoid causing the interference to corresponding communication device, and utilize the masonry structure or the glass that define the target detection space to weak signal form the absorption of microwave beam forms to the adaptability on the gradient border of microwave beam is defined to can ensure corresponding Doppler intermediate frequency signal to with the feedback precision of human activity characteristic.

Description

Microwave detection device with micro-transmitting power
Technical Field
The utility model relates to a microwave detection field, in particular to little transmitting power's microwave detection device based on doppler effect principle.
Background
With the development of the internet of things technology, the requirements of artificial intelligence, smart home and intelligent security technology on environment detection, particularly on detection accuracy of human existence, movement and micro motion are higher and higher, and accurate judgment basis can be provided for intelligent terminal equipment only by acquiring a stable enough detection result. The microwave detection technology based on the Doppler effect principle is used as a person and an object, and an important junction connected between the object and the object has unique advantages in behavior detection and existence detection technology, can detect moving objects such as action characteristics, movement characteristics and micro-movement characteristics of the person and even heartbeat and respiration characteristic information of the person under the condition of not invading the privacy of the person, and has wide application prospect. Specifically, a microwave detector is fed by an excitation signal to emit a microwave beam with a frequency corresponding to the excitation signal to the target space, so as to form a detection region in the target space, and a reflected echo formed by the microwave beam reflected by a corresponding object in the detection region is received to transmit an echo signal corresponding to the frequency of the reflected echo to a mixer detection unit, wherein the mixer detection unit mixes the excitation signal and the echo signal to output a doppler intermediate frequency signal corresponding to a frequency/phase difference between the excitation signal and the echo signal, wherein based on the doppler effect principle, when the object reflecting the microwave beam is in a moving state, the echo signal and the excitation signal have a certain frequency/phase difference and the doppler intermediate frequency signal exhibits corresponding amplitude fluctuation to feed back human body activity.
In ISM bands defined by ITU-R (ITU radio communication Sector) for unlicensed use by organizations such as industry, science and medicine, limited frequency band resources such as 2.4Ghz, 5.8Ghz, 10.525Ghz, 24.125 Ghz, etc., are mainly used for microwave detection, and the corresponding microwave detectors need to observe certain transmission power (generally, transmission power is lower than 1W) to reduce interference to other radio devices when using these frequency bands, although the definition and permission of different frequency bands can regulate the use frequency bands of radios to reduce the probability of mutual interference between radio devices of different frequency bands, under the permission of limited frequency band resources, with the high-speed development of the internet of things technology, the high-speed increase of radio use coverage rate corresponding to adjacent frequency bands or the same frequency band, such as the increasingly popular 5G wireless router, or the 5G wireless router based on the duplex mode on the basis of the original 2.4G wireless router, so that the problem of increasing mutual interference between adjacent frequency bands or the same frequency band based on the basis of the internet of the original 2.4G wireless router, and even the heartbeat movement is greatly increased as a competitive movement of people. Therefore, the anti-interference performance is one of the factors that measure the accuracy of the corresponding microwave detection module, and under the circumstance that the problem of mutual interference between radios is becoming serious, the accuracy of the existing microwave detector is difficult to maintain, and not to mention, the requirement of accurate detection of human motion characteristics including breathing motion and even heartbeat motion is satisfied.
Further, since the boundary of the corresponding microwave beam is a gradient boundary with the radiation energy attenuated to a certain degree, it is non-deterministic, and since there is no effective control means for the electromagnetic radiation, i.e. shaping means for the gradient boundary of the corresponding microwave beam, which is mainly reflected in the lack of adjusting means for the beam angle of the microwave beam, the actual detection space covered by the microwave beam emitted by the corresponding microwave detector is difficult to be stably controlled, and further based on the reflection and penetration behavior of the microwave beam in different target detection spaces, the actual detection space of the existing microwave detector cannot be matched with the corresponding target detection space based on the adjustment of the beam angle of the microwave beam independently, such that the problem of poor accuracy and/or interference resistance of the existing microwave detection technology based on the doppler effect principle is caused by the condition that the target detection space outside the actual detection space cannot be effectively detected, and/or the condition that the environment interference exists in the actual detection space outside the target detection space, including the action interference, the electromagnetic interference and the self-excitation interference caused by the environment, the problem that the boundary of the microwave beam is attenuated to a certain degree, while the gradient boundary of the microwave beam is poorly matched with the stability of the actual detection of the microwave detector, and the microwave beam is difficult to be applied in the existing microwave detection scene, and the microwave detector.
In order to solve the above drawbacks, the conventional microwave detector mainly reduces the probability of mutual interference between antennas in the same frequency band by narrowing the frequency bandwidth of the antennas, and increases the amplitude difference of the corresponding effective signal relative to the interference signal in the doppler intermediate frequency signal by increasing the strength of the echo signal, so as to set and reduce the sensitivity of the microwave detection module with the corresponding threshold value of the doppler intermediate frequency signal on the amplitude value, thereby eliminating the environmental interference of the actual detection space outside the target detection space corresponding to the interference signal with a low amplitude value based on the reduction of the sensitivity. On one hand, although the probability of mutual interference between antennas in the same frequency band can be reduced by narrowing the frequency bandwidth of the antennas, based on the difference in the operating principle, antennas for communication purposes (such as antennas in a wireless router) are often designed to have a wider frequency bandwidth to meet the requirement of multi-channel communication, and narrowing the frequency bandwidth of the antennas of the microwave probe cannot ensure that the antennas of the existing microwave probe are not interfered by the antennas for communication purposes or do not cause interference to the antennas for communication purposes under the background that the coverage rate of radio use in adjacent frequency bands or the same frequency band is increased at a high speed; in addition, based on the corresponding relationship between the frequency bandwidth of the antenna and the structural form and size of the antenna, the narrowing of the frequency bandwidth of the antenna of the microwave detector can simultaneously form high-precision requirements on the structure and size of the antenna, and the corresponding high-precision requirements are severer along with the improvement of the resonant frequency point of the antenna, so that additional cost burden is correspondingly generated. On the other hand, since the amplitude of the doppler intermediate frequency signal is related to the energy of the reflected echo and is also related to the size of the reflecting surface area in the environment, the size and the moving speed of the reflecting surface of the moving object and the distance between the microwave detection module, the reduction of the sensitivity of the microwave detector cannot accurately exclude the environmental interference and the motion interference of the actual detection space outside the target detection space, so that the detection of the target detection space is not stable and accurate; in addition, based on the high strength requirement of the existing microwave detector for the echo signal, the range adjustment for the actual detection space tends to have a higher electromagnetic radiation energy density in the target detection space while covering the corresponding target detection space, so that the existing microwave detector cannot avoid interference to the antenna for communication use in the target detection space based on the reduction of the sensitivity, and it is difficult to avoid interference to the antenna for communication use in the target detection space based on the reduction of the sensitivity in pursuit of the antenna for communication use for high signal strength.
SUMMERY OF THE UTILITY MODEL
An object of the utility model is to provide a little transmitted power's microwave detection device, wherein little transmitted power's microwave detection device has broken through technical staff in the field and has tended to improve the technical tendency of echo signal's intensity, based on the antenna of communication usage is to the universal pursuit of high signal strength, through reducing little transmitted power's microwave detection device's transmitting antenna's transmitting power's mode has reduced correspondingly the microwave beam with the signal strength of reflection echo has reduced promptly the microwave beam with the electromagnetic radiation energy density of reflection echo, and then can utilize communication device from the end of taking to make an uproar inhibition mechanism, it is right to avoid causing the interference to corresponding communication device and can reduce or even remove communication device's in the installation position in corresponding installation environment the restriction of little transmitted power's microwave detection device in the installation position of corresponding installation environment.
Another object of the present invention is to provide a microwave detecting device with micro transmitting power, wherein the signal intensity of the microwave beam is reduced by reducing the transmitting power of the transmitting antenna of the microwave detecting device with micro transmitting power, so that the loss generated by the penetrating action of the microwave beam on the concrete wall or glass of the masonry structure is much larger than the loss generated by the propagation in the space, and the signal intensity of the microwave beam is reduced to be in a weak signal form, the microwave detection device comprises a microwave beam, a target detection space and a micro-transmitting power microwave detection device, wherein the microwave beam is absorbed by a concrete wall or glass of a masonry structure for defining the target detection space, the microwave beam is in a weak signal form, the adaptability of a gradient boundary of the microwave beam in the weak signal form is defined, and the state of the space form of the target detection space is not limited correspondingly, so that an effective detection space of the micro-transmitting power microwave detection device, which is bounded by the concrete wall or glass of the masonry structure, can be matched with the corresponding target detection space, and the adaptability of the micro-transmitting power microwave detection device to different target detection spaces in practical application is improved.
Another object of the present invention is to provide a microwave detecting device of micro-transmitting power, wherein through reducing the transmitting power's of the transmitting antenna of the microwave detecting device of micro-transmitting power, the signal intensity of the microwave beam is reduced and is weak signal form, then based on the produced loss of the reflection action of the microwave beam for the ratio of the radiant energy of the microwave beam is improved, so as to avoid the self-excited interference based on the multiple reflection action.
Another object of the utility model is to provide a little transmitted power's microwave detection device, wherein through reducing little transmitted power's microwave detection device's transmitting antenna's transmitted power's mode, transmitting antenna's noise immunity is right transmitting antenna's frequency bandwidth's dependency is reduced, and it is right that the correspondence has been reduced transmitting antenna's required precision and be favorable to reducing transmitting antenna's manufacturing cost.
Another object of the present invention is to provide a microwave detecting device of micro transmitting power, wherein the reduction of the transmitting power of the transmitting antenna of the microwave detecting device of micro transmitting power is not intended to adjust the gradient boundary of the microwave beam in the conventional sense, the transmitting antenna of the microwave detecting device of micro transmitting power is excited to transmit the state of the microwave beam, based on the principle knowledge that the coverage space range of the microwave beam corresponds to the gain (dBd or dBi) of the transmitting antenna of the microwave detecting device of micro transmitting power and is not controlled by the transmitting power of the transmitting antenna, the present invention reduces the electromagnetic radiation energy density of the microwave beam in the coverage space by reducing the transmitting power of the transmitting antenna, so as to improve the ratio of the loss generated by the penetrating behavior of the microwave beam to the radiation energy of the microwave beam, thereby the signal strength of the microwave beam is reduced to be in a weak signal form, the absorption of the microwave beam to be in a weak signal form by using the wall or glass of the masonry structure defining the target detection space or the absorption of the glass to the weak signal form of the brick structure, thereby the gradient boundary of the microwave beam is adapted to the microwave detection device of the microwave beam in the target soil, thereby improving the application of the microwave beam in the microwave detection device of the microwave beam.
Another object of the present invention is to provide a microwave detecting device of micro transmitting power, wherein the reduction of the transmitting power of the transmitting antenna of the microwave detecting device of micro transmitting power is not aimed at adjusting the gradient boundary of the microwave beam in the conventional sense, and the transmitting antenna of the microwave detecting device of micro transmitting power is excited to transmit the microwave beam in the state that the coverage space range of the microwave beam corresponds to the gain (dBd or dBi) of the transmitting antenna of the microwave detecting device of micro transmitting power and is not controlled by the transmitting power of the transmitting antenna, so that the present invention reduces the electromagnetic radiation energy density of the microwave beam in the coverage space thereof to the weak signal form suitable for being suppressed by the corresponding communication device based on the self-contained bottom noise suppression mechanism by reducing the transmitting power of the transmitting antenna, thereby breaking through the technical tendency that the microwave beam tends to have higher electromagnetic radiation energy density in the target detection space while covering the corresponding target detection space.
Another object of the present invention is to provide a microwave detecting device of micro-transmitting power, wherein the transmitting power (dBm) = signal source power (dBm) -transmission line loss (dB) + the theoretical cognition of the transmitting antenna gain (dBd or dBi) of the transmitting antenna of the microwave detecting device based on the micro-transmitting power, and the experimental discovery cognition of the bottom noise suppression mechanism of the communication device in the non-field, the present invention reduces the transmitting power of the transmitting antenna to less than or equal to 0dBm to form the weak signal form of the microwave beam, corresponding to the electromagnetic radiation energy density of the microwave beam in the coverage space thereof approaching to the electromagnetic radiation energy density outside the gradient boundary and the gradient boundary in the traditional meaning, so that the reduction of the transmitting power of the transmitting antenna of the microwave detecting device of micro-transmitting power is not aimed at adjusting the gradient boundary in the traditional meaning of the microwave beam.
Another object of the present invention is to provide a microwave detecting device of micro transmitting power, wherein the detecting method of the microwave detecting device of micro transmitting power includes improving the conversion efficiency of the transmitting antenna, so as to avoid the transmitting antenna cannot complete the initial polarization and cannot transmit correspondingly in the state where its transmitting power is reduced based on the dielectric loss of itself the technical obstacle of the microwave beam corresponds to the guarantee the state of the stable transmission of the microwave beam is reduced the minimum transmitting power extreme value of the transmitting antenna, so as to reduce the state of the transmitting power of the transmitting antenna to the corresponding target transmitting power ensures the stable transmission of the microwave beam.
Another object of the present invention is to provide a microwave detecting device of micro transmitting power, wherein through the mode of phase difference feed, realize transmitting antenna's circular polarization form and reduce transmitting antenna's minimum transmitting power extreme is guaranteeing the state of the stable transmission of microwave beam reduces transmitting antenna's minimum transmitting power extreme, in order to reduce transmitting antenna's transmitting power to the state guarantee micro signal form of target transmitting power the stable transmission of microwave beam.
Another object of the utility model is to provide a little transmitted power's microwave detection device, wherein through the mode of difference feed transmitting antenna adopts the linear polarization form transmitting antenna's state, in transmitting antenna's linear polarization direction realizes right transmitting antenna is greater than the differential feed of 90 phase differences, in order to reduce transmitting antenna reduces based on the loss that electric field coupling produced at the initial polarization in-process transmitting antenna's minimum transmitted power extreme value, thereby reducing transmitting antenna's transmitted power to target transmitted power's state, the guarantee transmitting antenna is to the micro-signal form the stable transmission of microwave beam.
Another object of the utility model is to provide a little transmitted power's microwave detection device, wherein reduce based on the mode of transmitting antenna's self dielectric loss reduces transmitting antenna's minimum transmitted power extreme value, little transmitted power's microwave detection device adopts half-wave inflection formula directional microwave detection antenna as transmitting antenna, with based on half-wave inflection formula directional microwave detection antenna uses the air to reduce as the structural feature of medium transmitting antenna's self dielectric loss and reduction transmitting antenna's minimum transmitted power extreme value, and based on half-wave inflection formula directional microwave detection antenna's high gain characteristic further reduces transmitting antenna's minimum transmitted power extreme value, thereby reducing transmitting antenna's transmitted power to the state guarantee micro-signal form that is less than or equal to 0dBm or lower the stable transmission of microwave beam.
Another objective of the present invention is to provide a microwave detecting device of micro transmitting power, wherein the minimum transmitting power extreme value of the transmitting antenna is reduced based on the manner of reducing the self dielectric loss of the transmitting antenna, the microwave detecting device of micro transmitting power adopts a dual-end feeding differential antenna as the transmitting antenna, wherein the dual-end feeding differential antenna comprises a reference ground and two strip-shaped oscillators, wherein two ends of the two strip-shaped oscillators connected to the excitation signal are respectively the feeding ends of the two strip-shaped oscillators, the two strip-shaped oscillators extend from the same lateral space of the reference ground at the two feeding ends and respectively have a wavelength electrical length greater than or equal to 3/16 and less than or equal to 5/16, wherein the two strip-shaped oscillators respectively have a coupling section, wherein the end of the coupling section close to the feeding end of the strip-shaped oscillator to which the coupling section belongs is the near end of the coupling section, the two coupling sections extend in the direction opposite to the dislocation direction from the near end and have a dislocation distance which is greater than or equal to lambda/256 and less than or equal to lambda/6, namely, the distance from any point on one coupling section to the other coupling section is greater than or equal to lambda/256 and less than or equal to lambda/6, wherein lambda is a wavelength parameter corresponding to the frequency of the excitation signal, so that the double-ended feed type differential antenna is used as the transmitting antenna in a state that the excitation signals with the difference of more than 90 DEG are accessed to the two feeding ends of the two strip-shaped elements and are fed by the difference of phase, a polarization form tending to linear polarization is realized based on the fact that the coupling between the two strip-shaped elements and the reference ground has the difference of more than 90 DEG, and the coupling between the two coupling sections is formed based on a structural form that the two coupling sections extend in the direction opposite to the dislocation direction from the near end, and a common resonance frequency point is formed based on mutual coupling between the two coupling sections, namely, in a state that the double-feed differential antenna is used as the transmitting antenna to access excitation signals with a difference of more than 90 degrees at the two feeding ends of the two strip-shaped oscillators, differential feeding to the transmitting antenna is realized in a polarization direction of the transmitting antenna which tends to be linearly polarized, the minimum transmitting power extreme value of the transmitting antenna is reduced in a state of ensuring stable transmitting of the microwave beam, and further, stable transmitting of the microwave beam in a micro-signal form is ensured in a state of reducing the transmitting power of the transmitting antenna to a target transmitting power.
Another object of the present invention is to provide a microwave detecting device of micro-transmitting power, wherein the transmitting antenna is in a linear polarization state, the polarization direction of the transmitting antenna is preferably based on the balanced differential feeding that the transmitting antenna tends to 180 ° phase difference, or the dual-feed differential antenna is adopted as the state of the transmitting antenna is preferably based on the balanced differential feeding that the transmitting antenna tends to 180 ° phase difference, the state of the stable transmission of the microwave beam is ensured to reduce the minimum transmitting power extreme value of the transmitting antenna, so as to reduce the transmitting power of the transmitting antenna to the state of less than or equal to 0dBm or lower to ensure the stable transmission of the microwave beam.
Another object of the present invention is to provide a microwave detecting device of micro-transmitting power, wherein the microwave detecting device of micro-transmitting power includes a differential feeder circuit, wherein the differential feeder circuit is provided in the form of discrete components and has a three-pole circuit handler provided as an MOS transistor or a triode, an inductor, a first resistor, a second resistor, a third resistor, a first capacitor, a second capacitor, an oscillating capacitor and a power connection terminal adapted to be connected to a corresponding power source, wherein the three-pole circuit handler has a first connection terminal corresponding to a collector of the triode or a drain of the MOS transistor, a second connection terminal corresponding to a base of the triode or a gate of the MOS transistor, and a third connection terminal corresponding to an emitter of the triode or a source of the MOS transistor, wherein one end of the second resistor is electrically connected to the first connection terminal of the three-pole circuit handler, the other end of the second resistor is connected to the power connection terminal via the inductor, and is grounded via the first capacitor, wherein one end of the third resistor is electrically connected to the third connection terminal of the three-pole circuit processor, and the other end of the third resistor is grounded, wherein one end of the oscillating capacitor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the oscillating capacitor is grounded, wherein one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the first resistor is electrically connected between the inductor and the second resistor or to the power connection terminal, wherein two ends of the second capacitor are electrically connected to the first connection terminal and the third connection terminal of the three-pole circuit processor, respectively, the second resistor and the third resistor are set to be equal in resistance value, so that in the state that the differential feed circuit is connected to a corresponding power supply at the power supply connecting end, the excitation signal is output at two ends of the second capacitor in a balanced differential signal form with a phase difference approaching 180 degrees, and therefore phase difference feeding of the transmitting antenna approaching 180 degrees is achieved.
Another object of the present invention is to provide a microwave detecting device of micro-transmitting power, wherein the microwave detecting device of micro-transmitting power includes a differential feeding circuit, wherein the differential feeding circuit is configured in an integrated circuit manner and has two opposite phase outputs, so that two opposite phase outputs output a balanced differential signal having a phase difference of 180 ° to the excitation signal.
Another object of the present invention is to provide a microwave detecting device of micro-transmitting power, wherein the detecting method of the microwave detecting device of micro-transmitting power further includes improving the step of the accuracy of the echo signal, so that the intensity of the echo signal is based on the state that the transmitting power of the transmitting antenna is reduced, based on the improvement of the accuracy of the echo signal, the guarantee the microwave detecting device of micro-transmitting power moves, moves with the human body, and the accuracy and stability of the detection and the detection of the detection range of the activity characteristic corresponding to the breathing and the heartbeat.
Another object of the present invention is to provide a microwave detecting device of micro transmitting power, wherein the improvement step of the accuracy of the echo signal includes accessing the echo signal of a balanced differential signal form from the receiving antenna of the microwave detecting device of micro transmitting power, then the electromagnetic interference in the environment exists in the echo signal in a common mode interference form, so that the echo signal in the balanced differential signal form can be suppressed during the receiving and transmitting processes, and then the doppler intermediate signal in the balanced differential signal form is output based on the echo signal mixing processing step of the balanced differential signal form, and the doppler intermediate signal in the balanced differential signal form is output based on the intermediate frequency doppler signal differential to single-ended processing step of the intermediate frequency doppler signal in the balanced differential signal form, so that the further suppression effect of the common mode interference in the echo signal based on the balanced differential signal form and/or the doppler intermediate frequency signal differential processing step of the balanced differential signal form to the balanced differential signal form, the single-ended processing step of the balanced differential signal and/or the doppler intermediate frequency signal to the balanced differential signal form is output based on the balanced differential signal to single-ended processing step of the balanced differential signal form, thereby the single-ended signal to be detected and the micro transmitting power and the echo signal receiving system, thereby the micro transmitting power and the micro transmitting power detection system The detection range and the detection accuracy and stability of the micro-motion, the respiration and the heartbeat motion are corresponding to the activity characteristics.
Another object of the present invention is to provide a microwave detecting device of micro transmitting power, wherein it is right that the improvement step of the accuracy of the echo signal includes from the receiving antenna of the microwave detecting device of micro transmitting power accesses the step of the echo signal in the form of balanced differential signal, then the electromagnetic interference in the environment is in the form of common mode interference in the echo signal, so that the echo signal can be suppressed in the receiving and transmitting processes based on the balanced differential signal form, and in the subsequent step, the further suppression effect of the common mode interference in the echo signal based on the step of differential to single-ended processing of the echo signal changes the form of balanced differential signal, the echo signal in the form of single-ended signal free from environmental electromagnetic interference is output, and the feedback accuracy of the activity characteristics based on the form of mixing processing of the echo signal, the doppler intermediate frequency signal free from environmental electromagnetic interference is output, thereby improving the doppler intermediate frequency signal pair of the feedback accuracy of the activity characteristics corresponding to the breathing activity, micro-motion, and the micro-motion stability of the microwave detecting device based on the above self transmitting power, the microwave detecting device of micro transmitting power, the micro-transmission power, the microwave detecting device, and the micro-transmission power detection system.
Another object of the present invention is to provide a microwave detecting device with micro transmitting power, wherein the differential to single-end processing step of the doppler intermediate frequency signal to balance the differential signal form is based on the further suppressing effect of the common-mode interference in the doppler intermediate frequency signal to balance the differential signal form, or the differential to single-end processing step of the echo signal to balance the differential signal form is based on the further suppressing effect of the common-mode interference in the echo signal to balance the differential signal form, in the environment, the electromagnetic radiation interference which is not homologous to the echo signal is present in the state received by the receiving antenna in the common-mode form in the balance differential signal form the echo signal can be effectively suppressed, including in the environment, the electromagnetic radiation interference of the echo signal, so as to improve the feedback accuracy of the doppler intermediate frequency signal to the moving action, the micro-moving action, and the moving characteristic corresponding to breathing and the heartbeat action.
Another object of the present invention is to provide a microwave detecting device of little transmitted power, wherein from the receiving antenna of the microwave detecting device of little transmitted power inserts balanced differential signal form the step of echo signal includes that two states of receiving the feed point of receiving antenna are arranged by the quadrature insert balanced differential signal form based on the phase shift step of the echo signal that inserts to one of them receiving feed point echo signal, in order to be based on quadrature form guarantee between two receiving feed points of receiving antenna certainly isolation between the echo signal that two receiving feed points of receiving antenna insert corresponds the guarantee based on the balanced differential signal form of the phase shift step access of the echo signal that one of them receiving feed point inserts echo signal's precision of echo signal.
Another object of the present invention is to provide a microwave detecting device of micro-transmitting power, wherein the receiving antenna of the microwave detecting device of micro-transmitting power is connected to the balanced differential signal form in the step of the echo signal, two receiving feeding points of the receiving antenna are arranged in opposite phase, and two receiving feeding points are connected to the balanced differential signal form of the echo signal.
Another object of the present invention is to provide a microwave detecting device with micro transmitting power, wherein the transmitting antenna of the microwave detecting device with micro transmitting power and the receiving antenna share the structural configuration of the reference ground is set and favorable to the miniaturization design of the microwave detecting device with micro transmitting power.
Another object of the present invention is to provide a microwave detecting device of micro-transmitting power, wherein the micro-transmitting power microwave detecting device the transmitting antenna with the receiving antenna is set up by an organic whole with the receiving and dispatching separation form, in order to ensure isolation between the corresponding feed points (ends) and guarantee the accuracy of echo signal, and is favorable to the miniaturized design of the micro-transmitting power microwave detecting device.
Another object of the present invention is to provide a microwave detecting device of micro transmitting power, wherein the microwave detecting device of micro transmitting power the transmitting antenna with the receiving antenna is integrated with the receiving and transmitting integration form to simplify the circuit design of the microwave detecting device of micro transmitting power is favorable to the miniaturization design of the microwave detecting device of micro transmitting power.
According to an aspect of the utility model, the utility model provides a little transmitted power's microwave detection device, wherein little transmitted power's microwave detection device includes:
a differential feed circuit, wherein the differential feed circuit is configured to output excitation signals that differ by more than 90 ° in a powered state;
a transmitting antenna, wherein the transmitting antenna is configured as a dual-feed differential antenna, the transmitting antenna comprises a reference ground and two strip-shaped oscillators, two ends of an accessed excitation signal of the two strip-shaped oscillators are respectively feed ends of the two strip-shaped oscillators, the two strip-shaped oscillators extend from the two feed ends in the same lateral space of the reference ground and respectively have a wavelength electrical length of 3/16 or more and 5/16 or less, the two strip-shaped oscillators respectively have a coupling section, one end of the coupling section close to the feed end of the strip-shaped oscillator to which the coupling section belongs is a proximal end of the coupling section, the two coupling sections extend from the proximal end in a facing direction, and based on a structural form that the two coupling sections extend from the proximal end in the facing direction, a coupling between the two coupling sections is formed in a state that the two feed ends of the two strip-shaped oscillators are accessed into the excitation signal with a phase difference, and a polarization form of the two feed ends of the two strip-shaped oscillators is accessed into the excitation signal with a phase difference of 90 degrees, so that the two feed ends of the transmitting antenna are fed to realize a polarization state of the transmitting antenna relative to the feeding direction of the transmitting antenna;
a receiving antenna, wherein the receiving antenna has a polarization direction tending to linear polarization and outputs a corresponding echo signal in a balanced differential signal form with a phase difference tending to 180 ° after receiving a reflected echo formed by a microwave beam emitted by the transmitting antenna being reflected by a corresponding object, and then the echo signal contains a signal corresponding to a reflected echo formed by the microwave beam being reflected by the corresponding object, and electromagnetic interference in the environment exists in a common-mode interference form in the echo signal and can be suppressed during the receiving and transmitting processes of the echo signal in the balanced differential signal form; and
a mixer circuit electrically connected to the differential feed circuit and the receiving antenna for receiving the excitation signal and the echo signal in a balanced differential signal form and outputting a doppler intermediate frequency signal in a single-ended signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal.
In one embodiment, two of the coupling sections of the double-fed differential antenna extend from the proximal end in opposite directions of the offset, and have an offset distance of λ/256 or more and λ/6 or less, that is, a distance from any point on one of the coupling sections to the other coupling section is λ/256 or more and λ/6 or less, where λ is a wavelength parameter corresponding to the frequency of the excitation signal.
In one embodiment, the two coupling sections of the two strip-shaped oscillators extend from the near end to each other in parallel offset directions.
In one embodiment, the strip-shaped vibrator is disposed in a microstrip line carried on the circuit board.
In an embodiment, the receiving antenna is configured as the double-feed differential antenna, so that based on a structural characteristic that two coupling sections of two strip-shaped oscillators extend from the near end in opposite directions and can be coupled with each other to form a common resonant frequency point, the two strip-shaped oscillators are formed in a structural state in which the two strip-shaped oscillators are arranged in opposite phases in a polarization direction tending to linear polarization, and thus when the double-feed differential antenna is used as the receiving antenna, the echo signals in a balanced differential signal form are directly output at the two feed ends.
In an embodiment, the receiving antenna and the transmitting antenna are integrally arranged in a transceiving mode based on a structural form of sharing the transmitting antenna, the echo signals in a balanced differential signal form are directly output corresponding to the two feeding ends, and differential feeding to the transmitting antenna is realized in a polarization direction of the transmitting antenna tending to linear polarization by a state that excitation signals with a difference of more than 90 ° are accessed to the two feeding ends of the two strip-shaped oscillators, so as to form an integral structure of the transmitting antenna and the receiving antenna in the transceiving mode.
In one embodiment, wherein the differential feed circuit has a three-pole circuit processor configured as a MOS transistor or a triode, an inductor, a first resistor, a second resistor, a third resistor, a first capacitor, a second capacitor, an oscillation capacitor, and a power connection terminal adapted to be connected to a corresponding power source, wherein the three-pole circuit processor has a first connection terminal corresponding to a collector of the triode or a drain of the MOS transistor, a second connection terminal corresponding to a base of the triode or a gate of the MOS transistor, and a third connection terminal corresponding to an emitter of the triode or a source of the MOS transistor, wherein one end of the second resistor is electrically connected to the first connection terminal of the three-pole circuit processor, and the other end of the second resistor is connected to the power connection terminal via the inductor and is grounded via the first capacitor, wherein one end of the third resistor is electrically connected to the third connection terminal of the three-pole circuit processor, and the other end of the third resistor is grounded, wherein one end of the oscillation capacitor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the oscillation capacitor is grounded, wherein one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the first resistor is electrically connected between the inductor and the second resistor, wherein two ends of the second capacitor are electrically connected to the first connection terminal and the third connection terminal of the three-pole circuit processor, respectively, wherein the second resistor and the third resistor are set to have equal resistance values so as to switch the differential feed circuit into the corresponding power supply at the power connection terminal, and outputting the excitation signal in a balanced differential signal form with a phase difference of about 180 degrees at two ends of the second capacitor, so that the phase difference feeding of about 180 degrees of the transmitting antenna is realized.
In one embodiment, wherein the differential feed circuit has a three-pole circuit processor configured as a MOS transistor or a triode, an inductor, a first resistor, a second resistor, a third resistor, a first capacitor, a second capacitor, an oscillation capacitor and a power connection terminal adapted to connect to a corresponding power source, wherein the three-pole circuit processor has a first connection terminal corresponding to a collector of the triode or a drain of the MOS transistor, a second connection terminal corresponding to a base of the triode or a gate of the MOS transistor, and a third connection terminal corresponding to an emitter of the triode or a source of the MOS transistor, wherein one end of the second resistor is electrically connected to the first connection terminal of the three-pole circuit processor, and the other end of the second resistor is connected to the power connection terminal via the inductor and is grounded via the first capacitor, wherein one end of the third resistor is electrically connected to the third connection terminal of the three-pole circuit processor, and the other end of the third resistor is grounded, wherein one end of the oscillation capacitor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the oscillation capacitor is grounded, wherein one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the first resistor is electrically connected to the power connection terminal, wherein two ends of the second capacitor are electrically connected to the first connection terminal and the third connection terminal of the three-pole circuit processor, respectively, wherein the second resistor and the third resistor are set to be equal in resistance value, so as to output the excitation signal in a balanced differential signal form with a difference of approximately 180 ° between the two ends of the second capacitor in a state where the differential feed circuit is connected to the corresponding power supply at the power connection terminal, thus realizing phase difference feeding of the transmitting antenna which approaches 180 degrees.
In one embodiment, the differential feeding circuit outputs the excitation signal in a differential oscillating circuit in a balanced differential signal form with a phase difference of about 180 °, wherein the differential oscillating circuit has two N-channel MOS transistors, two P-channel MOS transistors, an oscillating inductor and an oscillating capacitor, wherein the sources of the two N-channel MOS transistors are electrically connected, the sources of the two P-channel MOS transistors are electrically connected, and the drains of the two N-channel MOS transistors are electrically connected to the drains of the different P-channel MOS transistors, respectively, so as to form a drain of one of the N-channel MOS transistors electrically connected to the drain of one of the P-channel MOS transistors, a source of the P-channel MOS transistor electrically connected to the source of the other P-channel MOS transistor, and a drain of the other P-channel MOS transistor electrically connected to the drain of the other N-channel MOS transistor, and the source of the other N-channel MOS transistor is electrically connected with the source of the previous N-channel MOS transistor in a sequential connection relationship, wherein in the two N-channel MOS transistors, the gate of any one N-channel MOS transistor is electrically connected with the drain of the other N-channel MOS transistor, wherein in the two P-channel MOS transistors, the gate of any one P-channel MOS transistor is electrically connected with the drain of the other P-channel MOS transistor, wherein the two ends of the oscillation inductor are respectively and electrically connected with the drains of the different P-channel MOS transistors, and the two ends of the oscillation capacitor are respectively and electrically connected with the drains of the different P-channel MOS transistors and are connected with the oscillation inductor in parallel, so that the oscillation and frequency selection are formed based on a parallel resonance loop consisting of the oscillation inductor and the oscillation capacitor, and electric signals with equal size and opposite directions are formed at the two ends of the oscillation inductor and the oscillation capacitor, and the other N-channel MOS tube and the P-channel MOS tube electrically connected with the grid electrode of the N-channel MOS tube can be simultaneously conducted at the other moment, so that the excitation signals are output at two ends of the oscillation inductor in a balanced differential signal form with a 180-degree difference.
In an embodiment, the differential feeding circuit further includes a low dropout regulator, an oscillator, a phase-locked loop, and a logic control unit, wherein the low dropout regulator provides a constant voltage for the differential oscillating circuit in a powered state, wherein the oscillator is configured to provide a basic clock signal for the logic control unit and is externally disposed or integrally disposed with a quartz crystal oscillator for the logic control unit, wherein the logic control unit is electrically connected to the oscillating inductor of the differential oscillating circuit, wherein the phase-locked loop is electrically connected between the logic control unit and the differential oscillating circuit in a state of being externally disposed or integrally disposed with the logic control unit, so as to calibrate a frequency of the excitation signal output by the differential oscillating circuit in a balanced differential signal form with a difference of 180 ° at two ends of the oscillating inductor based on a feedback of the excitation signal output by the logic control unit for the differential oscillating circuit, thereby ensuring a stable output of the excitation signal in a balanced differential signal form by the differential feeding circuit.
Drawings
Fig. 1A is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to an embodiment of the present invention.
Fig. 1B is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 1C is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 2A is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 2B is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 3A is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 3B is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 4A is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 4B is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 4C is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 4D is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 4E is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 4F is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 4G is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 4H is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 4I is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 4J is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 4K is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 4L is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 4M is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 4N is a schematic structural diagram of a transmitting antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 5A is a schematic structural diagram of a differential feed circuit of a microwave detection device with micro transmitting power according to an embodiment of the present invention.
Fig. 5B is a schematic structural diagram of a differential feeding circuit of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 6 is a schematic structural diagram of a differential oscillation circuit of a microwave detection device with micro-transmitting power according to an embodiment of the present invention.
Fig. 7A is a schematic structural diagram of a microwave detection device with micro-transmitting power according to an embodiment of the present invention.
Fig. 7B is a schematic structural diagram of a microwave detecting device with micro-transmitting power according to another embodiment of the present invention.
Fig. 7C is a schematic structural diagram of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 7D is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention.
Fig. 8A is a schematic structural diagram of a receiving antenna of a microwave detecting device with micro transmitting power according to an embodiment of the present invention.
Fig. 8B is a schematic structural diagram of a receiving antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 8C is a schematic structural diagram of a receiving antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 8D is a schematic structural diagram of a receiving antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 9A is a schematic structural diagram of a receiving antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 9B is a schematic structural diagram of a receiving antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 9C is a schematic structural diagram of a receiving antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 9D is a schematic structural diagram of a receiving antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 9E is a schematic structural diagram of a receiving antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention.
Fig. 10A is a schematic structural diagram illustrating a transmitting antenna and a receiving antenna of a microwave detecting device with micro transmitting power according to an embodiment of the present invention are integrally disposed.
Fig. 10B is a schematic structural diagram of a microwave detecting device with micro transmitting power according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Fig. 10C is a schematic structural diagram illustrating a transmitting antenna and a receiving antenna of a microwave detecting device with micro transmitting power according to another embodiment of the present invention are integrally disposed.
Fig. 10D is a schematic structural diagram of a microwave detecting device with micro transmitting power according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Fig. 10E is a schematic structural diagram of a microwave detecting device with micro transmitting power according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Fig. 10F is a schematic structural diagram of a microwave detecting device with micro transmitting power according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Fig. 10G is a schematic structural diagram of a microwave detecting device with micro transmitting power according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Fig. 10H is a schematic structural diagram of a microwave detecting device with micro transmitting power according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Fig. 10I is a schematic structural diagram of a microwave detecting device with micro transmitting power according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Fig. 10J is a schematic structural diagram of a microwave detecting device with micro transmitting power according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Detailed Description
The following description is presented to disclose the invention so as to enable any person skilled in the art to practice the invention. The preferred embodiments in the following description are given by way of example only, and other obvious variations will occur to those skilled in the art. The basic principles of the invention, as defined in the following description, may be applied to other embodiments, variations, modifications, equivalents and other technical solutions without departing from the spirit and scope of the invention.
It will be understood by those skilled in the art that in the present disclosure, the terms "longitudinal," "lateral," "upper," "lower," "front," "rear," "left," "right," "vertical," "horizontal," "top," "bottom," "inner," "outer," and the like are used in a generic and descriptive sense only and not for purposes of limitation, as the terms are used in the description to indicate that the referenced device or element must have the specified orientation, be constructed and operated in the specified orientation, and not for the purposes of limitation.
It is understood that the terms "a" and "an" should be interpreted as meaning that a number of one element or element is one in one embodiment, while a number of other elements is one in another embodiment, and the terms "a" and "an" should not be interpreted as limiting the number.
The utility model provides a little transmitted power's microwave detecting device, wherein little transmitted power's microwave detecting device has broken through the technical tendency that technical staff in the field tends to improve corresponding echo signal's intensity, and the antenna based on communication usage pursues high signal strength's universality, through reducing little transmitted power's microwave detecting device's transmitting antenna's transmitted power's mode has reduced correspondingly the signal strength of microwave beam and reflection echo has reduced promptly the microwave beam with the electromagnetic radiation energy density of reflection echo, and then can utilize communication device from the end of taking to make an uproar to restrain the mechanism, it is right to avoid causing the interference and can reduce or even remove communication device's in the installing position in corresponding installing environment to corresponding communication device's installed position.
The transmitting power of the transmitting antenna of the microwave detecting device with micro transmitting power is reduced, the signal intensity corresponding to the microwave beam is reduced and the signal intensity is in a weak signal form, and the corresponding communication device in the environment can resist the interference of the microwave detecting device with micro transmitting power based on a self-contained bottom noise suppression mechanism, so that the influence of the frequency bandwidth of the transmitting antenna of the microwave detecting device with micro transmitting power on the interference capability of the corresponding communication device with the microwave detecting device with micro transmitting power is reduced, namely the dependence of the immunity of the transmitting antenna on the narrowed frequency bandwidth is reduced, the precision requirement on the transmitting antenna is correspondingly reduced, and the production cost of the transmitting antenna is favorably reduced.
Meanwhile, because the signal intensity of the microwave beam is reduced, based on the characteristic that the loss generated by the penetration behavior of the microwave beam to a concrete wall or glass of a masonry structure is far larger than the loss generated by propagation in a space, when the signal intensity of the microwave beam is reduced to be in a weak signal form, the microwave beam in the weak signal form is absorbed by the concrete wall or glass of the masonry structure defining a target detection space, namely, the adaptive definition of the gradient boundary of the microwave beam in the weak signal form can be formed, and the state of not limiting the space form of the target detection space is corresponded, so that the effective detection space of the microwave detection device with the masonry structure of the concrete wall or glass as the boundary can be matched with the corresponding target detection space, and the adaptability of the microwave detection device with the micro emission power to different target detection spaces in practical application is improved.
Further, since the signal intensity of the microwave beam is reduced to be in a weak signal form, the ratio of the loss generated based on the reflection behavior of the microwave beam to the radiation energy of the microwave beam is increased, so that the self-excited interference generated based on the multiple reflection behavior can be avoided.
That is to say, the transmitting power of the transmitting antenna of the microwave detecting device with micro transmitting power is reduced, and the signal strength of the corresponding microwave beam is reduced to be in a weak signal form, the strength of the corresponding echo signal is reduced, so that the microwave detecting device with micro transmitting power breaks through the technical trend that a person skilled in the art tends to increase the strength of the corresponding echo signal and tends to have higher electromagnetic radiation energy density in the target detecting space while covering the corresponding target detecting space, wherein the reduction of the transmitting power of the transmitting antenna of the microwave detecting device with micro transmitting power is not intended to adjust the gradient boundary traditionally meaning of the microwave beam, but is in a state that the transmitting antenna of the microwave detecting device with micro transmitting power is excited to transmit the microwave beam, based on the principle that the coverage space range of the microwave beam corresponds to the gain (dBd or dBi) of the transmitting antenna of the microwave detection device with the micro transmitting power without being controlled by the transmitting power of the transmitting antenna, the electromagnetic radiation energy density of the microwave beam in the coverage space of the microwave beam is reduced to be in a weak signal form suitable for being inhibited by a corresponding communication device based on a self-contained bottom noise inhibition mechanism in a manner of reducing the transmitting power of the transmitting antenna, so that interference on the corresponding communication device is avoided, the ratio of loss generated by the penetrating action of the microwave beam to the radiation energy of the microwave beam is improved, and the absorption of the microwave beam in the weak signal form by a masonry-structured concrete wall or glass defining a target detection space can be utilized to form an adaptive boundary for the gradient boundary of the microwave beam in the weak signal form by taking the masonry-structured concrete wall or glass as the boundary And the adaptability of the microwave detection device with the micro transmitting power to different target detection spaces in practical application is correspondingly improved.
Further, based on the theoretical knowledge that the transmission power (dBm) = signal source power (dBm) -transmission line loss (dB) + transmission antenna gain (dBd or dBi) of the transmitting antenna of the microwave detection apparatus for micro transmission power, and the experimental exploration knowledge of the noise floor suppression mechanism of the communication apparatus not in the art, the microwave detection apparatus for micro transmission power may be characterized by feeding the transmitting antenna with a feeding power of less than 1mW, preferably by reducing the transmission power of the transmitting antenna to a target transmission power of 0dBm or less, for example by reducing the transmission power of the transmitting antenna to a target transmission power of-3 dBm or-6 dBm, to form a weak signal shape of the microwave beam corresponding to the electromagnetic radiation energy density of the microwave beam in its coverage space approaching the conventionally significant gradient boundary and the electromagnetic radiation energy density outside the gradient boundary, and thus the reduction of the transmission power of the transmitting antenna of the microwave detection apparatus for micro transmission power may be non-significant for the purpose of adjusting the conventionally significant microwave beam gradient boundary.
It can be understood that, due to the existence of the dielectric loss of the transmitting antenna itself, the conversion efficiency of the transmitting antenna may not reach 100%, and correspondingly, in the process that the transmitting power of the transmitting antenna is reduced, the transmitting antenna may not transmit the corresponding microwave beam when the transmitting power of the transmitting antenna is not reduced to the target transmitting power, that is, the initial polarization process cannot be completed based on the dielectric loss of the transmitting antenna itself. That is to say, the minimum transmission power capable of guaranteeing the stable transmission of the microwave beam is taken as the minimum transmission power extreme value of the transmitting antenna, and based on the dielectric loss of the transmitting antenna, the transmitting antenna has a technical obstacle that the minimum transmission power extreme value may be larger than the target transmission power and cannot be further reduced in a state of guaranteeing the stable transmission of the microwave beam. Based on this, the utility model discloses a little transmitted power's microwave detection device's detection method includes the improvement transmitting antenna's conversion efficiency's method step, in order to avoid transmitting antenna can't accomplish initial polarization and can't transmit correspondingly in its transmitted power reduced state based on the dielectric loss of self the technical obstacle of microwave beam corresponds the guarantee the state of the stable transmission of microwave beam reduces transmitting antenna's minimum transmitted power extreme value, in order to reduce transmitting antenna's transmitted power to the state guarantee micro signal form the stable transmission of microwave beam.
Specifically, in the method step of improving the conversion efficiency of the transmitting antenna, the circularly polarized form of the transmitting antenna is realized by the phase difference feeding to reduce the minimum transmitting power extreme value of the transmitting antenna, or the differential feeding with a phase difference larger than 90 ° is realized in the linear polarization direction of the transmitting antenna in the state that the transmitting antenna adopts the linearly polarized form of the transmitting antenna, so as to reduce the loss of the transmitting antenna generated based on the electric field coupling effect in the initial polarization process to reduce the minimum transmitting power extreme value of the transmitting antenna, thereby ensuring the stable transmission of the microwave beam in the form of a micro signal by the transmitting antenna in the state of reducing the transmitting power of the transmitting antenna to the target transmitting power.
Accordingly, referring to fig. 1A to 1C of the drawings accompanying the present invention, various embodiments of the transmitting antenna 10 for implementing a circular polarization mode based on a phase difference feeding mode are illustrated, wherein the transmitting antenna 10 is exemplified by a planar patch antenna configuration having a reference ground 11 and a radiation source 12, and wherein the radiation source 12 is disposed on a side of the reference ground 11 in a spaced state from the reference ground 11.
Corresponding to fig. 1A and 1B, the radiation source 12 is configured as a unit radiation source, and corresponding to the radiation source 12, the radiation element 12 has a single number of radiation elements 121, wherein corresponding to fig. 1A, the radiation element 121 has two feeding points 1211, wherein the two feeding points 1211 are orthogonally arranged, and connecting lines between the two feeding points 1211 and a physical central point 1212 of the radiation element 121 are perpendicular to each other, so that excitation signals with 90 ° difference are accessed to the two feeding points 1211 of the radiation element 121 by means of phase difference feeding to realize a circular polarization configuration of the transmitting antenna 10; corresponding to fig. 1B, the radiation element 121 has at least three feeding points 1211, wherein each of the feeding points 1211 is equidistantly arranged around the physical center point 1212 of the radiation element 121 in a state of being at the same distance from the physical center point 1212 of the radiation element 121, an angle between a connection line between any two adjacent feeding points 1211 and the physical center point 1212 of the radiation element 121 in a direction around the physical center point 1212 of the radiation element 121 is equal to 360 °/n, where n is the number of the feeding points 1211 of the radiation element 121, such that in a direction around the physical center point 1212 of the radiation element 121, an excitation signal with a difference of 360 °/n is sequentially inputted at the feeding points 1211 of the radiation element 121 to achieve a circular polarization state of the radiation antenna 10, in particular, in the radiation antenna 10 illustrated in fig. 1B, the number of the feeding points 1211 of the radiation element 121 is 4, in a direction around the physical center point 1212 of the radiation element 121, in a state of sequentially inputting an excitation signal with a difference of 360 °/n to achieve a circular polarization state, in a direction around the physical center point 1212 of the radiation element 121, in a state of 90 °, and in a connection line between any two adjacent feeding points 1211 and the physical center point 1212 of the radiation element 121, in a state of the radiation element 121, in a phase, in a state of the direction around the radiation element 90 ° is sequentially connected to achieve a phase-polarized signal in a phase-polarized state of the radiation element 121.
Corresponding to fig. 1C, the radiation source 12 is disposed in a multi-element radiation source configuration, and at least three radiation elements 121 are disposed corresponding to the radiation source 12, wherein each radiation element 121 has a feeding point 1211, and each radiation element 121 is circumferentially arranged such that, in a circumferential arrangement direction of the radiation elements 121, an angle between a connecting line between the feeding point 1211 and a physical central point 1212 of any two adjacent radiation elements 121 is equal to 360 °/m, where m is the number of the radiation elements 121, so that excitation signals with a difference of 360 °/m are sequentially connected to the feeding point 1211 of each radiation element 121 in the circumferential arrangement direction of the radiation elements 121 in a phase-difference feeding manner to achieve a circular polarization configuration of the transmitting antenna 10. Preferably, each of the radiation elements 121 further satisfies that, while an angle between a connecting line between the feeding point 1211 and a physical central point 1212 of any two adjacent radiation elements 121 is equal to 360 °/m in the circumferential arrangement direction of the radiation elements 121, a connecting line between the feeding point 1211 and the physical central point 1212 of each of the radiation elements 121 intersects at a point, and distances between the feeding point 1211 and the point of each of the radiation elements 121 are the same, or satisfies that a connecting line between the feeding point 1211 and the physical central point 1212 of each of the radiation elements 121 intersects to form a regular polygon corresponding to the number of the radiation elements 121, and distances between the feeding points 1211 and midpoints of the regular polygons of the radiation elements 121 are the same, in particular, in the transmitting antenna 10 illustrated in fig. 1C, the number of the radiation elements 121 is four, corresponding to the circumferential arrangement direction of the radiation elements 121, an angle between the feeding point 1211 and the physical central point 1212 of any two adjacent radiation elements 121 is equal to 90 °, and an intersection distance between the feeding point 1211 and the physical central point 1212 of each of the radiation element 121 intersects with the regular quadrilateral. In this way, the circular polarization form of the transmitting antenna 10 is realized in a manner of being based on phase difference feeding, and the stability of the circular polarization form of the transmitting antenna 10 is guaranteed.
It is worth mentioning that, in the embodiments of the present invention, based on the difference of the feeding structure of the radiation element 121, the definition of the position corresponding to the feeding point 1211 is different, specifically, in the state of the feeding structure in which the radiation element 121 adopts probe feeding or microstrip feeding (including microstrip angle feeding), the feeding point 1211 corresponds to the point of the radiation element 121 accessing the feeding signal (including the excitation signal), and in the state of the feeding structure in which the radiation element 121 adopts edge feeding, the feeding point 1211 corresponds to the middle point of the edge of the radiation element 121 accessing the feeding signal (including the excitation signal) based on the coupling effect, and in the description of the present invention, in the state in which the transmitting antenna 10 is set in the planar patch antenna state, the description of the feeding point 1211 does not constitute a limitation to the feeding structure corresponding to the radiation element 121.
Furthermore, in some embodiments of the present invention, when the transmitting antenna 10 is configured in a planar patch antenna configuration, the same two feeding points 1211 connected to the same phase excitation signal on the radiating element 121, the central line of the connection line of the two feeding points 1211 passes through the structural state of the physical central point 1212 of the radiating element 121, which is equivalent to the feeding point 1211 at the central point of the connection line of the two feeding points 1211 in the description of the present invention, which is not limited by the present invention.
Preferably, in these embodiments of the present invention, the radiating element 121 is further configured to be directly and/or equivalently grounded at its physical center point 1212, and the radiating element 121 is configured to be directly grounded at its physical center point 1212, specifically based on the electrical connection between the radiating element 121 and the ground reference 11, and the radiating element 121 is configured to be equivalently grounded at its physical center point 1212, based on the electrical connection between at least one set and/or at least one pair of ground points on the radiating element 121 and the ground reference 11, wherein the same set of ground points are located at each vertex of a same regular polygon with the physical center point 1212 of the radiating element 121 as a midpoint, and the ground points in the same set are arranged at equal angles around the physical center point 1212 of the radiating element 121 with a state equidistant from the physical center point 1212 of the radiating element 121, wherein the same pair of ground points are symmetrically distributed around the physical center point 1212 of the radiating element 121 with the physical center point 1212 of the radiating element 121, and the line segment connecting the radiating element 121 with the physical center point 1212 as the radiating element 1212 as a pair of the radiating element 121, and the ground points 1212 as the radiating element are symmetrically distributed around the physical center point 1212 as the radiating element 121, thereby increasing the radiating element 10 and the radiating element antenna.
Further, referring to fig. 2A and 2B of the drawings of the present disclosure, different embodiments of implementing differential feeding for a phase difference of more than 90 ° to the transmitting antenna 10 in the linear polarization direction of the transmitting antenna 10 based on a phase difference feeding mode in a state that the transmitting antenna 10 adopts a linear polarization state are illustrated, wherein the transmitting antenna 10 is disposed in a planar patch antenna state and has a reference ground 11 and a radiation source 12, and the radiation source 12 is disposed at one side of the reference ground 11 in a state spaced apart from the reference ground 11.
Corresponding to fig. 2A, the radiation source 12 is configured as a unit radiation source, and the radiation source 12 has a single number of radiation elements 121, wherein the radiation element 121 has two feeding points 1211, wherein the two feeding points 1211 are arranged in opposite phase, and a connection direction corresponding to one of the feeding points 1211 to a physical central point 1212 of the radiation element 121 coincides with a connection direction corresponding to the other of the feeding points 1211 to a physical central point 1212 of the radiation element 121, then the radiation element 121 has a polarization form of linear polarization in a state that the feeding points 1211 access an excitation signal and takes the connection direction of the two feeding points 1211 as the linear polarization direction, so that differential feeding to the transmission antenna 10 is realized in a state that the two feeding points 1211 access excitation signals with a phase difference larger than 90 ° in the linear polarization direction of the transmission antenna 10 by means of phase difference feeding, so as to reduce a minimum transmission power extreme value of the transmission antenna 10 based on a loss generated by an electric field coupling effect during initial polarization, thereby reducing the transmission power of the transmission antenna 10 to a transmission state, and ensuring stable microwave transmission beam of the transmission antenna 10.
Preferably, in this embodiment of the present invention, the two feeding points 1211 of the radiating element 121 are arranged symmetrically with respect to the physical center point 1212 of the radiating element 121, so that in a manner of feeding by phase difference, in a state that the two feeding points 1211 of the radiating element 121 access excitation signals with phase difference approaching 180 °, a balanced differential feeding to the transmitting antenna 10 is realized in the linear polarization direction of the transmitting antenna 10, so as to further reduce the loss generated by the transmitting antenna 10 based on the electric field coupling effect during the initial polarization process, so as to reduce the minimum transmitting power extreme value of the transmitting antenna 10, thereby ensuring stable transmission of the microwave beam in the form of micro-signal by the transmitting antenna 10 in a state of reducing the transmitting power of the transmitting antenna 10 to the target transmitting power.
Corresponding to fig. 2B, the radiation source 12 is configured as a binary radiation source, and the radiation source 12 has two radiation elements 121, wherein each of the radiation elements 121 has a feeding point 1211, wherein the two radiation elements 121 are arranged in opposite phase, and a connection direction of the feeding point 1211 of one of the radiation elements 121 to a physical central point 1212 is opposite to a connection direction of the feeding point 1211 of the other radiation element 121 to a physical central point, so that the two radiation elements 121 have a linearly polarized polarization state in a state where the two feeding points 1211 access an excitation signal, and a connection direction of the two feeding points 1211 is a linearly polarized direction, so that by means of phase-difference feeding, a differential feeding to the transmission antenna 10 is realized in a state where the two feeding points 1211 of the two radiation elements 121 access excitation signals with a phase difference of more than 90 ° in the linear polarization direction of the transmission antenna 10, so as to reduce a minimum transmission power extremum of the transmission antenna 10 based on a loss generated by an electric field coupling effect during an initial polarization process, thereby reducing the power of the transmission antenna 10 to a transmission power of a target transmission antenna 10, and ensuring a stable microwave beam of the transmission antenna 10.
Preferably, in this embodiment of the present invention, two of the radiating elements 121 are arranged in a mirror image, so as to implement a balanced differential feeding to the transmitting antenna 10 in the linear polarization direction of the transmitting antenna 10 in a manner of feeding by phase difference in a state that two of the feeding points 1211 of the radiating elements 121 access excitation signals with phase difference approaching 180 °, so as to further reduce the loss generated by the transmitting antenna 10 based on the electric field coupling effect during the initial polarization process, thereby reducing the minimum transmitting power extreme value of the transmitting antenna 10, and thus ensuring stable transmission of the microwave beam in the form of micro-signals by the transmitting antenna 10 in a state of reducing the transmitting power of the transmitting antenna 10 to the target transmitting power.
It is also worth mentioning that, in the two embodiments of the present invention, based on the difference of the feeding structure of the radiating element 121, the definition of the position of the corresponding feeding point 1211 is different, specifically, in the state of the feeding structure in which the radiating element 121 adopts probe feeding or microstrip feeding (including microstrip angle feeding), the feeding point 1211 corresponds to the point on the radiating element 121 where the feeding signal (including the excitation signal) is accessed, and in the state of the feeding structure in which the radiating element 121 adopts edge feeding, the feeding point 1211 corresponds to the middle point of the edge on the radiating element 121 where the feeding signal (including the excitation signal) is accessed based on the coupling effect, and in the description of the present invention, in the state in which the transmitting antenna 10 is set in the planar patch antenna state, the description of the feeding point 1211 does not constitute a limitation on the feeding structure of the corresponding radiating element 121.
Furthermore, in some embodiments of the present invention, when the transmitting antenna 10 is configured in a planar patch antenna configuration, the same two feeding points 1211 connected to the same phase excitation signal on the radiating element 121, the central line of the connection line of the two feeding points 1211 passes through the structural state of the physical central point 1212 of the radiating element 121, which is equivalent to the feeding point 1211 at the central point of the connection line of the two feeding points 1211 in the description of the present invention, which is not limited by the present invention.
Preferably, in these embodiments of the present invention, the radiating element 121 is further configured to be directly and/or equivalently grounded at its physical center point 1212, and the radiating element 121 is configured to be directly grounded at its physical center point 1212, specifically based on the electrical connection between the radiating element 121 and the ground reference 11, and the radiating element 121 is configured to be equivalently grounded at its physical center point 1212, based on the electrical connection between at least one set and/or at least one pair of ground points on the radiating element 121 and the ground reference 11, wherein the same set of ground points are located at each vertex of a same regular polygon with the physical center point 1212 of the radiating element 121 as a midpoint, and the ground points in the same set are arranged at equal angles around the physical center point 1212 of the radiating element 121 with a state equidistant from the physical center point 1212 of the radiating element 121, wherein the same pair of ground points are symmetrically distributed around the physical center point 1212 of the radiating element 121 with the physical center point 1212 of the radiating element 121, and the line segment connecting the radiating element 121 with the physical center point 1212 as the radiating element 1212 as a pair of the radiating element 121, and the ground points 1212 as the radiating element are symmetrically distributed around the physical center point 1212 as the radiating element 121, thereby increasing the radiating element 10 and the radiating element antenna.
Further, the minimum transmitting power extreme value of the transmitting antenna 10 is reduced based on a manner of reducing the self dielectric loss of the transmitting antenna 10, the microwave detecting device of the micro transmitting power adopts a half-wave folded-back directional microwave detecting antenna as the transmitting antenna 10, so as to reduce the self dielectric loss of the transmitting antenna 10 and reduce the minimum transmitting power extreme value of the transmitting antenna 10 based on the structural characteristic that the half-wave folded-back directional microwave detecting antenna takes air as a medium, and further reduce the minimum transmitting power extreme value of the transmitting antenna 10 based on the high-gain characteristic of the half-wave folded-back directional microwave detecting antenna, thereby ensuring stable transmission of the microwave beam in a micro signal form in a state of reducing the transmitting power of the transmitting antenna 10 to a target transmitting power.
Referring to fig. 3A and 3B of the drawings of the present invention, the structures of the half-wave folded directional microwave detecting antenna 10A in the vertical structure and the horizontal structure are illustrated respectively.
Corresponding to fig. 3A, the half-wave folded directional microwave detecting antenna 10A in a vertical structure includes a ground reference 11A, a half-wave oscillator 12A and two power feeding lines 13A, wherein the half-wave oscillator 12A has a wavelength electrical length of 1/2 or more and 3/4 or less and has two coupling sections 121A, wherein each of the coupling sections 121A has a wavelength electrical length of 1/6 or more, one end of each of the coupling sections 121A is a feeding end 1211A of the coupling section 121A, and the other ends of the coupling sections 121A are two ends of the half-wave oscillator 12A, wherein a distance between the feeding ends 1211A is λ/4 or less, a distance between two ends of the half-wave oscillator 12A is λ/128 or more and λ/6 or less, so that two poles of an excitation signal or an excitation signal having a phase difference are respectively accessed at the two feeding ends 1211A of the half-wave oscillator 12A to be fed, and two ends of the half-wave oscillator 12A can be coupled to each other by forming a phase difference, wherein a frequency of the excitation signal is a frequency parameter corresponding to the wavelength; wherein the half-wave vibrator 12A is spaced from the reference ground 11A in a state where a distance between both ends thereof and the reference ground 11A is λ/128 or more and λ/6 or less; the two feeder lines 13A are electrically connected to the corresponding feed ends 1211A, respectively, so that the half-wave oscillator 12A is fed by the feed ends 1211A of the half-wave oscillator 12A in a state where the two feeder lines 13A are electrically coupled to the corresponding feed circuits to access two poles of an excitation signal or access an excitation signal having a phase difference, and the half-wave oscillator 12A is spaced from the reference ground 11A by the electrical connection of the feeder lines 13A and the feed ends 1211A.
Corresponding to fig. 3B, the half-wave folded-back directional microwave detecting antenna 10A of the horizontal structure includes a ground reference 11A, a half-wave oscillator 12A and a feeding line 13A, wherein the half-wave oscillator 12A has a wavelength electrical length of 1/2 or more and 3/4 or less, wherein the half-wave oscillator 12A is folded back to form a state where a distance between both ends thereof is λ/128 or more and λ/6 or less, wherein the half-wave oscillator 12A has a feeding point 121A, the feeding point 121A has a wavelength electrical length of 1/6 or less along the half-wave oscillator 12A between the feeding point 121A and one end of the half-wave oscillator 12A, so that in the state where the half-wave oscillator 12A is fed by being connected to a corresponding excitation signal at the feeding point 121A, both ends of the half-wave oscillator 12A can be coupled to each other by forming a phase difference tending to be opposite, where λ is a wavelength parameter corresponding to a frequency of the excitation signal; wherein the half-wave vibrator 12A is spaced from the reference ground 11A in a state where a distance between both ends thereof and the reference ground 11A is λ/128 or more and a distance between at least one end thereof and the reference ground 11A is λ/6 or less; one end of the feeding line 13A is electrically connected to the feeding point 121A of the half-wave oscillator 12A, wherein the feeding line 13A has a wavelength electrical length of 1/128 or more and 1/4 or less, so that when the feeding line 13A is electrically coupled to a corresponding feeding circuit at the other end thereof to receive the excitation signal, the feeding line 13A feeds the half-wave oscillator 12A at the feeding point 121A of the half-wave oscillator 12A in a state where the feeding point and the half-wave oscillator 12A are electrically connected to each other at a distance from the half-wave oscillator 12A and the ground 11A.
Further, refer to the utility model discloses a it is shown that fig. 4A to fig. 4N of the specification attached drawing is based on reducing transmitting antenna 10's self dielectric loss's mode, the combination is in order to right transmitting antenna 10's difference feed reduces transmitting antenna 10's minimum transmitting power extreme value, the utility model discloses further provide a double-ended feed formula difference antenna 10B, with the microwave detection device of little transmitting power adopts double-ended feed formula difference antenna 10B regards as transmitting antenna 10's state reduces transmitting antenna 10's minimum transmitting power extreme value, with reducing transmitting antenna 10's transmitting power to the state guarantee micro-signal form of target transmitting power the stable transmission of microwave beam.
Corresponding to fig. 4A to 4N, the dual feed type differential antenna includes a reference ground 11B and two strip-shaped elements 12B, wherein two ends of the two strip-shaped elements 12B connected to excitation signals are respectively the feeding ends 121B of the two strip-shaped elements 12B, the two strip-shaped elements 12B extend from the two feeding ends 121B in the same lateral space of the reference ground 11B and respectively have a wavelength electrical length of 3/16 or more and 5/16 or less, wherein the two strip-shaped elements 12B respectively have a coupling section 122B, wherein one end of the coupling section 122B close to the feeding end 121B of the strip-shaped element 12B to which the coupling section belongs is a proximal end of the coupling section 122B, and the two coupling sections 122B extend from the proximal end in opposite directions, so that the dual feed type differential antenna 10B is used as the transmitting antenna 10 in a feeding state where two feeding ends 121B of the two strip-shaped elements 12B are connected to excitation signals with a phase difference of more than 90 ° and are different from each other, based on the fact that the coupling between the two strip-shaped oscillators 12B and the reference ground 11B has a polarization form with a phase difference larger than 90 degrees to realize a trend of linear polarization, and based on the fact that the two coupling sections 122B extend from the near end in opposite directions to form the coupling between the two coupling sections 122B, and based on the mutual coupling between the two coupling sections 122B, a common resonance frequency point is formed, that is, in a state that the double-ended feeding type differential antenna 10B is used as the transmitting antenna 10 and excitation signals with a phase difference larger than 90 degrees are accessed to the two feeding ends 121B of the two strip-shaped oscillators 12B, differential feeding to the transmitting antenna 10 is realized in the polarization direction of the transmitting antenna 10 which tends to linear polarization, and the minimum transmitting power extreme value of the transmitting antenna 10 is reduced in a state of ensuring stable transmission of the microwave beam, and further, the stable emission of the microwave beam in the form of a micro signal is ensured in a state of reducing the emission power of the emission antenna 10 to the target emission power.
Specifically, corresponding to fig. 4A, two of the strip-shaped oscillators 12B extend from two of the feeding terminals 121B in the same lateral spatial sequence of the reference ground 11B in a direction vertically away from the reference ground 11B, and extend toward each other at a position equidistant from the reference ground 11B to form the proximal ends of two of the coupling sections 122B at this position.
Corresponding to fig. 4B, two of the strip-shaped oscillators 12B extend from two of the feeding terminals 121B in the same lateral spatial order of the reference ground 11B in a direction vertically away from the reference ground 11B, extend toward each other at a position equidistant from the reference ground 11B to form the coupling section 122B, and extend in a direction vertically close to the reference ground 11B.
Corresponding to fig. 4C to 4N, the two coupling segments 122B extend from the proximal end in the offset direction and have an offset distance of λ/256 or more and λ/6 or less, i.e. the distance from any point on one coupling segment 122B to the other coupling segment 122B is λ/256 or more and λ/6 or less, where λ is a wavelength parameter corresponding to the frequency of the excitation signal.
Specifically, corresponding to fig. 4C to 4L, the two coupling sections 122B of the two strip-shaped oscillators 12B extend from the proximal ends toward each other in a mutually parallel offset direction.
Corresponding to fig. 4C, the two strip-shaped oscillators 12B extend in the direction away from the reference ground 11B vertically in the same lateral spatial order of the reference ground 11B from the two feeding terminals 121B, and extend in opposite directions parallel to each other at the same distance from the reference ground 11B, so as to form the proximal ends of the two coupling sections 122B at the same position.
Corresponding to fig. 4D, two of the strip-shaped oscillators 12B extend in the same lateral spatial sequence of the reference ground 11B from the two feeding terminals 121B in the direction vertically away from the reference ground 11B, extend in opposite directions at positions equidistant from the reference ground 11B in parallel offset directions to form the coupling sections 122B, and extend in the direction vertically close to the reference ground 11B.
Corresponding to fig. 4E, on the basis of the structure of the dual feed differential antenna illustrated in fig. 4D, one of the coupling sections 122B is electrically connected to the middle of the other coupling section 122B.
Corresponding to fig. 4F, the coupling segment 122B has a variation in cross-sectional area in the cross-sectional direction of the strip-shaped element 12B, based on the structure of the double-feed differential antenna illustrated in fig. 4D.
Corresponding to fig. 4G, two of the strip-shaped oscillators 12B extend in the direction perpendicular to and away from the reference ground 11B from the two feeding terminals 121B in the same lateral spatial order of the reference ground 11B, extend in the opposite directions parallel to each other in the offset direction at the positions equidistant from the reference ground 11B, extend in the direction perpendicular to and away from the reference ground 11B, and extend in the opposite directions parallel to each other in the offset direction at the positions equidistant from the reference ground 11B to form the coupling sections 122B.
Corresponding to fig. 4H, two of the strip-shaped oscillators 12B extend from two of the feeding terminals 121B in the same lateral spatial order of the reference ground 11B in the direction vertically away from the reference ground 11B, extend back to back in the mutually parallel offset directions at positions equidistant from the reference ground 11B, extend in the direction vertically away from the reference ground 11B, extend opposite in the mutually parallel offset directions at positions equidistant from the reference ground 11B to form the coupling sections 122B, and extend in the direction vertically close to the reference ground 11B.
Corresponding to fig. 4I, two of the strip-shaped oscillators 12B extend in the direction vertically away from the reference ground 11B in the same lateral spatial order of the reference ground 11B from the two feeding terminals 121B, extend toward each other in the offset directions parallel to each other at positions equidistant from the reference ground 11B to form the coupling sections 122B, extend in the direction vertically close to the reference ground 11B, and extend toward each other again in the offset directions parallel to each other at positions equidistant from the reference ground 11B.
Corresponding to fig. 4J, the two strip-shaped oscillators 12B extend from the two feeding terminals 121B in the same lateral spatial order of the reference ground 11B in the direction away from the reference ground 11B, extend back to the opposite direction in parallel with the offset direction at the position equidistant from the reference ground 11B, extend in the direction away from the reference ground 11B in the perpendicular direction, extend toward each other in parallel with the offset direction at the position equidistant from the reference ground 11B to form the coupling section 122B, extend in the direction approaching the reference ground 11B in the perpendicular direction, and extend toward each other again in parallel with the offset direction at the position equidistant from the reference ground 11B.
Corresponding to fig. 4K, two of the strip-shaped oscillators 12B extend in the direction perpendicular to and away from the reference ground 11B from two of the feeding terminals 121B in the same lateral spatial order of the reference ground 11B, and extend in opposite directions in mutually parallel offset directions at different distances from the reference ground 11B to form the coupling sections 122B, wherein the lengths of the two coupling sections 122B are not limited to be the same.
Corresponding to fig. 4L, the two strip-shaped oscillators 12B extend from the two feeding terminals 121B in the same lateral space of the reference ground 11B in the direction perpendicular to and away from the reference ground 11B, are bent in order at positions equidistant from the reference ground 11B to extend in opposite directions in parallel to each other in the offset direction, are bent to extend in opposite directions in parallel to each other in the offset direction to form the coupling sections 122B, and are bent again to extend in opposite directions in parallel to each other in the offset direction.
Corresponding to fig. 4M and 4N, the two coupling sections 122B of the two strip-shaped oscillators 12B extend from the near end in opposite directions with a staggered arrangement. Specifically, corresponding to fig. 4M, the two strip-shaped oscillators 12B extend in the direction perpendicular to and away from the reference ground 11B from the two feeding terminals 121B in the same lateral spatial sequence of the reference ground 11B, and extend in opposite directions away from and opposite to the reference ground 11B at positions equidistant from the reference ground 11B to form the coupling sections 122B. Corresponding to fig. 4N, the two strip-shaped oscillators 12B extend in the direction vertically away from the reference ground 11B in the same lateral spatial sequence of the reference ground 11B from the two feeding terminals 121B, extend in opposite directions away from the reference ground 11B at positions equidistant from the reference ground 11B to form the coupling sections 122B, and extend in the direction vertically away from the reference ground 11B at positions equidistant from the reference ground 11B.
It is worth mentioning that the structural configuration of the double-ended feed differential antenna is various, and when the end of the coupling section 122B close to the feeding end 121B of the strip-shaped oscillator 12B to which the coupling section 122B belongs is the proximal end of the coupling section 122B, the extending direction of each coupling section 122B is not limited to the fixed extending direction, that is, in some embodiments of the present invention, the two coupling sections 122B extend from the proximal end in the dynamic opposite direction to form the coupling section 122B in the bent configuration, and also the polarization configuration tending to the linear polarization can be realized when the double-ended feed differential antenna 10B is used as the transmitting antenna 10 in the state where the excitation signals differing by more than 90 ° are accessed into the two feeding ends 121B of the two strip-shaped oscillators 12B, and the coupling section 122B has the phase difference greater than 90 ° with respect to the coupling between the two feeding sections 122B extending from the proximal end in the opposite direction, and the coupling sections 122B are not limited to each other based on the practical coupling configuration of the coupling between the two coupling sections 122B.
Furthermore, in some embodiments of the present invention, the strip-shaped oscillator 12B is disposed in a microstrip line form carried on the circuit board, which is not limited by the present invention.
It should be noted that, in a state of the transmitting antenna 10 adopting a linear polarization form, preferably in a linear polarization or a polarization direction tending to the linear polarization of the transmitting antenna 10, based on feeding the transmitting antenna 10 tending to a phase difference of 180 °, a balanced differential feeding to the transmitting antenna 10 is implemented, so as to reduce a minimum transmitting power extreme value of the transmitting antenna 10 in a state of ensuring stable transmission of the microwave beam, thereby ensuring stable transmission of the microwave beam in a micro-signal form in a state of reducing the transmitting power of the transmitting antenna 10 to a target transmitting power.
Based on this, the present invention further provides a differential feed circuit, which corresponds to some embodiments of the present invention, the microwave detecting device of micro-transmitting power comprises the differential feed circuit, wherein corresponding to fig. 5A and 5B, the differential feed circuit is set in a discrete component form, and the circuit structures of the differential feed circuit 20 of different embodiments are respectively illustrated.
Corresponding to fig. 5A and 5B, in this embodiment of the invention, the differential feed circuit has a three-pole circuit processor (corresponding to Q1 in the figure) configured as a MOS transistor or a triode, an inductor (corresponding to L1 in the figure), a first resistor (corresponding to R1 in the figure), a second resistor (corresponding to R2 in the figure), a third resistor (corresponding to R3 in the figure), a first capacitor (corresponding to C1 in the figure), a second capacitor (corresponding to C2 in the figure), an oscillating capacitor (corresponding to C5 in the figure) and a power connection terminal (corresponding to Vcc in the figure) adapted to access a corresponding power supply, wherein the three-pole circuit processor has a first connection terminal corresponding to the collector of the triode or the drain of the MOS transistor, a second connection terminal corresponding to the base of the triode or the gate of the MOS transistor, and a third connection terminal corresponding to the emitter of the triode or the source of the MOS transistor, wherein one end of the second resistor is electrically connected to the first connection terminal of the three-pole circuit handler, the other end of the second resistor is connected to the power supply connection terminal via the inductor, and is grounded via the first capacitor, wherein one end of the third resistor is electrically connected to the third connection terminal of the three-pole circuit handler, the other end of the third resistor is grounded, wherein one end of the oscillation capacitor is electrically connected to the second connection terminal of the three-pole circuit handler, the other end of the oscillation capacitor is grounded, wherein one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit handler, and the other end of the first resistor is electrically connected between the inductor and the second resistor corresponding to fig. 5A, or is electrically connected to the power connection terminal corresponding to fig. 5B, wherein two ends of the second capacitor are electrically connected to the first connection terminal and the third connection terminal of the three-pole circuit processor, respectively, wherein the second resistor and the third resistor are set with equal resistance, so that in a state that the differential feeding circuit is connected to the corresponding power source at the power connection terminal, the excitation signal is output at two ends of the second capacitor in a balanced differential signal form with a phase difference approaching 180 °, thereby realizing phase difference feeding of the transmitting antenna approaching 180 °.
It should be noted that the inductor functions to isolate ac and dc to isolate a high-frequency ac excitation signal from a power supply voltage signal, and the first capacitor is a decoupling capacitor, which can prevent parasitic oscillation caused by a positive feedback path formed by a circuit through a power supply and prevent current fluctuation caused by the change of the current of the circuit before and after passing through a power supply from affecting the normal operation of the circuit, wherein since one end of the first resistor is electrically connected to the second connection end of the three-pole circuit processor to provide a divided current for the second connection end of the three-pole circuit processor, the inductor does not participate in voltage division, so that the other end of the first resistor may be electrically connected between the inductor and the second resistor corresponding to fig. 5A or electrically connected to the power supply connection end corresponding to fig. 5B.
Further, in the two embodiments of the present invention, the differential feeding circuit further has a third capacitor (corresponding to C3 in the figure) and a fourth capacitor (corresponding to C4 in the figure), wherein the third capacitor and the fourth capacitor are electrically connected to two ends of the second capacitor respectively, so as to output the excitation signal in a balanced differential signal form with a phase difference approaching 180 ° through the third capacitor and the fourth capacitor, thereby realizing phase difference feeding of the transmitting antenna approaching 180 °.
It is worth mentioning that, corresponding to the differential feed circuit illustrated in fig. 5A and 5B, in other embodiments of the present invention, the inductor may not be set, corresponding to one end of the second resistor electrically connected to the first connection end of the three-pole circuit processor, the other end of the second resistor electrically connected to the power connection end, and the first capacitor is grounded, one end of the first resistor electrically connected to the second connection end of the three-pole circuit processor, and the other end of the first resistor electrically connected to the power connection end.
Furthermore, it is worth mentioning that, in the embodiments of the present invention, the first capacitor, the second capacitor, the third capacitor, the fourth capacitor and the oscillating capacitor can be set in a micro-strip distributed capacitor form in an actual circuit structure, which is not limited by the present invention.
Referring further to fig. 6 of the drawings accompanying the present application, a partial circuit structure of a differential feed circuit according to an embodiment of the present invention is illustrated, in which the differential feed circuit is configured in an integrated circuit form and outputs the excitation signal in a differential oscillation circuit in a balanced differential signal form with a phase difference of approximately 180 °.
Specifically, the differential oscillation circuit has two N-channel MOS transistors (corresponding to Q1 and Q2 in the figure), two P-channel MOS transistors (corresponding to Q3 and Q4 in the figure), an oscillation inductor (corresponding to L in the figure) and an oscillation capacitor (corresponding to C in the figure), wherein the sources of the two N-channel MOS transistors are electrically connected, the sources of the two P-channel MOS transistors are electrically connected, and the drains of the two N-channel MOS transistors are electrically connected to the drains of different P-channel MOS transistors, respectively, so as to form a drain of one of the N-channel MOS transistors electrically connected to a drain of one of the P-channel MOS transistors, a source of the P-channel MOS transistor is electrically connected to a source of the other P-channel MOS transistor, and a drain of the other P-channel MOS transistor is electrically connected to a drain of the other N-channel MOS transistor, and the source of the other N-channel MOS transistor is electrically connected with the source of the previous N-channel MOS transistor in a sequential connection relationship, wherein in the two N-channel MOS transistors, the gate of any one N-channel MOS transistor is electrically connected with the drain of the other N-channel MOS transistor, wherein in the two P-channel MOS transistors, the gate of any one P-channel MOS transistor is electrically connected with the drain of the other P-channel MOS transistor, wherein the two ends of the oscillation inductor are respectively and electrically connected with the drains of the different P-channel MOS transistors, and the two ends of the oscillation capacitor are respectively and electrically connected with the drains of the different P-channel MOS transistors and are connected with the oscillation inductor in parallel, so that the oscillation and frequency selection are formed based on a parallel resonance loop consisting of the oscillation inductor and the oscillation capacitor, and electric signals with equal size and opposite directions are formed at the two ends of the oscillation inductor and the oscillation capacitor, and the other N-channel MOS tube and the P-channel MOS tube electrically connected with the grid electrode of the N-channel MOS tube can be simultaneously conducted at the other moment, so that the excitation signals are output at two ends of the oscillation inductor in a balanced differential signal form with a difference of 180 degrees.
With further reference to fig. 7A to 7D of the drawings accompanying the present disclosure, the differential feed circuit is configured in an integrated circuit form and outputs the state of the excitation signal in a balanced differential signal form with a phase difference approaching 180 °, and the structural block diagram of the microwave detecting device of micro-transmitting power according to different embodiments of the present disclosure is illustrated.
Wherein the differential feeding circuit comprises a low dropout linear regulator (corresponding to the internal LDO in the figure), the differential oscillating circuit, an oscillator (corresponding to the Osc in the figure), a phase-locked loop (corresponding to the PLL in the figure) and a logic control unit, wherein the low dropout linear regulator provides a constant voltage for the differential oscillating circuit in a powered state, wherein the oscillator is configured such that the logic control unit provides a basic clock signal and is externally configured with a quartz crystal oscillator or is integrally configured with an internal oscillating circuit in the logic control unit, wherein the logic control unit is configured with a DSP, a MCU or a RAM and is electrically connected to the oscillating inductor of the differential oscillating circuit, wherein the phase-locked loop is electrically connected between the logic control unit and the differential oscillating circuit in a state of being externally configured or integrated with the logic control unit, so as to calibrate the differential oscillating circuit to output the frequency/phase of the excitation signal in a balanced differential signal form with a phase difference of 180 ° at both ends of the oscillating inductor based on the feedback of the excitation signal output by the logic control unit to ensure the stable excitation signal output by the differential feeding circuit.
It is worth mentioning that, for the purpose of reducing the cost of the differential feeding circuit, in some embodiments of the present invention, the phase-locked loop may not be configured, that is, the logic control unit is electrically connected to the differential oscillating circuit, so as to control the stability of the frequency/phase of the excitation signal outputted from the differential oscillating circuit at two ends of the oscillating inductor in a balanced differential signal form with a 180 ° difference based on the feedback of the excitation signal outputted from the differential oscillating circuit.
Further, in the embodiments of the present invention, the differential feeding circuit further includes two amplifiers (corresponding to PA1 and PA2 directly led out from the differential oscillating circuit in the figure) for amplifying the excitation signal outputted from the differential oscillating circuit in a balanced differential signal form, wherein the logic control unit is electrically connected to the oscillating inductor of the differential oscillating circuit in a state of being electrically connected to at least one of the amplifiers, so as to receive the feedback of the amplifier to the excitation signal outputted from the differential oscillating circuit.
It is worth mentioning that in a state where the microwave beam is in a weak signal form due to the reduction of the transmitting power of the transmitting antenna, although the above-mentioned series of advantages are exhibited, since the strength of the corresponding echo signal is simultaneously reduced, in a state where there is ambient electromagnetic interference in the corresponding target detection space, the corresponding doppler intermediate frequency signal is more likely to be interfered by ambient electromagnetic radiation, and it is difficult to accurately feed back the motion characteristics corresponding to the human body movement motion, the inching motion, and the breathing and heartbeat motion. On the basis, correspond to the utility model discloses a what figure 7A to figure 7C of the description attached drawing illustrate little transmitted power's microwave detection device, it is corresponding little transmitted power's microwave detection device's detection method further includes the method step of improving echo signal's precision, with echo signal's intensity is based on the state that the transmitted power of emitting antenna (TX in the corresponding map) was reduced, based on the improvement of echo signal's precision, ensures little transmitted power's microwave detection device is to the accuracy and the stability with the detection of human body movement action, fine motion action, and the activity characteristic that respiratory and heartbeat action correspond.
In particular, the method step of improving the accuracy of the echo signal includes the step of accessing the echo signal in a balanced differential signal form from a receiving antenna (corresponding to RX in the figure) of the microwave detection device for micro-transmitting power, so that electromagnetic interference in the environment exists in a common-mode interference form in the echo signal, and thus can be suppressed during reception and transmission of the echo signal in a balanced differential signal form, corresponding to fig. 7D, outputting the doppler intermediate frequency signal in a balanced differential signal form based on a mixing processing step of the echo signal in a balanced differential signal form, and forming a digitized form of the doppler intermediate frequency signal in a balanced differential signal form based on digitized conversion of the doppler intermediate frequency signal in a balanced differential signal form by an a/D conversion unit, wherein a data processing unit connected to the a/D conversion unit is configured to process the common-mode interference information in the digitized form of the doppler intermediate frequency signal in a balanced differential signal form with a corresponding algorithm suppression (including cancellation) based on the digitized feature of the common-mode interference, so as to further suppress the common-mode interference information in the balanced differential signal form based on the digital intermediate frequency signal form of the digital interference of the data processing unit, and further improve the accuracy of the doppler signal, thereby forming a corresponding doppler signal processing action based on the digital signal processing algorithm, the digital signal, and the improving the accuracy of the doppler signal processing action of the doppler signal processing, the doppler signal processing, the corresponding to improve the accuracy of the doppler signal, the doppler signal processing, the electromagnetic interference suppression of the doppler signal processing, and the doppler signal processing, the electromagnetic interference suppression of the processing unit; or subsequently, corresponding to fig. 7B and 7C, outputting the doppler intermediate frequency signal in a balanced differential signal form based on a step of mixing the echo signals in a balanced differential signal form and outputting the doppler intermediate frequency signal in a single-ended signal form based on a step of differential-to-single-ended processing of the doppler intermediate frequency signal in a balanced differential signal form, to further suppress common-mode interference in the echo signals and/or the doppler intermediate frequency signals in a balanced differential signal form based on a step of mixing the echo signals in a balanced differential signal form and/or a step of differential-to-single-ended processing of the doppler intermediate frequency signals in a balanced differential signal form, for example, to output the doppler intermediate frequency signal in a single-ended signal form free from environmental electromagnetic interference by utilizing the characteristic that common-mode interference is moderately asymmetric in signals in a differential signal form having symmetric characteristics, through the cancellation effect in the processes of symmetry conversion and superposition of the single-ended interference in a differential-to-single-ended processing step based on the principle of differencing, thereby improving the accuracy of the doppler intermediate frequency signals in the micromovement of the micromotion activity corresponding to the human movement, cardiac movement, and breathing activity; or in the subsequent stage, corresponding to fig. 7A, based on the further suppressing effect of the step of processing the echo signals in the form of balanced differential signals from differential to single-ended processing on the echo signals in the form of balanced differential signals on common-mode interference in the echo signals in the form of balanced differential signals, the echo signals in the form of single-ended signals free from environmental electromagnetic interference are output, and based on the step of processing the echo signals in the form of single-ended signals free from environmental electromagnetic interference, the doppler intermediate frequency signals are output on the doppler intermediate frequency signals free from environmental electromagnetic interference, so that the feedback accuracy of the doppler intermediate frequency signals on the activity characteristics corresponding to the human body movement action, the micromotion action, and the respiration and heartbeat action is improved, and the processing system of the balanced differential signals, which is constructed in the step of accessing the echo signals in the form of balanced differential signals by the receiving antenna of the microwave detection device based on the micro transmission power and the subsequent steps, guarantees the accuracy and stability of the detection of the microwave detection device on the activity characteristics corresponding to the human body movement action, the micromotion action, and the respiration and heartbeat action.
It is worth mentioning that, since the echo signal is in a balanced differential signal form when accessed from the receiving antenna, and the electromagnetic radiation interference in the environment exists in a common mode interference form in the echo signal, it can be suppressed during the receiving and transmitting processes of the echo signal in the balanced differential signal form, that is, the echo signal simultaneously includes a signal corresponding to a reflected echo formed by a microwave beam emitted by the transmitting antenna being reflected by a corresponding object and an electromagnetic radiation interference signal in the common mode interference form, so that no matter in fig. 7D, the doppler intermediate frequency signal in the balanced differential signal form is output in a subsequent mixing processing step based on the echo signal in the balanced differential signal form, and the digitized form of the doppler intermediate frequency signal in the balanced differential signal form is formed based on the digitized conversion of the doppler intermediate frequency signal in the balanced differential signal form by the a/D conversion unit, and the common mode interference information in the digitized form of the doppler intermediate frequency signal in the balanced differential signal form is suppressed by the data processing unit according to a corresponding algorithm based on the digitized feature of the common mode interference; or to fig. 7B and 7C to output the doppler intermediate frequency signal in a balanced differential signal form in a subsequent mixing processing step based on the echo signal in a balanced differential signal form and to output the doppler intermediate frequency signal in a single-ended signal form in a subsequent differential-to-single-ended processing step based on the doppler intermediate frequency signal in a balanced differential signal form; or the echo signal in single-ended signal form outputted in the following differential-to-single-ended processing step based on the echo signal in balanced differential signal form corresponding to fig. 7A, and the doppler intermediate frequency signal outputted in the following mixing processing step based on the echo signal in single-ended signal form, the suppression effect of the differential-to-single-ended processing step based on the difference principle on the common-mode interference, wherein the suppression processing of the common-mode interference information in the digitized form of the doppler intermediate frequency signal in balanced differential signal form by the corresponding algorithm based on the digitization characteristics of the common-mode interference corresponding to fig. 7D, or the further suppression effect of the common-mode interference in the echo signal in balanced differential signal form and/or the doppler intermediate frequency signal in balanced differential signal form based on the mixing processing step of the echo signal in balanced differential signal form and/or the differential-to-single-end processing step of the doppler intermediate frequency signal in balanced differential signal form corresponding to fig. 7B and 7C, or corresponding to fig. 7A, based on the further suppressing effect of the step of processing the echo signals in the form of balanced differential signals from differential to single end on the common mode interference in the echo signals in the form of balanced differential signals, the doppler intermediate frequency signals in the form of digitized signals or analog signals which are finally output are free from the environmental electromagnetic interference, so that the feedback accuracy of the doppler intermediate frequency signals on the activity characteristics corresponding to the movement, micromotion, respiration and heartbeat of the human body can be improved, and the processing system of balanced differential signals is constructed corresponding to the step of accessing the echo signals in the form of balanced differential signals from the receiving antenna of the microwave detection device with micro-transmitting power and the subsequent steps, the microwave detection device for guaranteeing the micro-transmitting power can detect the activity characteristics corresponding to the movement action, the micro-movement action, the respiration action and the heartbeat action of the human body, and can ensure the accuracy and the stability of the detection.
Correspondingly, the microwave detecting apparatus for micro transmitting power further includes a mixer circuit and a differential-to-single-ended circuit corresponding to fig. 7A to 7C, wherein the mixer circuit is electrically connected between the differential oscillator circuit and the receiving antenna to output the doppler intermediate frequency signal in a single-ended signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal corresponding to fig. 7A based on the mixing processing of the echo signals in the excitation signal and single-ended signal form, or output the doppler intermediate frequency signal in a differential signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal corresponding to fig. 7B and 7C based on the mixing processing of the echo signals in the excitation signal and balanced differential signal form; accordingly, the differential-to-single-ended circuit is disposed between the receiving antenna and the mixer circuit corresponding to fig. 7A to perform differential-to-single-ended processing on the echo signals in a balanced differential signal form based on a difference finding principle and output the echo signals in a single-ended signal form free from electromagnetic environment interference to the mixer circuit, or disposed in electrical connection with the mixer circuit to receive the doppler intermediate frequency signals in a differential signal form output from the mixer circuit and perform differential-to-single-ended processing on the doppler intermediate frequency signals in a differential signal form based on a difference finding principle and output the doppler intermediate frequency signals in a single-ended signal form free from electromagnetic environment interference, so as to improve the feedback accuracy of the doppler intermediate frequency signals to activity characteristics corresponding to human body movement, micromotion, and respiration and heartbeat actions.
Corresponding to fig. 7D, the microwave detection device further comprises a mixer circuit and an a/D conversion unit and a data processing unit, wherein the mixer circuit is electrically connected between the differential oscillation circuit and the receiving antenna to output the doppler intermediate frequency signal in a differential signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal based on a mixing process of the echo signal in the form of the excitation signal and the balanced differential signal, wherein the a/D conversion unit is electrically connected to the mixer circuit in a structural state integrated with or external to the data processing unit to digitally convert the doppler intermediate frequency signal in the form of the balanced differential signal to form a digitized form of the doppler intermediate frequency signal in the form of the balanced differential signal, wherein the data processing unit is provided in a structural state integrated with or independent from the logic control unit and is configured to suppress (including eliminate) common mode interference information in a digitized form of the intermediate frequency signal in the form of the balanced differential signal based on a corresponding algorithm to suppress (including eliminate) the common mode interference information in a digitized form of the intermediate frequency signal in the time domain signal in the form of the balanced differential signal form, and to convert the two sets of the doppler intermediate frequency signals into two sets of equal magnitude of the same absolute phase difference, and to obtain two sets of equal magnitude of the equivalent absolute difference signal pairs based on a conversion of the equivalent magnitude of the doppler intermediate frequency signal in the two sets of the equivalent magnitude of the doppler intermediate frequency signal in the equivalent magnitude of the two sets of the averaged data processing The digital characteristics of two groups of numerical values with the same trend are differentiated through an algorithm for solving the difference between the two groups of numerical data or an algorithm for filtering the numerical data which do not conform to the opposite trend of change through the comparison of the two groups of numerical data, common-mode interference information in the digital form of the Doppler intermediate frequency signal which balances the form of the differential signal is inhibited or even eliminated, and the digital form of the Doppler intermediate frequency signal which is free from electromagnetic environment interference is correspondingly obtained, so that the feedback accuracy of the Doppler intermediate frequency signal on the activity characteristics corresponding to the movement action, the inching action and the respiration and heartbeat actions of a human body is improved. Or the difference component generated based on the common-mode interference is eliminated through the difference or comparison of the two sets of numerical data after the corresponding operation processing, for example, the two sets of numerical data are independently processed based on the corresponding operation to obtain two sets of control data, and the difference component generated based on the common-mode interference is eliminated through the subsequent comparison and analysis based on the two sets of control data, so that an accurate control result is output.
Further, corresponding to fig. 7A, in a state where the mixing circuit is configured to output the doppler intermediate frequency signal in a single-ended signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal based on the mixing process of the excitation signal and the echo signal in a single-ended signal form, the microwave detecting apparatus for micro-transmit power optionally includes another differential-to-single-ended circuit, where the differential-to-single-ended circuit is configured between the differential oscillating circuit and the mixing circuit to output the excitation signal in a single-ended signal form free from electromagnetic environment interference to the mixing circuit based on the differential-to-single-ended process of the excitation signal in a differential signal form, so as to facilitate improvement of accuracy of the doppler intermediate frequency signal in a single-ended signal form output from the mixing circuit, and to correspondingly guarantee feedback accuracy of activity characteristics of the doppler signal pair corresponding to a human body movement action, a micro-motion, and a respiration and a heartbeat action. That is, in a state where the differential-to-single-ended circuit is not set, the excitation signal in a single-ended signal form may be outputted to the mixer circuit by selecting a mode in which the excitation signal in a single-ended signal form is directly extracted from the differential oscillator circuit, which is not limited by the present invention.
It is worth mentioning that, based on the difference in the usage/transmission path of the signals derived from the differential oscillating circuit, in some documents in the art, the nomenclature of the signals derived from the respective oscillating circuit may be different, for example, in some documents in the art, the transmission object of the signals derived from the respective oscillating circuit is an antenna for feeding the respective antenna and is called an excitation signal, and the transmission object of the signals derived is a mixer and is called a local oscillation signal, the present invention is not limited thereto, i.e. in the description of the present invention, the same nomenclature is used for the excitation signal derived from the differential oscillating circuit and transmitted to the transmitting antenna and the excitation signal also derived from the differential oscillating circuit and transmitted to the mixer circuit, in order to facilitate understanding that the excitation signal is provided by the differential oscillating circuit, and the nomenclature of the excitation signal does not in itself constitute a limitation of the usage/transmission path thereof.
Corresponding to fig. 7B and 7D, in a state where the mixing circuit is set to output the doppler intermediate frequency signal of a balanced differential signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal of a balanced differential signal form based on the mixing process of the excitation signal and the echo signal of a balanced differential signal form, the mixing circuit illustrated in fig. 7C optionally corresponds to an integrated form of the mixing circuit of fig. 7B set to two mixing circuits suitable for the mixing process of the excitation signal and the echo signal of a single-ended signal form to output the doppler intermediate frequency signal of a differential signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal based on the mixing process of the excitation signal and the echo signal of a differential signal form by the mixing circuit.
It is understood that, in some embodiments of the present invention, the mixing circuit may be optionally implemented as an integrated form of the mixing circuit and the differential-to-single-ended circuit in structures or functions corresponding to fig. 7A to 7C, and the mixing circuit may be configured to output the doppler intermediate frequency signal in a single-ended signal form in a state of accessing the echo signal in a balanced differential signal form and the excitation signal, including but not limited to outputting the doppler intermediate frequency signal in a single-ended signal form corresponding to fig. 7A based on a differential-to-single-ended processing of the echo signal in a balanced differential signal form and a mixing processing of the echo signal in a single-ended signal form and the excitation signal, or outputting the doppler intermediate frequency signal in a single-ended signal form corresponding to fig. 7B and 7C based on a mixing processing of the echo signal in a balanced differential signal form and a mixing processing of the single-ended doppler intermediate frequency signal in a balanced differential signal form, and the present invention is not limited thereto.
Specifically, the signal based on balanced differential signal form has two ways and has the characteristic of symmetry characteristic for the signal of reference potential constant amplitude antiphase, in some embodiments of the utility model, the difference changes single-ended circuit is set up and is handled based on the opposition of one of these two way signals of the signal to differential signal form's signal of two way, outputs the signal of single-ended signal form after with another way signal stack, therefore can utilize the constant amplitude asymmetric characteristic in the signal of the differential signal form that has symmetry characteristic of common mode interference, changes single-ended processing based on the difference of the signal of balanced differential signal form of the single-ended circuit pair balance differential signal form, suppresses or even eliminates the common mode interference information in the signal of balanced differential signal form.
Correspondingly in the embodiments of the present invention, when the mixing circuit is implemented to correspond to all the integration forms of the mixing circuit and the differential-to-single-ended circuit in the functions to realize that the mixing circuit outputs the doppler intermediate frequency signal in the single-ended signal form in the state of accessing the echo signal in the balanced differential signal form and the excitation signal, the mixing circuit may also be implemented to output the doppler intermediate frequency signal in the single-ended signal form based on the inverse processing of one of the two signals of the echo signal in the balanced differential signal form, the mixing processing of the two signals, and the superposition processing of the two doppler intermediate frequency signals output by the mixing processing in sequence, so as to suppress or even eliminate the interference information generated by the corresponding common mode interference.
Correspondingly, in other embodiments of the present invention, when the mixing circuit is implemented to correspond to the partially integrated form of the function of the mixing circuit and the differential-to-single-ended circuit in fig. 7A to 7C to realize that the mixing circuit outputs the doppler intermediate frequency signal in the form of a single-ended signal in the state of the echo signal and the excitation signal that are connected to the balanced differential signal form, the mixing circuit may be implemented to sequentially perform inverse processing of one of the two signals of the echo signal in the form of a balanced differential signal, and output the doppler intermediate frequency signal in the form of two single-ended signals to the mixing processing of the two signals, so as to sequentially suppress or even eliminate interference information generated by corresponding common-mode interference based on the superposition processing of the two signals of the doppler intermediate frequency signals, or generate two sets of numerical data having the same absolute value and the same numerical value change trend with respect to a reference potential value in the time domain based on the digital conversion of the two signals, so as to add two sets of numerical data having the same absolute value and opposite numerical value change trend in the time domain based on the digital conversion of the two sets of doppler intermediate frequency signals, obtain two sets of numerical data corresponding doppler intermediate frequency interference information by filtering, and obtain two sets of corresponding doppler intermediate frequency interference information, which are not matched with the same doppler respiration information, and do not matched with the same doppler respiration information, so as the filtering, so as the doppler medium frequency. Or the difference component generated based on the common-mode interference is eliminated through the difference or comparison of the two sets of numerical data after the corresponding operation processing, for example, the two sets of numerical data are independently processed based on the corresponding operation to obtain two sets of control data, and the difference component generated based on the common-mode interference is eliminated through the subsequent comparison and analysis based on the two sets of control data, so that an accurate control result is output.
It should be noted that, in some embodiments of the present invention, the present invention further includes an amplifying step of the echo signal and/or the doppler intermediate frequency signal in balanced differential signal form, for example, on the basis of the circuit structure illustrated in fig. 7A, a corresponding amplifying circuit adapted to amplify the signal in differential signal form is further disposed between the receiving antenna and the corresponding differential-to-single-ended circuit, so as to amplify and output the echo signal in balanced differential signal form to the differential-to-single-ended circuit, or on the basis of the circuit structures illustrated in fig. 7B and 7C, a corresponding amplifying circuit adapted to amplify the signal in differential signal form is further disposed between the receiving antenna and the frequency mixing circuit and/or between the frequency mixing circuit and the differential-to-single-ended circuit, to amplify and output the echo signal in the form of balanced differential signal to the mixer circuit and/or amplify and output the doppler intermediate frequency signal in the form of differential signal to the differential-to-single-ended circuit, or on the basis of the circuit structure illustrated in fig. 7D, a corresponding amplifier circuit suitable for amplifying the signal in the form of differential signal is further disposed between the receiving antenna and the mixer circuit and/or between the mixer circuit and the a/D conversion unit, so as to amplify and output the echo signal in the form of balanced differential signal to the mixer circuit and/or amplify and output the doppler intermediate frequency signal in the form of differential signal to the a/D conversion unit, which is not limited by the present invention, wherein preferably, the differential-to-single-ended circuit is configured to employ a circuit having electrical characteristics of amplifying the signal in the form of differential signal, such as a circuit of an instrument amplifier, the signal amplification processing and the single-end conversion processing of the differential signal form are simultaneously realized, so that the method is simple and easy to implement.
In particular, in some embodiments of the present invention, the present invention further includes an amplifying step of amplifying the echo signal and/or the doppler intermediate frequency signal in the single-ended signal form, for example, on the basis of the circuit structure illustrated in fig. 7A, a corresponding amplifying circuit adapted to amplify the signal in the single-ended signal form is further disposed between the differential-to-single-ended circuit and the frequency mixing circuit and/or at the output end of the frequency mixing circuit, so as to amplify the echo signal in the single-ended signal form to the frequency mixing circuit and/or amplify the doppler intermediate frequency signal in the single-ended signal form, or on the basis of the circuit structures illustrated in fig. 7B and 7C, a corresponding amplifying circuit adapted to amplify the signal in the single-ended signal form is further disposed at the output end of the differential-to-single-ended circuit, so as to amplify the doppler intermediate frequency signal in the single-ended signal form, which the present invention is not limited thereto.
Further, in some embodiments of the present invention, the step of accessing the echo signal from the receiving antenna of the microwave detecting device of the micro transmitting power to the balanced differential signal form includes accessing the echo signal of the balanced differential signal form based on the phase shifting step of the echo signal accessed from one of the receiving feeding points (ends) in a state where the two receiving feeding points (ends) of the receiving antenna are orthogonally arranged, so as to ensure the isolation between the echo signals accessed from the two receiving feeding points (ends) of the receiving antenna based on the orthogonal form between the two receiving feeding points (ends) of the receiving antenna, and correspondingly ensure the accuracy of the echo signal accessed based on the phase shifting step of the echo signal accessed from one of the receiving feeding points (ends).
Corresponding refer to the utility model discloses a figure 8A to figure 8D of the specification attached drawing show two receipt feed points (end) of receiving antenna are based on the phase shift step of the echo signal of receiving one of them feed point (end) access and insert balanced difference signal form echo signal, different embodiments the structural style of receiving antenna is illustrated, wherein based on the receiving and dispatching reciprocity characteristic of antenna, to the nomenclature of the reference numeral and the corresponding structure of receiving antenna follows in the description and the figure of the utility model the nomenclature of the reference numeral and the corresponding structure of transmitting antenna.
In both embodiments of the present invention, the receiving antenna 10 is exemplified by a planar patch antenna configuration having a reference ground 11 and a radiation source 12, corresponding to fig. 8A and 8B, wherein the radiation source 12 is disposed on a side of the reference ground 11 in a spaced state from the reference ground 11.
Specifically, corresponding to fig. 8A, the radiation source 12 is configured as a unit radiation source, and the radiation source 12 has a single number of radiation elements 121, wherein the radiation element 121 has two feeding points 1211, wherein the two feeding points 1211 are orthogonally arranged, connecting lines between the two feeding points 1211 and a physical central point 1212 of the radiation element 121 are perpendicular to each other, one of the feeding points 1211 is electrically connected with a phase shifter, such as a microstrip line configured with a corresponding electrical length, so as to output the echo signal in a balanced differential signal form between one end of the phase shifter far from the feeding point 1211 and the other feeding point 1211 based on a phase shifting process of the phase shifter on the echo signal accessed from the feeding point 1211.
Corresponding to fig. 8B, the radiation source 12 is configured as a binary radiation source, and the radiation source 12 has two radiation elements 121, wherein each of the radiation elements 121 has a feeding point 1211, wherein the two radiation elements 121 are orthogonally arranged, a connection direction of the feeding point 1211 to the physical central point 1212 of one of the radiation elements 121 is perpendicular to a connection direction of the feeding point 1211 to the physical central point 1212 of the other radiation element 121, and one of the feeding points 1211 is electrically connected with a phase shifter, such as a microstrip line configured with a corresponding electrical length, so as to output the echo signal in a balanced differential signal form between an end of the phase shifter far from the feeding point 1211 and the other feeding point 1211 based on a phase shifting process of the phase shifter on the echo signal accessed from the feeding point 1211.
Corresponding to fig. 8C and 8D, in both embodiments of the present invention, the receiving antenna is exemplified by the half-wave folded directional microwave detecting antenna 10A of the orthogonal polarization.
Specifically, corresponding to fig. 8C, the half-wave folded-back directional microwave detecting antenna 10A of the horizontal structure with orthogonal polarization of the receiving antenna is disposed, and the half-wave folded-back directional microwave detecting antenna 10A includes two half-wave oscillators 12A, wherein the two half-wave oscillators 12A are orthogonally arranged, and corresponding to the direction perpendicular to the reference ground 11A as the height direction of the half-wave folded-back directional microwave detecting antenna 10A, the two half-wave oscillators 12A are perpendicular to each other in the extending direction perpendicular to the height direction of the half-wave folded-back directional microwave detecting antenna 10A, wherein the feeding point 121A of one half-wave oscillator 12A is connected with a phase shifter via the feeding line 13A, such as a microstrip line disposed with a corresponding electrical length, so as to output the echo signal in a balanced differential signal form between one end of the phase shifter far from the feeding point 121A and the other feeding point 121A based on the phase shift processing of the echo signal accessed from the feeding point 121A.
Corresponding to fig. 8D, the half-wave folded back directional microwave probe antenna 10A of the receiving antenna in a cross-polarized vertical structure is disposed, the half-wave folded back directional microwave probe antenna 10A includes two half-wave elements 12A, wherein the two half-wave elements 12A are orthogonally arranged, corresponding to a direction perpendicular to the reference ground 11A as a height direction of the half-wave folded back directional microwave probe antenna 10A, the two half-wave elements 12A are perpendicular to each other in an extending direction perpendicular to the height direction of the half-wave folded back directional microwave probe antenna 10A, wherein one of the feeding ends 1211A of one of the half-wave elements 12A is connected with a phase shifter via the feeding line 13A, such as a microstrip line disposed in a corresponding electrical length, to output the echo signal in a balanced signal form between an end of the phase shifter remote from the feeding end 1211A and one of the other half-wave elements 12A based on a phase shift processing of the echo signal accessed from the feeding end 1211A.
It is worth mentioning that in some preferred embodiments of the present invention, in the step of accessing the echo signal in the form of balanced differential signal from the receiving antenna of the microwave detecting device of micro transmitting power, two receiving feeding points of the receiving antenna are arranged in opposite phase to directly access the echo signal in the form of balanced differential signal from the two receiving feeding points.
Referring to fig. 9A to 9E of the drawings of the present invention, in a state where two receiving feeding points (ends) of the receiving antenna are arranged in opposite phases, the echo signals in a balanced differential signal form are directly accessed from the two receiving feeding points (ends), and the structural form of the receiving antenna in different embodiments is illustrated.
In both embodiments of the present invention, the receiving antenna 10 is exemplified by a planar patch antenna configuration having a reference ground 11 and a radiation source 12, corresponding to fig. 9A and 9B, wherein the radiation source 12 is disposed on a side of the reference ground 11 in a spaced state from the reference ground 11.
Specifically, corresponding to fig. 9A, the radiation source 12 is configured in a unit radiation source form, and the radiation source 12 has a single number of radiation elements 121, wherein the radiation element 121 has two feeding points 1211, wherein the two feeding points 1211 are arranged in opposite phases, and a connection direction from one of the feeding points 1211 to a physical center point 1212 of the radiation element 121 coincides with a connection direction from the other feeding point 1211 to the physical center point 1212 of the radiation element 121, so as to output the echo signals in a balanced differential signal form at the two feeding points 1211 based on a structural state that the two feeding points 1211 are arranged in opposite phases.
Preferably, in this embodiment of the present invention, the two feeding points 1211 of the radiating element 121 are symmetrically arranged with respect to the physical center point 1212 of the radiating element 121, such that the two feeding points 1211 are arranged in opposite phases, and the two feeding points 1211 are equidistant from the physical center point 1212 of the radiating element 121, and the echo signals with a phase difference of 180 ° and a balanced differential signal form are output at the two feeding points 1211.
Corresponding to fig. 9B, the radiation source 12 is configured in a binary radiation source form, and the radiation source 12 has two radiation elements 121, wherein each of the radiation elements 121 has a feeding point 1211, wherein the two radiation elements 121 are arranged in opposite phases, and a connection line direction from the feeding point 1211 to a physical central point 1212 of one of the radiation elements 121 is opposite to a connection line direction from the feeding point 1211 to a physical central point of the other radiation element 121, so that the two feeding points 1211 output the echo signals in a balanced differential signal form based on a structural state that the two radiation elements 121 are arranged in opposite phases.
Preferably, in this embodiment of the present invention, two of the radiation elements 121 are arranged in a mirror image, so that the two feed points 1211 output the echo signals with a phase difference of about 180 ° and a balanced differential signal form at the two feed points 1211 based on the structure state that the two radiation elements 121 are arranged in opposite phases and the two feed points 1211 are equidistant from the physical center point 1212 of the radiation element 121 to which the two feed points belong.
Corresponding to fig. 9C and 9D, in both embodiments of the present invention, the receiving antenna is exemplified by the half-wave folded directional microwave detecting antenna 10A polarized in reverse phase.
Specifically, corresponding to fig. 9C, the half-wave folded-back directional microwave detecting antenna 10A of the horizontal structure with the receiving antenna polarized in opposite phase is disposed, and the half-wave folded-back directional microwave detecting antenna 10A includes two half-wave oscillators 12A, wherein the two half-wave oscillators 12A are arranged in opposite phase, and the direction perpendicular to the reference ground 11A is taken as the height direction of the half-wave folded-back directional microwave detecting antenna 10A, and the extending direction of the two half-wave oscillators 12A from the feeding point 121A in the height direction of the half-wave folded-back directional microwave detecting antenna 10A is reversed, so that the echo signals in a balanced differential signal form are output at the two feeding points 121A based on the structural state that the two half-wave oscillators 12A are arranged in opposite phase.
Corresponding to fig. 9D, the half-wave folded-back directional microwave probe antenna 10A of the receiving antenna in a reverse-phase polarized vertical structure is provided, the half-wave elements 12A corresponding to the half-wave folded-back directional microwave probe antenna 10A are arranged in reverse phase, i.e., with the direction perpendicular to the reference ground 11A being the height direction of the half-wave folded-back directional microwave probe antenna 10A, the half-wave elements 12A are reversed from the two feeding ports 1211A in the extending direction perpendicular to the height direction of the half-wave folded-back directional microwave probe antenna 10A, so as to output the echo signals in a balanced differential signal form at the two feeding ports 1211A based on the structural state that the half-wave elements 12A are arranged in reverse phase.
Corresponding to fig. 9E, in this embodiment of the present invention, the receiving antenna is exemplified by the double-fed differential antenna 10B, so that two coupling sections 122B of the two strip-shaped oscillators 12B extend from the near end in opposite directions and can be coupled with each other to form a common structural characteristic of a resonant frequency point, and two strip-shaped oscillators 12B are formed in a structural state of being arranged in opposite directions in a polarization direction tending to linear polarization, and thus the echo signal in a balanced differential signal form can be directly output at two feeding ends 121B when the double-fed differential antenna 10B is used as the receiving antenna.
It is worth mentioning that, in other embodiments of the present invention, in a state that the microwave beam is in a weak signal form based on the transmission power of the transmitting antenna being reduced to a target transmission power, the transmitting antenna is allowed to be set in an orthogonal polarization form corresponding to a state that the strength of the echo signal is improved to improve the accuracy and stability of the feedback of the doppler intermediate frequency signal to the activity characteristics corresponding to the movement action, the inching action, and the respiration and the heartbeat action of the human body, and the radiation source is orthogonally set in a binary radiation source form corresponding to a state that the transmitting antenna is set in a planar patch antenna form, that is, the radiation source has two radiation elements, and a connection line direction from the feed point to a physical central point of one of the radiation elements is perpendicular to a connection line direction from the feed point to a physical central point of the other radiation element; and in the state that the transmitting antenna is set by the half-wave folded-back directional microwave detection antenna, the half-wave folded-back directional microwave detection antenna is set in an orthogonal polarization state, namely, the half-wave folded-back directional microwave detection antenna comprises two half-wave oscillators, wherein the two half-wave oscillators are orthogonally arranged, and correspondingly, the direction perpendicular to the reference ground direction is taken as the height direction of the half-wave folded-back directional microwave detection antenna, and the extending directions of the two half-wave oscillators perpendicular to the height direction of the half-wave folded-back directional microwave detection antenna are mutually perpendicular.
It should be noted that, in some embodiments of the present invention, different combinations of the transmitting antenna and the receiving antenna of the above embodiments can be integrally disposed in a transmitting and receiving separated form or a transmitting and receiving integrated form in a structural form sharing the reference ground, thereby facilitating the miniaturization design of the microwave detecting device of the micro transmitting power.
For example, referring to fig. 10A to 10J of the drawings of the present invention, based on different combinations of the transmitting antenna and the receiving antenna according to the above embodiments, the transmitting antenna and the receiving antenna that are integrally provided in a transmission/reception separated form or a transmission/reception integrated form in a structural form that shares the reference ground are illustrated.
Corresponding to fig. 10A, based on the combination of the transmitting antenna illustrated in fig. 1A and the receiving antenna illustrated in fig. 8A, in the structural form that the transmitting antenna and the receiving antenna share the reference ground 11 and the radiation source 12, the integral structure of the transmitting antenna and the receiving antenna is illustrated, wherein the integral structure of the transmitting antenna and the receiving antenna has the reference ground 11 and the radiation source 12, wherein the radiation source 12 is disposed at one side of the reference ground 11 in a spaced state from the reference ground 11, wherein the radiation source 12 is arranged in a unit radiation source configuration, having a single number of radiation elements 121 corresponding to the radiation source 12, wherein the radiating element 121 has four feeding points 1211, wherein in the direction around the physical center point 1212 of the radiating element 121, the included angle between the connecting line between any two adjacent feeding points 1211 and the physical center point 1212 of the radiating element 121 is equal to 90 °, so that by means of phase difference feeding, in the direction around the physical center point 1212 of the radiating element 121, two adjacent feeding points 1211 are sequentially connected to the excitation signals with a 90 ° difference therebetween, so as to realize the circular polarization form of the transmitting antenna 10, and outputting the echo signals in a balanced differential signal form between one of the two feeding points 1211 and an end of the phase shifter distant from the other feeding point 1211 based on a phase shift process of the phase shifter on the echo signals accessed from one of the two feeding points 1211 by accessing the phase shifter at one of the other two feeding points 1211, so as to form an integral structure of the transmitting antenna and the receiving antenna in a transceiving separated form.
On the basis of a combination of the transmitting antenna illustrated in fig. 2A and the receiving antenna illustrated in fig. 9A, corresponding to fig. 10B and 10C, in a structural configuration in which the transmitting antenna and the receiving antenna share the ground reference 11, a unitary structure of the transmitting antenna and the receiving antenna of different embodiments is illustrated, wherein the unitary structure of the transmitting antenna and the receiving antenna has the ground reference 11 and the radiation source 12, wherein the radiation source 12 is disposed on one side of the ground reference 11 in a state spaced apart from the ground reference 11, wherein corresponding to fig. 10B, the radiation source 12 is disposed in a unit radiation source configuration, corresponding to the radiation source 12 has a single number of radiation elements 121, wherein the radiation elements 121 have four of the feed points 1211, in the direction around the physical center point 1212 of the radiating element 121, an angle between a connecting line between any two adjacent feeding points 1211 and the physical center point 1212 of the radiating element 121 is equal to 90 °, and a structural state that two opposite feeding points 1211 are arranged in opposite phase is correspondingly formed, in a manner of phase difference feeding, a state that two opposite feeding points 1211 of the radiating element 121 access excitation signals with a phase difference larger than 90 ° to realize differential feeding to the transmitting antenna 10, and the other two opposite feeding points 1211 output the echo signals in a balanced differential signal form, so as to form an integrated structure of the transmitting antenna and the receiving antenna in a transceiving separated form; corresponding to fig. 10C, the radiation source 12 is configured as a binary radiation source, and has two radiation elements 121 corresponding to the radiation source 12, wherein each of the radiation elements 121 has two feeding points 1211, wherein the two feeding points 1211 of each of the radiation elements 121 are arranged in opposite phases, a connection direction from one of the feeding points 1211 to the physical central point 1212 of each of the radiation elements 121 coincides with a connection direction from the other of the feeding points 1211 to the physical central point 1212 thereof, so that a polarization direction of each of the radiation elements 121 corresponds to a connection direction of the two feeding points 1211 thereof, wherein the two radiation elements 121 are arranged orthogonally, the polarization direction of one of the radiation elements 121 is perpendicular to the polarization direction of the other radiation element 121, so that a differential feeding to the transmission antenna 10 is realized in a manner of feeding the two feeding points 1211 of one of the radiation elements 121 into excitation signals different by more than 90 ° in a manner of phase difference, and the two feeding points 1211 of the other radiation elements 121 output the echo signals in a form of a differential signal transmission and reception structure, and the transmission antenna and the reception structure in a separate form an integral structure.
Corresponding to fig. 10D, the transmitting antennas arranged in the orthogonal polarization form are combined based on the receiving antenna illustrated in fig. 8B for the purpose of improving the strength of the echo signal, in the structural form that the transmitting antenna and the receiving antenna share the reference ground 11, the integral structure of the transmitting antenna and the receiving antenna is illustrated, wherein the integral structure of the transmitting antenna and the receiving antenna has the reference ground 11 and the radiation source 12, wherein the radiation source 12 is disposed at one side of the reference ground 11 in a state of being spaced apart from the reference ground 11, wherein the radiation source 12 is arranged in a quaternary radiation source configuration, having four of the radiation elements 121 corresponding to the radiation source 12, wherein each of the radiating elements 121 has a feeding point 1211, wherein each of the radiating elements 121 is circumferentially arranged and satisfies that, in the circumferential arrangement direction of the radiating elements 121, an angle between a connecting line between the feeding point 1211 of any two adjacent radiating elements 121 and a physical center point 1212 thereof is equal to 90 degrees, one of the feeding points 1211 is electrically connected to a phase shifter, so that the echo signals in a balanced differential signal form are output between one end of the phase shifter far from the feeding point 1211 and another feeding point 1211 adjacent to the feeding point 1211 in the circumferential arrangement direction of the radiating element 121 based on the phase shifting processing of the phase shifter on the echo signals accessed from the feeding point 1211, and in the state that the other two feeding points 1211 are connected with the excitation signal, based on the orthogonal polarization state of the two radiation elements 121 to which the two feeding points 1211 belong, the intensity of the echo signal is improved, so as to form an integral structure of the transmitting antenna and the receiving antenna in a transceiving separated form.
Corresponding to fig. 10E, based on the combination of the transmitting antenna illustrated in fig. 2B and the receiving antenna illustrated in fig. 9B, a structure of the transmitting antenna and the receiving antenna integrated with each other is illustrated in a structure in which the transmitting antenna and the receiving antenna share the ground reference 11, wherein the structure of the transmitting antenna and the receiving antenna integrated with each other has the ground reference 11 and the radiation source 12, wherein the radiation source 12 is disposed on one side of the ground reference 11 in a state spaced apart from the ground reference 11, wherein the radiation source 12 is disposed in a quaternary radiation source configuration, and the radiation source 12 has four radiation elements 121, wherein each of the radiation elements 121 has a feeding point 1211, the angle between the feeding point 1211 of any two adjacent radiating elements 121 and the connecting line between the physical central points 1212 of the two adjacent radiating elements 121 is equal to 90 ° in the circumferential arrangement direction of the radiating elements 121, wherein the two feeding points 1211 of the two radiating elements 121 opposite in the circumferential arrangement direction of the radiating elements 121 are used as transmitting feeding points, and through a phase difference feeding mode, the two feeding points 1211 are connected with excitation signals with a phase difference larger than 90 ° to realize differential feeding on the transmitting antenna 10, and the other two feeding points 1211 output the echo signals in a balanced differential signal form, so as to correspondingly form an integrated structure of the transmitting antenna and the receiving antenna in a transceiving separation mode.
In particular, in the two embodiments of the present invention corresponding to fig. 10D and 10E, in the circumferential arrangement direction of the radiation elements 121, in two opposite radiation elements 121, the connection line from the feeding point 1211 to the physical central point 1212 of one radiation element 121 is staggered and opposite to the connection line from the feeding point 1211 to the physical central point 1212 of the other radiation element 121, and the feeding point 1211 and the connection line from the physical central point 1212 of each radiation element 121, which are correspondingly formed, intersect to form a regular quadrilateral structure, so as to facilitate reducing the radial area occupied by the arrangement of the radiation elements 121.
Corresponding to fig. 10F, on the basis of the receiving antenna illustrated in fig. 8C, the transmitting antenna provided in the orthogonal polarization form is combined for the purpose of improving the intensity of the echo signal, and the integrated structure of the transmitting antenna and the receiving antenna is illustrated in the structural form in which the transmitting antenna and the receiving antenna share the reference ground 11A, wherein the transmitting antenna and the receiving antenna are respectively provided in the half-wave folded-back directional microwave detecting antenna 10A of the orthogonal polarization horizontal structure, the half-wave folded-back directional microwave detecting antenna 10A includes four half-wave elements 12A, four of which are circumferentially arranged and satisfy the circumferential arrangement direction of the half-wave elements 12A, any two of the half-wave elements 12A adjacent to each other are orthogonally arranged, corresponding to the height direction of the half-wave folded-back directional microwave detecting antenna 10A in the direction perpendicular to the reference ground 11A, in the circumferential arrangement direction of the half-wave oscillators 12A, any two adjacent half-wave oscillators 12A are perpendicular to each other in the extending direction perpendicular to the height direction of the half-wave folded directional microwave detecting antenna 10A, wherein the feeding point 121A of one half-wave oscillator 12A is connected to a phase shifter via the feeding line 13A, so that the echo signal inputted from the feeding point 121A is outputted as a balanced differential signal between one end of the phase shifter remote from the feeding point 121A and another feeding point 121A adjacent to the feeding point 121A in the circumferential arrangement direction of the half-wave oscillator 12A based on the phase shift processing of the phase shifter on the echo signal inputted from the feeding point 121A, and in a state where the other two feeding points 121A are inputted with excitation signals, based on the structural form that the two half-wave oscillators 12A to which the two feeding points 121A belong are orthogonally arranged, and improving the strength of the echo signal so as to form an integral structure of the transmitting antenna and the receiving antenna in a transceiving separation mode.
Corresponding to fig. 10G, on the basis of the receiving antenna illustrated in fig. 9C, the transmitting antenna provided in a reverse polarization form is combined for the purpose of improving the accuracy of the echo signal, and an integrated structure of the transmitting antenna and the receiving antenna is illustrated in a structural form in which the transmitting antenna and the receiving antenna share the reference ground 11A, wherein the transmitting antenna and the receiving antenna are respectively provided in the half-wave folded-back type directional microwave detecting antenna 10A of a horizontal type structure in reverse polarization, the corresponding half-wave folded-back type directional microwave detecting antenna 10A includes four half-wave elements 12A, wherein the four half-wave elements 12A are arranged in the circumferential direction and satisfy that in the circumferential direction of the half-wave elements 12A, any two adjacent half-wave elements 12A are arranged orthogonally, correspondingly, the direction perpendicular to the reference ground 11A is taken as the height direction of the half-wave folded-back directional microwave detection antenna 10A, in the circumferential arrangement direction of the half-wave oscillators 12A, any two adjacent half-wave oscillators 12A are perpendicular to each other in the extension direction perpendicular to the height direction of the half-wave folded-back directional microwave detection antenna 10A, wherein two feeding points 121A of the two half-wave oscillators 12A opposite to the circumferential arrangement direction of the half-wave oscillators 12A are taken as transmission feeding points, and in a phase difference feeding manner, the two feeding points 121A are connected with excitation signals with a phase difference larger than 90 ° to realize differential feeding to the transmission antenna, and echo signals in a balanced differential signal form are output from the other two feeding points 121A, so as to correspondingly form an integrated structure of the transmission antenna and the reception antenna in a transceiving separation form.
Corresponding to fig. 10H, on the basis of the receiving antenna illustrated in fig. 8D, the transmitting antenna configured in an orthogonal polarization form is combined, specifically, the receiving antenna is the transmitting antenna, and an integrated structure of the transmitting antenna and the receiving antenna is illustrated, wherein the transmitting antenna and the receiving antenna are configured in the half-wave folded-back directional microwave detecting antenna 10A of a vertical structure of the same orthogonal polarization, the half-wave folded-back directional microwave detecting antenna 10A includes two half-wave oscillators 12A, two half-wave oscillators 12A are orthogonally arranged, and an extending direction of the two half-wave oscillators 12A in a direction perpendicular to a height direction of the half-wave folded-back directional microwave detecting antenna 10A is perpendicular to a direction perpendicular to the reference ground 11A, one of the feeding ends 1211A of the half-wave oscillators 12A is connected to a phase shifter through the feeding line 13A, so as to output the echo signal in a balanced differential signal form between one end of the phase shifter, which is far away from the feeding end 1211A of the half-wave oscillator 12A, and one of the feeding ends 1211A of the other half-wave oscillator 12A based on the phase shift processing of the echo signal accessed from the feeding end 1211A by the phase shifter, and to increase the intensity of the echo signal based on the structural form that the two half-wave oscillators 12A to which the two feeding ends 1211A belong are orthogonally arranged in a state that the other two feeding ends 1211A are accessed to an excitation signal, thereby forming an integrated structure of the transmitting antenna and the receiving antenna in a transceiving form.
Corresponding to fig. 10I, based on the combination of the transmitting antenna illustrated in fig. 3A and the receiving antenna illustrated in fig. 9D, in the structural form that the transmitting antenna and the receiving antenna share the reference ground 11A, the integrated structure of the transmitting antenna and the receiving antenna is illustrated, wherein the transmitting antenna and the receiving antenna are respectively provided with the half-wave folded-back directional microwave detecting antenna 10A of the vertical structure of the opposite-phase polarization, the integrated structure corresponding to the transmitting antenna and the receiving antenna includes two half-wave elements 12A, wherein each half-wave element 12A is arranged in the opposite phase, and the two half-wave elements 12A are arranged orthogonally to each other, corresponding to the direction perpendicular to the reference ground 11A as the height direction of the half-wave folded-back directional microwave detecting antenna 10A, each half-wave oscillator 12A is reversed in the extending direction perpendicular to the height direction of the half-wave folded-back directional microwave detecting antenna 10A from the two feeding ends 1211A, and the two half-wave oscillators 12A are perpendicular to each other in the extending direction perpendicular to the height direction of the half-wave folded-back directional microwave detecting antenna 10A, so that the two feeding ends 1211A of one half-wave oscillator 12A output the echo signal in a balanced differential signal form based on the structural state in which each half-wave oscillator 12A is arranged in reverse phase, and the differential feeding to the transmitting antenna is realized in the state in which the two feeding ends 1211A of the other half-wave oscillator 12A are connected to excitation signals with a difference of more than 90 °, so as to form an integrated structure of the transmitting antenna and the receiving antenna in a transceiving split form.
Corresponding to fig. 10J, on the basis of the receiving antenna illustrated in fig. 9E, based on the purpose of improving the accuracy of the echo signal, based on the transceiving reciprocity characteristic of the antenna, the receiving antenna is the transmitting antenna, and the integrated structure of the transmitting antenna and the receiving antenna is illustrated, wherein the receiving antenna is exemplified by the double feed differential antenna 10B, and based on the structural characteristic that the two coupling sections 122B of the two strip-shaped elements 12B extend from the proximal end in opposite directions and can be coupled with each other to form a common resonant frequency point, the two strip-shaped elements 12B are formed in a structural state in which they are arranged in opposite phases in the polarization direction tending to linear polarization, so that the echo signal in the form of a balanced differential signal can be directly output at the two feed ends 121B when the double feed differential antenna 10B is used as the receiving antenna, and the transmitting antenna and receiving antenna are integrated in the form of the transmitting antenna and receiving antenna by switching in the two feed ends 121B of the two strip-shaped elements 12B in a state in which excitation signals differ by more than 90 °.
Corresponding to the above description, according to the present invention, the detection method of the microwave detection device of micro-transmitting power includes the following steps:
A. feeding the transmitting antenna with an excitation signal with a phase difference larger than 90 degrees in the polarization direction of the transmitting antenna tending to linear polarization by means of phase difference feeding so as to realize differential feeding of the transmitting antenna with the phase difference larger than 90 degrees;
B. accessing the echo signals with phase difference of 180 degrees and in a balanced differential signal form from the receiving antenna; and
C. outputting the doppler intermediate frequency signal in a single-ended signal form with a frequency/phase difference between the excitation signal and the echo signal in a mixing processing step and a differential-to-single-ended processing step based on step (C1) or step (C2), wherein in step (C1), the echo signal in a single-ended signal form is output based on the differential-to-single-ended processing of the echo signal in a balanced differential signal form by the differential-to-single-ended circuit, and the doppler intermediate frequency signal in a single-ended signal form is output based on the mixing processing of the excitation signal and the echo signal in a balanced differential signal form by the mixing circuit, wherein in step (C2), the doppler intermediate frequency signal in a balanced differential signal form is output based on the mixing processing of the excitation signal and the echo signal in a balanced differential signal form by the mixing circuit, and the doppler intermediate frequency signal in a single-ended signal form is output based on the differential-to-single-ended processing of the doppler intermediate frequency signal in a balanced differential signal form by the differential-to single-ended circuit.
In some embodiments of the present invention, corresponding to fig. 2A, the transmitting antenna is configured with a ground reference 11 and a radiation source 12 in a planar patch antenna state, wherein the radiation source 12 is configured at one side of the ground reference 11 in a state spaced from the ground reference 11, the radiation source 12 is configured in a unit radiation source state, the radiation source 12 has a single number of radiation elements 121, the radiation elements 121 have two feeding points 1211, wherein the two feeding points 1211 are arranged in opposite phases, a connection direction corresponding to a physical central point 1212 of one of the feeding points 1211 to a physical central point 1212 of the radiation element 121 coincides with a connection direction corresponding to a physical central point 1212 of the other feeding point 1211 to a physical central point 1212 of the radiation element 121, then the radiation element 121 has a polarization state of linear polarization in a state where the feeding points 1211 is connected to an excitation signal, and a connection direction of the two feeding points 1211 is a linear polarization direction, so that a differential polarization state of the two feeding points 1211 connected to the excitation signal with a difference of more than 90 ° is realized by the phase-difference feeding of the transmitting antenna.
In some embodiments of the present invention, corresponding to fig. 2B, the transmitting antenna is configured with a ground reference 11 and a radiation source 12 in a planar patch antenna configuration, wherein the radiation source 12 is configured at one side of the ground reference 11 in a spaced state from the ground reference 11, the radiation source 12 is configured in a binary radiation source configuration, the radiation source 12 has two radiation elements 121, each of the radiation elements 121 has a feeding point 1211, wherein the two radiation elements 121 are arranged in opposite phases, a connection direction from the feeding point 1211 to a physical central point 1212 of one of the radiation elements 121 and a connection direction from the feeding point 1211 to the physical central point of the other radiation element 121 are opposite to each other, and then the two radiation elements 121 have a linear polarization configuration in a state where the two feeding points 1211 are connected to an excitation signal and have a linear polarization direction from the feeding point 1211 to the physical central point, so that a differential polarization state of the two feeding points 1211 of the two radiation elements 121 connected to the excitation signal with a difference of more than 90 ° is realized by a differential feeding direction of the transmitting antenna.
In some embodiments of the present invention, corresponding to fig. 3A, the transmitting antenna is configured as the half-wave folded directional microwave detecting antenna of a vertical structure, and includes a ground reference 11A, a half-wave oscillator 12A and two feeding lines 13A, wherein the half-wave oscillator 12A has an electrical length of 1/2 or more and 3/4 or less wavelength, and has two coupling sections 121A, each of the coupling sections 121A has an electrical length of 1/6 or more wavelength, one end of each of the coupling sections 121A is named as the feeding end 1211A of the coupling section 121A, and the other end of each of the coupling sections 121A is used as the two ends of the half-wave oscillator 12A, wherein the distance between the two feeding ends 1211A is λ/4 or less, the distance between the two ends of the half-wave oscillator 12A is λ/128 or more and λ/6 or less, the half-wave oscillator 12A is in a state that two feeding ends 1211A are respectively connected to two poles of an excitation signal or connected to an excitation signal with a phase difference to be fed, two ends of the half-wave oscillator 12A can form a phase difference to be mutually coupled to form a polarization form tending to linear polarization, and when the direction perpendicular to the reference ground 11A is the height direction of the half-wave folded-back directional microwave detecting antenna 10A, the extending direction of the half-wave oscillator 12A in the direction perpendicular to the height direction of the half-wave folded-back directional microwave detecting antenna 10A is taken as the linear polarization direction, so that differential feeding to the transmitting antenna is realized in the linear polarization direction of the transmitting antenna in a state that the two feeding ends 1211A of the half-wave oscillator are connected to the excitation signal with a phase difference larger than 90 ° in a phase difference feeding manner.
In some embodiments of the present invention, the transmitting antenna is disposed corresponding to the half-wave folded-back directional microwave detecting antenna 10A of the horizontal structure with reverse polarization of the receiving antenna illustrated in fig. 9C, and the half-wave folded-back directional microwave detecting antenna 10A includes two half-wave oscillators 12A, wherein the two half-wave oscillators 12A are arranged in reverse phase, and corresponding to the height direction of the half-wave folded-back directional microwave detecting antenna 10A perpendicular to the reference ground 11A direction, the two half-wave oscillators 12A are reversed in the extending direction perpendicular to the height direction of the half-wave folded-back directional microwave detecting antenna 10A from the feeding point 121A, based on the structural state that the two half-wave oscillators 12A are arranged in reverse phase, in a state that the two feeding points 121A are fed with the excitation signals having the phase difference, the two half-wave oscillators 12A can form the phase difference to mutually couple and form a polarization form tending to linear polarization, and when the direction perpendicular to the reference ground 11A is the height direction of the half-wave folded-back directional microwave detecting antenna 10A, the extending direction of the half-wave oscillators 12A in the height direction perpendicular to the half-wave folded-back directional microwave detecting antenna 10A is the linear polarization direction, so that in a manner of feeding by the phase difference, the differential feeding to the transmitting antenna is realized in the linear polarization direction of the transmitting antenna in a state that the two feeding points 121A are fed with the excitation signals having the phase difference larger than 90 °.
In some embodiments of the present invention, corresponding to fig. 4A to 4N, the transmitting antenna is configured as the dual-feed differential antenna, and the transmitting antenna includes a reference ground 11B and two strip-shaped oscillators 12B, wherein two ends of the two strip-shaped oscillators 12B, which are connected to the excitation signal, are respectively the feeding ends 121B of the two strip-shaped oscillators 12B, the two strip-shaped oscillators 12B extend from the two feeding ends 121B in the same lateral space of the reference ground 11B and respectively have the wavelength electrical length greater than or equal to 3/16 and less than or equal to 5/16, wherein the two strip-shaped oscillators 12B respectively have a coupling section 122B, wherein one end of the coupling section 122B, which is close to the feeding end 121B of the strip-shaped oscillator 12B to which the coupling section 122B belongs, is a proximal end of the coupling section 122B, and the two coupling sections 122B extend from the proximal ends in opposite directions, the two coupling sections 122B extend from the near end in opposite directions based on a structural form that the two coupling sections 122B extend from the near end, coupling between the two coupling sections 122B is formed in a state that the two feeding ends 121B of the two strip-shaped oscillators 12B are connected with excitation signals with phase difference, and a polarization form tending to linear polarization is formed, and when a direction perpendicular to the reference ground 11B is taken as a height direction of the double-ended feeding type differential antenna, an extending direction of the strip-shaped oscillators 12B in the direction perpendicular to the height direction of the double-ended feeding type differential antenna is taken as a linear polarization direction, so that the two feeding ends 121B of the two strip-shaped oscillators 12B are connected with excitation signals with phase difference larger than 90 degrees in a phase difference feeding manner, and differential feeding of the transmitting antenna is realized in the polarization direction tending to linear polarization of the transmitting antenna.
In some embodiments of the present invention, wherein in the step (a), the transmitting power of the transmitting antenna is less than or equal to 0dBm.
In response to the above description, according to another embodiment of the present invention, the detection method of the microwave detection device for micro-emission power includes the following steps:
A. setting a transmit power of the transmit antenna at a target transmit power of less than or equal to 0dBm based on a corresponding parameter setting of an excitation signal;
B. accessing the echo signals with phase difference of about 180 degrees and in a balanced differential signal form from the receiving antenna; and
C. outputting the doppler intermediate frequency signal in a single-ended signal form with a frequency/phase difference between the excitation signal and the echo signal in a mixing processing step and a differential-to-single-ended processing step based on step (C1) or step (C2), wherein in step (C1), the echo signal in a single-ended signal form is output based on the differential-to-single-ended processing of the echo signal in a balanced differential signal form by the differential-to-single-ended circuit, and the doppler intermediate frequency signal in a single-ended signal form is output based on the mixing processing of the excitation signal and the echo signal in a balanced differential signal form by the mixing circuit, wherein in step (C2), the doppler intermediate frequency signal in a balanced differential signal form is output based on the mixing processing of the excitation signal and the echo signal in a balanced differential signal form by the mixing circuit, and the doppler intermediate frequency signal in a single-ended signal form is output based on the differential-to-single-ended processing of the doppler intermediate frequency signal in a balanced differential signal form by the differential-to single-ended circuit.
In some embodiments of the present invention, in the step (a), the circular polarization form of the transmitting antenna is implemented and the minimum transmitting power extreme value of the transmitting antenna is reduced by means of phase difference feeding.
In some embodiments of the present invention, in the step (a), in a manner of phase difference feeding, the polarization direction of the transmitting antenna tending to linear polarization feeds the transmitting antenna with an excitation signal greater than 90 ° phase difference, so as to implement differential feeding greater than 90 ° phase difference for the transmitting antenna.
In the description herein, references to the description of the term "one embodiment," "some embodiments," "an example," "a specific example," or "some examples," etc., mean that a particular feature, structure, material, or characteristic described in connection with the embodiment or example is included in at least one embodiment or example of the invention. In this specification, the terminology used in the description above is not necessarily meant to be the same embodiment or example. Furthermore, the particular features, structures, materials, or characteristics described may be combined in any suitable manner in any one or more embodiments or examples. Moreover, various embodiments or examples and features of various embodiments or examples described in this specification can be combined and combined by one skilled in the art without being mutually inconsistent.
It will be understood by those skilled in the art that the embodiments of the present invention as described above and shown in the drawings are given by way of example only and are not limiting of the present invention. The objects of the present invention have been fully and effectively accomplished. The functional and structural principles of the present invention have been shown and described in the embodiments without departing from the principles, embodiments of the present invention may have any deformation or modification.

Claims (10)

1. Microwave detection device of little transmitted power, characterized by, includes:
a differential feed circuit, wherein the differential feed circuit is configured to output excitation signals that differ by more than 90 ° in a powered state;
a transmitting antenna, wherein the transmitting antenna is configured as a dual feed differential antenna, the transmitting antenna comprises a reference ground and two strip-shaped oscillators, two ends of an access excitation signal of the two strip-shaped oscillators are respectively used as feeding ends of the two strip-shaped oscillators, the two strip-shaped oscillators extend from the two feeding ends in the same lateral space of the reference ground and respectively have electrical lengths of wavelengths greater than or equal to 3/16 and less than or equal to 5/16, the two strip-shaped oscillators respectively have a coupling section, one end of the coupling section, which is close to the feeding end of the strip-shaped oscillator to which the coupling section belongs, is used as a proximal end of the coupling section, the two coupling sections extend from the proximal end in opposite directions, so that based on a structural form that the two coupling sections extend from the proximal ends in opposite directions, a coupling form between the two coupling sections is formed in a state that the two feeding ends of the two strip-shaped oscillators are accessed into the excitation signal with a phase difference, and a polarization form of the two feeding ends of the two strip-shaped oscillators into the differential antenna with a phase difference of greater than 90 ° so as to realize a polarization form of the transmitting antenna for the differential antenna;
a receiving antenna, wherein the receiving antenna has a polarization direction tending to linear polarization and outputs a corresponding echo signal in a balanced differential signal form with a phase difference tending to 180 ° after receiving a reflected echo formed by a microwave beam emitted by the transmitting antenna being reflected by a corresponding object, and then the echo signal contains a signal corresponding to a reflected echo formed by the microwave beam being reflected by the corresponding object, and electromagnetic interference in the environment exists in a common-mode interference form in the echo signal and can be suppressed during the receiving and transmitting processes of the echo signal in the balanced differential signal form; and
a mixer circuit electrically connected to the differential feed circuit and the receiving antenna for receiving the excitation signal and the echo signal in a balanced differential signal form and outputting a doppler intermediate frequency signal in a single-ended signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal.
2. The microwave detection device of claim 1, wherein the two coupling sections of the dual feed differential antenna extend from the proximal end in opposite directions of the offset, and have an offset distance of λ/256 or more and λ/6 or less, i.e. a distance from any point on one of the coupling sections to the other coupling section is λ/256 or more and λ/6 or less, where λ is a wavelength parameter corresponding to a frequency of the excitation signal.
3. The microwave detection apparatus according to claim 2, wherein the two coupling sections of the two strip oscillators extend from the proximal end toward each other in mutually parallel offset directions.
4. A microwave detection apparatus according to claim 3 wherein the strip vibrator is provided in the form of a microstrip line carried on a circuit board.
5. The microwave detecting apparatus of micro emitted power according to any of claims 1 to 4, wherein the receiving antenna is configured as the double-fed differential antenna, so that the two strip-shaped elements are formed in a structure state in which they are arranged in opposite phases in a polarization direction tending to linear polarization based on a structural characteristic that two coupling sections of the two strip-shaped elements extend in opposite directions from the proximal end and can be coupled with each other to form a common resonant frequency point, thereby directly outputting the echo signals in a balanced differential signal form at the two feeding ends when the double-fed differential antenna is used as the receiving antenna.
6. The microwave detecting device of micro transmitted power according to claim 5, wherein the receiving antenna is integrated with the transmitting antenna in a transceiving integration mode based on a structural configuration sharing the transmitting antenna, the two feeding terminals directly output the echo signals in a balanced differential signal configuration, and the two feeding terminals of the two strip-shaped elements are connected to excitation signals with a phase difference of more than 90 °, so as to realize differential feeding of the transmitting antenna in a polarization direction of the transmitting antenna tending to linear polarization, thereby forming an integrated structure of the transmitting antenna and the receiving antenna in the transceiving integration mode.
7. The micro transmitted-power microwave detecting device according to claim 5, wherein the differential feed circuit has a three-pole circuit processor configured as a MOS tube or a triode, an inductor, a first resistor, a second resistor, a third resistor, a first capacitor, a second capacitor, an oscillation capacitor and a power connection terminal adapted to be connected to a corresponding power source, wherein the three-pole circuit processor has a first connection terminal corresponding to a collector of the triode or a drain of the MOS tube, a second connection terminal corresponding to a base of the triode or a gate of the MOS tube, and a third connection terminal corresponding to an emitter of the triode or a source of the MOS tube, wherein one end of the second resistor is electrically connected to the first connection terminal of the three-pole circuit processor, and the other end of the second resistor is connected to the power connection terminal via the inductor and is grounded via the first capacitor, wherein one end of the third resistor is electrically connected to the third connection terminal of the three-pole circuit processor, and the other end of the third resistor is grounded, wherein one end of the oscillation capacitor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the oscillation capacitor is grounded, wherein one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the first resistor is electrically connected between the inductor and the second resistor, wherein two ends of the second capacitor are electrically connected to the first connection terminal and the third connection terminal of the three-pole circuit processor, respectively, wherein the second resistor and the third resistor are set to have equal resistance values so as to switch the differential feed circuit into the corresponding power supply at the power connection terminal, and outputting the excitation signal in a balanced differential signal form with a phase difference of about 180 degrees at two ends of the second capacitor, so that the phase difference feeding of about 180 degrees of the transmitting antenna is realized.
8. The micro transmitted-power microwave detecting device according to claim 5, wherein the differential feed circuit has a three-pole circuit processor configured as a MOS tube or a triode, an inductor, a first resistor, a second resistor, a third resistor, a first capacitor, a second capacitor, an oscillation capacitor and a power connection terminal adapted to be connected to a corresponding power source, wherein the three-pole circuit processor has a first connection terminal corresponding to a collector of the triode or a drain of the MOS tube, a second connection terminal corresponding to a base of the triode or a gate of the MOS tube, and a third connection terminal corresponding to an emitter of the triode or a source of the MOS tube, wherein one end of the second resistor is electrically connected to the first connection terminal of the three-pole circuit processor, and the other end of the second resistor is connected to the power connection terminal via the inductor, and is grounded via the first capacitor, wherein one end of the third resistor is electrically connected to the third connection terminal of the three-pole circuit handler, and the other end of the third resistor is grounded, wherein one end of the oscillation capacitor is electrically connected to the second connection terminal of the three-pole circuit handler, and the other end of the oscillation capacitor is grounded, wherein one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit handler, and the other end of the first resistor is electrically connected to the power connection terminal, wherein two ends of the second capacitor are electrically connected to the first connection terminal and the third connection terminal of the three-pole circuit handler, respectively, wherein the second resistor and the third resistor are set at equal resistances to switch on the respective power supply at the power connection terminal of the differential feed circuit, and outputting the excitation signal in a balanced differential signal form with a phase difference of about 180 degrees at two ends of the second capacitor, so that the phase difference feeding of about 180 degrees of the transmitting antenna is realized.
9. The microwave detecting device of micro transmitting power of claim 5, wherein the differential feeding circuit outputs the excitation signal in a differential oscillating circuit with balanced differential signals with a phase difference of about 180 °, wherein the differential oscillating circuit has two N-channel MOS transistors, two P-channel MOS transistors, an oscillating inductor and an oscillating capacitor, wherein the sources of the two N-channel MOS transistors are electrically connected, the sources of the two P-channel MOS transistors are electrically connected, the drains of the two N-channel MOS transistors are electrically connected to the drains of the different P-channel MOS transistors, respectively, so as to form the drain of one of the N-channel MOS transistors electrically connected to the drain of one of the P-channel MOS transistors, the source of the P-channel MOS transistor is electrically connected to the source of the other P-channel MOS transistor, and the drain of the other P-channel MOS transistor is electrically connected to the drain of the other N-channel MOS transistor, and the source of the other N-channel MOS transistor is electrically connected with the source of the previous N-channel MOS transistor in a sequential connection relationship, wherein in the two N-channel MOS transistors, the grid of any one N-channel MOS transistor is electrically connected with the drain of the other N-channel MOS transistor, wherein in the two P-channel MOS transistors, the grid of any one P-channel MOS transistor is electrically connected with the drain of the other P-channel MOS transistor, wherein the two ends of the oscillation inductor are respectively and electrically connected with the drains of the different P-channel MOS transistors, the two ends of the oscillation capacitor are respectively and electrically connected with the drains of the different P-channel MOS transistors and are connected with the oscillation inductor in parallel, so that the oscillation and the frequency selection are formed on the basis of a parallel resonance loop consisting of the oscillation inductor and the oscillation capacitor, and the sizes of the oscillation inductor and the two ends of the oscillation capacitor are equal, the electric signals in opposite directions enable one of the N-channel MOS tubes and the P-channel MOS tube electrically connected with the grid electrode of the N-channel MOS tube to be conducted at the same time, and enable the other N-channel MOS tube and the P-channel MOS tube electrically connected with the grid electrode of the N-channel MOS tube to be conducted at the same time, so that the excitation signals are output at two ends of the oscillation inductor in a balanced differential signal mode with a 180-degree difference.
10. The microwave detecting device for micro transmitting power according to claim 9, wherein the differential feeding circuit further comprises a low dropout regulator, an oscillator, a phase-locked loop and a logic control unit, wherein the low dropout regulator provides a constant voltage to the differential oscillating circuit in a powered state, wherein the oscillator is configured such that the logic control unit provides a basic clock signal and is externally disposed with a quartz crystal oscillator or integrally disposed with an internal oscillating circuit to the logic control unit, wherein the logic control unit is electrically connected to the oscillating inductor of the differential oscillating circuit, wherein the phase-locked loop is electrically connected between the logic control unit and the differential oscillating circuit in a state of being externally disposed or being integrated with the logic control unit, so as to calibrate a frequency of the excitation signal outputted by the differential oscillating circuit in a balanced differential signal form with a difference of 180 ° between both ends of the oscillating inductor based on a feedback of the excitation signal outputted by the logic control unit, thereby ensuring a stable output of the excitation signal in a balanced differential signal form by the differential feeding circuit.
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Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN114624698A (en) * 2022-01-25 2022-06-14 深圳迈睿智能科技有限公司 Microwave detection method and device for micro-emission power

Families Citing this family (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN115314069B (en) * 2022-08-08 2023-10-13 慷智集成电路(上海)有限公司 Full duplex transmitting and receiving circuit, deserializing circuit chip, electronic equipment and vehicle
CN220121002U (en) * 2023-04-16 2023-12-01 深圳迈睿智能科技有限公司 Microwave detection device
CN116315663A (en) * 2023-05-11 2023-06-23 深圳芯盛思技术有限公司 Anti-interference type receiving-transmitting integrated antenna based on differential transmitting and differential receiving mode

Family Cites Families (25)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4727311A (en) * 1986-03-06 1988-02-23 Walker Charles W E Microwave moisture measurement using two microwave signals of different frequency and phase shift determination
US7432772B2 (en) * 2001-06-14 2008-10-07 Telefonaktiebolaget L M Ericsson (Publ) Electrical oscillator circuit and an integrated circuit
JP3660623B2 (en) * 2001-07-05 2005-06-15 株式会社東芝 Antenna device
US7068122B2 (en) * 2004-09-28 2006-06-27 Industrial Technology Research Institute Miniaturized multi-layer balun
CN101471486A (en) * 2007-12-24 2009-07-01 联想（上海）有限公司 An antenna
CN101997515B (en) * 2009-08-31 2012-11-21 深圳市理邦精密仪器股份有限公司 Full-differential same-phase parallel amplifying device for acquiring bioelectric signal
US8089394B2 (en) * 2009-11-02 2012-01-03 Invention Planet, LLC Continuous-wave field disturbance sensing system
CN102522984B (en) * 2011-12-31 2014-02-19 杭州士兰微电子股份有限公司 Phase-locked loop and voltage-controlled oscillating circuit thereof
US8902109B2 (en) * 2012-02-05 2014-12-02 Auden Techno Corp. Communication device
CN104821426B (en) * 2015-03-26 2017-05-10 南京邮电大学 Loop-oscillator combined antenna
US10680465B2 (en) * 2015-09-25 2020-06-09 Samsung Electronics Co., Ltd. Wireless power transmitter
US10129635B1 (en) * 2017-08-08 2018-11-13 Google Llc Antenna for a wearable audio device
CN110398781A (en) * 2019-08-05 2019-11-01 深圳迈睿智能科技有限公司 Anti-interference microwave sounding module and anti-interference method
CN110579759A (en) * 2019-09-06 2019-12-17 深圳迈睿智能科技有限公司 Microwave detector and detection method tending to instant response
CN110824464A (en) * 2019-10-25 2020-02-21 深圳市海纳微传感器技术有限公司 Microwave sensor and intelligent detection device
AU2020411326B2 (en) * 2019-12-24 2024-03-14 Shenzhen Merrytek Technology Co., Ltd Microwave doppler detection module and device
US11749903B2 (en) * 2020-03-03 2023-09-05 Compal Electronics, Inc. Antenna structure
US20230187827A1 (en) * 2020-04-06 2023-06-15 Huawei Technologies Co., Ltd. Dual Mode Antenna Arrangement
CN212729795U (en) * 2020-04-15 2021-03-19 深圳市金安通电子有限公司 Narrow-beam microstrip Doppler radar organism motion detector
CN213520320U (en) * 2020-09-25 2021-06-22 深圳迈睿智能科技有限公司 Reverse-phase double-feed microwave detection module
CN112768908B (en) * 2020-12-29 2021-09-10 南通大学 Integrated structure of differential dielectric resonator antenna and independent controllable dual-passband filter
CN217427078U (en) * 2021-04-27 2022-09-13 深圳迈睿智能科技有限公司 Half-wave reverse-folding directional microwave detection antenna
CN113889751A (en) * 2021-04-27 2022-01-04 深圳迈睿智能科技有限公司 Space staggered type integrated receiving and transmitting separation microwave detection antenna
CN113949380A (en) * 2021-10-26 2022-01-18 南京砺行微电子科技有限公司 Dual-mode fundamental frequency integrated circuit
CN217332842U (en) * 2022-01-25 2022-08-30 深圳迈睿智能科技有限公司 Microwave detection device

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN114624698A (en) * 2022-01-25 2022-06-14 深圳迈睿智能科技有限公司 Microwave detection method and device for micro-emission power

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