CN217820849U - Microwave detection device - Google Patents

Microwave detection device Download PDF

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Publication number
CN217820849U
CN217820849U CN202220769625.4U CN202220769625U CN217820849U CN 217820849 U CN217820849 U CN 217820849U CN 202220769625 U CN202220769625 U CN 202220769625U CN 217820849 U CN217820849 U CN 217820849U
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signal
feeding
antenna
transmitting antenna
microwave
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邹高迪
孙毅
邹新
邹明志
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Shenzhen Merrytek Technology Co Ltd
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Shenzhen Merrytek Technology Co Ltd
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    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
    • G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
    • G01S13/50—Systems of measurement based on relative movement of target
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01N—INVESTIGATING OR ANALYSING MATERIALS BY DETERMINING THEIR CHEMICAL OR PHYSICAL PROPERTIES
    • G01N22/00—Investigating or analysing materials by the use of microwaves or radio waves, i.e. electromagnetic waves with a wavelength of one millimetre or more
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01V—GEOPHYSICS; GRAVITATIONAL MEASUREMENTS; DETECTING MASSES OR OBJECTS; TAGS
    • G01V3/00—Electric or magnetic prospecting or detecting; Measuring magnetic field characteristics of the earth, e.g. declination, deviation
    • G01V3/12—Electric or magnetic prospecting or detecting; Measuring magnetic field characteristics of the earth, e.g. declination, deviation operating with electromagnetic waves
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors

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  • Engineering & Computer Science (AREA)
  • Remote Sensing (AREA)
  • Physics & Mathematics (AREA)
  • Radar, Positioning & Navigation (AREA)
  • General Physics & Mathematics (AREA)
  • Life Sciences & Earth Sciences (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Electromagnetism (AREA)
  • General Life Sciences & Earth Sciences (AREA)
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  • Environmental & Geological Engineering (AREA)
  • Geophysics (AREA)
  • Health & Medical Sciences (AREA)
  • Chemical & Material Sciences (AREA)
  • Analytical Chemistry (AREA)
  • Geology (AREA)
  • General Health & Medical Sciences (AREA)
  • Immunology (AREA)
  • Pathology (AREA)
  • Radar Systems Or Details Thereof (AREA)
  • Waveguide Aerials (AREA)
  • Variable-Direction Aerials And Aerial Arrays (AREA)
  • Geophysics And Detection Of Objects (AREA)

Abstract

The utility model provides a microwave detection device, wherein microwave detection device makes the electromagnetic interference in the environment through from microwave detection device's receiving antenna inserts the echo signal's of balanced differential signal form the mode makes in the environment with the common mode interference form exist and can be in balanced differential signal form echo signal's receipt and transmission in-process restrain the environmental interference, and in the successor based on to balanced differential signal form echo signal and corresponding excitation signal's mixing process output is balanced differential signal form's Doppler intermediate frequency signal, so that the receipt of Doppler intermediate frequency signal guarantees with transmission in-process Doppler intermediate frequency signal's precision to can be in the successor based on right the suppression of common mode interference in the intermediate frequency Doppler signal is handled, at the inception echo signal is the state of differential signal form, further suppresses the electromagnetic interference in the environment and improves Doppler intermediate frequency signal's precision.

Description

Microwave detection device
Technical Field
The utility model relates to a microwave detection field, in particular to microwave detection device based on doppler effect principle.
Background
With the development of the internet of things technology, the requirements of artificial intelligence, smart home and intelligent security technology on environment detection, particularly on detection accuracy of human existence, movement and micro motion characteristics are higher and higher, and accurate judgment basis can be provided for intelligent terminal equipment only by obtaining a stable enough detection result. The microwave detection technology based on the Doppler effect principle is used as a person and an object, and an important junction connected between the object and the object has unique advantages in behavior detection and existence detection technology, can detect moving objects such as action characteristics, movement characteristics and micro-movement characteristics of the person and even heartbeat and respiration characteristic information of the person under the condition of not invading the privacy of the person, and has wide application prospect. Specifically, a microwave detector is fed by an excitation signal to emit a microwave beam with a frequency corresponding to the excitation signal to the target space, so as to form a detection region in the target space, and a reflected echo formed by the microwave beam reflected by a corresponding object in the detection region is received to transmit an echo signal corresponding to the frequency of the reflected echo to a mixer detection unit, wherein the mixer detection unit mixes the excitation signal and the echo signal to output a doppler intermediate frequency signal corresponding to a frequency/phase difference between the excitation signal and the echo signal, wherein based on the doppler effect principle, when the object reflecting the microwave beam is in a moving state, the echo signal and the excitation signal have a certain frequency/phase difference and the doppler intermediate frequency signal exhibits corresponding amplitude fluctuation to feed back human body activity.
In an unlicensed ISM band defined by ITU-R (ITU radio communication Sector) for use by organizations such as industry, science and medicine, frequency bands applied to microwave detection mainly include limited frequency band resources such as 2.4Ghz, 5.8Ghz, 10.525Ghz, 24.125Gh, etc., and a corresponding microwave detector needs to observe a certain transmission power (generally, the transmission power is lower than 1W) to reduce interference to other radio devices when using the frequency bands, although the definition and permission of different frequency bands can standardize the used frequency bands of radio and reduce the probability of mutual interference between radio devices of different frequency bands, under the permission of limited frequency band resources, with the high-speed development of the technology, the radio use coverage rate corresponding to adjacent frequency bands or the same frequency band is increased at a high speed, such as a popular 5G wireless router, or a 5G frequency band added based on a duplex mode on the basis of the original 2.4G wireless router, so that intelligent mutual interference between adjacent frequency bands or the same frequency band is increased, and even the heartbeat is greatly influenced by human beings and people is greatly increased. Therefore, the anti-interference performance is one of the factors that measure the accuracy of the corresponding microwave detection module, and under the circumstance that the problem of mutual interference between radios is becoming serious, the accuracy of the existing microwave detector is difficult to maintain, and not to mention, the requirement of accurate detection of human motion characteristics including breathing motion and even heartbeat motion is satisfied.
Further, since the boundary of the corresponding microwave beam is a gradient boundary with the radiation energy attenuated to a certain degree, it is non-deterministic, and since there is no effective control means for the electromagnetic radiation, i.e. shaping means for the gradient boundary of the corresponding microwave beam, which is mainly reflected in the lack of adjusting means for the beam angle of the microwave beam, the actual detection space covered by the microwave beam emitted by the corresponding microwave detector is difficult to be stably controlled, and further based on the reflection and penetration behavior of the microwave beam in different target detection spaces, the actual detection space of the existing microwave detector cannot be matched with the corresponding target detection space based on the adjustment of the beam angle of the microwave beam independently, such that the problem of poor accuracy and/or interference resistance of the existing microwave detection technology based on the doppler effect principle is caused by the condition that the target detection space outside the actual detection space cannot be effectively detected, and/or the condition that the environment interference exists in the actual detection space outside the target detection space, including the action interference, the electromagnetic interference and the self-excitation interference caused by the environment, the problem that the boundary of the microwave beam is attenuated to a certain degree, while the gradient boundary of the microwave beam is poorly matched with the stability of the actual detection of the microwave detector, and the microwave beam is difficult to be applied in the existing microwave detection scene, and the microwave detector.
In order to solve the above drawbacks, the conventional microwave detector mainly reduces the probability of mutual interference between antennas in the same frequency band by narrowing the frequency bandwidth of the antennas, and increases the amplitude difference of the corresponding effective signal relative to the interference signal in the doppler intermediate frequency signal by increasing the strength of the echo signal, so as to set and reduce the sensitivity of the microwave detection module with the corresponding threshold value of the doppler intermediate frequency signal on the amplitude value, thereby eliminating the environmental interference of the actual detection space outside the target detection space corresponding to the interference signal with a low amplitude value based on the reduction of the sensitivity. On one hand, although the probability of mutual interference between antennas in the same frequency band can be reduced by narrowing the frequency bandwidth of the antennas, based on the difference in the operating principle, antennas for communication use (such as antennas in a wireless router) are often designed to have a wider frequency bandwidth to meet the requirement of multi-channel communication, and narrowing the frequency bandwidth of the antennas for the microwave detector cannot ensure that the antennas for the existing microwave detector are not interfered by the antennas for communication use or do not cause interference to the antennas for communication use in the background that the coverage of radio use in adjacent frequency bands or the same frequency band is rapidly improved; in addition, based on the corresponding relationship between the frequency bandwidth of the antenna and the structural form and size of the antenna, the narrowing of the frequency bandwidth of the antenna of the microwave detector can simultaneously form high-precision requirements on the structure and size of the antenna, and the corresponding high-precision requirements are severer along with the improvement of the resonant frequency point of the antenna, so that additional cost burden is correspondingly generated. On the other hand, since the amplitude of the doppler intermediate frequency signal is related to the energy of the reflected echo and is also related to the size of the reflecting surface area in the environment, the size and the moving speed of the reflecting surface of the moving object and the distance between the microwave detection module, the reduction of the sensitivity of the microwave detector cannot accurately exclude the environmental interference and the motion interference of the actual detection space outside the target detection space, so that the detection of the target detection space is not stable and accurate; in addition, based on the high strength requirement of the existing microwave detector for the echo signal, the range adjustment for the actual detection space tends to have a higher electromagnetic radiation energy density in the target detection space while covering the corresponding target detection space, so that the existing microwave detector cannot avoid interference to the antenna for communication use in the target detection space based on the reduction of the sensitivity, and it is difficult to avoid interference to the antenna for communication use in the target detection space based on the reduction of the sensitivity in pursuit of the antenna for communication use for high signal strength.
SUMMERY OF THE UTILITY MODEL
An object of the utility model is to provide a microwave detection device, wherein microwave detection device's detection method has broken through technical staff in the field and has tended to improve the technical tendency of echo signal's intensity, and the antenna based on communication usage pursues high signal strength's universality, through reducing microwave detection device's transmitting antenna's transmitting power's mode has reduced correspondingly the microwave beam with the signal strength of reflection echo has reduced promptly the microwave beam with the electromagnetic radiation energy density of reflection echo, and then can utilize communication device from the end of taking to make an uproar inhibition mechanism, it is right to avoid causing the interference and can reduce or even remove communication device's in the installation position in corresponding installation environment to corresponding communication device's restriction.
Another object of the present invention is to provide a microwave detecting device, wherein through reducing microwave detecting device's transmitting antenna's transmitted power's mode, the signal strength of microwave beam is reduced, with based on the loss that microwave beam produced to the muddy earth wall of masonry structure or glass's the penetrating action is far greater than the characteristic of propagating produced loss in the space the signal strength of microwave beam is reduced and is the state of weak signal form, utilizes the muddy earth wall of masonry structure or glass who delimits the target detection space to weak signal form the absorption of microwave beam forms to weak signal form the adaptability of the gradient boundary of microwave beam is delimited, corresponds not restricting the state of the space form in target detection space, makes microwave detecting device's the effective detection space that uses muddy earth wall of masonry structure or glass as the boundary can with corresponding target detection space phase-match and improve microwave detecting device is in practical application to the adaptability in different target detection spaces.
Another object of the present invention is to provide a microwave detecting device, wherein the transmitting antenna of the microwave detecting device is reduced in the transmitting power mode, the signal intensity of the microwave beam is reduced and is weak signal form, and then the ratio of the loss generated by the reflection action of the microwave beam to the radiation energy of the microwave beam is increased, so as to avoid the self-excited interference generated by the multiple reflection action.
Another object of the present invention is to provide a microwave detecting device, wherein through reducing microwave detecting device's transmitting antenna's transmitting power's mode, transmitting antenna's immunity is right transmitting antenna's frequency bandwidth's dependency is reduced, and it is right that the correspondence has been reduced transmitting antenna's required precision and be favorable to reducing transmitting antenna's manufacturing cost.
Another object of the present invention is to provide a microwave detecting device, wherein the reduction of the transmitting power of the transmitting antenna of the microwave detecting device is not aimed at adjusting the gradient boundary of the microwave beam in the conventional sense, the transmitting antenna of the microwave detecting device is excited to transmit the state of the microwave beam, based on the coverage space range of the microwave beam and the gain (dBd or dBi) of the transmitting antenna of the microwave detecting device are corresponding and not controlled by the transmitting power of the transmitting antenna, the electromagnetic radiation energy density of the microwave beam in the coverage space is reduced by reducing the transmitting power of the transmitting antenna, so as to improve the ratio of the loss generated by the penetrating action of the microwave beam to the radiation energy of the microwave beam, thereby the signal intensity of the microwave beam is reduced to be in a weak signal form, and the absorption of the microwave beam by using the earth-concrete wall of the masonry structure or the glass defining the target detecting space to form the weak signal form the adaptability of the microwave beam in the microwave detecting device, thereby improving the adaptability of the microwave beam to different target detecting devices.
Another object of the present invention is to provide a microwave detecting device, wherein the reduction of the transmitting power of the transmitting antenna of the microwave detecting device is not aimed at adjusting the gradient boundary of the microwave beam in the conventional sense, the transmitting antenna of the microwave detecting device is excited to transmit the state of the microwave beam, based on the principle that the coverage space range of the microwave beam corresponds to the gain (dBd or dBi) of the transmitting antenna of the microwave detecting device and is not controlled by the transmitting power of the transmitting antenna, the utility model reduces the electromagnetic radiation energy density of the microwave beam in the coverage space thereof to a weak signal form suitable for being suppressed by the corresponding communication device based on the self-contained bottom noise suppression mechanism, thereby breaking through the technical tendency that those skilled in the art tend to improve the strength of the echo signal and tend to have higher electromagnetic radiation energy density in the target detecting space while covering the corresponding target detecting space.
Another object of the present invention is to provide a microwave detecting device, wherein the theory of the transmitting power (dBm) = signal source power (dBm) -transmission line loss (dB) + transmitting antenna gain (dBd or dBi) based on the transmitting antenna of the microwave detecting device is known, and the experimental exploration of the noise suppression mechanism of the communication device in the non-field is known, the utility model discloses a reduce the transmitting power of the transmitting antenna to the mode less than or equal to 0dBm, form the weak signal form of the microwave beam, correspond the electromagnetic radiation energy density of the microwave beam in its coverage space approaches the gradient boundary of the traditional meaning and the electromagnetic radiation energy density outside the gradient boundary, therefore the reduction of the transmitting power of the transmitting antenna of the microwave detecting device is not aimed at adjusting the gradient boundary of the traditional meaning of the microwave beam.
Another object of the present invention is to provide a microwave detecting device, wherein the detecting method of the microwave detecting device includes improving the conversion efficiency of the transmitting antenna, so as to avoid the transmitting antenna cannot complete the initial polarization and cannot transmit correspondingly in the state where its transmitting power is reduced based on the dielectric loss of itself the technical obstacle of the microwave beam corresponds to the guarantee the state of the stable transmission of the microwave beam is reduced the minimum transmitting power extreme value of the transmitting antenna, so as to reduce the state guarantee micro-signal form of the transmitting power of the transmitting antenna to the corresponding target transmitting power the stable transmission of the microwave beam.
Another object of the present invention is to provide a microwave detecting apparatus, wherein the feeding is achieved by phase difference, the circular polarization of the transmitting antenna is reduced the minimum transmitting power extreme value of the transmitting antenna is ensured the stable transmitting state of the microwave beam is reduced the minimum transmitting power extreme value of the transmitting antenna is reduced the stable transmitting of the microwave beam is ensured the state of the transmitting power of the transmitting antenna to the target transmitting power.
Another object of the utility model is to provide a microwave detection device, wherein through the mode of phase difference feed transmitting antenna adopts the linear polarization form transmitting antenna's state, in transmitting antenna's linear polarization direction, it is right to realize transmitting antenna is greater than the differential feed of 90 phase differences, in order to reduce transmitting antenna reduces based on the loss that electric field coupling produced at the initial polarization in-process transmitting antenna's minimum transmitting power extreme value, thereby reducing transmitting antenna's transmitting power to target transmitting power's state, the guarantee transmitting antenna is to the micro-signal form the stable transmission of microwave beam.
Another object of the utility model is to provide a microwave detection device, wherein reduce based on transmitting antenna's self dielectric loss's mode reduces transmitting antenna's minimum transmitting power extremum, microwave detection device adopts half-wave inflection formula directional microwave detection antenna as transmitting antenna, with based on half-wave inflection formula directional microwave detection antenna uses the air to reduce as the structural feature of medium transmitting antenna's self dielectric loss and reduce transmitting antenna's minimum transmitting power extremum, and based on half-wave inflection formula directional microwave detection antenna's high gain characteristic further reduces transmitting antenna's minimum transmitting power extremum, thereby reducing transmitting antenna's transmitting power to less than or equal to 0dBm or lower state guarantee micro-signal form the stable transmission of microwave beam.
Another objective of the present invention is to provide a microwave detecting device, wherein the minimum transmitting power extreme value of the transmitting antenna is reduced based on the manner of reducing the self dielectric loss of the transmitting antenna, the microwave detecting device adopts a double-ended feeding differential antenna as the transmitting antenna, wherein the double-ended feeding differential antenna comprises a reference ground and two strip-shaped oscillators, wherein two ends of the two strip-shaped oscillators, which are connected to the excitation signal, are respectively the feeding ends of the two strip-shaped oscillators, the two strip-shaped oscillators extend from the same lateral space of the reference ground and respectively have a wavelength electrical length greater than or equal to 3/16 and less than or equal to 5/16, wherein the two strip-shaped oscillators respectively have a coupling section, wherein one end of the coupling section, which is close to the feeding end of the strip-shaped oscillator to which the coupling section belongs, is the near end of the coupling section, the two coupling sections extend in the direction opposite to the dislocation direction from the near end and have a dislocation distance which is greater than or equal to lambda/256 and less than or equal to lambda/6, namely, the distance from any point on one coupling section to the other coupling section is greater than or equal to lambda/256 and less than or equal to lambda/6, wherein lambda is a wavelength parameter corresponding to the frequency of the excitation signal, so that the double-ended feed type differential antenna is used as the transmitting antenna in a state that the excitation signals with the difference of more than 90 DEG are accessed to the two feeding ends of the two strip-shaped elements and are fed by the difference of phase, a polarization form tending to linear polarization is realized based on the fact that the coupling between the two strip-shaped elements and the reference ground has the difference of more than 90 DEG, and the coupling between the two coupling sections is formed based on a structural form that the two coupling sections extend in the direction opposite to the dislocation direction from the near end, and a common resonant frequency point is formed based on mutual coupling between the two coupling sections, that is, in a state that the double-ended feed type differential antenna is used for the transmitting antenna to access excitation signals with a phase difference of more than 90 degrees at the two feeding ends of the two strip-shaped oscillators, differential feed to the transmitting antenna is realized in a polarization direction of the transmitting antenna tending to linear polarization, the minimum transmitting power extreme value of the transmitting antenna is reduced in a state of ensuring stable transmission of the microwave beam, and further stable transmission of the microwave beam in a micro-signal form is ensured in a state of reducing the transmitting power of the transmitting antenna to a target transmitting power.
Another object of the present invention is to provide a microwave detecting device, wherein the state of the transmitting antenna is in a linear polarization state the polarization direction of the transmitting antenna is preferably based on the balanced differential feeding that the transmitting antenna tends to 180 ° phase difference, or the dual feed type differential antenna is adopted as the state of the transmitting antenna is preferably based on the balanced differential feeding that the transmitting antenna tends to 180 ° phase difference, and the minimum transmitting power extreme value of the transmitting antenna is reduced in the state of the stable transmission of the microwave beam, so as to reduce the transmitting power of the transmitting antenna to the state of less than or equal to 0dBm or lower to ensure the stable transmission of the microwave beam.
It is another object of the present invention to provide a microwave detecting device, wherein the microwave detecting device includes a differential feed circuit, wherein the differential feed circuit is provided in the form of discrete components and has a three-pole circuit handler provided as an MOS transistor or a triode, an inductor, a first resistor, a second resistor, a third resistor, a first capacitor, a second capacitor, an oscillating capacitor and a power connection terminal adapted to be connected to a corresponding power source, wherein the three-pole circuit handler has a first connection terminal corresponding to a collector electrode of the triode or a drain electrode of the MOS transistor, a second connection terminal corresponding to a base electrode of the triode or a gate electrode of the MOS transistor, and a third connection terminal corresponding to an emitter electrode of the triode or a source electrode of the MOS transistor, wherein one end of the second resistor is electrically connected to the first connection terminal of the three-pole circuit handler, the other end of the second resistor is connected to the power connection terminal via the inductor, and is grounded via the first capacitor, wherein one end of the third resistor is electrically connected to the third connection terminal of the three-pole circuit processor, and the other end of the third resistor is grounded, wherein one end of the oscillating capacitor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the oscillating capacitor is grounded, wherein one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the first resistor is electrically connected between the inductor and the second resistor or to the power connection terminal, wherein two ends of the second capacitor are electrically connected to the first connection terminal and the third connection terminal of the three-pole circuit processor, respectively, the second resistor and the third resistor are set to be equal in resistance value, so that in the state that the differential feed circuit is connected to a corresponding power supply at the power supply connecting end, the excitation signal is output at two ends of the second capacitor in a balanced differential signal form with a phase difference approaching 180 degrees, and therefore phase difference feeding of the transmitting antenna approaching 180 degrees is achieved.
Another object of the present invention is to provide a microwave detecting device, wherein the microwave detecting device includes a differential feeding circuit, wherein the differential feeding circuit is configured in an integrated circuit form and has two opposite phase outputs, so that two opposite phase outputs output balanced differential signals with a phase difference of 180 ° to the excitation signals.
Another object of the present invention is to provide a microwave detecting device, wherein the detecting method of the microwave detecting device further includes improving the step of the accuracy of the echo signal, so that the intensity of the echo signal is based on the state that the transmitting power of the transmitting antenna is reduced, based on the improvement of the accuracy of the echo signal, the microwave detecting device is guaranteed to move the action, the fine motion action with the human body, and the accuracy and the stability of the detection and the detection of the respiration and the heartbeat corresponding movement characteristics.
Another object of the present invention is to provide a microwave detecting device, wherein the step of improving the accuracy of the echo signal comprises accessing the echo signal with a balanced differential signal form from a receiving antenna of the microwave detecting device, so that the electromagnetic interference in the environment exists in a common-mode interference form in the echo signal, thereby being able to be suppressed during the receiving and transmitting of the echo signal with a balanced differential signal form, and in the subsequent step, outputting the doppler intermediate frequency signal with a balanced differential signal form based on the step of mixing the echo signal with a balanced differential signal form, and outputting the intermediate frequency doppler signal with a balanced differential signal form based on the step of mixing the echo signal with a balanced differential signal form and/or the step of differential conversion of the doppler intermediate frequency signal with a balanced differential signal form, outputting the intermediate frequency signal with a balanced differential signal form based on the step of mixing the echo signal with a balanced differential signal form and/or the step of differential conversion of differential signal form to the doppler intermediate frequency signal, thereby improving the accuracy of the step of the echo signal obtained by moving the step of the intermediate frequency signal, and the step of differential signal obtained by mixing the intermediate frequency signal with a balanced differential signal form, and the step of differential signal obtained by mixing the echo signal with a balanced differential signal form, thereby ensuring the accuracy of the microwave detecting device, and the accuracy of the step of the microwave detecting device, wherein the step of the echo signal obtained by the step of the microwave detecting the intermediate frequency signal obtained by the microwave detecting is achieved by the microwave detecting The detection range and the detection accuracy and stability of the micro-motion, the respiration and the heartbeat motion are corresponding to the activity characteristics.
Another object of the present invention is to provide a microwave detecting device, wherein it is right that the improvement step of the accuracy of the echo signal includes from the receiving antenna of the microwave detecting device is accessed to the balanced differential signal form the step of the echo signal, then the electromagnetic interference in the environment is in the echo signal exists in the form of common mode interference, thus can be in the balanced differential signal form the reception and transmission process of the echo signal is suppressed, and in the subsequent, based on the further suppression effect of the common mode interference in the echo signal to the balanced differential signal form of the differential to single-ended processing step of the echo signal, the feedback accuracy of the doppler intermediate frequency signal to the activity characteristics corresponding to the movement, the micro-movement, and the respiration and the heartbeat movement of the human body is improved based on the feedback accuracy of the activity characteristics corresponding to the doppler intermediate frequency signal to the movement, the micro-movement, and the micro-movement of the microwave detecting device based on the above-receiving antenna of the micro-emission power, the stability of the microwave detecting device to the micro-movement, the micro-movement accuracy of the microwave detecting system, the micro-movement and the micro-movement stability of the microwave detecting system.
Another object of the present invention is to provide a microwave detecting device, wherein based on the balanced differential signal form the differential of the doppler intermediate frequency signal changes the further suppression effect of the common mode interference in the doppler intermediate frequency signal to the balanced differential signal form, or based on the balanced differential signal form the differential of the echo signal changes the further suppression effect of the common mode interference in the echo signal to the balanced differential signal form by the differential to single end processing step, the electromagnetic radiation interference of the echo signal common source in the environment is not being existed in the balanced differential signal form with the common mode form in the state that the receiving antenna receives the echo signal and can be effectively suppressed, including in the environment with the electromagnetic radiation interference of the same frequency of the echo signal, so that the feedback accuracy of the doppler intermediate frequency signal to the corresponding moving action, micro-moving action with the human body, and the corresponding moving characteristic of breathing and heart beat action can be improved.
Another object of the present invention is to provide a microwave detecting device, wherein from microwave detecting device's receiving antenna inserts balanced differential signal form echo signal's step includes that two receiving feed points of receiving antenna are inserted balanced differential signal form based on the phase shift step to one of them receiving feed point accessed echo signal's the state of arranging by the quadrature echo signal's echo signal, in order to be based on quadrature form guarantee between two receiving feed points of receiving antenna certainly isolation between two receiving feed point accessed echo signal of receiving antenna corresponds the guarantee based on the balanced differential signal form to one of them receiving feed point accessed echo signal's the phase shift step access echo signal's precision.
Another object of the present invention is to provide a microwave detecting device, wherein the receiving antenna of the microwave detecting device is connected to the balanced differential signal form in the step of the echo signal, two receiving feeding points of the receiving antenna are arranged in opposite phase, so that two receiving feeding points are connected to the balanced differential signal form of the echo signal.
Another object of the present invention is to provide a microwave detecting device, wherein the transmitting antenna and the receiving antenna of the microwave detecting device share the structural configuration of the reference ground is set up to facilitate the miniaturization design of the microwave detecting device.
Another object of the present invention is to provide a microwave detecting device, wherein the transmitting antenna of the microwave detecting device is integrated with the receiving antenna to form a separated receiving and transmitting device, so as to ensure the isolation between the corresponding feeding points (ends) and ensure the accuracy of the echo signal, and facilitate the miniaturization design of the microwave detecting device.
Another object of the present invention is to provide a microwave detecting device, wherein the transmitting antenna and the receiving antenna are integrally disposed in a receiving and transmitting integrated manner, so as to simplify the circuit design of the microwave detecting device and facilitate the miniaturization design of the microwave detecting device.
According to the utility model discloses an aspect, the utility model provides a microwave detection device, microwave detection device includes:
a transmitting antenna, wherein the transmitting antenna is configured to transmit a microwave beam corresponding to a frequency of an excitation signal in a state of being fed by the excitation signal;
a receiving antenna, wherein the receiving antenna is configured in a planar patch antenna configuration and has a ground reference and a radiation source, wherein the radiation source is configured in a state spaced apart from the ground reference, wherein the radiation source is configured in a binary radiation source configuration, and has two radiation elements corresponding to the radiation source, wherein each of the radiation elements has a feeding point, wherein the two radiation elements are arranged in opposite phases, and a connection direction from the feeding point to a physical center point of one of the radiation elements and a connection direction from the feeding point to the physical center point of the other radiation element are opposite to each other, so that, based on a structural state in which the two radiation elements are arranged in opposite phases, an echo signal in a balanced differential signal configuration is output at the two feeding points after receiving a reflected echo formed after the microwave beam is reflected by a corresponding object, the echo signal includes a signal corresponding to a reflected echo formed after the microwave beam is reflected by the corresponding object, and electromagnetic interference in an environment exists in a common mode interference configuration in the echo signal, and can be suppressed in the reception and transmission of the echo signal in the balanced differential signal configuration; and
a mixing circuit, wherein the mixing circuit is configured to output a doppler intermediate frequency signal of a balanced differential signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal based on a mixing process of the excitation signal and the echo signal of the balanced differential signal form in a state of accessing the excitation signal and the echo signal of the balanced differential signal form.
In one embodiment, at least one of the radiating elements is electrically connected to the reference ground at its physical center point.
In an embodiment, the radiating element has at least one group and/or at least one pair of grounding points electrically connected to the reference ground, wherein the same group of grounding points are located at each vertex of the same regular polygon with the physical center point of the radiating element as the midpoint, and the grounding points corresponding to the same group of grounding points are arranged at equal angles around the physical center point of the radiating element in a state of being equidistant from the physical center point of the radiating element, wherein the same pair of grounding points are symmetrically distributed on the radiating element with the physical center point of the radiating element, and the connecting line segment corresponding to the same pair of grounding points forms a zero potential point with the physical center point of the radiating element as the midpoint based on the electrical connection relationship between the grounding points and the reference ground, and is equivalent to the physical center point of the radiating element and the reference ground.
In an embodiment, the transmitting antenna is configured in a planar patch antenna configuration to have a ground reference and a radiation source, wherein the radiation source is configured in a state spaced apart from the ground reference on one side of the ground reference, the radiation source is configured in a binary radiation source configuration, the radiation source has two radiation elements corresponding to the radiation source, each of the radiation elements has a feeding point, the two radiation elements are arranged in an inverted phase, and a connection line direction from the feeding point to a physical center point of one of the radiation elements is opposite to a connection line direction from the feeding point to a physical center point of the other radiation element, so that the two feeding points are connected to an excitation signal to realize feeding of the transmitting antenna.
In an embodiment, the transmitting antenna and the receiving antenna are integrally disposed in a transceiving separated manner based on a structural form sharing the reference ground, the transmitting antenna and the receiving antenna integrally disposed in the transceiving separated manner include one reference ground and one radiation source, the radiation source is disposed in a quaternary radiation source form and has four radiation elements, each radiation element has a feeding point, the radiation elements are circumferentially arranged and satisfy a circumferential arrangement direction of the radiation elements, an included angle between a connecting line between the feeding point and a physical central point of any two adjacent radiation elements is equal to 90 °, two feeding points of two radiation elements opposite to each other in the circumferential arrangement direction of the radiation elements are used as transmitting feeding points, excitation signals are connected to the two feeding points to realize feeding of the transmitting antenna, echo signals in a balanced differential signal form are output from the other two feeding points, and an integral structure of the transmitting antenna and the receiving antenna in the transceiving separated manner is correspondingly formed.
In an embodiment, in the circumferential arrangement direction of the radiation elements, in two opposite radiation elements, a connection line from the feeding point to a physical central point of one of the radiation elements and a connection line from the feeding point to a physical central point of the other radiation element are staggered and opposite, and the feeding point of each radiation element and the connection line of the physical central point thereof intersect to form a regular quadrilateral structure.
In an embodiment, the transmitting antenna and the receiving antenna are integrally provided in a transceiving integrated form based on a structural form that shares the reference ground and the radiation source, the transmitting antenna and the receiving antenna integrally provided in the transceiving integrated form include one reference ground and one radiation source, the radiation source is provided in a binary radiation source form, the radiation source has two radiation elements, each radiation element has one feeding point, the two radiation elements are arranged in an inverted phase, so that an excitation signal is input to the two feeding points to realize feeding of the transmitting antenna, and the echo signal in a balanced differential signal form is output to the two feeding points of the two radiation elements, so as to form an integrated structure of the transmitting antenna and the receiving antenna in the transceiving integrated form.
In an embodiment, the microwave detection device further comprises at least one amplifying circuit adapted to amplify signals in differential signal form, wherein the amplifying circuit is disposed between the receiving antenna and the mixing circuit to amplify the echo signals in balanced differential signal form output to the mixing circuit.
In an embodiment, the microwave detection device further comprises another amplifying circuit adapted to amplify a signal in the form of a differential signal, wherein the amplifying circuit is configured to be connected to the mixing circuit to amplify the doppler intermediate frequency signal in the form of an output balanced differential signal.
In an embodiment, the microwave detection device further comprises at least one amplifying circuit adapted to amplify a signal in the form of a balanced differential signal, wherein the amplifying circuit is arranged to be connected to the mixing circuit to amplify the doppler intermediate frequency signal in the form of an output balanced differential signal.
Drawings
Fig. 1A is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to an embodiment of the present invention.
Fig. 1B is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 1C is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 2A is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 2B is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 3A is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 3B is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4A is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4B is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4C is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4D is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4E is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4F is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4G is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4H is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4I is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4J is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4K is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4L is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4M is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 4N is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 5A is a schematic structural diagram of a differential feed circuit of a microwave detection device according to an embodiment of the present invention.
Fig. 5B is a schematic structural diagram of a differential feed circuit of a microwave detecting device according to another embodiment of the present invention.
Fig. 6 is a schematic structural diagram of a differential oscillation circuit of a microwave detection device according to an embodiment of the present invention.
Fig. 7A is a schematic structural diagram of a microwave detection device according to an embodiment of the present invention.
Fig. 7B is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention.
Fig. 7C is a schematic structural diagram of a microwave detection device according to another embodiment of the present invention.
Fig. 7D is a schematic structural diagram of a microwave detection device according to another embodiment of the present invention.
Fig. 8A is a schematic structural diagram of a receiving antenna of a microwave detecting device according to an embodiment of the present invention.
Fig. 8B is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 8C is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 8D is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 9A is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 9B is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 9C is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 9D is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 9E is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.
Fig. 10A is a schematic structural diagram of a microwave detecting device according to an embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Fig. 10B is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Fig. 10C is a schematic structural diagram illustrating a transmitting antenna and a receiving antenna of a microwave detecting device according to another embodiment of the present invention are integrally disposed.
Fig. 10D is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Fig. 10E is a schematic structural diagram illustrating a transmitting antenna and a receiving antenna of a microwave detecting device according to another embodiment of the present invention are integrally disposed.
Fig. 10F is a schematic structural diagram illustrating a transmitting antenna and a receiving antenna of a microwave detecting device according to another embodiment of the present invention are integrally disposed.
Fig. 10G is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Fig. 10H is a schematic structural diagram illustrating a transmitting antenna and a receiving antenna of a microwave detecting device according to another embodiment of the present invention are integrally disposed.
Fig. 10I is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.
Fig. 10J is a schematic structural diagram illustrating a transmitting antenna and a receiving antenna of a microwave detecting device according to another embodiment of the present invention being integrally disposed.
Detailed Description
The following description is presented to disclose the invention so as to enable any person skilled in the art to practice the invention. The preferred embodiments in the following description are given by way of example only, and other obvious variations will occur to those skilled in the art. The basic principles of the invention, as defined in the following description, may be applied to other embodiments, variations, modifications, equivalents and other technical solutions without departing from the spirit and scope of the invention.
It will be understood by those skilled in the art that in the present disclosure, the terms "longitudinal," "lateral," "upper," "lower," "front," "rear," "left," "right," "vertical," "horizontal," "top," "bottom," "inner," "outer," and the like are used in a generic and descriptive sense only and not for purposes of limitation, as the terms are used in the description to indicate that the referenced device or element must have the specified orientation, be constructed and operated in the specified orientation, and not for the purposes of limitation.
It is understood that the terms "a" and "an" should be interpreted as meaning that a number of one element or element is one in one embodiment, while a number of other elements is one in another embodiment, and the terms "a" and "an" should not be interpreted as limiting the number.
The utility model provides a microwave detection method and device, wherein microwave detection method has broken through the technical tendency that technical staff in the field tends to improve corresponding echo signal's intensity, and antenna based on communication usage pursues high signal strength's universality, through reducing microwave detection device's transmitting antenna's transmitting power's mode has reduced correspondingly the signal strength of microwave beam and reflection echo has reduced promptly the microwave beam with the electromagnetic radiation energy density of reflection echo, and then can utilize communication device from the end suppression mechanism of making an uproar, it is right to avoid causing the interference and can reduce or even remove communication device's in the installing environment the mounted position of microwave detection device in corresponding installing environment restriction.
The transmitting power of the transmitting antenna of the microwave detection device is reduced, the signal intensity corresponding to the microwave beam is reduced and the microwave beam is in a weak signal form, and the corresponding communication device in the environment can resist the interference of the microwave detection device based on a self-contained bottom noise suppression mechanism, so that the influence of the frequency bandwidth of the transmitting antenna of the microwave detection device is reduced for the interference capability of the microwave detection device on the corresponding communication device, namely the dependence of the immunity of the transmitting antenna on the narrowed frequency bandwidth is reduced, the precision requirement on the transmitting antenna is correspondingly reduced, and the production cost of the transmitting antenna is favorably reduced.
Meanwhile, because the signal intensity of the microwave beam is reduced, based on the characteristic that the loss generated by the penetration behavior of the microwave beam to the concrete wall or the glass of the masonry structure is far larger than the loss generated by the propagation in the space, when the signal intensity of the microwave beam is reduced to be in a weak signal form, the microwave beam is absorbed by the concrete wall or the glass of the masonry structure defining the target detection space, namely, the adaptive definition of the gradient boundary of the microwave beam in the weak signal form can be formed, and the state of the spatial form of the target detection space is not limited correspondingly, so that the effective detection space of the microwave detection device with the concrete wall or the glass of the masonry structure as the boundary can be matched with the corresponding target detection space, thereby improving the adaptability of the microwave detection device to different target detection spaces in practical application.
Further, since the signal intensity of the microwave beam is reduced to be in a weak signal form, the ratio of the loss generated based on the reflection behavior of the microwave beam to the radiation energy of the microwave beam is increased, so that the self-excited interference generated based on the multiple reflection behavior can be avoided.
That is, the transmitting power of the transmitting antenna of the microwave detecting device is reduced, the signal strength of the corresponding microwave beam is reduced and the corresponding echo signal is in a weak signal form, and the intensity of the corresponding echo signal is reduced, so the microwave detecting method breaks through the technical trend that a person skilled in the art tends to improve the intensity of the corresponding echo signal and tends to have higher electromagnetic radiation energy density in the target detecting space while the microwave beam covers the corresponding target detecting space, wherein the reduction of the transmitting power of the transmitting antenna of the microwave detecting device is not aimed at adjusting the traditionally-significant gradient boundary of the microwave beam, but is in a state that the transmitting antenna of the microwave detecting device is excited to transmit the microwave beam, based on the principle that the coverage space range of the microwave beam corresponds to the gain (dBd or dBi) of the transmitting antenna of the microwave detection device and is not controlled by the transmitting power of the transmitting antenna, the electromagnetic radiation energy density of the microwave beam in the coverage space of the microwave beam is reduced to a weak signal form which is suitable for being suppressed by a corresponding communication device based on an own bottom noise suppression mechanism, so that the interference on the corresponding communication device is avoided, the ratio of the loss generated by the penetrating action of the microwave beam to the radiation energy of the microwave beam is improved, and the absorption of the microwave beam of the weak signal form by a concrete wall or glass of a masonry structure defining the target detection space can be utilized to form the adaptive definition of the gradient boundary of the microwave beam of the weak signal form by the concrete wall or glass of the masonry structure, correspondingly, the adaptability of the microwave detection device to different target detection spaces in practical application is improved.
Further, based on the theoretical knowledge that the transmit power (dBm) = signal source power (dBm) -transmission line loss (dB) + transmit antenna gain (dBd or dBi) of a transmit antenna of the microwave detection apparatus, and the experimental insight into the floor noise suppression mechanism of communication apparatuses not in the art, the microwave detection method may be characterized in particular by feeding the transmit antenna with a feed power of less than 1mW, preferably by reducing the transmit power of the transmit antenna to a target transmit power of 0dBm or less, such as by reducing the transmit power of the transmit antenna to a target transmit power of-3 dBm or-6 dBm, to form a weak signal morphology of the microwave beam corresponding to an electromagnetic radiation energy density of the microwave beam in its coverage space approaching a conventionally significant gradient boundary and an electromagnetic radiation energy density outside the gradient boundary, thus reducing the transmit power of the transmit antenna of the microwave detection apparatus is not aimed at adjusting the conventionally significant gradient boundary of the microwave beam.
It can be understood that, due to the existence of the dielectric loss of the transmitting antenna itself, the conversion efficiency of the transmitting antenna may not reach 100%, and correspondingly, in the process that the transmitting power of the transmitting antenna is reduced, the transmitting antenna may not transmit the corresponding microwave beam when the transmitting power of the transmitting antenna is not reduced to the target transmitting power, that is, the initial polarization process cannot be completed based on the dielectric loss of the transmitting antenna itself. That is to say, the minimum transmitting power capable of guaranteeing the stable transmission of the microwave beam is taken as the minimum transmitting power extreme value of the transmitting antenna, and in the state that the minimum transmitting power extreme value of the transmitting antenna is less than 0dBm, the specific type and structural form of the transmitting antenna are not limited, but based on the medium loss of the transmitting antenna, the transmitting antenna has a technical obstacle that the minimum transmitting power extreme value of the transmitting antenna may be greater than the target transmitting power and cannot be further reduced in the state of guaranteeing the stable transmission of the microwave beam. Based on this, the utility model discloses a microwave detection method still includes the improvement transmitting antenna's conversion efficiency's method step, in order to avoid transmitting antenna can't accomplish initial polarization and can't transmit correspondingly in its transmit power reduced state based on the dielectric loss of self the technical barrier of microwave beam corresponds the guarantee the state of the stable transmission of microwave beam reduces transmitting antenna's minimum transmit power extreme value, with reducing transmitting antenna's transmit power to the state guarantee micro-signal form the stable transmission of microwave beam.
Specifically, in the method step of improving the conversion efficiency of the transmitting antenna, the circularly polarized form of the transmitting antenna is realized by the phase difference feeding to reduce the minimum transmitting power extreme value of the transmitting antenna, or the differential feeding with a phase difference larger than 90 ° is realized in the linear polarization direction of the transmitting antenna in the state that the transmitting antenna adopts the linearly polarized form of the transmitting antenna, so as to reduce the loss of the transmitting antenna generated based on the electric field coupling effect in the initial polarization process to reduce the minimum transmitting power extreme value of the transmitting antenna, thereby ensuring the stable transmission of the microwave beam in the form of a micro signal by the transmitting antenna in the state of reducing the transmitting power of the transmitting antenna to the target transmitting power.
Accordingly, referring to fig. 1A to 1C of the drawings accompanying the present invention, various embodiments of the transmitting antenna 10 for implementing a circular polarization mode based on a phase difference feeding mode are illustrated, wherein the transmitting antenna 10 is exemplified by a planar patch antenna configuration having a reference ground 11 and a radiation source 12, and wherein the radiation source 12 is disposed on a side of the reference ground 11 in a spaced state from the reference ground 11.
Corresponding to fig. 1A and 1B, the radiation source 12 is configured as a unit radiation source, and corresponding to the radiation source 12, the radiation element 12 has a single number of radiation elements 121, wherein corresponding to fig. 1A, the radiation element 121 has two feeding points 1211, wherein the two feeding points 1211 are orthogonally arranged, and connecting lines between the two feeding points 1211 and a physical central point 1212 of the radiation element 121 are perpendicular to each other, so that excitation signals with 90 ° difference are accessed to the two feeding points 1211 of the radiation element 121 by means of phase difference feeding to realize a circular polarization configuration of the transmitting antenna 10; corresponding to fig. 1B, the radiation element 121 has at least three feeding points 1211, wherein each of the feeding points 1211 is equidistantly arranged around the physical center point 1212 of the radiation element 121 in a state of being at the same distance from the physical center point 1212 of the radiation element 121, an angle between a connection line between any two adjacent feeding points 1211 and the physical center point 1212 of the radiation element 121 in a direction around the physical center point 1212 of the radiation element 121 is equal to 360 °/n, where n is the number of the feeding points 1211 of the radiation element 121, such that in a direction around the physical center point 1212 of the radiation element 121, an excitation signal with a difference of 360 °/n is sequentially inputted at the feeding points 1211 of the radiation element 121 to achieve a circular polarization state of the radiation antenna 10, in particular, in the radiation antenna 10 illustrated in fig. 1B, the number of the feeding points 1211 of the radiation element 121 is 4, in a direction around the physical center point 1212 of the radiation element 121, in a state of sequentially inputting an excitation signal with a difference of 360 °/n to achieve a circular polarization state, in a direction around the physical center point 1212 of the radiation element 121, in a state of 90 °, and in a connection line between any two adjacent feeding points 1211 and the physical center point 1212 of the radiation element 121, in a state of the radiation element 121, in a phase, in a state of the direction around the radiation element 90 ° is sequentially connected to achieve a phase-polarized signal in a phase-polarized state of the radiation element 121.
Corresponding to fig. 1C, the radiation source 12 is disposed in a multi-element radiation source configuration, and at least three radiation elements 121 are disposed corresponding to the radiation source 12, wherein each radiation element 121 has a feeding point 1211, and each radiation element 121 is circumferentially arranged such that, in a circumferential arrangement direction of the radiation elements 121, an angle between a connecting line between the feeding point 1211 and a physical central point 1212 of any two adjacent radiation elements 121 is equal to 360 °/m, where m is the number of the radiation elements 121, so that excitation signals with a difference of 360 °/m are sequentially connected to the feeding point 1211 of each radiation element 121 in the circumferential arrangement direction of the radiation elements 121 in a phase-difference feeding manner to achieve a circular polarization configuration of the transmitting antenna 10. Preferably, each of the radiation elements 121 further satisfies that, while an angle between a connecting line between the feeding point 1211 and a physical center point 1212 of any two adjacent radiation elements 121 is equal to 360 °/m in the circumferential arrangement direction of the radiation elements 121, a connecting line between the feeding point 1211 and a physical center point 1212 of each of the radiation elements 121 intersects at a point, and a distance between the feeding point 1211 and the physical center point 1212 of each of the radiation elements 121 is the same, or satisfies that a connecting line between the feeding point 1211 and a physical center point 1212 of each of the radiation elements 121 intersects to form a regular polygon corresponding to the number of the radiation elements 121, and a distance between the feeding point 1211 and a center point 1212 of each of the radiation elements 121 is the same, in particular, in the transmitting antenna 10 illustrated in fig. 1C, the number of the radiation elements 121 is four, corresponding to the circumferential arrangement direction of the radiation elements 121, an angle between the feeding point 1211 and a connecting line between the physical center point 1211 and a physical center point 1212 of any two adjacent radiation elements 121 is equal to 90, and an angle between the feeding point 1211 and a connecting line between the physical center point 1212 of each of the radiation element 121 intersects at the same distance between the feeding point 1211 and the physical center point 1212 of each of the radiation element 121, and the positive quadrilateral, and the positive feeding point 121 intersect at the same distance. In this way, the circular polarization form of the transmitting antenna 10 is realized in a manner of being based on phase difference feeding, and the stability of the circular polarization form of the transmitting antenna 10 is guaranteed.
It is worth mentioning that, in the embodiments of the present invention, based on the difference of the feeding structure of the radiation element 121, the definition of the position corresponding to the feeding point 1211 is different, specifically, in the state of the feeding structure in which the radiation element 121 adopts probe feeding or microstrip feeding (including microstrip angle feeding), the feeding point 1211 corresponds to the point on the radiation element 121 where the feeding signal (including the excitation signal) is accessed, and in the state of the feeding structure in which the radiation element 121 adopts edge feeding, the feeding point 1211 corresponds to the middle point of the edge on the radiation element 121 where the feeding signal (including the excitation signal) is accessed based on the coupling effect, and in the description of the present invention, in the state in which the transmitting antenna 10 is set in the planar patch antenna state, the description of the feeding point 1211 does not constitute a limitation of the feeding structure corresponding to the radiation element 121.
Furthermore, in some embodiments of the present invention, when the transmitting antenna 10 is configured in a planar patch antenna configuration, the same two feeding points 1211 connected to the same phase excitation signal on the radiating element 121, the central line of the connection line of the two feeding points 1211 passes through the structural state of the physical central point 1212 of the radiating element 121, which is equivalent to the feeding point 1211 at the central point of the connection line of the two feeding points 1211 in the description of the present invention, which is not limited by the present invention.
Preferably, in these embodiments of the present invention, the radiating element 121 is further configured to be directly and/or equivalently grounded at its physical center point 1212, and the radiating element 121 is configured to be directly grounded at its physical center point 1212, specifically based on the electrical connection between the radiating element 121 and the ground reference 11, and the radiating element 121 is configured to be equivalently grounded at its physical center point 1212, based on the electrical connection between at least one set and/or at least one pair of ground points on the radiating element 121 and the ground reference 11, wherein the same set of ground points are located at each vertex of a same regular polygon with the physical center point 1212 of the radiating element 121 as a midpoint, and the ground points in the same set are arranged at equal angles around the physical center point 1212 of the radiating element 121 with a state equidistant from the physical center point 1212 of the radiating element 121, wherein the same pair of ground points are symmetrically distributed around the physical center point 1212 of the radiating element 121 with the physical center point 1212 of the radiating element 121, and the line segment connecting the radiating element 121 with the physical center point 1212 as the radiating element 1212 as a pair of the radiating element 121, and the ground points 1212 as the radiating element are symmetrically distributed around the physical center point 1212 as the radiating element 121, thereby increasing the radiating element 10 and the radiating element antenna.
Further, referring to fig. 2A and 2B of the drawings of the present disclosure, different embodiments of implementing differential feeding for the transmitting antenna 10 with a phase difference greater than 90 ° in the linear polarization direction of the transmitting antenna 10 based on a phase difference feeding mode in a state that the transmitting antenna 10 adopts a linear polarization state are illustrated, wherein the transmitting antenna 10 is disposed in a planar patch antenna state and has a reference ground 11 and a radiation source 12, and wherein the radiation source 12 is disposed at one side of the reference ground 11 in a state spaced apart from the reference ground 11.
Corresponding to fig. 2A, the radiation source 12 is configured as a unit radiation source, and the radiation source 12 has a single number of radiation elements 121, wherein the radiation element 121 has two feeding points 1211, wherein the two feeding points 1211 are arranged in opposite phase, and a connection direction corresponding to one of the feeding points 1211 to a physical central point 1212 of the radiation element 121 coincides with a connection direction corresponding to the other of the feeding points 1211 to a physical central point 1212 of the radiation element 121, then the radiation element 121 has a polarization form of linear polarization in a state that the feeding points 1211 access an excitation signal and takes the connection direction of the two feeding points 1211 as the linear polarization direction, so that differential feeding to the transmission antenna 10 is realized in a state that the two feeding points 1211 access excitation signals with a phase difference larger than 90 ° in the linear polarization direction of the transmission antenna 10 by means of phase difference feeding, so as to reduce a minimum transmission power extreme value of the transmission antenna 10 based on a loss generated by an electric field coupling effect during initial polarization, thereby reducing the transmission power of the transmission antenna 10 to a transmission state, and ensuring stable microwave transmission beam of the transmission antenna 10.
Preferably, in this embodiment of the present invention, the two feeding points 1211 of the radiating element 121 are arranged symmetrically with respect to the physical center point 1212 of the radiating element 121, so that in a manner of feeding by phase difference, in a state that the two feeding points 1211 of the radiating element 121 access excitation signals with phase difference approaching 180 °, a balanced differential feeding to the transmitting antenna 10 is realized in the linear polarization direction of the transmitting antenna 10, so as to further reduce the loss generated by the transmitting antenna 10 based on the electric field coupling effect during the initial polarization process, so as to reduce the minimum transmitting power extreme value of the transmitting antenna 10, thereby ensuring stable transmission of the microwave beam in the form of micro-signal by the transmitting antenna 10 in a state of reducing the transmitting power of the transmitting antenna 10 to the target transmitting power.
Corresponding to fig. 2B, the radiation source 12 is configured as a binary radiation source, and the radiation source 12 has two radiation elements 121, wherein each of the radiation elements 121 has a feeding point 1211, wherein the two radiation elements 121 are arranged in opposite phase, and a connection direction of the feeding point 1211 of one of the radiation elements 121 to a physical central point 1212 is opposite to a connection direction of the feeding point 1211 of the other radiation element 121 to a physical central point, so that the two radiation elements 121 have a linearly polarized polarization state in a state where the two feeding points 1211 access an excitation signal, and a connection direction of the two feeding points 1211 is a linearly polarized direction, so that by means of phase-difference feeding, a differential feeding to the transmission antenna 10 is realized in a state where the two feeding points 1211 of the two radiation elements 121 access excitation signals with a phase difference of more than 90 ° in the linear polarization direction of the transmission antenna 10, so as to reduce a minimum transmission power extremum of the transmission antenna 10 based on a loss generated by an electric field coupling effect during an initial polarization process, thereby reducing the power of the transmission antenna 10 to a transmission power of a target transmission antenna 10, and ensuring a stable microwave beam of the transmission antenna 10.
Preferably, in this embodiment of the present invention, two of the radiating elements 121 are arranged in a mirror image, so as to implement a balanced differential feeding to the transmitting antenna 10 in the linear polarization direction of the transmitting antenna 10 in a manner of feeding by phase difference in a state that two of the feeding points 1211 of the radiating elements 121 access excitation signals with phase difference approaching 180 °, so as to further reduce the loss generated by the transmitting antenna 10 based on the electric field coupling effect during the initial polarization process, thereby reducing the minimum transmitting power extreme value of the transmitting antenna 10, and thus ensuring stable transmission of the microwave beam in the form of micro-signals by the transmitting antenna 10 in a state of reducing the transmitting power of the transmitting antenna 10 to the target transmitting power.
It is also worth mentioning that, in the two embodiments of the present invention, based on the difference of the feeding structure of the radiating element 121, the definition of the position of the corresponding feeding point 1211 is different, specifically, in the state of the feeding structure in which the radiating element 121 adopts probe feeding or microstrip feeding (including microstrip angle feeding), the feeding point 1211 corresponds to the point on the radiating element 121 where the feeding signal (including the excitation signal) is accessed, and in the state of the feeding structure in which the radiating element 121 adopts edge feeding, the feeding point 1211 corresponds to the middle point of the edge on the radiating element 121 where the feeding signal (including the excitation signal) is accessed based on the coupling effect, and in the description of the present invention, in the state in which the transmitting antenna 10 is set in the planar patch antenna state, the description of the feeding point 1211 does not constitute a limitation on the feeding structure of the corresponding radiating element 121.
Furthermore, in some embodiments of the present invention, when the transmitting antenna 10 is configured in a planar patch antenna configuration, the same two feeding points 1211 connected to the same phase excitation signal on the radiating element 121 pass through a central line of a line of the two feeding points 1211 through a structural state of a physical central point 1212 of the radiating element 121, which is equivalent to the two feeding points 1211 at a central point of a line of the two feeding points 1211 in the description of the present invention, which is not limited by the present invention.
Preferably, in the embodiments of the present invention, the radiating element 121 is further disposed directly and/or equivalently at the physical center point 1212 thereof, and the structural state in which the radiating element 121 is disposed directly at the physical center point 1212 thereof is formed based on the electrical connection between the radiating element 121 at the physical center point 1212 thereof and the reference ground 11, and the structural state in which the radiating element 121 is disposed equivalently at the physical center point 1212 thereof is formed based on the electrical connection between the at least one group and/or at least one pair of ground points on the radiating element 121, wherein the same group of ground points are located at respective vertices of a same regular polygon with the physical center point 1212 of the radiating element 121 as a midpoint, and the ground points are arranged equiangularly around the physical center point 1212 of the radiating element 121 in a state equidistant from the physical center point 1212 of the radiating element 121 corresponding to each ground point in the same group, wherein the same pair of ground points are symmetrically distributed around the physical center point 1212 of the radiating element 121 with the physical center point 1212 of the radiating element 121, and the corresponding line segment of the radiating element 121 as the ground points are symmetrically distributed around the physical center point 1212 of the radiating element 121, and the ground points as the ground points 1212 as the antenna, thereby increasing the impedance of the antenna 10 and reducing the requirements for the antenna 10.
Further, the minimum transmitting power extremum of the transmitting antenna 10 is reduced based on a manner of reducing the self dielectric loss of the transmitting antenna 10, the microwave detecting device adopts a half-wave folded-back directional microwave detecting antenna as the transmitting antenna 10, reduces the self dielectric loss of the transmitting antenna 10 based on the structural characteristic that the half-wave folded-back directional microwave detecting antenna uses air as a medium to reduce the minimum transmitting power extremum of the transmitting antenna 10, and further reduces the minimum transmitting power extremum of the transmitting antenna 10 based on the high gain characteristic of the half-wave folded-back directional microwave detecting antenna, thereby ensuring stable transmission of the microwave beam in the form of the micro-signal in a state of reducing the transmitting power of the transmitting antenna 10 to the target transmitting power.
Referring to fig. 3A and 3B of the drawings of the present invention, the structures of the half-wave folded directional microwave detecting antenna 10A in the vertical structure and the horizontal structure are illustrated respectively.
Corresponding to fig. 3A, the half-wave folded directional microwave detecting antenna 10A of a vertical structure includes a reference ground 11A, a half-wave vibrator 12A and two power feeding lines 13A, wherein the half-wave vibrator 12A has a wavelength electrical length of 1/2 or more and 3/4 or less and has two coupling sections 121A, wherein each of the coupling sections 121A has a wavelength electrical length of 1/6 or more, one end of each of the coupling sections 121A is a feeding end 1211A of the coupling section 121A, and the other ends of the coupling sections 121A are both ends of the half-wave vibrator 12A, wherein a distance between the feeding ends 1211A is equal to or less than λ/4, a distance between both ends of the half-wave vibrator 12A is equal to or more than λ/128 and equal to or less than λ/6, so as to respectively access two poles of an excitation signal or an excitation signal with a phase difference to both ends 1211A of the half-wave vibrator 12A at both feeding ends 1211A to be fed, the two ends of the half-wave vibrator 12A can be coupled to each other with a phase difference, wherein λ is a wavelength parameter corresponding to a frequency of the excitation signal; wherein the half-wave vibrator 12A is spaced from the reference ground 11A in a state where a distance between both ends thereof and the reference ground 11A is λ/128 or more and λ/6 or less; the two feeder lines 13A are electrically connected to the corresponding feed ends 1211A, respectively, so that the half-wave oscillator 12A is fed by the feed ends 1211A of the half-wave oscillator 12A in a state where the two feeder lines 13A are electrically coupled to the corresponding feed circuits to access two poles of an excitation signal or access an excitation signal having a phase difference, and the half-wave oscillator 12A is spaced from the reference ground 11A by the electrical connection of the feeder lines 13A and the feed ends 1211A.
Corresponding to fig. 3B, the half-wave folded directional microwave detecting antenna 10A of the horizontal structure includes a ground reference 11A, a half-wave vibrator 12A and a feeding line 13A, wherein the half-wave vibrator 12A has a wavelength electrical length of 1/2 or more and 3/4 or less, wherein the half-wave vibrator 12A is folded back to form a state where a distance between both ends thereof is λ/128 or more and λ/6 or less, wherein the half-wave vibrator 12A has a feeding point 121A, the feeding point 121A has a wavelength electrical length of 1/6 or less along the half-wave vibrator 12A between one end thereof and the feeding point 121A to form a state where the half-wave vibrator 12A is fed with a corresponding excitation signal being connected to the feeding point 121A, both ends of the half-wave vibrator 12A can be coupled to each other with a phase difference tending to be in opposite phase, wherein λ is a wavelength parameter corresponding to a frequency of the excitation signal; wherein the half-wave vibrator 12A is spaced from the reference ground 11A in a state where a distance between both ends thereof and the reference ground 11A is equal to or greater than λ/128, and a distance between at least one end thereof and the reference ground 11A is equal to or less than λ/6; one end of the feeding line 13A is electrically connected to the feeding point 121A of the half-wave vibrator 12A, wherein the feeding line 13A has an electrical length of 1/128 wavelength or more and 1/4 wavelength or less, so that when the feeding line 13A is electrically coupled to a corresponding feeding circuit at the other end thereof to receive the excitation signal, the half-wave vibrator 12A is fed at the feeding point 121A of the half-wave vibrator 12A in a state where the feeding point is electrically connected to the half-wave vibrator 12A via the feeding line 13A and the half-wave vibrator 12A is spaced apart from the ground reference 11A.
Further, refer to the utility model discloses a figure 4A to figure 4N of the description drawings are shown, based on reducing the mode of transmitting antenna 10's self dielectric loss, the combination is in order to right transmitting antenna 10's difference feed reduces transmitting antenna 10's minimum transmit power extreme value, the utility model discloses a further provide a double feed formula difference antenna 10B, with microwave detection device adopts double feed formula difference antenna 10B regards as transmitting antenna 10's state reduces transmitting antenna 10's minimum transmit power extreme value, with reducing transmitting antenna 10's transmit power to the state guarantee micro-signal form of target transmit power the stable transmission of microwave beam.
Corresponding to fig. 4A to 4N, the dual feed type differential antenna includes a reference ground 11B and two strip-shaped elements 12B, wherein two ends of the two strip-shaped elements 12B connected to excitation signals are respectively the feeding ends 121B of the two strip-shaped elements 12B, the two strip-shaped elements 12B extend from the two feeding ends 121B in the same lateral space of the reference ground 11B and respectively have a wavelength electrical length of 3/16 or more and 5/16 or less, wherein the two strip-shaped elements 12B respectively have a coupling section 122B, wherein one end of the coupling section 122B close to the feeding end 121B of the strip-shaped element 12B to which the coupling section belongs is a proximal end of the coupling section 122B, and the two coupling sections 122B extend from the proximal end in opposite directions, so that the dual feed type differential antenna 10B is used as the transmitting antenna 10 in a feeding state where two feeding ends 121B of the two strip-shaped elements 12B are connected to excitation signals with a phase difference of more than 90 ° and are different from each other, based on the fact that the coupling between the two strip-shaped oscillators 12B and the reference ground 11B has a polarization form with a phase difference larger than 90 degrees to realize a trend of linear polarization, and based on the fact that the two coupling sections 122B extend from the near end in opposite directions to form the coupling between the two coupling sections 122B, and based on the mutual coupling between the two coupling sections 122B, a common resonance frequency point is formed, that is, in a state that the double-ended feeding type differential antenna 10B is used as the transmitting antenna 10 and excitation signals with a phase difference larger than 90 degrees are accessed to the two feeding ends 121B of the two strip-shaped oscillators 12B, differential feeding to the transmitting antenna 10 is realized in the polarization direction of the transmitting antenna 10 which tends to linear polarization, and the minimum transmitting power extreme value of the transmitting antenna 10 is reduced in a state of ensuring stable transmission of the microwave beam, and further, the stable transmission of the microwave beam in the form of a micro signal is ensured in a state of reducing the transmission power of the transmitting antenna 10 to the target transmission power.
Specifically, corresponding to fig. 4A, two strip-shaped oscillators 12B extend from two feeding terminals 121B in the same lateral space sequence of the reference ground 11B in the direction vertically away from the reference ground 11B, and extend toward each other at a position equidistant from the reference ground 11B to form the proximal ends of two coupling sections 122B at that position.
Corresponding to fig. 4B, two of the strip-shaped oscillators 12B extend from two of the feeding terminals 121B in the same lateral spatial order of the reference ground 11B in a direction vertically away from the reference ground 11B, extend toward each other at a position equidistant from the reference ground 11B to form the coupling section 122B, and extend in a direction vertically close to the reference ground 11B.
Corresponding to fig. 4C to 4N, the two coupling sections 122B extend from the proximal end in the opposite direction of the offset, and have an offset distance greater than or equal to λ/256 and less than or equal to λ/6, that is, the distance from any point on one of the coupling sections 122B to the other coupling section 122B is greater than or equal to λ/256 and less than or equal to λ/6, where λ is a wavelength parameter corresponding to the frequency of the excitation signal.
Specifically, corresponding to fig. 4C to 4L, the two coupling sections 122B of the two strip-shaped oscillators 12B extend from the proximal ends toward each other in a mutually parallel offset direction.
Corresponding to fig. 4C, the two strip-shaped oscillators 12B extend in the direction vertically away from the reference ground 11B in sequence from the two feeding terminals 121B in the same lateral space of the reference ground 11B, and extend in opposite directions parallel to each other at positions equidistant from the reference ground 11B, so as to form the proximal ends of the two coupling sections 122B at the positions.
Corresponding to fig. 4D, two of the strip-shaped oscillators 12B extend in the same lateral spatial sequence of the reference ground 11B from the two feeding terminals 121B in the direction vertically away from the reference ground 11B, extend in opposite directions at positions equidistant from the reference ground 11B in parallel offset directions to form the coupling sections 122B, and extend in the direction vertically close to the reference ground 11B.
Corresponding to fig. 4E, on the basis of the structure of the dual feed differential antenna illustrated in fig. 4D, one of the coupling sections 122B is electrically connected to the middle of the other coupling section 122B.
Corresponding to fig. 4F, the coupling segment 122B has a variation in cross-sectional area in the cross-sectional direction of the strip-shaped element 12B, based on the structure of the double-feed differential antenna illustrated in fig. 4D.
Corresponding to fig. 4G, two of the strip-shaped oscillators 12B extend in the direction perpendicular to and away from the reference ground 11B from the two feeding terminals 121B in the same lateral spatial order of the reference ground 11B, extend in the opposite directions parallel to each other in the offset direction at the positions equidistant from the reference ground 11B, extend in the direction perpendicular to and away from the reference ground 11B, and extend in the opposite directions parallel to each other in the offset direction at the positions equidistant from the reference ground 11B to form the coupling sections 122B.
Corresponding to fig. 4H, the two strip-shaped oscillators 12B extend in the direction vertically away from the reference ground 11B in the same lateral spatial order of the reference ground 11B from the two feeding terminals 121B, extend back in the mutually parallel offset directions at positions equidistant from the reference ground 11B, extend in the direction vertically away from the reference ground 11B, extend toward each other in the mutually parallel offset directions at positions equidistant from the reference ground 11B to form the coupling sections 122B, and extend in the direction vertically close to the reference ground 11B.
Corresponding to fig. 4I, two of the strip-shaped oscillators 12B extend in the direction vertically away from the reference ground 11B in the same lateral spatial order of the reference ground 11B from the two feeding terminals 121B, extend toward each other in the offset directions parallel to each other at positions equidistant from the reference ground 11B to form the coupling sections 122B, extend in the direction vertically close to the reference ground 11B, and extend toward each other again in the offset directions parallel to each other at positions equidistant from the reference ground 11B.
Corresponding to fig. 4J, the two strip-shaped oscillators 12B extend from the two feeding terminals 121B in the same lateral spatial order of the reference ground 11B in the direction away from the reference ground 11B, extend back to the opposite direction in parallel with the offset direction at the position equidistant from the reference ground 11B, extend in the direction away from the reference ground 11B in the perpendicular direction, extend toward each other in parallel with the offset direction at the position equidistant from the reference ground 11B to form the coupling section 122B, extend in the direction approaching the reference ground 11B in the perpendicular direction, and extend toward each other again in parallel with the offset direction at the position equidistant from the reference ground 11B.
Corresponding to fig. 4K, two of the strip-shaped oscillators 12B extend in the direction perpendicular to and away from the reference ground 11B from two of the feeding terminals 121B in the same lateral spatial order of the reference ground 11B, and extend in opposite directions in mutually parallel offset directions at different distances from the reference ground 11B to form the coupling sections 122B, wherein the lengths of the two coupling sections 122B are not limited to be the same.
Corresponding to fig. 4L, the two strip-shaped oscillators 12B extend from the two feeding terminals 121B in the same lateral space of the reference ground 11B in the direction perpendicular to and away from the reference ground 11B, are sequentially bent at positions equidistant from the reference ground 11B to extend in opposite directions parallel to each other in the offset direction, are bent to extend in opposite directions parallel to each other in the offset direction to form the coupling sections 122B, and are bent again to extend in opposite directions parallel to each other in the offset direction.
Corresponding to fig. 4M and 4N, the two coupling sections 122B of the two strip-shaped oscillators 12B extend from the near end in opposite directions in a staggered manner. Specifically, corresponding to fig. 4M, the two strip-shaped oscillators 12B extend in the direction perpendicular to and away from the reference ground 11B from the two feeding terminals 121B in the same lateral spatial sequence of the reference ground 11B, and extend in opposite directions away from and opposite to the reference ground 11B at positions equidistant from the reference ground 11B to form the coupling sections 122B. Corresponding to fig. 4N, the two strip-shaped oscillators 12B extend in the direction vertically away from the reference ground 11B in the same lateral spatial order of the two feeding terminals 121B at the reference ground 11B, extend oppositely in the staggered direction away from the reference ground 11B and facing each other at positions equidistant from the reference ground 11B to form the coupling sections 122B, and extend in the direction vertically away from the reference ground 11B at positions equidistant from the reference ground 11B.
It is worth mentioning that the structural configuration of the double-ended feed differential antenna is various, and when the end of the coupling section 122B close to the feeding end 121B of the strip-shaped oscillator 12B to which the coupling section 122B belongs is the proximal end of the coupling section 122B, the extending direction of each coupling section 122B is not limited to the fixed extending direction, that is, in some embodiments of the present invention, the two coupling sections 122B extend from the proximal end in the dynamic opposite direction to form the coupling section 122B in the bent configuration, and also the polarization configuration tending to the linear polarization can be realized when the double-ended feed differential antenna 10B is used as the transmitting antenna 10 in the state where the excitation signals differing by more than 90 ° are accessed into the two feeding ends 121B of the two strip-shaped oscillators 12B, and the coupling section 122B has the phase difference greater than 90 ° with respect to the coupling between the two feeding sections 122B extending from the proximal end in the opposite direction, and the coupling sections 122B are not limited to each other based on the practical coupling configuration of the coupling between the two coupling sections 122B.
Furthermore, in some embodiments of the present invention, the strip-shaped oscillator 12B is disposed in a microstrip line form carried on the circuit board, which is not limited by the present invention.
It should be noted that, in a state of the transmitting antenna 10 adopting a linear polarization form, preferably in a linear polarization or a polarization direction tending to the linear polarization of the transmitting antenna 10, based on feeding the transmitting antenna 10 tending to a phase difference of 180 °, a balanced differential feeding of the transmitting antenna 10 is implemented, so as to reduce a minimum transmitting power extreme value of the transmitting antenna 10 in a state of ensuring stable transmission of the microwave beam, thereby ensuring stable transmission of the microwave beam in a micro signal form in a state of reducing the transmitting power of the transmitting antenna 10 to a target transmitting power.
Based on this, the present invention further provides a differential feed circuit, which corresponds to some embodiments of the present invention, the microwave detecting device includes the differential feed circuit, wherein corresponding to fig. 5A and 5B, the differential feed circuit is set in a discrete component form, and the circuit structures of the differential feed circuit 20 of different embodiments are respectively illustrated.
Corresponding to fig. 5A and 5B, in this embodiment of the invention, the differential feed circuit has a three-pole circuit processor (corresponding to Q1 in the figure) configured as a MOS transistor or a triode, an inductor (corresponding to L1 in the figure), a first resistor (corresponding to R1 in the figure), a second resistor (corresponding to R2 in the figure), a third resistor (corresponding to R3 in the figure), a first capacitor (corresponding to C1 in the figure), a second capacitor (corresponding to C2 in the figure), an oscillating capacitor (corresponding to C5 in the figure) and a power connection terminal (corresponding to Vcc in the figure) adapted to access a corresponding power supply, wherein the three-pole circuit processor has a first connection terminal corresponding to the collector of the triode or the drain of the MOS transistor, a second connection terminal corresponding to the base of the triode or the gate of the MOS transistor, and a third connection terminal corresponding to the emitter of the triode or the source of the MOS transistor, wherein one end of the second resistor is electrically connected to the first connection terminal of the three-pole circuit handler, the other end of the second resistor is connected to the power connection terminal via the inductor, and is grounded via the first capacitor, wherein one end of the third resistor is electrically connected to the third connection terminal of the three-pole circuit handler, the other end of the third resistor is grounded, wherein one end of the oscillation capacitor is electrically connected to the second connection terminal of the three-pole circuit handler, the other end of the oscillation capacitor is grounded, wherein one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit handler, the other end of the first resistor is electrically connected between the inductor and the second resistor corresponding to fig. 5A, or is electrically connected to the power connection terminal corresponding to fig. 5B, wherein two ends of the second capacitor are electrically connected to the first connection terminal and the third connection terminal of the three-pole circuit processor, respectively, wherein the second resistor and the third resistor are set with equal resistance, so that in a state that the differential feeding circuit is connected to the corresponding power source at the power connection terminal, the excitation signal is output at two ends of the second capacitor in a balanced differential signal form with a phase difference approaching 180 °, thereby realizing phase difference feeding of the transmitting antenna approaching 180 °.
It should be noted that the inductor functions to isolate ac and dc, so as to isolate a high-frequency ac excitation signal from a power supply voltage signal, and the first capacitor is a decoupling capacitor, so as to prevent a parasitic oscillation caused by a positive feedback path formed by a circuit through a power supply, and prevent a current fluctuation caused by a change in the current magnitude of the circuit before and after the circuit in a power supply circuit from affecting the normal operation of the circuit, wherein since one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit processor to provide a divided current to the second connection terminal of the three-pole circuit processor, the inductor does not participate in voltage division, so that the other end of the first resistor may be electrically connected between the inductor and the second resistor corresponding to fig. 5A, or may be electrically connected to the power supply connection terminal corresponding to fig. 5B.
Further, in the two embodiments of the present invention, the differential feeding circuit further has a third capacitor (corresponding to C3 in the figure) and a fourth capacitor (corresponding to C4 in the figure), wherein the third capacitor and the fourth capacitor are electrically connected to two ends of the second capacitor respectively, so as to output the excitation signal in a balanced differential signal form with a phase difference approaching 180 ° through the third capacitor and the fourth capacitor, thereby realizing phase difference feeding of the transmitting antenna approaching 180 °.
It is worth mentioning that, corresponding to the differential feeding circuit illustrated in fig. 5A and 5B, in other embodiments of the present invention, the inductance may not be set, corresponding to one end of the second resistor electrically connected to the first connection end of the three-pole circuit processor, the other end of the second resistor electrically connected to the power connection end, and via the first capacitor grounded, one end of the first resistor electrically connected to the second connection end of the three-pole circuit processor, and the other end of the first resistor electrically connected to the power connection end.
Furthermore, it is worth mentioning that, in the embodiments of the present invention, the first capacitor, the second capacitor, the third capacitor, the fourth capacitor and the oscillating capacitor can be set in the actual circuit structure in the form of a microstrip distributed capacitor, which is not limited by the present invention.
Referring further to fig. 6 of the drawings accompanying the present application, a partial circuit structure of a differential feed circuit according to an embodiment of the present invention is illustrated, in which the differential feed circuit is configured in an integrated circuit form and outputs the excitation signal in a differential oscillation circuit in a balanced differential signal form with a phase difference of approximately 180 °.
Specifically, the differential oscillation circuit has two N-channel MOS transistors (corresponding to Q1 and Q2 in the figure), two P-channel MOS transistors (corresponding to Q3 and Q4 in the figure), an oscillation inductor (corresponding to L in the figure) and an oscillation capacitor (corresponding to C in the figure), wherein the sources of the two N-channel MOS transistors are electrically connected, the sources of the two P-channel MOS transistors are electrically connected, and the drains of the two N-channel MOS transistors are electrically connected to the drains of different P-channel MOS transistors, respectively, so as to form a drain of one of the N-channel MOS transistors electrically connected to a drain of one of the P-channel MOS transistors, a source of the P-channel MOS transistor is electrically connected to a source of the other P-channel MOS transistor, and a drain of the other P-channel MOS transistor is electrically connected to a drain of the other N-channel MOS transistor, and the source of the other N-channel MOS transistor is electrically connected with the source of the previous N-channel MOS transistor in a sequential connection relationship, wherein in the two N-channel MOS transistors, the gate of any one N-channel MOS transistor is electrically connected with the drain of the other N-channel MOS transistor, wherein in the two P-channel MOS transistors, the gate of any one P-channel MOS transistor is electrically connected with the drain of the other P-channel MOS transistor, wherein the two ends of the oscillation inductor are respectively and electrically connected with the drains of the different P-channel MOS transistors, and the two ends of the oscillation capacitor are respectively and electrically connected with the drains of the different P-channel MOS transistors and are connected with the oscillation inductor in parallel, so that the oscillation and frequency selection are formed based on a parallel resonance loop consisting of the oscillation inductor and the oscillation capacitor, and electric signals with equal size and opposite directions are formed at the two ends of the oscillation inductor and the oscillation capacitor, and the other N-channel MOS tube and the P-channel MOS tube electrically connected with the grid electrode of the N-channel MOS tube can be simultaneously conducted at the other moment, so that the excitation signals are output at two ends of the oscillation inductor in a balanced differential signal form with a 180-degree difference.
With further reference to fig. 7A to 7D of the drawings of the present disclosure, the differential feed circuit is configured in an integrated circuit form and outputs the state of the excitation signal in a balanced differential signal form with a phase difference approaching 180 °, and the structural block diagram of the microwave detecting device according to different embodiments of the present disclosure is illustrated.
Wherein the differential feed circuit comprises a low dropout linear regulator (corresponding to the internal LDO in the figure), the differential oscillating circuit, an oscillator (corresponding to the Osc in the figure), a phase-locked loop (corresponding to the PLL in the figure), and a logic control unit, wherein the low dropout linear regulator provides a constant voltage to the differential oscillating circuit in a powered state, wherein the oscillator is configured such that the logic control unit provides a basic clock signal and is externally configured with a quartz crystal oscillator or is integrally configured with an internal oscillating circuit in the logic control unit, wherein the logic control unit is configured with a DSP, MCU, or RAM and is electrically connected to the oscillating inductor of the differential oscillating circuit, wherein the phase-locked loop is electrically connected between the logic control unit and the differential oscillating circuit in a state of being externally configured or integrated with the logic control unit, so as to calibrate the differential oscillating circuit to output the frequency/phase of the excitation signal in a balanced differential signal form with a phase difference of 180 ° between both ends of the oscillating inductor based on the feedback of the excitation signal output by the logic control unit from the differential oscillating circuit, thereby ensuring a stable output of the excitation signal to the differential feed circuit.
It is worth mentioning that, for the purpose of reducing the cost of the differential feeding circuit, in some embodiments of the present invention, the phase-locked loop may not be configured, that is, the logic control unit is electrically connected to the differential oscillating circuit, so as to control the stability of the frequency/phase of the excitation signal outputted from the differential oscillating circuit at two ends of the oscillating inductor in a balanced differential signal form with a 180 ° difference based on the feedback of the excitation signal outputted from the differential oscillating circuit.
Further, in the embodiments of the present invention, the differential feeding circuit further includes two amplifiers (corresponding to PA1 and PA2 directly led out from the differential oscillating circuit in the figure) for amplifying the excitation signal outputted from the differential oscillating circuit in a balanced differential signal form, wherein the logic control unit is electrically connected to the oscillating inductor of the differential oscillating circuit in a state of being electrically connected to at least one of the amplifiers, so as to receive the feedback of the amplifier to the excitation signal outputted from the differential oscillating circuit.
It is worth mentioning that in a state where the microwave beam is in a weak signal form due to the reduction of the transmitting power of the transmitting antenna, although the above-mentioned series of advantages are exhibited, since the strength of the corresponding echo signal is simultaneously reduced, in a state where there is ambient electromagnetic interference in the corresponding target detection space, the corresponding doppler intermediate frequency signal is more likely to be interfered by ambient electromagnetic radiation, and it is difficult to accurately feed back the motion characteristics corresponding to the human body movement motion, the inching motion, and the breathing and heartbeat motion. Based on this, it corresponds to the utility model discloses a fig. 7A to fig. 7C of the specification attached drawing illustrate the microwave detection device, correspondingly the microwave detection method further includes the method step of improving the precision of echo signal, in order to be in the state that the intensity of echo signal is based on the transmission power of transmitting antenna (corresponding TX in the figure) is reduced, based on the improvement of the precision of echo signal, guarantee the accuracy and the stability of microwave detection method and device to the detection of the activity characteristics corresponding to human body movement action, fine motion action, and breathing and heartbeat action.
Specifically, the method step of improving the accuracy of the echo signal includes the step of accessing the echo signal in a balanced differential signal form from a receiving antenna (corresponding to RX in the figure) of the microwave detection device, so that the electromagnetic interference in the environment exists in a common mode interference form in the echo signal, and thus can be suppressed during the reception and transmission of the echo signal in a balanced differential signal form, and subsequently, corresponding to fig. 7D, outputting the doppler intermediate frequency signal in a balanced differential signal form based on a mixing processing step of the echo signal in a balanced differential signal form, and forming a digitized form of the doppler intermediate frequency signal in a balanced differential signal form based on the digitized conversion of the doppler intermediate frequency signal in a balanced differential signal form by an a/D conversion unit, the data processing unit connected with the A/D conversion unit is set to suppress (including eliminate) common-mode interference information in the digitized form of the Doppler intermediate frequency signal in the balanced differential signal form by a corresponding algorithm based on the digitized feature of the common-mode interference, so as to further suppress and process the common-mode interference information in the digitized form of the Doppler intermediate frequency signal in the balanced differential signal form by the data processing unit based on the corresponding algorithm, thereby forming the Doppler intermediate frequency signal in the digitized form free from environmental electromagnetic interference, and further improving the feedback accuracy of the Doppler intermediate frequency signal in the digitized form on activity features corresponding to human body movement, micromotion and respiration and heartbeat; or subsequently, corresponding to fig. 7B and 7C, outputting the doppler intermediate frequency signals in a balanced differential signal form based on a step of mixing the echo signals in a balanced differential signal form and outputting the doppler intermediate frequency signals in a single-ended signal form based on a step of differential to single-ended processing of the doppler intermediate frequency signals in a balanced differential signal form, to further suppress common-mode interference in the echo signals and/or the doppler intermediate frequency signals in a balanced differential signal form based on a step of mixing the echo signals in a balanced differential signal form and/or a step of differential to single-ended processing of the doppler intermediate frequency signals in a balanced differential signal form, for example by exploiting the characteristic of common-mode interference that is equally asymmetric in signals in a differential signal form having a symmetric characteristic, to output the doppler intermediate frequency signals in a signal form free from environmental electromagnetic interference by a cancellation effect in a process of symmetry conversion and superposition of the single-ended interference in a differential to single-ended processing step based on the principle of differencing, thereby improving the accuracy of the doppler intermediate frequency signals in the feedback characteristic corresponding to the movement, micromotion, breathing and heartbeat movements of the human body; or in the subsequent stage, corresponding to fig. 7A, based on the further suppressing effect of the step of processing the echo signals in the form of balanced differential signals from differential to single-ended processing on the echo signals in the form of balanced differential signals, the echo signals in the form of single-ended signals free from environmental electromagnetic interference are output, and based on the step of processing the echo signals in the form of single-ended signals free from environmental electromagnetic interference, the doppler intermediate frequency signals free from environmental electromagnetic interference are output, so as to improve the feedback accuracy of the doppler intermediate frequency signals on the activity characteristics corresponding to the human body movement action, the micromotion action, and the respiration and heartbeat action, and to improve the accuracy and stability of the detection range and detection of the activity characteristics corresponding to the human body movement action, the micromotion action, and the respiration and heartbeat action, corresponding to the processing system of the balanced differential signals constructed in the step of accessing the echo signals in the form of balanced differential signals from the receiving antenna of the microwave detection device of the micro transmission power and the subsequent steps.
It is worth mentioning that, since the echo signal is in a balanced differential signal form when accessed from the receiving antenna, and the electromagnetic radiation interference in the environment exists in a common mode interference form in the echo signal, it can be suppressed during the receiving and transmitting processes of the echo signal in the balanced differential signal form, that is, the echo signal simultaneously includes a signal corresponding to a reflected echo formed by a microwave beam emitted by the transmitting antenna being reflected by a corresponding object and an electromagnetic radiation interference signal in the common mode interference form, so that no matter in fig. 7D, the doppler intermediate frequency signal in the balanced differential signal form is output in a subsequent mixing processing step based on the echo signal in the balanced differential signal form, and the digitized form of the doppler intermediate frequency signal in the balanced differential signal form is formed based on the digitized conversion of the doppler intermediate frequency signal in the balanced differential signal form by the a/D conversion unit, and the common mode interference information in the digitized form of the doppler intermediate frequency signal in the balanced differential signal form is suppressed by the data processing unit according to a corresponding algorithm based on the digitized feature of the common mode interference; or to fig. 7B and 7C to output the doppler intermediate frequency signal in a balanced differential signal form in a subsequent mixing processing step based on the echo signal in a balanced differential signal form and to output the doppler intermediate frequency signal in a single-ended signal form in a subsequent differential-to-single-ended processing step based on the doppler intermediate frequency signal in a balanced differential signal form; or the echo signal in single-ended signal form outputted in the following differential-to-single-ended processing step based on the echo signal in balanced differential signal form corresponding to fig. 7A, and the doppler intermediate frequency signal outputted in the following mixing processing step based on the echo signal in single-ended signal form based on the doppler intermediate frequency signal in differential-to-single-ended processing step, wherein the suppression processing of the common-mode interference information in the digitized form of the doppler intermediate frequency signal in balanced differential signal form by the corresponding algorithm based on the digitized feature of the common-mode interference corresponding to fig. 7D, or the further suppression of the common-mode interference in the echo signal in balanced differential signal form and/or the doppler intermediate frequency signal in balanced differential signal form corresponding to fig. 7B and 7C based on the mixing processing step of the echo signal in balanced differential signal form and/or the differential-to-single-ended processing step of the doppler intermediate frequency signal in balanced differential signal form, or corresponding to fig. 7A, based on the further suppressing effect of the step of processing the echo signals in the form of balanced differential signals from differential to single end on the common mode interference in the echo signals in the form of balanced differential signals, the doppler intermediate frequency signals in the form of digitized signals or analog signals which are finally output are free from the environmental electromagnetic interference, so that the feedback accuracy of the doppler intermediate frequency signals on the activity characteristics corresponding to the movement, micromotion, respiration and heartbeat of the human body can be improved, and the processing system of balanced differential signals is constructed corresponding to the step of accessing the echo signals in the form of balanced differential signals from the receiving antenna of the microwave detection device with micro-transmitting power and the subsequent steps, the microwave detection method and the device for guaranteeing the micro-transmitting power have the advantages of ensuring the detection range and the detection accuracy and stability of the activity characteristics corresponding to the movement action, the micro-motion action, the respiration action and the heartbeat action of the human body.
Correspondingly, the microwave detecting apparatus further includes a mixing circuit and a differential-to-single-ended circuit corresponding to fig. 7A to 7C, wherein the mixing circuit is electrically connected between the differential oscillating circuit and the receiving antenna to output the doppler intermediate frequency signal in a single-ended signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal corresponding to fig. 7A based on the frequency mixing process of the echo signal in the excitation signal and the single-ended signal form, or output the doppler intermediate frequency signal in a differential signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal corresponding to fig. 7B and 7C based on the frequency mixing process of the echo signal in the excitation signal and the balanced differential signal form; accordingly, the differential-to-single-ended circuit is disposed between the receiving antenna and the mixing circuit corresponding to fig. 7A to perform differential-to-single-ended processing on the echo signals in balanced differential signal form based on the difference finding principle and output the echo signals in single-ended signal form free from electromagnetic environment interference to the mixing circuit, or is disposed in electrical connection with the mixing circuit corresponding to fig. 7B and 7C to receive the doppler intermediate frequency signals in differential signal form output from the mixing circuit and perform differential-to-single-ended processing on the doppler intermediate frequency signals in differential signal form based on the difference finding principle and output the doppler intermediate frequency signals in single-ended signal form free from electromagnetic environment interference, so as to improve the feedback accuracy of the intermediate frequency doppler signals on activity characteristics corresponding to human body movement, micromotion, and breathing and heartbeat movements.
Corresponding to fig. 7D, the microwave detecting device further comprises a mixing circuit and an a/D converting unit and a data processing unit, wherein the mixing circuit is electrically connected between the differential oscillating circuit and the receiving antenna to output the doppler intermediate frequency signal in a differential signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal based on the mixing process of the excitation signal and the echo signal in a balanced differential signal form, wherein the a/D converting unit is electrically connected to the mixing circuit in a structural state of being integrated with or external to the data processing unit to digitally convert the doppler intermediate frequency signal in a balanced differential signal form to form a digitized form of the doppler intermediate frequency signal in a balanced differential signal form, the data processing unit is arranged in a structural state which is integrated with the logic control unit or is independent of the logic control unit, and is capable of suppressing (including eliminating) common-mode interference information in a digitized form of the Doppler intermediate frequency signal in a balanced differential signal form by a corresponding algorithm based on the digitized feature of the common-mode interference, for example, the Doppler intermediate frequency signal in the balanced differential signal form has the feature of two paths of signals with equal amplitude and opposite phase relative to a reference potential, and the Doppler intermediate frequency signal in the balanced differential signal form can be converted into two groups of numerical data with equal absolute values and opposite numerical value change trends relative to the reference potential value in a time domain based on the digitized conversion processing of the Doppler intermediate frequency signal in the balanced differential signal form, so that after the two groups of numerical data are added with equal numerical values and different numerical values respectively in the time domain based on the common-mode interference The digital characteristics of two groups of numerical values with the same change trend are subjected to an algorithm of calculating the difference of the two groups of numerical data or an algorithm of filtering the numerical data which do not accord with the opposite change trend by comparing the two groups of numerical data, common-mode interference information in the digital form of the Doppler intermediate frequency signal which balances the differential signal form is inhibited or even eliminated, and the digital form of the Doppler intermediate frequency signal which is free from electromagnetic environment interference is correspondingly obtained, so that the feedback accuracy of the Doppler intermediate frequency signal on the activity characteristics corresponding to the movement action, the inching action and the breathing and heartbeat actions of a human body is improved. Or the difference component generated based on the common-mode interference is eliminated through the difference or comparison of the two sets of numerical data after corresponding operation processing, for example, the two sets of numerical data are independently processed based on corresponding operation to obtain two sets of control data, and then the difference component generated based on the common-mode interference is eliminated through comparison and analysis based on the two sets of control data, so as to output an accurate control result.
Further, corresponding to fig. 7A, in a state where the mixing circuit is configured to output the doppler intermediate frequency signal in a single-ended signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal based on the mixing process of the echo signal in the excitation signal and the single-ended signal form, the microwave detecting apparatus optionally includes another differential to single-ended circuit, where the differential to single-ended circuit is configured between the differential oscillating circuit and the mixing circuit to output the excitation signal in a single-ended signal form free from electromagnetic environment interference to the mixing circuit based on the differential to single-ended process of the excitation signal in a differential signal form, so as to facilitate improvement of accuracy of the doppler intermediate frequency signal in a single-ended signal form output from the mixing circuit, and to correspondingly secure feedback accuracy of the doppler intermediate frequency signal to activity characteristics corresponding to human body movement, micromotion, and respiration and heartbeat actions. That is, in a state where the differential-to-single-ended circuit is not set, the excitation signal in a single-ended signal form may be outputted to the mixer circuit by selecting a mode of directly drawing the excitation signal in a single-ended signal form from the differential oscillator circuit, which is not limited by the present invention.
It is worth mentioning that, based on the difference in the usage/transmission path of the signals derived from the differential oscillating circuit, in some documents in the field, the nomenclature of the signals derived from the respective oscillating circuit may be different, for example, in some documents in the field, the transmission object of the signals derived from the respective oscillating circuit is called an excitation signal when the antenna is used for feeding the respective antenna, and is called a local oscillation signal when the transmission object of the derived signals is a mixer, the present invention is not limited thereto, i.e. in the description of the present invention, the same nomenclature is used for the excitation signal derived from the differential oscillating circuit and transmitted to the transmitting antenna and the excitation signal also derived from the differential oscillating circuit and transmitted to the mixer circuit, in order to facilitate understanding that the excitation signal is provided by the differential oscillating circuit, and the nomenclature of the excitation signal does not in itself constitute a limitation of the usage/transmission path thereof.
Corresponding to fig. 7B to 7D, in a state where the mixing circuit is set to output the doppler intermediate frequency signal in a balanced differential signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal in a balanced differential signal form based on the mixing process of the excitation signal and the echo signal in a balanced differential signal form, the mixing circuit illustrated in fig. 7C may alternatively correspond to an integrated form of fig. 7B set to two mixing circuits adapted to the mixing process of the excitation signal and the echo signal in a single-ended signal form to output the doppler intermediate frequency signal in a differential signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal based on the mixing process of the excitation signal and the echo signal in a differential signal form by the mixing circuit.
It is understood that, in some embodiments of the present invention, the mixing circuit may be optionally implemented as an integrated form of the mixing circuit and the differential-to-single-ended circuit in structures or functions corresponding to fig. 7A to 7C, and the mixing circuit may be configured to output the doppler intermediate frequency signal in a single-ended signal form in a state of accessing the echo signal in a balanced differential signal form and the excitation signal, including but not limited to outputting the doppler intermediate frequency signal in a single-ended signal form corresponding to fig. 7A based on a differential-to-single-ended processing of the echo signal in a balanced differential signal form and a mixing processing of the echo signal in a single-ended signal form and the excitation signal, or outputting the doppler intermediate frequency signal in a single-ended signal form corresponding to fig. 7B and 7C based on a mixing processing of the echo signal in a balanced differential signal form and a mixing processing of the single-ended doppler intermediate frequency signal in a balanced differential signal form, and the present invention is not limited thereto.
Specifically, the signal based on the balanced differential signal form has two signals with equal amplitude and opposite phase relative to the reference potential and has a symmetrical characteristic, in some embodiments of the present invention, the differential to single-ended circuit is configured to perform the inverse phase processing on one of the two signals based on the signal with the differential signal form, and output the signal with the single-ended signal form after being superimposed with the other signal, so that the common-mode interference information in the signal with the balanced differential signal form can be suppressed or even eliminated by using the characteristic that the common-mode interference is equal amplitude and asymmetrical in the signal with the symmetrical characteristic in the signal with the differential signal form based on the differential to single-ended processing on the signal with the balanced differential signal form by the differential to single-ended circuit.
Correspondingly, in the embodiments of the present invention, when the mixing circuit is implemented in a fully integrated manner corresponding to the mixing circuit and the differential-to-single-ended circuit in fig. 7A to 7C to implement that the mixing circuit outputs the doppler intermediate frequency signal in a single-ended signal form in a state of accessing the echo signal and the excitation signal in a balanced differential signal form, the mixing circuit may be further implemented to output the doppler intermediate frequency signal in a single-ended signal form sequentially based on an inversion process on one of two signals of the echo signal in a balanced differential signal form, a mixing process on the two signals respectively, and a superposition process on the two doppler intermediate frequency signals output by the mixing process, so as to suppress or even eliminate interference information generated by corresponding common-mode interference.
In other embodiments of the present invention, when the mixer circuit is implemented as a partially integrated form corresponding to the functions of the mixer circuit and the differential-to-single-ended circuit in fig. 7A to 7C to achieve that the mixer circuit outputs the doppler intermediate frequency signal in a single-ended signal form in a state of accessing the echo signal and the excitation signal in a balanced differential signal form, the mixer circuit may be implemented as a method sequentially based on an inverse process of one of two signals of the echo signal in a balanced differential signal form, and a method for outputting the doppler intermediate frequency signal in a two-way signal form by mixing the two signals, so as to subsequently suppress or even eliminate interference information generated by corresponding common-mode interference based on a superposition process of the two doppler intermediate frequency signals, or generate two sets of numerical data having the same absolute value and the same numerical value change trend with respect to a reference potential value based on a digital conversion of the two doppler intermediate frequency signals, so as to perform a digital interference suppression operation on the two sets of numerical data having the same absolute value and opposite numerical value change trend in a time domain based on a digital conversion of the two sets of doppler intermediate frequency signals, so as to obtain two sets of numerical data corresponding doppler signals by adding the same absolute value and filtering the same doppler respiration trend, and obtaining a fine motion of the two sets of the same doppler intermediate frequency signals, so as a doppler signals, so as to obtain a doppler signal, and obtain a corresponding interference suppression operation. Or the difference component generated based on the common-mode interference is eliminated through the difference or comparison of the two sets of numerical data after the corresponding operation processing, for example, the two sets of numerical data are independently processed based on the corresponding operation to obtain two sets of control data, and the difference component generated based on the common-mode interference is eliminated through the subsequent comparison and analysis based on the two sets of control data, so that an accurate control result is output.
It should be noted that, in some embodiments of the present invention, the present invention further includes an amplifying step of the echo signal and/or the doppler intermediate frequency signal in balanced differential signal form, for example, on the basis of the circuit structure illustrated in fig. 7A, a corresponding amplifying circuit adapted to amplify the signal in differential signal form is further disposed between the receiving antenna and the corresponding differential-to-single-ended circuit, so as to amplify and output the echo signal in balanced differential signal form to the differential-to-single-ended circuit, or on the basis of the circuit structures illustrated in fig. 7B to 7C, a corresponding amplifying circuit adapted to amplify the signal in differential signal form is further disposed between the receiving antenna and the frequency mixing circuit and/or between the frequency mixing circuit and the differential-to-single-ended circuit, to amplify and output the echo signal in the form of balanced differential signal to the mixer circuit and/or amplify and output the doppler intermediate frequency signal in the form of differential signal to the differential-to-single-ended circuit, or on the basis of the circuit structure illustrated in fig. 7D, a corresponding amplifier circuit suitable for amplifying the signal in the form of differential signal is further disposed between the receiving antenna and the mixer circuit and/or between the mixer circuit and the a/D conversion unit, so as to amplify and output the echo signal in the form of balanced differential signal to the mixer circuit and/or amplify and output the doppler intermediate frequency signal in the form of differential signal to the a/D conversion unit, which is not limited by the present invention, wherein preferably, the differential-to-single-ended circuit is configured to employ a circuit having electrical characteristics of amplifying the signal in the form of differential signal, such as a circuit of an instrument amplifier, so as to simultaneously realize the amplification processing and the single-end conversion processing of the signals in the differential signal form, thereby being simple and easy.
In particular, in some embodiments of the present invention, the present invention further includes an amplifying step of amplifying the echo signal and/or the doppler intermediate frequency signal in the form of a single-ended signal, for example, on the basis of the circuit structure illustrated in fig. 7A, a corresponding amplifying circuit adapted to amplify the signal in the form of a single-ended signal is further disposed between the differential-to-single-ended circuit and the mixing circuit and/or at the output end of the mixing circuit, so as to amplify the echo signal in the form of a single-ended signal to the mixing circuit and/or amplify the doppler intermediate frequency signal in the form of a single-ended signal, or on the basis of the circuit structures illustrated in fig. 7B and 7C, a corresponding amplifying circuit adapted to amplify the signal in the form of a single-ended signal is further disposed at the output end of the differential-to-single-ended signal, so as to amplify the doppler intermediate frequency signal in the form of a single-ended signal, which the present invention is not limited thereto.
Further, in some embodiments of the present invention, the step of accessing the echo signal from the receiving antenna of the microwave detecting device to the balanced differential signal form includes accessing the echo signal of the balanced differential signal form based on a phase shifting step of the echo signal accessed from one of the receiving feeding points (ends) in a state where the two receiving feeding points (ends) of the receiving antenna are orthogonally arranged, so as to ensure isolation between the echo signals accessed from the two receiving feeding points (ends) of the receiving antenna based on the orthogonal form between the two receiving feeding points (ends) of the receiving antenna, and correspondingly ensure accuracy of the echo signal of the balanced differential signal form accessed based on the phase shifting step of the echo signal accessed from one of the receiving feeding points (ends).
Corresponding reference to the utility model discloses a state that two receipt feed points (end) of receiving antenna were arranged by the quadrature is based on the phase shift step of the echo signal of receiving one of them feed point (end) access and is inserted balanced differential signal form echo signal, different embodiments receiving antenna's structural form is illustrated, wherein based on the receiving and dispatching reciprocity characteristic of antenna, right receiving antenna's reference numeral and the name of corresponding structure follow in the description and the figure of the utility model the name of transmitting antenna's reference numeral and corresponding structure.
In both embodiments of the present invention, the receiving antenna 10 is exemplarily provided in a planar patch antenna configuration to have a reference ground 11 and a radiation source 12, wherein the radiation source 12 is provided on a side of the reference ground 11 in a spaced state from the reference ground 11, corresponding to fig. 8A and 8B.
Specifically, corresponding to fig. 8A, the radiation source 12 is configured as a unit radiation source, and the radiation source 12 has a single number of radiation elements 121, wherein the radiation element 121 has two feeding points 1211, wherein the two feeding points 1211 are orthogonally arranged, connecting lines between the two feeding points 1211 and a physical central point 1212 of the radiation element 121 are perpendicular to each other, one of the feeding points 1211 is electrically connected with a phase shifter, such as a microstrip line configured with a corresponding electrical length, so as to output the echo signal in a balanced differential signal form between one end of the phase shifter far from the feeding point 1211 and the other feeding point 1211 based on a phase shifting process of the phase shifter on the echo signal accessed from the feeding point 1211.
Corresponding to fig. 8B, the radiation source 12 is configured as a binary radiation source, and the radiation source 12 has two radiation elements 121, wherein each of the radiation elements 121 has a feeding point 1211, wherein the two radiation elements 121 are orthogonally arranged, a connection direction of the feeding point 1211 to the physical central point 1212 of one of the radiation elements 121 is perpendicular to a connection direction of the feeding point 1211 to the physical central point 1212 of the other radiation element 121, and one of the feeding points 1211 is electrically connected with a phase shifter, such as a microstrip line configured with a corresponding electrical length, so as to output the echo signal in a balanced differential signal form between an end of the phase shifter far from the feeding point 1211 and the other feeding point 1211 based on a phase shifting process of the phase shifter on the echo signal accessed from the feeding point 1211.
Corresponding to fig. 8C and 8D, in both embodiments of the present invention, the receiving antenna is set as an example with the half-wave folded directional microwave detecting antenna 10A of orthogonal polarization.
Specifically, corresponding to fig. 8C, the receiving antenna is configured as a half-wave folded-back directional microwave detecting antenna 10A in a cross-polarized horizontal structure, the half-wave folded-back directional microwave detecting antenna 10A includes two half-wave oscillators 12A, wherein the two half-wave oscillators 12A are orthogonally arranged, and corresponding to a direction perpendicular to the reference ground 11A as a height direction of the half-wave folded-back directional microwave detecting antenna 10A, the two half-wave oscillators 12A are perpendicular to each other in an extending direction perpendicular to the height direction of the half-wave folded-back directional microwave detecting antenna 10A, wherein the feeding point 121A of one half-wave oscillator 12A is connected with a phase shifter via the feeding line 13A, such as a microstrip line configured with a corresponding electrical length, so as to output the echo signal in a balanced differential signal form between one end of the phase shifter far from the feeding point 121A and the other feeding point 121A based on the phase shift processing of the echo signal accessed from the feeding point 121A.
Corresponding to fig. 8D, the half-wave folded back directional microwave probe antenna 10A of the receiving antenna in a cross-polarized vertical structure is disposed, the half-wave folded back directional microwave probe antenna 10A includes two half-wave elements 12A, wherein the two half-wave elements 12A are orthogonally arranged, corresponding to a direction perpendicular to the reference ground 11A as a height direction of the half-wave folded back directional microwave probe antenna 10A, the two half-wave elements 12A are perpendicular to each other in an extending direction perpendicular to the height direction of the half-wave folded back directional microwave probe antenna 10A, wherein one of the feeding ends 1211A of one of the half-wave elements 12A is connected with a phase shifter via the feeding line 13A, such as a microstrip line disposed in a corresponding electrical length, to output the echo signal in a balanced signal form between an end of the phase shifter remote from the feeding end 1211A and one of the other half-wave elements 12A based on a phase shift processing of the echo signal accessed from the feeding end 1211A.
It is worth mentioning that in some preferred embodiments of the present invention, in the step of accessing the echo signal in the form of balanced differential signal from the receiving antenna of the microwave detecting device, two receiving feeding points of the receiving antenna are arranged in opposite phase to directly access the echo signal in the form of balanced differential signal from the two receiving feeding points.
Referring to fig. 9A to 9E of the drawings of the present disclosure, in a state that two receiving feeding points (ends) of the receiving antenna are arranged in opposite phases, the two receiving feeding points (ends) are directly connected to the echo signal in a balanced differential signal form, and the structural form of the receiving antenna in different embodiments is illustrated.
In both embodiments of the present invention, the receiving antenna 10 is exemplified by a planar patch antenna configuration having a reference ground 11 and a radiation source 12, corresponding to fig. 9A and 9B, wherein the radiation source 12 is disposed on a side of the reference ground 11 in a spaced state from the reference ground 11.
Specifically, corresponding to fig. 9A, the radiation source 12 is configured in a unit radiation source form, and the radiation source 12 has a single number of radiation elements 121, wherein the radiation element 121 has two feeding points 1211, wherein the two feeding points 1211 are arranged in opposite phases, and a connection direction from one of the feeding points 1211 to a physical center point 1212 of the radiation element 121 coincides with a connection direction from the other feeding point 1211 to the physical center point 1212 of the radiation element 121, so as to output the echo signals in a balanced differential signal form at the two feeding points 1211 based on a structural state that the two feeding points 1211 are arranged in opposite phases.
Preferably, in this embodiment of the present invention, the two feeding points 1211 of the radiating element 121 are arranged symmetrically with respect to the physical center point 1212 of the radiating element 121, so that the echo signals in a balanced differential signal form are output at the two feeding points 1211 with a phase difference of about 180 ° based on the two feeding points 1211 arranged in opposite phases and the equidistant configuration from the two feeding points 1211 to the physical center point 1212 of the radiating element 121.
Corresponding to fig. 9B, the radiation source 12 is configured in a binary radiation source form, and the radiation source 12 has two radiation elements 121, wherein each of the radiation elements 121 has a feeding point 1211, wherein the two radiation elements 121 are arranged in opposite phases, and a connection line direction from the feeding point 1211 to a physical central point 1212 of one of the radiation elements 121 is opposite to a connection line direction from the feeding point 1211 to a physical central point of the other radiation element 121, so that the two feeding points 1211 output the echo signals in a balanced differential signal form based on a structural state that the two radiation elements 121 are arranged in opposite phases.
Preferably, in this embodiment of the present invention, the two radiating elements 121 are arranged in a mirror image, so that the two feeding points 1211 output the echo signals with a phase difference of 180 ° to form a balanced differential signal based on the two radiating elements 121 being arranged in opposite phases and the equidistant configuration of the feeding points 1211 to the physical center point 1212 of the radiating element 121.
Corresponding to fig. 9C and 9D, in both embodiments of the present invention, the receiving antenna is exemplified by the half-wave folded directional microwave detecting antenna 10A polarized in reverse phase.
Specifically, corresponding to fig. 9C, the half-wave folded-back directional microwave detecting antenna 10A of the horizontal structure with the receiving antenna polarized in opposite phase is disposed, and the half-wave folded-back directional microwave detecting antenna 10A includes two half-wave oscillators 12A, wherein the two half-wave oscillators 12A are arranged in opposite phase, and the direction perpendicular to the reference ground 11A is taken as the height direction of the half-wave folded-back directional microwave detecting antenna 10A, and the extending direction of the two half-wave oscillators 12A from the feeding point 121A in the height direction of the half-wave folded-back directional microwave detecting antenna 10A is reversed, so that the echo signals in a balanced differential signal form are output at the two feeding points 121A based on the structural state that the two half-wave oscillators 12A are arranged in opposite phase.
Corresponding to fig. 9D, the half-wave folded-back directional microwave detecting antenna 10A of the receiving antenna in a vertical structure with reverse polarization is disposed, the half-wave elements 12A corresponding to the half-wave folded-back directional microwave detecting antenna 10A are arranged in reverse phase, i.e., the direction perpendicular to the reference ground 11A is the height direction of the half-wave folded-back directional microwave detecting antenna 10A, the half-wave elements 12A are reversed from the two feeding terminals 1211A in the extending direction perpendicular to the height direction of the half-wave folded-back directional microwave detecting antenna 10A, so as to output the echo signals in a balanced differential signal form at the two feeding terminals 1211A based on the structural state that the half-wave elements 12A are arranged in reverse phase.
Corresponding to fig. 9E, in this embodiment of the present invention, the receiving antenna is exemplified by the double-fed differential antenna 10B, so that two coupling sections 122B of the two strip-shaped oscillators 12B extend from the near end in opposite directions and can be coupled with each other to form a common structural characteristic of a resonant frequency point, and two strip-shaped oscillators 12B are formed in a structural state of being arranged in opposite directions in a polarization direction tending to linear polarization, and thus the echo signal in a balanced differential signal form can be directly output at two feeding ends 121B when the double-fed differential antenna 10B is used as the receiving antenna.
It is worth mentioning that, in other embodiments of the present invention, in a state that the microwave beam is in a weak signal form based on the transmission power of the transmitting antenna being reduced to a target transmission power, the transmitting antenna is allowed to be set in an orthogonal polarization form corresponding to a state that the transmitting antenna is set in a planar patch antenna form, and the radiation source is orthogonally set in a binary radiation source form, that is, the radiation source has two radiation elements, and a connection line direction from the feeding point to a physical central point of one of the radiation elements is perpendicular to a connection line direction from the feeding point to a physical central point of the other radiation element, based on a purpose of improving the feedback accuracy and stability of the doppler intermediate frequency signal to the motion characteristics corresponding to the movement, the inching motion, and the breathing and the heartbeat motion of the human body in a manner of improving the strength of the echo signal; and in a state that the transmitting antenna is set by the half-wave folded directional microwave detection antenna, the half-wave folded directional microwave detection antenna is set in an orthogonal polarization state, namely the half-wave folded directional microwave detection antenna comprises two half-wave oscillators, wherein the two half-wave oscillators are orthogonally arranged, and correspondingly, the direction perpendicular to the reference ground direction is taken as the height direction of the half-wave folded directional microwave detection antenna, and the extension directions of the two half-wave oscillators perpendicular to the height direction of the half-wave folded directional microwave detection antenna are mutually perpendicular.
It should be noted that, in some embodiments of the present invention, different combinations of the transmitting antenna and the receiving antenna of the above embodiments can be integrally disposed in a transceiving separated form or a transceiving integrated form in a structural form sharing the reference ground, thereby facilitating miniaturization design of the microwave detection apparatus.
For example, referring to fig. 10A to 10J of the drawings of the present invention, based on different combinations of the transmitting antenna and the receiving antenna of the embodiments, the transmitting antenna and the receiving antenna that are integrally provided in a transceiving separated form or a transceiving integrated form in a structural form that shares the reference ground are illustrated.
Corresponding to fig. 10A, based on the combination of the transmitting antenna illustrated in fig. 1A and the receiving antenna illustrated in fig. 8A, in the structural form that the transmitting antenna and the receiving antenna share the reference ground 11 and the radiation source 12, the integral structure of the transmitting antenna and the receiving antenna is illustrated, wherein the integral structure of the transmitting antenna and the receiving antenna has the reference ground 11 and the radiation source 12, wherein the radiation source 12 is disposed at one side of the reference ground 11 in a spaced state from the reference ground 11, wherein the radiation source 12 is arranged in a unit radiation source configuration, having a single number of radiation elements 121 corresponding to the radiation source 12, wherein the radiating element 121 has four feeding points 1211, wherein in the direction around the physical center point 1212 of the radiating element 121, the included angle between the connecting line between any two adjacent feeding points 1211 and the physical center point 1212 of the radiating element 121 is equal to 90 °, so that by means of phase difference feeding, in the direction around the physical center point 1212 of the radiating element 121, two adjacent feeding points 1211 are sequentially connected to the excitation signals with a 90 ° difference therebetween, so as to realize the circular polarization form of the transmitting antenna 10, and outputting the echo signals in a balanced differential signal form between one of the two feeding points 1211 and an end of the phase shifter distant from the other feeding point 1211 based on a phase shift process of the phase shifter on the echo signals accessed from one of the two feeding points 1211 by accessing the phase shifter at one of the other two feeding points 1211, so as to form an integral structure of the transmitting antenna and the receiving antenna in a transceiving separated form.
Corresponding to fig. 10B and 10C, based on the combination of the transmitting antenna illustrated in fig. 2A and the receiving antenna illustrated in fig. 9A, in a structural configuration in which the transmitting antenna and the receiving antenna share the reference ground 11, an integrated structure of the transmitting antenna and the receiving antenna of different embodiments is illustrated, wherein the integrated structure of the transmitting antenna and the receiving antenna has the reference ground 11 and the radiation source 12, wherein the radiation source 12 is disposed on one side of the reference ground 11 in a state of being spaced apart from the reference ground 11, wherein corresponding to fig. 10B, the radiation source 12 is disposed in a unit radiation source configuration, corresponding to the radiation source 12 has a single number of radiation elements 121, wherein the radiation elements 121 have four feeding points 1211, in the direction around the physical center point 1212 of the radiating element 121, an angle between a connecting line between any two adjacent feeding points 1211 and the physical center point 1212 of the radiating element 121 is equal to 90 °, and a structural state that two opposite feeding points 1211 are arranged in opposite phase is correspondingly formed, in a manner of phase difference feeding, a state that two opposite feeding points 1211 of the radiating element 121 access excitation signals with a phase difference larger than 90 ° to realize differential feeding to the transmitting antenna 10, and the other two opposite feeding points 1211 output the echo signals in a balanced differential signal form, so as to form an integrated structure of the transmitting antenna and the receiving antenna in a transceiving separated form; corresponding to fig. 10C, the radiation source 12 is configured as a binary radiation source, and has two radiation elements 121 corresponding to the radiation source 12, wherein each of the radiation elements 121 has two feeding points 1211, wherein the two feeding points 1211 of each of the radiation elements 121 are arranged in opposite phases, a connection direction from one of the feeding points 1211 to the physical central point 1212 of each of the radiation elements 121 coincides with a connection direction from the other of the feeding points 1211 to the physical central point 1212 thereof, so that a polarization direction of each of the radiation elements 121 corresponds to a connection direction of the two feeding points 1211 thereof, wherein the two radiation elements 121 are arranged orthogonally, the polarization direction of one of the radiation elements 121 is perpendicular to the polarization direction of the other radiation element 121, so that a differential feeding to the transmission antenna 10 is realized in a manner of feeding the two feeding points 1211 of one of the radiation elements 121 into excitation signals different by more than 90 ° in a manner of phase difference, and the two feeding points 1211 of the other radiation elements 121 output the echo signals in a form of a differential signal transmission and reception structure, and the transmission antenna and the reception structure in a separate form an integral structure.
Corresponding to fig. 10D, the transmitting antennas arranged in the orthogonal polarization form are combined based on the receiving antenna illustrated in fig. 8B for the purpose of improving the strength of the echo signal, in the structural form that the transmitting antenna and the receiving antenna share the reference ground 11, the integral structure of the transmitting antenna and the receiving antenna is illustrated, wherein the integral structure of the transmitting antenna and the receiving antenna has the reference ground 11 and the radiation source 12, wherein the radiation source 12 is disposed at one side of the reference ground 11 in a state of being spaced apart from the reference ground 11, wherein the radiation source 12 is arranged in a quaternary radiation source configuration, having four of the radiation elements 121 corresponding to the radiation source 12, wherein each of the radiating elements 121 has a feeding point 1211, wherein each of the radiating elements 121 is circumferentially arranged and satisfies that, in the circumferential arrangement direction of the radiating elements 121, an angle between a connecting line between the feeding point 1211 of any two adjacent radiating elements 121 and a physical center point 1212 thereof is equal to 90 degrees, one of the feeding points 1211 is electrically connected to a phase shifter, so that the echo signals in a balanced differential signal form are output between one end of the phase shifter far from the feeding point 1211 and another feeding point 1211 adjacent to the feeding point 1211 in the circumferential arrangement direction of the radiating element 121 based on the phase shifting processing of the phase shifter on the echo signals accessed from the feeding point 1211, and in the state that the other two feeding points 1211 are connected with the excitation signal, based on the orthogonal polarization state of the two radiation elements 121 to which the two feeding points 1211 belong, the intensity of the echo signal is improved, so as to form an integral structure of the transmitting antenna and the receiving antenna in a transceiving separated form.
Corresponding to fig. 10E, based on the combination of the transmitting antenna illustrated in fig. 2B and the receiving antenna illustrated in fig. 9B, a structure of the transmitting antenna and the receiving antenna integrated with each other is illustrated in a structure in which the transmitting antenna and the receiving antenna share the ground reference 11, wherein the structure of the transmitting antenna and the receiving antenna integrated with each other has the ground reference 11 and the radiation source 12, wherein the radiation source 12 is disposed on one side of the ground reference 11 in a state spaced apart from the ground reference 11, wherein the radiation source 12 is disposed in a quaternary radiation source configuration, and the radiation source 12 has four radiation elements 121, wherein each of the radiation elements 121 has a feeding point 1211, the angle between the feeding point 1211 of any two adjacent radiating elements 121 and the connecting line between the physical central points 1212 of the two adjacent radiating elements 121 is equal to 90 ° in the circumferential arrangement direction of the radiating elements 121, wherein the two feeding points 1211 of the two radiating elements 121 opposite in the circumferential arrangement direction of the radiating elements 121 are used as transmitting feeding points, and through a phase difference feeding mode, the two feeding points 1211 are connected with excitation signals with a phase difference larger than 90 ° to realize differential feeding on the transmitting antenna 10, and the other two feeding points 1211 output the echo signals in a balanced differential signal form, so as to correspondingly form an integrated structure of the transmitting antenna and the receiving antenna in a transceiving separation mode.
In particular, in the two embodiments of the present invention corresponding to fig. 10D and 10E, in the circumferential arrangement direction of the radiation elements 121, in two opposite radiation elements 121, the connection line from the feeding point 1211 to the physical central point 1212 of one radiation element 121 is staggered and opposite to the connection line from the feeding point 1211 to the physical central point 1212 of the other radiation element 121, and the feeding point 1211 and the connection line from the physical central point 1212 of each radiation element 121, which are correspondingly formed, intersect to form a regular quadrilateral structure, so as to facilitate reducing the radial area occupied by the arrangement of the radiation elements 121.
Corresponding to fig. 10F, on the basis of the receiving antenna illustrated in fig. 8C, the transmitting antenna provided in an orthogonal polarization form is combined for the purpose of improving the intensity of the echo signal, and in a structural form in which the transmitting antenna and the receiving antenna share the reference ground 11A, an integrated structure of the transmitting antenna and the receiving antenna is illustrated, wherein the transmitting antenna and the receiving antenna are respectively provided in the half-wave folded-back type directional microwave detecting antenna 10A of an orthogonally polarized horizontal structure, the half-wave folded-back type directional microwave detecting antenna 10A includes four half-wave vibrators 12A, wherein the four half-wave vibrators 12A are arranged circumferentially and satisfy the circumferential arrangement direction of the half-wave vibrators 12A, any two adjacent half-wave vibrators 12A are arranged orthogonally, corresponding to a height direction of the half-wave folded-back type directional microwave detecting antenna 10A in a direction perpendicular to the reference ground 11A direction, in the circumferential arrangement direction of the half-wave oscillators 12A, any two adjacent half-wave oscillators 12A are perpendicular to each other in the extending direction perpendicular to the height direction of the half-wave folded directional microwave detection antenna 10A, wherein the feeding point 121A of one half-wave oscillator 12A is connected with a phase shifter via the feeding line 13A, so that the echo signal inputted from the feeding point 121A is phase-shifted by the phase shifter, the echo signal in a balanced differential signal form is outputted between one end of the phase shifter remote from the feeding point 121A and another feeding point 121A adjacent to the feeding point 121A in the circumferential arrangement direction of the half-wave oscillator 12A, and in a state where the other two feeding points 121A are inputted with excitation signals, based on a structural form in which the two half-wave oscillators 12A to which the two feeding points 121A belong are orthogonally arranged, and improving the strength of the echo signal so as to form an integral structure of the transmitting antenna and the receiving antenna in a transceiving separation mode.
Corresponding to fig. 10G, on the basis of the receiving antenna illustrated in fig. 9C, the transmitting antenna provided in a reverse polarization form is combined for the purpose of improving the accuracy of the echo signal, and an integrated structure of the transmitting antenna and the receiving antenna is illustrated in a structural form in which the transmitting antenna and the receiving antenna share the reference ground 11A, wherein the transmitting antenna and the receiving antenna are respectively provided in the half-wave folded-back type directional microwave detecting antenna 10A of a horizontal type structure in reverse polarization, the corresponding half-wave folded-back type directional microwave detecting antenna 10A includes four half-wave elements 12A, wherein the four half-wave elements 12A are arranged in the circumferential direction and satisfy that in the circumferential direction of the half-wave elements 12A, any two adjacent half-wave elements 12A are arranged orthogonally, correspondingly, the direction perpendicular to the reference ground 11A is taken as the height direction of the half-wave folded-back directional microwave detection antenna 10A, in the circumferential arrangement direction of the half-wave oscillators 12A, any two adjacent half-wave oscillators 12A are perpendicular to each other in the extension direction perpendicular to the height direction of the half-wave folded-back directional microwave detection antenna 10A, wherein two feeding points 121A of the two half-wave oscillators 12A opposite to the circumferential arrangement direction of the half-wave oscillators 12A are taken as transmission feeding points, and in a phase difference feeding manner, the two feeding points 121A are connected with excitation signals with a phase difference larger than 90 ° to realize differential feeding to the transmission antenna, and echo signals in a balanced differential signal form are output from the other two feeding points 121A, so as to correspondingly form an integrated structure of the transmission antenna and the reception antenna in a transceiving separation form.
Corresponding to fig. 10H, on the basis of the receiving antenna illustrated in fig. 8D, the transmitting antenna configured in an orthogonal polarization form is combined, specifically, the receiving antenna is the transmitting antenna, and an integrated structure of the transmitting antenna and the receiving antenna is illustrated, wherein the transmitting antenna and the receiving antenna are configured in the half-wave folded-back directional microwave detecting antenna 10A of a vertical structure of the same orthogonal polarization, the half-wave folded-back directional microwave detecting antenna 10A includes two half-wave oscillators 12A, two half-wave oscillators 12A are orthogonally arranged, and an extending direction of the two half-wave oscillators 12A in a direction perpendicular to a height direction of the half-wave folded-back directional microwave detecting antenna 10A is perpendicular to a direction perpendicular to the reference ground 11A, one of the feeding ends 1211A of the half-wave oscillators 12A is connected to a phase shifter through the feeding line 13A, so as to output the echo signal in a balanced differential signal form between one end of the phase shifter, which is far away from the feeding end 1211A of the half-wave oscillator 12A, and one of the feeding ends 1211A of the other half-wave oscillator 12A based on the phase shift processing of the echo signal accessed from the feeding end 1211A by the phase shifter, and to increase the intensity of the echo signal based on the structural form that the two half-wave oscillators 12A to which the two feeding ends 1211A belong are orthogonally arranged in a state that the other two feeding ends 1211A are accessed to an excitation signal, thereby forming an integrated structure of the transmitting antenna and the receiving antenna in a transceiving form.
Corresponding to fig. 10I, based on the combination of the transmitting antenna illustrated in fig. 3A and the receiving antenna illustrated in fig. 9D, an integrated structure of the transmitting antenna and the receiving antenna is illustrated in a structural form in which the transmitting antenna and the receiving antenna share the ground reference 11A, wherein the transmitting antenna and the receiving antenna are respectively provided with the half-wave folded-back directional microwave detection antenna 10A of a vertical structure of opposite-phase polarization, the integrated structure corresponding to the transmitting antenna and the receiving antenna includes two half-wave elements 12A, wherein each of the half-wave elements 12A is arranged in opposite phase, and the two half-wave elements 12A are arranged orthogonally to each other, corresponding to a height direction of the half-wave folded-back directional microwave detection antenna 10A perpendicular to the ground reference 11A direction, each of the half-wave elements 12A is reversed from the two feeding terminals 1211A in an extending direction perpendicular to the height direction of the half-wave folded-back directional microwave detection antenna 10A, and the two half-wave elements 12A are arranged in an extending direction perpendicular to each other in a direction perpendicular to the feeding terminal 1211 of the two half-wave folded-back directional microwave detection antenna 10A direction, wherein a differential signal transmission and reception signals are transmitted and received by the two half-wave elements 12A are arranged in a manner such that the two half-wave excitation antenna 12A are balanced in a phase difference in a state.
In particular, in correspondence to the integrated structure of the transmitting antenna and the receiving antenna illustrated in fig. 10H and 10I, each half-wave element 12A is shifted backward from the two feeding ends 1211A in the extending direction perpendicular to the height direction of the half-wave backfolding type directional microwave detecting antenna 10A, wherein the state in which the two half-wave elements 12A are orthogonally arranged corresponds to the state in which the four feeding ends 1211A are located at the four vertex positions of the square in which the connecting line of the two feeding ends 1211A of each half-wave element 12A is a double diagonal line, so as to maintain the state in which the distance between the two feeding ends 1211A of each half-wave element 12A is equal to or less than λ/4 and the distance between the two ends of each half-wave element 12A is equal to or greater than λ/128 and equal to or less than λ/6, which is advantageous for ensuring the state in which the two half-wave elements 12A are orthogonally arranged, based on the fact that the distance between the two feeding ends 1211A of each half-wave element 12A in the extending direction perpendicular to the height direction of the half-wave backfolding type directional microwave detecting antenna 10A from the two feeding ends 1211A of each half-wave elements 12A is limited by the displacement of the feeding ends 1211A and the corresponding half-wave element 12A, and the stability of the receiving antenna 12A is prevented.
Corresponding to fig. 10J, on the basis of the receiving antenna illustrated in fig. 9E, based on the purpose of improving the accuracy of the echo signal, based on the transceiving reciprocity characteristic of the antenna, the receiving antenna is the transmitting antenna, and the integrated structure of the transmitting antenna and the receiving antenna is illustrated, wherein the receiving antenna is exemplified by the double feed differential antenna 10B, and based on the structural characteristic that the two coupling sections 122B of the two strip-shaped elements 12B extend from the proximal end in opposite directions and can be coupled with each other to form a common resonant frequency point, the two strip-shaped elements 12B are formed in a structural state in which they are arranged in opposite phases in the polarization direction tending to linear polarization, so that the echo signal in the form of a balanced differential signal can be directly output at the two feed ends 121B when the double feed differential antenna 10B is used as the receiving antenna, and the transmitting antenna and receiving antenna are integrated in the form of the transmitting antenna and receiving antenna by switching in the two feed ends 121B of the two strip-shaped elements 12B in a state in which excitation signals differ by more than 90 °.
Corresponding to the above description, according to the present invention, the microwave detection method includes the following steps:
A. feeding the transmitting antenna with an excitation signal with a phase difference larger than 90 degrees in the polarization direction of the transmitting antenna tending to linear polarization by a phase difference feeding mode so as to realize differential feeding of the transmitting antenna with the phase difference larger than 90 degrees;
B. accessing the echo signals with phase difference of about 180 degrees and in a balanced differential signal form from the receiving antenna; and
C. outputting the doppler intermediate frequency signal in a single-ended signal form with a frequency/phase difference between the excitation signal and the echo signal in a mixing processing step and a differential-to-single-ended processing step based on step (C1) or step (C2), wherein in step (C1), the echo signal in a single-ended signal form is output based on the differential-to-single-ended processing of the echo signal in a balanced differential signal form by the differential-to-single-ended circuit, and the doppler intermediate frequency signal in a single-ended signal form is output based on the mixing processing of the excitation signal and the echo signal in a balanced differential signal form by the mixing circuit, wherein in step (C2), the doppler intermediate frequency signal in a balanced differential signal form is output based on the mixing processing of the excitation signal and the echo signal in a balanced differential signal form by the mixing circuit, and the doppler intermediate frequency signal in a single-ended signal form is output based on the differential-to-single-ended processing of the doppler intermediate frequency signal in a balanced differential signal form by the differential-to single-ended circuit.
In some embodiments of the present invention, corresponding to fig. 2A, the transmitting antenna is configured with a ground reference 11 and a radiation source 12 in a planar patch antenna configuration, wherein the radiation source 12 is configured on one side of the ground reference 11 in a spaced state from the ground reference 11, the radiation source 12 is configured in a unit radiation source configuration, the radiation source 12 has a single number of radiation elements 121, the radiation element 121 has two feeding points 1211, wherein the two feeding points 1211 are arranged in an inverted phase, a connection direction corresponding to one of the feeding points 1211 to a physical central point 1212 of the radiation element 121 and a connection direction corresponding to the other of the feeding points 1211 to a physical central point 1212 of the radiation element 121 coincide with each other, and then the radiation element 121 has a polarization configuration of linear polarization in a state where the feeding points 1211 are connected to an excitation signal and uses the connection direction of the two feeding points 1211 as a linear polarization direction, and thus in a manner of phase-difference feeding, and the two feeding points 1211 of the radiation element 121 are connected to a polarization state of the excitation signal having a phase difference of more than 90 ° to realize a differential feeding to the transmitting antenna with the polarization direction of the transmitting antenna.
In some embodiments of the present invention, corresponding to fig. 2B, the transmitting antenna is configured with a ground reference 11 and a radiation source 12 in a planar patch antenna configuration, wherein the radiation source 12 is configured on one side of the ground reference 11 in a spaced state from the ground reference 11, the radiation source 12 is configured in a binary radiation source configuration, the radiation source 12 has two radiation elements 121, each of the radiation elements 121 has a feeding point 1211, two of the radiation elements 121 are arranged in an inverted phase, a direction of a connection line from the feeding point 1211 to a physical central point 1212 of one of the radiation elements 121 is opposite to a direction of a connection line from the feeding point 1211 to a physical central point of the other radiation element 121, and then two of the radiation elements 121 have a linear polarization configuration in a state where two of the feeding points 1211 are connected to an excitation signal, and have a linear polarization direction of the feeding point 1211 as a linear polarization direction, so that a differential feeding is realized in a state where two of the feeding points 1211 of two radiation elements 121 are connected to the excitation signal with a difference of more than 90 ° in the linear polarization direction of the transmitting antenna.
In some embodiments of the present invention, corresponding to fig. 3A, the transmitting antenna is configured as the half-wave folded directional microwave detecting antenna of a vertical structure, and includes a ground reference 11A, a half-wave oscillator 12A and two feeding lines 13A, wherein the half-wave oscillator 12A has an electrical length of 1/2 or more and 3/4 or less wavelength, and has two coupling sections 121A, each of the coupling sections 121A has an electrical length of 1/6 or more wavelength, one end of each of the coupling sections 121A is named as the feeding end 1211A of the coupling section 121A, and the other end of each of the coupling sections 121A is used as the two ends of the half-wave oscillator 12A, wherein the distance between the two feeding ends 1211A is λ/4 or less, the distance between the two ends of the half-wave oscillator 12A is λ/128 or more and λ/6 or less, the half-wave oscillator 12A is in a state that the two feeding ends 1211A are respectively connected to two poles of an excitation signal or connected to an excitation signal with a phase difference to be fed, two ends of the half-wave oscillator 12A can form a phase difference to be mutually coupled to form a polarization form tending to linear polarization, and when the direction perpendicular to the reference ground 11A is the height direction of the half-wave folded directional microwave detecting antenna 10A, the extending direction of the half-wave oscillator 12A in the direction perpendicular to the height direction of the half-wave folded directional microwave detecting antenna 10A is a linear polarization direction, so that differential feeding to the transmitting antenna is realized in the linear polarization direction of the transmitting antenna in a state that the two feeding ends 1211A of the half-wave oscillator are connected to the excitation signal with a phase difference of more than 90 ° in a manner of phase difference feeding.
In some embodiments of the present invention, the transmitting antenna is disposed corresponding to the half-wave folded-back directional microwave detecting antenna 10A of the horizontal structure with reverse polarization of the receiving antenna illustrated in fig. 9C, and the half-wave folded-back directional microwave detecting antenna 10A includes two half-wave oscillators 12A, wherein the two half-wave oscillators 12A are arranged in reverse phase, and corresponding to the height direction of the half-wave folded-back directional microwave detecting antenna 10A perpendicular to the reference ground 11A direction, the two half-wave oscillators 12A are reversed in the extending direction perpendicular to the height direction of the half-wave folded-back directional microwave detecting antenna 10A from the feeding point 121A, based on the structural state that the two half-wave oscillators 12A are arranged in reverse phase, in a state that the two feeding points 121A are fed with the excitation signals having the phase difference, the two half-wave oscillators 12A can form the phase difference to mutually couple and form a polarization form tending to linear polarization, and when the direction perpendicular to the reference ground 11A is the height direction of the half-wave folded-back directional microwave detecting antenna 10A, the extending direction of the half-wave oscillators 12A in the height direction perpendicular to the half-wave folded-back directional microwave detecting antenna 10A is the linear polarization direction, so that in a manner of feeding by the phase difference, the differential feeding to the transmitting antenna is realized in the linear polarization direction of the transmitting antenna in a state that the two feeding points 121A are fed with the excitation signals having the phase difference larger than 90 °.
In some embodiments of the present invention, corresponding to fig. 4A to 4N, the transmitting antenna is configured as the double-fed differential antenna, and the transmitting antenna includes a reference ground 11B and two strip-shaped elements 12B, wherein two ends of an access excitation signal of the two strip-shaped elements 12B are respectively the feeding ends 121B of the two strip-shaped elements 12B, the two strip-shaped elements 12B extend from the two feeding ends 121B in the same lateral space of the reference ground 11B and respectively have a wavelength electrical length greater than or equal to 3/16 and less than or equal to 5/16, wherein the two strip-shaped elements 12B respectively have a coupling section 122B, wherein one end of the coupling section 122B close to the feeding end 121B of the strip-shaped element 12B to which the coupling section belongs is a proximal end of the coupling section 122B, the two coupling sections 122B extend from the proximal end in a facing direction, so as to form a structural form that the two coupling sections 122B extend from the proximal ends in the facing direction based on a phase difference between two feeding ends of the two strip-shaped elements 12B having a phase difference, and polarization of the two feeding excitation signals of the two coupling sections 122B are formed by a polarization mode that the phase difference of the feeding line polarization of the feeding line excitation signal tends to be greater than 90 ° of the feeding line.
In some embodiments of the present invention, wherein in the step (a), the transmitting power of the transmitting antenna is less than or equal to 0dBm.
In response to the above description, the microwave detection method according to another embodiment of the present invention includes the following steps:
A. setting a transmit power of the transmit antenna at a target transmit power of less than or equal to 0dBm based on a corresponding parameter setting of an excitation signal;
B. accessing the echo signals with phase difference of 180 degrees and in a balanced differential signal form from the receiving antenna; and
C. outputting the doppler intermediate frequency signals in a single-ended signal form with a frequency/phase difference between the excitation signals and the echo signals in a mixing processing step and a differential-to-single-ended processing step based on step (C1) or step (C2), wherein in step (C1), the echo signals in a single-ended signal form are output based on a differential-to-single-ended processing of the echo signals in a balanced differential signal form by the differential-to-single-ended circuit, and the doppler intermediate frequency signals in a single-ended signal form are output based on a mixing processing of the echo signals in the excitation signals and the balanced differential signal form by the mixing circuit, wherein in step (C2), the doppler intermediate frequency signals in a balanced differential signal form are output based on a mixing processing of the excitation signals and the echo signals in the balanced differential signal form by the mixing circuit, and the doppler intermediate frequency signals in a differential-to single-ended signal form are output based on a differential-to-single-ended processing of the doppler intermediate frequency signals in a balanced differential signal form by the differential-to single-ended circuit.
In some embodiments of the present invention, in the step (a), the circular polarization form of the transmitting antenna is implemented and the minimum transmitting power extreme value of the transmitting antenna is reduced by means of phase difference feeding.
In some embodiments of the present invention, in the step (a), in a manner of phase difference feeding, the polarization direction of the transmitting antenna tending to linear polarization feeds the transmitting antenna with an excitation signal greater than 90 ° phase difference, so as to implement differential feeding greater than 90 ° phase difference for the transmitting antenna.
In the description herein, references to the description of the term "one embodiment," "some embodiments," "an example," "a specific example," or "some examples," etc., mean that a particular feature, structure, material, or characteristic described in connection with the embodiment or example is included in at least one embodiment or example of the invention. In this specification, the terminology used in the description above is not necessarily meant to be the same embodiment or example. Furthermore, the particular features, structures, materials, or characteristics described may be combined in any suitable manner in any one or more embodiments or examples. Furthermore, various embodiments or examples and features of different embodiments or examples described in this specification can be combined and combined by one skilled in the art without contradiction.
It will be understood by those skilled in the art that the embodiments of the present invention as described above and shown in the drawings are given by way of example only and are not limiting of the present invention. The objects of the present invention have been fully and effectively accomplished. The functional and structural principles of the present invention have been shown and described in the embodiments without departing from the principles, embodiments of the present invention may have any deformation or modification.

Claims (10)

1. Microwave detection device, its characterized in that includes:
a transmitting antenna, wherein the transmitting antenna is configured to transmit a microwave beam corresponding to a frequency of an excitation signal in a state of being fed by the excitation signal;
a receiving antenna, wherein the receiving antenna is configured as a planar patch antenna and has a ground reference and a radiation source, wherein the radiation source is configured as a binary radiation source, the radiation source has two radiation elements corresponding to the radiation source, each of the radiation elements has a feeding point, the two radiation elements are arranged in opposite phases, a connection line from the feeding point to a physical center point of one of the radiation elements is opposite to a connection line from the feeding point to a physical center point of the other radiation element, and based on a structural state that the two radiation elements are arranged in opposite phases, an echo signal in a balanced differential signal form is output at the two feeding points after receiving a reflected echo formed after the microwave beam is reflected by a corresponding object, the echo signal includes a signal corresponding to a reflected echo formed after the microwave beam is reflected by the corresponding object, and electromagnetic interference in an environment exists in a common mode interference form in the echo signal and can be suppressed during receiving and transmitting the echo signal in the balanced differential signal form; and
a mixing circuit, wherein the mixing circuit is configured to output a doppler intermediate frequency signal of a balanced differential signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal based on a mixing process of the excitation signal and the echo signal of the balanced differential signal form in a state of accessing the excitation signal and the echo signal of the balanced differential signal form.
2. A microwave detection apparatus as claimed in claim 1 wherein at least one of the radiating elements is electrically connected to the reference ground at its physical centre point.
3. The microwave detecting device according to claim 2, wherein the radiating element has at least one set and/or at least one pair of grounding points electrically connected to the reference ground, wherein the same set of grounding points is located at each vertex of the same regular polygon with the physical center point of the radiating element as a midpoint, and each grounding point corresponding to the same set of grounding points is arranged at an equal angle around the physical center point of the radiating element in a state of being equidistant from the physical center point of the radiating element, wherein the same pair of grounding points are symmetrically distributed on the radiating element with the physical center point of the radiating element, and a connecting line segment corresponding to the same pair of grounding points forms a zero potential point with the physical center point of the radiating element as a midpoint based on the electrical connection relationship between the grounding points and the reference ground to form a point equivalent to the physical center point of the radiating element and electrically connected to the reference ground.
4. A microwave detecting device according to any one of claims 1 to 3, wherein the transmitting antenna is configured in a planar patch antenna configuration to have a reference ground and a radiation source, wherein the radiation source is configured in a state spaced apart from the reference ground on one side of the reference ground, the radiation source is configured in a binary radiation source configuration, the radiation source has two radiating elements, each of the radiating elements has a feeding point, the two radiating elements are arranged in an inverted phase, and a connecting line direction from the feeding point to a physical central point of one of the radiating elements is opposite to a connecting line direction from the feeding point to a physical central point of the other radiating element, so that the two feeding points are connected with an excitation signal to realize feeding to the transmitting antenna.
5. The microwave detecting apparatus according to claim 4, wherein the transmitting antenna and the receiving antenna are integrally disposed in a transceiving split manner based on a structural configuration sharing the reference ground, the transmitting antenna and the receiving antenna integrally disposed in the transceiving split manner include one reference ground and one radiation source, wherein the radiation source is disposed in a quaternary radiation source configuration and has four radiating elements, each of the radiating elements has a feeding point, each of the radiating elements is circumferentially arranged and satisfies a circumferential arrangement direction of the radiating element, an included angle between a connecting line between the feeding point of any two adjacent radiating elements and a physical central point thereof is equal to 90 °, wherein two feeding points of two radiating elements opposite to each other in the circumferential arrangement direction of the radiating element are transmitting feeding points, so that an excitation signal is input to the two feeding points to realize feeding of the transmitting antenna, and the other two feeding points output the echo signals in a balanced differential signal configuration, so as to correspondingly form an integral structure of the transmitting antenna and the receiving antenna in the transceiving split manner.
6. The microwave detecting device according to claim 5, wherein in the circumferential arrangement direction of the radiating elements, in two opposite radiating elements, a connecting line from the feeding point to a physical central point of one of the radiating elements is staggered and opposite to a connecting line from the feeding point to a physical central point of the other radiating element, so that the feeding point of each radiating element and the connecting line of the physical central point intersect to form a regular quadrilateral structure.
7. The microwave detecting device according to claim 4, wherein the transmitting antenna and the receiving antenna are integrally provided in a transceiving integrated form based on a structural form that shares the reference ground and the radiation source, the transmitting antenna and the receiving antenna integrally provided in the transceiving integrated form include one of the reference ground and one of the radiation sources, wherein the radiation source is provided in a binary radiation source form, the radiation source has two radiation elements, each of the radiation elements has one of the feeding points, the two radiation elements are arranged in an inverted phase, so that an excitation signal is input to the two feeding points to realize feeding of the transmitting antenna, and the echo signal in a balanced differential signal form is output to the two feeding points of the two radiation elements, thereby forming an integrated structure of the transmitting antenna and the receiving antenna in the transceiving integrated form.
8. The microwave detection apparatus according to claim 4, wherein the microwave detection apparatus further comprises at least one amplifying circuit adapted to amplify a signal in a differential signal form, wherein the amplifying circuit is disposed between the receiving antenna and the mixing circuit to amplify and output the echo signal in a balanced differential signal form to the mixing circuit.
9. A microwave detection arrangement according to claim 8, wherein the microwave detection arrangement further comprises a further amplification circuit adapted to amplify signals in differential signal form, wherein the amplification circuit is arranged in connection with the mixing circuit to amplify the doppler intermediate frequency signals in output balanced differential signal form.
10. A microwave detection arrangement according to claim 4, wherein the microwave detection arrangement further comprises at least one amplification circuit adapted to amplify a signal in the form of a balanced differential signal, wherein the amplification circuit is arranged in connection with the mixing circuit to amplify the Doppler intermediate frequency signal in the form of an output balanced differential signal.
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