CN109215583B - 数据驱动器和有机发光显示装置 - Google Patents

数据驱动器和有机发光显示装置 Download PDF

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CN109215583B
CN109215583B CN201711376515.1A CN201711376515A CN109215583B CN 109215583 B CN109215583 B CN 109215583B CN 201711376515 A CN201711376515 A CN 201711376515A CN 109215583 B CN109215583 B CN 109215583B
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data
compensation
voltage
input
light emitting
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CN109215583A (zh
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金泰勋
权奇泰
金奎珍
金池娥
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LG Display Co Ltd
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Abstract

本公开涉及数据驱动器以及有机发光显示装置。该数据驱动器包括：输入单元，被配置为接收输入数据；补偿数据生成器，被配置为通过对输入数据应用补偿值来生成补偿数据；转换单元，被配置为将输入数据转换成图像数据电压以及将补偿数据转换成补偿数据电压；以及输出单元，被配置为将图像数据电压和补偿数据电压分开地输出至有机发光显示器的数据线。

Description

数据驱动器和有机发光显示装置
技术领域
本发明涉及有源矩阵有机发光显示装置。
背景技术
有源矩阵型电致发光显示装置包括自发光有机发光二极管(OLED)并且具有响应时间快、发光效率高、高亮度以及宽视角的优点。
用作自发光元件的OLED包括阳极电极、阴极电极以及形成在阳极电极与阴极电极之间的有机化合物层。有机化合物层包括空穴注入层HIL、空穴传输层HTL、发光层EML、电子传输层ETL以及电子注入层EIL。当向阳极电极和阴极电极施加驱动电压时，穿过空穴传输层HTL的空穴和穿过电子传输层ETL的电子迁移至发光层EML并且形成激子。结果，发光层EML产生可见光。
有机发光显示装置包括用于控制在OLED中流动的驱动电流的驱动薄膜晶体管(TFT)。期望驱动TFT被设计成在每个像素处具有相同的电特性如阈值电压和迁移率。然而，由于工艺条件和驱动环境，在每个像素处电特性不一致。为此，在每个像素处根据相同数据电压的驱动电流不同，这导致像素之间的亮度差异。为了解决这个问题，存在用于感测每个像素中的驱动TFT的特性参数(阈值、迁移率)并且基于感测结果适当地补偿输入数据以降低亮度的不均匀性的图像质量补偿技术。
图像质量补偿技术的内部补偿方法是控制像素结构和操作定时，以在有机发光二极管发光时消除驱动TFT的电特性的影响。基本上，内部补偿方法是执行采样，其中，以源极跟随器方法将驱动TFT的栅电压增加为在预定电平饱和。为了使驱动TFT的栅电压在预定电平饱和，需要足够长的时间。然而，由于显示面板倾向于具有大屏幕和高分辨率，因此减少了用于对一个像素线进行采样的时间，因此不能顺利地执行采样操作。
发明内容
根据一个实施例，提供一种用于OLED的数据驱动器。该数据驱动器包括：输入单元，被配置为接收输入数据；补偿数据生成器，被配置为通过将补偿值应用至输入数据来生成补偿数据；转换单元，被配置为将输入数据转换成图像数据电压以及将补偿数据转换成补偿数据电压；以及输出单元，被配置为将图像数据电压和补偿数据电压分开地输出至有机发光显示器的数据线。
根据另一个实施例，提供一种包括根据本公开的实施例的数据驱动器的OLED装置。
附图说明
附图示出了本发明的实施方式并且与描述一起用于说明本发明的原理，附图被包括以提供对本发明的进一步理解并且被并入且构成本说明书的一部分。在附图中：
图1是示出根据本发明的实施方式的有机发光显示装置的图；
图2是示出像素的示例的图；
图3是根据本发明的实施方式的像素的电路图；
图4是示出用于驱动图3所示的像素的栅极信号的定时的图；
图5是示出图3所示的第一节点的电压的变化的图；
图6是示出根据本发明的第一实施方式的数据驱动器的图；
图7是示出图6所示的第一控制信号和第二控制信号的定时的图；
图8是示出根据本发明的第一实施方式的在初始化时段和采样时段中第一节点的电压的变化的图；
图9是示出根据本发明的第二实施方式的数据驱动器的图；以及
图10是示出根据本发明的第三实施方式的数据驱动器的图。
具体实施方式
现在将详细参考本发明的实施方式，实施方式的示例在附图中示出。在可能的情况下，将贯穿附图使用相同的附图标记来指代相同或相似的部件。如果确定现有技术可能误导本发明的实施方式，则将省略对现有技术的详细描述。
在下文中，将参考附图来描述本发明的实施方式。
图1是示出根据本发明的实施方式的有机发光显示装置的图。
参考图1，根据本发明的实施方式的有机发光显示装置包括：显示面板10、数据驱动器12、栅极驱动器13以及定时控制器11。
多个数据线14和多个栅极线15在显示面板10上彼此交叉，并且以矩阵形式在交点处布置像素P。从附图中未示出的电力生成器向像素P中的每个像素供应高电势驱动电压VDD和低电势驱动电压VSS。
基于定时信号如垂直同步信号Vsync、水平同步信号Hsync、点时钟信号DCLK和数据使能信号DE，定时控制器11生成用于控制数据驱动器12的操作定时的数据控制信号DCC和用于控制栅极驱动器13的操作定时的栅极控制信号GDC。
另外，定时控制器11包括补偿值设置单元100。补偿值设置单元100计算从数据驱动器12输出的补偿数据电压的放大率。补偿数据电压用于在感测时段期间感测驱动薄膜晶体管(TFT)的阈值电压的过程中的过驱动，稍后将提供其详细描述。
在补偿时段期间，数据驱动器12向像素P供应感测数据电压，将通过数据线14从显示面板10接收的感测电压转换成数字值，以及向定时控制器11供应数字值。在图像显示时段期间，数据驱动器12向数据线14供应图像显示数据电压。
栅极驱动器13可以基于来自定时控制器11的栅极控制信号GDC来生成栅极信号，栅极信号可以包括扫描信号和发射信号。取决于像素结构，栅极信号可以不同并且在补偿时段期间应用的栅极信号的定时与在图像显示时段期间应用的栅极信号的定时不同。可以通过面板内栅极驱动器(GIP)处理在显示面板10上直接形成栅极驱动器13。
在图2中，(a)和(b)示出了根据本发明的实施方式的像素结构的示例。
参考图2中的(a)，一个像素包括开关晶体管SW、驱动TFT DT、补偿电路CC以及有机发光二极管(OLED)。OLED进行操作以由于驱动TFT DT所形成的驱动电流而发光。
响应于通过第一栅极线GL供应的栅极信号，开关晶体管SW执行开关操作，使得通过第一数据线DL供应的数据信号被作为数据电压存储在电容器中。取决于存储在电容器中的数据电压，驱动TFT DT进行操作以使驱动电流在高电势电力线VDD与低电势电力线GND之间流动。补偿电路CC是用于对驱动TFT DT的阈值电压进行补偿的电路。另外，连接至开关晶体管SW或驱动TFT DT的电容器可以位于补偿电路CC内。
补偿电路CC包括一个或更多个薄膜晶体管(TFT)和电容器。补偿电路CC的配置可以取决于补偿方法而变化，此处省略其详细示例和描述。
另外，如图2的(b)所示，当包括补偿电路CC时，像素还可以包括信号线和电力线以在驱动补偿TFT时供应特定信号或电力。附加信号线可以被限定为用于驱动像素中包括的补偿TFT的第二栅极线SL2。另外，附加电力线可以被限定为用于将像素的特定节点初始化为特定电压的初始化电力线INIT。然而，这些仅是示例性的，并且本发明的各方面不限于此。
图3是示出执行内部补偿的像素的示例的图。此处，在图3所示的像素内实现的内部补偿方法将被描述为如下。
参考图3，根据本发明的实施方式的像素包括：驱动TFT、第一晶体管T1至第六晶体管T6以及存储电容器Cst。
基于驱动TFT DT的源栅电压Vsg，驱动TFT DT控制要施加至OLED的驱动电流。驱动TFT DT包括：连接至第一节点N1的栅电极、连接至第三节点N3的源电极以及连接至第二节点N2的漏电极。响应于第n个扫描信号SCAN(n)，第一晶体管T1连接第一节点N1与第二节点N2。响应于第n个扫描信号SCAN(n)，第二晶体管T2连接数据线14与第三节点N3。响应于第n个发射信号EM(n)，第三晶体管T3连接第三节点N3与高电势驱动电压VDD的输入端子。响应于第n个发射信号EM(n)，第四晶体管T4连接第二节点N2与第四节点N4。响应于第n-1个扫描信号SCAN(n-1)，第五晶体管T5连接第一节点N1与初始化电压Vinit的输入端子。响应于第n个扫描信号SCAN(n)，第六晶体管T6连接初始化电压Vinit的输入端子与第四节点N4。另外，存储电容器Cst连接在第一节点N1与高电势驱动电压VDD的输入端子之间。
图4是示出用于驱动图3所示的像素的栅极信号的定时的图。参考图3和图4，对像素的操作被描述为如下。
在初始化时段Ti中，第五晶体管T5响应于第n-1个扫描信号SCAN(n-1)来连接第一节点N1与初始化电压Vinit的输入端子。结果，第一节点N1被初始化为初始化电压Vinit。可以在充分低于OLED的操作电压的电压范围内选择初始化电压Vinit，并且可以将初始化电压Vinit设置为等于或低于低电势驱动电压VSS。
在采样时段Ts中，第一晶体管T1、第二晶体管T2以及第六晶体管T6响应于第n个扫描信号SCAN(n)而导通。结果，第一晶体管T1在第一节点N1与第二节点N2之间建立二极管连接。第二晶体管T2将第三节点N3充电至通过数据线DL供应的数据电压Vdata。第六晶体管T6将第四节点N4充电至初始化电压Vinit。
在采样时段Ts中，电流在驱动TFT DT的源电极与漏电极之间流动，并且因此，第二节点N2的电压变为Vdata-|Vth|，Vdata-|Vth|指示通过从数据电压Vdata减去驱动TFT DT的阈值电压Vth的绝对值而获得的值。第一节点N1变为具有与第二节点N2的电压相同的电压。
在发射时段Te中，第三晶体管T3响应于第n个发射信号EM(n)向第三节点N3供应高电势驱动电压VDD。第四晶体管T4导通以连接第二节点N2与第四节点N4。在发射时段Te中，由于驱动TFT DT的设置的栅源电压，因此产生从第三节点N3旁路至第二节点N2的电流。
在发射时段Te中在OLED中流动的电流IOLED可以由如下的等式1表示。
[等式1]
IOLED＝k/2(Vgs-Vth)2＝k/2(Vg-Vs-Vth)2＝k/2{(Vdata-|Vth|)-VDD-Vth)}2
此时，Vth＜0，因此，等式1可以被概括为“k/2(Vdata-VDD)2”。
在等式1中，k/2表示由驱动TFT DT的电子迁移率、寄生电容以及沟道电容确定的比例常数。在发射时段Te中，在OLED中流动的驱动电流不受驱动TFT DT的阈值电压Vth的影响。
为了排除在发射时段Te期间在内部补偿电路的操作中驱动TFT DT的阈值电压Vth的影响的任何可能性，第一节点应当在Vdata-|Vth|的值处充分地饱和。
然而，随着显示面板10的分辨率增加，用于驱动一个像素线的一个水平时段1H减小，并且因此，甚至采样时段Ts也减小。如图5所示，如果在一个水平时段1H的采样时段期间第一节点N1不能饱和至足够的值，则可能存在采样偏差ΔV，并且这可能造成内部补偿的误差。
根据本发明的补偿值设置单元100和数据驱动器12能够在短的采样时段内对驱动TFT的阈值电压更准确地进行采样。下面提供其描述。
定时控制器11设置补偿值α，补偿值α被用于产生补偿数据电压。补偿值α可以被计算为以下值，该值是电压Vsam与电压值Vsat之比，其中在一个水平时段1H的采样时段中电压Vsam对第一节点N1充电，在给定足够长的采样时段Ts的情况下第一节点N1在电压值Vsat处饱和。也就是说，补偿值α被计算为“Vsat/Vsam”。在第一水平时段1H期间在第一节点N1中充电的电压Vsam等于或小于第一节点N1饱和的电压值Vsat，并且因此，补偿值α大于1。可以将补偿值α设置为针对每个灰度等级相同或不同。
图1示出了补偿值设置单元100被包括在定时控制器11中的示例，但是补偿值设置单元100可以被包括在附加的集成电路(IC)中。
图6是示出根据本发明的第一实施方式的数据驱动器的图。图6示出了数据电压被输出至一个数据线的示例。
参考图6，根据第一实施方式的数据驱动器12包括锁存单元Latch1和Latch2、第一开关SW1、第一数模转换器DAC1、补偿数据生成器120、补偿锁存单元MLatch1和MLatch2、第二开关SW2、第二数模转换器DAC2以及输出缓冲器BF。锁存单元Latch1和Latch2包括第一锁存器Latch1和第二锁存器Latch2，并且补偿锁存单元MLatch1和MLatch2包括第一补偿锁存器MLatch1和第二补偿锁存器MLatch2。
第一锁存器Latch1采样并锁存从定时控制器11接收的数字图像数据Data，同时输出所有锁存的数据。第二锁存器Latch2锁存从第一锁存器Latch1接收的图像数据Data，同时与其他源极驱动器的第二锁存器Latch2同步地输出所有锁存的图像数据。
响应于第一控制信号S1，第一开关SW1连接第二锁存器Latch2与第一数模转换器DAC1。
第一数模转换器DAC1将从第二锁存器Latch2接收的图像数据Data转换成模拟数据电压Vdata。
补偿数据生成器120通过对从第一锁存器Latch1接收的数据应用补偿值α来产生补偿数据Mdata。可以按照数据乘以补偿值α来产生补偿数据Mdata。补偿数据生成器120将补偿数据Mdata输出至第一补偿锁存器MLatch1。
第一补偿锁存器MLatch1采样并锁存从补偿数据生成器120接收的补偿数据Mdata，同时输出所有锁存的数据。
第二补偿锁存器MLatch2锁存从第一补偿锁存器MLatch1接收的补偿数据Mdata，同时与其他源极驱动器的第二补偿锁存器MLatch2同步地输出所有锁存的补偿数据。
响应于第二控制信号S2，第二开关SW2可以连接第二补偿锁存器MLatch2与第二数模转换器DAC2。
第二数模转换器DAC2将从第二补偿锁存器MLatch2接收的补偿数据Mdata转换成模拟补偿数据电压MVdata。
输出缓冲器BF向数据线DL提供来自第一数模转换器DAC1的数据电压Vdata或来自第二数模转换器DAC2的补偿数据电压MVdata。
图7是示出图6所示的第一控制信号和第二控制信号的定时的图。图8是示出根据本发明的第一实施方式的在初始化时段和采样时段中第一节点的电压的变化的图。在第一实施方式中用于驱动像素的栅极信号与比较示例中的栅极信号相同。也就是说，可以使用图4所示的栅极信号来驱动图3所示的像素。
参考图3、图4、图6和图8，通过使用补偿数据电压进行的采样操作被描述为如下。
在初始化时段Ti中，第五晶体管T5响应于第(n-1)个扫描信号SCAN(n-1)来连接第一节点N1与初始化电压Vinit的输入端子。结果，第一节点N1被初始化为初始化电压Vinit。可以在充分低于OLED的操作电压的电压范围内选择初始化电压Vinit，并且可以将初始化电压Vinit设置为等于或低于低电势驱动电压VSS。
在第一采样时段Ts1和第二采样时段Ts2中，第一晶体管T1、第二晶体管T2和第六晶体管T6响应于第n个扫描信号SCAN(n)而导通。结果，第一晶体管T1在第一节点N1与第二节点N2之间建立二极管连接。
在第一采样时段Ts1期间，第二控制信号S2变为导通电压。结果，第二数模转换器DAC2从第二补偿锁存器MLatch2接收补偿数据Mdata，并且产生补偿数据电压MVdata。在第一采样时段Ts1期间，输出缓冲器BF向数据线DL输出补偿数据电压MVdata。
第二晶体管T2将第三节点N3充电为通过数据线DL供应的数据电压Vdata。补偿数据电压MVdata具有大于数据电压Vdata的值，因此，在第一采样时段Ts1期间将第三节点N3充电为大于数据电压Vdata的值。结果，由于过驱动效应，在第一采样时段Ts1中第一节点N1的电压具有大于对第三节点N3充电的数据电压Vdata的值。
在第二采样时段Ts2期间，第二控制信号S2变为关断电压，并且第一控制信号S1变为导通电压。结果，第一数模转换器DAC1从第一锁存器Latch1接收图像数据，并且产生图像数据电压Vdata。在第二采样时段Ts2期间，输出缓冲器BF向数据线输出图像数据电压Vdata。
第二晶体管T2将第三节点N3充电为通过数据线DL供应的数据电压。图像数据电压Vdata具有小于补偿数据电压MVdata的值，因此，在第二采样时段Ts2期间将第一节点N1充电为某电压的速度降低。特别地，由于图像数据电压Vdata是与由定时控制器11接收的图像数据Data对应的电压，因此可以在第二采样时段Ts2之后将第一节点N1准确地采样为具有值Vdata-|Vth|的电压，该值对应于期望的灰度级别。
在发射时段Te中，由于驱动TFT DT的设置的栅源电压，产生从第三节点N3旁路至第二节点N2的电流，并且OLED发射具有期望的灰度级别的光。
如上所述，根据本发明的数据驱动器12通过使用应用了补偿值α的补偿数据电压MVdata在第一采样时段Ts1期间执行采样操作，因此，采样操作可以被快速执行。因此，尽管一个水平时段1H减小，但是可以在采样时段期间将驱动TFT DT的栅源电压采样为具有反映阈值电压的准确值的电压Vsat。也就是说，如果一个水平时段1H减小，则在采样时段Ts1和Ts2期间将第一节点N1充电为Vsam的电压电平，因此，采样操作可能被不准确地执行。然而，根据本发明，由于第一采样时段Ts1的过驱动，可以将第一节点N1的电压采样为具有反映驱动TFT DT的阈值电压的准确值的电压Vsat。
特别地，期望本发明具有过驱动效应而不增加驱动频率。因此，如果仅通过增加数据电压来执行采样，则待采样的电压值可能超过期望的电平。为了防止这个问题，需要将在采样时段中施加的数据电压控制在与输入图像数据对应的电平。然而，确定有机发光显示装置的采样时段的扫描信号的脉冲宽度长度对应于最少一个水平时段，因此，需要增加驱动频率以执行两次采样。
相反，本发明被实现为使得数据驱动器12在一个水平时段1H内分别输出图像数据Data的图像数据电压Vdata和反映补偿值α的补偿数据电压MVdata。因此，可以在不增加驱动频率和改变扫描信号的定时的情况下执行过驱动。
图9是示出根据本发明的第二实施方式的数据驱动器的图。
参考图9，根据本发明的第二实施方式的数据驱动器12包括锁存单元Latch1、第一开关SW1、第一数模转换器DAC1、补偿数据生成器120、补偿锁存单元MLatch1、第二开关SW2、第二数模转换器DAC2以及输出缓冲器BF。也就是说，在第二实施方式中，锁存单元Latch1和补偿锁存单元MLatch1中的每个被实现为单个锁存器。第一实施方式和第二实施方式中的锁存单元的数目可以取决于数据驱动器的定时控制器的设计而变化。在第二实施方式中，补偿锁存单元MLatch1的操作与第一实施方式中所描述的相同，并且用于数据驱动器输出补偿数据电压的定时与第一实施方式中所描述的相同。
图10是示出根据本发明的第三实施方式的数据驱动器的图。
参考图10，根据本发明的第三实施方式的数据驱动器12包括锁存单元(Latch1、Latch2)、第一开关SW1、补偿数据生成器120、补偿锁存单元(MLatch1、MLatch2)、第二开关SW2、数模转换器DAC以及输出缓冲器BF。锁存单元(Latch1、Latch2)包括第一锁存器Latch1和第二锁存器Latch2，补偿锁存单元(MLatch1、MLatch2)包括第一补偿锁存器MLatch1和第二补偿锁存器MLatch2。当第一开关SW1导通时，数模转换器DAC将从第二锁存器Latch2接收的图像数据Data转换成模拟数据电压Vdata。当第二开关SW2导通时，数模转换器DAC将从第二补偿锁存器MLatch2接收的输入数据Mdata转换成模拟补偿数据电压MVdata。
同样地，在第三实施方式中，可以选择性地生成图像数据电压Vdata或补偿数据电压MVData，并且通过使用一个数模转换器DAC来输出所选择的电压。
图10所示的锁存单元和补偿锁存单元中的每个可以被实现为单个锁存器，这与第二实施方式相同。
虽然已经参考本发明的多个说明性实施方式描述了实施方式，但是应当理解的是，本领域技术人员可以设计出将落入本公开内容的原理的范围内的许多其他修改和实施方式。更具体地，在本公开内容、附图和所附权利要求的范围内，主组合布置的组成部件和/或布置中各种变化和修改是可能的。除了组成部件和/或布置的变化和修改之外，对于本领域技术人员而言替代用途还将是明显的。

Claims (10)

1.一种用于有机发光显示器的数据驱动器，所述数据驱动器包括：
输入单元，被配置为接收输入数据；
补偿数据生成器，被配置为通过对所述输入数据应用补偿值来生成补偿数据；
转换单元，被配置为将所述输入数据转换成图像数据电压以及将所述补偿数据转换成补偿数据电压；以及
输出单元，被配置为将所述图像数据电压和所述补偿数据电压分开地输出至所述有机发光显示器的数据线，
其中，所述输入单元包括：输入锁存器，被配置为锁存所述输入数据以及将所述输入数据提供至所述补偿数据生成器。
2.根据权利要求1所述的数据驱动器，
其中，所述输出单元被配置为在用于驱动所述有机发光显示器的一个像素线的一个水平周期内分开地输出所述图像数据电压和所述补偿数据电压。
3.根据权利要求1所述的数据驱动器，
其中，所述补偿数据生成器被配置为通过将所述输入数据乘以补偿值来生成所述补偿数据。
4.根据权利要求1所述的数据驱动器，
其中，所述输入数据和所述补偿值是从用于所述有机发光显示器的定时控制器接收的。
5.根据权利要求1所述的数据驱动器，
其中，所述输出单元包括：输出缓冲器，被配置为将所述图像数据电压或所述补偿数据电压提供给所述数据线。
6.根据权利要求1所述的数据驱动器，
其中，所述转换单元包括：第一数模转换器，用于将所述输入数据转换成所述图像数据电压；以及第二数模转换器，用于将所述补偿数据转换成所述补偿数据电压。
7.根据权利要求1所述的数据驱动器，
其中，所述转换单元包括：公共数模转换器，用于将所述输入数据转换成所述图像数据电压以及将所述补偿数据转换成所述补偿数据电压。
8.根据权利要求1所述的数据驱动器，其包括：
至少一个补偿锁存器，用于锁存所述补偿数据。
9.根据权利要求8所述的数据驱动器，还包括：
第一开关，被配置为响应于第一控制信号将所述输入锁存器与所述转换单元连接；以及
第二开关，被配置为响应于第二控制信号将所述补偿锁存器与所述转换单元连接。
10.一种有机发光显示装置，其包括根据权利要求1-9中任一项所述的数据驱动器。
CN201711376515.1A 2017-06-30 2017-12-19 数据驱动器和有机发光显示装置 Active CN109215583B (zh)

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