CN105229984A - Transposition modulating system, method and apparatus - Google Patents
Transposition modulating system, method and apparatus Download PDFInfo
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- CN105229984A CN105229984A CN201480012702.XA CN201480012702A CN105229984A CN 105229984 A CN105229984 A CN 105229984A CN 201480012702 A CN201480012702 A CN 201480012702A CN 105229984 A CN105229984 A CN 105229984A
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- H—ELECTRICITY
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- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
Abstract
The invention discloses for send, receive and demodulation transposition modulation signal, for increasing limit communication channel inromation bandwidth and for the system according to input control signal time delay shift input signal, method and apparatus.A kind of like this method increasing the inromation bandwidth limiting communication channel comprises the first modulation signal receiving and have first carrier signal frequency; Receive second modulation signal with the second frequency of carrier signal, the information of the second modulation signal independent of modulation first carrier signal is modulated, and the second carrier information frequency is relevant to first carrier signal frequency harmonic wave or subharmonic; And combine the first signal and secondary signal.
Description
The application is in the continuation part application that on March 15th, 2013 submits to, sequence number is the unsettled U. S. application of 13/841,889.The application also requires that the sequence number submitted on March 15th, 2013 is 61/798,437, the sequence number submitted on March 15th, 2013 is 61/794,786, the sequence number submitted on March 15th, 2013 is 61/798,120, the sequence number submitted on March 15th, 2013 is 61/794,942 and in the sequence number submitted on March 15th, 2013 be the priority of the U.S. Provisional Application of 61/794,642; Its content is incorporated to herein by reference.
The present invention relates generally to signal transacting, relate more specifically to for send and receive and demodulation transposition modulation signal, for increasing limit communication channel information bandwidth sum for the system according to input control signal time delay shift input signal, method and apparatus.
Existing transmission system of carrying voice, video or data all has the bandwidth applied by the internal and international regulator controlling spectrum utilization and limits.Carrier modulating method from original Modulation and Amplitude Modulation develop till now various combination by method that two or more carrier wave is combined with amplitude, frequency or phase-modulation.Develop advanced carrier modulating method to maximize the energy of the channel width running through distributed, thus provide maximum available information bandwidth for the communication channel of distributing.
A kind of new fundamental carrier modulation is developed out and obtains the authorization (for example, see the U.S. Patent number 4 of the people such as Vokac first, 613,974, its entirety is incorporated to herein), its apply not with the novel carrier modulation coexisting in the amplitude of same carrier signal, frequency and/or phase-modulation interfere.
The concept of transposition modulation (TM) based on how when not affecting its amplitude, frequency or phase place interpolation information to the early stage concept (see the U.S. Patent number 4,613,974 of the people such as Vokac, its entirety is incorporated to this paper) of carrier signal.As follows, by producing flex point, information can by carrier signal transmission.The method does not detect by the demodulator of existing amplitude, frequency or phase-modulation.
Use the generation method of previous patent, produce time domain waveform below, flex point is in order to clear and amplify.In the application of real world, this flex point is sightless.
The weak point producing the earlier processes of this kind of waveform is the little amplitude variations needing to be removed by Circuit tuning.Such as, Fig. 1 is according to U.S. Patent number 4, the schematic diagram of the TM modulation signal 100 of the prior art generation of 613,974 instructions.Can see, amplitude variations error is present between negative peak 101 and 102.
Therefore, in order to address the aforementioned drawbacks and deficiency, in industry, there is still unsolved demand so far.
Embodiment disclosed by the invention provide for send and receive and demodulation transposition modulation signal, for increasing limit communication channel information bandwidth and for the system according to input control signal time delay shift input signal, method and apparatus.In one embodiment, provide the method for the inromation bandwidth increasing the communication channel limited, it comprises the following steps: receive first modulation signal with first carrier signal frequency; Receive second modulation signal with the second frequency of carrier signal, this second modulation signal information of the information independent of modulation first carrier signal is modulated, and this second frequency of carrier signal is relevant to first carrier signal frequency harmonic wave or subharmonic ground; And combine the first signal and secondary signal.
In another embodiment, provide according to the time shift modulation device of input control signal for time delay shift input signal.Time shift modulation device comprises the all-pass filter improved with voltage control time delay.
In another embodiment, provide the method increasing communication bandwidth in fixing communication channel, it comprises the following steps: add the second transposition modulation signal to a composite signal, this composite signal comprises the first transposition modulation signal and first fundamental wave carrier signal, wherein uses identical with first fundamental wave frequency of carrier signal and the second fundamental wave carrier signal relative to first fundamental wave carrier signal with 90 degree of phase angles adds the second transposition modulation signal to composite signal.
In another embodiment, provide the method for the ultrasonic communication inromation bandwidth for providing increase, it comprises by the single ultrasonic transducer of direct Modulation and Amplitude Modulation, transposition modulation is added to the step of ultrasonic communication signal.
In another embodiment, provide the method for the ultrasonic communication inromation bandwidth for providing increase, it comprises the following steps: by fundamental carrier signal component direct Modulation and Amplitude Modulation first ultrasonic transducer modulated with transposition; With third harmonic carrier signal components direct Modulation and Amplitude Modulation second ultrasonic transducer modulated with transposition, add transposition modulation to ultrasonic communication signal.
In another embodiment, provide the method for the ultrasonic communication inromation bandwidth for providing increase, it comprises the following steps: to use wide bandwidth modulated technology, by the single ultrasonic transducer of direct Modulation and Amplitude Modulation, transposition is modulated fundamental carrier signal and third harmonic carrier signal components adds ultrasonic communication signal to.
In another embodiment, the method for the ultrasonic communication inromation bandwidth for providing increase is provided.It comprises the following steps: by fundamental carrier signal component direct angle modulated first ultrasonic transducer modulated with transposition and third harmonic carrier signal components direct angle modulated second ultrasonic transducer modulated with transposition, add transposition modulation to ultrasonic communication signal.
In another embodiment, the method for the ultrasonic communication inromation bandwidth for providing increase is provided.It comprises the following steps: use wide bandwidth modulated technology, by the single ultrasonic transducer of direct angle modulated, transposition is modulated fundamental carrier signal and third harmonic carrier signal components adds ultrasonic communication signal to.
In yet another embodiment, the system of the optical information communication bandwidth for providing increase is provided.This system comprises light beam and optical modulator.This system configuration is for using transposition modulation signal directly modulation light beam.
In another embodiment, provide the method for the optical information communication bandwidth for providing increase, it comprises step: with the light beam of transposition modulation fundamental carrier frequency component directly modulation first frequency.
In yet another embodiment, provide the method for the optical information communication bandwidth for providing increase, it comprises step: with the light beam of transposition modulation third harmonic component signal directly modulation second frequency.
For invention technician, according to the following drawings and detailed description, other system of the present invention, method, feature and advantage will be maybe will become apparent.Intention is, all these spare systems, method, feature and advantage are included in this specification, within the scope of the present invention and protect by claims.
Many aspects of the present invention better can be understood with reference to the following drawings.Parts in accompanying drawing need not be drawn in proportion, but focus on principle of the present invention is clearly described.In addition, in the accompanying drawings, identical Reference numeral represents the corresponding part in some views.
Fig. 1 is the TM modulation signal schematic diagram produced according to prior art.
Fig. 2 is the flow chart of the method illustrated according to the first exemplary modulated carrier signal of the present invention.
The schematic diagram of signal is produced when Fig. 3 is 1/4th cycle according to an embodiment of the invention.
Fig. 4 is the schematic diagram after the summation of signal 1/4th cycle shown in Fig. 3 according to an embodiment of the invention.
Fig. 5 is in order to produce the schematic diagram of the input modulating signal of signal shown in Fig. 4 by embodiment provided by the invention.
Fig. 6 is the curve chart of signal spectrum shown in key diagram 4.
Fig. 7 is according to an embodiment provided by the invention, the spectrum curve figure that the third harmonic component of signal shown in key diagram 6 and second harmonic heterodyne produce.
Fig. 8 can be applicable to the filter schematic in embodiment provided by the invention.
Fig. 9 a is the block diagram of the direct spectrum systems based on software for generation of signal illustrated according to embodiment provided by the invention.
Fig. 9 b is the block diagram of the hardware based direct spectrum systems for generation of signal illustrated according to embodiment provided by the invention.
Figure 10 is the block diagram of the subcycle calibration system for restituted signal illustrated according to embodiment provided by the invention.
Figure 11 is the block diagram of the third harmonic phase detection for restituted signal illustrated according to embodiment provided by the invention.
Figure 12 is the block diagram of the system based on fast Fourier transform for restituted signal illustrated according to embodiment provided by the invention.
Figure 13 be illustrate according to embodiment provided by the invention for generation of with the block diagram sending the TM reflector of signal be made up of the TM signal adding existing signal to.
Figure 14 is the block diagram of the exemplary execution TM reflector carrier signal generating portion illustrated according to embodiment provided by the invention.
Figure 15 is the block diagram of the exemplary execution TM reflector TM modulation signal processing section illustrated according to embodiment provided by the invention.
Figure 16 be illustrate according to embodiment provided by the invention for accepting to have the signal of the TM signal having added existing signal to and extracting and the block diagram of TM receiver of demodulation TM signal.
Figure 17 illustrates the exemplary carrier signal of execution TM receiver according to embodiment provided by the invention and the block diagram of harmonic wave recovery section.
Figure 18 illustrates the exemplary block diagram performing TM receiver TM separation and demodulation part according to embodiment provided by the invention.
Figure 19 is the figure of the frequency response behavior of the filter circuit based on separator delay function illustrated according to embodiment provided by the invention.
Many embodiments of the present invention can take the form of computer executable instructions, comprise the algorithm performed by programmable calculator or microprocessor.But the present invention also can utilize other computer system configurations to realize.Some aspect of the present invention can be implemented in special-purpose computer or data processor, described special-purpose computer or data processor by concrete programming, configuration or structure, to perform following one or more method or algorithm.
Following each aspect of the present invention can store or be distributed in computer-readable medium, comprise magnetic and readable and removable computer disks, fixed disk, floppy disk, CD drive, magneto optical driver, tape, hard disk drive (HDD), solid-state drive (SSD), mini-flash or the nonvolatile memory of light, and electron distributions is on the network comprising cloud.Particularly the data structure of each side of the present invention and transfer of data are also included within scope of the present invention.
Fig. 2 is flow process Figure 200, describes the method for the modulated carrier signal according to the present invention first exemplary.Should be understood that, in flow chart, any process prescription or square frame are construed as and represent module, section, partial code or step, comprise in this process for realizing one or more instructions of specific logical function, and substituting implementation procedure comprises within the scope of the invention, wherein function can perform not according to order that is shown or that discuss, and comprise and performing in reverse order in fact simultaneously, this depends on the function related to, for the technical staff in field of the present invention, this is understandable.This method solve the problem (such as, as above shown in Fig. 1) of amplitude variations in prior art, and can realize in hardware or software or its combination in any.Method as shown in Figure 2, (QC) method that it can be called as " assembling of 1/4th cycles ", can comprise (LUT) 210 that table look-up as the fast method obtaining result, otherwise can utilize mathematical function to produce, and without the need to performing mathematics continuously.This QC method is based on time domain.
With reference to Fig. 3, the modulated output signal 300 from method shown in Fig. 2 comprises four 1/4th different constant time ranges for each complete signal cycle.Fig. 3 show three complete cycles (such as, the cycle a, b and c), it exports by 1/4th cycle methods shown in Fig. 2.Each cycle is made up of four 1/4th constant time ranges (such as, 301,302,303 and 304).The gap only supplying illustration purpose is shown between 1/4th constant time ranges.In addition, the amplitude position (a1, a2, b1, b2, c1, c2) of each flex point is exaggerated for purpose of explanation.As shown in the figure, each flex point is formed between 1/4th adjacent constant time ranges.
As shown in Figure 3, " first " 1/4th (301a, 301b and 301c) in each cycle can have different amplitudes according to the value applying modulation.This be equally applicable to shown in each cycle each other 1/4th.Namely second (302a, 302b, the 302c), the 3rd (303a, 303b, 303c) in each cycle and the 4th (304a, 304b, 304c) 1/4th can have different amplitudes according to the value applying modulation.When " first " 1/4th in the cycle (such as, 301a, 301b, 301c) when there is short arc, in same period, " second " 1/4th (such as, 302a, 302b, 302c) there is higher complimentary amplitude, with the negative peak (Pk making constant amplitude always be present in the whole cycle
-) with the positive peak (Pk in this cycle
+) between." the 3rd " and " the 4th " 1/4th in each cycle are also like this.This causes each cycle positive peak (Pk
+) always identical.Negative peak (Pk
-) be also equal, the amplitude variations caused with the modulation value eliminated owing to applying.
Further as shown in Figure 3, for a respective cycle, " first " (301a, 301b, 301c) and " the 3rd " (303a, 303b, 303c) 1/4th has same-amplitude.Similarly, for a respective cycle, " second " (302a, 302b, 302c) and " the 4th " (304a, 304b, 304c) 1/4th also has same-amplitude.The object done like this makes the area under each cyclic curve identical, has nothing to do with the modulation value applied.The mean value which ensure that each cycle is zero, which avoid any " DC " value skew caused by the modulation value applied in carrier signal.
But it should be noted, for some application, DC skew can accept, and therefore can there is inconsistent area under the curve, namely need not be symmetrical in each cycle.Under these circumstances, information or " symbol " can the speed transmission of each cycle two symbols, or two different flex points can be there are (such as in each cycle, one is positioned at negative peak and just peak-to-peak rising half period, and another is positioned at posivtive spike and negative peak-to-peak decline half period).
Each 1/4th cycles produce by constant clock or time step, therefore, do not have the frequency change that the modulation value owing to applying causes from one-period to next cycle.Each flex point (a1, a2, b1, b2, c1, c2) accurately occurs in 180 degree of angle equivalents be separated from a half period to the next half period.Which ensure that the phase place do not caused due to the modulation value applied changes.
By suing for peace for 1/4th cycles (such as, as shown in Figure 3 those), as shown in Figure 4, obtain smooth and continuous print waveform 300.
Fig. 5 describes TM modulation signal 500, and it is for generation of modulation signal 300 as shown in Figure 4.As shown in Figures 4 and 5, each carrier cycle has a TM modulation value 500.But as noted above, each carrier cycle can have two TM modulation values, and wherein this cycle can have different TG-AUCs, namely need not be symmetrical in each cycle, so that people can transmit two symbols on each cycle.Under these circumstances, each carrier cycle can have two TM modulation values, thus the symbol (or information) that expression two is different on each carrier cycle.This technology is applicable to such as through Optical Fiber Transmission, because do not have other signals to take transmission bandwidth; But DC skew is not suitable for usually through other medium transmissions.
Be appointed as the variable t of TM modulation period
tMM, be the time keeping TM modulation value, and be the integral multiple of carrier cycle.This will show, in the case, and maximum TM modulating frequency f
tMMcarrier frequency f
c1/2nd.That is, modulation bandwidth is defined as f
c1/2, as everyone knows, Nyquist rate or the twice for without the lower limit of the frequently sampling rate of folded signal sampling being band-limited signal bandwidth.But, if there are two TM modulation values in each carrier cycle, so maximum TM modulating frequency f
tMMequal carrier frequency f
c.Comprise the f of DC response
tMM, there is no minimum value.
Refer again to Fig. 2, LUT210 stored for 1/4th unique cycles of each TM modulation value.For each carrier cycle, there are four 1/4th cycles (such as, as shown in Figure 3).If each TM modulation has the distribution of 1 digit order number (N=1) period, so only two unique TM modulation levels will be needed, or two of two 1/4th cycles unique collection to be stored in LUT210-one level flag and logical zero and second electrical level indicates logical one.If each t
tMMthere are two digit order numbers (N=2), so will have four potential TM modulation levels.Similarly, if each t
tMMhave three (N=3), so will have eight TM modulation levels, etc.
LUT210 comprises 2
nindividual 1/4th different periodic waveforms or 4*2
ntotal waveform, because each complete waveform is made up of 4 1/4th periodic waveforms.The time step number in per quart cycle or clock periodicity (such as, for reading processor or the cpu clock of LUT210) will depend on permissible waveform disturbances, and it is the admissible disturbance of electronics for realizing the method.In the carrier frequency in 300MHz region, this may need the time step of subnanosecond.Low carrier frequency may be more suitable for two TM methods (such as, LUT branch as herein described and " branch of mathematics ") and can by upwards heterodyne to carrier frequency.
In square frame 202, TM modulation signal is input to LUT210.TM modulation signal can be the digit order number (such as N bit width signal) comprising any amount or the signal represented by the digit order number of any amount.This LUT210 comprises value or the expression in 1/4th cycles that can additionally be produced by branch of mathematics 220.Such as, for can by row 210a (such as, 1 to 2
n) each TM modulation value of representing, 1/4th cycles can associate with TM modulation value and represent during period (such as, from initial time to 1/4 cycle) of the time increased and save as coordinate data (such as x, y) arranging in 210b.In block 204, incoming carrier frequency is f
ccarrier signal.Carrier signal may be RF signal, and can be used as clock signal.In square frame 206, make about whether using LUT210 or use branch of mathematics 220 to perform the decision of modulation.LUT210 or branch of mathematics 220 can be used to the output signal producing modulation.If use LUT210,1/4th cycles relevant to received TM modulation value will export from LUT210 to simulating grid 208.
If use branch of mathematics 220, such as from square frame 206, choose branch of mathematics 210, so TM modulation signal is input to mathematics square frame 220.It is identical that 1/4th periodic waveforms that mathematics square frame 220 exports substantially and the LUT square frame 210 accepting identical TM modulation value export.But mathematics square frame 220 produces 1/4th cycles of each reception TM modulation value, instead of stores 1/4th relevant periodic quantities of each TM modulation value.Mathematics square frame 220 generates cosine section, with the frequency (2f of carrier frequency twice by first of 180 ° of length
c), in 1/4th cycles of 0 °-90 °, equivalent carrier frequency quadrant, 90 °-180 °, 180 °-270 ° and 270 °-360 ° generation modulation.Therefore, these cosine sections generated compensate for 1/4th constant time ranges with carrier frequency.The complementary modulation value of the TM modulation value that amplitude is received by 0 °-90 ° and 180 ° of-270 ° of quadrants (that is, " first " and " the 3rd " 1/4th cycles) and 90 °-180 ° and 270 °-360 ° of quadrants is arranged.Those of ordinary skill in the related art are it is easily understood that any sinusoidal signal that can realize in circuit and/or software can use known mathematical relation to produce.Therefore, the cosine section with the branch of mathematics 220 of the amplitude arranged by received TM modulation value can correspondingly produce.
Branch of mathematics 220 uses the processor with clock to perform mathematical computations and produces 1/4th constant time ranges, this clock is the higher multiple of carrier frequency, thus software code or drive hardware based waveform generator, it can be any known waveform generator.Probably branch of mathematics 220 needs the clock frequency higher than LUT branch 210.The output of LUT210 or branch of mathematics 220 is directed to simulation grid 208, and each 1/4th periodic groups are dressed up a continuous signal and it are directed to forward heterodyne square frame 212 by it.
In order to transmit the object with heterodyne, frequency domain provides each side of the present invention and understands in depth.Fig. 6 is the spectrum curve figure of the modulation signal of TM shown in Fig. 4 300, wherein f
cfrequency of carrier signal, and 2f
c, 3f
cetc. second, third harmonic wave such as grade being carrier frequency.Signal 300 has frequency spectrum as shown in Figure 6 at original point place, has visible flex point in some cases.
Except fundamental carrier frequency component 610, comprise the third harmonic component 620 of the signal 300 of phase-modulation in addition.TM modulation product is only at third harmonic place, and namely TM modulation product is third harmonic component 620.There is no second harmonic signal.Using blender circuit heterodyne third harmonic component by producing second harmonic signal at square frame 214 as local oscillator, two output frequencies will be had: (3fc-2fc) and (3fc+2fc).This is shown in Figure 7.TM modulation product, i.e. third harmonic component 620, will be moved down into fundamental carrier frequency (signal 710).Heterodyne additive component, i.e. the 5th harmonic component 730, can leach at square frame 214 (such as, the filter 810 by shown in Fig. 8), and can be filtered to mate the output for the designated communication channel transmitted.
Compared with known modulation techniques, as offered by the present invention, third harmonic is phase shift, but this phase shift is relative to fundamental carrier, instead of third harmonic.In normal FM and PM transmission, phase shift be exactly carrier wave itself.TM can not change first-harmonic, and third harmonic phase place is only relevant with first-harmonic.
For several reason, difference is very important.Every half period (i.e. each TM modulation symbol) for fundamental carrier has 1.5 unmodulated third harmonic cycles.When data variation (that is, when TM modulation signal 500 changes), third harmonic only has a change.Therefore, to power and spectral contributions very little, and we have for the transparent Another reason of conventional modulated, in most of practical application,, there are 100 or more carrier cycles, during this period in each TM symbol-be limited to communication channel-as AM and FM broadcasting station, third harmonic does not change (that is, modulation not change).It is relative to first-harmonic only (in time) skew in phase place.
As use third harmonic (such as 3f
c) time, the enforcement of QC method needs the analog bandwidth of wider than carrier frequency three times or more multiples.In addition, QC method needs the clock frequency of 16 times of the frequency of carrier signal for per quart cycle four time steps.QC can compared with low carrier signal produce and upwards heterodyne to expectation carrier frequency.The upper limiting frequency of TM modulation value will be determined compared with low carrier frequency.
Fig. 9 a and Fig. 9 b is the block diagram that direct frequency spectrum (DS) generation system and method in another embodiment of the present invention are described.DS generation method can be more simply realize TM modulation.DS method directly produces the Sideband Spectrum and energy is added to any other carrier wave existed in communication channel bandwidth.This DS method is based on frequency domain.
With reference to Fig. 6, existing reflector has the complex modulated of some forms.The typical types of the complex modulated used comprises QAM, QPSK, OFDM etc.The sideband energy component 610 as shown in Figure 6 of existing modulation represents.Add TM modulation and produce third harmonic, and TM sideband energy is represented by component 620.It is noted that second harmonic component may exist but not comprise modulation.
Second harmonic signal has value, because it can be used to TM sideband energy 620 to be moved down into fundamental carrier frequency 610.This uses mixed function to be multiplied by two sinusoidal input signals by heterodyne and produces subtraction and addition rate-adaptive pacemaker has come.With reference to Fig. 7, hacures representative has been transformed into the energy of first-harmonic 710 and the 5th harmonic wave 730 from third harmonic 720.
Optional use second harmonic.Phase-locked loop known in the art can provide stable second harmonic.In addition, may exist non-linear can some sideband energies of down-conversion practically, but be not method that is stable or down-conversion reliably.
Communication laws and regulations requirement, all reflectors must use output filter to ensure the energy emission of the communication channel outside of not specifying.As shown in Figure 8, output filter 810 can be used for eliminating the harmonic wave in the traffic channel of specifying.This filter can comprise passband 812.
Utilize above-mentioned concept, Fig. 9 a and Fig. 9 b describes two system and methods generated for direct frequency spectrum.Fig. 9 a describes the system and method based on software generated for direct frequency spectrum, and Fig. 9 b describes the hardware based system and method generated for direct frequency spectrum.In fig. 9 a, clock signal 910 and digital modulation signals 920 are input to microprocessor 901.In figure 9b, carrier signal 915 and modulated-analog signal 925 are input to non-linear analog circuit 902.According to input signal, third harmonic sideband (such as, TM modulation product 620) is directly produced by microprocessor 901 and/or circuit 902.Microprocessor 901 and/or circuit 902 can further direct by third harmonic sideband 620 and input clock 910 (Fig. 9 a) or carrier wave 915 (Fig. 9 b) heterodyne directly to generate sideband energy (such as 710) in fundamental frequency.DS method relies on the Software Create of overall mathematical expression or performs the non-linear analog circuit of mathematical expression.That is, microprocessor 901 (Fig. 9 a) and/or circuit 902 (Fig. 9 b) utilize known mathematical relation directly to calculate and generate the third harmonic sideband 620 based on input signal.Third harmonic sideband 620 then by microprocessor 901 and/or non-linear analog circuit 902 heterodyne so that third harmonic sideband is displaced to fundamental frequency.
To openly be used for the system and method receiving and demodulating transposition modulation now.Figure 10 is the block diagram of the system and method described for demodulation TM modulation signal, and it can be described as " subcycle calibration " (SCC).The SCC demodulation method of TM modulation runs by rebuilding waveform in time domain, such as shown in QC method part (such as, the signal 300 of Fig. 4).
In wide bandwidth environment, SCC method increases third harmonic to Received signal strength 1001.Phase-locked loop 1010 produces accurate and unmodulated third harmonic signal, and it is added with Received signal strength 1001 or is multiplied in element 1020.Then detected the voltage level at each plus or minus peak by positive Peak detector 1030 and/or negative peak detector 1040, and use the voltage level at plus or minus peak to produce reference slope (by referring to ramp generator 1050) of negative peak and the positive peak with coupling.Therefore, in every 1/2 cycle of Received signal strength 1001, when producing new reference slope, system (that is, the appearance at each peak) is calibrated.Slope is regenerated in every half period of carrier signal 1001.Use the timing of peak value to set the timing with reference to slope by peak value timing element 1060, flex point is detected by detector 1030 and 1040, and the timing of flex point is for the reference slope exported by referring to ramp generator 1050 of sampling, and keeps the ramp value of sampling.This voltage is that TM modulates the analogue value, and is exported by sampling and holding element 1070, and can directly use or can be exchanged into numeral.For bearing the positive carrier half period, there is positive slope with reference to slope.Ensuing half carrier cycle (that is, just arriving negative half-cycle), with reference to slope, there is negative slope.
The advantage of SCC demodulating system and method is, it provides a kind of demodulation techniques reliably.This is because SCC demodulation only relates to the generation of negative peak and posivtive spike, and the existence of these peak-to-peak flex points.Therefore, the impact of error that do not cause by noise compared with other demodulation techniques of SCC demodulation.
Figure 11 describes to can be described as " third harmonic phase-detection " demodulating system of (3PD) and the block diagram of method according to another embodiment of the present invention.Third harmonic phase-detection (3PD) demodulation method of TM modulation is present in this component phase-modulation by regenerating third harmonic component and demodulation runs.
As shown in figure 11, used by phase-locked loop 1110 the TM modulation signal 1101 received to produce stable, unmodulated fundamental carrier signal, deducted from Received signal strength 1101 by subtraction element 1120.Can filter to fall any spurious emissions at fundamental carrier frequency filter to the output from subtraction element 1120 by first-harmonic notch filter 1130.Therefore remaining signal is sideband energy (such as, TM modulation product), and it drives third harmonic phase detectors 1140.Third harmonic phase detectors 1140 can be the phase detectors of any known or routine.The output 1150 of gained is that TM modulates the analogue value.
Figure 12 is the block diagram describing further demodulating system according to another embodiment of the present invention and method.Demodulating system shown in Figure 12 and method are fast fourier transform (TMFFT) demodulation methods of TM modulation, and are run by the analysis of the Sideband Spectrum.
TMFFT method can provide the simplest hardware implementing, but it also may be the most complicated in signal transacting.Once it is quantized by analog to digital converter, analyze TM modulated received signal 1201 by FFT function 1210.Once receiver amplifying signal to being suitable for the level converting digital bit to, signal outputs to element 1210, it can be a kind of processor, such as computer CPU or a more special processor, such as field programmable gate array or any specialized designs calculate the customer designed IC of Fourier transform.The output of FFT element 1210 is multinomial data values, and it represents the signal strength signal intensity of the TM signal 1201 received under discrete frequency.Because it relates to quantity (that is, every TM to distribute modulation period bit number) and the symbol rate of the bit of TM pattern-each symbol of operation, TM frequency spectrum is known.
Symbol rate equals carrier frequency divided by every symbol carrier periodicity.In illustrative example, mathematical expression is: every symbol=100 of carrier cycle, 1MHz carrier frequency/10,000 symbol is per second.
The frequency of symbol is: 100,000 symbol is per second/and 2=50,000 symbol period is per second.
Therefore object frequency is 50kHz in this example, i.e. symbol period frequency, and it is 50kHz on or below carrier frequency.FFT demodulating process also will consider 100kHz and 150kHz more accurately, to comprise the relevant sideband of extra Bezier, when now having many modulation levels, and such as 6 bits per symbol or 64 modulation levels.In addition, when only having the every symbol of some carrier cycles, more sideband frequencies decrease demodulating error rate.In some receivers, carrier frequency heterodyne is to the intermediate frequency (IF) for increasing or to base band, carrier frequency is set to zero by it.
50kHzFFT output valve follows the value of TM modulation by having.If TM modulation has 4 bits per symbol, the numerical value then exported from FFT is divided into 16 level and the conversion being transformed into 4 binary bits creates TM modulation value.
The block diagram of Figure 13 describes and has added existing signal (such as, the RF signal of modulation) to for generation of with TM reflector 1300, the TM signal sending the signal be made up of TM signal.TM reflector 1300 comprises carrier signal generating portion 1310 and TM modulation signal processing section 1320.There is shown the exemplary embodiment of carrier signal generating portion 1310 at the frame of Figure 14, and there is shown the exemplary embodiment of TM modulation signal processing section 1320 at the frame of Figure 15.
The effect of carrier signal generating portion 1310 be obtain existing signal 1301 (it is modulation or unmodulated) low level sample (such as, by directional coupler 1312), and peel off any existing traditional modulation (such as, AM, FM or other traditional modulation form any) to obtain single fundamental frequency carrier signal (FC-fundamental carrier).Can peel off existing traditional modulation from the sample of existing signal 1301 by band pass filter level 1314, band pass filter level 1314 can have narrow bandpass region, selects to remove traditional modulation from frequency carrier signal.Second harmonic generator 1316 produces second harmonic signal (H2-second harmonic), such as, by it self and FC signal multiplication.Similarly, third harmonic generator 1318 produces third harmonic signal (H3), such as, by being multiplied by FC and H2.It should be understood that the first and second harmonic oscillators 1316,1318 can be or comprise any known method for generation of harmonic wave or circuit, comprise such as phase-locked loop.
As shown in figure 14, band pass filter level 1314 can comprise there is very narrow bandwidth the first SAW filter 1313, gain stage 1315, for stabilized amplitude comparator 1317 and there is the second SAW filter 1310 of narrow bandwidth.Phase place adjustment level 1311 can be included in carrier signal generating portion 1310 and export fundamental carrier and existing fundamental signal (that is, FC) to match and to lock TM.Second and third harmonic generator can realize as signal multiplier 1316,1318.
As shown in FIG. 14 and 15, TM fundamental carrier and existing signal fundamental carrier are labeled as and lock mutually (such as, by phase place adjustment level 1311).This completes by feedback loop, and TM modulation circuit is placed on inside large phase-locked loop by it, and the fundamental carrier signal exported to make TM matches with the fundamental carrier of the existing signal in combiner 1338.
Circuit shown in Figure 14 is important, because it produces signal in the frequency of the existing signal frequency accurately of placing one's entire reliance upon.Affect TM to the inoperation of cut-off frequency (off-frequency) signal.
TM modulation signal is processed by TM modulation signal processing section 1320.TM modulation is positioned over third harmonic, and frequency translation is first-harmonic (FC), and is combined with existing signal 1301.
TM modulation signal input 1302 to the TM modulation signal processing section 1320 of TM reflector 1300 is simulation in itself, and be band-limited (such as, by low-pass modulation Nyquist restriction filter 1322), to create the sideband energy consistent with communication channel bandwidth.Then TM modulation signal is processed by anti-phase optimizer 1324 and TM modulator (or time shift modulation device) 1326.As shown in figure 15, gain stage 1321 can be comprised, and anti-phase optimizer 1324 can comprise sampling and keep function, and optimizational function.Low pass filter 1322, gain stage 1321 and Reverse optimization device 1324 for restricted T M modulation bandwidth to this communication channel bandwidth.Optimization can be opened via the presence or absence of the input signal to anti-phase optimizer 1324 or close.
Third harmonic signal (H3) drives TM modulator (or time shift modulation device) 1326 by time shift third harmonic.This generates one group of Bessel function sideband.For TM demodulation, only need one group of upper sideband and lower sideband.Before TM modulation treatment, by the filtration of TM modulation signal, relative to third harmonic, these sidebands are restricted in bandwidth, to mate communication channel bandwidth.
The present inventor confirms in simulations, as disclosed herein, contrary with phase shift modulated, and time shift modulation only produces a pair sideband.This is confirmed by the oscilloscope in experiment and spectrum analyzer.As expection, phase-modulation produces the sideband of Bezier series.On the other hand, time shift modulation only produces one group of upper sideband and lower sideband.
TM modulator (or time shift modulation device) 1326 performs time shift modulation by the all-pass filter improved with voltage control time delay.Control voltage is provided with the TM modulation signal (have or do not have optimization) of adjustment.Time shift occurs in third harmonic (H3) signal.Although TM modulator 1326 described herein relates generally to time shift modulation, those skilled in the relevant art understand, and TM modulator 1326 can be phaseshift modulator similarly.
There has been described the further details about time delay shift circuit, principle and function that can adopt in TM modulator (or time shift modulation device) 1326.For single-frequency input signal, such as sinusoidal wave, time delay is similar to phase shift.
All-pass filter can comprise the operational amplifier with feedback resistor, feedback resistor is connected from operational amplifier output terminal with negative or rp-op amp input, with the second resistor of equivalence, it is connected to signal input from negative or rp-op amp input, just or non-inverting input, it is connected to the intermediate node of a series capacitance and resistor network, and series capacitance and resistor network one end are connected to signal input part and other end ground connection.
Series electrical perhaps resistor value by use four-quadrant multiplier utilize control signal correction, multiplier exports the grounding connection that substituted for series connection R-C network, and an input of four-quadrant multiplier is connected to the intermediate node of series network, second input is as control signal input (that is, TM modulation signal).
According to input control signal, the time delay displacement of input signal can produce skew along with time migration in phase place.
TM ON/OFF selector 1328 can be included, select unmodulated third harmonic (H3) signal (such as, output from third harmonic generator 1318) or TM modulation third harmonic signal (such as, from the output of time shift modulation device 1326).No matter whether use TM, this function retains the gross power being transported to transmitting antenna 1340.
In low-converter 1330 (or " heterodyne frequency conversion " square frame 1330 shown in Figure 15), by the H3 signal modulated by TM and second harmonic (H2) signal multiplication, down-conversion is carried out to the H3 signal of TM modulation.This displacement TM modulates the sideband energy of H3 signal to FC frequency, then filters modulation band by band pass filter 1332 at FC and leads to.
Then, gained provides conventional amplification to set up available power level based on the TM signal of FC through amplifier 1334.Amplifier 1334 can be such as a kind of RF power amplifier.TM signal based on FC is added into the combiner 1338 of existing signal 1301 through final bandwidth check strap bandpass filter 1338 with by TM output signal.The composite signal obtained is connected to transmitting antenna 1340 and is used for transmission.Phase place is locked between TM output signal and existing signal 1301.
Figure 16 is the block diagram describing TM receiver 1600, and it is for receiving composite signal 1641 (such as, being added into the TM signal of existing signal), and extracts and demodulation TM signal.
TM receiver 1600 obtains the composite signal received, as far as possible near antenna 1640 or the IF (intermediate frequency) (such as, the output of existing receiver, this is very common in some communication equipments) that produces near first as far as possible.
TM receiver 1600 comprises carrier signal and is separated and demodulation part 1620 with TM with harmonic wave recovered part 1610.The one exemplary embodiment of carrier signal and harmonic wave recovered part 1610 illustrates in the block diagram of Figure 17, and TM is separated and the one exemplary embodiment of demodulation part 1620 illustrates in the block diagram of Figure 18.
It is as follows to perform that the carrier signal of TM receiver 1600 and harmonic wave recovered part 1610 comprise circuit: (a) recovers existing fundamental carrier signal (FC) as unmodulated signal, and (b) produces second and (c) third harmonic signal of the fundamental signal recovered.These all serve as local oscillated signal, except they are accurately from the signal received.Accomplish that such circuit is similar to the circuit for reflector 1300.
In carrier signal and harmonic wave recovered part 1610, from reception antenna 1640 or the Received signal strength 1641 that exports from the IF (intermediate frequency) of existing receiver (common in some communication equipments) (such as, TM signal is made to be added into the combination RF signal of existing signal) filtered by very narrow bandpass filtering level 1614, to remove any existing modulation, thus produce pure fundamental carrier signal (FC-fundamental carrier).FC is multiplied with self in second harmonic generator 1616, to produce second harmonic signal (H2).FC is multiplied in third harmonic generator 1618 with second harmonic signal (H2), to produce third harmonic signal (H3).
As shown in figure 17, receiver 1600 front end can have the gain that AGC (automatic growth control) controls, and can comprise SAW filter 1613 and gain stage 1615.Be similar to the carrier signal generating portion 1310 of reflector 1300, the carrier signal of receiver 1600 and harmonic wave recovered part 1610 can comprise comparator 1617 and the second SAW filter 1619.Phase place adjustment level 1611 can be included in carrier signal and harmonic wave recovered part 1610 to compensate SAW filter phase shift.Second and third harmonic generator can realize as signal multiplier 1616,1618.
To be separated and in demodulation part 1620 at TM, Received signal strength 1641 (after by the receiver front end process with AGC ride gain) carries out bandpass filtering by band pass filter 1636, and band pass filter 1636 bandwidth equals communication channel bandwidth.
Then wideband received signal enters separation and extraction process.First function is the difference (being performed by time delay amplifier 1634) between Received signal strength and the delay version of that signal.Postpone to equal 1/4th of the third harmonic cycle.Time delay amplifier 1634 adopts the filter circuit (such as, delay-level 1633 and differential amplifier stage 1635) based on time delay, and it is separated the TM energy received.
Separation signal (such as, fundamental frequency differential signal) carries out up-conversion by being multiplied by (H2) signal in upconverter 1630.That is, the frequency of the third harmonic receiving fundamental signal (FC) is worse than outside separation signal.Result is the third harmonic frequency signal (after filtering to remove first-harmonic product term by band pass filter 1632) with TM modulation.Due to the impact of existing carrier modulation and transmission medium, amplitude variations may be had in this.Therefore, this signal is supplied to the analog comparator 1650 with the common reference of signal, it produces the signal not having amplitude variations.The third harmonic carrier frequency with TM modulation is selected in the filtration of band pass filter 1631, and eliminates other harmonic wave.
Output signal from band pass filter 1632 is not only directed to analog comparator 1650 as above, and it is also used as the input to TM signal detector 1628, TM signal detector 1628 detect the TM based on correlation function existence (that is, receive from band pass filter 1632 as the signal exported and from third harmonic generator 1618 receive as between the third harmonic signal (H3) exported relatively or relevant).TM signal detector 1628 output signal represents that whether TM is in use, that is, whether TM signal is present in Received signal strength 1641.
Leaching process completes from Received signal strength 1641 separation and extraction TM signal.The signal extracted (such as, output from band pass filter 1631) comprise TM modulation, it is time shift that the recovery of itself and demodulation TM informational needs is compared with reference to third harmonic signal (such as, (H3) is from the existing carrier signal of reception being used as reference).
TM demodulator 1626 is by detecting the time shift demodulation TM signal between third harmonic signal (H3) (accepting from third harmonic generator 1618 as with reference to input) and the third harmonic signal (receiving from band pass filter 1631 as input) with TM modulation.TM demodulator 1626 adopts the product of two signals can detect the time shift between input signal as correlation function.Alternatively, TM demodulator 1626 can use XOR function to detect (H3) reference and from separation and extraction process TM modulation signal between timing differences.
TM is separated and demodulation part 1620 can comprise anti-phase optimizer 1624 alternatively to recover the signal of reflector transmission, and reflector has anti-phase optimizer 1324 as above.
Restituted signal to remove any carrier wave and other noise source, thus obtains TM modulated output signal 1602 through ovennodulation low pass filter 1622.
Figure 18 illustrates basic collection of functions, and it for retrieving received TM signal from composite signal.Time delay differentiator or filter (i.e. delay-level 1633) can have the time of delay of a best setting: (.25)/(3*f
fc).The TM signal level of separation is merely reduced, although in fact some value will cancel the TM signal level be separated from the deviation of this value.Extract the amplitude variations that function only eliminates separation signal.
Based on the time delay of the separator function of Figure 18 of filter circuit, as shown in figure 19, there is unique frequency respective behavior.Periodic signal is had to eliminate in DC, the 6th harmonic wave equifrequent.
Existing signal receiver does not make response to TM signal frequency side band energy.TM is added into the effect that existing signal has the signal to noise ratio (SNR) of the existing signal that minimizing receives.Similarly, the noise from existing signal has contribution to the TM signal received.
TM receiver 1600 depends on second and the third harmonic signal relevant to received fundamental signal.Frequency shifting caused by Doppler effect or variable signal path length (mobile receiver or reflector) does not affect TM signal receiving, because whole process is with reference to existing signal frequency.
As mentioned above, about Figure 13 to 19, TM can be provided over the carrier signal to modulate, it can from any existing launcher signal.Then modulated TM signal can combine with existing launcher signal (modulate or unmodulated), thus improves the inromation bandwidth of previously defined communication channel.Although Figure 13 to 19 has carried out above-mentioned discussion especially in regard to TM signal, this has not also meant that restriction, because identical characteristic sum principle can be applied with the signal of any modulation.Information can be used as time between two signals of different frequency or phase angle difference transmission.
Therefore, provide the method increasing the inromation bandwidth of the communication channel of any restriction by adding the second carrier signal, second carrier signal has the humorous rolling land frequency relevant to first carrier signal frequency, and with the modulates information independent of modulation first carrier signal message.Secondary signal and modulation sideband, can be worse than the frequency of first carrier signal outward, and modulation sideband, can be equal to or less than the bandwidth of communication channel.
The first carrier signal and the second modulated carrier signal that do not do any correction can be sent.
First carrier signal can modulated (modulation by any type) or unmodulated, and the second carrier signal can have time shift or angle modulated.Second carrier signal can have the frequency having known relation with the frequency of first carrier signal.Similarly, the second carrier signal can have phase angle or relation regularly with first carrier signal.The information transmitted can cause time shift or the angle modulated of the second carrier signal, and the modulator approach of the second carrier signal can change and the time of first carrier signal or angle relationship.
The time shift of the second carrier signal or angle modulated produce sideband energy, by its frequency displacement to take identical with the frequency range of the modulation of first carrier signal (if any) or identical with the frequency range in the communication channel bandwidth be placed on for communicating frequency range.First carrier signal can transmit with the combination of the second carrier signal sideband together with in the frequency range of communication channel, and is received by receiving system.In addition, the combination of two carrier signals can not have bandwidth to transmit with limiting, and is received by receiving system.
Receiving system adopts first carrier signal can the modulation intelligence of demodulation second carrier signal as the contrast signal for demodulation.
Additionally provide orthogonal transposition modulator approach herein, or for adding the method for second transposition modulation (TM) signal to existing transposition modulation signal, thus the inromation bandwidth increased in fixed communication channel, exceed and modulated by transposition the inromation bandwidth provided as previously mentioned.
In one embodiment, by using identical from existing transposition frequency modulating signal but have the fundamental carrier signal frequency of the different or quadrature phase of 90 degree in phase place, the second transposition modulation signal can be added into existing transposition modulation signal.This maintains the mutual transparent attribute of transposition modulation, it has conventional amplitude, frequency and phase-modulation.The interpolation of orthogonal transposition modulation signal also has the mutual transparency between two transposition modulated carriers, and all has the transparency with existing traditional modulation signal.
Transposition modulation can be used for many aspects, comprises, such as, for optical communication.Provided herein is wide bandwidth transposition modulation signal is directly placed on method light frequency bundle being used for improving data bandwidth communication.
Light beam is applied due to their wide bandwidth characteristic.They are modulated by various method.In various manners transposition can be modulated the light beam be positioned over for information communication, thus these be all can expect in scope of the present invention and within the scope of the invention.
Such example can illustrate as follows.For any modulator approach, carrier signal conveys a message required.Transposition modulation can use existing modulated carrier signal, for transposition modulated carrier.If there is no, transposition modulation also can provide carrier signal.Whether no matter use existing signal, the carrier signal of transposition modulation is all for driving optical modulator.
Optical modulator scope is from LED drive, laser diode drive to beam modulator, and it changes opacity or the phase place of light beam.The present invention is to provide the ability carrier signal that transposition is modulated being applied to single modulating device.This can improve the existing information bandwidth using conventional amplitude, frequency or phase-modulation.
At present without any other modulation, will send unrestricted bandwidth transposition modulation signal, it will comprise the third harmonic component of transposition modulation.This places fundamental frequency component with lower frequency, wherein usually has less decay.Transposition demodulation depends on this component for reference.The third harmonic component of upper frequency has wider bandwidth, allows the widest possible modulates information bandwidth.
In another embodiment, can adopt two independently light beams, wherein lower frequency light beam is traditional modulation (such as, with amplitude or phase-modulation), and is also used as with reference to carrier wave for transposition modulation.Upper frequency light beam is used for transposition modulation third harmonic component.
The another kind of mode using transposition modulation is in supersonic communication, such as, for radio communication under water.Such as, in one embodiment, transposition modulation signal can be applicable to ultrasonic transducer to produce voice signal, and voice signal can be received and demodulation, to recover original modulation intelligence.Modulated process applies nearly zero impedance and drives, and forced transducer runs under the natural resonance frequency exceeding transducer.
Except the wide bandwidth of modulation, receiver can use nature wide bandwidth transducer, and it is based on the technology when not having resonance peak to respond, acoustic energy being converted to electric energy.Using provides the micro-electromechanical system (MEMS) technology of the broadband response with sensitivity can manufacture such receiving transducer.
A transposition modulated carrier frequencies can be used.Two independently ultrasonic frequency may be used for transmitting separately fundamental carrier signal component and third harmonic component signal.
It is emphasized that above-mentioned embodiment of the present invention, particularly any " preferably " embodiment, being only the example possible implemented, proposing just to being expressly understood principle of the present invention.Under substantially not departing from the spirit and principles in the present invention; many changes and amendment can be made to above-mentioned embodiment of the present invention; all such modifications and change are all intended to be included in the present invention and scope disclosed by the invention, and are protected by following claim.
Claims (17)
1. improve the method limiting communication channel information bandwidth, comprising:
Receive first modulation signal with first carrier signal frequency;
Receive second modulation signal with the second frequency of carrier signal, the information of described second modulation signal independent of modulation first carrier signal is modulated, and the second frequency of carrier signal is relevant to first carrier signal frequency harmonic wave or subharmonic,
And combine the first signal and secondary signal.
2. method according to claim 1, is worse than the frequency of first carrier signal outside wherein said secondary signal.
3. method according to claim 1 and 2, also comprises:
Composite signal is sent by dispensing device;
Composite signal is received by receiving system; And
Use first carrier signal as reference from composite signal demodulation second modulation signal.
4., for the time shift modulation device according to input control signal time delay shift input signal, comprise the all-pass filter improved with voltage control time delay.
5. time shift modulation device according to claim 4, wherein said all-pass filter comprises:
Operational amplifier, it has the feedback resistor be connected between operational amplifier output with the reverse input of operational amplifier;
Second resistor, it has the resistance being substantially equal to feedback resistor resistance; Described second resistor is connected between the reverse input of operational amplifier and signal input; With
Series capacitance and resistor network, series capacitance and resistor network have be connected to signal input first end, be connected to second end on ground and be connected to the intermediate node of non-return input of operational amplifier.
6. time shift modulation device according to claim 5, wherein by using four-quadrant multiplier, by the value of control signal correction series capacitor or resistor, multiplier exports the grounding connection replacing series capacitor and resistor network, wherein an input of four-quadrant multiplier is connected to the intermediate node of series capacitor and resistor network, and the second input of four-quadrant multiplier is connected to control signal input.
7. in fixed communication channel, improve the method for communication bandwidth, comprising:
For composite signal adds the second transposition modulation signal, composite signal comprises the first transposition modulation signal and first fundamental wave carrier signal, second fundamental wave carrier signal is wherein used to add the second transposition modulation signal for composite signal, second fundamental wave carrier signal has the frequency identical with first fundamental wave carrier signal, and has the phase angle relative to first fundamental wave carrier signal 90 degree.
8. the method for raising communication bandwidth according to claim 7, is characterized in that one or two following feature:
A () wherein inromation bandwidth doubles, and do not increase communication channel bandwidth; With
B () wherein increases the spectrum efficiency of transposition modulation.
9., for providing the method for the ultrasonic communication inromation bandwidth of increase, comprising:
By the direct Modulation and Amplitude Modulation of single ultrasonic transducer, add transposition modulation to ultrasonic communication signal.
10., for providing the method for the ultrasonic communication inromation bandwidth of increase, comprising:
Be there is by direct Modulation and Amplitude Modulation the first ultrasonic transducer of the fundamental carrier signal component of transposition modulation; With
Direct Modulation and Amplitude Modulation has the second ultrasonic transducer of the third harmonic carrier signal components of transposition modulation, adds transposition modulation to ultrasonic communication signal.
11., for providing the method for the ultrasonic communication inromation bandwidth of increase, comprising:
Use wide bandwidth modulated technology by the single ultrasonic transducer of direct Modulation and Amplitude Modulation, transposition is modulated fundamental carrier signal and third harmonic carrier signal components adds ultrasonic communication signal to.
12., for providing the method for the ultrasonic communication inromation bandwidth of increase, comprising:
Be there is by direct angle modulated the first ultrasonic transducer of the fundamental carrier signal component of transposition modulation, and directly angle modulated has the second ultrasonic transducer of the third harmonic carrier signal components of transposition modulation, add transposition modulation to ultrasonic communication signal.
13., for providing the method for the ultrasonic communication inromation bandwidth of increase, comprising:
Use wide bandwidth modulated technology by the single ultrasonic transducer of direct angle modulated, transposition is modulated fundamental carrier signal and third harmonic carrier signal components adds ultrasonic communication signal to.
14., for providing the system of the optical information communication bandwidth of increase, comprising:
Light beam; With
Optical modulator,
Wherein system configuration is for using transposition modulation signal directly modulation light beam.
15. systems according to claim 14, wherein said system configuration is for using transposition modulation signal amplitude modulated light beam, or wherein said system configuration is for using transposition modulating signal phase modulated beam of light.
16., for providing the method for the optical information communication bandwidth of increase, comprising:
Directly modulation has the light beam of the first frequency of transposition modulation fundamental carrier frequency component.
17., for providing the method for the optical information communication bandwidth of increase, comprising:
Directly modulation has the light beam of the second frequency of transposition modulation third harmonic component signal.
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Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN109328433A (en) * | 2016-04-26 | 2019-02-12 | Tm Ip控股有限公司 | The transposition modulation communication of equipment room |
| CN109417362A (en) * | 2016-04-26 | 2019-03-01 | Tm Ip控股有限公司 | Transposition modulation communication |
Families Citing this family (9)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US9014293B2 (en) | 2013-03-15 | 2015-04-21 | Tm Ip Holdings, Llc | Transpositional modulation systems and methods |
| US9515815B2 (en) | 2013-03-15 | 2016-12-06 | Tm Ip Holdings, Llc | Transpositional modulation systems, methods and devices |
| US9338041B1 (en) | 2015-07-24 | 2016-05-10 | Tm Ip Holdings, Llc | Extracting carrier signals from modulated signals |
| US9338042B1 (en) | 2015-07-27 | 2016-05-10 | Tm Ip Holdings, Llc | Separating and extracting modulated signals |
| US9516490B1 (en) * | 2016-04-20 | 2016-12-06 | Tm Ip Holdings, Llc | Identifying devices with transpositional modulation |
| US9882764B1 (en) | 2017-04-13 | 2018-01-30 | Tm Ip Holdings, Llc | Transpositional modulation |
| US10578709B1 (en) | 2017-04-20 | 2020-03-03 | Tm Ip Holdings, Llc | Transpositional modulation for defensive measures |
| US10341161B2 (en) | 2017-07-10 | 2019-07-02 | Tm Ip Holdings, Llc | Multi-dimensional signal encoding |
| WO2019236746A1 (en) | 2018-06-05 | 2019-12-12 | Tm Ip Holdings, Llc | Transpositional modulation and demodulation |
Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5200822A (en) * | 1991-04-23 | 1993-04-06 | National Broadcasting Company, Inc. | Arrangement for and method of processing data, especially for identifying and verifying airing of television broadcast programs |
| US20070212076A1 (en) * | 2006-02-22 | 2007-09-13 | Nortel Networks Limited | Integrated optical waveform modulation |
Family Cites Families (11)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4989219A (en) * | 1984-03-16 | 1991-01-29 | Gerdes Richard C | Midlevel carrier modulation and demodulation techniques |
| US5200715A (en) * | 1991-09-06 | 1993-04-06 | Wavephore, Inc. | Waveform modulation and demodulation methods and apparatus |
| US6173062B1 (en) * | 1994-03-16 | 2001-01-09 | Hearing Innovations Incorporated | Frequency transpositional hearing aid with digital and single sideband modulation |
| US6522697B1 (en) * | 1999-02-11 | 2003-02-18 | Lockhead Martin Corporation | Use of higher order modulation techniques to transmit large aggregate data rates on an optical link with relatively low speed electronics |
| JP2001186376A (en) * | 1999-12-27 | 2001-07-06 | Casio Comput Co Ltd | Video signal processor |
| DE10007476A1 (en) * | 2000-02-18 | 2001-08-23 | Sennheiser Electronic | Filter circuit for stereo transmitter, has active all-pass filter connected to output of low pass filter |
| JP2004159985A (en) * | 2002-11-14 | 2004-06-10 | Ge Medical Systems Global Technology Co Llc | Rf signal generator and magnetic resonance imaging apparatus |
| US7042958B2 (en) * | 2003-06-04 | 2006-05-09 | Tropian, Inc. | Digital time alignment in a polar modulator |
| US8107551B2 (en) * | 2007-12-14 | 2012-01-31 | Cellnet Innovations, Inc. | Systems and methods for signal modulation and demodulation using phase |
| US20120155344A1 (en) * | 2010-12-16 | 2012-06-21 | Qualcomm Incorporated | Out-of-band communication on harmonics of the primary carrier in a wireless power system |
| US8854985B2 (en) * | 2010-12-31 | 2014-10-07 | Yossef TSFATY | System and method for using ultrasonic communication |
-
2014
- 2014-03-17 MX MX2015012767A patent/MX2015012767A/en unknown
- 2014-03-17 WO PCT/US2014/030704 patent/WO2014145868A2/en active Application Filing
- 2014-03-17 EP EP14762390.4A patent/EP2967266A4/en not_active Withdrawn
- 2014-03-17 CA CA2906183A patent/CA2906183A1/en not_active Abandoned
- 2014-03-17 JP JP2016503446A patent/JP6509190B2/en active Active
- 2014-03-17 EA EA201591202A patent/EA031050B1/en not_active IP Right Cessation
- 2014-03-17 AU AU2014232378A patent/AU2014232378B2/en not_active Ceased
- 2014-03-17 BR BR112015022595A patent/BR112015022595A2/en not_active Application Discontinuation
- 2014-03-17 CN CN201480012702.XA patent/CN105229984B/en active Active
- 2014-03-17 KR KR1020157025206A patent/KR20150131043A/en not_active Application Discontinuation
-
2015
- 2015-09-01 IL IL241003A patent/IL241003B/en active IP Right Grant
-
2016
- 2016-07-05 HK HK16107802.5A patent/HK1219823A1/en unknown
- 2016-07-13 AU AU2016204884A patent/AU2016204884B2/en not_active Ceased
-
2017
- 2017-10-27 AU AU2017251820A patent/AU2017251820A1/en not_active Abandoned
Patent Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5200822A (en) * | 1991-04-23 | 1993-04-06 | National Broadcasting Company, Inc. | Arrangement for and method of processing data, especially for identifying and verifying airing of television broadcast programs |
| US20070212076A1 (en) * | 2006-02-22 | 2007-09-13 | Nortel Networks Limited | Integrated optical waveform modulation |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN109328433A (en) * | 2016-04-26 | 2019-02-12 | Tm Ip控股有限公司 | The transposition modulation communication of equipment room |
| CN109417362A (en) * | 2016-04-26 | 2019-03-01 | Tm Ip控股有限公司 | Transposition modulation communication |
| CN109417362B (en) * | 2016-04-26 | 2023-05-26 | Tm Ip控股有限公司 | Translocation modulation communication |
| CN109328433B (en) * | 2016-04-26 | 2023-05-26 | Tm Ip控股有限公司 | Translocation modulation communication between devices |
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| WO2014145868A9 (en) | 2015-01-08 |
| EA031050B1 (en) | 2018-11-30 |
| IL241003A0 (en) | 2015-11-30 |
| BR112015022595A2 (en) | 2017-07-18 |
| WO2014145868A2 (en) | 2014-09-18 |
| EP2967266A2 (en) | 2016-01-20 |
| CA2906183A1 (en) | 2014-09-18 |
| JP2016519472A (en) | 2016-06-30 |
| AU2014232378B2 (en) | 2018-07-12 |
| IL241003B (en) | 2019-06-30 |
| JP6509190B2 (en) | 2019-05-08 |
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