WO2025141870A1 - 交流直流変換装置、回転機駆動装置及び冷凍サイクル適用機器 - Google Patents

交流直流変換装置、回転機駆動装置及び冷凍サイクル適用機器 Download PDF

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Publication number
WO2025141870A1
WO2025141870A1 PCT/JP2023/047281 JP2023047281W WO2025141870A1 WO 2025141870 A1 WO2025141870 A1 WO 2025141870A1 JP 2023047281 W JP2023047281 W JP 2023047281W WO 2025141870 A1 WO2025141870 A1 WO 2025141870A1
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WIPO (PCT)
Prior art keywords
power supply
converter
switching
phase
switching element
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PCT/JP2023/047281
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English (en)
French (fr)
Japanese (ja)
Inventor
慎也 豊留
謙吾 河内
浩一 有澤
和徳 畠山
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Mitsubishi Electric Corp
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Mitsubishi Electric Corp
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Priority to PCT/JP2023/047281 priority Critical patent/WO2025141870A1/ja
Priority to JP2025566166A priority patent/JPWO2025141870A1/ja
Publication of WO2025141870A1 publication Critical patent/WO2025141870A1/ja
Pending legal-status Critical Current
Anticipated expiration legal-status Critical

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/02—Conversion of AC power input into DC power output without possibility of reversal
    • H02M7/04—Conversion of AC power input into DC power output without possibility of reversal by static converters
    • H02M7/12—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode

Definitions

  • This disclosure relates to an AC/DC converter that converts AC power into desired DC power, as well as a rotating machine drive device and a refrigeration cycle application device that are equipped with the AC/DC converter.
  • a power factor correction circuit When obtaining DC voltage from an AC power source, it is common to use a power factor correction circuit.
  • a power factor correction circuit has the functions of controlling the bus voltage at a constant level and controlling the power supply current so as to comply with harmonic standards.
  • a power factor correction circuit and one of its control methods is a method in which switching is performed at least once per half cycle of the power supply voltage, which is the voltage of the AC power supply, and has the characteristic of being able to control the bus voltage to be lower than the peak value of the power supply voltage.
  • the operating circuit switches from a boost chopper to a capacitor-input type diode rectifier, which creates the problem of distorting the power supply current.
  • Patent Document 1 determines whether the combination of reactor capacity and switching timing complies with harmonic standards by repeating the design for each load power.
  • the present disclosure has been made in consideration of the above, and aims to provide an AC/DC conversion device that can comply with harmonic standards without relying on trial-and-error adjustments, while suppressing the occurrence of overcurrent.
  • the AC-DC conversion device includes a rectifier circuit having at least one switching element and rectifying a power supply voltage applied from a single-phase AC power supply, a capacitor connected to a DC bus and smoothing an output voltage of the rectifier circuit, a reactor arranged on the single-phase AC power supply side of the capacitor, and a control unit that generates a switching signal for controlling the switching element.
  • the switching element is arranged on the single-phase AC power supply side of the capacitor.
  • the control unit generates the switching signal so that the pulse width of the switching signal when the switching element is turned on satisfies a conditional expression defined by the period from the zero crossing of the power supply voltage of the single-phase AC power supply to the output of the switching signal, the effective value of the power supply voltage of the single-phase AC power supply, the inductance of the reactor, the angular frequency of the power supply current of the single-phase AC power supply, and a specified overcurrent threshold.
  • the AC-DC converter disclosed herein has the advantage of being able to comply with harmonic standards without relying on trial-and-error adjustments, while also being able to suppress the occurrence of overcurrent.
  • FIG. 1 is a diagram showing a configuration example of an AC-DC converter according to a second embodiment
  • FIG. 13 is a diagram showing a configuration example of an AC-DC converter according to a third embodiment
  • FIG. 13 is a diagram showing a configuration example of an AC-DC converter according to a fourth embodiment
  • FIG. 13 is a diagram showing a configuration example of an AC-DC converter according to a fifth embodiment
  • FIG. 13 is a diagram showing a configuration example of an AC-DC converter according to a sixth embodiment
  • FIG. 1 is a diagram showing a configuration example of an AC-DC converter according to a second embodiment
  • FIG. 13 is a diagram showing a configuration example of an AC-DC converter according to a third embodiment
  • FIG. 13 is a diagram showing a configuration example of an AC-DC converter according to a fourth embodiment
  • FIG. 13 is a diagram showing a configuration example of an AC-DC converter according to a fifth embodiment
  • FIG. 13 is a diagram showing a configuration example of an AC-DC converter according to
  • the control unit 6 receives the detection values of the voltage detection units 217a, 217b and the current detection unit 211. Based on each detection value, the control unit 6 generates a switching signal for controlling the on/off of the switching element 215.
  • An example of the switching element 215 is an IGBT (Insulated Gate Bipolar Transistor) as shown in the figure, but is not limited to an IGBT. Any element capable of switching operation may be used as the switching element 215.
  • Another example of the switching element 215 is a MOSFET (Metal-Oxide-Semiconductor Field-Effect Transistor).
  • ACR is an abbreviation of Automatic Current Regulator.
  • KpACR is a proportional gain
  • KsACR is an S control gain
  • ⁇ n is an angular frequency
  • s is a Laplace operator.
  • the PS control is a control in which the S control, which is a Laplace transform expression of a cos function, is introduced in addition to the proportional control (P control). As shown in FIG. 3, the PS controller 60 is configured such that the lower S controller is connected in parallel to the upper P controller.
  • the S controller has a feature of improving the tracking performance for a sinusoidal input with an angular frequency ⁇ n .
  • the reason why the tracking performance of the S controller improves for an input pulsating with an angular frequency ⁇ n can be explained from the internal model principle.
  • the internal model principle states that if the controller's denominator has the same factors as the denominator polynomial of the command value expressed by the Laplace transform, the controller can follow the command value without deviation.
  • control unit 6 may be configured to include a target value filter, which is a filter for canceling zero points of the transfer function with the poles of the filter and adjusting the response of the transfer function, on the input side of the current command value I L * of the multiplier that multiplies the current command value I L * by the vibration signal in the configuration shown in Fig. 3.
  • a target value filter which is a filter for canceling zero points of the transfer function with the poles of the filter and adjusting the response of the transfer function, on the input side of the current command value I L * of the multiplier that multiplies the current command value I L * by the vibration signal in the configuration shown in Fig. 3.
  • the configuration of the control unit 6 shown in Fig. 3 shows a configuration in which the control unit 6 generates a switching signal, but since the parts preceding the PS controller 60 and following the PS controller 60 have general configurations, detailed description will be omitted.
  • the control unit 6 also includes a PS controller 60 as a current controller, but the configuration of the PS controller 60 is not limited to the example in FIG. 3.
  • the control unit 6 may include a PS controller 60 including multiple S controllers.
  • the control unit 6 includes a PS controller 60 that is a current controller that controls the power supply current of the AC power supply 1, and the PS controller 60 that is a current controller includes at least one controller that satisfies the internal model principle for sine waves.
  • FIG. 4 is a diagram showing an example of the operating waveforms of the power supply voltage, the bus voltage Vdc , and the power supply current when the control unit 6 of the AC-DC converter 2 according to the first embodiment includes the PS controller 60.
  • the upper part of FIG. 4 shows the waveforms of the bus voltage Vdc and the absolute value of the power supply voltage
  • the lower part of FIG. 4 shows the waveforms of the detected power supply current, the fundamental component of the detected power supply current, and the power supply current command value.
  • the fundamental component of the detected power supply current is almost equal to the power supply current command value.
  • the fundamental wave of the detected power supply current can track the power supply current command value even under conditions in which the bus voltage Vdc is equal to or less than the peak value of the absolute value of the power supply voltage.
  • FIG. 4 shows the results of the operating conditions in which the bus voltage Vdc is equal to or less than the peak value of the absolute value of the power supply voltage, but it goes without saying that the fundamental wave of the detected power supply current tracks the power supply current command value even under operating conditions in which the bus voltage Vdc exceeds the peak value of the absolute value of the power supply voltage.
  • FIG. 5 is a diagram showing an example of current harmonic characteristics when the control unit 6 of the AC-DC converter 2 according to the first embodiment includes a PS controller 60.
  • the current harmonic standard used in FIG. 5 is IEC (International Electrotechnical Commission) 61000-3-2 Class A. Note that IEC 61000-3-2 Class A is an example of a current harmonic standard, and is not limited to this standard.
  • the second to fortieth current harmonic standard values shown in IEC 61000-3-2 Class A are shown by solid lines. Also, in FIG. 5, the effective values of the second to fortieth harmonic components during rated operation are shown by dashed lines.
  • the harmonic components during rated operation represent the remaining components obtained by excluding the fundamental wave component of the power supply current from the power supply current that flows when the AC-DC converter 2 is operated at rated power.
  • the second to fortieth harmonics are defined as "low-order harmonics".
  • the waveforms of the dashed lines are lower than the waveforms of the solid lines from the 2nd to the 40th orders. This shows that if a PS controller 60 with high tracking performance for sine wave input is applied to the control unit 6, the low-order harmonics contained in the power supply current will comply with the harmonic standard value of the power supply current.
  • FIG. 5 shows the harmonic components during rated operation as an example, but it goes without saying that the effect of suppressing harmonic components by the PS controller 60 can be obtained even when not operating at rated speed.
  • the control unit 6 controls the bus voltage Vdc under the condition that the bus voltage Vdc is smaller than the peak value of the power supply voltage, it is necessary to switch from a passive operation in which the switching element 215 is not switched to a feedback control in which the switching element 215 is switched, due to the characteristics of the operating conditions.
  • the operating conditions for example, the timing to turn on the switching element 215 and the pulse width of the switching signal which is the period during which the switching element 215 is turned on, are not appropriate, an overcurrent, an overvoltage, or the like may occur in the AC-DC converter 2 when the control is switched.
  • the control unit 6 needs to take measures to suppress the occurrence of an overcurrent, an overvoltage, or the like when the control is switched.
  • the control unit 6 under the condition that the bus voltage Vdc is smaller than the peak value of the power supply voltage, the control unit 6 prevents the occurrence of an overcurrent, an overvoltage, or the like by setting the timing to start the feedback control, i.e., the timing to turn on the switching element 215, to the zero crossing of the power supply voltage or the period during which the power supply current of the AC power supply 1 becomes zero.
  • the feedback control refers to the current PS control described above.
  • the operating conditions for switching the switching element 215 while suppressing the occurrence of overcurrent, overvoltage, etc. in the AC-DC converter 2 will be described. Specifically, since overcurrent, overvoltage, etc. occur in the AC-DC converter 2 at the first pulse after feedback control by the switching element 215 begins, the conditions for the occurrence of overcurrent, overvoltage, etc. will be described using as an example the operating waveform during partial switching control in which the switching element 215 is switched once. Note that the timing at which overcurrent and overvoltage occur is the same, and hereinafter, an example will be described in which the occurrence of overcurrent is suppressed. The concept of this embodiment can also be applied to control in which the control unit 6 switches the switching element 215 two or more times per half cycle of the power supply voltage of the AC power supply 1, and the control unit 6 can suppress the occurrence of overcurrent even during such control.
  • FIG. 6 is a diagram showing an example of the relationship between the ON timing of the switching signal by the control unit 6 of the AC-DC converter 2 according to the first embodiment and the excitation period of the power supply current iL .
  • the operating conditions under which an overcurrent does not occur are expressed using the equation for the power supply current iL .
  • a phase expression is easier to handle than a time expression, so an equation for the power supply current iL expressed in phase is derived.
  • the power supply voltage vS is defined as equation (2). Note that Vs in equation (2) is the effective value of the power supply voltage vS supplied from the AC power supply 1.
  • equation (8) can be obtained by integrating both sides of equation (7) over time.
  • the equation for the power supply current iL when the switching element 215 is switched once per half cycle of the power supply voltage vS of the AC power supply 1.
  • the equation for the power supply current iL can be derived by deriving the relational equation for the voltage applied to the reactor 212 in the same manner.
  • the condition under which the current during the excitation period of the ⁇ section, which mainly causes an overcurrent, becomes an overcurrent is derived. If the threshold for determining whether the power supply current iL has become an overcurrent is the overcurrent threshold Ioc , the condition under which an overcurrent occurs can be expressed as equation (13) from equation (6).
  • the control unit 6 In this manner, in the AC-DC converter 2, the control unit 6 generates a switching signal such that the ⁇ section, which is the pulse width of the switching signal when the switching element 215 is turned on, satisfies a conditional expression defined by the ⁇ section, which is the period from the zero crossing of the power supply voltage v s of the AC power supply 1 to the output of the switching signal, the effective value V s of the power supply voltage v s of the AC power supply 1, the inductance L of the reactor 212, the angular frequency ⁇ of the power supply current i L of the AC power supply 1, and the specified overcurrent threshold I oc .
  • the conditional expression is defined by the phase angle of the ⁇ section, which is the pulse width of the switching signal when the power supply current i L flowing through the reactor 212 becomes the overcurrent threshold I oc , which is derived from the relational expression of the voltage applied to the reactor 212 when the switching element 215 is turned on once in a half cycle of the power supply voltage v s of the AC power supply 1.
  • the effective value V s of the power supply voltage v s of the AC power supply 1 may be multiplied by ⁇ (2) and expressed as the maximum value or peak value of the power supply voltage v s of the AC power supply 1.
  • ⁇ (2) is the square root of 2.
  • control unit 6 prevents the occurrence of overcurrent, overvoltage, and the like in the ⁇ section where the switching element 215 is turned on, and can also prevent the occurrence of overcurrent, overvoltage, and the like in the ⁇ section which is the section next to the ⁇ section and in which the power supply voltage v.s of the AC power supply 1 is higher than that in the ⁇ section.
  • the positions and connection forms of the switching element 215 and the reactor 212 are different, but in both configurations, the switching element 215 and the reactor 212 are arranged closer to the AC power source 1 than the capacitor 216. This arrangement relationship is similar in other embodiments described later.
  • the switching element 215 is shown as an IGBT, but any element capable of switching operation may be used.
  • the AC-DC converter 2 shown in FIG. 7 is configured as a closed loop, it may also be configured as an open loop. When the AC-DC converter 2 is configured as an open loop, the detection values of the voltage detectors 217a, 217b and the current detector 211 do not need to be used.
  • the full PAM circuit of FIG. 7 may be used in the first embodiment, and the simple switching circuit of FIG. 2 may be used in the second embodiment. That is, when the AC-DC converter 2 has a step-up function or a step-down function, the rectifier circuit 20 has at least one switching element, but the control method described in this paper is applicable even if the control method for controlling the switching element is different.
  • the transfer function of the PIR controller will be described.
  • the transfer function G PIR(s) of the PIR controller can be expressed by the following equation (16).
  • Kp is a proportional gain
  • Ki is an integral gain
  • Kr is a resonance control gain
  • ⁇ 1 is the angular frequency of the current control response
  • ⁇ 2 is the angular frequency of the sine wave command to be followed.
  • a PIR controller having such a transfer function G PIR(s) may be applied to the control unit 6 of the first embodiment. The use of a PIR controller can also provide the same effect as the PS control.
  • the control unit 6 generates switching signals for the four switching elements 220a, 220b, 220c, and 220d using the control method described in embodiment 1 to drive them. This allows the AC-DC converter 2 shown in FIG. 8 to achieve the same effects as in embodiment 1.
  • FIG. 9 is a diagram showing an example of the configuration of an AC-DC converter 2 according to embodiment 4.
  • the rectifier circuit 20 is composed of a single-phase H-bridge cell including two diodes 218a, 218b and two switching elements 220c, 220d.
  • one leg is composed of a series circuit of diodes 218a, 218b, and the other leg is composed of a series circuit of switching elements 220c, 220d. Note that the configuration and operation of the rectifier circuit 20 shown in FIG. 9 are publicly known, and further description will be omitted here.
  • the control unit 6 generates switching signals for the two switching elements 220c and 220d using the control method described in embodiment 1 to drive them. This allows the AC-DC converter 2 shown in FIG. 9 to achieve the same effects as in embodiment 1.
  • the switching elements 220c and 220d are shown as IGBTs, but any elements capable of switching operation may be used.
  • the AC-DC converter 2 shown in FIG. 9 is configured as a closed loop, but it may also be configured as an open loop. When the AC-DC converter 2 is configured as an open loop, the detection values of the voltage detectors 217a and 217b and the current detector 211 do not need to be used.
  • Embodiment 5 a different example of the AC-DC converter 2 including the control unit 6 described in the first embodiment will be described. Components having the same or equivalent functions as those of the AC-DC converter 2 described in the first embodiment will be denoted by the same reference numerals, and the description of the overlapping contents will be omitted.
  • FIG. 10 is a diagram showing an example of the configuration of an AC-DC converter 2 according to embodiment 5.
  • the rectifier circuit 20 is composed of a single-phase H-bridge cell including two diodes 218a, 218c and two switching elements 220b, 220d.
  • the diodes 218a, 218c are arranged in the upper arms of the two legs, and the switching elements 220b, 220d are arranged in the lower arms of the two legs.
  • the configuration and operation of the rectifier circuit 20 shown in FIG. 10 are publicly known, and further description will be omitted here.
  • the control unit 6 generates switching signals for the two switching elements 220b and 220d using the control method described in embodiment 1 to drive them. This allows the AC-DC converter 2 shown in FIG. 10 to achieve the same effects as in embodiment 1.
  • the switching elements 220b and 220d are shown as IGBTs, but any elements capable of switching operation may be used.
  • the AC-DC converter 2 shown in FIG. 10 is configured as a closed loop, but it may also be configured as an open loop. When the AC-DC converter 2 is configured as an open loop, the detection values of the voltage detectors 217a and 217b and the current detector 211 do not need to be used.
  • Embodiment 6 a different example of the AC-DC converter 2 including the control unit 6 described in the first embodiment will be described. Components having the same or equivalent functions as those of the AC-DC converter 2 described in the first embodiment will be denoted by the same reference numerals, and a description of the overlapping contents will be omitted.
  • FIG. 11 is a diagram showing an example of the configuration of an AC-DC converter 2 according to embodiment 6.
  • the rectifier circuit 20 is composed of a single-phase H-bridge cell including two diodes 218a, 218b, four switching elements 220a, 220b, 220c, 220d, a capacitor 216b, and a voltage detector 217c.
  • the voltage detector 217c may be provided outside the rectifier circuit 20.
  • the capacitor 216 is shown as capacitor 216a.
  • one leg is composed of a series circuit of diodes 218a and 218b, and the other leg is composed of a series circuit of switching elements 220a, 220b, 220c, and 220d.
  • the capacitor 216b is connected between the connection point of the switching elements 220a and 220b and the connection point of the switching elements 220c and 220d.
  • the voltage detection unit 217c detects the voltage of the capacitor 216b and outputs the detection value to the control unit 6.
  • the control unit 6 generates a switching signal for controlling the switching elements 220a, 220b, 220c, and 220d based on the detection values of the voltage detection units 217a, 217b, and 217c and the current detection unit 211.
  • the configuration and operation of the rectifier circuit 20 shown in FIG. 11 are publicly known, and further description will be omitted here.
  • the control unit 6 generates switching signals for the four switching elements 220a, 220b, 220c, and 220d using the control method described in embodiment 1 to drive them. This allows the AC-DC converter 2 shown in FIG. 11 to achieve the same effects as in embodiment 1.
  • the switching elements 220a, 220b, 220c, and 220d are shown as IGBTs, but any elements capable of switching operation may be used.
  • the AC-DC converter 2 shown in FIG. 11 is configured as a closed loop, but it may also be configured as an open loop. When the AC-DC converter 2 is configured as an open loop, the detection values of the voltage detectors 217a, 217b, and 217c and the current detector 211 do not need to be used.
  • Embodiment 7 a different example of the AC-DC converter 2 including the control unit 6 described in the first embodiment will be described. Components having the same or equivalent functions as those of the AC-DC converter 2 described in the first embodiment will be denoted by the same reference numerals, and the description of the overlapping contents will be omitted.
  • FIG. 12 is a diagram showing an example of the configuration of an AC-DC converter 2 according to embodiment 7.
  • the rectifier circuit 20 is composed of a single-phase H-bridge cell 221 and a switching cell 222.
  • the single-phase H-bridge cell 221 includes two diodes 218a and 218c and two switching elements 220b and 220d.
  • the switching cell 222 includes four switching elements 220e, 220f, 220g, and 220h, a capacitor 216c, and a voltage detection unit 217c.
  • the voltage detection unit 217c may be provided outside the switching cell 222.
  • diodes 218a and 218c are arranged in the upper arms of the two legs, and switching elements 220b and 220d are arranged in the lower arms of the two legs.
  • switching cell 222 shown in FIG. 12 four switching elements 220e, 220f, 220g, and 220h are bridge-connected.
  • the capacitor 216c is connected in parallel to the first leg consisting of the switching elements 220e and 220f and the second leg consisting of the switching elements 220g and 220h.
  • the voltage detection unit 217c detects the voltage of the capacitor 216c and outputs the detection value to the control unit 6.
  • the control unit 6 generates switching signals for controlling the switching elements 220b, 220d, 220e, 220f, 220g, and 220h based on the detection values of the voltage detection units 217a, 217b, and 217c and the current detection unit 211. Note that the configuration and operation of the rectifier circuit 20 shown in FIG. 12 are publicly known, and further explanation will be omitted here.
  • the control unit 6 generates switching signals for the six switching elements 220b, 220d, 220e, 220f, 220g, and 220h using the control method described in embodiment 1 to drive them. This allows the AC-DC converter 2 shown in FIG. 12 to achieve the same effects as in embodiment 1.

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PCT/JP2023/047281 2023-12-28 2023-12-28 交流直流変換装置、回転機駆動装置及び冷凍サイクル適用機器 Pending WO2025141870A1 (ja)

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Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2015070724A (ja) * 2013-09-30 2015-04-13 三菱電機株式会社 電力変換装置
WO2016051487A1 (ja) * 2014-09-30 2016-04-07 三菱電機株式会社 電力変換装置

Patent Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2015070724A (ja) * 2013-09-30 2015-04-13 三菱電機株式会社 電力変換装置
WO2016051487A1 (ja) * 2014-09-30 2016-04-07 三菱電機株式会社 電力変換装置

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