WO2024257407A1 - 交流直流変換装置、回転機駆動装置及び冷凍サイクル適用機器 - Google Patents

交流直流変換装置、回転機駆動装置及び冷凍サイクル適用機器 Download PDF

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Publication number
WO2024257407A1
WO2024257407A1 PCT/JP2024/006338 JP2024006338W WO2024257407A1 WO 2024257407 A1 WO2024257407 A1 WO 2024257407A1 JP 2024006338 W JP2024006338 W JP 2024006338W WO 2024257407 A1 WO2024257407 A1 WO 2024257407A1
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Prior art keywords
voltage
current
power supply
command value
switching
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English (en)
French (fr)
Japanese (ja)
Inventor
謙吾 河内
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Mitsubishi Electric Corp
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Mitsubishi Electric Corp
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Priority to CN202480035988.7A priority Critical patent/CN121312053A/zh
Priority to JP2024560348A priority patent/JP7603906B1/ja
Publication of WO2024257407A1 publication Critical patent/WO2024257407A1/ja
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/02—Conversion of AC power input into DC power output without possibility of reversal
    • H02M7/04—Conversion of AC power input into DC power output without possibility of reversal by static converters
    • H02M7/12—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode

Definitions

  • This disclosure relates to an AC/DC converter that converts AC power into desired DC power, as well as a rotating machine drive device and a refrigeration cycle application device that are equipped with the AC/DC converter.
  • a power factor correction circuit When obtaining DC voltage from an AC power source, it is common to use a power factor correction circuit.
  • a power factor correction circuit has the functions of controlling the bus voltage at a constant level and controlling the power supply current so as to comply with harmonic standards.
  • a power factor correction circuit and one of its control methods is a method in which switching is performed at least once per half cycle of the power supply voltage, which is the voltage of the AC power supply, and has the characteristic of being able to control the bus voltage to be lower than the peak value of the power supply voltage.
  • the operating circuit switches from a boost chopper to a capacitor-input type diode rectifier, which creates the problem of distorting the power supply current.
  • Patent Document 1 determines whether the combination of reactor capacity and switching timing complies with harmonic standards by repeating the design for each load power.
  • Patent Document 1 is a method for checking whether or not compliance with harmonic standards can be achieved through repeated trials, which poses the problem that the number of trials increases exponentially as the number of pulses increases.
  • the present disclosure has been made in consideration of the above, and aims to shorten the time required for design by obtaining an AC/DC conversion device that can comply with harmonic standards without relying on trial-and-error adjustments.
  • the AC-DC conversion device includes a rectifier circuit, a capacitor, a reactor, and a control unit.
  • the rectifier circuit has at least one switching element and rectifies the power supply voltage applied from the AC power supply.
  • the capacitor is connected to the DC bus and smoothes the output voltage of the rectifier circuit.
  • the reactor is arranged on the AC power supply side of the capacitor.
  • the control unit When generating a switching signal for controlling the switching element arranged on the AC power supply side of the capacitor, the control unit generates the switching signal so that the harmonic components contained in the power supply current flowing between the AC power supply and the rectifier circuit comply with the harmonic standard value of the power supply current.
  • the switching element performs switching operation at least once per half cycle of the power supply voltage.
  • the AC-DC converter disclosed herein can comply with harmonic standards without relying on trial-and-error adjustments, which has the effect of shortening the time required for design.
  • FIG. 1 is a block diagram showing a configuration example of a rotary machine driving device according to a first embodiment; A circuit diagram showing a configuration example of an AC-DC converter according to a first embodiment.
  • FIG. 1 is a block diagram showing a configuration example of a control unit according to a first embodiment;
  • FIG. 1 is a block diagram showing a configuration example of a voltage control unit according to a first embodiment;
  • FIG. 1 is a block diagram showing a configuration example of a current control unit according to a first embodiment;
  • FIG. 6 is a block diagram showing a configuration example in which a target value filter is introduced into the current control unit shown in FIG.
  • FIG. 7 is a block diagram for explaining a transfer function of a current control system in an AC-DC converter including the current control unit shown in FIG.
  • FIG. 1 is a block diagram showing a configuration example of a switching signal generating unit according to a first embodiment
  • FIG. 7 is a diagram showing an example of the operation waveforms of a power supply voltage, a bus voltage, and a power supply current when PI control is applied to the current controller shown in FIG.
  • FIG. 7 is a diagram showing an example of the operation waveforms of the power supply voltage, the bus voltage, and the power supply current when the PS control is applied to the current controller shown in FIG.
  • FIG. 7 is a diagram showing an example of current harmonic characteristics when PS control is applied to the current controller shown in FIG.
  • FIG. 7 is a diagram showing an example of the relationship between the ratio of the sum of harmonic components and the operating power when PS control is applied to the current controller shown in FIG.
  • FIG. 1 is a diagram showing a configuration example of an AC-DC converter according to a second embodiment
  • FIG. 13 is a diagram showing a configuration example of a refrigeration cycle application device according to a third embodiment.
  • Embodiment 1. 1 is a block diagram showing a configuration example of a rotating machine driving device 8 according to embodiment 1.
  • the rotating machine driving device 8 is connected to an AC power source 1 and a load 4 including a motor 41.
  • the rotating machine driving device 8 includes an AC/DC converter 2 and a DC/AC converter 3.
  • the load 4 is a compressor or a fan
  • the motor 41 is a compressor motor or a fan motor.
  • FIG. 2 is a circuit diagram showing an example of the configuration of the AC-DC converter 2 according to the first embodiment.
  • the AC-DC converter 2 according to the first embodiment mainly comprises a control unit 6, a rectifier circuit 20, a reactor 212, and a capacitor 216.
  • the AC-DC converter 2 also comprises a current detector 211 and voltage detectors 217a and 217b as means for detecting voltage or current.
  • the voltage detector 217b when the voltage detectors 217a and 217b are to be distinguished from each other without reference numbers, the voltage detector 217b will be referred to as the "first voltage detector” and the voltage detector 217a will be referred to as the "second voltage detector.”
  • the rectifier circuit 20 includes single-phase diode bridge cells 213a and 213b in which four diodes are bridge-connected, and a switching element 215 connected in parallel to both ends of the single-phase diode bridge cell 213b.
  • the single-phase diode bridge cells 213a and 213b are connected in parallel to each other with the AC power source 1.
  • the rectifier circuit 20 as shown in FIG. 2 is called a "simple switching circuit.”
  • the single-phase diode bridge cell 213b and the switching element 215 constitute a switching cell 225.
  • the switching element 215 performs a switching operation at least once per half cycle of the power source voltage.
  • the capacitor 216 is connected between the DC bus 9a and the DC bus 9b.
  • the reactor 212 is disposed closer to the AC power source than the capacitor 216.
  • the rectifier circuit 20 receives the power source voltage applied from the AC power source 1 via the reactor 212, and rectifies the received power source voltage.
  • the capacitor 216 smoothes the output voltage of the rectifier circuit 20.
  • the voltage detection unit 217b detects the bus voltage, which is the voltage of the DC buses 9a and 9b to which the capacitor 216 is connected.
  • the voltage detection unit 217a detects the power supply voltage.
  • the current detection unit 211 detects the power supply current flowing between the AC power supply 1 and the rectifier circuit 20.
  • the control unit 6 receives the detection values of the voltage detection units 217a, 217b and the current detection unit 211. Based on each detection value, the control unit 6 generates a switching signal for controlling the on/off of the switching element 215.
  • An example of the switching element 215 is an IGBT (Insulated Gate Bipolar Transistor) as shown in the figure, but is not limited to an IGBT. Any element capable of switching operation may be used as the switching element 215.
  • Another example of the switching element 215 is a MOSFET (Metal-Oxide-Semiconductor Field-Effect Transistor).
  • the AC-DC converter 2 shown in FIG. 2 is configured as a closed loop using the detection values of the voltage detectors 217a, 217b and the current detector 211, but may be configured as an open loop using target values, estimated values, etc. If the AC-DC converter 2 is configured as an open loop, it is also possible to control the switching element 215 without using the detection values of the voltage detectors 217a, 217b and the current detector 211.
  • FIG. 3 is a block diagram showing an example configuration of the control unit 6 according to the first embodiment.
  • the control unit 6 includes a voltage control unit 61, a current control unit 62, and a switching signal generation unit 63.
  • the voltage control unit 61 generates a first current command value using a first voltage command value.
  • the current control unit 62 generates a second voltage command value using the first current command value.
  • the switching signal generation unit 63 generates a switching signal using the second voltage command value.
  • FIG. 4 is a block diagram showing an example of the configuration of the voltage control unit 61 according to the first embodiment.
  • the voltage control unit 61 includes a voltage controller 611 and a subtractor 612.
  • the voltage control unit 61 generates a first current command value using a first voltage command value that is a command value for the bus voltage.
  • the subtractor 612 generates a voltage deviation that is the difference between the first voltage command value and the detected voltage detected by the voltage detection unit 217b.
  • the voltage controller 611 generates the first current command value using the voltage deviation output from the subtractor 612.
  • the voltage controller 611 can be configured, for example, as a PI (Proportional Integral) controller.
  • the transfer function G AVR(s) can be expressed by the following equation (1).
  • AVR in the transfer function G AVR(s) is an abbreviation for "Automatic Voltage Regulator.”
  • K pAVR is a proportional gain
  • K iAVR is an integral gain
  • s is a Laplace operator.
  • the proportional gain K pAVR and the integral gain K iAVR can be determined arbitrarily. Note that the proportional gain K pAVR may be set to zero to configure an I controller, or the integral gain K iAVR may be set to zero to configure a P controller.
  • FIG. 5 is a block diagram showing an example of the configuration of the current control unit 62 according to the first embodiment.
  • the current control unit 62 includes a current controller 621, a subtractor 622, and a multiplier 623.
  • the current control unit 62 generates a second voltage command value using a second current command value obtained by making the first current command value follow a sine wave.
  • the multiplier 623 multiplies the first current command value by an excitation signal.
  • the excitation signal is a sine wave synchronized with the phase of the power supply voltage.
  • the sine wave is generated based on the voltage phase, which is the phase of the detected voltage detected by the voltage detection unit 217a.
  • the output of the multiplier 623 is input to the subtractor 622 as a second current command value.
  • the subtractor 622 generates a current deviation, which is the difference between the second current command value and the detected current detected by the current detection unit 211.
  • the current controller 621 generates a second voltage command value using the current deviation output from the subtractor 622.
  • the current controller 621 can be configured, for example, as a PS (Proportional Sinusoidal) controller.
  • the transfer function G ACR(s) can be expressed by the following equation (2).
  • ACR in the transfer function G ACR(s) is an abbreviation for "Automatic Current Regulator.”
  • K pACR is a proportional gain
  • K sACR is an S control gain
  • ⁇ n is an angular frequency
  • s is a Laplace operator.
  • the proportional gain K pACR , the S control gain K sACR , and the angular frequency ⁇ n can be arbitrarily determined.
  • the PS controller is a controller in which an S controller, which is a Laplace transform expression of a sine wave function or a cosine wave function, is inserted in parallel to a P controller.
  • the S controller is a controller with improved tracking performance for a sine wave input with an angular frequency ⁇ n .
  • the reason why the S controller has improved tracking performance for an input pulsating with an angular frequency ⁇ n can be explained by the internal model principle.
  • the internal model principle is that if the denominator of the controller has the same factor as the denominator polynomial of the command value expressed by the Laplace transform, the command value can be tracked without deviation.
  • the current controller 621 may be configured as a PIS controller by inserting an I controller in parallel to the PS controller.
  • FIG. 6 is a block diagram showing a configuration example in which a target value filter 624 is introduced into the current control unit 62 shown in FIG. 5.
  • FIG. 7 is a block diagram used to explain the transfer function of the current control system 7 in the AC/DC converter 2 including the current control unit 62 shown in FIG. 6.
  • a target value filter 624 is inserted before the current control unit 62 shown in FIG. 5.
  • the target value filter 624 is inserted to adjust the response of the transfer function of the current control unit 62 shown in FIG. 5. Specifically, the response of the transfer function of the current control unit 62 is adjusted by canceling the zero points of the transfer function of the current control unit 62 with the poles of the target value filter 624.
  • the closed loop transfer function G close(s) in the current control system 7 in FIG.
  • Gc is the transfer function of an arbitrary controller 72
  • Gp is the transfer function of an arbitrary controlled plant 73.
  • G X is an arbitrary transfer function.
  • the transfer function G X may be the value of the zeroth power term of the Laplace operator s in the denominator polynomial of the transfer function G' close(s) , or may have an arbitrary zero point.
  • the controller response can be adjusted.
  • a PI controller may be used as a controller that obtains the same effect as the target value filter 74.
  • FIG. 8 is a block diagram showing an example of the configuration of the switching signal generating unit 63 according to the first embodiment.
  • the switching signal generating unit 63 includes a normalizer 630, a carrier signal generator 631, and a comparator 632.
  • the normalizer 630 normalizes the second voltage command value input to the switching signal generating unit 63. Note that if the control gain of the current controller 621 that outputs the second voltage command value is designed taking normalization into consideration, the normalizer 630 is not necessary.
  • the carrier signal generator 631 generates a carrier signal used to generate a switching signal and outputs it to the comparator 632.
  • the carrier signal is a bipolar or unipolar signal having a triangular waveform that operates at any frequency.
  • the comparator 632 generates a switching signal based on the output of the standardizer 630 and the output of the carrier signal generator 631. In more detail, the comparator 632 compares the output value of the standardizer 630 with the output value of the carrier signal generator 631, and if the output value of the standardizer 630 is greater than the output value of the carrier signal generator 631, it outputs a signal to turn on the switching element 215.
  • the comparator 632 outputs a signal to turn off the switching element 215.
  • the configuration may be such that an ON operation signal is generated when the output value of the scaler 630 is smaller than the output value of the carrier signal generator 631, and an OFF operation signal is generated when the output value of the scaler 630 is larger than the output value of the carrier signal generator 631.
  • the carrier signal generated by the carrier signal generator 631 does not have to be triangular, and can have any configuration as long as it can generate a switching signal from the second voltage command value.
  • the switching signal generating unit 63 To suppress switching loss in the switching element 215 in the switching cell 225, it is desirable to have a small number of switching operations. To reduce the number of switching operations, the switching frequency can be lowered. On the other hand, if the switching frequency is lowered too much, the frequency components of the carrier signal will be included in the components up to the 40th order of the fundamental frequency defined by the current harmonics standard.
  • the fundamental frequency is the frequency of the power supply voltage, which in Japan is 50 Hz or 60 Hz.
  • the 40th order of 50 Hz is 2 kHz
  • the 40th order of 60 Hz is 2.4 kHz. Therefore, when the frequency of the power supply voltage is 50 Hz, the carrier frequency, which is the frequency of the carrier signal, must be 2 kHz or higher. Also, when the frequency of the power supply voltage is 60 Hz, the carrier frequency must be 2.4 kHz or higher. This can be expressed mathematically as in the following equation (5).
  • fsw is the carrier frequency
  • fsi is the frequency of a sideband wave relative to the carrier frequency fsw
  • fs is the frequency of the power supply voltage
  • n is an integer of 1 or more.
  • the carrier frequency fsw which is the switching frequency when the switching element 215 performs a switching operation, may be determined so that the component of the sideband frequency fsi satisfies the harmonic standard. Specifically, the carrier frequency fsw is determined so as to satisfy the following formula (6).
  • Nsw is the number of switching times in one cycle of the power supply voltage.
  • ( fsw / fs ) shown on the right side is the ratio of the carrier frequency fsw to the frequency fs of the power supply voltage, and is the frequency obtained by dividing the carrier frequency fsw by the frequency fs of the power supply voltage, i.e., normalized by the frequency fs of the power supply voltage. That is, in the first embodiment, the number of switching times Nsw in one cycle of the power supply voltage is determined to be 1 or more and equal to or less than the value ( fsw / fs ) obtained by dividing the carrier frequency fsw by the frequency fs of the power supply voltage.
  • the above formula (6) is shown as a constraint on the number of switching times Nsw in one cycle of the power supply voltage, but it is not necessary to satisfy this in all operation regions of the load 4. For example, when the load 4 operates in a light load region, the switching operation of the switching element 215 may be stopped, so the above formula (6) does not have to be satisfied.
  • FIG. 9 is a diagram showing example operating waveforms of the power supply voltage, bus voltage, and power supply current when PI control is applied to the current controller 621 shown in FIG. 6.
  • the upper part of FIG. 9 shows the waveforms of the absolute values of the bus voltage and power supply voltage.
  • the lower part of FIG. 9 shows the waveforms of the detected power supply current, the fundamental wave component of the detected power supply current, and the power supply current command value.
  • the detected power supply current is the detected waveform of the power supply current detected by the current detection unit 211.
  • the operating conditions in Figure 9 are those in which the bus voltage is equal to or lower than the peak absolute value of the power supply voltage, as shown in the upper part of Figure 9.
  • the rectifier circuit 20 operates as a capacitor-input type diode rectifier circuit rather than as a boost circuit, making it impossible to control the bus voltage.
  • an excessive amount of value accumulates in the integrator of the PI control, causing a wind-up phenomenon and preventing the detected power supply current from following the power supply current command value.
  • FIG. 10 is a diagram showing example operating waveforms of the power supply voltage, bus voltage, and power supply current when PS control is applied to the current controller 621 shown in FIG. 6.
  • the upper part of FIG. 10 shows the waveforms of the absolute values of the bus voltage and power supply voltage
  • the middle part of FIG. 10 shows the waveforms of the detected power supply current, the fundamental wave component of the detected power supply current, and the power supply current command value.
  • the lower part of FIG. 10 shows a switching signal for controlling the switching element 215.
  • the fundamental wave component of the detected power supply current is almost equal to the power supply current command value.
  • the fundamental wave of the detected power supply current can track the power supply current command value even under conditions where the bus voltage is equal to or below the peak value of the absolute value of the power supply voltage.
  • Figure 10 shows the results for operating conditions where the bus voltage is equal to or below the peak value of the absolute value of the power supply voltage, but it goes without saying that the fundamental wave of the detected power supply current will track the power supply current command value even under operating conditions where the bus voltage exceeds the peak value of the absolute value of the power supply voltage.
  • FIG. 11 is a diagram showing an example of current harmonic characteristics when PS control is applied to the current controller 621 shown in FIG. 6.
  • the current harmonic standard used in FIG. 11 is IEC 61000-3-2 Class A. Note that IEC 61000-3-2 Class A is an example of a current harmonic standard, and is not limited to this standard.
  • the solid lines indicate the standard values for current harmonics from the 2nd to the 40th orders specified in IEC 61000-3-2 Class A. Also in Figure 11, the dashed lines indicate the effective values of the 2nd to the 40th harmonic components during rated operation.
  • the harmonic components during rated operation represent the components remaining after subtracting the fundamental wave component of the power supply current from the power supply current that flows when the AC-DC converter 2 is operated at rated power.
  • the 2nd to the 40th harmonics are defined as "low-order harmonics".
  • the proportion of the sum of the harmonic components is 10% or more in all operating regions shown in FIG. 12.
  • the fact that the proportion of the sum of the harmonic components is 10% or more is specific to the method of embodiment 1 in which PS control is applied to the current controller 621 to control the switching element 215.
  • PS control is applied to the current controller 621 to control the switching element 215.
  • the proportion of the sum of the harmonic components increases, but the harmonic standard value when the operating power is small also increases, and as shown in FIG. 11, the effective value of the current harmonics does not exceed the harmonic standard value of the power supply current.
  • the control method of the first embodiment is characterized in that a current controller 621 is applied to the control unit 6, and then PS control, which has high tracking performance for sine wave input, is applied to the current controller 621.
  • PS control which has high tracking performance for sine wave input
  • the application of PS control to improve tracking performance for sine wave input is considered to be a relatively common practice, but the application of PS control to comply with harmonic standards is considered to be a novel method that has not been used before.
  • the AC-DC converter includes a rectifier circuit that rectifies the power supply voltage applied from the AC power supply, a capacitor that smoothes the output voltage of the rectifier circuit, and a reactor that is arranged on the AC power supply side of the capacitor.
  • the rectifier circuit has at least one switching element that is arranged on the AC power supply side of the capacitor.
  • the control unit When generating a switching signal for controlling the switching element, the control unit generates the switching signal so that the harmonic components contained in the power supply current flowing between the AC power supply and the rectifier circuit comply with the harmonic standard value of the power supply current.
  • the switching element performs switching operation at least once per half cycle of the power supply voltage.
  • the AC-DC converter according to the first embodiment it is possible to comply with the harmonic standard without relying on a trial-and-error adjustment method that confirms whether or not compliance with the harmonic standard can be achieved by repeated trials. Furthermore, according to the AC-DC converter according to the first embodiment, it is possible to comply with the harmonic standard while improving the input power factor even under operating conditions in which the bus voltage exceeds the peak value of the absolute value of the power supply voltage.
  • the control unit is configured to include a voltage control unit that generates a first current command value using a first voltage command value that is a command value for the bus voltage, a current control unit that generates a second voltage command value using a second current command value that causes the first current command value to follow a sine wave, and a switching signal generation unit that generates a switching signal using the second voltage command value.
  • the current control unit has a current controller, and PS control is applied to the current controller.
  • the input stage of the current control unit is configured to include a filter that operates the zero point of a feedback loop that feeds back the second voltage command value output by the current control unit to the input stage of the second current command value.
  • control unit configured in this way, it is no longer necessary to repeat the design for each load power to determine whether the combination of reactor capacity and switching timing complies with the harmonic standard, so that trial and error adjustment work is eliminated, and it is possible to shorten the time required for design work and the time until design is completed.
  • the switching signal generating unit prefferably to generate a switching signal so that the number of switching operations in one power supply voltage cycle when the switching element performs switching operation is at least once, and the carrier frequency, which is the frequency of the carrier signal, is equal to or less than the value normalized by the frequency of the power supply voltage.
  • the control system of the AC/DC converter when configured as a closed loop, a current detection unit that detects the power supply current flowing between the AC power supply and the rectifier circuit, a first voltage detection unit that detects the bus voltage, and a second voltage detection unit that detects the power supply voltage are provided.
  • the first current command value may be generated using a voltage deviation that is the difference between the first voltage command value and the detected voltage detected by the first voltage detection unit, and the sine wave that excites the first current command value may be generated based on the voltage phase detected by the second voltage detection unit.
  • the second voltage command value may be generated using a current deviation that is the difference between the second current command value and the detected current detected by the current detection unit.
  • Embodiment 2 In the first embodiment, a configuration has been described in which PS control is applied to the current controller 621 of the current control unit 62 for the purpose of improving the tracking performance for a sine wave command. In the second embodiment, a configuration will be described in which PIR (Proportional Integral Resonant) control is applied to the current controller 621 of the current control unit 62 for the same purpose.
  • PS control is applied to the current controller 621 of the current control unit 62 for the purpose of improving the tracking performance for a sine wave command.
  • PIR Proportional Integral Resonant
  • FIG. 13 is a diagram showing an example of the configuration of an AC-DC converter 2 according to embodiment 2. Components having the same or equivalent functions as those in FIG. 2 are indicated with the same reference numerals. Note that descriptions of contents that overlap with embodiment 1 will be omitted as appropriate.
  • the rectifier circuit 20 shown in FIG. 13 has a configuration called a full PAM (Pulse Amplitude Modulation) circuit.
  • the rectifier circuit 20 includes a single-phase diode bridge cell 213a, a switching element 215, and a diode 218.
  • the switching element 215 performs a switching operation at least once per half cycle of the power supply voltage.
  • the reactor 212 described in the configuration of FIG. 2 is disposed between the single-phase diode bridge cell 213a and the diode 218.
  • the switching element 215 is connected in parallel to the single-phase diode bridge cell 213a and the capacitor 216 between the single-phase diode bridge cell 213a and the capacitor 216.
  • the current detection unit 211 described in the configuration of FIG. 2 is disposed between the single-phase diode bridge cell 213a and the diode 218.
  • the positions and connection forms of the switching element 215 and the reactor 212 are different, but in both configurations, the switching element 215 and the reactor 212 are arranged closer to the AC power source 1 than the capacitor 216.
  • the switching element 215 is shown as an IGBT, but any element capable of switching operation may be used.
  • the AC-DC converter 2 shown in FIG. 13 is configured as a closed loop, but it may be configured as an open loop. When the AC-DC converter 2 is configured as an open loop, the detection values of the voltage detectors 217a, 217b and the current detector 211 do not need to be used.
  • the full PAM circuit of FIG. 13 may be used in the first embodiment, and the simple switching circuit of FIG. 2 may be used in the second embodiment. That is, when the AC-DC converter 2 has a step-up function or a step-down function, the rectifier circuit 20 has at least one switching element, but the control method described in this paper is applicable even if the control method for controlling the switching element is different.
  • the transfer function of the PIR controller will be described.
  • the transfer function G PIR(s) of the PIR controller can be expressed by the following equation (7).
  • Kp is a proportional gain
  • Ki is an integral gain
  • Kr is a resonance control gain
  • ⁇ 1 is the angular frequency of the current control response
  • ⁇ 2 is the angular frequency of the sine wave command to be followed.
  • a PIR controller having such a transfer function G PIR(s) may be applied to the current controller 621 in Fig. 5 or 6. The same effect as that of PS control can be obtained by using a PIR controller.
  • PIR control is applied to the current controller provided in the current control unit. Even when PIR control is applied instead of PS control, the same effect as in the first embodiment can be obtained.
  • Embodiment 3 14 is a diagram showing a configuration example of a refrigeration cycle-applied device 900 according to embodiment 3.
  • the refrigeration cycle-applied device 900 according to embodiment 3 includes the rotating machine drive device 8 described in embodiment 1.
  • the refrigeration cycle-applied device 900 according to embodiment 3 can be applied to products including a refrigeration cycle, such as air conditioners, refrigerators, freezers, and heat pump water heaters.
  • the refrigeration cycle application device 900 includes a compressor 42 incorporating the motor 41 in the first embodiment, a four-way valve 902, an indoor heat exchanger 906, an expansion valve 908, and an outdoor heat exchanger 910 attached via refrigerant piping 912. Inside the compressor 42, there is provided a compression mechanism 904 that compresses the refrigerant, and a motor 41 that operates the compression mechanism 904.
  • the refrigeration cycle application device 900 can perform heating or cooling operation by switching the four-way valve 902.
  • the compression mechanism 904 is driven by a motor 41 that is variable speed controlled.
  • the refrigerant is pressurized by the compression mechanism 904 and sent out, and returns to the compression mechanism 904 through the four-way valve 902, the indoor heat exchanger 906, the expansion valve 908, the outdoor heat exchanger 910, and the four-way valve 902.
  • the refrigerant is pressurized by the compression mechanism 904 and sent out, and returns to the compression mechanism 904 through the four-way valve 902, the outdoor heat exchanger 910, the expansion valve 908, the indoor heat exchanger 906, and the four-way valve 902.
  • the indoor heat exchanger 906 acts as a condenser to release heat, and the outdoor heat exchanger 910 acts as an evaporator to absorb heat.
  • the outdoor heat exchanger 910 acts as a condenser to release heat, and the indoor heat exchanger 906 acts as an evaporator to absorb heat.
  • the expansion valve 908 reduces the pressure of the refrigerant and causes it to expand.
  • the refrigeration cycle application device 900 according to the third embodiment has been described as being equipped with the rotating machine drive device 8 described in the first embodiment, but is not limited to this. It may be equipped with a rotating machine drive device 8 equipped with the rectifier circuit 20 described in the second embodiment. Furthermore, the rotating machine drive device 8 may be equipped with a rectifier circuit other than the rectifier circuit 20 described in the first and second embodiments, as long as the control method of the first or second embodiment can be applied.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Rectifiers (AREA)
PCT/JP2024/006338 2023-06-12 2024-02-21 交流直流変換装置、回転機駆動装置及び冷凍サイクル適用機器 Ceased WO2024257407A1 (ja)

Priority Applications (2)

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CN202480035988.7A CN121312053A (zh) 2023-06-12 2024-02-21 交流直流变换装置、旋转机械驱动装置以及冷冻循环应用设备
JP2024560348A JP7603906B1 (ja) 2023-06-12 2024-02-21 交流直流変換装置、回転機駆動装置及び冷凍サイクル適用機器

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Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2000125545A (ja) * 1999-11-24 2000-04-28 Mitsubishi Electric Corp 直流電源装置および空気調和機
JP2009100558A (ja) * 2007-10-17 2009-05-07 Panasonic Corp モータ駆動用インバータ制御装置

Patent Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2000125545A (ja) * 1999-11-24 2000-04-28 Mitsubishi Electric Corp 直流電源装置および空気調和機
JP2009100558A (ja) * 2007-10-17 2009-05-07 Panasonic Corp モータ駆動用インバータ制御装置

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JP7603906B1 (ja) 2024-12-20
CN121312053A (zh) 2026-01-09

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