WO2023105570A1 - 電力変換装置、モータ駆動装置及び冷凍サイクル適用機器 - Google Patents

電力変換装置、モータ駆動装置及び冷凍サイクル適用機器 Download PDF

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Publication number
WO2023105570A1
WO2023105570A1 PCT/JP2021/044712 JP2021044712W WO2023105570A1 WO 2023105570 A1 WO2023105570 A1 WO 2023105570A1 JP 2021044712 W JP2021044712 W JP 2021044712W WO 2023105570 A1 WO2023105570 A1 WO 2023105570A1
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WIPO (PCT)
Prior art keywords
current
load
power supply
power
motor
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Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
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PCT/JP2021/044712
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English (en)
French (fr)
Japanese (ja)
Inventor
浩一 有澤
謙吾 河内
貴昭 ▲高▼原
知宏 沓木
遥 松尾
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Mitsubishi Electric Corp
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Mitsubishi Electric Corp
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Priority to CN202180104554.4A priority Critical patent/CN118339759A/zh
Priority to JP2023565678A priority patent/JPWO2023105570A1/ja
Priority to US18/698,117 priority patent/US20240405694A1/en
Priority to PCT/JP2021/044712 priority patent/WO2023105570A1/ja
Publication of WO2023105570A1 publication Critical patent/WO2023105570A1/ja
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/14—Estimation or adaptation of machine parameters, e.g. flux, current or voltage
    • H02P21/18—Estimation of position or speed
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0009—Devices or circuits for detecting current in a converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/12—Arrangements for reducing harmonics from AC input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from DC input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/40—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC
    • H02M5/42—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters
    • H02M5/44—Conversion of AC power input into AC power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into DC by static converters using discharge tubes or semiconductor devices to convert the intermediate DC into AC
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/02—Conversion of AC power input into DC power output without possibility of reversal
    • H02M7/04—Conversion of AC power input into DC power output without possibility of reversal by static converters
    • H02M7/05—Capacitor coupled rectifiers
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/14—Estimation or adaptation of machine parameters, e.g. flux, current or voltage
    • H02P21/20—Estimation of torque
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using DC to AC converters or inverters

Definitions

  • the present disclosure relates to a power conversion device, a motor drive device, and a refrigeration cycle application device that convert AC power into desired power.
  • a power conversion device that converts AC power supplied from an AC power supply into desired AC power and supplies it to a load such as an air conditioner.
  • a power converter which is a control device for an air conditioner, rectifies AC power supplied from an AC power supply with a diode stack, which is a rectifier, and smoothes the power with a smoothing capacitor
  • a technology is disclosed in which an inverter comprising a plurality of switching elements converts the AC power into desired AC power and outputs the AC power to a compressor motor as a load.
  • the present disclosure has been made in view of the above, and aims to obtain a power conversion device that can suppress deterioration of a smoothing capacitor, avoid an increase in size of the device, and can drive the device with high efficiency. aim.
  • the power conversion device includes a rectifier, a capacitor connected to the output end of the rectifier, an inverter connected to both ends of the capacitor, and a capacitor.
  • a detection unit for detecting a power state and a control unit are provided.
  • the rectifier rectifies a power supply voltage applied from an AC power supply.
  • the inverter converts the DC power output from the capacitor into AC power, and outputs the AC power to the device on which the motor is mounted.
  • the control unit controls the inverter to perform load pulsation compensation for compensating for load pulsation in the load unit including the inverter and equipment, and power supply pulsation compensation for compensating for power supply pulsation in the load unit.
  • the degree of ripple compensation for at least one of load ripple compensation and power supply ripple compensation is adjusted based on.
  • the power conversion device it is possible to suppress the deterioration of the smoothing capacitor, avoid an increase in the size of the device, and drive the device with high efficiency.
  • FIG. 1 is a diagram showing a configuration example of a power converter according to Embodiment 1;
  • FIG. FIG. 2 is a block diagram showing the power conversion device according to Embodiment 1, focusing on its functions;
  • FIG. 2 is a block diagram showing a configuration example of a control unit included in the power converter according to Embodiment 1;
  • FIG. 5 is a diagram for explaining a setting example of the first adjustment coefficient in the current adjustment calculation unit according to the first embodiment;
  • FIG. 5 is a diagram for explaining a setting example of the second adjustment coefficient in the current adjustment calculation unit according to the first embodiment;
  • FIG. 4 is a diagram for explaining a setting example of a first adjustment coefficient with respect to a mechanical angular frequency in a current adjustment calculation unit according to Embodiment 1;
  • FIG. 4 is a diagram for explaining a setting example of the second adjustment coefficient for the second current in the current adjustment calculation unit according to the first embodiment; 1 is a block diagram showing an example of a hardware configuration realizing functions of a control unit according to Embodiment 1; FIG. FIG. 4 is a block diagram showing another example of a hardware configuration that implements the functions of the control unit according to Embodiment 1; A diagram showing a configuration example of a refrigeration cycle application device according to Embodiment 2
  • FIG. 1 is a diagram showing a configuration example of a power conversion device 1 according to Embodiment 1.
  • the power converter 1 is connected to a commercial power source 110 and a compressor 315 .
  • the commercial power supply 110 is an example of an AC power supply
  • the compressor 315 is an example of the equipment referred to in the first embodiment.
  • a motor 314 is mounted on the compressor 315 .
  • a motor drive device 2 is configured by the power conversion device 1 and the motor 314 included in the compressor 315 .
  • the power converter 1 includes a reactor 120, a rectifying section 130, current detecting sections 501 and 502, a voltage detecting section 503, a smoothing section 200, an inverter 310, current detecting sections 313a and 313b, and a control section 400. , provided.
  • the reactor 120 is connected between the commercial power supply 110 and the rectifying section 130 .
  • the rectifying section 130 has a bridge circuit composed of rectifying elements 131-134.
  • the rectifying unit 130 rectifies the power supply voltage applied from the commercial power supply 110 and outputs the rectified power supply voltage.
  • the rectifier 130 performs full-wave rectification.
  • the smoothing section 200 is connected to the output terminal of the rectifying section 130 .
  • Smoothing section 200 has capacitor 210 as a smoothing element, and smoothes the rectified voltage output from rectifying section 130 .
  • the capacitor 210 is, for example, an electrolytic capacitor, a film capacitor, or the like.
  • Capacitor 210 is connected to the output terminal of rectifying section 130 .
  • Capacitor 210 has a capacity corresponding to the degree of smoothing the rectified voltage. Due to this smoothing, the voltage generated in the capacitor 210 does not have a full-wave rectified waveform of the rectified voltage, but has a waveform in which a voltage ripple corresponding to the frequency of the commercial power supply 110 is superimposed on the DC component, and does not pulsate greatly.
  • the frequency of this voltage ripple is a component twice the frequency of the power supply voltage when the commercial power supply 110 is single-phase, and a main component is a frequency component six times the frequency of the power supply voltage when the commercial power supply 110 is three-phase. If the power input from commercial power supply 110 and the power output from inverter 310 do not change, the amplitude of this voltage ripple is determined by the capacitance of capacitor 210 . However, in the power conversion device 1 according to the present disclosure, an increase in capacitance is avoided in order to suppress an increase in cost of the capacitor 210 . As a result, a certain amount of voltage ripple is generated in the capacitor 210 . For example, the voltage across capacitor 210 is a pulsating voltage in a range such that the maximum value of the voltage ripple is less than twice the minimum value.
  • Current detection unit 501 detects first current I ⁇ b>1 that flows out from rectification unit 130 and outputs a detection value of detected first current I ⁇ b>1 to control unit 400 .
  • Current detection unit 502 detects second current I ⁇ b>2 that flows into inverter 310 and outputs the detected value of second current I ⁇ b>2 to control unit 400 .
  • Voltage detection unit 503 detects DC bus voltage Vdc , which is the voltage across capacitor 210 , and outputs a detected value of detected DC bus voltage Vdc to control unit 400 . Both the current detection units 501 and 502 and the voltage detection unit 503 can be used as detection units for detecting the power state of the capacitor 210 .
  • the inverter 310 is connected to both ends of the smoothing section 200 , that is, the capacitor 210 .
  • the inverter 310 has switching elements 311a-311f and freewheeling diodes 312a-312f.
  • the inverter 310 turns on and off the switching elements 311a to 311f under the control of the control unit 400, converts the power output from the rectifying unit 130 and the smoothing unit 200 into AC power having a desired amplitude and phase, and the motor 314 is mounted. It outputs to the compressor 315, which is a device that has been processed.
  • the current detection units 313 a and 313 b each detect the current value of one phase out of the three-phase motor currents output from the inverter 310 to the motor 314 .
  • Each detection value of the current detection units 313 a and 313 b is input to the control unit 400 .
  • the control unit 400 calculates the current of the remaining one phase based on the detected value of the current of any two phases detected by the current detection units 313a and 313b. Note that this example shows a method of acquiring the current flowing through the motor 314 and reproducing the three-phase current, but is not limited to this, and acquires the current flowing between the capacitor 210 of the smoothing unit 200 and the inverter 310 Then, a method of reproducing three-phase current may be used.
  • a motor 314 mounted on the compressor 315 rotates according to the amplitude and phase of the AC power supplied from the inverter 310 to perform compression operation.
  • the compressor 315 is a hermetic compressor used in an air conditioner or the like, the load torque of the compressor 315 can often be regarded as a constant torque load.
  • FIG. 1 shows a case where the motor windings in the motor 314 are Y-connected
  • the present invention is not limited to this example.
  • the motor windings of the motor 314 may be delta-connection, or may be switchable between Y-connection and delta-connection.
  • reactor 120 may be arranged after rectifying section 130 .
  • the power conversion device 1 may include a booster section, or the rectifier section 130 may have the function of the booster section.
  • the current detection units 501 and 502, the voltage detection unit 503 and the current detection units 313a and 313b may be simply referred to as "detection units”.
  • the current values detected by the current detection units 501 and 502, the voltage value detected by the voltage detection unit 503, and the current values detected by the current detection units 313a and 313b may be simply referred to as "detected values". be.
  • the control unit 400 controls the detection value of the first current I1 detected by the current detection unit 501, the detection value of the second current I2 detected by the current detection unit 502, and the DC bus voltage V detected by the voltage detection unit 503. Get the detected value of dc . Further, the control unit 400 acquires the detected value of the motor current when detected by the current detection units 313a and 313b. Control unit 400 controls the operation of inverter 310, specifically, the on/off of switching elements 311a to 311f included in inverter 310, using the detection values detected by the respective detection units.
  • control unit 400 controls the operation of the inverter 310 so that AC power including pulsation corresponding to the pulsation of the power flowing from the rectifying unit 130 into the capacitor 210 of the smoothing unit 200 is output from the inverter 310 to the compressor 315. do.
  • the pulsation according to the pulsation of the power flowing into the capacitor 210 of the smoothing section 200 is, for example, the pulsation that varies depending on the frequency of the pulsation of the power flowing into the capacitor 210 of the smoothing section 200 .
  • control unit 400 suppresses third current I3 flowing through capacitor 210 of smoothing unit 200 .
  • a third current I3 is a charge/discharge current in the capacitor 210 of the smoothing section 200 .
  • the control unit 400 performs control so that any one of the speed, voltage, and current of the motor 314 is in a desired state. Note that the control unit 400 does not have to use all the detection values acquired from each detection unit, and can perform control using some of the detection values
  • the control unit 400 controls the motor 314 without a position sensor.
  • position sensorless control methods for the motor 314 There are two types of position sensorless control methods for the motor 314: primary magnetic flux constant control and sensorless vector control. Embodiment 1 will be described based on sensorless vector control as an example. It should be noted that the control method described below can be applied to the primary magnetic flux constant control with minor modifications.
  • the first current I1 that flows out from the rectifying section 130 is basically affected by the phase of the commercial power source 110 and the characteristics of elements installed before and after the rectifying section 130.
  • n is an integer greater than or equal to 1).
  • the third current I3, which is a charging/discharging current is large, aging deterioration of the capacitor 210 is accelerated.
  • the control unit 400 controls the inverter 310 so that the first current I1 becomes equal to the second current I2, and controls the third current I3 to approach zero.
  • control unit 400 needs to control inverter 310 with the ripple component taken into consideration.
  • the control unit 400 monitors the power state of the smoothing unit 200, that is, the capacitor 210, and provides appropriate pulsation to the motor 314 so that the third current I3 decreases.
  • the current detection section 501 detects the current value of the first current I1 to the capacitor 210 and outputs the detected value to the control section 400 .
  • Control unit 400 controls inverter 310 so that the value obtained by removing the PWM ripple from second current I2 from capacitor 210 to inverter 310 matches first current I1, and adds pulsation to the power output to motor 314. .
  • the controller 400 can reduce the third current I3 of the capacitor 210 by appropriately pulsating the second current I2. Ripple compensation by this control is called "power supply ripple compensation".
  • the power converter 1 needs to pulsate the second current I2 and the q-axis current of the motor 314 appropriately.
  • the load on the compressor 315 when the compressor 315 is used in an air conditioner, even if the load on the compressor 315 is substantially constant, that is, even if the effective value of the second current I2 is constant, the load on the compressor 315 It is known that some types of motors have a mechanism that causes periodic rotational fluctuations. Therefore, when driving a compressor load having such a mechanism, the load torque has periodic fluctuations. In this case, if the compressor 315 is driven with a constant output current from the inverter 310, that is, with a constant torque output, speed fluctuations will occur due to the torque difference. A characteristic of the speed fluctuation is that it occurs remarkably in the low speed range and becomes smaller as the operating point moves to the high speed range.
  • the speed fluctuation part flows out to the outside, it will be observed as vibration, and it is necessary to add parts for vibration countermeasures. Therefore, in addition to the constant current output from the inverter 310, i.e., the constant torque output current, the pulsating torque, i.e., the pulsating current, is supplied to the compressor 315 so that the torque corresponding to the load torque fluctuation is supplied from the inverter 310 to the compressor. 315 is often used. As a result, the torque difference between the output torque of inverter 310 and the load torque can be brought close to zero. As a result, speed fluctuation of the motor 314 provided in the compressor 315 can be reduced, and vibration of the compressor 315 can be suppressed. Ripple compensation by this control is called "load ripple compensation".
  • control unit 400 performs power supply ripple compensation for power supply ripple and load ripple compensation for load ripple. These pulsation compensations can be performed based on the detected value of the first current I1, the second current I2, or the DC bus voltage Vdc , which is information for grasping the power state of the capacitor 210.
  • FIG. The third current I3 can be obtained from the difference between the first current I1 and the second current I2. Therefore, the third current I3 may be used as information for grasping the power state of the capacitor 210.
  • FIG. 2 is a block diagram showing the power converter 1 according to Embodiment 1, focusing on its functions.
  • the same reference numerals are assigned to the same or equivalent components as those shown in FIG.
  • FIG. 2 shows a power supply section 860, a smoothing section 200, current detection sections 501 and 502, a voltage detection section 503, and a load section 800 as circuit elements.
  • Power supply unit 860 is a concept that includes commercial power supply 110 and rectification unit 130 .
  • Load section 800 is a concept including inverter 310 , compressor 315 with motor 314 mounted thereon, and control section 400 .
  • Load section 800 includes a constant current load section 810, a pulsation compensation section 820, and an adjustment section 850 as components.
  • ripple compensator 820 includes load ripple compensator 830 and power supply ripple compensator 840 as components. When the physical quantity that handles the load is current, it is convenient to describe it as a current source. Therefore, FIG. 2 shows each component as a current source.
  • inverter 310 When driving such a compressor motor load, the aforementioned load ripple compensation is implemented.
  • inverter 310 outputs a constant current, but in load ripple compensation, a ripple current component corresponding to load ripple compensation torque is supplied to the load in addition to the constant current.
  • the element that allows this pulsating current component to flow can be represented by adding a load pulsation compensation section 830 in parallel to the constant current load section 810 . That is, the load ripple compensator 830 is a component that performs load ripple compensation. The detailed configuration and operation of load ripple compensator 830 will be described later.
  • the ripple current component due to the power supply ripple compensation is supplied to the load.
  • the element that allows this pulsating current component to flow can be represented by adding a power supply pulsation compensator 840 in parallel. That is, the power ripple compensator 840 is a component that performs power ripple compensation. The detailed configuration and operation of power supply ripple compensator 840 will be described later.
  • an adjustment section 850 is provided in order to drive the device with high efficiency.
  • the adjustment unit 850 is a component that adjusts the degree of at least one of load ripple compensation and power supply ripple compensation. A detailed configuration and operation of the adjustment unit 850 will be described later.
  • FIG. 3 is a block diagram showing a configuration example of the control unit 400 included in the power converter 1 according to Embodiment 1.
  • the control unit 400 includes a rotor position estimation unit 401, a subtraction unit 402, a speed control unit 403, a current control unit 404, coordinate conversion units 405 and 406, a PWM signal generation unit 407, and a q-axis current pulsation calculation. It includes a section 408 , a flux-weakening control section 409 , a current adjustment calculation section 410 , an addition section 411 and a subtraction section 412 .
  • the rotor position estimator 401 uses the dq-axis voltage command vector V dq * and the dq-axis current vector i dq for driving the motor 314 to estimate the dq-axis of the rotor magnetic poles of the rotor (not shown) of the motor 314 .
  • Estimate an estimated phase angle ⁇ est which is the direction
  • an estimated speed ⁇ est which is the rotor speed.
  • the subtraction unit 402 and the speed control unit 403 are components that implement the function of the load ripple compensation unit 830 in FIG.
  • Subtraction unit 402 calculates speed deviation ⁇ , which is the difference between speed command ⁇ * and estimated speed ⁇ est, and outputs it to speed control unit 403 .
  • the speed command ⁇ * is a command value for the rotation speed of the motor 314 .
  • the speed control unit 403 automatically adjusts the q-axis current pulsation command i q1 * so that the speed deviation ⁇ becomes zero, that is, the speed command ⁇ * and the estimated speed ⁇ est match.
  • the speed command ⁇ * is, for example, a temperature detected by a temperature sensor (not shown) or a setting indicated by a remote control that is an operation unit (not shown). It is based on information indicating temperature, operation mode selection information, operation start and operation end instruction information, and the like.
  • the operation modes are, for example, heating, cooling, and dehumidification.
  • the current control unit 404 automatically adjusts the dq-axis voltage command vector V dq * so that the dq-axis current vector i dq follows the d-axis current command id * and the q-axis current command i q * .
  • the coordinate conversion unit 405 coordinates-converts the dq-axis voltage command vector V dq * from the dq coordinates into the voltage command V uvw * of the AC quantity according to the estimated phase angle ⁇ est .
  • a coordinate transformation unit 406 coordinates-transforms the current I uvw flowing through the motor 314 from an alternating current quantity to a dq-axis current vector i dq of dq coordinates in accordance with the estimated phase angle ⁇ est .
  • the control unit 400 controls the two-phase current values detected by the current detection units 313a and 313b among the three-phase current values output from the inverter 310 for the current Iuvw flowing through the motor 314, It can be obtained by calculating the current value of the remaining one phase using the current values of the two phases.
  • PWM signal generation unit 407 generates a PWM signal based on voltage command V uvw * coordinate-transformed by coordinate transformation unit 405 .
  • Control unit 400 applies a voltage to motor 314 by outputting the PWM signal generated by PWM signal generation unit 407 to switching elements 311 a to 311 f of inverter 310 .
  • the q-axis current ripple calculator 408 is a component that implements the function of the power supply ripple compensator 840 in FIG.
  • a q-axis current ripple calculation unit 408 calculates a q-axis current ripple command i q2 * based on the detected value of the DC bus voltage V dc detected by the voltage detection unit 503 and the estimated speed ⁇ est .
  • the q-axis current ripple command i q2 * is generated upon execution of power supply ripple compensation control.
  • the q-axis current pulsation command i q2 * is a q-axis current command value for reducing the third current I3.
  • the flux-weakening control unit 409 automatically adjusts the d-axis current command i d * so that the absolute value of the dq-axis voltage command vector V dq * falls within the limits of the voltage limit value V lim * . Further, in Embodiment 1, the flux-weakening control unit 409 performs flux-weakening control in consideration of the q-axis current ripple command i q2 * calculated by the q-axis current ripple calculation unit 408 .
  • the flux-weakening control can be broadly divided into a method of calculating the d-axis current command id * from the equation of the voltage limit ellipse, and a method in which the absolute value deviation between the voltage limit value Vlim * and the dq-axis voltage command vector Vdq * is zero. There are two methods of calculating the d-axis current command i d * so that
  • Current adjustment calculation section 410 is a component that implements the function of adjustment section 850 in FIG.
  • Speed command ⁇ * , q-axis current pulsation command i q1 * , q-axis current pulsation command i q2 * , and the detected value of second current I2 are input to current adjustment calculation unit 410 .
  • a current adjustment calculation unit 410 calculates a first adjustment coefficient k1 based on the speed command ⁇ * .
  • the current adjustment calculation unit 410 calculates the first adjustment coefficient k1 based on the speed command ⁇ * and the detected value of the second current I2.
  • the current adjustment calculation unit 410 calculates the second adjustment coefficient k2 based on the detected value of the second current I2.
  • the first adjustment coefficient k1 is a coefficient for adjusting the degree of load ripple compensation
  • the second adjustment coefficient k2 is a coefficient for adjusting the degree of power supply ripple compensation.
  • Both the first and second adjustment coefficients k1 and k2 are real numbers of 0 or more and 1 or less.
  • the current adjustment calculation unit 410 calculates the q-axis current pulsation adjustment command iq3 * using the calculated first and second adjustment coefficients k1 and k2.
  • the q-axis current ripple command i q2 * is a q-axis current command value for adjusting the degree of ripple compensation for at least one of load ripple compensation and power supply ripple compensation.
  • the values of the q-axis current pulsation command i q1 * and the q-axis current pulsation command i q2 * are adjusted by the first and second adjustment coefficients k1 and k2, and the adjusted value is the q-axis current pulsation adjustment command i q3 *. It is output to the subtraction unit 412 .
  • the current adjustment calculation unit 410 in FIG. 3 uses the detected value of the second current I2 as the input signal, but the detected value of the first current I1 may be used as the input signal instead of the second current I2.
  • Addition unit 411 adds q-axis current pulsation command i q1 * output from speed control unit 403 and q-axis current pulsation command i q2 * calculated by q-axis current pulsation calculation unit 408, and obtains the calculated value is output to the subtraction unit 412 .
  • the subtraction unit 412 adds the q-axis current pulsation command i q1 * and the q-axis current pulsation command i q2 * output from the addition unit 411 to the q-axis current pulsation calculated by the current adjustment calculation unit 410 .
  • the adjustment command i q3 * is subtracted, and the q-axis current command i q * , which is the calculated value, is output as the torque current command to the current control unit 404 .
  • I2 A+B ⁇ cos(2 ⁇ f1 ⁇ t)+C ⁇ cos(2 ⁇ f2 ⁇ t)...(1)
  • a in the first term represents the constant current in the constant current load section 810
  • the second term represents the load ripple current in the load ripple compensation section 830
  • the third term represents the power ripple compensation.
  • Power supply pulsating current in section 840 is represented.
  • f1 represents the mechanical angular frequency of periodic load pulsations
  • f2 represents the power supply pulsation frequency in the smoothing section 200 .
  • the capacitance of the capacitor 210 in the smoothing section 200 is relatively small, typically several hundred ⁇ F to several thousand ⁇ F, and a voltage ripple of several tens of volts or more is generated.
  • the third term of the above equation (1) can be omitted. That is, when the voltage value of the voltage ripple is sufficiently small, the power ripple compensator 840 may be omitted.
  • the compressor 315 is a scroll compressor
  • the second term of the above equation (1) can be omitted. That is, depending on the type of periodic load in load section 800, load ripple compensation section 830 may be omitted.
  • equation of motion of the rotating system can be expressed by the following equation (2).
  • the concept of performing pulsation compensation in the load section 800 can reduce various pulsations including load pulsation compensation and power supply pulsation compensation.
  • the effective values of the motor current and the inverter current increase, so the loss in the semiconductor element and the motor winding increases, leading to a decrease in the efficiency of the device. Therefore, depending on the operating state of the load, it is necessary to adjust the operation while also considering the losses in the semiconductor elements and the motor windings.
  • an adjustment section 850 is provided as shown in FIG.
  • the adjustment current in the adjustment section 850 is assumed to be "I4".
  • This adjustment current I4 can be expressed by the following equation (3) using the above-described first and second adjustment coefficients k1 and k2.
  • I4 ⁇ k1 ⁇ B ⁇ cos(2 ⁇ f1 ⁇ t) ⁇ k2 ⁇ C ⁇ cos(2 ⁇ f2 ⁇ t) (3)
  • the second current I2 in the case of having the adjustment unit 850 is a combined current of the above formulas (1) and (3). Therefore, the second current I2 in the case of having the adjustment section 850 can be expressed by the following equation (4).
  • I2 A+(1 ⁇ k1) ⁇ B ⁇ cos(2 ⁇ f1 ⁇ t) +(1 ⁇ k2) ⁇ C ⁇ cos(2 ⁇ f2 ⁇ t) (4)
  • the second current I2 can be reduced by setting the first and second adjustment coefficients k1 and k2 to values other than 0. Therefore, by causing the adjustment current I4 shown in the above equation (3) to flow in the adjustment section 850, the influence on the ripple compensation operation in the ripple compensation section 820 can be reduced, and the semiconductor element and the motor winding can be adjusted by a relatively simple method. It is possible to adjust the pulsating current considering the loss in the line. As a result, the device can be driven with high efficiency, and the device can be operated stably.
  • FIG. 4 is a diagram for explaining a setting example of first adjustment coefficient k1 in current adjustment calculation section 410 according to the first embodiment.
  • Setting the first adjustment coefficient k1 to a small value means suppressing the load ripple compensation adjustment current I4, and setting the first adjustment coefficient k1 to a large value actively increases the load ripple compensation adjustment current I4. means to shed.
  • the first adjustment coefficient k1 described above can be expressed as the following equation (5) as a function of the current In and the mechanical angular frequency fm.
  • FIG. 4 shows the relationship between the current In and the mechanical angular frequency fm when setting the first adjustment coefficient k1.
  • Information on the mechanical angular frequency fm can be obtained from the speed command ⁇ * , which is the input signal to the current adjustment calculation unit 410 .
  • the first adjustment coefficient k1 is set small in order to suppress load pulsation. As a result, load ripple compensation is actively performed, and load ripple is suppressed.
  • the first adjustment coefficient k1 is also set to an intermediate value.
  • the above-described second adjustment coefficient k2 can be expressed as the following equation (6) as a function of the current In.
  • FIG. 5 is a diagram for explaining a setting example of second adjustment coefficient k2 in current adjustment calculation section 410 according to the first embodiment. Setting the second adjustment coefficient k2 to a small value means suppressing the adjustment current I4 for power supply ripple compensation, and setting the second adjustment coefficient k2 to a large value means that the adjustment current I4 for power supply ripple compensation is positively increased. means to shed.
  • the second adjustment coefficient k2 is set small in order to suppress power supply pulsation. As a result, power supply ripple compensation is actively performed, and power supply ripple is suppressed. Also, when the current In is small, the power supply ripple is small. Therefore, by setting the second adjustment coefficient k2 large, the current for power supply ripple compensation can be suppressed appropriately. As a result, it is possible to reduce losses in the semiconductor elements and the motor windings while suppressing power supply pulsation.
  • FIG. 6 is a diagram for explaining a setting example of the first adjustment coefficient k1 with respect to the mechanical angular frequency fm in the current adjustment calculation unit 410 according to Embodiment 1.
  • FIG. The horizontal axis of FIG. 6 represents the mechanical angular frequency fm
  • the vertical axis of FIG. 6 represents the first adjustment coefficient k1.
  • a small mechanical angular frequency fm means that the rotational speed of the motor 314 is low
  • a large mechanical angular frequency fm means that the rotational speed of the motor 314 is high.
  • FIG. 6 shows an example of characteristics when the second current I2 is relatively large.
  • the control unit 400 sets the first adjustment coefficient k1 small when the rotation speed of the motor 314 is fast, and sets the first adjustment coefficient k1 large when the rotation speed of the motor 314 is slow.
  • the adjustment current I4 for adjusting the degree of load ripple compensation becomes smaller when the rotation speed is low than when the rotation speed is high.
  • an appropriate first adjustment coefficient k1 can be set, the load ripple compensation current can be adjusted to an appropriate level, and excessive losses in the semiconductor elements and the motor windings can be reduced.
  • FIG. 7 is a diagram for explaining a setting example of the second adjustment coefficient k2 for the second current I2 in the current adjustment calculation section 410 according to the first embodiment.
  • the horizontal axis of FIG. 7 represents the second current I2, and the vertical axis of FIG. 7 represents the second adjustment coefficient k2. Further, FIG. 7 shows an example of characteristics when the mechanical angular frequency fm is relatively large.
  • the control unit 400 sets the second adjustment coefficient k2 large when the load of the motor 314 is light, and sets the second adjustment coefficient k2 small when the load of the motor 314 is high.
  • the adjustment current I4 for adjusting the degree of power supply ripple compensation becomes smaller when the load of the motor 314 is high than when the load is light.
  • an appropriate second adjustment coefficient k2 can be set, the power supply ripple compensation current can be adjusted to an appropriate level, and excessive losses in the semiconductor elements and the motor windings can be reduced.
  • FIG. 8 is a block diagram showing an example of a hardware configuration realizing functions of the control unit 400 according to the first embodiment.
  • FIG. 9 is a block diagram showing another example of the hardware configuration that implements the functions of the control unit 400 according to the first embodiment.
  • the configuration may include an interface 424 .
  • the processor 420 is an example of computing means.
  • the processor 420 may be a computing means called a microprocessor, microcomputer, CPU (Central Processing Unit), or DSP (Digital Signal Processor).
  • the memory 422 includes nonvolatile or volatile semiconductor memories such as RAM (Random Access Memory), ROM (Read Only Memory), flash memory, EPROM (Erasable Programmable ROM), EEPROM (registered trademark) (Electrically EPROM), Magnetic discs, flexible discs, optical discs, compact discs, mini discs, and DVDs (Digital Versatile Discs) can be exemplified.
  • the memory 422 stores programs for executing the functions of the control unit 400 .
  • the processor 420 transmits and receives necessary information via the interface 424, the processor 420 executes the program stored in the memory 422, and the processor 420 refers to the data stored in the memory 422, thereby performing the above-described processing. can be executed. Results of operations by processor 420 may be stored in memory 422 .
  • the processor 420 and memory 422 shown in FIG. 8 may be replaced with a processing circuit 423 as shown in FIG.
  • the processing circuit 423 corresponds to a single circuit, a composite circuit, an ASIC (Application Specific Integrated Circuit), an FPGA (Field-Programmable Gate Array), or a combination thereof.
  • Information to be input to the processing circuit 423 and information to be output from the processing circuit 423 can be obtained via the interface 424 .
  • part of the processing in the control unit 400 may be performed by the processing circuit 423 and the processing not performed by the processing circuit 423 may be performed by the processor 420 and the memory 422 .
  • the control unit controls the inverter to compensate for load pulsation in the load unit including the inverter and the device, and the power supply in the load unit.
  • Power supply ripple compensation is performed to compensate for ripple, and the degree of ripple compensation for at least one of load ripple compensation and power supply ripple compensation is adjusted based on the detected value of the detector.
  • the current for at least one of the load ripple compensation and the power supply ripple compensation can be adjusted appropriately, so that the losses in the semiconductor elements and the motor windings can be reduced.
  • the control unit determines the degree of power supply ripple compensation based on the detection value of the first current or the second current. can be adjusted. Also, the control unit can adjust the degree of load pulsation based on a speed command, which is a command value for the rotation speed of the motor. Also, the control unit can adjust the degree of power supply ripple compensation based on the speed command and the detected value of at least one of the first current and the second current.
  • the current for adjusting the degree of load ripple compensation can be set to be smaller when the motor rotation speed is low than when the motor rotation speed is high. By setting in this way, the compensating current for load ripple can be adjusted to an appropriate level, and excessive losses in the semiconductor elements and motor windings can be reduced.
  • the current for adjusting the degree of power supply ripple compensation can be set so that it is smaller when the motor load is high than when the load is light. With this setting, the compensation current for power supply ripple can be adjusted to an appropriate level, and excessive losses in the semiconductor elements and motor windings can be reduced.
  • the current for adjusting the degree of load ripple compensation and power supply ripple compensation can be configured to be superimposed on the torque current command. With this configuration, it is possible to reduce the influence on existing control blocks that perform load ripple compensation and power supply ripple compensation.
  • FIG. 10 is a diagram showing a configuration example of a refrigeration cycle device 900 according to Embodiment 2.
  • a refrigerating cycle-applied equipment 900 according to the second embodiment includes the power converter 1 described in the first embodiment.
  • the refrigerating cycle applied equipment 900 according to Embodiment 1 can be applied to products equipped with a refrigerating cycle, such as air conditioners, refrigerators, freezers, and heat pump water heaters.
  • constituent elements having functions similar to those of the first embodiment are denoted by the same reference numerals as those of the first embodiment.
  • Refrigerating cycle applied equipment 900 includes compressor 315 incorporating motor 314 according to Embodiment 1, four-way valve 902, indoor heat exchanger 906, expansion valve 908, and outdoor heat exchanger 910 with refrigerant pipe 912. attached through
  • a compression mechanism 904 that compresses the refrigerant and a motor 314 that operates the compression mechanism 904 are provided inside the compressor 315 .
  • the refrigeration cycle applied equipment 900 can perform heating operation or cooling operation by switching operation of the four-way valve 902 .
  • the compression mechanism 904 is driven by a variable speed controlled motor 314 .
  • the refrigerant is pressurized by the compression mechanism 904 and sent out through the four-way valve 902, the indoor heat exchanger 906, the expansion valve 908, the outdoor heat exchanger 910, and the four-way valve 902. Return to compression mechanism 904 .
  • the refrigerant is pressurized by the compression mechanism 904 and sent through the four-way valve 902, the outdoor heat exchanger 910, the expansion valve 908, the indoor heat exchanger 906, and the four-way valve 902. Return to compression mechanism 904 .
  • the indoor heat exchanger 906 acts as a condenser to release heat, and the outdoor heat exchanger 910 acts as an evaporator to absorb heat.
  • the outdoor heat exchanger 910 acts as a condenser to release heat, and the indoor heat exchanger 906 acts as an evaporator to absorb heat.
  • the expansion valve 908 reduces the pressure of the refrigerant to expand it.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Control Of Ac Motors In General (AREA)
PCT/JP2021/044712 2021-12-06 2021-12-06 電力変換装置、モータ駆動装置及び冷凍サイクル適用機器 Ceased WO2023105570A1 (ja)

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CN202180104554.4A CN118339759A (zh) 2021-12-06 2021-12-06 电力转换装置、马达驱动装置以及制冷循环应用设备
JP2023565678A JPWO2023105570A1 (https=) 2021-12-06 2021-12-06
US18/698,117 US20240405694A1 (en) 2021-12-06 2021-12-06 Power converting apparatus, motor drive unit, and refrigeration cycle-incorporating device
PCT/JP2021/044712 WO2023105570A1 (ja) 2021-12-06 2021-12-06 電力変換装置、モータ駆動装置及び冷凍サイクル適用機器

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WO2025254086A1 (ja) * 2024-06-07 2025-12-11 三菱重工サーマルシステムズ株式会社 モータ制御装置及びモータ制御方法

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WO2022091184A1 (ja) * 2020-10-26 2022-05-05 三菱電機株式会社 電力変換装置、モータ駆動装置および冷凍サイクル適用機器

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JPH10271900A (ja) * 1997-03-28 1998-10-09 Toshiba Corp 電力変換装置
JP2014027804A (ja) * 2012-07-27 2014-02-06 Daikin Ind Ltd 電力変換装置
JP2019037135A (ja) * 2018-12-05 2019-03-07 三菱電機株式会社 電力変換装置および空調装置
JP2021158874A (ja) * 2020-03-30 2021-10-07 パナソニックＩｐマネジメント株式会社 モータインバータ制御装置

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Publication number Priority date Publication date Assignee Title
JPH10271900A (ja) * 1997-03-28 1998-10-09 Toshiba Corp 電力変換装置
JP2014027804A (ja) * 2012-07-27 2014-02-06 Daikin Ind Ltd 電力変換装置
JP2019037135A (ja) * 2018-12-05 2019-03-07 三菱電機株式会社 電力変換装置および空調装置
JP2021158874A (ja) * 2020-03-30 2021-10-07 パナソニックＩｐマネジメント株式会社 モータインバータ制御装置

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2025254086A1 (ja) * 2024-06-07 2025-12-11 三菱重工サーマルシステムズ株式会社 モータ制御装置及びモータ制御方法

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